TM MP1593 3A, 28V, 385KHz Step-Down Converter The Future of Analog IC Technology TM DESCRIPTION FEATURES The MP1593 is a step-down regulator with an internal Power MOSFET. It achieves 3A of continuous output current over a wide input supply range with excellent load and line regulation. • • • • Current mode operation provides fast transient response and eases loop stabilization. • • • • • • • • • Fault condition protection includes cycle-by-cycle current limiting and thermal shutdown. An adjustable soft-start reduces the stress on the input source at startup. In shutdown mode the regulator draws 20µA of supply current. The MP1593 requires a minimum number of readily available external components, providing a compact solution. EVALUATION BOARD REFERENCE Board Number Dimensions EV1593DN-00A 2.1”X x 1.3”Y x 0.4”Z 3A Output Current Programmable Soft-Start 100mΩ Internal Power MOSFET Switch Stable with Low ESR Output Ceramic Capacitors Up to 95% Efficiency 20µA Shutdown Mode Fixed 385KHz Frequency Thermal Shutdown Cycle-by-Cycle Over Current Protection Wide 4.75V to 28V Operating Input Range Output Adjustable from 1.22V Under-Voltage Lockout Available in 8-Pin SOIC Package APPLICATIONS • • • • • • • Distributed Power Systems Battery Chargers Pre-Regulator for Linear Regulators Flat Panel TVs Set-Top Boxes Cigarette Lighter Powered Devices DVD/PVR Devices “MPS” and “The Future of Analog IC Technology” are Trademarks of Monolithic Power Systems, Inc. TYPICAL APPLICATION INPUT 4.75V to 28V 100 8 MP1593 SS GND FB COMP 6 4 C6 (optional) OUTPUT 3.3V 3A 5 C3 8.2nF VIN = 9V 95 1 BS 3 SW 2 IN 7 EN D1 B340A 90 EFFICIENCY (%) OFF ON Efficiency vs Load Current C5 10nF 85 VIN = 24V 80 VIN = 12V 75 70 65 60 55 50 0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 LOAD CURRENT (A) MP1593 Rev. 1.9 9/14/2006 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. 1 MP1593 – 3A, 28V, 385KHz STEP-DOWN CONVERTER ABSOLUTE MAXIMUM RATINGS (1) PACKAGE REFERENCE TOP VIEW BS 1 8 SS IN 2 7 EN SW 3 6 COMP GND 4 5 FB Supply Voltage VIN ....................... –0.3V to +30V Switch Voltage VSW .............. –0.5V to VIN + 0.3V Boost Voltage VBS ..........VSW – 0.3V to VSW + 6V All Other Pins................................. –0.3V to +6V Junction Temperature...............................150°C Lead Temperature ....................................260°C Storage Temperature .............–65°C to +150°C Recommended Operating Conditions EXPOSED PAD ON BACKSIDE CONNECT TO PIN 4 Input Voltage VIN ............................ 4.75V to 28V Ambient Operating Temp............. –40°C to +85°C Thermal Resistance Part Number* Package Temperature MP1593DN SOIC8E (Exposed Pad) –40°C to +85°C * (2) For Tape & Reel, add suffix –Z (eg. MP1593DN–Z) For RoHS Compliant Packaging, add suffix –LF (eg. MP1593DN–LF–Z) (3) θJA θJC SOIC8E (Exposed Pad).......... 50 ...... 10... °C/W Notes: 1) Exceeding these ratings may damage the device. 2) The device is not guaranteed to function outside of its operating conditions. 3) Measured on approximately 1” square of 1 oz copper. ELECTRICAL CHARACTERISTICS VIN = 12V, TA = +25°C, unless otherwise noted. Parameter Shutdown Supply Current Supply Current Symbol Condition VEN = 0V VEN = 2.6V, VFB = 1.4V Feedback Voltage VFB Error Amplifier Voltage Gain Error Amplifier Transconductance High-Side Switch On-Resistance Low-Side Switch On-Resistance High-Side Switch Leakage Current Current Limit Current Sense to COMP Transconductance Oscillation Frequency Short Circuit Oscillation Frequency Maximum Duty Cycle Minimum Duty Cycle AEA MP1593 Rev. 1.9 9/14/2006 4.75V ≤ VIN ≤ 28V VCOMP < 2V Min Typ 20 1.0 Max 30 1.2 Units µA mA 1.194 1.222 1.250 V 400 ∆ICOMP = ±10µA 800 1120 µA/V RDS(ON)1 100 140 mΩ RDS(ON)2 10 GEA 500 V/V VEN = 0V, VSW = 0V 4.8 GCS Ω 0 10 µA 6.2 7.6 A 5.4 fOSC1 fOSC2 VFB = 0V DMAX DMIN VFB = 1.0V VFB = 1.5V A/V 335 385 435 KHz 25 45 60 KHz 0 % % 90 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. 2 MP1593 – 3A, 28V, 385KHz STEP-DOWN CONVERTER ELECTRICAL CHARACTERISTICS (continued) VIN = 12V, TA = +25°C, unless otherwise noted. Parameter EN Threshold Voltage Enable Pull Up Current Under-Voltage Lockout Threshold Under-Voltage Lockout Threshold Hysteresis Soft-Start Period Symbol Condition VEN = 0V Min 0.9 1.0 Typ 1.2 1.7 Max 1.5 2.5 Units V µA VIN Rising 2.3 2.6 2.9 V CSS = 0.1µF Thermal Shutdown 210 mV 10 ms 160 °C TYPICAL PERFORMANCE CHARACTERISTICS Refer to Typical Application Schematic on Page 1 Feedback Voltage vs Temperature Peak Current Limit vs Temperature 1.235 1.225 1.215 1.205 1.195 -60 -40 -20 0 20 40 60 80 100 120 140 TEMPERATURE (°C) OSCILLATION FREQUENCY (KHz) 5.0 PEAK CURRENT LIMIT (A) FEEDBACK VOLTAGE (V) 1.245 4.9 4.8 4.7 4.6 4.5 4.4 4.3 4.2 4.1 4.0 -50 -25 Oscillation Frequency vs Temperature -0 25 50 75 100 125 150 420 410 400 390 380 370 360 350 340 -60 -40 -20 0 20 40 60 80 100 120 140 TEMPERATURE (°C) TEMPERATURE (°C) Turn Off Waveforms Soft-Start Waveforms VOUT 1V/Div. IL 1A/Div. Load Transient Waveforms VOUT VOUT 100mV/Div. 1V/Div. IL 1A/Div. IL 1A/Div. 4ms/Div. VIN = 12V, VOUT = 3.3V, 1A - 2A STEP MP1593 Rev. 1.9 9/14/2006 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. 3 MP1593 – 3A, 28V, 385KHz STEP-DOWN CONVERTER TYPICAL PERFORMANCE CHARACTERISTICS (continued) Refer to Typical Application Schematic on Page 1 Switching Waveforms Efficiency vs Load Current Efficiency vs Load Current VIN = 9V 95 90 85 VIN = 24V 80 VIN = 12V 75 70 65 EFFICIENCY (%) 90 EFFICIENCY (%) VIN 100mV/Div. VIN = 5V 95 1A/Div. VOUT 10mV/Div. 100 100 IL 85 VIN = 24V 80 VIN = 12V 75 70 65 VSW 60 60 10V/Div. 55 55 50 50 0 500 1000 1500 2000 2500 3000 3500 LOAD CURRENT (mA) 0 500 1000 1500 2000 2500 3000 3500 LOAD CURRENT (mA) PIN FUNCTIONS Pin # Name Description 1 2 3 4 5 6 7 8 High-Side Gate Drive Boost Input. BS supplies the drive for the high-side N-Channel MOSFET switch. Connect a 10nF or greater capacitor from SW to BS to power the high-side switch. Power Input. IN supplies power to the IC. Drive IN with a 4.75V to 28V power source. Bypass IN IN to GND with a suitably large capacitor to eliminate noise on the input to the IC. See Input Capacitor. Power Switching Output. SW is the switching node that supplies power to the output. Connect SW the output LC filter from SW to the output load. Note that a capacitor is required from SW to BS to power the high-side switch. GND Ground. Note: Connect the exposed pad to Pin 4. Feedback Input. FB senses the output voltage and regulates it. Drive FB with a resistive voltage FB divider from the output voltage to ground. The feedback threshold is 1.222V. See Setting the Output Voltage. Compensation Node. COMP is used to compensate the regulation control loop. Connect a series COMP RC network from COMP to GND. In some cases, an additional capacitor from COMP to GND is required. See Compensation. Enable Input. EN is a digital input that turns the regulator on or off. Drive EN high to turn on the regulator; low to turn it off. An Under-Voltage Lockout (UVLO) function can be implemented by EN the addition of a resistor divider from VIN to GND. For complete low current shutdown the EN pin voltage needs to be less than 0.7V. For automatic startup leave EN disconnected. Soft-Start Control Input. SS controls the soft-start period. Connect a capacitor from SS to GND SS to set the soft-start period. A 0.1µF capacitor sets the soft-start period to 10ms. To disable the soft-start feature, leave SS disconnected. BS MP1593 Rev. 1.9 9/14/2006 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. 4 MP1593 – 3A, 28V, 385KHz STEP-DOWN CONVERTER OPERATION IN 2 CURRENT SENSE AMPLIFIER INTERNAL REGULATORS OSCILLATOR 45/385KHz + 1.2V -- EN 7 -2.60V/ 2.39V + FREQUENCY FOLDBACK COMPARATOR + SLOPE COMP 5V -- CLK + SHUTDOWN COMPARATOR -- S Q R Q 1 BS 3 SW 4 GND M1 CURRENT COMPARATOR M2 LOCKOUT COMPARATOR 1.8V -- + -- 0.7V 1.22V 5 FB + ERROR AMPLIFIER 6 COMP 8 SS Figure 1—Functional Block Diagram The converter uses an internal N-Channel The MP1593 is a current-mode step-down MOSFET switch to step-down the input voltage regulator. It regulates input voltages from 4.75V to to the regulated output voltage. Since the 28V down to an output voltage as low as 1.22V, MOSFET requires a gate voltage greater than and is able to supply up to 3A of continuous load the input voltage, a boost capacitor connected current. between SW and BS drives the gate. The The MP1593 uses current-mode control to capacitor is internally charged when SW is low. regulate the output voltage. The output voltage An internal 10Ω switch from SW to GND is used is measured at FB through a resistive voltage to insure that SW is pulled to GND when it is divider and amplified through the internal error low to fully charge the BS capacitor. amplifier. The output current of the transconductance error amplifier is presented at COMP where a network compensates the regulation control system. The voltage at COMP is compared to the internally measured switch current to control the output voltage. MP1593 Rev. 1.9 9/14/2006 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. 5 MP1593 – 3A, 28V, 385KHz STEP-DOWN CONVERTER APPLICATION INFORMATION COMPONENT SELECTION Setting the Output Voltage The output voltage is set using a resistive voltage divider from the output voltage to the FB pin. The voltage divider divides the output voltage down to the feedback voltage by the ratio: VFB = VOUT R2 R1 + R2 Thus the output voltage is: R1 + R2 R2 R1 = 8.18 × ( VOUT − 1.22)(kΩ ) For a 3.3V output voltage, R2 is 10kΩ and R1 is 17kΩ. Inductor The inductor is required to supply constant current to the output load while being driven by the switched input voltage. A larger value inductor will result in less ripple current that will result in lower output ripple voltage. However, larger value inductors will have larger physical size, higher series resistance and/or lower saturation current. A good standard for determining the inductance to use is to allow the inductor peak-to-peak ripple current to be approximately 30% of the maximum switch current limit. Also, make sure that the peak inductor current is below the maximum switch current limit. The inductance value can be calculated by: ⎛ V VOUT × ⎜⎜1 − OUT fS × ∆IL ⎝ VIN ⎛ VOUT V × ⎜⎜1 − OUT 2 × fS × L ⎝ VIN ⎞ ⎟⎟ ⎠ Table 1 lists a number of suitable inductors from various manufacturers. The choice of which inductor to use mainly depends on the price vs. size requirements and any EMI requirement. Table 1—Inductor Selection Guide R2 can be as high as 100kΩ, but a typical value is 10kΩ. Using that value, R1 is determined by: L= ILP = ILOAD + Where ILOAD is the load current. Where VFB is the feedback voltage and VOUT is the output voltage. VOUT = 1.22 × Choose an inductor that will not saturate under the maximum inductor peak current. The peak inductor current can be calculated by: Vendor/ Model Core Type Package Dimensions (mm) Core Material W L H Sumida CR75 Open Ferrite 7.0 7.8 5.5 CDH74 Open Ferrite 7.3 8.0 5.2 CDRH5D28 Shielded Ferrite 5.5 5.7 5.5 CDRH5D28 Shielded Ferrite 5.5 5.7 5.5 CDRH6D28 Shielded Ferrite 6.7 6.7 3.0 CDRH104R Shielded Ferrite 10.1 10.0 3.0 Toko D53LC Type A Shielded Ferrite 5.0 5.0 3.0 D75C Shielded Ferrite 7.6 7.6 5.1 D104C Shielded Ferrite 10.0 10.0 4.3 D10FL Open Ferrite 9.7 1.5 4.0 DO3308 Open Ferrite 9.4 13.0 3.0 DO3316 Open Ferrite 9.4 13.0 5.1 Coilcraft ⎞ ⎟⎟ ⎠ Where VIN is the input voltage, fS is the switching frequency and ∆IL is the peak-to-peak inductor ripple current. MP1593 Rev. 1.9 9/14/2006 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. 6 MP1593 – 3A, 28V, 385KHz STEP-DOWN CONVERTER Output Rectifier Diode The output rectifier diode supplies current to the inductor when the high-side switch is off. Use a Schottky diode to reduce losses due to diode forward voltage and recovery times. Choose a diode whose maximum reverse voltage rating is greater than the maximum input voltage, and whose current rating is greater than the maximum load current. Table 2 lists example Schottky diodes and manufacturers. The input capacitor can be electrolytic, tantalum or ceramic. When using electrolytic or tantalum capacitors, a small, high quality ceramic capacitor (i.e. 0.1µF) should be placed as close to the IC as possible. When using ceramic capacitors, make sure that they have enough capacitance to provide sufficient charge to prevent excessive voltage ripple at the input. The input voltage ripple caused by the capacitance can be estimated by: ∆VIN = Table 2—Diode Selection Guide Diode Voltage/Current Rating Manufacture SK33 SK34 B330 B340 MBRS330 MBRS340 30V, 3A 40V, 3A 30V, 3A 40V, 3A 30V, 3A 40V, 3A Diodes Inc. Diodes Inc. Diodes Inc. Diodes Inc. On Semiconductor On Semiconductor Input Capacitor The input current to the step-down converter is discontinuous, therefore a capacitor is required to supply the AC current to the step-down converter while maintaining the DC input voltage. Use low ESR capacitors for the best performance. Ceramic capacitors are preferred, but tantalum or low-ESR electrolytic capacitors will also suffice. Since the input capacitor (C1) absorbs the input switching current it requires an adequate ripple current rating. The RMS current in the input capacitor can be estimated by: I C1 = ILOAD VOUT ⎛⎜ VOUT × 1− × VIN ⎜⎝ VIN ⎞ ⎟ ⎟ ⎠ The worst-case condition occurs at VIN = 2VOUT, where: IC1 = ILOAD 2 For simplification, choose the input capacitor whose RMS current rating is greater than half of the maximum load current. MP1593 Rev. 1.9 9/14/2006 ⎛ ILOAD V V × OUT × ⎜1 − OUT fS × C1 VIN ⎜⎝ VIN ⎞ ⎟⎟ ⎠ Output Capacitor The output capacitor is required to maintain the DC output voltage. Ceramic, tantalum or low ESR electrolytic capacitors are recommended. Low ESR capacitors are preferred to keep the output voltage ripple low. The output voltage ripple can be estimated by: ∆VOUT = VOUT ⎛ V × ⎜1 − OUT f S × L ⎜⎝ VIN ⎞ ⎞ ⎛ 1 ⎟ ⎟⎟ × ⎜ R ESR + ⎜ 8 × f S × C2 ⎟⎠ ⎠ ⎝ Where L is the inductor value, C2 is the output capacitance value and RESR is the equivalent series resistance (ESR) value of the output capacitor. In the case of ceramic capacitors, the impedance at the switching frequency is dominated by the capacitance, which is the main cause of the output voltage ripple. For simplification, the output voltage ripple can be estimated by: ∆VOUT = ⎛ ⎞ V × ⎜⎜1 − OUT ⎟⎟ VIN ⎠ × L × C2 ⎝ VOUT 8 × fS 2 In the case of tantalum or electrolytic capacitors, the ESR dominates the impedance at the switching frequency. For simplification, the output ripple can be approximated to: ∆VOUT = VOUT ⎛ V × ⎜⎜1 − OUT fS × L ⎝ VIN ⎞ ⎟⎟ × R ESR ⎠ The characteristics of the output capacitor also affect the stability of the regulation system. The MP1593 can be optimized for a wide range of capacitance and ESR values. www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. 7 MP1593 – 3A, 28V, 385KHz STEP-DOWN CONVERTER Compensation Components The MP1593 employs current mode control for easy compensation and fast transient response. The system stability and transient response are controlled through the COMP pin. COMP is the output of the internal transconductance error amplifier. A series capacitor-resistor combination sets a pole-zero combination to control the characteristics of the control system. The DC gain of the voltage feedback loop is given by: A VDC = R LOAD × G CS × A VEA × VFB VOUT Where AVEA is the error amplifier voltage gain, GCS is the current sense transconductance and RLOAD is the load resistor value. The system has two poles of importance. One is due to the compensation capacitor (C3) and the output resistor of error amplifier, while the other is due to the output capacitor and the load resistor. These poles are located at: fP1 = GEA 2π × C3 × A VEA fP2 = 1 2π × C2 × R LOAD Where GEA is transconductance. the error In this case (as shown in Figure 3), a third pole set by the compensation capacitor (C6) and the compensation resistor (R3) is used to compensate the effect of the ESR zero on the loop gain. This pole is located at: f P3 = 1 2π × C6 × R3 The goal of compensation design is to shape the converter transfer function to get a desired loop gain. The system crossover frequency (where the feedback loop has unity gain) is important. Lower crossover frequencies result in slower line and load transient responses, while higher crossover frequencies could cause system instability. A good standard is to set the crossover frequency to approximately one-tenth of the switching frequency. The switching frequency for the MP1593 is 385KHz, so the desired crossover frequency is around 38KHz. Table 3 lists the typical values of compensation components for some standard output voltages with various output capacitors and inductors. The values of the compensation components have been optimized for fast transient responses and good stability at given conditions. amplifier The system has one zero of importance, due to the compensation capacitor (C3) and the compensation resistor (R3). This zero is located at: f Z1 = 1 2π × C3 × R3 The system may have another zero of importance, if the output capacitor has a large capacitance and/or a high ESR value. The zero, due to the ESR and capacitance of the output capacitor, is located at: fESR = MP1593 Rev. 1.9 9/14/2006 1 2π × C2 × R ESR www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. 8 MP1593 – 3A, 28V, 385KHz STEP-DOWN CONVERTER Table 3—Compensation Values for Typical Output Voltage/Capacitor Combinations VOUT 1.8V L 4.7µH C2 R3 C3 C6 100µF Ceramic 5.6kΩ 3.3nF None 2.5V 4.76.8µH 47µF Ceramic 3.9kΩ 5.6nF None 3.3V 6.810µH 22µFx2 Ceramic 5.6kΩ 8.2nF None 5V 1015µH 22µFx2 Ceramic 7.5kΩ 10nF None 12V 1522µH 22µFx2 Ceramic 10kΩ 3.3nF None 1.8 4.7µH 100µF SP-CAP 5.6kΩ 3.3nF 100pF 2.5V 4.76.8µH 47µF SP-CAP 4.7kΩ 5.6nF None 3.3V 6.810µH 47µF SP-CAP 6.8kΩ 10nF None 5V 1015µH 47µF SP CAP 10kΩ 10nF None 2.5V 4.76.8µH 560µF Al. 30mΩ ESR 10kΩ 5.6nF 1.5nF 3.3V 6.810µH 560µF Al 30mΩ ESR 10kΩ 8.2nF 1.5nF 5V 1015µH 470µF Al. 30mΩ ESR 15kΩ 5.6nF 1nF 12V 1522µH 220µF Al. 30mΩ ESR 15kΩ 4.7nF 390pF To optimize the compensation components for conditions not listed in Table 3, the following procedure can be used. 1. Choose the compensation resistor (R3) to set the desired crossover frequency. Determine R3 by the following equation: R3 = 2π × C2 × f C VOUT × G EA × G CS VFB Where fC is the desired crossover frequency (which typically has a value no higher than 38KHz). 2. Choose the compensation capacitor (C3) to achieve the desired phase margin. For applications with typical inductor values, setting the compensation zero, fZ1, below one forth of the crossover frequency provides sufficient phase margin. MP1593 Rev. 1.9 9/14/2006 Determine C3 by the following equation: C3 > 4 2π × R3 × f C Where R3 is the compensation resistor value. 3. Determine if the second compensation capacitor (C6) is required. It is required if the ESR zero of the output capacitor is located at less than half of the 385KHz switching frequency, or the following relationship is valid: f 1 < S 2π × C2 × R ESR 2 Where C2 is the output capacitance value, RESR is the ESR value of the output capacitor and fS is the switching frequency. If this is the case, then add the second compensation capacitor (C6) to set the pole fP3 at the location of the ESR zero. Determine C6 by the equation: C6 = C2 × R ESR R3 Where C2 is the output capacitance value, RESR is the ESR value of the output capacitor and R3 is the compensation resistor. External Bootstrap Diode It is recommended that an external bootstrap diode be added when the system has a 5V fixed input or the power supply generates a 5V output. This helps improve the efficiency of the regulator. The bootstrap diode can be a low cost one such as IN4148 or BAT54. 5V 1 BS 10nF MP1593 3 SW Figure 2—External Bootstrap Diode This diode is also recommended for high duty cycle operation (when VOUT >65%) and high VIN output voltage (VOUT>12V) applications. www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. 9 MP1593 – 3A, 28V, 385KHz STEP-DOWN CONVERTER TYPICAL APPLICATION CIRCUITS C5 10nF INPUT 4.75V to 28V OFF ON 7 1 BS 3 SW 2 IN EN OUTPUT 2.5V 3A MP1593 8 SS GND FB COMP 4 6 C6 5 C3 3.3nF D1 B340A (optional) Figure 3—MP1593 with AVX 47µF, 6.3V Ceramic Output Capacitor C5 10nF INPUT 4.75V to 28V OFF ON 1 BS 3 SW 2 IN 7 EN OUTPUT 2.5V 3A MP1593 8 SS GND FB COMP 4 5 6 C6 C3 3.3nF D1 B340A (optional) Figure 4—MP1593 with Panasonic 47µF, 6.3V Special Polymer Output Capacitor MP1593 Rev. 1.9 9/14/2006 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. 10 MP1593 – 3A, 28V, 385KHz STEP-DOWN CONVERTER PACKAGE INFORMATION SOIC8E (EXPOSED PAD) 0.189(4.80) 0.197(5.00) 0.124(3.15) 0.136(3.45) 8 5 0.150(3.80) 0.157(4.00) PIN 1 ID 1 0.228(5.80) 0.244(6.20) 0.089(2.26) 0.101(2.56) 4 TOP VIEW BOTTOM VIEW SEE DETAIL "A" 0.051(1.30) 0.067(1.70) SEATING PLANE 0.000(0.00) 0.006(0.15) 0.013(0.33) 0.020(0.51) 0.0075(0.19) 0.0098(0.25) SIDE VIEW 0.050(1.27) BSC FRONT VIEW 0.010(0.25) x 45o 0.020(0.50) GAUGE PLANE 0.010(0.25) BSC 0.050(1.27) 0.024(0.61) 0o-8o 0.016(0.41) 0.050(1.27) 0.063(1.60) DETAIL "A" 0.103(2.62) 0.213(5.40) NOTE: 0.138(3.51) RECOMMENDED LAND PATTERN 1) CONTROL DIMENSION IS IN INCHES. DIMENSION IN BRACKET IS IN MILLIMETERS. 2) PACKAGE LENGTH DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. 3) PACKAGE WIDTH DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. 4) LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.004" INCHES MAX. 5) DRAWING CONFORMS TO JEDEC MS-012, VARIATION BA. 6) DRAWING IS NOT TO SCALE. NOTICE: The information in this document is subject to change without notice. Users should warrant and guarantee that third party Intellectual Property rights are not infringed upon when integrating MPS products into any application. MPS will not assume any legal responsibility for any said applications. MP1593 Rev. 1.9 9/14/2006 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. 11