POWERINT TNY377G

Obsolete Product – Not Recommended for New Designs
TNY375-380
TinySwitch-PK Family
®
Energy-Efficient, Off-Line Switcher With
Enhanced Peak Power Performance
Product Highlights
Lowest System Cost with Enhanced Flexibility
• Simple ON/OFF control, no loop compensation needed
• Unique Peak Mode feature extends power range without
increasing transformer size
• Maximum frequency and current limit boosted at peak loads
• Selectable current limit through BP/M capacitor value
• Higher current limit extends maximum power in open frame
• Lower current limit improves efficiency in enclosed adapters
• Allows optimum TinySwitch-PK choice by swapping devices
with no other circuit redesign
• Tight I2f parameter tolerance reduces system cost
• Maximizes MOSFET and magnetics power delivery
• ON time extension – typically extends low line regulation range/
hold-up time to reduce input bulk capacitance
• Self-biased: no bias winding required for TNY375-376; winding
required for TNY377-380
• Frequency jittering reduces EMI filter costs
• Optimized pin out eases pcb/external heat sinking
• Quiet source-connected heat sink pins for low EMI
Enhanced Safety and Reliability Features
• Accurate hysteretic thermal shutdown with automatic recovery
provides complete system level overload protection and
eliminates need for manual reset
• Auto-restart delivers <3% maximum power in short circuit and
open loop fault conditions
• Output overvoltage shutdown with optional Zener
• Line undervoltage detect threshold set using a single resistor
• Very low component count enhances reliability and enables
single sided printed circuit board layout
• High bandwidth provides fast turn on with no overshoot and
excellent transient load response
• Extended creepage between DRAIN and all other pins improves
field reliability
®
EcoSmart – Extremely Energy Efficient
• Easily meets all global energy efficiency regulations
• No-load <170 mW at 265 VAC without bias winding, <60 mW
with bias winding
• ON/OFF control provides constant efficiency down to very light
loads – ideal for mandatory CEC efficiency regulations and 1 W
PC standby requirements
Applications
• Applications with high peak-to-continuous power demands –
DVDs, PVRs, active speakers (e.g. PC audio), audio amplifiers,
modems, photo printers
• Applications with high power demands at startup (large output
capacitance or motor loads) – PC standby, low voltage motor
drives
www.powerint.com +
AC
IN
DC
OUT
D
TinySwitch-PK
EN/UV
BP/M
S
PI-4266-012009
Figure 1.
Typical Peak Power Application.
Output Power Table
230 VAC ± 15%
Product3
Adapter1
Open
Frame2
85-265 VAC
Peak Adapter1
Open
Frame2
Peak
TNY375P/G/D4
8.5 W
15 W
16.5 W
6W
TNY376P/G/D4
10 W
19 W
22 W
7W
15 W
17 W
TNY377P/G
13 W
23.5 W
28 W
8W
18 W
23 W
11.5 W 12.5 W
TNY378P/G
16 W
28 W
34 W
10 W
21.5 W
27 W
TNY379P/G
18 W
32 W
39 W
12 W
25 W
31 W
TNY380P/G
20 W
36.5 W
45 W
14 W
28.5 W
35 W
Table 1. Output Power Table.
Notes:
1. Minimum continuous power in a typical non-ventilated enclosed adapter
measured at +50 °C ambient. Use of an external heat sink will increase power
capability.
2. Minimum continuous power in an open frame design (see Key Applications
Considerations).
3. Packages: P: DIP-8C, G: SMD-8C, D: SO-8C. Lead free only. See Part Ordering
Information.
4. See Key Application Considerations.
Description
TinySwitch-PK incorporates a 700 V MOSFET, oscillator, highvoltage switched current source, current limit (user selectable),
and thermal shutdown circuitry. A unique peak mode feature
boosts current limit and frequency for peak load conditions. The
boosted current limit provides the peak output power while the
increased peak mode frequency ensures the transformer can be
sized for continuous load conditions rather than peak power
demands.
September 2012
TNY375-380
BYPASS/
MULTI-FUNCTION
(BP/M)
115 A
DRAIN
(D)
REGULATOR
5.85 V
LINE UNDER-VOLTAGE
25 A
FAULT
PRESENT
AUTORESTART
COUNTER
RESET
+
BYPASS PIN
UNDER-VOLTAGE
BYPASS
CAPACITOR
SELECT AND 5.85 V
4.9 V
CURRENT
LIMIT STATE
MACHINE
VI
LIMIT
CURRENT LIMIT
COMPARATOR
ENABLE
-
+
JITTER 2X
CLOCK
1.0 V + VT
DCMAX
THERMAL
SHUTDOWN
OSCILLATOR
ENABLE/
UNDERVOLTAGE
(EN/UV)
1.0 V
6.4 V
S
Q
R
Q
LEADING
EDGE
BLANKING
OVP
LATCH
RESET
SOURCE
(S)
PI-4550-121406
Figure 2
Functional Block Diagram.
Pin Functional Description
DRAIN (D) Pin:
This pin is the power MOSFET drain connection. It provides
internal operating current for both start-up and steady-state
operation.
BYPASS/MULTI-FUNCTION (BP/M) Pin:
This pin has multiple functions:
1. It is the connection point for an external bypass capacitor for
the internally generated 5.85 V supply.
2. It is a mode selector for the current limit value, depending on
the value of the capacitance added. Use of a 0.1 mF
capacitor results in the standard current limit value. Use of a
1 mF capacitor results in the current limit being reduced to
that of the next smaller device size. Use of a 10 mF capacitor
results in the current limit being increased to that of the next
larger device.
3. It provides a shutdown function. When the current into the
bypass pin exceeds 7 mA, the device latches off until the
BP/M voltage drops below 4.9 V, during a power down or
when a line undervoltage is detected. This can be used to
provide an output overvoltage function with a Zener diode
connected from the BP/M pin to a bias winding supply.
P Package (DIP-8C)
G Package (SMD-8C)
D Package (SO-8C)
EN/UV
1
8
S
BP/M
2
7
S
6
S
5
S
D
4
PI-4348-042809
Figure 3. Pin Configuration.
ENABLE/UNDERVOLTAGE (EN/UV) Pin:
This pin has dual functions: enable input and line undervoltage
sense. During normal operation, switching of the power
MOSFET is controlled by this pin. MOSFET switching is
terminated when a current greater than a threshold current is
drawn from this pin. Switching resumes when the current being
2
Rev. C 09/12
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TNY375-380
pulled from the pin drops to less than a threshold current. A
modulation of the threshold current reduces group pulsing. The
threshold current is between 75 mA and 115 mA.
The EN/UV pin also senses line undervoltage conditions through
an external resistor connected to the DC line voltage. If there is
no external resistor connected to this pin,
TinySwitch-PK detects its absence and disables the line undervoltage function.
SOURCE (S) Pin:
This pin is internally connected to the output MOSFET source for
high voltage power return and control circuit common.
TinySwitch-PK Functional Description
TinySwitch-PK combines a high voltage power MOSFET switch
with a power supply controller in one device. Unlike conventional
PWM (pulse width modulator) controllers, it uses a simple ON/
OFF control to regulate the output voltage.
The controller consists of an oscillator, enable circuit (sense and
logic), current limit state machine, 5.85 V regulator, BYPASS/
MULTI-FUNCTION pin undervoltage, overvoltage circuit, and
current limit selection circuitry, over-temperature protection,
current limit circuit, leading edge blanking, and a 700 V power
MOSFET. TinySwitch-PK incorporates additional circuitry for line
undervoltage sense, auto-restart, adaptive switching cycle
on-time extension, and frequency jitter. Figure 2 shows the
functional block diagram with the most important features.
Oscillator
The typical oscillator frequency is internally set to an average of
264 kHz (at the highest current limit level). Two signals are generated
from the oscillator: the maximum duty cycle signal (DCMAX) and the
clock signal that indicates the beginning of each cycle.
The oscillator incorporates circuitry that introduces a small
amount of frequency jitter, typically ±3% of the oscillator
frequency, to minimize EMI emission. The modulation rate of the
PI-4539-102207
600
500
VDRAIN
400
300
200
100
0
280 kHz
248 kHz
0
2.5
5
frequency jitter is set to 1 kHz to optimize EMI reduction for both
average and quasi-peak emissions. The frequency jitter should
be measured with the oscilloscope triggered at the falling edge of
the DRAIN waveform. The waveform in Figure 4 illustrates the
frequency jitter with an oscillator frequency of 264 kHz.
Enable Input and Current Limit State Machine
The enable input circuit at the EN/UV pin consists of a low
impedance source follower output set at 1.2 V. The current
through the source follower is limited to 115 mA. When the
current out of this pin exceeds the threshold current, a low logic
level (disable) is generated at the output of the enable circuit
until the current out of this pin is reduced to less than the
threshold current. This enable circuit output is sampled at the
beginning of each cycle on the rising edge of the clock signal.
If high, the power MOSFET is turned on for that cycle (enabled).
If low, the power MOSFET remains off (disabled). Since the
sampling is done only at the beginning of each cycle,
subsequent changes in the EN/UV pin voltage or current during
the remainder of the cycle are ignored. When a cycle is
disabled, the EN/UV pin is sampled at 264 kHz. This faster
sampling enables the power supply to respond faster without
being required to wait for completion of the full period.
The current limit state machine reduces the current limit by
discrete amounts at light loads when TinySwitch-PK is likely to
switch in the audible frequency range. The lower current limit
raises the effective switching frequency above the audio range
and reduces the transformer flux density, including the
associated audible noise. The state machine monitors the
sequence of enable events to determine the load condition and
adjusts the current limit level accordingly in discrete amounts.
Under most operating conditions (except when close to
no-load), the low impedance of the source follower keeps the
voltage on the EN/UV pin from going much below 1.2 V in the
disabled state. This improves the response time of the
optocoupler that is usually connected to this pin.
5.85 V Regulator and 6.4 V Shunt Voltage Clamp
The 5.85 V regulator charges the bypass capacitor connected
to the BYPASS pin to 5.85 V by drawing a current from the
voltage on the DRAIN pin whenever the MOSFET is off. The
BYPASS/MULTI-FUNCTION pin is the internal supply voltage
node. When the MOSFET is on, the device operates from the
energy stored in the bypass capacitor. Extremely low power
consumption of the internal circuitry allows the TNY375 and
TNY376 to operate continuously from current taken from the
DRAIN pin. A bypass capacitor value of 0.1 mF is sufficient for
both high frequency decoupling and energy storage.
In addition, there is a 6.4 V shunt regulator clamping the
BYPASS/MULTI-FUNCTION pin at 6.4 V when current is provided
to the BYPASS/MULTI-FUNCTION pin through an external
resistor. This facilitates powering of TinySwitch-PK externally
through a bias winding as required for TNY377-380. Powering
the TinySwitch-PK externally in this way also decreases the
no-load consumption to below 60 mW.
Time (µs)
Figure 4. Frequency Jitter.
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Rev. C 09/12
TNY375-380
BYPASS/MULTI-FUNCTION Pin Undervoltage
The BYPASS/MULTI-FUNCTION pin undervoltage circuitry
disables the power MOSFET when the BYPASS/MULTIFUNCTION pin voltage drops below 4.9 V in steady state
operation. Once the BYPASS/MULTI-FUNCTION pin voltage
drops below 4.9 V in steady state operation, it must rise back to
5.85 V to enable (turn-on) the power MOSFET.
Over Temperature Protection
The thermal shutdown circuitry senses the die temperature.
The threshold is typically set at 142 °C with 75 °C hysteresis.
When the die temperature rises above this threshold, the power
MOSFET is disabled and remains disabled, until the die
temperature falls by 75 °C, at which point it is re-enabled. A
large hysteresis of 75 °C (typical) is provided to prevent
overheating of the PC board due to a continuous fault condition.
Current Limit
The current limit circuit senses the current in the power
MOSFET. When this current exceeds the internal threshold
(ILIMIT ), the power MOSFET is turned off for the remainder of that
cycle. The current limit state machine reduces the current limit
threshold by discrete amounts under medium and light loads.
The leading edge blanking circuit inhibits the current limit
comparator for a short time (tLEB) after the power MOSFET is
turned on. This leading edge blanking time has been set so
that current spikes caused by typical capacitance and
secondary-side rectifier reverse recovery time will not cause
premature termination of the switching pulse.
PI-4320-030106
Auto-Restart
In the event of a fault condition such as output overload, output
short circuit, or an open loop condition, TinySwitch-PK enters
into auto-restart operation. An internal counter clocked by the
oscillator is reset every time the EN/UV pin is pulled low. If the
EN/UV pin is not pulled low for 8192 switching cycles
(or 32 ms), the power MOSFET switching is normally disabled
for 1 second (except in the case of line undervoltage condition,
in which case it is disabled until the condition is removed). The
V
300
DRAIN
200
100
0
10
V
DC-OUTPUT
5
0
1000
0
2000
auto-restart alternately enables and disables the switching of
the power MOSFET until the fault condition is removed.
Figure 5 illustrates auto-restart circuit operation in the presence
of an output short circuit.
In the event of a line undervoltage condition, the switching of
the power MOSFET is disabled beyond its normal 1 second
until the line undervoltage condition ends.
Adaptive Switching Cycle On-Time Extension
Adaptive switching cycle on-time extension keeps the cycle on
until current limit is reached, instead of prematurely terminating
after the DCMAX signal goes low. This feature reduces the
minimum input voltage required to maintain regulation, typically
extending hold-up time and minimizing the size of bulk
capacitor required. The on-time extension is disabled during
the startup of the power supply, and after auto-restart, until the
power supply output reaches regulation.
Line Undervoltage Sense Circuit
The DC line voltage can be monitored by connecting an
external resistor from the DC line to the EN/UV pin. During
power-up or when the switching of the power MOSFET is
disabled in auto-restart, the current into the EN/UV pin must
exceed 25 mA to initiate switching of the power MOSFET.
During power-up, this is accomplished by holding the BYPASS/
MULTI-FUNCTION pin to 4.9 V while the line undervoltage
condition exists. After the line undervoltage condition goes
away and the BYPASS/MULTI-FUNCTION pin has stabilized at
5.85 V, switching is initiated. Once MOSFET switching is
enabled, the DC line voltage is ignored unless the power supply
enters auto-restart mode in the event of a fault condition. When
the switching of the power MOSFET is disabled in auto-restart
mode and a line undervoltage condition exists, the auto-restart
counter is stopped. This stretches the disable time beyond its
normal 1 second until the line undervoltage condition ends.
The line undervoltage circuit also detects when there is no
external resistor connected to the EN/UV pin (less than ~1 mA
into the pin). In this case the line undervoltage function is
disabled.
TinySwitch-PK Operation
TinySwitch-PK devices operate in the current limit mode.
When enabled, the oscillator turns the power MOSFET on at the
beginning of each cycle. The MOSFET is turned off when the
current ramps up to the current limit or when the DCMAX limit is
reached (applicable when On-Time Extension is disabled).
Since the highest current limit level and frequency of a
TinySwitch-PK design are constant, the power delivered to the
load is proportional to the primary inductance of the transformer
and peak primary current squared. Hence, designing the
supply involves calculating the primary inductance of the
transformer for the maximum output power required. If the
TinySwitch-PK is appropriately chosen for the power level, the
current in the calculated inductance will ramp up to current limit
before the DCMAX limit is reached.
Time (ms)
Figure 5. Auto-Restart Operation.
4
Rev. C 09/12
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TNY375-380
The EN/UV pin signal is generated on the secondary by
comparing the power supply output voltage with a reference
voltage. The EN/UV pin signal is high when the power supply
output voltage is less than the reference voltage. In a typical
implementation, the EN/UV pin is driven by an optocoupler.
The collector of the optocoupler transistor is connected to the
EN/UV pin, and the emitter is connected to the SOURCE pin.
The optocoupler LED is connected in series with a Zener diode
across the DC output voltage to be regulated. When the output
voltage exceeds the target regulation voltage level (optocoupler
LED voltage drop plus Zener voltage), the optocoupler LED will
start to conduct, pulling the EN/UV pin low. The Zener diode
can be replaced by a TL431 reference circuit for improved
accuracy.
V
EN
CLOCK
DC
MAX
I DRAIN
V DRAIN
PI-2749-082305
Figure 6. Operation at Near Maximum Loading (fOSC 264 kHz).
V
EN
At near maximum load, TinySwitch-PK will conduct during
nearly all of its clock cycles (Figure 6). At slightly lower load, it
will “skip” additional cycles in order to maintain voltage
regulation at the power supply output (Figure 7). At medium
loads, more cycles will be skipped, the current limit will be
CLOCK
DC
ON/OFF Operation with Current Limit State Machine
The internal clock of the TinySwitch-PK runs at all times. At the
beginning of each clock cycle, it samples the EN/UV pin to
decide whether or not to implement a switch cycle, and based
on the sequence of samples over multiple cycles, it determines
the appropriate current limit. At high loads, the state machine
sets the current limit to its highest value. With TinySwitch-PK,
when the state machine sets the current limit to its highest
value, the oscillator frequency is also doubled, providing the
unique peak mode operation. At lighter loads, the state
machine sets the current limit to reduced values. At these lower
current limit levels, the oscillator frequency returns to the
standard value.
MAX
I DRAIN
V
EN
CLOCK
V DRAIN
DC
PI-2667-082305
Figure 7. Operation at Moderately Heavy Loading (fOSC 264 kHz).
Enable Function
TinySwitch-PK senses the EN/UV pin to determine whether or
not to proceed with the next switching cycle. The sequence of
cycles is used to determine the current limit. Once a cycle is
started, it always completes the cycle (even when the EN/UV
pin changes state halfway through the cycle). This operation
results in a power supply in which the output voltage ripple is
determined by the output capacitor, amount of energy per
switch cycle, and the delay of the feedback.
MAX
I DRAIN
V DRAIN
PI-4540-050407
Figure 8. Operation at Medium Loading (fOSC 132 kHz).
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Rev. C 09/12
TNY375-380
V
100
V
EN
PI-4866-101007
200
DC-INPUT
0
CLOCK
10
D
MAX
V
5
BYPASS
0
400
I DRAIN
200
0
V DRAIN
V
DRAIN
0
1
2
Time (ms)
PI-2348-030801
Figure 11. Power-up Without Optional External UV Resistor Connected
to EN/UV Pin.
PI-4541-042507
200
Figure 9. Operation at Very Light Load (fOSC 132 kHz).
V
100
PI-4865-101007
200
V
100
DC-INPUT
0
DC-INPUT
0
400
300
10
5
BYPASS
DRAIN
100
0
0
400
200
V
200
V
V
0
.5
1
Time (s)
Figure 12. Normal Power-down Timing (Without UV Resistor).
DRAIN
0
1
Time (ms)
Figure 10. Power-up With Optional External UV Resistor (4 MW) Connected
to EN/UV Pin.
PI-2395-030801
0
2
200
V
100
DC-INPUT
0
400
300
V
200
DRAIN
100
0
0
2.5
5
Time (s)
Figure 13. Slow Power-down Timing With Optional External (4 MW) UV Resistor Connected to EN/UV Pin.
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Rev. C 09/12
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TNY375-380
reduced, and the clock frequency is reduced to half that at the
highest current limit level (Figure 8). At very light loads, the
current limit will be reduced even further (Figure 9). Only a small
percentage of cycles will occur to satisfy the power consumption
of the power supply. The response time of the ON/OFF control
scheme is very fast compared to PWM control. This provides
tight regulation and excellent transient response.
Power Up/Down
The TinySwitch-PK requires only a 0.1 mF capacitor on the
BYPASS/MULTI-FUNCTION pin to operate with standard
current limit. Because of its small size, the time to charge this
capacitor is kept to an absolute minimum, typically 0.6 ms. The
time to charge will vary in proportion to the BYPASS/MULTIFUNCTION pin capacitor value when selecting different current
limits. Due to the high bandwidth of the ON/OFF feedback,
there is no overshoot at the power supply output. When an
external resistor (4 MW) is connected from the power supply
positive DC input to the EN/UV pin, the power MOSFET
switching will be delayed during power-up until the DC line
voltage exceeds the threshold (100 V). Figures 10 and 11 show
the power-up timing waveform in applications with and without
an external resistor (4 MW) connected to the EN/UV pin.
During power-down, when an external resistor is used, the
power MOSFET will switch for 32 ms after the output loses
regulation. The power MOSFET will then remain off without any
glitches since the undervoltage function prohibits restart when
the line voltage is low.
Figure 12 illustrates a typical power-down timing waveform.
Figure 13 illustrates a very slow power-down timing waveform,
as in standby applications. The external resistor (4 MW) is
connected to the EN/UV pin in this case to prevent unwanted
restarts.
With the TNY375 and TNY376, no bias winding is needed to
provide power to the chip because it draws the power directly
from the DRAIN pin (see Functional Description above). This
eliminates the cost of a bias winding and associated components.
For the TNY377-380 or for applications that require very low
no-load power consumption (50 mW), a resistor from a bias
winding to the BYPASS/MULTI-FUNCTION pin can provide the
power to the chip. The minimum recommended current supplied
is IS2 + IDIS. The BYPASS/MULTI-FUNCTION pin in this case will
be clamped at 6.4 V. This method will eliminate the power draw
from the DRAIN pin, thereby reducing the no-load power
consumption and improving full-load efficiency.
Current Limit Operation
Each switching cycle is terminated when the DRAIN current
reaches the current limit of the device. Current limit operation
provides good line ripple rejection and relatively constant power
delivery independent of input voltage.
BYPASS/MULTI-FUNCTION Pin Capacitor
The BYPASS/MULTI-FUNCTION pin can use a ceramic
capacitor as small as 0.1 mF for decoupling the internal power
supply of the device. A larger capacitor size can be used to
adjust the current limit. A 1 mF BP/M pin capacitor will select a
lower current limit equal to the standard current limit of the next
smaller device, and a 10 mF BP/M pin capacitor will select a
higher current limit equal to the standard current limit of the next
larger device. The TNY375 and TNY376 MOSFETs do not have
the capability to match the current limit of the next larger
devices in the family. The current limit is therefore increased to
the maximum capability of their respective MOSFETs. The
higher current limit level of the TNY380 is set to 1105 mA typical.
The smaller current limit of the TNY375 is set to 325 mA.
7
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Rev. C 09/12
TNY375-380
C5
330 pF
250 VAC
T1
EEL19
D1
FR106
L
F1
3.15 A
L1
5 mH
85-265
VAC
R1
100 Ω
C2
22 µF
400 V
C1
22 µF
400 V
C3
10 nF
1 kV
N
D3
1N4007
1
4
R2
47 Ω
D4
1N4007
D6
UF4003
L2
3.3 µH
D7
1N5819
L3
3.3 µH
D8
SB340
L4
3.3 µH
+12 V, 0.25 A
N.C.
VR1
P6KE180A
D2
FR106
6
11
7
3
8,9,10
D5
FR106
C9
1000 µF
10 V
5
JP2
C7
1000 µF
25 V
C5
220 µF
25 V
R4
200 Ω
1/2 W
R6
20 kΩ
1%
+5.0 V, 0.5 A
+3.3 V, 0.5 A
C6
100 µF
25 V
C10
470 µF
10 V
RTN
12
TinySwitch-PK
U1
TNY376P
D
EN/UV
U2B
LTV817A
BP
S
C4
10 µF
50 V
C11
47 µF
25 V
D9
UF4003
C8
470 µF
10 V
C12
220 µF
25 V
R3
1Ω
1/2 W
-12 V, 0.03 A
U2A
LTV817A
R5
1 kΩ
C14
100 nF
50 V
JP1
C13
10 µF
50 V
R7
6.34 kΩ
1%
R9
3.3 kΩ
U3
L431
2%
R8
10 kΩ
1%
PI-4673-012009
Figure 14. TNY376PN, Four Output, 7.5 W, 13 W Peak Universal Input Power Supply.
Applications Examples
The circuit shown in Figure 14 is a low cost universal AC input,
four-output flyback power supply utilizing a TNY376. The
continuous output power is 7.5 W with a peak of 13 W. The
output voltages are 3.3 V, 5 V, 12 V, and –12 V.
The rectified and filtered input voltage is applied to the primary
winding of T1. The other side of the transformer’s primary is
driven by the integrated MOSFET in U1. Diode D5, C3, R1, R2,
and VR1 compose the clamp circuit, limiting the leakage
inductance turn-off voltage spike on the DRAIN pin to a safe
value. The use of a combination Zener clamp and parallel RC
optimizes both EMI and energy efficiency.
Both the 3.3 V and 5 V outputs are sensed through resistors R6
and R7. The voltage across R8 is regulated to 2.5 V by reference
IC U3. If the voltage across R8 begins to exceed 2.5 V, then
current will flow in the LED inside the optocoupler U2, driven by
the cathode of U3. This will cause the transistor of the
optocoupler to sink current from the EN/UV pin of U1. When the
current exceeds the ENABLE pin threshold current, the next
switching cycle is inhibited. Conversely, when the voltage across
resistor R8 falls below 2.5 V, and the current out of the ENABLE
pin is below the threshold, a conduction cycle is allowed to
occur. By adjusting the number of enabled cycles, regulation is
maintained. As the load reduces, the number of enabled cycles
decreases, lowering the effective switching frequency and
scaling switching losses with load. This provides almost
constant efficiency down to very light loads, ideal for meeting
energy efficiency requirements.
The input filter circuit (C1, L1 and C2) reduces conducted EMI. To
improve common mode EMI, this design makes use of E-ShieldTM
shielding techniques in the transformer, reducing common mode
displacement currents, and reducing EMI. These techniques,
combined with the frequency jitter of TNY376, give excellent EMI
performance, with this design achieving >10 dBmV of margin to
EN55022 Class B conducted EMI limits.
For design flexibility, the value of C4 can be selected to pick one
of the three current limit options in U4. Doing so allows the
designer to select the current limit appropriate for the application.
•
•
•
Standard current limit is selected with a 0.1 mF BP/M pin
capacitor and is the normal choice for typical applications.
When a 1 mF BP/M pin capacitor is used, the current limit is
reduced, offering reduced RMS device currents and therefore
improved efficiency, but at the expense of maximum power
capability. This is ideal for thermally challenging designs where
dissipation must be minimized.
When a 10 mF BP/M pin capacitor is used, the current limit is
increased, extending the power capability for applications
requiring higher peak power or continuous power where the
thermal conditions allow.
Further flexibility comes from the current limits between adjacent
TinySwitch-PK family members being compatible. The reduced
current limit of a given device is equal to the standard current limit
of the next smaller device, and the increased current limit is equal
to the standard current limit of the next larger device.
8
Rev. C 09/12
www.powerint.com
TNY375-380
Key Application considerations
Peak Output Power Table
230 VAC ± 15%
TinySwitch-PK Design Considerations
Product
Output Power Table
Data sheet maximum output power table (Table 1) represents
the maximum practical continuous output power level that can
be obtained under the following assumed conditions:
1. The minimum DC input voltage is 100 V or higher for 85 VAC
input, or 220 V or higher for 230 VAC input or 115 VAC with
a voltage doubler. The value of the input capacitance should
be sized to meet these criteria for AC input designs.
2. Efficiency of 75%.
3. Minimum data sheet value of I2f.
4. Transformer primary inductance tolerance of ±10%.
5. Reflected output voltage (VOR) of 135 V.
6. Voltage only output of 12 V with an ultrafast PN rectifier diode.
7. Continuous conduction mode operation with transient KP*
value of 0.25.
8. Increased current limit is selected for peak and open frame
power columns and standard current limit for adapter
columns.
9. The part is board mounted with SOURCE pins soldered to
sufficient area of copper and/or a heat sink is used to keep
the SOURCE pin temperature at or below 110 °C for P and
G package and 100 °C for D packaged devices.
10.Ambient temperature of 50 °C for open frame designs and
40 °C for sealed adapters.
*KP. Below a value of 1, KP is the ratio of ripple to peak primary
current. A transient KP limit of ≥0.25 is recommended to avoid
premature termination of switching cycles due to initial current
limit (IINIT ) being exceeded, which reduces maximum output
power capability.
ILIMIT-
ILIMITPEAK
PEAKred
TNY375P/G/D
TNY376P/G/D
8.5 W
10 W
85-265 VAC
ILIMIT-
ILIMIT-
PEAKinc
PEAKred
14.5 W 16.5 W
19 W
22 W
5.5 W
6W
ILIMIT-
ILIMITPEAK
PEAKinc
11.5 W 12.5 W
15 W
17 W
TNY377P/G
13 W
23 W
28 W
8W
18 W
23 W
TNY378P/G
16 W
27.5 W
34 W
10 W
21.5 W
27 W
TNY379P/G
18 W
31.5 W
39 W
12 W
25 W
31 W
TNY380P/G
20 W
36 W
45 W
14 W
28 W
35 W
Table 2.
Peak Output Power Capability vs Current Limit Mode Selection.
The values shown in Table 1 for peak power assume operation
in ILIMITPEAKinc. For reference, Table 2 provides peak output
powers for each family member at all three selectable current
limit modes.
For both Table 1 and Table 2, the peak output power values are
limited electronically, based on minimum device I2f. Stated
differently, with sufficient heat sinking, these values could be
delivered indefinitely, but in most cases this would be
impractical. Adapter and open frame power values are
thermally limited and represent the practical continuous (or
average) output power in two common thermal environments.
Over Voltage Protection
The output overvoltage protection provided by TinySwitch-PK
uses an internal latch that is triggered by a threshold current of
approximately 7 mA into the BYPASS pin. In addition to an
internal filter, the BYPASS pin capacitor forms an external filter,
providing noise immunity from inadvertent triggering. For the
bypass capacitor to be effective as a high frequency filter, it
C9
2.2 nF
250 VAC
D1
1N4007
L
F1
3.15 A
D2
1N4007
C1
10 µF
400 V
185 - 265
VAC
T1
EFD25
1
VR3
P6KE170A
C2
22 µF
400 V
C8
10 nF
1 kV
3
D3
1N4007
D4
1N4007
L1
1 mH
5
2
VR2
1N5251B, 22 V
TinySwitch-PK
U1
TNY380P
D
EN/UV
R5
47 Ω
R6
21 kΩ 1/8 W
1%
BP
S
C5
220 µF
16 V +12 V
RTN
R4
20 Ω
VR1
BZX55B11
11 V, 2%
D6
UF4004
D7
UF4007
R10
3.9 MΩ
C4
1000 µF
16 V
6,7,8
R7
22 Ω
1/2 W
R9
3.9 MΩ
C3
D5
SB560 1000 µF
16 V
L2
3.3 µH
R1
1 kΩ
N
9,10
C6
10 µF
50 V
C7
1 µF
50 V
U2
PC817A
R2
390 Ω
1/8 W
R3
2 kΩ
1/8 W
PI-4674-012009
Figure 15. Single 230 VAC Input 20 W Continuous and 45 W Peak Power Supply Using TNY380PN.
9
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Rev. C 09/12
TNY375-380
should be located as close as possible to the SOURCE and
BYPASS pins of the device.
For best performance of the OVP function, it is recommended
that a relatively high bias winding voltage is used, in the range of
15 V-30 V. This minimizes the error voltage on the bias winding
due to leakage inductance and also ensures adequate voltage
during no-load operation from which to supply the IC device
consumption.
Selecting the Zener diode voltage to be approximately 6 V
above the bias winding voltage (28 V for 22 V bias winding)
gives good OVP performance for most designs but can be
adjusted to compensate for variations in leakage inductance.
Adding additional filtering can be achieved by inserting a low
value (10 W to 47 W) resistor in series with the bias winding
diode and/or the OVP Zener, as shown by R4 and R5 in
Figure 15. The resistor in series with the OVP Zener also limits
the maximum current into the BYPASS pin.
Reducing No-load Consumption
With the exception of the TNY375 and TNY376, a bias winding
must be used to provide supply current for the IC. This has the
additional benefit of reducing the typical no-load consumption
to <60 mW. Select the value of the resistor (R6 in Figure 15) to
provide the data sheet supply current equal to IS2 + |IDIS|. Although
in practice the bias voltage falls at low load, the reduction in
supply current through R6 is balanced against the reduced IC
consumption as the effective switching frequency reduces with
load.
Audible Noise
The cycle skipping mode of operation used in the TinySwitch-PK
devices can generate audio frequency components in the
transformer. To limit this audible noise generation, the
transformer should be designed such that the peak core flux
density is below 3000 Gauss (300 mT). Following this guideline,
and using the standard transformer production technique of dip
varnishing practically eliminates audible noise. Vacuum
impregnation of the transformer should not be used due to the
high primary capacitance and increased losses that results.
Ceramic capacitors that use dielectrics such as Z5U, when
used in clamp circuits, may also generate audio noise. If this is
the case, try replacing them with a capacitor having a different
dielectric or construction such as the film foil or metallized foil type.
TinySwitch-PK Layout Considerations
Single Point Grounding
Use a single point ground connection from the input filter
capacitor to the area of copper connected to the SOURCE pins.
When used as an auxiliary supply in a larger converter, a local
DC bus decoupling capacitor is recommended. A value of
100 nF is typical.
The bias winding should be returned directly to the input or
decoupling capacitor. This routes surge currents away from the
device during common mode line surge events.
Bypass Capacitor (CBP)
The BYPASS pin capacitor should be located as near as
possible to the BYPASS and SOURCE pins using a Kelvin
connection. No power current should flow through traces
connected to the BYPASS pin capacitor or optocoupler. If
using SMD components, a capacitor can be placed underneath
the package directly between BP and SOURCE pins.
When using a capacitor value of 1 mF or 10 mF to select the
reduced or increased current limit mode, it is recommended
that an additional 0.1 mF ceramic capacitor is placed directly
between BP and SOURCE pins.
Enable/Undervoltage Pin Node Connections
The EN/UV pin is a low-current, low-voltage pin, and noise
coupling can cause poor regulation and/or inaccurate line UV
levels. Traces connected to the EN/UV pin must be routed
away from any high current or high-voltage switching nodes,
including the drain pin and clamp components. This also
applies to the placement of the line undervoltage sense resistor
(RUV ). Drain connected traces must not be routed underneath
this component.
TinySwitch-PK determines the presence of the UV resistor via a
~1 mA current into the EN/UV pin at startup. When the undervoltage feature is not used ensure that leakage current into the
EN/UV pin is <<1 mA. This prevents false detection of the
presence of a UV resistor which may prevent correct start-up.
As the use of no-clean flux may increase leakage currents (by
reducing surface resistivity) care should be taken to follow the
flux suppliers guidance, specifically avoiding flux contamination.
Placing a 100 kW, 5% resistor between BP and EN/UV pins
eliminates this requirement by feeding current >ILUV(MAX) into the
EN/UV pin.
Primary Loop Area
The area of the primary loop that connects the input filter
capacitor, transformer primary, and TinySwitch-PK device
should be kept as small as possible.
Primary Clamp Circuit
A clamp is used to limit peak voltage on the DRAIN pin at turn
off. This can be achieved by using an RCD clamp or a Zener
and diode clamp across the primary winding. In all cases, to
minimize EMI, care should be taken to minimize the loop length
from the clamp components to the transformer and the
TinySwitch-PK device.
Thermal Considerations
The four SOURCE pins are internally connected to the IC lead
frame and provide the main path to remove heat from the
device. Therefore all the SOURCE pins should be connected to
a copper area underneath the TinySwitch-PK integrated circuit
to act not only as a single point ground, but also as a heat sink.
As this area is connected to the quiet source node, it should be
maximized for good heat sinking. Similarly, for axial output
diodes, maximize the PCB area connected to the cathode.
10
Rev. C 09/12
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TNY375-380
Return bias winding
directly to input capacitor
Copper area for
heat sinking
Maximize hatched copper
areas (
) for optimum
heat sinking
Safety Spacing
Y1Capacitor
Output
Rectifier
+
High-Voltage
Input Filter Capacitor
-
PRI
BIAS
S
TOP VIEW
TinySwitch-PK
S
S
PRI
D
BP/M
BIAS
T
r
a
n
s
f
o
r
m
e
r
SEC
S
EN/UV
CBP
Optocoupler
RUV
Bypass capacitor connection
to device should be short
Route connections to EN/UV pin
(including undervoltage resistor)
away from drain connected traces
-
DC +
OUT
PI-4675-090712
Figure 16. Layout Considerations for TinySwitch-PK Using P Package.
Output Diode
For best performance, the area of the loop connecting the
secondary winding, the Output Diode, and the Output Filter
Capacitor should be minimized. In addition, for axial diodes,
sufficient copper area should be provided at the anode and
cathode terminal of diode for heat sinking. A larger area is
preferred at the quiet cathode terminal. A large anode area can
increase high frequency radiated EMI.
1. Maximum drain voltage – Verify the VDS does not exceed
650 V at highest input voltage and peak (overload) output
power. The 50 V margin to the 700 V BVDSS specification
gives margin for design variation.
2. Maximum drain current – At maximum ambient temperature,
maximum input voltage, and peak output (overload) power,
verify drain current waveforms for any signs of transformer
saturation and excessive leading edge current spikes at
startup. Repeat under steady state conditions and verify that
the leading edge current spike event is below IINIT at the end
of the tLEB(Min). Under all conditions the maximum drain
current should be below the specified absolute maximum
ratings.
3. Thermal Check – At specified maximum output power,
minimum input voltage, and maximum ambient temperature,
verify that the temperature specifications are not exceeded
for TinySwitch-PK device, transformer, output diode, and
output capacitors. Enough thermal margin should be allowed
for part-to-part variation of the RDS(ON) of TinySwitch-PK device
as specified in the data sheet. Under low-line maximum
power, a maximum TinySwitch-PK device SOURCE pin
temperature of 110 °C is recommended to allow for these
variations.
Quick Design Checklist
Design Tools
As with any power supply design, all TinySwitch-PK designs
should be verified on the bench to make sure that component
specifications are not exceeded under worst case conditions.
The following minimum set of tests is strongly recommended:
Up-to-date information on design tools can be found at the
Power Integrations web site: www.powerint.com.
Y-Capacitor
The placement of the Y-capacitor should be directly from the
primary input filter capacitor positive terminal to the common/
return terminal of the transformer secondary. Such a placement
will route high magnitude common mode surge currents away
from the TinySwitch-PK device. Note – if an input π (C, L, C)
EMI filter is used, then the inductor in the filter should be placed
between the negative terminals on the input filter capacitors.
Optocoupler
Place the optocoupler physically close to the TinySwitch-PK
device to minimize the primary side trace lengths. Keep the
high current, high voltage drain and clamp traces away from the
optocoupler to prevent noise pick up.
11
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Rev. C 09/12
TNY375-380
Absolute Maximum Ratings(1,4)
DRAIN Voltage ....................................................-0.3 V to 700 V
DRAIN Peak Current: TNY375....................................... 0.6 A(5)
TNY376....................................... 0.8 A(5)
TNY377....................................... 1.4 A(5)
TNY378........................................2.2 A5)
TNY379....................................... 2.9 A(5)
TNY380....................................... 4.3 A(5)
EN/UV Voltage ....................................................... -0.3 V to 9 V
EN/UV Current ............................................................... 100 mA
BP/M Voltage ......................................................... -0.3 V to 9 V
Storage Temperature .......................................-65 °C to 150 °C
Operating Junction Temperature(2).................... -40 °C to 150 °C
Lead Temperature(3).........................................................260 °C
Notes:
1. All voltages referenced to SOURCE, TA = 25 °C.
2. Normally limited by internal circuitry.
3. 1/16 in. from case for 5 seconds.
4. Maximum ratings specified may be applied one at a time without causing permanent damage to the product.
Exposure to Absolute Maximum Rating conditions for
extended periods of time may affect product reliability.
5. The peak DRAIN current is allowed while the DRAIN voltage is simultaneously less than 400 V.
Thermal Impedance
Thermal Impedance: P or G Package:
(qJA) .................................70 °C/W(2); 60 °C/W(3)
(qJC)(1) ..................................................11 °C/W
D Package:
(qJA) ...............................100 °C/W(2); 80 °C/W(3)
(qJC)(2) ..................................................30 °C/W
Parameter
Symbol
Notes:
1. Measured on the SOURCE pin close to plastic interface.
2. Soldered to 0.36 sq. in. (232 mm2), 2 oz. (610 g/m2) copper
clad.
3. Soldered to 1 sq. in. (645 mm2), 2 oz. (610 g/m2) copper
clad.
Conditions
SOURCE = 0 V; TJ = -40 to 125 °C
See Figure 17
(Unless Otherwise Specified)
Min
Typ
Max
248
264
280
Units
Control Functions
fOSC
State Machine at
Highest Current
Limit Level
TJ = 25 °C
fOSC-Low
All Lower Current
Limit Levels
TJ = 25 °C
Output Frequency
See Note A
Maximum Duty Cycle
DCMAX
EN/UV Pin Upper
Turnoff Threshold
Current
IDIS
EN/UV Pin Voltage
VEN
IS1
DRAIN Supply Current
IS2
Average
pk-pk Jitter
16
Average
132
pk-pk Jitter
8
S1 Open
kHz
62
65
-150
-115
-90
IEN/UV = 25 mA
1.8
2.2
2.6
IEN/UV = -25 mA
0.8
1.2
1.6
EN/UV Current > IDIS (MOSFET Not
Switching) See Note B
EN/UV Open
(MOSFET
Switching at fOSC)
See Note C
%
290
mA
V
mA
TNY375
385
520
TNY376
460
600
TNY377
570
710
TNY378
740
900
TNY379
870
1060
TNY380
1100
1350
mA
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Rev. C 09/12
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TNY375-380
Parameter
Symbol
Conditions
SOURCE = 0 V; TJ = -40 to 125 °C
See Figure 17
(Unless Otherwise Specified)
Min
Typ
Max
Units
TNY375-378
-8.3
-5.4
-2.5
TNY379-380
-9.7
-7.1
-3.9
TNY375-378
-5
-3.5
-1.5
TNY379-380
-6.6
-4.8
-2.1
5.6
5.85
6.15
V
0.80
0.95
1.20
V
Control Functions (cont.)
BP/M Pin Charge
Current
BP/M Pin Voltage
BP/M Pin Voltage
Hysteresis
BP/M Pin Shunt
Voltage
EN/UV Pin Line Undervoltage Threshold
ICH1
ICH2
VBP/M
VBP/M = 0 V,
TJ = 25 °C
See Note D, E
VBP/M = 4 V,
TJ = 25 °C
See Note D, E
See Note D
VBP/MH
mA
VSHUNT
IBP = 2 mA
6.0
6.4
6.7
V
ILUV
TJ = 25 °C
22.5
25
27.5
mA
TNY375P
330
355
380
TNY375G/D
330
355
387
TNY376P
423
455
487
TNY376G/D
423
455
496
TNY377P
544
585
626
TNY377G
544
585
638
TNY378P
665
715
765
TNY378G
665
715
779
TNY379P
786
845
904
TNY379G
786
845
921
TNY380P
907
975
1043
TNY380G
907
975
1063
TNY375P
302
325
361
TNY375G/D
302
325
367
TNY376P
330
355
391
TNY376G/D
330
355
401
TNY377P
423
455
501
TNY377G
423
455
514
TNY378P
544
585
644
TNY378G
544
585
661
TNY379P
665
715
787
TNY379G
TNY380GN
665
715
808
786
845
930
786
845
955
Circuit Protection
di/dt = 72 mA/ms
TJ = 25 °C
See Note F
di/dt = 91 mA/ms
TJ = 25 °C
See Note F
Peak Current Limit
(BP/M Capacitor =
0.1 mF) See Note E
ILIMITPEAK
di/dt = 117 mA/ms
TJ = 25 °C
See Note F
di/dt = 143 mA/ms
TJ = 25 °C
See Note F
di/dt = 169 mA/ms
TJ = 25 °C
See Note F
di/dt = 195 mA/ms
TJ = 25 °C
See Note F
di/dt = 72 mA/ms
TJ = 25 °C
See Note F
di/dt = 91 mA/ms
TJ = 25 °C
See Note F
Peak Current Limit
(BP/M Capacitor =
1 mF) See Note E
di/dt = 117 mA/ms
TJ = 25 °C
See Note F
ILIMITPEAKred
di/dt = 143 mA/ms
TJ = 25 °C
See Note F
di/dt = 169 mA/ms
TJ = 25 °C
See Note F
di/dt = 195 mA/ms
TJ = 25 °C
See Note F
TNY380P
TNY380G
mA
mA
13
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Rev. C 09/12
TNY375-380
Parameter
Symbol
Conditions
SOURCE = 0 V; TJ = -40 to 125 °C
See Figure 17
(Unless Otherwise Specified)
Min
Typ
Max
TNY375P
349
375
413
TNY375G/D
349
375
424
TNY376P
465
500
550
TNY376G/D
465
500
565
TNY377P
665
715
787
TNY377G
665
715
808
TNY378P
786
845
930
TNY378G
786
845
955
TNY379P
907
975
1073
TNY379G
907
975
1102
TNY380P
1028
1105
1216
TNY380G
1028
1105
1249
Units
Circuit Protection (cont.)
Peak Current Limit
(BP/M Capacitor =
10 mF) See Note E
ILIMITPEAKinc
di/dt = 72 mA/ms
TJ = 25 °C
See Note F
di/dt = 91 mA/ms
TJ = 25 °C
See Note F
di/dt = 117 mA/ms
TJ = 25 °C
See Note F
di/dt = 143 mA/ms
TJ = 25 °C
See Note F
di/dt = 169 mA/ms
TJ = 25 °C
See Note F
di/dt = 195 mA/ms
TJ = 25 °C
See Note F
I2f = ILIMITPEAK(TYP)2 ×
fOSC(TYP)
TJ = 25 °C
BP/M Capacitor =
0.1 mF
Power Coefficient
I2f
I2f = ILIMITPEAKred(TYP)2 ×
fOSC(TYP)
TJ = 25 °C
BP/M Capacitor =
1 mF
I2f = ILIMITPEAKinc(TYP)2 ×
fOSC(TYP)
TJ = 25 °C
BP/M Capacitor =
10 mF
TNY375-380P
TNY375-376D
TNY375-380G
TNY375-380P
TNY375-376D
TNY375-380G
TNY375-380P
TNY375-376D
TNY375-380G
See Figure 20
TJ = 25 °C, See Note G
0.9 ×
I2f
0.9 ×
I2f
0.9 ×
I2f
0.9 ×
I2f
0.9 ×
I2f
0.9 ×
I2f
0.9 ×
I2f
0.9 ×
I2f
0.9 ×
I2f
I 2f
I2f
I2f
I2f
I2f
I2f
I2f
I2f
I2f
1.12 ×
I2f
1.16 ×
I2f
1.16 ×
I2f
1.16 ×
I2f
1.20 ×
I2f
1.20 ×
I2f
1.16 ×
I2f
1.20 ×
I2f
1.20 ×
I2f
0.75 ×
ILIMIT(MIN)
mA
A2Hz
Initial Current Limit
IINIT
Leading Edge
Blanking Time
tLEB
Current Limit Delay
tILD
Thermal Shutdown
Temperature
TSD
Thermal Shutdown
Hysteresis
TSDH
BP/M Pin Shutdown
Threshold Current
ISD
4
7
9
mA
BP/M Pin Power-Up
Reset Threshold
Voltage
VBP/M(RESET)
1.6
2.6
3.6
V
TJ = 25 °C
See Note G
mA
TNY375-377
190
235
TNY378-380
145
190
TJ = 25 °C
See Note G, H
ns
200
135
142
ns
150
75
°C
°C
14
Rev. C 09/12
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TNY375-380
Parameter
Symbol
Conditions
SOURCE = 0 V; TJ = -40 to 125 °C
See Figure 17
(Unless Otherwise Specified)
Min
Typ
Max
TJ = 25 °C
19
22
TJ = 100 °C
29
33
TJ = 25 °C
14
16
TJ = 100 °C
21
24
TJ = 25 °C
7.8
9.0
TJ = 100 °C
11.7
13.5
TJ = 25 °C
5.2
6.0
TJ = 100 °C
7.8
9.0
TJ = 25 °C
3.9
4.5
TJ = 100 °C
5.8
6.7
Units
Output
TNY375
ID = 28 mA
TNY376
ID = 35 mA
ON-State
Resistance
TNY377
ID = 45 mA
RDS(ON)
TNY378
ID = 55 mA
TNY379
ID = 65 mA
OFF-State Drain
Leakage Current
IDSS1
IDSS2
Breakdown
Voltage
BVDSS
TNY380
ID = 75 mA
TJ = 25 °C
2.6
3.0
TJ = 100 °C
3.9
4.5
VBP/M = 6.2 V
TNY375-376
50
VEN/UV = 0 V
VDS = 560 V
TJ = 125 °C
See Note I
TNY377-378
100
TNY379-380
200
VBP/M = 6.2 V
VDS = 375 V,
TJ = 50 °C
See Note G, I
VEN/UV = 0 V
VBP = 6.2 V, VEN/UV = 0 V,
See Note J, TJ = 25 °C
DRAIN Supply Voltage
Auto-Restart
ON-Time At fOSC
Auto-Restart
Duty Cycle
W
mA
15
700
V
50
V
tAR
TJ = 25 °C
See Note K
32
ms
DCAR
TJ = 25 °C
3
%
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Rev. C 09/12
TNY375-380
NOTES:
A. For all BP/M pin capacitor values.
B. IS1 is an accurate estimate of device controller current consumption at no-load, since operating frequency is so low under these
conditions. Total device consumption at no-load is the sum of IS1 and IDSS2.
C. Since the output MOSFET is switching, it is difficult to isolate the switching current from the supply current at the DRAIN. An
alternative is to measure the BP/M pin current at 6.1 V.
D. BP/M pin is not intended for sourcing supply current to external circuitry.
E. To ensure correct current limit, it is recommended that nominal 0.1 mF / 1 mF / 10 mF capacitors are used. In addition, the BP/M
capacitor value tolerance should be equal to or better than indicated below across the ambient temperature range of the target
application. The minimum and maximum capacitor values are guaranteed by characterization.
Nominal BP/M
Pin Cap Value
Tolerance Relative to Nominal
Capacitor Value
Min
Max
0.1 mF
-60%
+100%
1 mF
-50%
+100%
10 mF
-50%
NA
F. For current limit at other di/dt values, refer to Figure 24. Measurements made with device self-biased.
G. This parameter is derived from characterization.
H. This parameter is derived from the change in current limit measured at 1X and 4X of the di/dt shown in the ILIMIT specification.
I. IDSS1 is the worst-case OFF state leakage specification at 80% of BVDSS and maximum operating junction temperature. IDSS2 is a
typical specification under worst-case application conditions (rectified 265 VAC) for no-load consumption calculations.
J. Breakdown voltage may be checked against minimum BVDSS specification by ramping the DRAIN pin voltage up to but not
exceeding minimum BVDSS.
K. Auto-restart on time has the same temperature characteristics as the oscillator (inversely proportional to frequency).
16
Rev. C 09/12
www.powerint.com
TNY375-380
470 Ω
5W
S2
470 Ω
S
D
S1
S
S
S
2 MΩ
50 V
BP/M
EN/UV
10 V
0.1 μF
150 V
NOTE: This test circuit is not applicable for current limit or output characteristic measurements.
PI-4079-080905
Figure 17. General Test Circuit.
DCMAX
(internal signal)
tP
EN/UV
VDRAIN
tP =
tEN/UV
1
fOSC
PI-2364-012699
Figure 19. Output Enable Timing.
Figure 18. Duty Cycle Measurement.
0.8
Figure 20. Current Limit Envelope at fOSC = 132 kHz.
17
www.powerint.com
Rev. C 09/12
TNY375-380
1.0
PI-2680-012301
1.2
Output Frequency
(Normalized to 25 °C)
PI-2213-012301
Breakdown Voltage
(Normalized to 25 °C)
1.1
1.0
0.8
0.6
0.4
0.2
0
0.9
-50 -25
0
25
50
-50
75 100 125 150
Junction Temperature (°C)
50
75
100 125
0.8
0.6
0.4
0.2
PI-4268-042707
Normalized Current Limit
PI-4102-010906
1
1.4
1.2
1.0
0.8
TNY375
TNY376
TNY377
TNY378
TNY379
TNY380
0.6
0.4
0.2
Normalized
di/dt = 1
72 mA/µs
91 mA/µs
117 mA/µs
143 mA/µs
169 mA/µs
195 mA/µs
Note: For the
normalized current
limit value, use the
typical current limit
specified for the
appropriate BP/M
capacitor.
0
0
-50
0
50
100
1
150
2
300
225
150
TCASE=25 ϒC
TCASE=100 ϒC
75
0
2
4
6
DRAIN Voltage (V)
Figure 25. Output Characteristics.
8
10
PI-4269-120406
1000
Drain Capacitance (pF)
Scaling Factors:
TNY375 1.0
TNY376 1.33
TNY377 2.33
TNY378 3.67
TNY379 4.87
TNY380 7.33
375
4
Figure 24. Current Limit vs. di/dt.
PI-4267-120406
450
3
Normalized di/dt
Temperature (°C)
Figure 23. Standard Current Limit vs. Temperature.
Drain Current (mA)
25
Figure 22. Frequency vs. Temperature.
1.2
0
0
Junction Temperature (°C)
Figure 21. Breakdown vs. Temperature.
Standard Current Limit
(Normalized to 25 °C)
-25
100
Scaling Factors:
TNY375 1.0
TNY376 1.33
TNY377 2.33
TNY378 3.67
TNY379 4.87
TNY380 7.33
10
1
0
100
200
300
400
500
600
Drain Voltage (V)
Figure 26. COSS vs. Drain Voltage.
18
Rev. C 09/12
www.powerint.com
TNY375-380
90
60
30
0
1.0
0.8
0.6
0.4
0.2
0
0
200
400
DRAIN Voltage (V)
Figure 27. Drain Capacitance Power.
600
PI-2698-012301
1.2
Under-Voltage Threshold
(Normalized to 25 °C)
Scaling Factors:
TNY375 1.0
TNY376 1.33
TNY377 2.33
TNY378 3.67
TNY379 4.87
TNY380 7.33
120
Power (mW)
PI-4270-120406
150
-50
-25
0
25
50
75
100 125
Junction Temperature (°C)
Figure 28. Undervoltage Threshold vs. Temperature.
19
www.powerint.com
Rev. C 09/12
TNY375-380
SMD-8C (G Package)
⊕ D S .004 (.10)
.046 .060
.060 .046
-E-
.080
.086
.186
.372 (9.45)
.388 (9.86)
⊕ E S .010 (.25)
.240 (6.10)
.260 (6.60)
Pin 1
.286
Pin 1
.100 (2.54) (BSC)
.137 (3.48)
MINIMUM
Solder Pad Dimensions
.367 (9.32)
.387 (9.83)
-D-
.057 (1.45)
.068 (1.73)
(NOTE 5)
.125 (3.18)
.145 (3.68)
.032 (.81)
.037 (.94)
.420
Notes:
1. Controlling dimensions are
inches. Millimeter sizes are
shown in parentheses.
2. Dimensions shown do not
include mold flash or other
protrusions. Mold flash or
protrusions shall not exceed
.006 (.15) on any side.
3. Pin locations start with Pin 1,
and continue counter-clockwise to Pin 8 when viewed
from the top. Pin 3 is omitted.
4. Minimum metal to metal
spacing at the package body
for the omitted lead location
is .137 inch (3.48 mm).
5. Lead width measured at
package body.
6. D and E are referenced
datums on the package
body.
.004 (.10)
.048 (1.22)
.053 (1.35)
.009 (.23)
.004 (.10)
.012 (.30)
.036 (0.91)
.044 (1.12)
0°- 8°
G08C
PI-4015-101507
PDIP-8C (P Package)
-E-
⊕D S
.004 (.10)
.240 (6.10)
.260 (6.60)
Pin 1
-D-
.367 (9.32)
.387 (9.83)
.057 (1.45)
.068 (1.73)
(NOTE 6)
.125 (3.18)
.145 (3.68)
-T-
Notes:
1. Package dimensions conform to JEDEC specification
MS-001-AB (Issue B 7/85) for standard dual-in-line (DIP)
package with .300 inch row spacing.
2. Controlling dimensions are inches. Millimeter sizes are
shown in parentheses.
3. Dimensions shown do not include mold flash or other
protrusions. Mold flash or protrusions shall not exceed
.006 (.15) on any side.
4. Pin locations start with Pin 1, and continue counter-clockwise to Pin 8 when viewed from the top. The notch and/or
dimple are aids in locating Pin 1. Pin 3 is omitted.
5. Minimum metal to metal spacing at the package body for
the omitted lead location is .137 inch (3.48 mm).
6. Lead width measured at package body.
7. Lead spacing measured with the leads constrained to be
perpendicular to plane T.
.015 (.38)
MINIMUM
SEATING
PLANE
.120 (3.05)
.140 (3.56)
.100 (2.54) BSC
.014 (.36)
.022 (.56)
.048 (1.22)
.053 (1.35)
⊕T E D
.137 (3.48)
MINIMUM
S .010 (.25) M
.008 (.20)
.015 (.38)
.300 (7.62) BSC
(NOTE 7)
.300 (7.62)
.390 (9.91)
P08C
PI-3933-040110
20
Rev. C 09/12
www.powerint.com
TNY375-380
SO-8C (D Package)
4
B
0.10 (0.004) C A-B 2X
2
DETAIL A
4.90 (0.193) BSC
A
4
8
D
5
2 3.90 (0.154) BSC
GAUGE
PLANE
SEATING
PLANE
6.00 (0.236) BSC
0-8
C
1.04 (0.041) REF
2X
0.10 (0.004) C D
1
Pin 1 ID
4
1.35 (0.053)
1.75 (0.069)
0.25 (0.010)
BSC
0.40 (0.016)
1.27 (0.050)
0.20 (0.008) C
2X
7X 0.31 - 0.51 (0.012 - 0.020)
0.25 (0.010) M C A-B D
1.27 (0.050) BSC
o
1.25 - 1.65
(0.049 - 0.065)
DETAIL A
0.10 (0.004)
0.25 (0.010)
7X
0.10 (0.004) C
H
SEATING PLANE
0.17 (0.007)
0.25 (0.010)
C
Reference
Solder Pad
Dimensions
+
2.00 (0.079)
+
4.90 (0.193)
+
+
1.27 (0.050)
D07C
Notes:
1. JEDEC reference: MS-012.
2. Package outline exclusive of mold flash and metal burr.
3. Package outline inclusive of plating thickness.
4. Datums A and B to be determined at datum plane H.
5. Controlling dimensions are in millimeters. Inch dimensions
are shown in parenthesis. Angles in degrees.
0.60 (0.024)
PI-4526-040110
Part Ordering Information
• TinySwitch Product Family
• Series Number
• Package Identifier
G
Plastic Surface Mount SMD-8C
P
Plastic DIP-8C
D
Plastic Surface Mount SO-8C
• Lead Finish
N
Pure Matte Tin (Pb-Free) (Not available in D Package)
G
RoHS Compliant and Halogen Free (D Package only)
• Tape & Reel and Other Options
Blank
TNY 278 G N - TL
TL
Standard Configuration
Tape & Reel, 1000 pcs min./mult., G Package, 2500 pcs min./mult., D Package
21
www.powerint.com
Rev. C 09/12
Revision
Notes
Date
A
Release final data sheet.
05/07
B
Added G package and updated Limits.
11/07
C
Updated Part Ordering Information section with Halogen Free and added D package parts.
07/09
C
Updated Figure 16 layout schematic.
09/12
For the latest updates, visit our website: www.powerint.com
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Integrations does not assume any liability arising from the use of any device or circuit described herein. POWER INTEGRATIONS MAKES
NO WARRANTY HEREIN AND SPECIFICALLY DISCLAIMS ALL WARRANTIES INCLUDING, WITHOUT LIMITATION, THE IMPLIED
WARRANTIES OF MERCHANTABILITY, FITNESS FOR A PARTICULAR PURPOSE, AND NON-INFRINGEMENT OF THIRD PARTY RIGHTS.
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The products and applications illustrated herein (including transformer construction and circuits external to the products) may be covered
by one or more U.S. and foreign patents, or potentially by pending U.S. and foreign patent applications assigned to Power Integrations. A
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certain patent rights as set forth at http://www.powerint.com/ip.htm.
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POWER INTEGRATIONS PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR
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2. A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to cause
the failure of the life support device or system, or to affect its safety or effectiveness.
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