2050 MHz to 3000 MHz Quadrature Modulator with 2500 MHz to 2900 MHz Frac-N PLL and Integrated VCO ADRF6704 Data Sheet modulator, PLL, and VCO provides for significant board savings and reduces the BOM and design complexity. FEATURES IQ modulator with integrated fractional-N PLL Output frequency range: 2050 MHz to 3000 MHz Internal LO frequency range: 2500 MHz to 2900 MHz Output P1dB: 12.1 dBm @ 2700 MHz Output IP3: 27.2 dBm @ 2700 MHz Noise floor: −158.3 dBm/Hz @ 2700 MHz Baseband bandwidth: 750 MHz (3 dB) SPI serial interface for PLL programming Integrated LDOs and LO buffer Power supply: 5 V/226 mA 40-lead 6 mm × 6 mm LFCSP The integrated fractional-N PLL/synthesizer generates a 2× fLO input to the IQ modulator. The phase detector together with an external loop filter is used to control the VCO output. The VCO output is applied to a quadrature divider. To reduce spurious components, a sigma-delta (Σ-Δ) modulator controls the programmable PLL divider. The IQ modulator has wideband differential I and Q inputs, which support baseband as well as complex IF architectures. The single-ended modulator output is designed to drive a 50 Ω load impedance and can be disabled. APPLICATIONS Cellular communications systems GSM/EDGE, CDMA2000, W-CDMA, TD-SCDMA, LTE Broadband wireless access systems Satellite modems The ADRF6704 is fabricated using an advanced silicongermanium BiCMOS process. It is available in a 40-lead, exposed-paddle, Pb-free, 6 mm × 6 mm LFCSP package. Performance is specified from −40°C to +85°C. A lead-free evaluation board is available. GENERAL DESCRIPTION Table 1. The ADRF6704 provides a quadrature modulator and synthesizer solution within a small 6 mm × 6 mm footprint while requiring minimal external components. Part No. ADRF6701 The ADRF6704 is designed for RF outputs from 2050 MHz to 3000 MHz. The low phase noise VCO and high performance quadrature modulator make the ADRF6704 suitable for next generation communication systems requiring high signal dynamic range and linearity. The integration of the IQ IQ Modulator ±3 dB RF Output Range 400 MHz 1250 MHz 1200 MHz 2400 MHz 1550 MHz 2650 MHz 2050 MHz 3000 MHz Internal LO Range 750 MHz 1150 MHz 1550 MHz 2150 MHz 2100 MHz 2600 MHz 2500 MHz 2900 MHz ADRF6702 ADRF6703 ADRF6704 FUNCTIONAL BLOCK DIAGRAM VCC7 VCC6 VCC5 VCC4 VCC3 VCC2 VCC1 34 29 27 22 17 10 1 LOSEL 36 ADRF6704 DIVIDER ÷2 BUFFER LOP 38 BUFFER DATA 12 CLK 13 LE 14 FRACTION REG SPI INTERFACE MODULUS 2:1 MUX INTEGER REG THIRD-ORDER FRACTIONAL INTERPOLATOR ×2 REFIN 6 ÷2 N COUNTER 21 TO 123 MUX TEMP SENSOR ÷4 7 11 15 20 21 23 25 28 30 31 35 GND ÷2 0/90 CHARGE PUMP 250µA, 500µA (DEFAULT), 750µA, 1000µA – PHASE + FREQUENCY DETECTOR MUXOUT 8 4 VCO CORE PRESCALER ÷2 24 5 NC RSET NOTES 1. NC = NO CONNECT. DO NOT CONNECT TO THIS PIN. 3 39 16 40 DECL3 9 DECL2 2 DECL1 18 QP 19 QN 32 IN 33 IP 26 CP VTUNE ENOP RFOUT 08571-001 LON 37 Figure 1. Rev. 0 Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 www.analog.com Fax: 781.461.3113 ©2011 Analog Devices, Inc. All rights reserved. ADRF6704 Data Sheet TABLE OF CONTENTS Features .............................................................................................. 1 Baseband Bandwidth ................................................................. 19 Applications....................................................................................... 1 Device Programming and Register Sequencing..................... 19 General Description ......................................................................... 1 Register Summary .......................................................................... 20 Functional Block Diagram .............................................................. 1 Register Description....................................................................... 21 Revision History ............................................................................... 2 Register 0—Integer Divide Control (Default: 0x0001C0) .... 21 Specifications..................................................................................... 3 Register 1—Modulus Divide Control (Default: 0x003001).. 22 Timing Characteristics ................................................................ 6 Register 2—Fractional Divide Control (Default: 0x001802) ..22 Absolute Maximum Ratings............................................................ 7 Register 3—Σ-Δ Modulator Dither Control (Default: 0x10000B).................................................................................... 23 ESD Caution.................................................................................. 7 Pin Configuration and Function Descriptions............................. 8 Typical Performance Characteristics ........................................... 10 Theory of Operation ...................................................................... 16 PLL + VCO.................................................................................. 16 Register 4—PLL Charge Pump, PFD, and Reference Path Control (Default: 0x12A7E4).................................................... 24 Register 5—LO Path and Modulator Control (Default: 0x0000E5).................................................................................... 26 Basic Connections for Operation............................................. 16 Register 6—VCO Control and VCO Enable (Default: 0x1E2106).................................................................................... 27 External LO ................................................................................. 16 Characterization Setups................................................................. 28 Loop Filter ................................................................................... 17 Evaluation Board ............................................................................ 30 DAC-to-IQ Modulator Interfacing .......................................... 18 Evaluation Board Control Software......................................... 30 Adding a Swing-Limiting Resistor ........................................... 18 Outline Dimensions ....................................................................... 35 IQ Filtering .................................................................................. 19 Ordering Guide .......................................................................... 35 REVISION HISTORY 10/11—Revision 0: Initial Version Rev. 0 | Page 2 of 36 Data Sheet ADRF6704 SPECIFICATIONS VS = 5 V; TA = 25°C; baseband I/Q amplitude = 1 V p-p differential sine waves in quadrature with a 500 mV dc bias; baseband I/Q frequency (fBB) = 1 MHz; fPFD = 38.4 MHz; fREF = 153.6 MHz at +4 dBm Re:50 Ω (1 V p-p); 130 kHz loop filter, unless otherwise noted. Table 2. Parameter Test Conditions/Comments Min OPERATING FREQUENCY RANGE IQ modulator (±3 dB RF output range) PLL LO range RFOUT pin Baseband VIQ = 1 V p-p differential RF output divided by baseband input voltage 2050 2500 RF OUTPUT = 2500 MHz Nominal Output Power IQ Modulator Voltage Gain OP1dB Carrier Feedthrough Sideband Suppression Quadrature Error I/Q Amplitude Balance Second Harmonic Third Harmonic Output IP2 Output IP3 Noise Floor RF OUTPUT = 2700 MHz Nominal Output Power IQ Modulator Voltage Gain OP1dB Carrier Feedthrough Sideband Suppression Quadrature Error I/Q Amplitude Balance Second Harmonic Third Harmonic Output IP2 Output IP3 Noise Floor RF OUTPUT = 2900 MHz Nominal Output Power IQ Modulator Voltage Gain OP1dB Carrier Feedthrough Sideband Suppression Quadrature Error I/Q Amplitude Balance Second Harmonic Third Harmonic Output IP2 Output IP3 Noise Floor SYNTHESIZER SPECIFICATIONS Internal LO Range Figure of Merit (FOM) 1 POUT − P (fLO ± (2 × fBB)) POUT − P (fLO ± (3 × fBB)) f1BB = 3.5 MHz, f2BB = 4.5 MHz, POUT ≈ −2 dBm per tone f1BB = 3.5 MHz, f2BB = 4.5 MHz, POUT ≈ −2 dBm per tone I/Q inputs = 0 V differential with 500 mV dc bias, 20 MHz carrier offset RFOUT pin Baseband VIQ = 1 V p-p differential RF output divided by baseband input voltage POUT − P (fLO ± (2 × fBB)) POUT − P (fLO ± (3 × fBB)) f1BB = 3.5 MHz, f2BB = 4.5 MHz, POUT ≈ −2 dBm per tone f1BB = 3.5 MHz, f2BB = 4.5 MHz, POUT ≈ −2 dBm per tone I/Q inputs = 0 V differential with 500 mV dc bias, 20 MHz carrier offset RFOUT pin Baseband VIQ = 1 V p-p differential RF output divided by baseband input voltage POUT − P (fLO ± (2 × fBB)) POUT − P (fLO ± (3 × fBB)) f1BB = 3.5 MHz, f2BB = 4.5 MHz, POUT ≈ −2 dBm per tone f1BB = 3.5 MHz, f2BB = 4.5 MHz, POUT ≈ −2 dBm per tone) I/Q inputs = 0 V differential with 500 mV dc bias, 20 MHz carrier offset Synthesizer specifications referenced to the modulator output Typ Unit MHz MHz 6.2 2.2 12.9 −41.2 −42.4 ±1 0.06 −67 −45.6 65.4 25.4 −157.8 dBm dB dBm dBm dBc Degrees dB dBc dBc dBm dBm dBm/Hz 5.5 1.5 12.1 −40.6 −37.7 0 to 2 0.06 −66 −47.1 63.8 27.2 −158.3 dBm dB dBm dBm dBc Degrees dB dBc dBc dBm dBm dBm/Hz 4.1 0.1 11.8 −41.5 −32.7 1 to 2.8 0.1 −67 −51.4 62.7 29.6 −157.5 dBm dB dBm dBm dBc Degrees dB dBc dBc dBm dBm dBm/Hz 2500 2900 −221.4 Rev. 0 | Page 3 of 36 Max 3000 2900 MHz dBc/Hz/Hz ADRF6704 Data Sheet Parameter Test Conditions/Comments REFERENCE CHARACTERISTICS REFIN Input Frequency REFIN Input Capacitance Phase Detector Frequency MUXOUT Output Level REFIN, MUXOUT pins Min 11 22 Integrated Phase Noise Reference Spurs PHASE NOISE (FREQUENCY = Unit 160 MHz pF MHz V 40 0.25 Low (lock detect output selected) High (lock detect output selected) PHASE NOISE (FREQUENCY = 2500 MHz, fPFD = 38.4 MHz) Max 4 2.7 MUXOUT Duty Cycle CHARGE PUMP Charge Pump Current Output Compliance Range Typ V 50 Programmable to 250 μA, 500 μA, 750 μA, 1000 μA % 500 1 2.8 μA V Closed loop operation (see Figure 35 for loop filter design) 10 kHz offset 100 kHz offset 1 MHz offset 10 MHz offset 1 kHz to 10 MHz integration bandwidth fPFD/2 fPFD fPFD × 2 fPFD × 3 fPFD × 4 Closed loop operation (see Figure 35 for loop filter design) −100.9 −100 −126 −148.3 0.37 −111 −87.3 −93.6 −92.8 −98.2 dBc/Hz dBc/Hz dBc/Hz dBc/Hz °rms dBc dBc dBc dBc dBc 10 kHz offset 100 kHz offset 1 MHz offset 10 MHz offset 1 kHz to 10 MHz integration bandwidth fPFD/2 fPFD fPFD × 2 fPFD × 3 fPFD × 4 Closed loop operation (see Figure 35 for loop filter design) −97.7 −97.6 −126.1 −148.4 0.46 −110.4 −89.9 −92 −89.9 −94.5 dBc/Hz dBc/Hz dBc/Hz dBc/Hz °rms dBc dBc dBc dBc dBc 10 kHz offset 100 kHz offset 1 MHz offset 10 MHz offset 1 kHz to 10 MHz integration bandwidth fPFD/2 fPFD fPFD × 2 fPFD × 3 fPFD × 4 Measured at RFOUT, frequency = 2700 MHz Second harmonic Third harmonic LOP, LON Divide by 2 circuit in LO path enabled Divide by 2 circuit in LO path disabled 1× LO mode, into a 50 Ω load, LO buffer enabled Externally applied 2× LO, PLL disabled Externally applied 2× LO, PLL disabled −92.3 −96.4 −125.2 −148.5 0.62 −110.7 −90.9 −89.8 −92.1 −93.7 dBc/Hz dBc/Hz dBc/Hz dBc/Hz °rms dBc dBc dBc dBc dBc −44.4 −76.7 dBc dBc 2700 MHz, fPFD = 38.4 MHz) Integrated Phase Noise Reference Spurs PHASE NOISE (FREQUENCY = 2900 MHz, fPFD = 38.4 MHz) Integrated Phase Noise Reference Spurs RF OUTPUT HARMONICS LO INPUT/OUTPUT Output Frequency Range LO Output Level at 2700 MHz LO Input Level LO Input Impedance Rev. 0 | Page 4 of 36 2500 5000 2900 5800 −2 0 50 MHz MHz dBm dBm Ω Data Sheet ADRF6704 Parameter Test Conditions/Comments BASEBAND INPUTS I and Q Input DC Bias Level Bandwidth IP, IN, QP, QN pins Differential Input Impedance Differential Input Capacitance LOGIC INPUTS Input High Voltage, VINH Input Low Voltage, VINL Input Current, IINH/IINL Input Capacitance, CIN TEMPERATURE SENSOR Output Voltage Temperature Coefficient POWER SUPPLIES Voltage Range Supply Current 1 Min Typ Max Unit 400 500 600 mV POUT ≈ −7 dBm, RF flatness of IQ modulator output calibrated out 0.5 dB 3 dB 350 750 920 1 MHz MHz Ω pF CLK, DATA, LE, ENOP, LOSEL 1.4 0 3.3 0.7 0.1 5 VPTAT voltage measured at MUXOUT TA = 25°C, RL ≥10 kΩ (LO buffer disabled) TA = −40°C to +85°C, RL ≥10 kΩ VCC1, VCC2, VCC3, VCC4, VCC5, VCC6, VCC7 1.579 3.8 4.75 Normal Tx mode (PLL and IQMOD enabled, LO buffer disabled) Tx mode using external LO input (internal VCO/PLL disabled) Tx mode with LO buffer enabled Power-down mode 5 226 135 276 22 V V μA pF V mV/°C 5.25 V mA mA mA mA The figure of merit (FOM) is computed as phase noise (dBc/Hz) – 10log10(fPFD) – 20log10(fLO/fPFD). The FOM was measured across the full LO range, with fREF = 80 MHz, fREF power = 10 dBm (500 V/μs slew rate) with a 40 MHz fPFD. The FOM was computed at 50 kHz offset. Rev. 0 | Page 5 of 36 ADRF6704 Data Sheet TIMING CHARACTERISTICS Table 3. Parameter t1 t2 t3 t4 t5 t6 t7 Limit 20 10 10 25 25 10 20 Unit ns min ns min ns min ns min ns min ns min ns min Test Conditions/Comments LE to CLK setup time DATA to CLK setup time DATA to CLK hold time CLK high duration CLK low duration CLK to LE setup time LE pulse width t4 t5 CLK t2 DATA DB23 (MSB) t3 DB22 DB2 (CONTROL BIT C3) DB1 (CONTROL BIT C2) DB0 (LSB) (CONTROL BIT C1) t7 t1 08571-002 t6 LE Figure 2. Timing Diagram Rev. 0 | Page 6 of 36 Data Sheet ADRF6704 ABSOLUTE MAXIMUM RATINGS Table 4. Parameter Supply Voltage (VCC1 to VCC7) Digital I/O, CLK, DATA, LE LOP, LON IP, IN, QP, QN REFIN θJA (Exposed Paddle Soldered Down)1 Maximum Junction Temperature Operating Temperature Range Storage Temperature Range 1 Rating 5.5 V −0.3 V to +3.6 V 18 dBm −0.5 V to +1.5 V −0.3 V to +3.6 V 35°C/W 150°C −40°C to +85°C −65°C to +150°C Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. ESD CAUTION Per JDEC standard JESD 51-2. Rev. 0 | Page 7 of 36 ADRF6704 Data Sheet 40 39 38 37 36 35 34 33 32 31 DECL3 VTUNE LOP LON LOSEL GND VCC7 IP IN GND PIN CONFIGURATION AND FUNCTION DESCRIPTIONS PIN 1 INDICATOR ADRF6704 TOP VIEW (Not to Scale) 30 29 28 27 26 25 24 23 22 21 GND VCC6 GND VCC5 RFOUT GND NC GND VCC4 GND NOTES 1. NC = NO CONNECT. DO NOT CONNECT TO THIS PIN. 2. THE EXPOSED PADDLE SHOULD BE SOLDERED TO A LOW IMPEDANCE GROUND PLANE. 08571-003 GND DATA CLK LE GND ENOP VCC3 QP QN GND 11 12 13 14 15 16 17 18 19 20 VCC1 1 DECL1 2 CP 3 GND 4 RSET 5 REFIN 6 GND 7 MUXOUT 8 DECL2 9 VCC2 10 Figure 3. Pin Configuration Table 5. Pin Function Descriptions Pin No. 1, 10, 17, 22, 27, 29, 34 2 3 4, 7, 11, 15, 20, 21, 23, 25, 28, 30, 31, 35 24 5 Mnemonic VCC1, VCC2, VCC3, VCC4, VCC5, VCC6, VCC7 DECL1 CP GND NC RSET Description Power Supply Pins. The power supply voltage range is 4.75 V to 5.25 V. Drive all of these pins from the same power supply voltage. Decouple each pin with 100 pF and 0.1 μF capacitors located close to the pin. Decoupling Node for Internal 3.3 V LDO. Decouple this pin with 100 pF and 0.1 μF capacitors located close to the pin. Charge Pump Output Pin. Connect VTUNE to this pin through the loop filter. Ground. Connect these pins to a low impedance ground plane. Do not connect to this pin. Charge Pump Current. The nominal charge pump current can be set to 250 μA, 500 μA, 750 μA, or 1000 μA using DB10 and DB11 of Register 4 and by setting DB18 to 0 (CP reference source). In this mode, no external RSET is required. If DB18 is set to 1, the four nominal charge pump currents (INOMINAL) can be externally tweaked according to the following equation: ⎛ 217.4 × I CP R SET = ⎜⎜ ⎝ I NOMINAL 6 REFIN 8 MUXOUT 9 DECL2 12 DATA 13 CLK ⎞ ⎟ − 37.8 Ω ⎟ ⎠ where ICP is the base charge pump current in microamps. For further details on the charge pump current, see the Register 4—PLL Charge Pump, PFD, and Reference Path Control section. Reference Input. The nominal input level is 1 V p-p. Input range is 11 MHz to 160 MHz. This pin has high input impedance and should be ac-coupled. If REFIN is being driven by laboratory test equipment, the pin should be externally terminated with a 50 Ω resistor (place the ac-coupling capacitor between the pin and the resistor). When driven from an 50 Ω RF signal generator, the recommended input level is 4 dBm. Multiplexer Output. This output allows a digital lock detect signal, a voltage proportional to absolute temperature (VPTAT), or a buffered, frequency-scaled reference signal to be accessed externally. The output is selected by programming DB21 to DB23 in Register 4. Decoupling Node for 2.5 V LDO. Connect 100 pF, 0.1 μF, and 10 μF capacitors between this pin and ground. Serial Data Input. The serial data input is loaded MSB first with the three LSBs being the control bits. Serial Clock Input. This serial clock input is used to clock in the serial data to the registers. The data is latched into the 24-bit shift register on the CLK rising edge. Maximum clock frequency is 20 MHz. Rev. 0 | Page 8 of 36 Data Sheet ADRF6704 Pin No. 14 Mnemonic LE 16 18, 19, 32, 33 ENOP QP, QN, IN, IP 26 RFOUT 36 LOSEL 37, 38 LON, LOP 39 VTUNE 40 DECL3 EP Description Latch Enable. When the LE input pin goes high, the data stored in the shift registers is loaded into one of the six registers, the relevant latch being selected by the first three control bits of the 24-bit word. Modulator Output Enable/Disable. See Table 6. Modulator Baseband Inputs. Differential in-phase and quadrature baseband inputs. These inputs should be dc-biased to 0.5 V. RF Output. Single-ended, 50 Ω internally biased RF output. RFOUT must be ac-coupled to its load. LO Select. This digital input pin determines whether the LOP and LON pins operate as inputs or outputs. This pin should not be left floating. LOP and LON become inputs if the LOSEL pin is set low and the LDRV bit of Register 5 is set low. External LO drive must be a 2× LO. In addition to setting LOSEL and LDRV low and providing an external 2× LO, the LXL bit of Register 5 (DB4) must be set to 1 to direct the external LO to the IQ modulator. LON and LOP become outputs when LOSEL is high or if the LDRV bit of Register 5 (DB3) is set to 1. A 1× LO or 2× LO output can be selected by setting the LDIV bit of Register 5 (DB5) to 1 or 0 respectively (see Table 7). Local Oscillator Input/Output. The internally generated 1× LO or 2× LO is available on these pins. When internal LO generation is disabled, an external 1× LO or 2× LO can be applied to these pins. VCO Control Voltage Input. This pin is driven by the output of the loop filter. Nominal input voltage range on this pin is 1.3 V to 2.5 V. Decoupling Node for VCO LDO. Connect a 100 pF capacitor and a 10 μF capacitor between this pin and ground. Exposed Paddle. The exposed paddle should be soldered to a low impedance ground plane. Table 6. Enabling RFOUT ENOP X1 0 1 1 Register 5 Bit DB6 0 X1 1 RFOUT Disabled Disabled Enabled X = don’t care. Table 7. LO Port Configuration 1, 2 LON/LOP Function LOSEL Register 5 Bit DB5(LDIV) Register 5 Bit DB4(LXL) Register 5 Bit DB3 (LDRV) Input (2× LO) Output (Disabled) Output (1× LO) Output (1× LO) Output (1× LO) Output (2× LO) Output (2× LO) Output (2× LO) 0 0 0 1 1 0 1 1 X X 0 0 0 1 1 1 1 0 0 0 0 0 0 0 0 0 1 0 1 1 0 1 1 2 X = don’t care. LOSEL should not be left floating. Rev. 0 | Page 9 of 36 ADRF6704 Data Sheet TYPICAL PERFORMANCE CHARACTERISTICS VS = 5 V; TA = 25°C; baseband I/Q amplitude = 1 V p-p differential sine waves in quadrature with a 500 mV dc bias; baseband I/Q frequency (fBB) = 1 MHz; fPFD = 38.4 MHz; fREF = 153.6 MHz at +4 dBm Re:50 Ω (1 V p-p); 130 kHz loop filter, unless otherwise noted. 10 10 –40°C +25°C +85°C 9 8 SSB OUTPUT POWER (dBm) 7 6 5 4 3 2 7 6 5 4 3 2 2550 2600 2650 2700 2750 2800 2850 0 2500 08571-004 0 2500 2900 LO FREQUENCY (MHz) 2550 2600 2650 2700 2750 2800 2850 2900 LO FREQUENCY (MHz) Figure 4. Single Sideband (SSB) Output Power (POUT) vs. LO Frequency (fLO) and Temperature; Multiple Devices Shown Figure 7. Single Sideband (SSB) Output Power (POUT) vs. LO Frequency (fLO) and Power Supply; Multiple Devices Shown 20 20 –40°C +25°C +85°C 19 17 16 15 14 13 12 11 10 9 18 17 16 15 14 13 12 11 10 9 2650 2700 2750 2800 2850 2900 LO FREQUENCY (MHz) 7 2500 20 0 10 –30 5 –40 0 –50 –5 –60 –10 –15 –70 SECOND-ORDER DISTORTION (dBc) –80 0.1 SSB OUTPUT POWER (dBm) 15 –20 1 –20 10 BASEBAND INPUT VOLTAGE (Vp-p Differential) Figure 6. SSB Output Power, Second- and Third-Order Distortion, Carrier Feedthrough, and Sideband Suppression vs. Baseband Differential Input Voltage (fOUT = 2500 MHz) 2650 2700 2750 2800 2850 2900 Figure 8. SSB Output 1dB Compression Point (OP1dB) vs. LO Frequency (fLO) and Power Supply –10 SSB OUTPUT POWER (dBm) SIDEBAND SUPRESSION (dBc) THIRD-ORDER DISTORTION (dBc) CARRIER FEEDTHROUGH (dBm) 20 15 –20 10 –30 5 –40 0 –50 –5 –60 –10 –15 –70 SECOND-ORDER DISTORTION (dBc) –80 0.1 08571-006 –10 SSB OUTPUT POWER (dBm) THIRD-ORDER DISTORTION (dBc) CARRIER FEEDTHROUGH (dBm) SIDEBAND SUPRESSION (dBc) 2600 LO FREQUENCY (MHz) Figure 5. SSB Output 1dB Compression Point (OP1dB) vs. LO Frequency (fLO) and Temperature; Multiple Devices Shown 0 2550 SSB OUTPUT POWER (dBm) 2600 SECOND-ORDER DISTORTION (dBc), THIRD-ORDER DISTORTION (dBc), CARRIER FEEDTHROUGH (dBm), SIDEBAND SUPPRESSION (dBc) 2550 08571-005 7 2500 08571-008 8 8 SECOND-ORDER DISTORTION (dBc), THIRD-ORDER DISTORTION (dBc), CARRIER FEEDTHROUGH (dBm), SIDEBAND SUPPRESSION (dBc) 4.75V 5.25V 5V 19 1dB OUTPUT COMPRESSION (dBm) 18 08571-007 1 1 –20 10 BASEBAND INPUT VOLTAGE (Vp-p Differential) Figure 9. SSB Output Power, Second- and Third-Order Distortion, Carrier Feedthrough, and Sideband Suppression vs. Baseband Differential Input Voltage (fOUT = 2900 MHz) Rev. 0 | Page 10 of 36 08571-009 SSB OUTPUT POWER (dBm) 8 1 1dB OUTPUT COMPRESSION (dBm) 4.75V 5.25V 5V 9 Data Sheet –10 –20 –30 –40 –50 –60 2650 2700 2750 2800 2850 2900 Figure 10. Carrier Feedthrough vs. LO Frequency (fLO) and Temperature; Multiple Devices Shown –50 –60 –70 2650 2700 2750 2800 2850 2900 Figure 11. Sideband Suppression vs. LO Frequency (fLO) and Temperature; Multiple Devices Shown 2800 2850 2900 –30 –40 –50 –60 –70 –90 2500 OIP3 30 25 20 15 2600 2650 2700 2750 2800 2850 2900 Figure 14. Sideband Suppression vs. LO Frequency (fLO) and Temperature After Nulling at 25°C; Multiple Devices Shown THIRD-ORDER DISTORTION (dBc), SECOND-ORDER DISTORTION (dBc) OIP2 2550 LO FREQUENCY (MHz) –40°C +25°C +85°C –30 –35 –40 THIRD-ORDER DISTORTION –45 –50 –55 SECOND-ORDER DISTORTION –60 –65 –70 –75 2550 2600 2650 2700 2750 2800 2850 2900 LO FREQUENCY (MHz) Figure 12. OIP3 and OIP2 vs. LO Frequency (fLO) and Temperature (POUT ≈ −2 dBm per Tone); Multiple Devices Shown –80 2500 08571-012 OUTPUT IP3 AND IP2 (dBm) 2750 –20 –25 65 60 10 2500 2700 –40°C +25°C +85°C –20 –40°C +25°C +85°C 75 70 40 35 2650 08571-014 2600 08571-011 2550 LO FREQUENCY (MHz) 50 45 2600 –80 –80 55 2550 Figure 13. Carrier Feedthrough vs. LO Frequency (fLO) and Temperature After Nulling at 25°C; Multiple Devices Shown –10 –40 85 80 –60 0 –30 90 –50 LO FREQUENCY (MHz) –40°C +25°C +85°C –20 –90 2500 –40 –80 2500 SIDEBAND SUPPRESSION (dBc) SIDEBAND SUPPRESSION (dBc) –10 –30 08571-013 2600 08571-010 2550 LO FREQUENCY (MHz) 0 –20 –70 –70 –80 2500 –40°C +25°C +85°C 2550 2600 2650 2700 2750 LO FREQUENCY (MHz) 2800 2850 2900 08571-015 CARRIER FEEDTHROUGH (dBm) –10 0 –40°C +25°C +85°C CARRIER FEEDTHROUGH (dBm) 0 ADRF6704 Figure 15. Second- and Third-Order Distortion vs. LO Frequency (fLO) and Temperature Rev. 0 | Page 11 of 36 0 –10 1.0 –40°C +25°C +85°C 0.9 INTEGRATED PHASE NOISE (dBc/Hz) –20 –30 –40 –50 –60 –70 2.5kHz LOOP FILTER –80 –90 –100 –110 –120 –130 130kHz LOOP FILTER 0.8 0.7 0.6 0.5 0.4 0.3 0.2 0.1 1 10 100 1000 10000 100000 OFFSET FREQUENCY (kHz) 0 2500 0 –10 PHASE NOISE (dBc/Hz) 2.5kHz LOOP FILTER –70 –80 –90 –100 –110 –120 130kHz LOOP FILTER 2900 OFFSET = 1kHz –100 OFFSET = 100kHz –110 –120 –40°C +25°C +85°C –130 1 10 100 1000 10000 100000 Figure 17. Phase Noise vs. Offset Frequency and Temperature, fLO = 2700 MHz 0 –10 –150 2500 –80 –90 PHASE NOISE (dBc/Hz) 2.5kHz LOOP FILTER –70 –80 –90 –100 –110 –120 2650 2700 2750 2800 2850 2900 Figure 20. Phase Noise vs. LO Frequency at 1 kHz, 100 kHz, and 5 MHz Offsets –40 –50 –60 2600 LO FREQUENCY (MHz) –40°C +25°C +85°C –20 –30 2550 08571-020 –140 –140 –150 OFFSET FREQUENCY (kHz) 130kHz LOOP FILTER –130 –40°C +25°C +85°C OFFSET = 10kHz –100 –110 –120 OFFSET = 1MHz –130 1 10 100 1000 10000 100000 OFFSET FREQUENCY (kHz) Figure 18. Phase Noise vs. Offset Frequency and Temperature, fLO = 2900 MHz –150 2500 2550 2600 2650 2700 2750 2800 2850 2900 LO FREQUENCY (MHz) Figure 21. Phase Noise vs. LO Frequency at 10 kHz and 1 MHz Offsets Rev. 0 | Page 12 of 36 08571-021 –140 –140 –150 08571-018 PHASE NOISE, LO FREQUENCY = 2900MHz (dBc/Hz) 2850 OFFSET = 5MHz –130 –160 2650 2700 2750 2800 LO FREQUENCY (MHz) –90 –40 –50 –60 2600 –80 –40°C +25°C +85°C –20 –30 2550 Figure 19. Integrated Phase Noise vs. LO Frequency 08571-017 PHASE NOISE, LO FREQUENCY = 2700MHz (dBc/Hz) Figure 16. Phase Noise vs. Offset Frequency and Temperature, fLO = 2500 MHz –160 –40°C +25°C +85°C 08571-019 –140 –150 –160 Data Sheet 08571-016 PHASE NOISE, LO FREQUENCY = 2500MHz (dBc/Hz) ADRF6704 Data Sheet –70 –70 –40°C +25°C +85°C 2× PFD FREQUENCY 4× PFD FREQUENCY –75 –80 –80 –85 –85 –90 –95 –100 –105 –110 –90 –95 –100 –105 2550 2600 2650 2700 2750 2800 2850 2900 –70 1× PFD FREQUENCY 3× PFD FREQUENCY –75 –80 –85 –85 SPUR LEVEL (dBc) –80 –105 0.5× PFD FREQUENCY 2700 2750 2800 1× PFD FREQUENCY 3× PFD FREQUENCY –75 –100 2650 2850 2900 Figure 25. PLL Reference Spurs vs. LO Frequency (2× PFD and 4× PFD) at LO Output –70 –95 2600 LO FREQUENCY (MHz) –40°C +25°C +85°C –90 2550 08571-025 –115 –120 2500 08571-022 –115 –120 2500 Figure 22. PLL Reference Spurs vs. LO Frequency (2× PFD and 4× PFD) at Modulator Output –110 –40°C +25°C +85°C –90 –95 –100 –105 0.5× PFD FREQUENCY –115 –120 2500 –120 2500 2550 2600 2650 2700 2750 2800 2850 2900 LO FREQUENCY (MHz) 08571-023 –115 Figure 23. PLL Reference Spurs vs. LO Frequency (0.5× PFD, 1× PFD, and 3× PFD) at Modulator Output 2.8 2600 2650 2700 2750 2800 2850 2900 LO FREQUENCY (MHz) Figure 26. PLL Reference Spurs vs. LO Frequency (0.5× PFD, 1× PFD, and 3× PFD) at LO Output 0 –40°C +25°C +85°C 2.6 2550 08571-026 –110 –20 PHASE NOISE (dBm/Hz) 2.4 2.2 2.0 1.8 1.6 1.4 LO = 2519.9MHz LO = 2702.7MHz LO = 2884.7MHz –40 –60 –80 –100 –120 –140 1.2 2550 2600 2650 2700 2750 2800 2850 LO FREQUENCY (MHz) Figure 24. VTUNE vs. LO Frequency and Temperature 2900 –160 1k 08571-024 1.0 2500 10k 100k FREQUENCY (Hz) 1M 10M 08571-027 SPUR LEVEL (dBc) –40°C +25°C +85°C –110 LO FREQUENCY (MHz) VTUNE (V) 2× PFD FREQUENCY 4× PFD FREQUENCY –75 SPUR LEVEL (dBc) SPUR LEVEL (dBc) ADRF6704 Figure 27. Open-Loop VCO Phase Noise at 2519.9 MHz, 2702.7 MHz, and 2884.7 MHz Rev. 0 | Page 13 of 36 CUMULATIVE PERCENTAGE (%) 80 70 60 50 40 30 20 0 –161 –160 –159 –158 –157 –156 –155 NOISE FLOOR (dBm/Hz) 08571-028 10 –35 –40 –45 –50 –55 –60 –65 –70 –75 –80 –85 –90 –95 –100 2500 1.9 15 1.8 10 1.7 5 1.6 VPTAT (V) 2.0 20 0 –15 1.2 –20 1.1 50 100 150 200 250 TIME (µs) 300 2600 2650 2700 2750 2800 2850 2900 1.4 1.3 0 2550 1.5 –10 –25 LO FEEDTHROUGH Figure 30. SSB Output Power and LO Feedthrough with RF Output Disabled 25 –5 SSB OUTPUT POWER LO FREQUENCY (MHz) 08571-029 FREQUENCY DEVIATION FROM 2700MHz (MHz) Figure 28. IQ Modulator Noise Floor Cumulative Distributions at 2500 MHz, 2700 MHz, and 2900 MHz –30 08571-030 2500MHz 2700MHz 2900MHz 90 Figure 29. Frequency Deviation from LO Frequency at LO = 2.71 GHz to 2.7 GHz vs. Lock Time 1.0 –40 –15 10 35 60 TEMPERATURE (°C) Figure 31. VPTAT Voltage vs. Temperature Rev. 0 | Page 14 of 36 85 08571-031 100 Data Sheet SSB OUTPUT POWER AND LO FEEDTHROUGH (dBm) ADRF6704 Data Sheet ADRF6704 0 –1 –2 RETURN LOSS (dB) –3 LO INPUT –4 –5 RF OUT –6 2500MHz –7 2900MHz –8 2600 2650 2700 2750 2800 2850 FREQUENCY (MHz) 2900 08571-034 2550 08571-032 –9 –10 2500 Figure 32. Input Return Loss of LO Input (LON, LOP Driven Through MABA-07159 1:1 Balun) and Output Return Loss of RFOUT vs. Frequency 300 SUPPLY CURRENT (mA) 280 Figure 34. Smith Chart Representation of RF Output –40°C +25°C +85°C 260 240 220 200 160 2500 2550 2600 2650 2700 2750 2800 2850 2900 LO FREQUENCY (MHz) 08571-033 180 Figure 33. Power Supply Current vs. Frequency and Temperature (PLL and IQMOD Enabled, LO Buffer Disabled) Rev. 0 | Page 15 of 36 ADRF6704 Data Sheet THEORY OF OPERATION The ADRF6704 integrates a high performance IQ modulator with a state of the art fractional-N PLL. The ADRF6704 also integrates a low noise VCO. The programmable SPI port allows the user to control the fractional-N PLL functions and the modulator optimization functions. This includes the capability to operate with an externally applied LO. The quadrature modulator core within the ADRF6704 is a part of the next generation of industry-leading modulators from Analog Devices, Inc. The baseband inputs are converted to currents and then mixed to RF using high performance NPN transistors. The mixer output currents are transformed to a single-ended RF output using an integrated RF transformer balun. The high performance active mixer core, coupled with the low-loss RF transformer balun results in an exceptional OIP3 and OP1dB, with a very low output noise floor for excellent dynamic range. The use of a passive transformer balun rather than an active output stage leads to an improvement in OIP3 with no sacrifice in noise floor. At 2700 MHz the ADRF6704 typically provides an output P1dB of 12.1 dBm, OIP3 of 27.2 dBm, and an output noise floor of −158.3 dBm/Hz. Typical image rejection under these conditions is −37.7 dBc with no additional I and Q gain compensation. PLL + VCO The fractional divide function of the PLL allows the frequency multiplication value from REFIN to the LOP/LON outputs to be a fractional value rather than restricted to an integer as in traditional PLLs. In operation, this multiplication value is INT + (FRAC/MOD) where INT is the integer value, FRAC is the fractional value, and MOD is the modulus value, all of which are programmable via the SPI port. In previous fractional-N PLL designs, the fractional multiplication was achieved by periodically changing the fractional value in a deterministic way. The downside of this was often spurious components close to the fundamental signal. In the ADRF6704, a sigma delta modulator is used to distribute the fractional value randomly, thus significantly reducing the spurious content due to the fractional function. BASIC CONNECTIONS FOR OPERATION Figure 35 shows the basic connections for operating the ADRF6704 as they are implemented on the device’s evaluation board. The seven power supply pins should be individually decoupled using 100 pF and 0.1 μF capacitors located as close as possible to the pins. A single 10 μF capacitor is also recommended. The three internal decoupling nodes (labeled DECL3, DECL2, and DECL1) should be individually decoupled with capacitors as shown in Figure 35. The four I and Q inputs should be driven with a bias level of 500 mV. These inputs are generally dc-coupled to the outputs of a dual DAC (see the DAC-to-IQ Modulator Interfacing and IQ Filtering sections for more information). A 1 V p-p (0.353 V rms) differential sine wave on the I and Q inputs results in a single sideband output power of +5.5 dBm (at 2700 MHz) at the RFOUT pin (this pin should be ac-coupled as shown in Figure 35). This corresponds to an IQ modulator voltage gain of +1.5 dB. The reference frequency for the PLL (typically 1 V p-p between 11 MHz and 160 MHz) should be applied to the REFIN pin, which should be ac-coupled. If the REFIN pin is being driven from a 50 Ω source (for example, a lab signal generator), the pin should be terminated with 50 Ω as shown in Figure 35 (an RF drive level of +4 dBm should be applied). Multiples or fractions of the REFIN signal can be brought back off-chip at the multiplexer output pin (MUXOUT). A lock-detect signal and an analog voltage proportional to the ambient temperature can also be brought out on this pin by setting the appropriate bits on (DB21-DB23) in Register 4 (see the Register Description section). EXTERNAL LO The internally generated local oscillator (LO) signal can be brought off-chip as either a 1× LO or a 2× LO (via pins LOP and LON) by asserting the LOSEL pin and making the appropriate internal register settings. The LO output must be disabled whenever the RF output of the IQ modulator is disabled. The LOP and LON pins can also be used to apply an external LO. This can be used to bypass the internal PLL/VCO. To turn off the PLL Register 6, Bits[20:17] must be zero. Rev. 0 | Page 16 of 36 Data Sheet ADRF6704 VCC VDD R47 10kΩ (0402) C7 0.1µF (0402) C27 0.1µF (0402) C25 0.1µF (0402) C23 0.1µF (0402) C20 0.1µF (0402) C19 0.1µF (0402) C9 0.1µF (0402) C8 100pF (0402) C26 100pF (0402) C24 100pF (0402) C22 100pF (0402) C21 100pF (0402) C18 100pF (0402) C10 100pF (0402) VDD VDD VDD VDD VDD VDD LE (USB) DATA (USB) CLK (USB) DECL2 R40 10kΩ (0402) C16 100pF (0402) C17 0.1µF (0402) C42 10µF (0603) DECL1 C12 100pF (0402) C11 0.1µF (0402) C41 OPEN (0603) LOSEL SPI INTERFACE LON 5 1 4 3 MABA-007159 C5 100pF (0402) C29 100pF (0402) REF_IN DIVIDER ÷2 C6 100pF LOP (0402) REFIN R73 49.9Ω (0402) SEE TEXT REFOUT OPEN FRACTION REG ADRF6704 THIRD-ORDER FRACTIONAL INTERPOLATOR ×2 ÷2 MODULUS MUX ÷4 TEMP SENSOR MUXOUT 2:1 MUX INTEGER REG QP N COUNTER 21 TO 123 PRESCALER ÷2 NC R2 R37 OPEN 0Ω (0402) (0402) GND CP TEST POINT (OPEN) R38 OPEN (0402) C14 22pF (0603) RSET IN IP CP VTUNE DECL3 R62 0Ω (0402) R10 3kΩ (0603) C15 2.7nF (1206) C13 6.8pF (0603) C2 OPEN (0402) C40 22pF (0603) R3 OPEN (0402) QP QN IN IP RFOUT OPEN VTUNE OPEN R9 10kΩ R65 10kΩ (0402) (0402) C3 100pF (0402) RFOUT R63 OPEN (0402) R12 0Ω (0402) R11 OPEN (0402) C43 10µF (0603) QN R23 OPEN (0402) ÷2 0/90 CHARGE PUMP 250µA, 500µA (DEFAULT), 750µA, 1000µA – PHASE + FREQUENCY DETECTOR R16 OPEN (0402) VCO CORE C1 100pF (0402) 08571-035 EXT LO LE S1 S2 DATA R39 10kΩ (0402) C28 10µF (3216) R20 0Ω (0402) CLK VCC R43 10kΩ (0402) ENOP VCC RED +5V NOTES 1. NC = NO CONNECT. DO NOT CONNECT TO THIS PIN. Figure 35. Basic Connections for Operation (Loop Filter Set to 130 kHz) LOOP FILTER Table 8. Recommended Loop Filter Components The loop filter is connected between the CP and VTUNE pins. The return for the loop filter components should be to Pin 40 (DECL3). The loop filter design in Figure 35 results in a 3 dB loop bandwidth of 130 kHz. The ADRF6704 closed loop phase noise was also characterized using a 2.5 kHz loop filter design. The recommended components for both filter designs are shown in Table 8. For assistance in designing loop filters with other characteristics, download the most recent revision of ADIsimPLL™ from www.analog.com/adisimpll. Component C14 R10 C15 R9 C13 R65 C40 R37 R11 R12 Rev. 0 | Page 17 of 36 130 kHz Loop Filter 22 pF 3 kΩ 2.7 nF 10 kΩ 6.8 pF 10 kΩ 22 pF 0Ω Open 0Ω 2.5 kHz Loop Filter 0.1 μF 68 Ω 4.7 μF 270 Ω 47 nF 0Ω Open 0Ω Open 0Ω ADRF6704 Data Sheet AD9122 The ADRF6704 is designed to interface with minimal components to members of the Analog Devices, Inc., family of TxDACs®. These dual-channel differential current output DACs provide an output current swing from 0 mA to 20 mA. The interface described in this section can be used with any DAC that has a similar output. An example of an interface using the AD9122 TxDAC is shown in Figure 36. The baseband inputs of the ADRF6704 require a dc bias of 500 mV. The average output current on each of the outputs of the AD9122 is 10 mA. Therefore, a single 50 Ω resistor to ground from each of the DAC outputs results in an average current of 10 mA flowing through each of the resistors, thus producing the desired 500 mV dc bias for the inputs to the ADRF6704. ADRF6704 OUT1_P IN RBIP 50Ω RBIN 50Ω IP OUT1_N OUT2_N 08571-036 OUT2_P QN RBQN 50Ω RBQP 50Ω QP Figure 36. Interface Between the AD9122 and ADRF6704 with 50 Ω Resistors to Ground to Establish the 500 mV DC Bias for the ADRF6704 Baseband Inputs The AD9122 output currents have a swing that ranges from 0 mA to 20 mA. With the 50 Ω resistors in place, the ac voltage swing going into the ADRF6704 baseband inputs ranges from 0 V to 1 V (with the DAC running at 0 dBFS). So the resulting drive signal from each differential pair is 2 V p-p differential with a 500 mV dc bias. OUT1_P IP RBIP 50Ω RSL1 (SEE TEXT) RBIN 50Ω IN OUT1_N OUT2_N OUT2_P QN RBQN 50Ω RBQP 50Ω RSL2 (SEE TEXT) QP Figure 37. AC Voltage Swing Reduction Through the Introduction of a Shunt Resistor Between the Differential Pair The value of this ac voltage swing limiting resistor (RSL as shown in Figure 37) is chosen based on the desired ac voltage swing and IQ modulator output power. Figure 38 shows the relationship between the swing-limiting resistor and the peak-to-peak ac swing that it produces when 50 Ω bias-setting resistors are used. A higher value of swing-limiting resistor will increase the output power of the ADRF6704 and signal-to-noise ratio (SNR) at the cost if higher intermodulation distortion. For most applications, the optimum value for this resistor will be between 100 Ω and 300 Ω. When setting the size of the swing-limiting resistor, the input impedance of the I and Q inputs should be taken into account. The I and Q inputs have a differential input resistance of 920 Ω. As a result, the effective value of the swing-limiting resistance is 920 Ω in parallel with the chosen swing-limiting resistor. For example, if a swing-limiting resistance of 200 Ω is desired (based on Figure 37), the value of RSL should be set such that 200 Ω = (920 × RSL)/(920 + RSL) resulting in a value for RSL of 255 Ω. 2.0 1.8 The voltage swing for a given DAC output current can be reduced by adding a third resistor to the interface. This resistor is placed in the shunt across each differential pair, as shown in Figure 37. It has the effect of reducing the ac swing without changing the dc bias already established by the 50 Ω resistors. DIFFERENTIAL SWING (V p-p) ADDING A SWING-LIMITING RESISTOR 1.6 1.4 1.2 1.0 0.8 0.6 0.4 0.2 0 10 100 1000 RSL (Ω) 10000 08571-038 AD9122 ADRF6704 08571-037 DAC-TO-IQ MODULATOR INTERFACING Figure 38. Relationship Between the AC Swing-Limiting Resistor and the Peak-to-Peak Voltage Swing with 50 Ω Bias-Setting Resistors Rev. 0 | Page 18 of 36 Data Sheet ADRF6704 BASEBAND BANDWIDTH Figure 39 shows the frequency response of the ADRF6704’s baseband inputs. This plot shows 0.5 dB and 3 dB bandwidths of 350 MHz and 750 MHz respectively. Any flatness variations across frequency at the ADRF6704 RF output have been calibrated out of this measurement. 2 0 RESISTANCE 700 0.6 600 0.4 500 0.2 400 0 100 200 300 400 CAPACITANCE (pF) 0.8 800 0 500 BASEBAND FREQUENCY (MHz) Figure 40. Differential Baseband Input R and Input C Equivalents (Shunt R and Shunt C) DEVICE PROGRAMMING AND REGISTER SEQUENCING The device is programmed via a 3-pin SPI port. The timing requirements for the SPI port are shown in Table 3 and Figure 2. Seven programmable registers, each with 24 bits, control the operation of the device. The register functions are listed in Table 9. The seven registers should initially be programmed in reverse order, starting with Register 6 and finishing with Register 0. Once all seven registers have been initially programmed, any of the registers can be updated without any attention to sequencing. Software is available on the ADRF6704 product page at www.analog.com that allows programming of the evaluation board from a PC running Windows® XP or Windows Vista. –2 –4 To operate correctly under Windows XP, Version 3.5 of Microsoft .NET must be installed. To run the software on a Windows 7 PC, XP emulation mode must be used (using Virtual PC). –6 –8 100 BB FREQUENCY (MHz) 1000 08571-039 BASEBAND FREQUENCY RESPONSE (dBc) 4 CAPACITANCE 08571-040 Unless a swing-limiting resistor of 100 Ω is chosen, the filter must be designed to support different source and load impedances. In addition, the differential input capacitance of the I and Q inputs (1 pF) should be factored into the filter design. Modern filter design tools allow for the simulation and design of filters with differing source and load impedances as well as inclusion of reactive load components. 1.0 900 RESISTANCE (Ω) An antialiasing filter must be placed between the DAC and modulator to filter out Nyquist images and broadband DAC noise. The interface for setting up the biasing and ac swing discussed in the Adding a Swing-Limiting Resistor section, lends itself well to the introduction of such a filter. The filter can be inserted between the dc bias setting resistors and the ac swing-limiting resistor. Doing so establishes the input and output impedances for the filter. –10 10 1.2 1000 IQ FILTERING Figure 39. Baseband Bandwidth Rev. 0 | Page 19 of 36 ADRF6704 Data Sheet REGISTER SUMMARY Table 9. Register Functions Register Register 0 Register 1 Register 2 Register 3 Register 4 Register 5 Register 6 Function Integer divide control (for the PLL) Modulus divide control (for the PLL) Fractional divide control (for the PLL) Σ-Δ modulator dither control PLL charge pump, PFD, and reference path control LO path and modulator control VCO control and VCO enable Rev. 0 | Page 20 of 36 Data Sheet ADRF6704 REGISTER DESCRIPTION Integer Divide Ratio REGISTER 0—INTEGER DIVIDE CONTROL (DEFAULT: 0x0001C0) The integer divide ratio bits are used to set the integer value in Equation 2. The INT, FRAC, and MOD values make it possible to generate output frequencies that are spaced by fractions of the PFD frequency. The VCO frequency (fVCO) equation is With Register 0, Bits[2:0] set to 000, the on-chip integer divide control register is programmed as shown in Figure 41. Divide Mode fVCO = 2 × fPFD × (INT + (FRAC/MOD)) Divide mode determines whether fractional mode or integer mode is used. In integer mode, the RF VCO output frequency (fVCO) is calculated by where: INT is the preset integer divide ratio value (24 to 119 in fractional mode). MOD is the preset fractional modulus (1 to 2047). FRAC is the preset fractional divider ratio value (0 to MOD − 1). (1) where: fVCO is the output frequency of the internal VCO. fPFD is the frequency of operation of the phase-frequency detector. INT is the integer divide ratio value (21 to 123 in integer mode). RESERVED DIVIDE MODE DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 DB7 DB6 DB5 DB4 DB3 DB2 DM ID6 ID5 ID4 ID3 ID2 ID1 ID0 C3(0) C2(0) C1(0) 0 0 0 0 0 0 0 0 0 0 0 INTEGER DIVIDE RATIO 0 0 DM DIVIDE MODE 0 FRACTIONAL (DEFAULT) 1 INTEGER CONTROL BITS DB1 ID6 ID5 ID4 ID3 ID2 ID1 ID0 INTEGER DIVIDE RATIO 0 0 1 0 1 0 1 21 (INTEGER MODE ONLY) 0 0 1 0 1 1 0 22 (INTEGER MODE ONLY) 0 0 1 0 1 1 1 23 (INTEGER MODE ONLY) 0 0 1 1 0 0 0 24 ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... 0 1 1 1 0 0 0 56 (DEFAULT) ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... 1 1 1 0 1 1 1 119 1 1 1 1 0 0 0 120 (INTEGER MODE ONLY) 1 1 1 1 0 0 1 121 (INTEGER MODE ONLY) 1 1 1 1 0 1 0 122 (INTEGER MODE ONLY) 1 1 1 1 0 1 1 123 (INTEGER MODE ONLY) Figure 41. Register 0—Integer Divide Control Register Map Rev. 0 | Page 21 of 36 DB0 08571-041 fVCO = 2 × fPFD × (INT) (2) ADRF6704 Data Sheet REGISTER 1—MODULUS DIVIDE CONTROL (DEFAULT: 0x003001) REGISTER 2—FRACTIONAL DIVIDE CONTROL (DEFAULT: 0x001802) With Register 1, Bits[2:0] set to 001, the on-chip modulus divide control register is programmed as shown in Figure 42. With Register 2, Bits[2:0] set to 010, the on-chip fractional divide control register is programmed as shown in Figure 43. Modulus Value Fractional Value The modulus value is the preset fractional modulus ranging from 1 to 2047. The FRAC value is the preset fractional modulus ranging from 0 to <MDR. RESERVED 0 0 0 0 0 0 0 0 0 DB13 DB12 DB11 DB10 DB9 DB8 DB7 DB6 DB5 DB4 DB3 DB2 MD10 MD9 MD6 MD5 MD4 MD3 MD2 MD1 MD0 C3(0) C2(0) C1(1) MD8 MD7 DB1 DB0 MD10 MD9 MD8 MD7 MD6 MD5 MD4 MD3 MD2 MD1 MD0 MODULUS VALUE 0 0 0 0 0 0 0 0 0 0 1 1 0 0 0 0 0 0 0 0 0 1 0 2 ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... 1 1 0 0 0 0 0 0 0 0 0 1536 (DEFAULT) ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... 1 1 1 1 1 1 1 1 1 1 1 2047 08571-042 0 CONTROL BITS MODULUS VALUE DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 Figure 42. Register 1—Modulus Divide Control Register Map 0 0 0 0 0 0 CONTROL BITS FRACTIONAL VALUE 0 0 DB12 DB11 DB10 DB9 DB8 DB7 DB6 DB5 DB4 DB3 FD10 FD9 FD8 FD6 FD5 FD4 FD3 FD2 FD1 FD0 FD10 FD9 FD8 FD7 FD6 FD5 FD4 FD3 FD2 FD1 FD0 FRACTIONAL VALUE 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 1 1 ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... 0 1 1 0 0 0 0 0 0 0 0 768 (DEFAULT) ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... ... 0 0 FD7 DB2 <MDR FRACTIONAL VALUE MUST BE LESS THAN MODULUS. Figure 43. Register 2—Fractional Divide Control Register Map Rev. 0 | Page 22 of 36 DB1 DB0 C3(0) C2(1) C1(0) 08571-043 RESERVED DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 Data Sheet ADRF6704 REGISTER 3—Σ-Δ MODULATOR DITHER CONTROL (DEFAULT: 0x10000B) enabled (1). The default value of the dither magnitude (15) should be set to a recommended value of 1. With Register 3, Bits[2:0] set to 011, the on-chip Σ-Δ modulator dither control register is programmed as shown in Figure 44. The recommended and default setting for dither enable is The dither restart value can be programmed from 0 to 217 − 1, though a value of 1 is typically recommended. DITHER DITHER RESTART VALUE CONTROL BITS ENABLE DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 DB7 DB6 DB5 DB4 DB3 DB2 DB1 DB0 DEN DV16 DV15 DV14 DV13 DV12 DV11 DV10 DV9 DV8 DV7 DV6 DV5 DV4 DV3 DV2 DV1 DV0 C3(0) C2(1) C1(1) DITH1 0 0 DITH0 0 1 DITHER MAGNITUDE 15 (DEFAULT) 7 1 0 3 1 1 1 (RECOMMENDED) DEN 0 1 DITHER ENABLE DISABLE ENABLE (DEFAULT, RECOMMENDED) DV16 DV15 DV14 DV13 DV12 DV11 DV10 DV9 DV8 DV7 DV6 DV5 DV4 DV3 DV2 DV1 DV0 DITHER RESTART VALUE 0 ... ... 1 0 ... ... 1 0 ... ... 1 0 ... ... 1 0 ... ... 1 0 ... ... 1 0 ... ... 1 0 ... ... 1 0 ... ... 1 0x00001 (DEFAULT) ... ... 0x1FFFF 0 ... ... 1 0 ... ... 1 0 ... ... 1 0 ... ... 1 0 ... ... 1 Figure 44. Register 3—Σ-Δ Modulator Dither Control Register Map Rev. 0 | Page 23 of 36 0 ... ... 1 0 ... ... 1 1 ... ... 1 08571-044 DB23 0 DITHER MAGNITUDE DB22 DB21 DITH1 DITH0 ADRF6704 Data Sheet fractional spurs. The magnitude of the phase offset is determined by the following equation: REGISTER 4—PLL CHARGE PUMP, PFD, AND REFERENCE PATH CONTROL (DEFAULT: 0x12A7E4) With Register 4, Bits[2:0] set to 100, the on-chip charge pump, PFD, and reference path control register is programmed as shown in Figure 45. CP Current The nominal charge pump current can be set to 250 μA, 500 μA, 750 μA, or 1000 μA using DB10 and DB11 of Register 4 and by setting DB18 to 0 (CP reference source). In this mode, no external RSET is required. If DB18 is set to 1, the four nominal charge pump currents (INOMINAL) can be externally tweaked according to the following equation: ⎛ 217.4 × I CP R SET = ⎜⎜ ⎝ I NOMINAL ⎞ ⎟ − 37.8 Ω ⎟ ⎠ (3) where ICP is the base charge pump current in microamps. The PFD phase offset multiplier (θPFD,OFS), which is set by Bits[16:12] of Register 4, causes the PLL to lock with a nominally fixed phase offset between the PFD reference signal and the divided-down VCO signal. This phase offset is used to linearize the PFD-to-CP transfer function and can improve ΔΦ (deg) = 22.5 θ PFD ,OFS I CP , MULT (4) The default value of the phase offset multiplier (10 × 22.5°) should be set to a recommended value of 6 × 22.5°. This phase offset can be either positive or negative depending on the value of DB17 in Register 4. The reference frequency applied to the PFD can be manipulated using the internal reference path source. The external reference frequency applied can be internally scaled in frequency by 2×, 1×, 0.5×, or 0.25×. This allows a broader range of reference frequency selections while keeping the reference frequency applied to the PFD within an acceptable range. The device also has a MUXOUT pin that can be programmed to output a selection of several internal signals. The default mode is to provide a lock-detect output to allow the user to verify when the PLL has locked to the target frequency. In addition, several other internal signals can be passed to the MUXOUT pin as described in Figure 35. Rev. 0 | Page 24 of 36 REF OUPUT MUX SELECT DB23 DB22 ADRF6704 CP INPUT REF CURRENT REF PATH SOURCE DB21 DB20 DB19 RMS2 RMS1 RMS0 RS1 RS0 PFD POL PFD PHASE OFFSET MULTIPLIER CP CURRENT CP SOURCE Data Sheet CP CONTROL PFD EDGE DB8 PFD ANTIBACKLASH DELAY DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB7 DB6 DB5 CPM CPBD CPB4 CPB3 CPB2 CPB1 CPB0 CPP1 CPP0 CPS CPC1 CPC0 PE1 PE0 DB4 DB3 CONTROL BITS DB2 DB1 DB0 PAB1 PAB0 C3(1) C2(0) C1(0) PAB1 PAB0 PFD ANTIBACKLASH DELAY 0 1 0 1 0 0 1 1 0ns (DEFAULT) 0.5ns 0.75ns 0.9ns PE0 REFERENCE PATH EDGE SENSITIVITY 0 1 FALLING EDGE (RECOMMENDED) RISING EDGE (DEFAULT) PE1 0 1 DIVIDER PATH EDGE SENSITIVITY FALLING EDGE (RECOMMENDED) RISING EDGE (DEFAULT) CPC1 CPC0 CHARGE PUMP CONTROL 0 0 1 1 0 1 0 1 BOTH ON PUMP DOWN PUMP UP TRISTATE (DEFAULT) CPS CHARGE PUMP CONTROL SOURCE 0 1 CONTROL BASED ON STATE OF DB7/DB8 (CP CONTROL) CONTROL FROM PFD (DEFAULT) CPP1 CPP0 CHARGE PUMP CURRENT 0 0 1 1 0 1 0 1 250µA 500µA (DEFAULT) 750µA 1000µA CPB4 CPB3 CPB2 CPB1 CPB0 PFD PHASE OFFSET MULTIPLIER 0 0 0 0 1 1 CPM 0 1 0 0 0 1 0 1 0 0 1 0 0 1 0 0 1 1 0 1 0 1 0 0 0 1 CPBD PFD PHASE OFFSET POLARITY 0 1 NEGATIVE POSITIVE (DEFAULT) 0 × 22.5°/ICP,MULT 1 × 22.5°/ICP,MULT 6 × 22.5°/ICP,MULT (RECOMMENDED) 10 × 22.5°/ICP,MULT (DEFAULT) 16 × 22.5°/ICP,MULT 31 × 22.5°/ICP,MULT CHARGE PUMP CURRENT REFERENCE SOURCE INTERNAL (DEFAULT) EXTERNAL RS1 INPUT REF RS0 PATH SOURCE 0 1 0 1 0 0 1 1 2× REFIN REFIN (DEFAULT) 0.5× REFIN 0.25× REFIN RMS2 RMS1 RMS0 REF OUTPUT MUX SELECT 0 0 1 1 0 0 1 1 0 1 0 1 0 1 0 1 LOCK DETECT (DEFAULT) VPTAT REFIN (BUFFERED) 0.5× REFIN (BUFFERED) 2× REFIN (BUFFERED) TRISTATE RESERVED RESERVED 08571-045 0 0 0 0 1 1 1 1 Figure 45. Register 4—PLL Charge Pump, PFD, and Reference Path Control Register Map Rev. 0 | Page 25 of 36 ADRF6704 Data Sheet Table 10. LO Port Configuration1, 2 REGISTER 5—LO PATH AND MODULATOR CONTROL (DEFAULT: 0X0000E5) LON/LOP Function Input (2× LO) Output (Disabled) Output (1× LO) Output (1× LO) Output (1× LO) Output (2× LO) Output (2× LO) Output (2× LO) With Register 5, Bits[2:0] set to 101, the LO path and modulator control register is programmed as shown in Figure 46. The modulator output or the complete modulator can be disabled using the modulator bias enable and modulator output enable addresses of Register 5. The LO port (LOP and LON pins) can be used to apply an external 2× LO (that is, bypass internal PLL) to the IQ modulator. A differential LO drive of 0 dBm is recommended. The LO port can also be used as an output where a 2× LO or 1× LO can be brought out and used to drive another mixer. The nominal output power provided at the LO port is 3 dBm. The mode of operation of the LO port is determined by the status of the LOSEL pin (3.3 V logic) along with the settings in a number of internal registers (see Table 10). 1 2 Register 5, Bit DB5 (LDIV) X X 0 0 0 1 1 1 LOSEL 0 0 0 1 1 0 1 1 Register 5, Bit DB4 (LXL) 1 0 0 0 0 0 0 0 Register 5, Bit DB3 (LDRV) 0 0 1 0 1 1 0 1 X = don’t care. LOSEL should not be left floating. LO OUTPUT MOD RF LO LO CONTROL BITS DRIVER BIAS OUTPUT OUTPUT IN/OUT RESERVED ENABLE ENABLE DIVIDER CONTROL ENABLE DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 DB7 DB6 DB5 DB4 DB3 DB2 DB1 DB0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 MBE RFEN LDIV LXL LDRV C3(1) C2(0) C1(1) LO OUTPUT DRIVER LDRV ENABLE 0 1 LXL LO INPUT/OUTPUT CONTROL 0 1 LO OUTPUT (DEFAULT) LO INPUT LDIV LO OUTPUT DIVIDE MODE 0 1 DIVIDE BY 1 DIVIDE BY 2 (DEFAULT) RFEN RF OUTPUT ENABLE 0 1 DISABLE ENABLE (DEFAULT) MBE MOD BIAS ENABLE 0 1 DISABLE ENABLE (DEFAULT) Figure 46. Register 5—LO Path and Modulator Control Register Map Rev. 0 | Page 26 of 36 DRIVER OFF (DEFAULT) DRIVER ON 08571-046 0 Data Sheet ADRF6704 The VCO amplitude can be controlled through Register 6. The VCO amplitude setting can be controlled between 0 and 63. The default value of 8 should be set to a recommended value of 63. REGISTER 6—VCO CONTROL AND VCO ENABLE (DEFAULT: 0X1E2106) With Register 6, Bits[2:0] set to 110, the VCO control and enable register is programmed as shown in Figure 47. The internal VCOs can be disabled using Register 6. The internal charge pump can be disabled through Register 6. By default, the charge pump is enabled. The VCO tuning band is normally selected automatically by the band calibration algorithm, although the user can directly select the VCO band using Register 6. To turn off the PLL (for example, if the ADRF6704 is being driven by an external LO), set Register 6, Bits[20:17] to zero. The VCO BS SRC bit (DB9) determines whether the result of the calibration algorithm is used to select the VCO band or if the band selected is based on the value in VCO band select (DB8 to DB3). CHARGE 3.3V VCO LDO VCO VCO LDO PUMP ENABLE ENABLE ENABLE ENABLE SWITCH DB23 DB22 DB21 0 0 0 DB20 CPEN DB19 L3EN DB18 LVEN DISABLE ENABLE (DEFAULT) L3EN 3.3V LDO ENABLE 0 1 DISABLE ENABLE (DEFAULT) LVEN VCO LDO ENABLE 0 1 DISABLE ENABLE (DEFAULT) VCO BW SW CTRL VCO BAND SELECT FROM SPI CONTROL BITS DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 DB7 DB6 DB5 DB4 DB3 DB2 DB1 DB0 VCO EN VCO SW VC5 VC4 VC3 VC2 VC1 VC0 VBSRC VBS5 VBS4 VBS3 VBS2 VBS1 VBS0 C3(1) C2(1) C1(0) CPEN CHARGE PUMP ENABLE 0 1 VCO AMPLITUDE VC[5:0] VCO AMPLITUDE VBS[5:0] VCO BAND SELECT FROM SPI 0x00 …. 0x08 …. 0x2B …. 0x3F 0x00 0x01 …. 0x3F DEFAULT 0x20 0 …. 8 (DEFAULT) …. 43 …. 63 (RECOMMENDED) VCO SW VCO SWITCH CONTROL FROM SPI 0 1 REGULAR (DEFAULT) BAND CAL VCO EN VCO ENABLE 0 1 DISABLE ENABLE (DEFAULT) VBSRC VCO BW CAL AND SW SOURCE CONTROL 0 1 BAND CAL (DEFAULT) SPI Figure 47. Register 6—VCO Control and VCO Enable Register Map Rev. 0 | Page 27 of 36 08571-047 RESERVED ADRF6704 Data Sheet CHARACTERIZATION SETUPS Figure 48 and Figure 49 show characterization bench setups used to characterize the ADRF6704. The setup shown in Figure 48 was used to do most of the testing. An automated VEE program was used to control equipment over the IEEE bus. The setup was used to measure SSB, OIP2, OIP3, OP1dB, LO, and USB NULL. For phase noise and reference spurs measurements, see the phase noise setup on Figure 49. Phase noise was measured on LO and modulator output. ADRF670x TEST RACK ASSEMBLY (INTERNAL VCO CONFIGURATION) ALL INSTRUMENTS ARE CONNECTED IN DAISY CHAIN FASHION VIA GBIP CABLE UNLESS OTHERWISE NOTED. E3631A POWER SUPPLY (+6V ADJUSTED TO 5V) +5V FOR VPOS TO 34950 MODULE 34401A DMM (FOR SUPPLY CURRENT MEASUREMENT) 34980A WITH 34950 AND (×2) 34921 MODULES PROGRAMMING AND DC CABLE (×6 FOR MULTISITE) INPUT (RFOUT) AGILENT E4440A PSA SPECTRUM ANALYZER 10-PIN CONNECTOR DC HEADER 9-PIN DSUB CONNECTOR (REGISTER PROGRAMMING) REF IN 6dB KEITHLEY S46 SWITCH SYSTEM #1 (FOR RFOUT AND REFIN ON 6 SITES) OUTPUT (REF) RF OUT KEITHLEY S46 SWITCH SYSTEM #2 (FOR BASEBAND INPUTS ON 6 SITES) ADRF6704 EVAL BOARD 6dB ROHDE AND SCHWARTZ SMT 06 SIGNAL GENERATOR (REFIN) BASEBAND INPUTS AT 1MHz PC CONTROL CONNECTED TO SYSTEM VIA USB TO GPIB ADAPTER Figure 48. General Characterization Setup Rev. 0 | Page 28 of 36 08571-049 BASEBAND OUTPUTS (IN, IP, QN, QP) AEROFLEX IFR 3416 FREQUENCY GENERATOR (WITH BASEBAND OUTPUTS AT 1MHz) Data Sheet ADRF6704 ADRF670x PHASE NOISE STAND SETUP ALL INSTRUMENTS ARE CONNECTED IN DAISY CHAIN FASHION VIA GBIP CABLE UNLESS OTHERWISE NOTED. ROHDE AND SCHWARTZ SMA 100 SIGNAL GENERATOR REFIN AGILENT E5052 SIGNAL SOURCE ANALYZER AGILENT E4440A SPECTRUM ANALYZER IF OUT KEITHLEY S46 SWITCH SYSTEM 2 (FOR IF OUT AND REFIN ON 6 SITES) REFIN LO OUT BASEBAND INPUTS (IP, IN, QP, QN) IFR 3416 SIGNAL GENERATOR (BASEBAND SOURCE) KEITHLEY S46 SWITCH SYSTEM 1 (FOR BASEBAND INPUTS ON 6 SITES) 10 PIN CONNECTOR (DC MEASUREMENT, +5V POS) AND 9 PIN DSUB CONNECTOR (VCO AND PLL PROGRAMMING) ADRF6704 EVAL BOARD 34980A MULTIFUNCTION SWITCH (WITH 34950 AND 34921 MODULES) INPUT DC AGILENT 34401A DMM (IN DC I MODE, SUPPLY CURRENT MEASUREMENT) PC CONTROL CONNECTED TO SYSTEM VIA USB TO GPIB ADAPTER Figure 49. Characterization Setup for Phase Noise and Reference Spur Measurements Rev. 0 | Page 29 of 36 08571-050 AGILENT E3631A POWER SUPPLY ADRF6704 Data Sheet EVALUATION BOARD Figure 51 shows the schematic of the device’s RoHS-compliant evaluation board. This board was designed using Rogers 4350 material to minimize losses at high frequencies. FR4 material would also be adequate but with the slightly higher trace loss of this material. Windows 7 PC, XP emulation mode must be used (using Virtual PC). Whereas the on-board USB interface circuitry of the evaluation board is powered directly from the PC, the main section of the evaluation board requires a separate 5 V power supply. The serial port of the ADRF6704 can be programmed from a PC’s USB port (a USB cable is provided with the evaluation board). The on-board USB interface circuitry can if desired be bypassed by removing the 0 Ω resistors, R15, R17, and R18 (see Figure 51) and driving the ADRF6704 serial interface through the P3 4-pin header (P3 must be first installed, Samtec TSW104-08-G-S). EVALUATION BOARD CONTROL SOFTWARE USB-based programming software is available to download from the ADRF6704 product page at www.analog.com (Evaluation Board Software Rev 6.1.0). To install the software, download and extract the zip file. Then run the following installation file: ADRF6X0X_6p1p0_customer_installer.exe. To operate correctly under Windows XP, Version 3.5 of Microsoft .NET must be installed. To run the software on a 08571-051 The evaluation board is designed to operate using the internal VCO (default configuration) of the device. Additional configuration options for the evaluation board are described in Table 11. Figure 50. Control Software Opening Menu Figure 50 shows the opening window of the software where the user selects the device being programmed. Figure 54 shows a screen shot of the control software’s main controls with the default settings displayed. The text box in the bottom left corner provides an immediate indication of whether the software is successfully communicating with the evaluation board. If the evaluation board is connected to the PC via the USB cable provided and the software is successfully communicating with the on-board USB circuitry, this text box shows the following message: ADRF6X0X eval board connected. Rev. 0 | Page 30 of 36 Data Sheet ADRF6704 VCC VDD C7 0.1µF (0402) C27 0.1µF (0402) C25 0.1µF (0402) C23 0.1µF (0402) C20 0.1µF (0402) C19 0.1µF (0402) C9 0.1µF (0402) C8 100pF (0402) C26 100pF (0402) C24 100pF (0402) C22 100pF (0402) C21 100pF (0402) C18 100pF (0402) C10 100pF (0402) VDD VDD VDD VDD VDD VDD LE (USB) DATA (USB) CLK (USB) DECL2 R40 10kΩ (0402) C16 100pF (0402) C17 0.1µF (0402) C42 10µF (0603) DECL1 C12 100pF (0402) C11 0.1µF (0402) C41 OPEN (0603) LOSEL SPI INTERFACE LON 5 1 4 3 MABA-007159 C5 100pF (0402) C29 100pF (0402) REF_IN DIVIDER ÷2 C6 100pF LOP (0402) REFIN R73 49.9Ω (0402) SEE TEXT REFOUT OPEN FRACTION REG ADRF6704 THIRD-ORDER FRACTIONAL INTERPOLATOR ×2 ÷2 MODULUS MUX ÷4 TEMP SENSOR MUXOUT 2:1 MUX INTEGER REG QP N COUNTER 21 TO 123 PRESCALER ÷2 NC R2 R37 OPEN 0Ω (0402) (0402) GND CP TEST POINT (OPEN) R38 OPEN (0402) C14 22pF (0603) RSET IN IP CP VTUNE DECL3 R62 0Ω (0402) R10 3kΩ (0603) C15 2.7nF (1206) C13 6.8pF (0603) C2 OPEN (0402) C40 22pF (0603) R3 OPEN (0402) QP QN IN IP RFOUT OPEN VTUNE OPEN R9 10kΩ R65 10kΩ (0402) (0402) C3 100pF (0402) RFOUT R63 OPEN (0402) R12 0Ω (0402) R11 OPEN (0402) C43 10µF (0603) QN R23 OPEN (0402) ÷2 0/90 CHARGE PUMP 250µA, 500µA (DEFAULT), 750µA, 1000µA – PHASE + FREQUENCY DETECTOR R16 OPEN (0402) VCO CORE C1 100pF (0402) 08571-052 EXT LO LE S1 R47 10kΩ (0402) DATA R39 10kΩ (0402) S2 C28 10µF (3216) R20 0Ω (0402) CLK VCC R43 10kΩ (0402) ENOP VCC RED +5V NOTES 1. NC = NO CONNECT. DO NOT CONNECT TO THIS PIN. 08571-053 08571-054 Figure 51. Evaluation Board Schematic (Loop Filter Set to 130 kHz) Figure 53. Evaluation Board Bottom Layer Figure 52. Evaluation Board Top Layer Rev. 0 | Page 31 of 36 ADRF6704 Data Sheet Table 11. Evaluation Board Configuration Options Component S1, R39, R40 EXT LO, T3 REFIN SMA Connector, R73 REFOUT SMA Connector, R16 CP Test Point, R38 C13, C14, C15, C40R9, R10, R37, R65 R11, R12, R62, R63, VTUNE SMA Connector R2 R23, R3 P3 4-Pin Header, R15, R17, R18 Description LO select. Switch and resistors to ground LOSEL pin. The LOSEL pin setting in combination with internal register settings, determines whether the LOP/LON pins function as inputs or outputs. With the LOSEL pin grounded, register settings can set the LOP/LON pins to be inputs or outputs. LO input/output. An external 1× LO or 2× LO can be applied to this single-ended input connector. Alternatively, the internal 1× or 2× LO can be brought out on this pin. The differential LO signal on LOP and LON is converted to a single-ended signal using a broadband 1:1 balun (Macom MABA-007159, 4.5 MHz to 3000 MHz frequency range). The balun footprint on the evaluation board is also designed to accommodate Johanson baluns: 3600BL14M050 (1:1, 3.3 GHz to 3.9 GHz) and 3700BL15B050E (1:1, 3.4 GHz to 4 GHz). Reference input. The input reference frequency for the PLL is applied to this connector. Input resistance is set by R73 (49.9 Ω). Multiplexer output. The REFOUT connector connects directly to the device’s MUXOUT pin. The on-board multiplexer can be programmed to bring out the following signals: REFIN, 2× REFIN, REFIN/2, REFIN/4, Temperature sensor output voltage (VPTAT), Lock detect indicator. Charge pump test point. The unfiltered charge pump signal can be probed at this test point. Note that this pin should not be probed during critical measurements such as phase noise. Loop filter. Loop filter components. When the internal VCO is enabled, the loop filter components connect directly to the VTUNE pin (Pin 39) by installing a 0 Ω resistor in R62. In addition, the loop filter components should be returned to Pin 40 (DECL3) by installing a 0 Ω resistor in R12. RSET. This pin is unused and should be left open. Baseband input termination. Termination resistors for the baseband filter of the DAC can be placed on R23 and R3. In addition to terminating the baseband filters, these resistors also scale down the baseband voltage from the DAC without changing the bias level. These resistors are generally set in the 100 Ω to 300 Ω range. USB circuitry bypass. The USB circuitry can be bypassed, allowing for the serial port of the ADRF6704 to be driven directly. P3 (Samtec TSW-104-08-G-S) must be installed, and 0 Ω resistors (R15, R17 and R18) must be removed. Rev. 0 | Page 32 of 36 Default Condition/Option Settings T3 = Macom MABA-007159 EXT LO SMA connector = installed FREFIN = 153.6 MHz R73 = 49.9 Ω REFOUT SMA connector = open R16 = open CP = open R38 = open See Table 8 R12 = 0 Ω (0402) R11 = open (0402) R62 = 0 Ω (0402) R63 = open (0402) VTUNE = open R2 = open (0402) R3 = R23 = open (0402) P3 = open R15, R17, R18 = 0 Ω (0402) ADRF6704 08571-055 Data Sheet Figure 54. Main Controls of the Evaluation Board Control Software Rev. 0 | Page 33 of 36 Data Sheet 08571-056 ADRF6704 Figure 55. USB Interface Circuitry on the Customer Evaluation Board Rev. 0 | Page 34 of 36 Data Sheet ADRF6704 OUTLINE DIMENSIONS 6.00 BSC SQ 0.60 MAX 0.60 MAX TOP VIEW 0.50 BSC 5.75 BSC SQ 0.50 0.40 0.30 12° MAX 0.80 MAX 0.65 TYP 0.30 0.23 0.18 4.25 4.10 SQ 3.95 EXPOSED PAD (BOT TOM VIEW) 21 20 11 10 0.25 MIN 4.50 REF 0.05 MAX 0.02 NOM SEATING PLANE 40 1 0.20 REF COPLANARITY 0.08 FOR PROPER CONNECTION OF THE EXPOSED PAD, REFER TO THE PIN CONFIGURATION AND FUNCTION DESCRIPTIONS SECTION OF THIS DATA SHEET. COMPLIANT TO JEDEC STANDARDS MO-220-VJJD-2 072108-A PIN 1 INDICATOR 1.00 0.85 0.80 PIN 1 INDICATOR 31 30 Figure 56. 40-Lead Lead Frame Chip Scale Package [LFCSP_VQ] 6 mm × 6 mm Body, Very Thin Quad (CP-40-1) Dimensions shown in millimeters ORDERING GUIDE Model 1 ADRF6704ACPZ-R7 ADRF6704-EVALZ 1 Temperature Range (°C) −40°C to +85°C Package Description 40-Lead Lead Frame Chip Scale Package [LFCSP_VQ] Evaluation Board Z = RoHS Compliant Part. Rev. 0 | Page 35 of 36 Package Option CP-40-1 ADRF6704 Data Sheet NOTES ©2011 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D08571-0-10/11(0) Rev. 0 | Page 36 of 36