U211B2/ B3 Phase Control Circuit - General Purpose Feedback Description The integrated circuit U211B2/ B3 is designed as a phase control circuit in bipolar technology with an internal frequency-voltage converter. Furthermore, it has an internal control amplifier which means it can be used for speedregulated motor applications. It has an integrated load limitation, tacho monitoring and soft-start functions, etc. to realize sophisticated motor control systems. Features D D D D D D D D D D D Internal frequency-to-voltage converter Externally-controlled integrated amplifier Overload limitation with a “fold back” characteristic Optimized soft-start function Tacho monitoring for shorted and open loop Triggering pulse typ. 155 mA Voltage and current synchronization Internal supply-voltage monitoring Temperature reference source Current requirement ≤ 3 mA Package: Automatic retriggering switchable 17(16) 1(1) DIP18 - U211B2, SO16 - U211B3 5*) Automatic retriggering Voltage / Current detector Output pulse Control amplifier 11(10) + 4(4) 6(5) 7(6) 10(9) – Phase control unit ö = f (V12) 3(3) Supply voltage limitation Reference voltage 14(13) 15(14) Load limitation speed / time controlled 2(2) –V S GND 16(15) Voltage monitoring controlled current sink Soft start Pulse-blocking tacho monitoring Frequencyto-voltage converter 18*) –VRef 12(11) 13(12) 9(8) 8(7) 95 10360 Figure 1. Block diagram (Pins in brackets refer to SO16) *) Pins 5 and 18 connected internally TELEFUNKEN Semiconductors Rev. A1, 29-May-96 1 (20) 2 (20) R19 100 k W R14 56 k W Actual speed voltage 4.7m F /16V C9 1 MW R 9 R 10 1 kW 2.2 m F /16V C 10 Set speed voltage R 31 100 kW 47 k W R13 C6 100 nF 15 14 10 11 Control amplifier 22 k W R7 C8 C3 220 nF 2.2 m F 16 V C5 1 nF 8 R5 1 kW C4 R6 100 kW 10 m F /16V C7 9 C2 16 Speed sensor 95 10361 GND C 11 C1 1 MW 3.3 nF R2 R 12 180 W 2 –V S 3 7 6 4 Pulse blocking tacho 18 monitoring 2 MW 13 Frequency to voltage converter Voltage monitoring Reference voltage Supply voltage limitation Output pulse 220 nF 12 –V Ref Soft start Phase control unit ö = f (V12 ) Automatic retriggering 5 R11 controlled current sink Load limitation speed / time controlled – + 1 R4 470 k W Voltage / Current detector 17 R3 220 k W 18 kW 2W 1N4007 M 2.2 m F 22 m F 25 V R8 33 m W 1W TIC 226 R1 D1 N VM = 230 V ~ L U211B2/ B3 Figure 2. Speed control, automatic retriggering, load limiting, soft start TELEFUNKEN Semiconductors Rev. A1, 29-May-96 U211B2/ B3 Description Mains Supply The U211B2 is fitted with voltage limiting and can therefore be supplied directly from the mains. The supply voltage between Pin 2 (+ pol/ ) and Pin 3 builds up across D1 and R1 and is smoothed by C1. The value of the series resistance can be approximated using (see figure 2): ă R1 + V 2 –I V M When the potential on Pin 7 reaches the nominal value predetermined at Pin 12, then a trigger pulse is generated whose width tp is determined by the value of C2 (the value of C2 and hence the pulse width can be evaluated by assuming 8 ms/nF). At the same time, a latch is set, so that as long as the automatic retriggering has not been activated, then no more pulses can be generated in that half cycle. S S Further information regarding the design of the mains supply can be found in the data sheets in the appendix. The reference voltage source on Pin 16 of typ. –8.9 V is derived from the supply voltage and is used for regulation. Operation using an externally stabilised DC voltage is not recommended. If the supply cannot be taken directly from the mains because the power dissipation in R1 would be too large, then the circuit shown in the following figure 3 should be used. The current sensor on Pin 1 ensures that, for operations with inductive loads, no pulse will be generated in a new half-cycle as long as a current from the previous half cycle is still flowing in the opposite direction to the supply voltage at that instant. This makes sure that “gaps” in the load current are prevented. The control signal on Pin 12 can be in the range 0 V to –7 V (reference point Pin 2). If V12 = –7 V then the phase angle is at maximum = amax i.e., the current flow angle is a minimum. The phase angle amin is minimum when V12 = V2. ~ Voltage Monitoring 24 V~ 1 R1 2 3 4 5 C1 95 10362 As the voltage is built up, uncontrolled output pulses are avoided by internal voltage surveillance. At the same time, all of the latches in the circuit (phase control, load limit regulation, soft start) are reset and the soft-start capacitor is short circuited. Used with a switching hysteresis of 300 mV, this system guarantees defined start-up behavior each time the supply voltage is switched on or after short interruptions of the mains supply. Figure 3. Supply voltage for high current requirements Phase Control There is a general explanation in the data sheet, TEA1007, on the common phase control function. The phase angle of the trigger pulse is derived by comparing the ramp voltage (which is mains synchronized by the voltage detector) with the set value on the control input Pin 12. The slope of the ramp is determined by C2 and its charging current. The charging current can be varied using R2 on Pin 6. The maximum phase angle amax can also be adjusted using R2. TELEFUNKEN Semiconductors Rev. A1, 29-May-96 Soft-Start As soon as the supply voltage builds up (t1), the integrated soft-start is initiated. The figure below shows the behaviour of the voltage across the soft-start capacitor and is identical with the voltage on the phase control input on Pin 12. This behaviour guarantees a gentle start-up for the motor and automatically ensures the optimum run-up time. 3 (20) U211B2/ B3 95 10272 VC3 V12 The converter is based on the charge pumping principle. With each negative half wave of the input signal, a quantity of charge determined by C5 is internally amplified and then integrated by C6 at the converter output on Pin 10. The conversion constant is determined by C5, its charge transfer voltage of Vch, R6 (Pin 10) and the internally adjusted charge transfer gain. Gi V0 ƪ ƫ+ I 10 I9 k = Gi t t1 t3 t2 ttot Figure 4. Soft-start t1 t2 t1 + t2 t3 ttot = build-up of supply voltage = charging of C3 to starting voltage = dead time = run-up time = total start-up time to required speed C3 is first charged up to the starting voltage V0 with typical 45 mA current (t2). By then reducing the charging current to approx. 4 mA, the slope of the charging function is substantially reduced so that the rotational speed of the motor only slowly increases. The charging current then increases as the voltage across C3 increases giving a progressively rising charging function which accelerates the motor more and more strongly with increasing rotational speed. The charging function determines the acceleration up to the set-point. The charging current can have a maximum value of 55 mA. Frequency to Voltage Converter The internal frequency to voltage converter (f/Vconverter) generates a DC signal on Pin 10 which is proportional to the rotational speed using an AC signal from a tacho-generator or a light beam whose frequency is in turn dependent on the rotational speed. The high impedance input Pin 8, compares the tacho-voltage to a switch-on threshold of typ. –100 mV. The switch-off threshold is given with –50 mV. The hysteresis guarantees very reliable operation even when relatively simple tacho-generators are used. The tacho-frequency is given by: f where: 4 (20) + 60n p (Hz) n = revolutions per minute p = number of pulses per revolution 8.3 C5 R6 Vch The analog output voltage is given by VO = k @f The values of C5 and C6 must be such that for the highest possible input frequency, the maximum output voltage VO does not exceed 6 V. While C5 is charging up, the Ri on Pin 9 is .approx. 6.7 kW. To obtain good linearity of the f/V converter the time constant resulting from Ri and C5 should be considerably less (1/5) than the time span of the negative half-cycle for the highest possible input frequency. The amount of remaining ripple on the output voltage on Pin 10 is dependent on C5, C6 and the internal charge amplification. ∆VO = Gi Vch C5 C6 The ripple ∆Vo can be reduced by using larger values of C6. However, the increasing speed will then also be reduced. The value of this capacitor should be chosen to fit the particular control loop where it is going to be used. Pulse Blocking The output of pulses can be blocked using Pin 18 (standby operation) and the system reset via the voltage monitor if V18 ≥ –1.25 V. After cycling through the switching point hysteresis, the output is released when V18 ≤ –1.5 V followed by a soft-start such as that after turn on. Monitoring of the rotation can be carried out by connecting an RC network to Pin 18. In the event of a short or open circuit, the triac triggering pulses are cut off by the time delay which is determined by R and C. The capacitor C is discharged via an internal resistance Ri = 2 kW with each charge transfer process of the f/V converter. If there are no more charge transfer processes C is charged up via R until the switch-off threshold is exceeded and the triac triggering pulses are cut off. For operation without trigger pulse blocking or monitoring of the rotation, Pins 18 and 16 must be connected together. TELEFUNKEN Semiconductors Rev. A1, 29-May-96 U211B2/ B3 (reference voltage Pin 16) then a latch is set and the load limiting is turned on. A current source (sink) controlled by the control voltage on Pin 15 now draws current from Pin 12 and lowers the control voltage on Pin 12 so that the phase angle is increased to max. C = 1 F 10 V 18 17 16 15 R = 1 M 1 2 3 4 95 10363 Figure 5. Operation delay Control Amplifier (Figure 2) The integrated control amplifier with differential input compares the set value (Pin 11) with the instantaneous value on Pin 10 and generates a regulating voltage on the output Pin 12 (together with the external circuitry on Pin 12) which always tries to hold the actual voltage at the value of the set voltages. The amplifier has a transmittance of typically 1000 A/V and a bipolar current source output on Pin 12 which operates with typically ±110 A. The amplification and frequency response are determined by R7, C7, C8 and R11 (can be left out). For open loop operation, C4, C5, R6, R7, C7, C8 and R11 can be omitted. Pin 10 should be connected with Pin 12 and Pin 8 with Pin 2. The phase angle of the triggering pulse can be adjusted using the voltage on Pin 11. An internal limitation circuit prevents the voltage on Pin 12 from becoming more negative than V16 + 1 V. Load Limitation The load limitation, with standard circuitry, provides absolute protection against overloading of the motor. the function of the load limiting takes account of the fact that motors operating at higher speeds can safely withstand large power dissipations than at lower speeds due to the increased action of the cooling fan. Similary, considerations have been made for short term overloads for the motor which are, in practice, often required. These finctions are not damaging and can be tolerated. In each positive half-cycle, the circuit measures via R10 the load current on Pin 14 as a potential drop across R8 and produces a current proportional to the voltage on Pin 14. This current is available on Pin 15 and is integrated by C9. If, following high current amplitudes or a large phase angle for current flow, the voltage on C9 exceeds an internally set threshold of approx. 7.3 V TELEFUNKEN Semiconductors Rev. A1, 29-May-96 The simultaneous reduction of the phase angle during which current flows causes firstly: a reduction of the rotational speed of the motor which can even drop to zero if the angular momentum of the motor is excessively large, and secondly: a reduction of the potential on C9 which in turn reduces the influence of the current sink on Pin 12. The control voltage can then increase again and bring down the phase angle. This cycle of action sets up a “balanced condition” between the “current integral” on Pin 15 and the control voltage on Pin 12. Apart from the amplitude of the load current and the time during which current flows, the potential on Pin 12 and hence the rotational speed also affects the function of the load limiting. A current proportional to the potential on Pin 10 gives rise to a voltage drop across R10, via Pin 14, so that the current measured on Pin 14 is smaller than the actual current through R8. This means that higher rotational speeds and higher current amplitudes lead to the same current integral. Therefore, at higher speeds, the power dissipation must be greater than that at lower speeds before the internal threshold voltage on Pin 15 is exceeded. The effect of speed on the maximum power is determined by the resistor R10 and can therefore be adjusted to suit each individual application. If, after the load limiting has been turned on, the momentum of the load sinks below the “o-momentum” set using R10, then V15 will be reduced. V12 can then increase again so that the phase angle is reduced. A smaller phase angel corresponds to a larger momentum of the motor and hence the motor runs up - as long as this is allowed by the load momentum. For an already rotating machine, the effect of rotation on the measured “current integral” ensures that the power dissipation is able to increase with the rotational speed. the result is: a current controlled accelleration run-up., which ends in a small peak of accelleraton when the set point is reached. The latch of the load limiting is simultaneously reset. The speed of the motor is then again under control and it is capable of carrying its full load. The above mentioned peak of accelleration depends upon the ripple of actual speed voltage. A large amount of ripple also leads to a large peak of accelleration. The measuring resistor R8 should have a value which ensures that the amplitude of the voltage across it does not exceed 600 mV. 5 (20) U211B2/ B3 Design Hints Practical trials are normally needed for the exact determination of the values of the relevant components in the load limiting. To make this evaluation easier, the Parameters Pmax Pmin Pmax / min td tr Pmax Pmin td tr n.e following table shows the effect of the circuitry on the important parameters of the load limiting and summarises the general tendencies. Component affected R10 increases increases increases n.e. n.e. – maximum continuous power dissipation – power dissipation with no rotation – operation delay time – recovery time – no effect R9 decreases decreases n.e. decreases increases C9 n.e. n.e. n.e. increases increases 0 P1 = f(n) n 0 P1 = f(n) n = 0 Pulse Output Stage General Hints and Explanation of Terms The pulse output stage is short circuit protected and can typically deliver currents of 125 mA. For the design of smaller triggering currents, the function IGT = f(RGT) has been given in the data sheets in the appendix. To ensure safe and trouble-free operation, the following points should be taken into consideration when circuits are being constructed or in the design of printed circuit boards. – The connecting lines from C2 to Pin 7 and Pin 2 should be as short as possible: The connection to Pin 2 should not carry any additional high current such as the load current. When selecting C2, a low temperature coefficient is desirable. – The common (earth) connections of the set-point generator, the tacho-generator and the final interference suppression capacitor C4 of the f/V converter should not carry load current. – The tacho-generator should be mounted without influence by strong stray fields from the motor. – The connections from R10 and C5 should be as short as possible. To achieve a high noise immunity, a maximum ramp voltage of 6 V should be used. The typical resistance Rö can be calculated from Iö as follows: T(ms) 1.13(V) 10 3 R ö (kW) C nF) 6(V) Automatic Retriggering The variable automatic retriggering prevents half cycles without current flow, even if the triac is turned off earlier e.g. due to a collector which is not exactly centered (brush lifter) or in the event of unsuccessful triggering. If it is necessary, another triggering pulse is generated after a time lapse which is determined by the repetition rate set by resistance between Pin 5 and Pin 3 (R5-3). With the maximum repetition rate (Pin 5 directly connected to Pin 3), the next attempt to trigger comes after a pause of 4.5 tp and this is repeated until either the triac fires or the half-cycle finishes. If Pin 5 is connected, then only one trigger pulse per half-cycle is generated. Because the value of R5-3 determines the charging current of C2, any repetition rate set using R5-3 is only valid for a fixed value of C2. + ń T = Period duration for mains frequency (10 ms at 50 Hz) Cö = Ramp capacitor, max. ramp voltage 6 V and constant voltage drop at Rö = 1.13 V. A 10% lower value of Rö (under worst case conditions) is recommended. 6 (20) TELEFUNKEN Semiconductors Rev. A1, 29-May-96 U211B2/ B3 95 10716 V Mains Supply p/2 p 3/2p 2p VGT Trigger Pulse tp tpp = 4.5 tp VL Load Voltage ö IL Load Current F Figure 6. Explanation of terms in phase relationship Design Calculations for Mains Supply The following equations can be used for the evaluation of the series resistor R1 for worst case conditions: R 1max + 0.85 V P (R1max) + (V – V Smax 2 I tot Mmin R 1min + V 2 –I V M Smin Smax – V Smin) 2 2 R1 Mmax where: = Mains voltage = Supply voltage on Pin 3 = Total DC current requirement of the circuit Itot = IS + Ip + Ix ISmax = Current requirement of the IC in mA Ip = Average current requirement of the triggering pulse = Current requirement of other peripheral components Ix R1 can be easily evaluated from the figures 20 to 22. VM VS TELEFUNKEN Semiconductors Rev. A1, 29-May-96 7 (20) U211B2/ B3 Absolute Maximum Ratings Reference point Pin 2, unless otherwise specified Parameters Current requirement Pin 3 t ≤ 10 ms Synchronization current t t f/V converter Input current t Load limiting Limiting current, neg. half wave t Input voltage Phase control Input voltage Input current Soft-start Input voltage Pulse output Reverse voltage Pulse blocking Input voltage Amplifier Input voltage Pin 9 open Reference voltage source Output current Storage temperature range Junction temperature Ambient temperature range t 10 ms t 10 ms t 10 ms t 10 ms Pin 1 Pin 17 Pin 1 Pin 17 Pin 8 Symbol –IS Value 30 Unit mA –is 100 IsyncI IsyncV ±iI ±iI 5 5 35 35 mA II 3 mA ±iI 13 II 5 Pin 14 mA 35 Pin 14 Pin 15 ±Vi –VI 1 V16 to 0 Pin 12 Pin 12 Pin 6 –VI ±II –II 0 to 7 500 1 mA Pin 13 –VI V16 to 0 V Pin 4 VR VS to 5 V Pin 18 –VI V16 to 0 V Pin 11 Pin 10 VI –VI 0 to VS V16 to 0 V Pin 16 Io Tstg Tj Tamb 7.5 –40 to +125 125 –10 to +100 mA °C °C °C Symbol RthJA Maximum 120 180 100 Unit K/W V V mA Thermal Resistance Parameters Junction ambient 8 (20) DIP18 SO16 on p.c. SO16 on ceramic TELEFUNKEN Semiconductors Rev. A1, 29-May-96 U211B2/ B3 Electrical Characteristics –VS = 13.0 V, Tamb = 25°C, reference point Pin 2, unless otherwise specified Parameters Test Conditions / Pins Supply voltage for mains opPin 3 eration Supply voltage limitation –IS = 4 mA Pin 3 –IS = 30 mA DC current requirement –VS = 13.0 V Pin 3 Reference voltage source –IL = 10 mA Pin 16 –IL = 5 mA Temperature coefficient Pin 16 Voltage monitoring Turn-on threshold Pin 3 Turn-off threshold Pin 3 Phase control currents Synchronization current Pin 1 Voltage limitation Reference ramp, figure 7 Charge current Rö-reference voltage Temperature coefficient Pulse output, figure 18 Output pulse current Reverse current Output pulse width Amplifier Common mode signal range Input bias current Input offset voltage Output current Pin 17 IL = 5 mA Pins 1 and 17 " I7 = f (R6); Pin 7 R6 = 50 k to 1 MW a ≥ 180°C Pins 6 and 3 Pin 6 Pin 4 RGT = 0, VGT = 1.2 V Cϕ = 10 nF Pins 10 and 11 Pin 11 Pins 10 and 11 Pin 12 Short circuit forward, Figure 14 Pin 12 transmittance I12 = f(V10 -11) Pulse blocking, tacho-monitoring Pin 18 Logic-on Logic-off Input current V18 = VTOFF = 1.25 V V18 = V16 Output resistance TELEFUNKEN Semiconductors Rev. A1, 29-May-96 Symbol –VS Min. 13.0 –VS –VS IS –VRef 14.6 14.7 1.2 8.6 8.3 –TCVRef –VSON –VSOFF "I "I "V 11.2 9.9 Typ. 2.5 8.9 Max. VLimit Unit V 16.6 16.8 3.0 9.2 9.1 V mA V 0.5 mV/K 13.0 10.9 V V syncI 0.35 2.0 syncV 0.35 2.0 I 1.4 1.6 1.8 V I7 VöRef TCVöRef 1 1.06 20 1.13 0.5 1.18 A V mV/K Io Ior tp 100 155 0.01 80 V10, 11 IIO V10 –IO +IO V16 75 88 Yf –VTON –VTOFF II RO 0.01 10 110 120 m 190 3.0 mA mA ms –1 1 V mA mV mA 145 165 1000 3.7 14.5 1.5 mA m A/V 1.5 1.25 0.3 V 1.0 1 m 6 10 kW A 9 (20) U211B2/ B3 Parameters Test Conditions / Pins Frequency to voltage converter Pin 8 Input bias current Input voltage limitation Figure 13 II = –1 mA II = +1 mA Turn-on threshold Turn-off threshold Charge amplifier Discharge current Figure 2 C5 = 1 nF, Pin 9 Charge transfer voltage Pins 9 to 16 Charge transfer gain I10/I9 Pins 9 and 10 Conversion factor Figure 2 C5 = 1 nF, R6 = 100 kW Output operating range Pins 10 to 16 Linearity Soft-start, figures 8, 9, 10, 11, 12 f/v-converter non-active Starting current V13 = V16, V8 = V2 Pin 13 Final current V13 = 0.5 Pin 13 f/v-converter active Starting current V13 = V16 Pin 13 Final current V13 = 0.5 Discharge current Restart pulse Pin 13 Automatic retriggering, figure 19 Pin 5 Repetition rate R5-3 = 0 p R5-3 = 15 kW Load limiting, figures 15, 16, 17 Pin 14 Operating voltage range Pin 14 Offset current V10 = V16 Pin 14 V14 = V2 via 1 kW Pin 15–16 Input current V10 = 4.5 V Pin 14 Output current V14 = 300 mV Pin 15–16 Overload ON Pin 15–16 10 (20) Symbol Min. IIB –VI +VI –VTON –VTOFF Max. Unit 0.6 2 mA 750 8.05 150 mV V mV mV 660 7.25 20 Idis Vch Gi Typ. 100 50 0.5 6.50 7.5 K VO 6.70 8.3 mA 6.90 9.0 5.5 0-6 1 V mV/Hz V % mA IO 20 50 45 85 55 130 IO IO 2 30 0.5 4 55 3 7 80 10 mA tpp 3 4.5 20 6 tp VI IO –1.0 5 1.0 12 V II IO VTON 60 110 7.05 0.1 90 7.4 1.0 120 140 7.7 mA mA mA V TELEFUNKEN Semiconductors Rev. A1, 29-May-96 U211B2/ B3 240 10 Phase Control Reference Point Pin 2 200 4.7nF Soft Start 2.2nF V13 ( V ) Phase Angle (° ) 8 10nF 160 120 6 4 C /t=1.5nF 80 2 f/V-Converter Non Active Reference Point Pin 16 0 0 0 0.2 95 10302 0.4 0.6 R ( M ) 0.8 1.0 t=f(C3) 95 10305 Figure 7. Figure 10. 100 10 Soft Start Soft Start 8 V13 ( V ) I 13 ( A ) 80 60 40 f/V-Converter Active Reference Point Pin 16 6 4 20 2 f/V-Converter Non Active Reference Point Pin 16 0 0 0 2 4 6 8 10 V13 ( V ) 95 10303 t=f(C3) 95 10306 Figure 8. Figure 11. Soft Start Soft Start 8 80 Reference Point Pin 16 V13 ( V ) f/V-Converter Active Reference Point Pin 16 I 13 ( A ) 95 10307 10 100 60 6 4 40 2 20 0 0 0 95 10304 2 4 6 8 10 t=f(C3) Motor Standstill ( Dead Time ) Motor in Action V13 ( V ) Figure 9. TELEFUNKEN Semiconductors Rev. A1, 29-May-96 Figure 12. 11 (20) U211B2/ B3 200 500 f/V–Converter Load Limit Control 250 150 I 14–2 ( m A) I 8 (mA ) Reference Point Pin 2 0 100 –250 50 –500 –10 0 –8 –6 –4 –2 0 2 4 V8 ( V ) 95 10308 0 2 4 8 6 V10–16 (V) 95 10311 Figure 13. Figure 16. 250 Load current detection 100 Control Amplifier 200 I 15–16 ( m A ) I 12 ( mA ) 50 0 150 100 –50 I15=f ( VShunt ) V10=V16 50 Reference Point for I12 = –4V –100 –300 –200 –100 0 0 100 200 300 V10–11 ( V ) 95 10309 0 100 200 300 400 Figure 14. 600 700 Figure 17. 200 100 Load Limit Control Pulse Output 80 I GT ( mA ) m A) 150 100 –I 12–16 ( 500 V14–2 ( mV ) 95 10312 60 40 1.4V VGT=0.8V 50 20 0 0 0 95 10310 2 4 V15–16 ( V ) Figure 15. 12 (20) 6 8 0 95 10313 200 400 600 RGT ( W ) 800 1000 Figure 18. TELEFUNKEN Semiconductors Rev. A1, 29-May-96 U211B2/ B3 20 6 Automatic Retriggering 5 Mains Supply P(R1) ( W ) R 5–3 ( kW ) 15 10 4 3 2 5 1 0 0 0 6 12 18 24 30 tpp/tp 95 10314 0 10 40 30 Figure 21. 50 6 5 40 Mains Supply P(R1) ( W ) Mains Supply R 1( kW ) R1 ( kW ) 95 10316 Figure 19. 30 20 4 3 2 10 1 0 0 0 95 10315 20 4 8 Itot ( mA ) Figure 20. TELEFUNKEN Semiconductors Rev. A1, 29-May-96 12 16 0 95 10317 3 6 9 12 15 Itot ( mA ) Figure 22. 13 (20) Speed sensor R5 1 kW 9 C4 220 nF C5 R7 15 k W 10 680 pF 2.2 mF / 10 V R13 47 k W Set speed voltage C7 7 12 5 4 GND R8= 3 x 11 m W 1W C1 22 mF 25 V 180 W 470 k W M N 230 V~ L R1 1N4004 18 kW 1.5 W R4 1 R12 2 17 R3 R10 2.2 k W 47 k W R16 R15 T1 D1 47 k W T2 220 k W 18 10 kW R14 3 16 –VS C9 R9 470 kW 2.2 m F C11 95 10364 BZX55 R2 1 MW 6 U211B2 15 14 2.2 mF 10 V 13 R ö C3 220 nF 4.7m F 10 V C8 ö C2 2.2 nF C /t 8 11 1 MW R11 100 k W C6 R6 C10 100 nF R31 250 k W 2.2 m F 10 V U211B2/ B3 Figure 23. Speed control, automatic retriggering, load switch-off, soft start The switch-off level at maximum load shows in principle the same speed dependency as the original version (see figure 2), but when reaching the maximum load, the motor is switched off completely. 14 (20) This function is effected by the thyristor (formed by T1 and T2) which ignites when the voltage at Pin 15 reaches typ. 7.4 V (Reference point Pin 16). The circuit is thereby switched into the “stand-by” over the release Pin 18. TELEFUNKEN Semiconductors Rev. A1, 29-May-96 Speed sensor /t ö ö R R2 1 MW 22 m F 25 V 180W N 230 V~ M R8 = 3 x 11 mW 1W C1 470 k W R12 2 1 18 kW 1.5 W R4 R1 D1 1N4004 L R10 2.2 k W 47 k W GND –VS 4 3 16 17 18 R3 220 k W T2 R16 C2 2.2 nF C 7 6 5 U211B2 13 15 14 2.2 m F 10 V R14 10 kW T1 95 10366 BZX55 C4 220 nF R5 1 kW 9 8 11 12 C3 C8 4.7m F 10 V C9 2.2 m F C 11 R9 470 kW 33 kW R15 C5 R7 15 k W 10 680 pF 2.2 m F 10 / V R13 47 k W Set speed voltage C7 1 MW C6 R 11 100 kW 220 nF R6 C10 100 nF R31 250 k W 2.2 m F 10 V U211B2/ B3 Figure 24. Speed control, automatic retriggering, load switch-off, soft-start The maximum load regulation shows the principle in the same speed dependency as the original version (see figure 2). When reaching the maximum load, the control unit is turned to amax, adjustable with R2. Then only IO flows. This function is effected by the thyristor, formed by T1 and T2 which ignites as soon as the voltage at Pin 15 reaches ca. 6.8 V (Reference point Pin 16). The potential TELEFUNKEN Semiconductors Rev. A1, 29-May-96 at Pin 15 is lifted and kept by R14 over the internally operating threshold whereby the maximum load regulation starts and adjusts the control unit constantly to amax (IO), inspite of a reduced load current. The motor shows that the circuit is still in operation by a quiet buzzing noise. 15 (20) 16 (20) N 230 V~ L 95 10365 M R8 = 3 x 11 m W 1W R10 1 kW C1 R1 1N4004 D1 R4 22 m F 25 V 470 k W 18 k W 1.5 W R3 220 k W 1 MW 220 W R12 1 18 2 17 GND 1m F /10 V 22 nF C 11 3 16 –VS 4 15 C9 4.7m F 5 R2 1 MW U211B2 14 2.2 m F 10 V 6 13 7 12 C2 2.2 nF C ö R C3 C8 R9 1 M W 220 nF /t ö R5 1 kW C7 100 nF C 10 220 nF C4 C5 1 nF 2.2 m F /10 V 10 9 R6 C6 Speed sensor 8 11 1.5 MW R11 68 k W R7 22 k W R 13 47 k W Set speed voltage 250 k W R31 2.2 m F 10 V U211B2/ B3 Figure 25. Speed control, automatic retriggering, load limiting, soft-start, tacho control TELEFUNKEN Semiconductors Rev. A1, 29-May-96 TELEFUNKEN Semiconductors Rev. A1, 29-May-96 95 10687 C12 230 V~ 150 nF 250 V~ ca 220 Pulses / Revolution 47 m F 25 V 1 18 2 GND 17 D2 1N4004 IGT = 50 mA 470 k W 18 k W 1.5 W R14 C1 R1 1N4004 R5 L2 D1 R4 220 k W 100 W M L1 all diodes BYW83 –VS 100 W 3 16 15 4 C11 14 13 R3 4.7 k W R2 1 MW R15 3.5 k W / 8 W R6 5 6 C2 Rö R7 C3 U211B2 22 nF 2.2 m F 10 V 7 Cö/t C10 R10 8 C6 C5 Z3 BZX55 C9V1 100 W R11 16 k W R17 R16 470 W R13 Set speed max R18 Set speed min CNY 70 R31 100 k W C13 10 V 470 nF C7 C8 10 m F 4.7 m F 10 V 470 nF 220 k W 100 m F 10 V 1.5 k W R9 9 C4 220 nF 10 680 pF 11 3.3 nF 12 470 k W R8 47 k W U211B2/ B3 Figure 26. Speed control with reflective opto coupler CNY70 as emitter 17 (20) 18 (20) 230 V~ 95 10688 C12 100 W M R8= 3 x 0.1 W 150 nF 250 V~ R10 1.1 k W C1 R1 D1 –VS 15 14 13 R4 22 mF 25 V 1 IGT = 50 mA 220 k W 10 k W 1.1 W 1N4004 2 GND 100 W 3 4 R12 R2 1 MW 5 6 U211B2 C2 Rö 12 3.3 nF Cö/t R5 2.2 k W 7 8 11 820 k W C4 10 C5 470 nF C6 10 mF 47 mF 10 V 1 nF R16 10 kW 680 pF 9 C13 1mF 470 nF C8 16 R11 C3 R6 82 k W R3 17 2.2 mF 10 V 4.7 mF 10 V C7 22 nF C9 110 k W 18 220 k W C11 R9 R31 R17 33 k W R7 16 k W R18 470 W 9V R13 Set speed max R14 Set speed min CNY 70 220 k W C10 U211B2/ B3 Figure 27. Speed control, max. load control with reflective opto coupler CNY70 as emitter TELEFUNKEN Semiconductors Rev. A1, 29-May-96 U211B2/ B3 The circuit is designed as a speed control on the reflection-coupled principle with 4 periods per revolution and a max. speed of 30.000 rpm. The separation of the coupler from the rotating aperture should be 1 mm approximately. In this experimental circuit, the power supply for the coupler was provided externally because of the relatively high current consumption. Instructions for adjusting: D In the initial adjustment of the phase-control circuit, R2 should be adjusted so that when R14 = 0 and R31 are in min. position, the motor just turns. D The speed can now be adjusted as desired by means of R31 between the limits determined by R13 and R14. D The switch-off power of the limit load control can be set by R9. The lower R9, the higher the switch-off power. Dimensions in mm Package: DIP18 – U211B2 94 8877 Package: SO16 – U211B3 94 8875 TELEFUNKEN Semiconductors Rev. A1, 29-May-96 19 (20) U211B2/ B3 Ozone Depleting Substances Policy Statement It is the policy of TEMIC TELEFUNKEN microelectronic GmbH to 1. Meet all present and future national and international statutory requirements. 2. Regularly and continuously improve the performance of our products, processes, distribution and operating systems with respect to their impact on the health and safety of our employees and the public, as well as their impact on the environment. It is particular concern to control or eliminate releases of those substances into the atmosphere which are known as ozone depleting substances ( ODSs). The Montreal Protocol ( 1987) and its London Amendments ( 1990) intend to severely restrict the use of ODSs and forbid their use within the next ten years. Various national and international initiatives are pressing for an earlier ban on these substances. TEMIC TELEFUNKEN microelectronic GmbH semiconductor division has been able to use its policy of continuous improvements to eliminate the use of ODSs listed in the following documents. 1. Annex A, B and list of transitional substances of the Montreal Protocol and the London Amendments respectively 2 . Class I and II ozone depleting substances in the Clean Air Act Amendments of 1990 by the Environmental Protection Agency ( EPA) in the USA 3. Council Decision 88/540/EEC and 91/690/EEC Annex A, B and C ( transitional substances ) respectively. TEMIC can certify that our semiconductors are not manufactured with ozone depleting substances and do not contain such substances. We reserve the right to make changes to improve technical design and may do so without further notice. Parameters can vary in different applications. All operating parameters must be validated for each customer application by the customer. Should the buyer use TEMIC products for any unintended or unauthorized application, the buyer shall indemnify TEMIC against all claims, costs, damages, and expenses, arising out of, directly or indirectly, any claim of personal damage, injury or death associated with such unintended or unauthorized use. TEMIC TELEFUNKEN microelectronic GmbH, P.O.B. 3535, D-74025 Heilbronn, Germany Telephone: 49 ( 0 ) 7131 67 2831, Fax number: 49 ( 0 ) 7131 67 2423 20 (20) TELEFUNKEN Semiconductors Rev. A1, 29-May-96