VCA821 VC A8 21 VC A821 www.ti.com ....................................................................................................................................... SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 Ultra-Wideband, > 40dB Gain Adjust Range, Linear in dB VARIABLE GAIN AMPLIFIER FEATURES 1 DESCRIPTION • 710MHz SMALL-SIGNAL BANDWIDTH (G = +2V/V) • 320MHz, 4VPP BANDWIDTH (G = +10V/V) • 0.1dB GAIN FLATNESS to 135MHz • 2500V/µs SLEW RATE • > 40dB GAIN ADJUST RANGE • HIGH GAIN ACCURACY: 20dB ±0.3dB • HIGH OUTPUT CURRENT: ±90mA 23 The VCA821 is a dc-coupled, wideband, linear in dB, continuously variable, voltage-controlled gain amplifier. It provides a differential input to single-ended conversion with a high-impedance gain control input used to vary the gain down 40dB from the nominal maximum gain set by the gain resistor (RG) and feedback resistor (RF). APPLICATIONS • • • • • AGC RECEIVERS with RSSI DIFFERENTIAL LINE RECEIVERS PULSE AMPLITUDE COMPENSATION VARIABLE ATTENUATORS VOLTAGE-TUNABLE ACTIVE FILTERS VIN1 RF +VIN RG+ RS R1 RL FB RG VOUT VCA821 C1 CL RG- VIN2 -VIN 20W The VCA821 internal architecture consists of two input buffers and an output current feedback amplifier stage integrated with a multiplier core to provide a complete variable gain amplifier (VGA) system that does not require external buffering. The maximum gain is set externally with two resistors, providing flexibility in designs. The maximum gain is intended to be set between 6dB and 32dB. Operating from ±5V supplies, the gain control voltage for the VCA821 adjusts the gain linearly in dB as the control voltage varies from 0V to +2V. For example, set at a maximum gain of 20dB, the VCA821 provides 20dB, at VG = +2V, to less than –20dB at VG = 0V. The VCA821 offers excellent gain linearity. For a 20dB maximum gain, and a gain-control input voltage varying between +1V and +2V, the gain does not deviate by more than ±0.3dB (maximum at +25°C). RS VCA821 RELATED PRODUCTS DUALS GAIN ADJUST RANGE (dB) VCA810 — 80 2.4 35 6 — VCA2612 45 1.25 80 3 — VCA2613 45 1 80 — VCA2615 52 0.8 50 -6 — VCA2617 48 4.1 50 -9 VCA820 — 40 8.2 150 -15 VCA821 — 40 6.0 420 -18 VCA822 — 40 8.2 150 VCA824 — 40 6.0 420 Differential Equalizer SINGLES INPUT NOISE (nV/√Hz) SIGNAL BANDWIDTH (MHz) 9 Equalized Frequency Response Gain (dB) 0 Initial Frequency Response of the VCA821 with RC Load -3 -12 -21 -24 1M 10M 100M 1G Frequency (Hz) Differential Equalization of an RC Load 1 2 3 Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. X2Y is a trademark of X2Y Attenuators LLC. All other trademarks are the property of their respective owners. PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of the Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. Copyright © 2007–2008, Texas Instruments Incorporated VCA821 SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 ....................................................................................................................................... www.ti.com This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled with appropriate precautions. Failure to observe proper handling and installation procedures can cause damage. ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may be more susceptible to damage because very small parametric changes could cause the device not to meet its published specifications. ORDERING INFORMATION (1) SPECIFIED TEMPERATURE RANGE PACKAGE MARKING PRODUCT PACKAGE-LEAD PACKAGE DESIGNATOR VCA821 SO-14 D –40°C to +85°C VCA821ID VCA821 MSOP-10 DGS –40°C to +85°C BOR (1) ORDERING NUMBER TRANSPORT MEDIA, QUANTITY VCA821ID Rail, 50 VCA821IDR Tape and Reel, 2500 VCA821IDGST Tape and Reel, 250 VCA821IDGSR Tape and Reel, 2500 For the most current package and ordering information see the Package Option Addendum at the end of this document, or see the TI web site at www.ti.com. ABSOLUTE MAXIMUM RATINGS over operating free-air temperature range (unless otherwise noted) VCA821 UNIT ±6.5 V Power Supply Internal Power Dissipation See Thermal Characteristics Input Voltage Range Storage Temperature Range ±VS V –65 to +125 °C Lead Temperature (soldering, 10s) +260 °C Junction Temperature (TJ) +150 °C Junction Temperature (TJ), Maximum Continuous Operation +140 C 2000 V ESD Rating: Charge Device Model (CDM) Human Body Model (HBM) 1000 V Machine Model 200 V PIN CONFIGURATIONS D PACKAGE SO-14 (TOP VIEW) DGS PACKAGE MSOP-10 (TOP VIEW) +VCC 1 14 +VCC VG 2 +VIN FB 1 10 GND 13 NC +VCC 2 9 VOUT 3 12 FB VG 3 8 -VCC +RG 4 11 GND +VIN 4 7 -VIN -RG 5 10 VOUT +RG 5 6 -RG -VIN 6 9 VREF -VCC 7 8 -VCC NC = No Connection 2 Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 VCA821 www.ti.com ....................................................................................................................................... SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 ELECTRICAL CHARACTERISTICS: VS = ±5V At AVMAX = 20dB, RF = 402Ω, RG = 80Ω, RL = 100Ω, unless otherwise noted. VCA821 MIN/MAX OVER TEMPERATURE TYP PARAMETER CONDITIONS +25°C +25°C (2) 0°C to 70°C (3) –40°C to +85°C (3) UNITS MIN/ MAX TEST LEVEL (1) AC PERFORMANCE Small-Signal Bandwidth G = 6dB, VO = 500mVPP 710 MHz typ C G = 20dB, VO = 500mVPP 420 MHz typ C G = 40dB, VO = 500mVPP 170 MHz typ C Large-Signal Bandwidth G = 20dB, VO = 4VPP 320 MHz typ C Gain Control Bandwidth VO = 200mVPP 330 MHz min B Bandwidth for 0.1dB Flatness G = 20dB, VO = 200mVPP 135 MHz typ C Slew Rate G = 20dB, VO = 5V Step 2500 1800 1700 1700 V/µs min B Rise-and-Fall Time G = 20dB, VO = 5V Step 1.5 1.8 1.9 1.9 ns max B Settling Time to 0.01% G = 20dB, VO = 5V Step 11 ns typ C 2nd Harmonic VO = 2VPP, f = 20MHz –66 –64 –64 –64 dBc min B 3rd Harmonic VO = 2VPP, f = 20MHz –63 –61 –61 –61 dBc min B Input Voltage Noise f > 100kHz 6.0 nV/√Hz typ C Input Current Noise f > 100kHz 2.6 pA/√Hz typ C dB max A V typ C 240 235 235 Harmonic Distortion GAIN CONTROL Absolute Gain Error GMAX = 20dB, VG = 2V Vctrl0 ±0.1 ±0.4 ±0.5 ±0.6 0.85 VSlope 0.09 Absolute Gain Error Gain at VG = 0.2V V typ C ±0.6 dB max A –24 –23 dB max A 16.6 16.7 µA max A ±12 nA/°C max B MΩ || pF typ C GMAX = 20dB, VG = 1V, (G = 18.06 dB) ±0.3 ±0.4 relative to max gain –26 –24 10 16 ±12 Gain Control Bias Current Average Gain Control Bias Current Drift Gain Control Input Impedance ±0.5 1.5 || 0.6 DC PERFORMANCE Input Offset Voltage Average Input Offset Voltage Drift Input Bias Current Average Input Bias Current Drift Input Offset Current Average Input Offset Current Drift G = 20dB, VCM = 0V, VG = 1V ±4 ±17 G = 20dB, VCM = 0V, VG = 1V G = 20dB, VCM = 0V, VG = 1V 19 25 G = 20dB, VCM = 0V, VG = 1V G = 20dB, VCM = 0V, VG = 1V ±0.5 ±2.5 G = 20dB, VCM = 0V, VG = 1V Max Current Through Gain Resistance ±17.8 ±19 mV max A 30 30 µV/°C max B 29 31 µA max A 90 90 nA/°C max B ±3.2 ±3.5 µA max A ±16 ±16 nA/°C max B max B ±2.6 ±2.55 ±2.55 ±2.5 mA INPUT Most Positive Common Mode Input Voltage RL = 100Ω +1.6 +1.6 +1.6 +1.6 V min A Most Negative Common Mode Input Voltage RL = 100Ω –2.1 -2.1 –2.1 –2.1 V max A VCM = ±0.5V 80 65 60 60 dB min A 0.9 || 0.6 MΩ || pF typ C 1 || 2 MΩ || pF typ C Common-Mode Rejection Ratio Input Impedance Differential Common-Mode (1) (2) (3) Test levels: (A) 100% tested at +25°C. Over temperature limits set by characterization and simulation. (B) Limits set by characterization and simulation. (C) Typical value only for information. Junction temperature = ambient for +25°C tested specifications. Junction temperature = ambient at low temperature limit; junction temperature = ambient +23°C at high temperature limit for over temperature specifications. Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 3 VCA821 SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 ....................................................................................................................................... www.ti.com ELECTRICAL CHARACTERISTICS: VS = ±5V (continued) At AVMAX = 20dB, RF = 402Ω, RG = 80Ω, RL = 100Ω, unless otherwise noted. VCA821 MIN/MAX OVER TEMPERATURE TYP PARAMETER CONDITIONS +25°C +25°C (2) 0°C to 70°C (3) –40°C to +85°C (3) UNITS MIN/ MAX TEST LEVEL (1) OUTPUT Output Voltage Swing RL = 1kΩ ±3.9 ±3.6 ±3.4 ±3.3 V min A RL = 100Ω ±3.6 ±3.5 ±3.3 ±3.2 V min A VO = 0V, RL = 10Ω ±90 ±60 ±50 ±45 mA min A G = +10V/V, f > 100kHz 0.01 Ω typ C Specified Operating Voltage ±5 V typ C Minimum Operating Voltage ±3.5 V typ C Output Current Output Impedance POWER SUPPLY Maximum Operating Voltage ±6 ±6 ±6 V max A Maximum Quiescent Current VG = 1V 34 35 35.5 36 mA max A Minimum Quiescent Current VG = 1V 34 32.5 32 31.5 mA max A –68 –61 –59 –58 dB min A –40 to +85 °C typ C Power-Supply Rejection Ratio (–PSRR) THERMAL CHARACTERISTICS Specified Operating Range D Package Thermal Resistance θJA Junction-to-Ambient DGS MSOP-10 130 °C/W typ C D SO-14 80 °C/W typ C 4 Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 VCA821 www.ti.com ....................................................................................................................................... SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 TYPICAL CHARACTERISTICS: VS = ±5V, DC Parameters At TA = +25°C, RL = 100Ω, VG = +2V, and VIN = single-ended input on +VIN with –VIN at ground, unless otherwise noted. MAXIMUM DIFFERENTIAL INPUT VOLTAGE vs RG MAXIMUM GAIN ADJUST RANGE vs RF 40 IRG MAX = 2.6mA VIN MAX(VPP) = 2 ´ RG ´ IRG MAX (AP) Maximum Gain Adjust Range (dB) Differential Input Voltage (VPP) 10 1 30 25 VO = 1VPP 20 VO = 2VPP 15 VO = 4VPP 10 VO = 3VPP 5 0 0.1 10 100 1k 100 1k 10k Gain Resistor (W) Feedback Resistor (W) Figure 1. Figure 2. MAXIMUM GAIN ADJUST RANGE vs PEAK-TO-PEAK OUTPUT VOLTAGE GAIN ERROR BAND vs GAIN CONTROL VOLTAGE 12 60 Absolute Error IRG = 2.6mA AVMAX(V/V) = 2 ´ [RF/VIN(VPP)] ´ 2 ´ IRG (AP) 50 10 RF = 3kW Absolute Error 8 40 RF = 4kW Gain (V/V) Maximum Gain Adjust Range (dB) IRG = 2.6mA AVMAX(V/V) = 2 ´ [RF/VIN(VPP)] ´ 2 ´ IRG (AP) 35 RF = 5kW 30 RF = 500W 6 Relative Error to Maximum Gain 4 20 RF = 1kW 2 10 RF = 1.5kW RF = 2kW 0 0 0.1 1 10 0 0.2 0.4 0.6 0.8 1.0 1.2 Output Voltage (VPP) Control Voltage (V) Figure 3. Figure 4. GAIN ERROR BAND vs GAIN CONTROL VOLTAGE 1.4 1.6 1.8 2.0 RECOMMENDED RF vs AVMAX 40 460 For > 40dB Gain Adjust Range 20 Feedback Resistor (W) 450 Gain (dB) 0 -20 Equation A(V/V) = K ´ -40 RF ´ RG 1 ( VV G0 1+e - VG ) SLOPE -60 Data VCTRL0 = 0.85V VSLOPE = 90mV -80 440 430 420 410 400 NOTE: -3dB bandwidth varies with package type. See the Applications Information section for more details. 390 -100 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 1 10 Control Voltage (V) AVMAX (V/V) Figure 5. Figure 6. Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 100 5 VCA821 SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 ....................................................................................................................................... www.ti.com TYPICAL CHARACTERISTICS: VS = ±5V, DC and Power-Supply Parameters At TA = +25°C, RL = 100Ω, VG = +2V, and VIN = single-ended input on +VIN with –VIN at ground, unless otherwise noted. SUPPLY CURRENT vs CONTROL VOLTAGE (AVMAX = 6dB) SUPPLY CURRENT vs CONTROL VOLTAGE (AVMAX = 20dB) 36 36 +IQ +IQ 35 -IQ -IQ Quiescent Current (mA) Quiescent Current (mA) 35 34 33 32 31 34 33 32 31 30 30 29 29 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 0 0.8 1.0 1.2 1.4 Figure 7. Figure 8. 1.6 Input Offset Voltage (mV) +IQ 34 33 32 31 1.0 1.2 1.4 1.6 1.8 2.0 5 0 -3.0 -4.5 0.8 Input Offset Voltage (VOS) Left Scale -2.5 -4.0 0.6 10 -2.0 -3.5 20 15 -1.5 29 0.4 25 Input Bias Current (IB) Right Scale -1.0 30 0.2 30 -0.5 35 0 2.0 -5 Right Scale 10 x Input Offset Current (IOS) -50 Gain Control Voltage (V) -25 0 25 -10 50 75 100 Input Bias and Offset Current (mA) -IQ 36 1.8 TYPICAL DC DRIFT vs TEMPERATURE 0 37 Quiescent Current (mA) 0.6 0.4 Gain Control Voltage (V) SUPPLY CURRENT vs CONTROL VOLTAGE (AVMAX = 32dB) -15 125 Temperature (°C) Figure 9. 6 0.2 Gain Control Voltage (V) Figure 10. Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 VCA821 www.ti.com ....................................................................................................................................... SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = 6dB At TA = +25°C, RL = 100Ω, RF = 453Ω, RG = 453Ω, VG = +2V, VIN = single-ended input on +VIN with –VIN at ground, and SO-14 package, unless otherwise noted. SMALL-SIGNAL FREQUENCY RESPONSE LARGE-SIGNAL FREQUENCY RESPONSE 3 3 VO = 1VPP VG = +1V 0 0 Normalized Gain (dB) Normalized Gain (dB) VO = 2VPP -3 VG = +2V -6 -9 -12 -3 -6 -12 VO = 5VPP AVMAX = 6dB VIN = 1VPP RL = 100W -15 -18 1M VO = 4VPP -9 -15 -18 10M 100M 1G 2G 1M Figure 11. Figure 12. SMALL-SIGNAL PULSE RESPONSE 1G 2G LARGE-SIGNAL PULSE RESPONSE 4.0 200 3.0 100 0 -100 VIN = 2VPP f = 20MHz 2.0 Output Voltage (V) Output Voltage (mV) 100M Frequency (Hz) 300 -200 10M Frequency (Hz) 1.0 0 -1.0 -2.0 VIN = 250mVPP f = 20MHz -300 -3.0 Time (10ns/div) Time (10ns/div) Figure 13. Figure 14. COMPOSITE VIDEO dG/dP GAIN FLATNESS, DEVIATION FROM LINEAR PHASE 0 0 -0.3 -0.015 -0.4 -0.020 -dP, VG = 0V -0.5 -0.025 -0.6 -0.030 -dP, VG = +1V -0.7 -0.8 -0.040 -0.045 -0.9 2 3 0.1 0.10 0 0.05 0 -0.1 Right Scale -0.2 -0.05 -0.3 -0.10 -0.035 -dG, VG = +1V 1 Magnitude (dB) -0.010 Differential Phase (°) Differential Gain (%) -0.005 -dG, VG = 0V -0.2 0.15 Left Scale 4 -0.4 -0.15 AVMAX = 6dB VG = +2V -0.5 Deviation from Linear Phase (°) -0.1 0.2 -0.20 0 50 100 150 200 Frequency (MHz) Number of Video Loads Figure 15. Figure 16. Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 7 VCA821 SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 ....................................................................................................................................... www.ti.com TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = 6dB (continued) At TA = +25°C, RL = 100Ω, RF = 453Ω, RG = 453Ω, VG = +2V, VIN = single-ended input on +VIN with –VIN at ground, and SO-14 package, unless otherwise noted. HARMONIC DISTORTION vs LOAD RESISTANCE -60 -60 -65 -65 -70 3rd Harmonic -75 -80 AVMAX = 6dB VG = +2V VO = 2VPP RL = 100W 2nd Harmonic -85 Harmonic Distortion (dBc) Harmonic Distortion (dBc) HARMONIC DISTORTION vs FREQUENCY -90 -70 2nd Harmonic -75 -80 3rd Harmonic -85 -90 0.1 1 10 100 100 1k Frequency (MHz) Resistance (W) Figure 17. Figure 18. HARMONIC DISTORTION vs OUTPUT VOLTAGE HARMONIC DISTORTION vs GAIN CONTROL VOLTAGE -10 AVMAX = 6dB VG = +2V RL = 100W f = 20MHz -35 -40 -45 -50 -55 -60 -65 2nd Harmonic -70 -75 AVMAX = 6dB VO = 2VPP RL = 100W f = 20MHz -20 Maximum Current Through RG Limited Harmonic Distortion (dBc) -30 Harmonic Distortion (dBc) AVMAX = 6dB VG = +2V VO = 2VPP f = 20MHz 3rd Harmonic -30 -40 Maximum Current Through RG Limited -50 -60 2nd Harmonic -70 3rd Harmonic -80 -80 -90 -85 0.1 1 0.8 10 1.0 1.2 1.4 1.6 1.8 2.0 Output Voltage Swing (VPP) Gain Control Voltage (V) Figure 19. Figure 20. TWO-TONE, 3RD-ORDER INTERMODULATION INTERCEPT TWO-TONE, 3RD-ORDER INTERMODULATION INTERCEPT vs GAIN CONTROL VOLTAGE 38 40 36 35 Intercept Point (+dBm) Intercept Point (+dBm) Constant Input Voltage 34 32 30 28 30 Constant Output Voltage 25 20 15 26 At 50W Matched Load 10 24 0 8 10 20 30 40 50 60 70 80 90 100 f = 20MHz At 50W Matched Load 0.8 1.0 1.2 1.4 1.6 Frequency (MHz) Gain Control Voltage (V) Figure 21. Figure 22. Submit Documentation Feedback 1.8 2.0 Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 VCA821 www.ti.com ....................................................................................................................................... SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = 6dB (continued) At TA = +25°C, RL = 100Ω, RF = 453Ω, RG = 453Ω, VG = +2V, VIN = single-ended input on +VIN with –VIN at ground, and SO-14 package, unless otherwise noted. GAIN vs GAIN CONTROL VOLTAGE GAIN CONTROL FREQUENCY RESPONSE 2.2 3 2.0 1.8 0 Normalized Gain (dB) 1.6 Gain (V/V) 1.4 1.2 1.0 0.8 0.6 0.4 -3 -6 -9 0.2 VG = 1VDC + 10mVPP VIN =0.5VDC 0 -12 -0.2 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 10M 1M 2.0 Frequency (Hz) Figure 23. Figure 24. GAIN CONTROL PULSE RESPONSE 1G FULLY-ATTENUATED RESPONSE 20 4 2 1 2.5 0 2.0 -1 1.5 1.0 10 VG = +2V 0 Normalized Gain (dB) 3 Output Voltage (V) VIN = 1VDC Input Voltage (V) 100M Gain Control Voltage (V) -10 -30 -40 -50 -60 0.5 -70 0 -80 -0.5 VO = 2VPP -20 Input Referred VG = 0V -90 10M 1M Time (10ns/div) 100M 1G Frequency (Hz) Figure 25. Figure 26. GROUP DELAY vs GAIN CONTROL VOLTAGE GROUP DELAY vs FREQUENCY 2.0 1.6 1.8 1.4 10MHz 1.6 Group Delay (ns) Group Delay (ns) 1.2 1.4 1.2 1.0 1MHz 0.8 20MHz 0.6 1.0 0.8 0.6 0.4 0.4 VG = +2V VO = 1VPP 0.2 0.2 0 0 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 0 20 40 60 Gain Control Voltage (V) Frequency (MHz) Figure 27. Figure 28. 80 Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 100 9 VCA821 SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 ....................................................................................................................................... www.ti.com TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = 6dB (continued) At TA = +25°C, RL = 100Ω, RF = 453Ω, RG = 453Ω, VG = +2V, VIN = single-ended input on +VIN with –VIN at ground, and SO-14 package, unless otherwise noted. RECOMMENDED RS vs CAPACITIVE LOAD FREQUENCY RESPONSE vs CAPACITIVE LOAD 9 100 VO = 0.5VPP CL = 10pF 6 CL = 22pF CL = 100pF RS (W) RS (W) 3 10 CL = 47pF 0 RF -3 VIN + RS VCA821 NOTE: (1) 1kW is optional. -9 1 10 100 1 1k 10 100 Capacitive Load (pF) Capacitive Load (pF) Figure 29. Figure 30. OUTPUT VOLTAGE NOISE DENSITY 1k INPUT CURRENT NOISE DENSITY 200 10 Input Voltage Noise Density (pA/ÖHz) Output Voltage Noise Density (nV/ÖHz) 1kW(1) - 0.1dB Flatness Targeted 1 VG = +1V 100 VG = +2V VG = 0V 10 1 100 10 VOUT CL -6 1k 10k 100k 1M 10M 100 1k 10k 100k Frequency (Hz) Frequency (Hz) Figure 31. Figure 32. Submit Documentation Feedback 1M 10M Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 VCA821 www.ti.com ....................................................................................................................................... SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = 20dB At TA = +25°C, RL = 100Ω, RF = 402Ω, RG = 80Ω, VG = +2V, and VIN = single-ended input on +VIN with –VIN at ground, unless otherwise noted. SMALL-SIGNAL FREQUENCY RESPONSE LARGE-SIGNAL FREQUENCY RESPONSE 3 3 0 0 Normalized Gain (dB) Normalized Gain (dB) VG = +1V -3 -6 VG = +2V -9 -12 AVMAX = 20dB VIN = 200mVPP RL = 100W -15 -18 1M VO = 1VPP -3 VO = 2VPP -6 -9 VO = 4VPP -12 VO = 5VPP -15 -18 10M 100M 1G 1M Figure 33. Figure 34. 200 2 100 0 -100 1 0 -1 -2 VIN = 50mVPP VIN = 400mVPP f = 20MHz f = 20MHz -3 -300 Time (10ns/div) Time (10ns/div) Figure 35. Figure 36. Left Scale -0.1 0.10 -0.2 0.05 0 -0.3 Right Scale -0.05 -0.4 -0.10 AVMAX = 20dB VG = +2V 0 50 -0.15 100 150 200 Deviation from Linear Phase (°) 0.15 0 Magnitude (dB) OUTPUT VOLTAGE NOISE DENSITY 0.20 Output Voltage Noise Density (nV/ÖHz) GAIN FLATNESS, DEVIATION FROM LINEAR PHASE 0.1 -0.6 1G LARGE-SIGNAL PULSE RESPONSE 3 Output Voltage (V) Output Voltage (mV) SMALL-SIGNAL PULSE RESPONSE -0.5 100M Frequency (Hz) 300 -200 10M Frequency (Hz) 200 VG = +2V 100 VG = 0V VG = +1V 10 100 Frequency (MHz) 1k 10k 100k 1M 10M Frequency (Hz) Figure 37. Figure 38. Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 11 VCA821 SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 ....................................................................................................................................... www.ti.com TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = 20dB (continued) At TA = +25°C, RL = 100Ω, RF = 402Ω, RG = 80Ω, VG = +2V, and VIN = single-ended input on +VIN with –VIN at ground, unless otherwise noted. HARMONIC DISTORTION vs LOAD RESISTANCE -50 -66 -55 -68 Harmonic Distortion (dBc) Harmonic Distortion (dBc) HARMONIC DISTORTION vs FREQUENCY -60 3rd Harmonic -65 -70 -75 AVMAX = 20dB VG = +2V VO = 2VPP RL = 100W 2nd Harmonic -80 -72 3rd Harmonic -74 -76 -78 2nd Harmonic -85 -80 0.1 1 10 -40 100 1k Resistance (W) Figure 39. Figure 40. HARMONIC DISTORTION vs OUTPUT VOLTAGE HARMONIC DISTORTION vs GAIN CONTROL VOLTAGE -10 AVMAX = +10V/V VG = +2V RL = 100W f = 20MHz -30 100 Frequency (MHz) AVMAX = 20dB VO = 2VPP RL = 100W f = 20MHz -20 Maximum Current Through RG Limited Harmonic Distortion (dBc) -20 Harmonic Distortion (dBc) -70 AVMAX = 20dB VG = +2V VO = 1VPP f = 20MHz -50 -60 2nd Harmonic -70 3rd Harmonic -80 -30 -40 Maximum Current through RG Limited. -50 -60 2nd Harmonic -70 3rd Harmonic -80 -90 -90 0.1 1 0.6 10 0.8 1.0 1.2 1.4 1.6 1.8 2.0 Output Voltage Swing (VPP) Gain Control Voltage (V) Figure 41. Figure 42. TWO-TONE, 3RD-ORDER INTERMODULATION INTERCEPT TWO-TONE, 3RD-ORDER INTERMODULATION INTERCEPT vs GAIN CONTROL VOLTAGE 37 40 35 35 Intercept Point (+dBm) Intercept Point (+dBm) Constant Input Voltage 33 31 29 30 25 Constant Output Voltage 20 VG = +2V At 50W Matched Load 15 27 0 12 10 20 30 40 50 60 70 80 90 100 f = 20MHz At 50W Matched Load 0.8 1.0 1.2 1.4 1.6 Frequency (MHz) Gain Control Voltage (V) Figure 43. Figure 44. Submit Documentation Feedback 1.8 2.0 Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 VCA821 www.ti.com ....................................................................................................................................... SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = 20dB (continued) At TA = +25°C, RL = 100Ω, RF = 402Ω, RG = 80Ω, VG = +2V, and VIN = single-ended input on +VIN with –VIN at ground, unless otherwise noted. GAIN vs GAIN CONTROL VOLTAGE GAIN CONTROL FREQUENCY RESPONSE 11 3 10 9 0 Normalized Gain (dB) 8 Gain (V/V) 7 6 5 4 3 2 -3 -6 -9 1 -12 0 -15 -1 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 10M 1M 2.0 100M Gain Control Voltage (V) Frequency (Hz) Figure 45. Figure 46. GAIN CONTROL PULSE RESPONSE 2 1 2.5 0 2.0 -1 4 3 Output Voltage (V) 3 Output Voltage (V) VIN = 0.2VDC 1G OUTPUT VOLTAGE AND CURRENT LIMITATIONS 5 4 Input Voltage (V) VG = 1VDC + 10mVPP VIN = 0.1VDC 1.5 1.0 1W Internal Power Dissipation 100W Load 2 1 50W Load 0 25W Load -1 -2 0.5 -3 0 -4 -5 -150 -0.5 Time (10ns/div) 1W Internal Power Dissipation -100 -50 0 50 100 150 Output Current (mA) Figure 47. Figure 48. FULLY-ATTENUATED RESPONSE IRG LIMITED OVERDRIVE RECOVERY 0.4 30 20 Input Voltage (V) 0 -10 VO = 2VPP -20 -30 -40 -50 -60 Input Referred -70 VG = 0V -80 0.2 1.0 0.1 0.5 0 -0.1 0 Output Voltage Right Scale 1M 10M 100M -0.5 -0.2 -1.0 -0.3 -1.5 -0.4 -90 1.5 1G Output Voltage (V) Normalized Gain (dB) 0.3 VG = +2V 10 2.0 AVMAX = +10V/V VG = 0.7V Input Voltage Left Scale -2.0 Time (40ns/div) Frequency (Hz) Figure 49. Figure 50. Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 13 VCA821 SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 ....................................................................................................................................... www.ti.com TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = 20dB (continued) At TA = +25°C, RL = 100Ω, RF = 402Ω, RG = 80Ω, VG = +2V, and VIN = single-ended input on +VIN with –VIN at ground, unless otherwise noted. OUTPUT LIMITED OVERDRIVE RECOVERY Output Voltage Right Scale 2 0 0 -0.4 -2 Input Voltage Left Scale 10MHz 4 0.2 -0.2 1.65 1.60 Output Voltage (V) Input Voltage (V) 0.4 GROUP DELAY vs GAIN CONTROL VOLTAGE 6 AVMAX = +10V/V VG = +2V 1.55 1MHz 1.50 20MHz 1.45 -4 -0.6 Group Delay (ns) 0.6 -6 1.40 Time (40ns/div) 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 Gain Control Voltage (V) Figure 51. Figure 52. GROUP DELAY vs FREQUENCY 1.8 1.6 Group Delay (ns) 1.4 1.2 1.0 0.8 0.6 0.4 VG = +2V VO = 1VPP 0.2 0 0 20 40 60 80 100 Frequency (MHz) Figure 53. 14 Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 VCA821 www.ti.com ....................................................................................................................................... SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = 32dB At TA = +25°C, RL = 100Ω, RF = 402Ω, RG = 18Ω, VG = +2V, VIN = single-ended input on +VIN with –VIN at ground, and SO-14 package, unless otherwise noted. LARGE-SIGNAL FREQUENCY RESPONSE 3 0 0 Normalized Gain (dB) Normalized Gain (dB) SMALL-SIGNAL FREQUENCY RESPONSE 3 -3 VG = +1V -6 VG = +2V -9 -12 AVMAX = 32dB VIN = 50mVPP RL = 100W -15 VO = 1VPP, 2VPP, 4VPP, 5VPP -3 -6 -9 -12 -15 -18 -18 1M 10M 100M 1G 0 100 200 300 Frequency (Hz) Frequency (MHz) Figure 54. Figure 55. SMALL-SIGNAL PULSE RESPONSE 400 500 LARGE-SIGNAL PULSE RESPONSE 400 2.5 2.0 300 1.5 Output Voltage (V) Output Voltage (V) 200 100 0 -100 -200 1.0 0.5 0 -0.5 -1.0 -1.5 VIN = 12.5mVPP -2.0 f = 20MHz -300 VIN = 100mVPP f = 20MHz -2.5 Time (10ns/div) Time (10ns/div) Figure 56. Figure 57. 0.10 0.05 0 0 -0.1 -0.2 -0.05 -0.3 -0.10 -0.4 -0.15 -0.20 -0.5 0 20 40 60 200 Deviation from Linear Phase (°) AVMAX = 32dB VG = +2V 0.1 Magnitude (dB) OUTPUT VOLTAGE NOISE DENSITY 0.15 Output Voltage Noise Density (nV/ÖHz) GAIN FLATNESS, DEVIATION FROM LINEAR PHASE 0.2 1000 VG = +2V VG = +1V 100 VG = 0V 10 100 Frequency (MHz) 1k 10k 100k 1M 10M Frequency (Hz) Figure 58. Figure 59. Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 15 VCA821 SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 ....................................................................................................................................... www.ti.com TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = 32dB (continued) At TA = +25°C, RL = 100Ω, RF = 402Ω, RG = 18Ω, VG = +2V, VIN = single-ended input on +VIN with –VIN at ground, and SO-14 package, unless otherwise noted. HARMONIC DISTORTION vs FREQUENCY -35 -50 AVMAX = 32dB VG = +2V VO = 2VPP RL = 100W -45 -55 Harmonic Distortion (dBc) -40 Harmonic Distortion (dBc) HARMONIC DISTORTION vs LOAD RESISTANCE -50 -55 -60 2nd Harmonic -65 -60 3rd Harmonic -65 -70 -75 -80 3rd Harmonic -70 -85 0.1 -30 100 100 1k Resistance (W) Figure 60. Figure 61. HARMONIC DISTORTION vs OUTPUT VOLTAGE HARMONIC DISTORTION vs GAIN CONTROL VOLTAGE -10 AVMAX = 32dB VO = 2VPP RL = 100W f = 20MHz -15 Maximum Current Through RG Limited -40 -50 2nd Harmonic Frequency (MHz) AVMAX = 32dB VG = +2V RL = 100W f = 20MHz -20 Harmonic Distortion (dBc) 10 Harmonic Distortion (dBc) -10 1 AVMAX = 32dB VG = +2V VO = 1VPP f = 20MHz 2nd Harmonic -60 3rd Harmonic -70 -20 -25 -30 Maximum Current Through RG Limited -35 -40 -45 3rd Harmonic -50 -55 2nd Harmonic -60 -80 0.1 1 0.6 10 0.8 1.0 1.2 1.4 1.6 1.8 2.0 Output Voltage Swing (VPP) Gain Control Voltage (V) Figure 62. Figure 63. TWO-TONE, 3RD-ORDER INTERMODULATION INTERCEPT TWO-TONE, 3RD-ORDER INTERMODULATION INTERCEPT vs GAIN CONTROL VOLTAGE 35 34 Constant Output Voltage 30 Intercept Point (+dBm) Intercept Point (+dBm) 32 30 28 26 24 VG = +2V At 50W Matched Load 22 0 16 10 20 30 Constant Input Voltage 25 20 15 10 40 50 60 70 80 90 100 f = 20MHz At 50W Matched Load 0.8 1.0 1.2 1.4 1.6 Frequency (MHz) Gain Control Voltage (V) Figure 64. Figure 65. Submit Documentation Feedback 1.8 2.0 Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 VCA821 www.ti.com ....................................................................................................................................... SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = 32dB (continued) At TA = +25°C, RL = 100Ω, RF = 402Ω, RG = 18Ω, VG = +2V, VIN = single-ended input on +VIN with –VIN at ground, and SO-14 package, unless otherwise noted. GAIN vs GAIN CONTROL VOLTAGE GAIN CONTROL FREQUENCY RESPONSE 3 45 40 0 Normalized Gain (dB) 35 Gain (V/V) 30 25 20 15 10 -3 -6 -9 -12 5 -15 0 VG = 1VDC + 10mVPP VIN = 10mVDC -18 -5 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 10M 1M Frequency (Hz) Figure 66. Figure 67. GAIN CONTROL PULSE RESPONSE 1G FULLY ATTENUATED RESPONSE 30 4 2 1 2.5 0 2.0 -1 20 VG = +2V 10 Normalized Gain (dB) 3 Output Voltage (V) VIN = 50mVDC Input Voltage (V) 100M Gain Control Voltage (V) 1.5 1.0 0.5 0 -10 VO = 2VPP -20 -30 -40 -50 -60 Input Referred -70 0 VG = 0V -80 -90 -0.5 10M 1M Time (10ns/div) 100M 1G Frequency (Hz) Figure 68. Figure 69. IRG LIMITED OVERDRIVE RECOVERY 0.4 1.2 0.8 0.1 0.4 0 0 -0.1 -0.4 -0.2 -0.8 -0.3 Output Voltage Right Scale -0.4 -1.2 -1.6 6 AVMAX = 32dB VG = +2V Output Voltage Right Scale 4 0.1 2 0 0 -0.1 -0.2 -2 Input Voltage Left Scale -0.3 Output Voltage (V) 0.2 0.2 Input Voltage (V) AVMAX = 32dB VG = 0.7V Input Voltage Left Scale Output Voltage (V) Input Voltage (V) 0.3 OUTPUT LIMITED OVERDRIVE RECOVERY 0.3 1.6 -4 -6 Time (40ns/div) Time (40ns/div) Figure 70. Figure 71. Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 17 VCA821 SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 ....................................................................................................................................... www.ti.com TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = 32dB (continued) At TA = +25°C, RL = 100Ω, RF = 402Ω, RG = 18Ω, VG = +2V, VIN = single-ended input on +VIN with –VIN at ground, and SO-14 package, unless otherwise noted. GROUP DELAY vs GAIN CONTROL VOLTAGE GROUP DELAY vs FREQUENCY 2.5 2.15 10MHz 2.10 2.0 Group Delay (ns) Group Delay (ns) 20MHz 2.05 2.00 1MHz 1.95 1.90 1.5 1.0 0.5 VG = +2V VO = 1VPP 1.85 0 1.80 0 18 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 0 20 40 60 Gain Control Voltage (V) Frequency (MHz) Figure 72. Figure 73. Submit Documentation Feedback 80 100 Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 VCA821 www.ti.com ....................................................................................................................................... SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 APPLICATION INFORMATION WIDEBAND VARIABLE GAIN AMPLIFIER OPERATION For test purposes, the input impedance is set to 50Ω with a resistor to ground and the output impedance is set to 50Ω with a series output resistor. Voltage swings reported in the Electrical Characteristics table are taken directly at the input and output pins, while output power (dBm) is at the matched 50Ω load. For the circuit in Figure 74, the total effective load is 100Ω 1kΩ. Note that for the SO-14 package, there is a voltage reference pin, VREF (pin 9). For the SO-14 package, this pin must be connected to ground through a 20Ω resistor in order to avoid possible oscillations of the output stage. In the MSOP-10 package, this pin is internally connected and does not require such precaution. An X2Y™ capacitor has been used for power-supply bypassing. The combination of low inductance, high resonance frequency, and integration of three capacitors in one package (two capacitors to ground and one across the supplies) enables the VCA821 to achieve the low second-harmonic distortion reported in the Electrical Characteristics table. More information on how the VCA821 operates can be found in the Operating Suggestions section. The VCA821 provides an exceptional combination of high output power capability with a wideband, greater than 40dB gain adjust range, linear in dB variable gain amplifier. The VCA821 input stage places the transconductance element between two input buffers, using the output currents as the forward signal. As the differential input voltage rises, a signal current is generated through the gain element. This current is then mirrored and gained by a factor of two before reaching the multiplier. The other input of the multiplier is the voltage gain control pin, VG. Depending on the voltage present on VG, up to two times the gain current is provided to the transimpedance output stage. The transimpedance output stage is a current-feedback amplifier providing high output current capability and high slew rate, 2500V/µs. This exceptional full-power performance comes at the price of relatively high quiescent current (34mA), but low input voltage noise for this type of architecture (6nV/√Hz). Figure 74 shows the dc-coupled, gain of +10V/V, dual power-supply circuit used as the basis of the ±5V Electrical Characteristics and Typical Characteristics. ® 0.1mF +5V X2Y Capacitor Detail X2Yâ Capacitor (see detail) +VS -5V A G1 + 2.2mF VG B -VS +VIN VIN 20W x1 FB IRG RG+ RG 200W G2 + 2.2mF RF 1kW x2 RG- VOUT VOUT x1 20W -VIN VREF SO-14 VCA821 20W Figure 74. DC-Coupled, AVMAX = 20dB, Bipolar Supply Specification and Test Circuit Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 19 VCA821 SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 ....................................................................................................................................... www.ti.com DIFFERENCE AMPLIFIER Because both inputs of the VCA821 are high-impedance, a difference amplifier can be implemented without any major problem. Figure 75 shows this implementation. This circuit provides excellent common-mode rejection ratio (CMRR) as long as the input is within the CMRR range of –2.1V to +1.6V. Note that this circuit does not make use of the gain control pin, VG. Also, it is recommended to choose RS such that the pole formed by RS and the parasitic input capacitance does not limit the bandwidth of the circuit. Figure 76 shows the common-mode rejection ratio for this circuit implemented in a gain of 20dB for VG = +2V. Note that because the gain control voltage is fixed and is normally set to +2V, the feedback element can be reduced in order to increase the bandwidth. When reducing the feedback element, make sure that the VCA821 is not limited by common-mode input voltage, the current flowing through RG, or any other limitation described in this data sheet. be used advantageously because its architecture allows the application to isolate the input from the gain setting elements. Figure 77 shows an implementation of such a configuration. The transfer function is shown in Equation 1. RF 1 + sRGC1 ´ G=2´ RG 1 + sR1C1 (1) VIN1 R1 RG 20W RS Figure 75. Difference Amplifier 85 C1 RGVIN2 -VIN 20W RS 80 Input Referred 75 70 65 9 Equalized Frequency Response 60 6 55 3 0 50 45 40 10k 100k 1M 10M 100M Frequency (Hz) Gain (dB) Common-Mode Rejection Ratio (dB) VCA821 This transfer function has one pole, P1 (located at RGC1), and one zero, Z1 (located at R1C1). When equalizing an RC load, RL and CL, compensate the pole added by the load located at RLCL with the zero Z1. Knowing RL, CL, and RG allows the user to select C1 as a first step and then calculate R1. Using RL = 75Ω, CL = 100pF and wanting the VCA821 to operate at a gain of +2V/V, which gives RF = RG = 453Ω, allows the user to select C1 = 15.5pF to ensure a positive value for the resistor R1. With all these values known, to achieve greater than 300MHz bandwidth, R1 can be calculated to be 20Ω. Figure 78 shows the frequency response for both the initial, unequalized frequency response and the resulting equalized frequency response. FB VCA821 RG-VIN VIN- FB RG Figure 77. Differential Equalizer +VIN RG+ RS RG+ RS RF VIN+ RF +VIN Initial Frequency Response of the VCA821 with RC Load -3 -6 -9 -12 -15 Figure 76. Common-Mode Rejection Ratio -18 -21 -24 1M DIFFERENTIAL EQUALIZER 100M 1G Frequency (Hz) If the application requires frequency shaping (the transition from one gain to another), the VCA821 can 20 10M Figure 78. Differential Equalization of an RC Load Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 VCA821 www.ti.com ....................................................................................................................................... SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 DIFFERENTIAL CABLE EQUALIZER AGC LOOP A differential cable equalizer can easily be implemented using the VCA821. An example of a cable equalization for 100 feet of Belden cable 1694F is illustrated in Figure 78, with Figure 79 showing the result for this implementation. This implementation has a maximum error of 0.2dB from dc to 70MHz. In the typical AGC loop shown in Figure 81, the OPA695 follows the VCA821 to provide 40dB of overall gain. The output of the OPA695 is rectified and integrated by an OPA820 to control the gain of the VCA821. when the output level exceeds the reference voltage (VREF), the integrator ramps down reducing the gain of the AGC loop. Conversely, if the output is too small, the integrator ramps up increasing the net gain and the output voltage. Note that this implementation shows the cable attenuation side-by-side with the equalization in the same plot. For a given frequency, the equalization function realized with the VCA821 matches the cable attenuation. The circuit in Figure 80 is a driver circuit. To implement a receiver circuit, the signal is received differentially between the +VIN and –VIN inputs. 1694F Cable Attenuation (dB) Equalizer Gain (dB) 2.0 1.5 1.0 Cable Attenuation 0.5 VCA821 Equalization 0 -0.5 -1.0 1 10 100 Frequency (MHz) Figure 79. Cable Attenuation versus Equalizer Gain VIN R2 453W +VIN R8 50W RG+ R18 13.6kW R17 6kW R21 3kW R9 432W VCA821 C7 300mF RG- GND VG -VIN C6 320mF VOUT FB VREF R1 20W R10 75W VOUT 75W Load R5 50W C5 4pF VG = +1VDC C9 10mF Figure 80. Differential Cable Equalizer Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 21 VCA821 SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 ....................................................................................................................................... www.ti.com 1kW VIN +VIN RG+ FB 50W 200W 50W VCA821 Out RG- VG -VIN 50W OPA695 50W VOUT 950W 100W 50W 0.1mF 1kW 1N4150 OPA820 VREF Figure 81. AGC Loop predict typical small-signal ac performance, transient steps, dc performance, and noise under a wide variety of operating conditions. The models include the noise terms found in the electrical specifications of the relevant product data sheet. DESIGN-IN TOOLS DEMONSTRATION BOARDS Two printed circuit boards (PCBs) are available to assist in the initial evaluation of circuit performance using the VCA821 in its two package options. Both of these are offered free of charge as unpopulated PCBs, delivered with a user's guide. The summary information for these fixtures is shown in Table 1. Table 1. EVM Ordering Information PRODUCT PACKAGE BOARD PART NUMBER LITERATURE REQUEST NUMBER VCA821ID SO-14 DEM-VCA-SO-1B SBOU050 VCA821IDGS MSOP-10 DEM-VCA-MSOP-1A SBOU051 The demonstration fixtures can be requested at the Texas Instruments web site (www.ti.com) through the VCA821 product folder. MACROMODELS AND APPLICATIONS SUPPORT Computer simulation of circuit performance using SPICE is often useful when analyzing the performance of analog circuits and systems. This principle is particularly true for video and RF amplifier circuits where parasitic capacitance and inductance can play a major role in circuit performance. A SPICE model for the VCA821 is available through the TI web page. The applications group is also available for design assistance. The models available from TI 22 OPERATING SUGGESTIONS Operating the VCA821 optimally for a specific application requires trade-offs between bandwidth, input dynamic range and the maximum input voltage, the maximum gain of operation and gain, output dynamic range and the maximum input voltage, the package used, loading, and layout and bypass recommendations. The Typical Characteristics have been defined to cover as much ground as possible to describe the VCA821 operation. There are four sections in the Typical Characteristics: • VS = ±5V DC Parameters and VS = ±5V DC and Power-Supply Parameters, which include dc operation and the intrinsic limitation of a VCA821 design • VS = ±5V, AVMAX = 6dB Gain of 6dB Operation • VS = ±5V, AVMAX = 20dB Gain of 20dB Operation • VS = ±5V, AVMAX = 32dB Gain of 32dB Operation Where the Typical Characteristics describe the actual performance that can be achieved by using the amplifier properly, the following sections describe in detail the trade-offs needed to achieve this level of performance. Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 VCA821 www.ti.com ....................................................................................................................................... SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 PACKAGE CONSIDERATIONS The VCA821 is available in both SO-14 and MSOP-10 packages. Each package has, for the different gains used in the typical characteristics, different values of RF and RG in order to achieve the same performance detailed in the Electrical Characteristics table. Figure 82 shows a test gain circuit for the VCA821. Table 2 lists the recommended configuration for the SO-14 and MSOP-10 packages. There are no differences between the packages in the recommended values for the gain and feedback resistors. However, the bandwidth for the VCA821IDGS (MSOP-10 package) is lower than the bandwidth for the VCA821ID (SO-14 package). This difference is true for all gains, but especially true for gains greater than 5V/V, as can be seen in Figure 83 and Figure 84. Note that the scale must be changed to a linear scale to view the details. 3 AVMAX = 2V/V +VIN VIN R1 50W Source RF RG+ 50W RG VOUT RGR3 R2 50W Load Normalized Gain (dB) 0 AVMAX = 5V/V -3 -6 -9 AVMAX = 10V/V -12 AVMAX = 20V/V -15 -VIN 50W AVMAX = 40V/V -18 0 200 400 600 800 1000 Frequency (MHz) VG Figure 83. SO-14 Recommended RF and RG versus AVMAX Figure 82. Test Circuit Table 2. SO-14 and MSOP-10 RF and RG Configurations 3 AVMAX = 2V/V G=2 G = 10 G = 40 RF 453Ω 402Ω 402Ω RG 453Ω 80Ω 18Ω Normalized Gain (dB) 0 AVMAX = 5V/V -3 -6 -9 AVMAX = 10V/V -12 AVMAX = 20V/V -15 AVMAX = 40V/V -18 0 200 400 600 800 1000 Frequency (MHz) Figure 84. MSOP-10 Recommended RF and RG versus AVMAX Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 23 VCA821 SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 ....................................................................................................................................... www.ti.com MAXIMUM GAIN OF OPERATION This section describes the use of the VCA821 in a fixed-gain application in which the VG control pin is set at VG = +1V. The tradeoffs described here are with bandwidth, gain, and output voltage range. In the case of an application that does not make use of the VGAIN, but requires some other characteristic of the VCA821, the RG resistor must be set such that the maximum current flowing through the resistance IRG is less than ±2.6mA typical, or 5.2mAPP as defined in the Electrical Characteristics table, and must follow Equation 2. VOUT IRG = AVMAX ´ RG (2) As Equation 2 illustrates, once the output dynamic range and maximum gain are defined, the gain resistor is set. This gain setting in turn affects the bandwidth, because in order to achieve the gain (and with a set gain element), the feedback element of the output stage amplifier is set as well. Keeping in mind that the output amplifier of the VCA821 is a current-feedback amplifier, the larger the feedback element, the lower the bandwidth because the feedback resistor is the compensation element. Limiting the discussion to the input voltage only and ignoring the output voltage and gain, Figure 1 illustrates the tradeoff between the input voltage and the current flowing through the gain resistor. OUTPUT CURRENT AND VOLTAGE The VCA821 provides output voltage and current capabilities that are unsurpassed in a low-cost monolithic VCA. Under no-load conditions at +25°C, the output voltage typically swings closer than 1V to either supply rails; the +25°C swing limit is within 1.2V of either rails. Into a 15Ω load (the minimum tested load), it is tested to deliver more than ±90mA. The specifications described above, though familiar in the industry, consider voltage and current limits separately. In many applications, it is the voltage × current, or V-I product, that is more relevant to circuit operation. Refer to the Output Voltage and Current Limitations plot (Figure 48) in the Typical Characteristics. The X- and Y-axes of this graph show the zero-voltage output current limit and the zero-current output voltage limit, respectively. The four quadrants give a more detailed view of the VCA821 output drive capabilities, noting that the graph is bounded by a Safe Operating Area of 1W maximum internal power dissipation. Superimposing resistor load lines onto the plot shows that the 24 VCA821 can drive ±2.5V into 25Ω or ±3.5V into 50Ω without exceeding the output capabilities or the 1W dissipation limit. A 100Ω load line (the standard test circuit load) shows the full ±3.9V output swing capability, as shown in the Typical Characteristics. The minimum specified output voltage and current over-temperature are set by worst-case simulations at the cold temperature extreme. Only at cold startup do the output current and voltage decrease to the numbers shown in the Electrical Characteristics tables. As the output transistors deliver power, the respective junction temperatures increase, thereby increasing the available output voltage swing and output current. In steady-state operation, the available output voltage and current are always greater than the temperature shown in the over-temperature specifications because the output stage junction temperatures are higher than the specified operating ambient. INPUT VOLTAGE DYNAMIC RANGE The VCA821 has a input dynamic range limited to +1.6V and –2.1V. Increasing the input voltage dynamic range can be done by using an attenuator network on the input. If the VCA821 is trying to regulate the amplitude at the output, such as in an AGC application, the input voltage dynamic range is directly proportional to Equation 3. VIN(PP) = RG ´ IRG(PP) (3) As such, for unity-gain or under-attenuated conditions, the input voltage must be limited to the CMIR of ±1.6V (3.2VPP) and the current (IRQ) must flow through the gain resistor, ±2.6mA (5.2mAPP). This configuration sets a minimum value for RE such that the gain resistor must be greater than Equation 4. 3.2VPP RGMIN = = 615.4W 5.2mAPP (4) Values lower than 615.4Ω are gain elements that result in reduced input range, as the dynamic input range is limited by the current flowing through the gain resistor RG (IRG). If the IRG current limits the performance of the circuit, the input stage of the VCA821 goes into overdrive, resulting in limited output voltage range. Such IRG-limited overdrive conditions are shown in Figure 50 for the gain of 20dB and Figure 70 for the 32dB gain. Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 VCA821 www.ti.com ....................................................................................................................................... SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 OUTPUT VOLTAGE DYNAMIC RANGE OFFSET ADJUSTMENT With its large output current capability and its wide output voltage swing of ±3.9V typical on 100Ω load, it is easy to forget other types of limitations that the VCA821 can encounter. For these limitations, careful analysis must be done to avoid input stage limitation: either voltage or IRG current. Note that if control pin VG varies, the gain limitation may affect other aspects of the circuit. As a result of the internal architecture used on the VCA821, the output offset voltage originates from the output stage and from the input stage and multiplier core. Figure 85 shows how to compensate both sources of the output offset voltage. Use this procedure to compensate the output offset voltage: starting with the output stage compensation, set VG = –1V to eliminate all offset contribution of the input stage and multiplier core. Adjust the output stage offset compensation potentiometer. Finally, set VG = +1V to the maximum gain and adjust the input stage and multiplier core potentiometer. This procedure effectively eliminates all offset contribution at the maximum gain. Because adjusting the gain modifies the contribution of the input stage and the multiplier core, some residual output offset voltage remains. BANDWIDTH The output stage of the VCA821 is a wideband current-feedback amplifier. As such, the feedback resistance is the compensation of the last stage. Reducing the feedback element and maintaining the gain constant limits the useful range of IRG, and therefore, reduces the gain adjust range. For a given gain, reducing the gain element limits the maximum achievable output voltage swing. +5V Output Stage Offset Compensation Circuit 10kW 4kW 0.1mF -5V RF VIN +VIN RG+ 50W RG FB VOUT VCA821 RG-VIN +5V 1kW 50W 10kW 0.1mF -5V Input Stage and Multiplexer Core Offset Compensation Circuit Figure 85. Adjusting the Input and Output Voltage Sources Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 25 VCA821 SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 ....................................................................................................................................... www.ti.com NOISE This model is formulated in Equation 5 and Figure 86. The VCA821 offers 6nV/√Hz input-referred voltage noise density at a gain of 20dB and 2.6pA/√Hz input-referred current noise density. The input-referred voltage noise density considers that all noise terms (except the input current noise but including the thermal noise of both the feedback resistor and the gain resistor) are expressed as one term. eO = AVMAX ´ 2 ´ (RS ´ in)2 + en2 + 2 ´ 4kTRS (5) A more complete model is shown in Figure 87. For additional information on this model and the actual modeled noise terms, please contact the High-Speed Product Application Support team at www.ti.com. RF in RS +VIN RG+ eO RG FB VCA821 eO RG-VIN * 4kTRS in RS * 4kTRS NOTE: RF and RG are noiseless. Figure 86. Simple Noise Model VG inINPUT VG +VIN V+ RS1 * * enINPUT 4kTRS1 FB x1 RF +RG * inINPUT VOUT RG (Noiseless) ICORE 4kTRF * eO iinOUTPUT -RG VREF x1 RF enOUTPUT * enINPUT iniOUTPUT * -VIN 4kTRF VRS2 inINPUT GND * 4kTRS2 Figure 87. Full Noise Model 26 Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 VCA821 www.ti.com ....................................................................................................................................... SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 THERMAL ANALYSIS The VCA821 does not require heatsinking or airflow in most applications. The maximum desired junction temperature sets the maximum allowed internal power dissipation as described in this section. In no case should the maximum junction temperature be allowed to exceed +150°C. Operating junction temperature (TJ) is given by Equation 6: TJ = TA + PD ´ qJA (6) The total internal power dissipation (PD) is the sum of quiescent power (PDQ) and additional power dissipated in the output stage (PDL) to deliver load power. Quiescent power is simply the specified no-load supply current times the total supply voltage across the part. PDL depends on the required output signal and load; for a grounded resistive load, however, it is at a maximum when the output is fixed at a voltage equal to one-half of either supply voltage (for equal bipolar supplies). Under this worst-case condition, PDL = VS2/(4 × RL), where RL is the resistive load. Note that it is the power in the output stage and not in the load that determines internal power dissipation. As a worst-case example, compute the maximum TJ using a VCA821ID (SO-14 package) in the circuit of Figure 74 operating at maximum gain and at the maximum specified ambient temperature of +85°C. PD = 10V(36mA) + 52/(4 ´ 100W) = 422.5mW (7) Maximum TJ = +85°C + (0.443W ´ 80°C/W) = 120.5°C (8) This maximum operating junction temperature is well below most system level targets. Most applications should be lower because an absolute worst-case output stage power was assumed in this calculation of VCC/2, which is beyond the output voltage range for the VCA821. BOARD LAYOUT Achieving optimum performance with a high-frequency amplifier such as the VCA821 requires careful attention to printed circuit board (PCB) layout parasitics and external component types. Recommendations to optimize performance include: a) Minimize parasitic capacitance to any ac ground for all of the signal I/O pins. This recommendation includes the ground pin (pin 2). Parasitic capacitance on the output can cause instability: on both the inverting input and the noninverting input, it can react with the source impedance to cause unintentional band limiting. To reduce unwanted capacitance, a window around the signal I/O pins should be opened in all of the ground and power planes around those pins. Otherwise, ground and power planes should be unbroken elsewhere on the board. Place a small series resistance (greater than 25Ω) with the input pin connected to ground to help decouple package parasitics. b) Minimize the distance (less than 0.25 inches, or 6.3mm) from the power-supply pins to high-frequency 0.1µF decoupling capacitors. At the device pins, the ground and power plane layout should not be in close proximity to the signal I/O pins. Avoid narrow power and ground traces to minimize inductance between the pins and the decoupling capacitors. The power-supply connections should always be decoupled with these capacitors. Larger (2.2µF to 6.8µF) decoupling capacitors, effective at lower frequencies, should also be used on the main supply pins. These capacitors may be placed somewhat farther from the device and may be shared among several devices in the same area of the PCB. c) Careful selection and placement of external components preserve the high-frequency performance of the VCA821. Resistors should be a very low reactance type. Surface-mount resistors work best and allow a tighter overall layout. Metal-film and carbon composition, axially-leaded resistors can also provide good high-frequency performance. Again, keep the leads and PCB trace length as short as possible. Never use wire-wound type resistors in a high-frequency application. Because the output pin is the most sensitive to parasitic capacitance, always position the series output resistor, if any, as close as possible to the output pin. Other network components, such as inverting or non-inverting input termination resistors, should also be placed close to the package. d) Connections to other wideband devices on the board may be made with short direct traces or through onboard transmission lines. For short connections, consider the trace and the input to the next device as a lumped capacitive load. Relatively wide traces (50mils to 100mils, or 1.27mm to 2.54mm) should be used, preferably with ground and power planes opened up around them. e) Socketing a high-speed part like the VCA821 is not recommended. The additional lead length and pin-to-pin capacitance introduced by the socket can create an extremely troublesome parasitic network, which can make it almost impossible to achieve a smooth, stable frequency response. Best results are obtained by soldering the VCA821 onto the board. Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 27 VCA821 SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 ....................................................................................................................................... www.ti.com INPUT AND ESD PROTECTION The VCA821 is built using a very high-speed complementary bipolar process. The internal junction breakdown voltages are relatively low for these very small geometry devices. These breakdowns are reflected in the Section 2 table. All pins on the VCA821 are internally protected from ESD by means of a pair of back-to-back reverse-biased diodes to either power supply, as shown in Figure 88. These diodes begin to conduct when the pin voltage exceeds either power supply by about 0.7V. This situation can occur with loss of the amplifier power supplies while a signal source is still present. The diodes can typically withstand a continuous current of 30mA without destruction. To ensure long-term reliability, however, diode current should be externally limited to 10mA whenever possible. 28 +VS External Pin ESD protection diodes internally connected to all pins. Internal Circuitry -VS Figure 88. Internal ESD Protection Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 VCA821 www.ti.com ....................................................................................................................................... SBOS407B – DECEMBER 2007 – REVISED DECEMBER 2008 Revision History Changes from Revision A (August 2008) to Revision B ................................................................................................ Page • Revised second paragraph in Wideband Variable Gain Amplifier Operation section describing pin 9 ............................... 19 Changes from Original (December 2007) to Revision A ................................................................................................ Page • Changed storage temperature range rating in Absolute Maximum Ratings table from –40°C to +125°C to –65°C to +125°C ................................................................................................................................................................................... 2 Submit Documentation Feedback Copyright © 2007–2008, Texas Instruments Incorporated Product Folder Link(s): VCA821 29 PACKAGE OPTION ADDENDUM www.ti.com 19-Nov-2012 PACKAGING INFORMATION Orderable Device Status (1) Package Type Package Pins Package Qty Drawing Eco Plan Lead/Ball Finish (2) MSL Peak Temp Samples (3) (Requires Login) VCA821ID ACTIVE SOIC D 14 50 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR VCA821IDG4 ACTIVE SOIC D 14 50 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR VCA821IDGSR ACTIVE VSSOP DGS 10 2500 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR VCA821IDGSRG4 ACTIVE VSSOP DGS 10 2500 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR VCA821IDGST ACTIVE VSSOP DGS 10 250 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR VCA821IDGSTG4 ACTIVE VSSOP DGS 10 250 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR VCA821IDR ACTIVE SOIC D 14 2500 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR VCA821IDRG4 ACTIVE SOIC D 14 2500 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability information and additional product content details. TBD: The Pb-Free/Green conversion plan has not been defined. Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes. Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above. Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material) (3) MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature. Addendum-Page 1 PACKAGE OPTION ADDENDUM www.ti.com 19-Nov-2012 Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release. In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis. Addendum-Page 2 PACKAGE MATERIALS INFORMATION www.ti.com 19-Nov-2012 TAPE AND REEL INFORMATION *All dimensions are nominal Device Package Package Pins Type Drawing VCA821IDGSR VSSOP DGS 10 VCA821IDGST VSSOP DGS VCA821IDR SOIC D SPQ Reel Reel A0 Diameter Width (mm) (mm) W1 (mm) B0 (mm) K0 (mm) P1 (mm) W Pin1 (mm) Quadrant 2500 330.0 12.4 5.3 3.4 1.4 8.0 12.0 Q1 10 250 180.0 12.4 5.3 3.4 1.4 8.0 12.0 Q1 14 2500 330.0 16.4 6.5 9.0 2.1 8.0 16.0 Q1 Pack Materials-Page 1 PACKAGE MATERIALS INFORMATION www.ti.com 19-Nov-2012 *All dimensions are nominal Device Package Type Package Drawing Pins SPQ Length (mm) Width (mm) Height (mm) VCA821IDGSR VSSOP DGS 10 2500 367.0 367.0 35.0 VCA821IDGST VSSOP DGS 10 250 210.0 185.0 35.0 VCA821IDR SOIC D 14 2500 367.0 367.0 38.0 Pack Materials-Page 2 IMPORTANT NOTICE Texas Instruments Incorporated and its subsidiaries (TI) reserve the right to make corrections, enhancements, improvements and other changes to its semiconductor products and services per JESD46, latest issue, and to discontinue any product or service per JESD48, latest issue. Buyers should obtain the latest relevant information before placing orders and should verify that such information is current and complete. All semiconductor products (also referred to herein as “components”) are sold subject to TI’s terms and conditions of sale supplied at the time of order acknowledgment. TI warrants performance of its components to the specifications applicable at the time of sale, in accordance with the warranty in TI’s terms and conditions of sale of semiconductor products. Testing and other quality control techniques are used to the extent TI deems necessary to support this warranty. Except where mandated by applicable law, testing of all parameters of each component is not necessarily performed. TI assumes no liability for applications assistance or the design of Buyers’ products. Buyers are responsible for their products and applications using TI components. To minimize the risks associated with Buyers’ products and applications, Buyers should provide adequate design and operating safeguards. TI does not warrant or represent that any license, either express or implied, is granted under any patent right, copyright, mask work right, or other intellectual property right relating to any combination, machine, or process in which TI components or services are used. Information published by TI regarding third-party products or services does not constitute a license to use such products or services or a warranty or endorsement thereof. Use of such information may require a license from a third party under the patents or other intellectual property of the third party, or a license from TI under the patents or other intellectual property of TI. Reproduction of significant portions of TI information in TI data books or data sheets is permissible only if reproduction is without alteration and is accompanied by all associated warranties, conditions, limitations, and notices. TI is not responsible or liable for such altered documentation. Information of third parties may be subject to additional restrictions. Resale of TI components or services with statements different from or beyond the parameters stated by TI for that component or service voids all express and any implied warranties for the associated TI component or service and is an unfair and deceptive business practice. TI is not responsible or liable for any such statements. Buyer acknowledges and agrees that it is solely responsible for compliance with all legal, regulatory and safety-related requirements concerning its products, and any use of TI components in its applications, notwithstanding any applications-related information or support that may be provided by TI. Buyer represents and agrees that it has all the necessary expertise to create and implement safeguards which anticipate dangerous consequences of failures, monitor failures and their consequences, lessen the likelihood of failures that might cause harm and take appropriate remedial actions. Buyer will fully indemnify TI and its representatives against any damages arising out of the use of any TI components in safety-critical applications. In some cases, TI components may be promoted specifically to facilitate safety-related applications. With such components, TI’s goal is to help enable customers to design and create their own end-product solutions that meet applicable functional safety standards and requirements. Nonetheless, such components are subject to these terms. No TI components are authorized for use in FDA Class III (or similar life-critical medical equipment) unless authorized officers of the parties have executed a special agreement specifically governing such use. Only those TI components which TI has specifically designated as military grade or “enhanced plastic” are designed and intended for use in military/aerospace applications or environments. Buyer acknowledges and agrees that any military or aerospace use of TI components which have not been so designated is solely at the Buyer's risk, and that Buyer is solely responsible for compliance with all legal and regulatory requirements in connection with such use. TI has specifically designated certain components as meeting ISO/TS16949 requirements, mainly for automotive use. In any case of use of non-designated products, TI will not be responsible for any failure to meet ISO/TS16949. Products Applications Audio www.ti.com/audio Automotive and Transportation www.ti.com/automotive Amplifiers amplifier.ti.com Communications and Telecom www.ti.com/communications Data Converters dataconverter.ti.com Computers and Peripherals www.ti.com/computers DLP® Products www.dlp.com Consumer Electronics www.ti.com/consumer-apps DSP dsp.ti.com Energy and Lighting www.ti.com/energy Clocks and Timers www.ti.com/clocks Industrial www.ti.com/industrial Interface interface.ti.com Medical www.ti.com/medical Logic logic.ti.com Security www.ti.com/security Power Mgmt power.ti.com Space, Avionics and Defense www.ti.com/space-avionics-defense Microcontrollers microcontroller.ti.com Video and Imaging www.ti.com/video RFID www.ti-rfid.com OMAP Applications Processors www.ti.com/omap TI E2E Community e2e.ti.com Wireless Connectivity www.ti.com/wirelessconnectivity Mailing Address: Texas Instruments, Post Office Box 655303, Dallas, Texas 75265 Copyright © 2012, Texas Instruments Incorporated