MOTOROLA MC33368D

Order this document by MC33368/D

The MC33368 is an active power factor controller that functions as a
boost preconverter in off–line power supply applications. MC33368 is
optimized for low power, high density power supplies requiring a minimum
board area, reduced component count and low power dissipation. The
narrow body SOIC package provides a small footprint. Integration of the high
voltage startup saves approximately 0.7 W of power compared to resistor
bootstrapped circuits.
The MC33368 features a watchdog timer to initiate output switching, a
one quadrant multiplier to force the line current to follow the instantaneous
line voltage a zero current detector to ensure critical conduction operation, a
transconductance error amplifier, a current sensing comparator, a 5.0 V
reference, an undervoltage lockout (UVLO) circuit which monitors the VCC
supply voltage and a CMOS driver for driving MOSFETs. The MC33368 also
includes a programmable output switching frequency clamp. Protection
features include an output overvoltage comparator to minimize overshoot, a
restart delay timer and cycle–by–cycle current limiting.
•
•
•
•
•
HIGH VOLTAGE
GREENLINE POWER
FACTOR CONTROLLER
SEMICONDUCTOR
TECHNICAL DATA
16
1
P SUFFIX
PLASTIC PACKAGE
CASE 648
(DIP–16)
Lossless Off–Line Startup
16
1
Output Overvoltage Comparator
D SUFFIX
PLASTIC PACKAGE
CASE 751K
(SO–16)
Leading Edge Blanking (LEB) for Noise Immunity
Watchdog Timer to Initiate Switching
Restart Delay Timer
PIN CONNECTIONS
Device
Operating
Temperature Range
MC33368D
MC33368P
Package
SO–16
TJ = –25° to +125°C
1
16 Line
2
15 N/C
Voltage FB
3
14 N/C
Comp
4
Mult
5
Current Sense
6
12 VCC
11 Gate
Zero Current
7
10 PGnd
AGnd
8
9 LEB
DIP–16
DIP–16
ORDERING INFORMATION
5.0 Vref
Restart Delay
13 Frequency Clamp
(Top View)
16 Line
5.0 Vref
Restart Delay
1
Voltage FB
3
Comp
4
Mult
5
Current Sense
6
12 VCC
11 Gate
Zero Current
7
10 PGnd
AGnd
8
9 LEB
2
SO–16
GreenLine is a trademark of Motorola, Inc.
13 Frequency Clamp
(Top View)
This document contains information on a new product. Specifications and information herein
are subject to change without notice.
MOTOROLA ANALOG IC DEVICE DATA
 Motorola, Inc. 1997
Rev 2
1
MC33368
Representative Block Diagram
Line
Restart Delay
Restart Delay
VCC
Output
Overvoltage
FB
Comp
Mult
UVLO
Multiplier/
Error
Amplifier
LEB
PWM
R
Q
Gate
PGnd
WatchdogTimer/
Zero Current Detector
ZC Det
Vref
AGnd
S
Current
Sense
Current Sense
Internal Bias
Generator
S
Frequency
Clamp
Frequency
Clamp
This device contains 240 active transistors.
MAXIMUM RATINGS (TA = 25°C, unless otherwise noted.)
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
Symbol
Value
Unit
Power Supply Voltage (Transient)
VCC
20
V
Power Supply Voltage (Operating)
VCC
16
V
Line Voltage
VLine
500
V
Current Sense, Multiplier, Compensation, Voltage
Feedback, Restart Delay and Zero Current Input
Voltage
Vin1
–1.0 to +10
V
LEB Input, Frequency Clamp Input
Vin2
–1.0 to +20
V
Zero Current Detect Input
Iin
±5.0
mA
Restart Diode Current
Rating
Iin
5.0
mA
Power Dissipation and Thermal Characteristics
P Suffix, Plastic Package Case 648
Maximum Power Dissipation @ TA = 70°C
Thermal Resistance, Junction–to–Air
PD
RθJA
1.25
100
mW
°C/W
Power Dissipation and Thermal Characteristics
D Suffix, Plastic Package Case 751K
Maximum Power Dissipation @ TA = 70°C
Thermal Resistance, Junction–to–Air
PD
RθJA
450
178
mW
°C/W
Operating Junction Temperature
TJ
150
°C
Operating Ambient Temperature
TA
–25 to +125
°C
Tstg
–55 to +150
°C
Storage Temperature Range
NOTE: ESD data available upon request.
2
MOTOROLA ANALOG IC DEVICE DATA
MC33368
ELECTRICAL CHARACTERISTICS (VCC = 14.5 V, for typical values TA = 25°C, for min/max values TJ = –25 to +125°C)
Characteristic
Symbol
Min
Typ
Max
Unit
Input Bias Current (VFB = 5.0 V)
IIB
–
0
1.0
µA
Input Offset Voltage (VComp = 3.0 V)
VIO
–
2.0
50
mV
Transconductance (VComp = 3.0 V)
gm
30
51
80
µmho
Output Source (VFB = 4.6 V, VComp = 3.0 V)
Output Sink (VFB = 5.4 V, VComp = 3.0 V)
IO
IO
9.0
9.0
17.5
17.5
30
30
µA
VFB(OV)
1.07 VFB
1.084 VFB
1.1 VFB
V
TP
–
705
–
ns
IIB
–
–0.2
–1.0
µA
Vth(M)
1.8
2.1
2.4
V
VMult
VComp
0 to 2.5
Vth(M) to
(Vth(M) + 1.0)
0 to 3.5
Vth(M) to
(Vth(M) + 2.0)
–
–
K
0.25
0.51
0.75
1/V
Vref
4.95
5.0
5.05
V
Line Regulation (VCC = 10 V to 16 V)
Regline
–
5.0
100
mV
Load Regulation (IO = 0 – 5.0 mA)
Regload
–
5.0
100
mV
Vref
4.8
–
5.2
V
Maximum Output Current
IO
5.0
10
–
mA
Reference Undervoltage Lockout Threshold
Vth
–
4.5
–
V
Input Threshold Voltage (Vin Increasing)
Vth
1.0
1.2
1.4
V
Hysteresis (Vin Decreasing)
VH
100
200
300
mV
Delay to Output
Tpd
–
127
–
ns
Input Bias Current (VCS = 0 to 2.0 V)
IIB
–
0.2
1.0
µA
Input Offset Voltage (VMult = –0.2 V)
VIO
–
4.0
50
mV
Vth(max)
1.3
1.5
1.8
V
tPHL(in/out)
50
270
425
ns
Vth(FC)
1.9
2.0
2.1
V
Frequency Clamp Capacitor Reset Current (VFC = 0.5 V)
Ireset
0.5
1.7
4.0
mA
Frequency Clamp Disable Voltage
VDFC
–
7.3
8.0
V
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ȡȧ +
ȣȧ
ÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ǓȤ
Ȣ ǒ
ÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ERROR AMPLIFIER
OVERVOLTAGE COMPARATOR
Voltage Feedback Input Threshold
Propagation Time to Output
MULTIPLIER
Input Bias Current, VMult (VFB = 0 V)
Input Threshold, VComp
Dynamic Input Voltage Range
Multiplier Input
Compensation
Multiplier Gain (VMult = 0.5 V, VComp = Vth(M) + 1.0 V)
V
K
V
CS
Mult
V
V
Threshold
– V
th(M)
Comp
VOLTAGE REFERENCE
Voltage Reference (IO = 0 mA, TJ = 25°C)
Total Output Variation Over Line, Load and Temperature
ZERO CURRENT DETECTOR
CURRENT SENSE COMPARATOR
Maximum Current Sense Input Threshold (VComp = 5.0 V,
VMult = 5.0 V)
Delay to Output (VLEB = 12 V, VComp = 5.0 V, VMult = 5.0 V)
(VCS = 0 to 5.0 V Step, CL = 1.0 nF)
FREQUENCY CLAMP
Frequency Clamp Input Threshold
MOTOROLA ANALOG IC DEVICE DATA
3
MC33368
ELECTRICAL CHARACTERISTICS (continued) (VCC = 14.5 V, for typical values TA = 25°C, for min/max values TJ = –25 to +125°C)
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
Characteristic
Symbol
Min
Typ
Max
Unit
Source Resistance (Current Sense = 0 V, VGate = VCC – 1.0 V)
Sink Resistance (Current Sense = 3.0 V, VGate = 1.0 V)
ROH
ROL
4.0
4.0
8.6
7.2
20
20
Ω
Output Voltage Rise Time (25% – 75%) (CL = 1.0 nF)
tr
–
55
200
ns
Output Voltage Fall Time (75% – 25%) (CL = 1.0 nF)
tf
–
70
200
ns
VO(UV)
–
0.01
0.25
V
Input Bias Current
Ibias
–
0.1
0.5
µA
Threshold (as Offset from VCC) (VLEB Increasing)
VLEB
1.0
2.25
2.75
V
VH
100
270
500
mV
Vth(on)
11.5
13
14.5
V
VShutdown
7.0
8.5
10
V
VH
–
4.5
–
V
tDLY
180
385
800
µs
Vth(restart)
1.5
2.3
3.0
V
Irestart
3.1
5.2
7.1
mA
Line Startup Current (VCC = 0 V, VLine = 50 V)
ISU
5.0
16
25
mA
Line Operating Current (VCC = Vth(on), VLine = 50 V)
IOP
3.0
12.9
20
mA
VCC Dynamic Operating Current (50 kHz, CL = 1.0 nF)
VCC Static Operating Current (IO = 0)
ICC
–
–
5.3
3.0
8.5
–
mA
Line Pin Leakage (VLine = 500 V)
ILine
–
30
80
µA
DRIVE OUTPUT
Output Voltage in Undervoltage (VCC = 7.0 V, ISink = 1.0 mA)
LEADING EDGE BLANKING
Hysteresis (VLEB Decreasing)
UNDERVOLTAGE LOCKOUT
Startup Threshold (VCC Increasing)
Minimum Operating Voltage After Turn–On (VCC Decreasing)
Hysteresis
TIMER
Watchdog Timer
Restart Timer Threshold
Restart Pin Output Current (Vrestart = 0 V, Vref = 5.0 V)
TOTAL DEVICE
4
MOTOROLA ANALOG IC DEVICE DATA
MC33368
1.6
VCC = 14 V
TA = 25°C
1.4
VCS, CURRENT SENSE PIN 6 THRESHOLD (V)
VCS, CURRENT SENSE PIN 6 THRESHOLD (V)
Figure 1. Current Sense Input Threshold
versus Multiplier Input
VPin 4 = 4.0 V
= 3.75 V
= 3.0 V
1.2
= 3.5 V
1.0
= 2.75 V
= 3.25 V
0.8
= 2.5 V
0.6
0.4
= 2.25 V
0.2
= 2.0 V
0.6
1.4
2.2
3.0
0.08
= 3.0 V
0.06
= 2.75 V
0.05
0.04
= 2.5 V
0.03
0.02
= 2.25 V
0.01
= 2.0 V
0
–0.12
–0.06
0
0.06
0.12
0.20
VM, MULTIPLIER PIN 5 INPUT VOLTAGE (V)
Figure 3. Reference Voltage versus Temperature
Figure 4. Overvoltage Comparator Input
Threshold versus Temperature
16
VCC = 14 V
12
8.0
4.0
0
–4.0
–55
–25
0
25
50
75
100
125
TA, AMBIENT TEMPERATURE (°C)
110
VCC = 14 V
109
108
107
106
–55
30
60
60
Transconductance
0
–20
10
90
VCC = 14 V
VO = 2.0 to 4.0 V
RL = 10 kΩ
TA = 25°C
100
120
150
1.0 k
10 k
100 k
f, FREQUENCY (Hz)
MOTOROLA ANALOG IC DEVICE DATA
1.0 M
180
10 M
θ, EXCESS PHASE (DEGREES)
80
20
25
50
75
100
125
Figure 6. Error Amplifier Transient Response
Phase
40
0
6.0 V
0
100
–25
TA, AMBIENT TEMPERATURE (°C)
Figure 5. Error Amplifier Transconductance
and Phase versus Frequency
g m, TRANSCONDUCTANCE (µ mho)
VPin 4 = 4.0 V
0.07
VM, MULTIPLIER PIN 5 INPUT VOLTAGE (V)
VFB(OV), OVERVOLTAGE INPUT THRESHOLD (% VFB )
∆VFB , VOLTAGE FEEDBACK THRESHOLD
CHANGE (mV)
0
–0.2
Figure 2. Current Sense Input Threshold
versus Multiplier Input, Expanded View
VCC = 14 V
TA = 25°C
4.0 V
2.0 V
0V
–1.0 V
5.0 µs/DIV
5
MC33368
1.50
1.80
VCC = 14 V
Voltage
1.76
1.10
1.72
Current
1.68
1.64
–55
–25
0
25
50
75
100
0.90
0.70
125
500
VCC = 14 V
460
420
380
340
–55
–25
0
25
50
75
100
TA, AMBIENT TEMPERATURE (°C)
TA, AMBIENT TEMPERATURE (°C)
Figure 9. Drive Output Waveform
Figure 10. Supply Current versus
Supply Voltage
125
6.0
20
VCC = 14 V
CL = 1000 pF
TA = 25°C
15
OUTPUT VOLTAGE (V)
1.30
I chg, QUICKSTART CHARGE CURRENT (mA)
t DLY, WATCHDOG TIME DELAY ( µ s)
Figure 8. Watchdog Timer Delay
versus Temperature
I CC, SUPPLY CURRENT (mA)
Vchg, QUICKSTART CHARGE VOLTAGE (V)
Figure 7. Quickstart Charge Current
versus Temperature
10
5.0
0
Pulse tested with a 4.0 V peak, 50 kHz square
wave through a 22 k resistance into Pin 7.
4.0
2.0
0
2.0
–5.0
CO = 1000 pF
Pin 3, 6, 8= Gnd
Pin 5 = 1.0 k to Gnd
TA = 25°C
4.0
6.0
8.0
10
5.0 µs/DIV
VCC, SUPPLY VOLTAGE (V)
Figure 11. Transient Thermal Resistance
Figure 12. Low Load Detection
Response Waveform
12
14
1000
200
Output
Voltage
2.0
1.0
0
Load
Current
OUTPUT CURRENT (A)
OUTPUT VOLTAGE (V)
Rθ JA(t), THERMAL RESISTANCE
JUNCTION–TO–AIR (°C/W)
100
0
10
0.01
0.1
1.0
t, TIME (s)
6
3.0
400
10
100
200 ms/DIV
MOTOROLA ANALOG IC DEVICE DATA
MC33368
FUNCTIONAL DESCRIPTION
INTRODUCTION
With the goal of exceeding the requirements of legislation
on line current harmonic content, there is an ever increasing
demand for an economical method of obtaining a unity power
factor. This data sheet describes a monolithic control IC that
was specifically designed for power factor control with
minimal external components. It offers the designer a simple
cost effective solution to obtain the benefits of active power
factor correction.
Most electronic ballasts and switching power supplies use
a bridge rectifier and a bulk storage capacitor to derive raw dc
voltage from the utility ac line, Figure 13.
Figure 13. Uncorrected Power Factor Circuit
Converter
Rectifiers
Bulk
Storage
Capacitor
AC
Line
Load
This simple rectifying circuit draws power from the line
when the instantaneous ac voltage exceeds the capacitor
voltage. This occurs near the line voltage peak and results in
a high charge current spike, Figure 14. Since power is only
taken near the line voltage peaks, the resulting spikes of
current are extremely nonsinusoidal with a high content of
harmonics. This results in a poor power factor condition
where the apparent input power is much higher than the real
power. Power factor ratios of 0.5 to 0.7 are common.
Figure 14. Uncorrected Power Factor Input Waveforms
Vpk
Rectified
DC
0
Line Sag
AC Line
Voltage
0
AC Line
Current
Power factor correction can be achieved with the use of
either a passive or active input circuit. Passive circuits
usually contain a combination of large capacitors, inductors,
and rectifiers that operate at the ac line frequency. Active
circuits incorporate some form of a high frequency switching
converter for the power processing with the boost converter
MOTOROLA ANALOG IC DEVICE DATA
being the most popular topology. Since active input circuits
operate at a frequency much higher than that of the ac line,
they are smaller, lighter in weight, and more efficient than a
passive circuit that yields similar results. With proper control
of the preconverter, almost any complex load can be made to
appear resistive to the ac line, thus significantly reducing the
harmonic current content.
Operating Description
The MC33368 contains many of the building blocks and
protection features that are employed in modern high
performance current mode power supply controllers.
Referring to the block diagram in Figure 15, note that a
multiplier has been added to the current sense loop and that
this device does not contain an oscillator. A description of
each of the functional blocks is given below.
Error Amplifier
An Error Amplifier with access to the inverting input and
output is provided. The amplifier is a transconductance type,
meaning that it has high output impedance with controlled
voltage–to–current gain (gm 50 µmhos). The noninverting
input is internally biased at 5.0 V ±2.0%. The output voltage
of the power factor converter is typically divided down and
monitored by the inverting input. The maximum input bias
current is –1.0 µA which can cause an output voltage error
that is equal to the product of the input bias current and the
value of the upper divider resistor R2. The Error Amplifier
output is internally connected to the Multiplier and is pinned
out (Pin 4) for external loop compensation. Typically, the
bandwidth is set below 20 Hz so that the amplifier’s output
voltage is relatively constant over a given ac line cycle. In
effect, the error amplifier monitors the average output voltage
of the converter over several line cycles resulting in a fixed
Drive Output on–time. The amplifier output stage can sink
and source 11.5 µA of current and is capable of swinging
from 1.7 to 5.0 V, assuring that the Multiplier can be driven
over its entire dynamic range.
Note that by using a transconductance type amplifier, the
input is allowed to move independently with respect to the
output, since the compensation capacitor is connected to
ground. This allows dual usage of the Voltage Feedback pin
by the Error Amplifier and Overvoltage Comparator.
Overvoltage Comparator
An Overvoltage Comparator is incorporated to eliminate
the possibility of runaway output voltage. This condition can
occur during initial startup, sudden load removal, or during
output arcing and is the result of the low bandwidth that must
be used in the Error Amplifier control loop. The Overvoltage
Comparator monitors the peak output voltage of the
converter, and when exceeded, immediately terminates
MOSFET switching. The comparator threshold is internally
set to 1.08 Vref. In order to prevent false tripping during
normal operation, the value of the output filter capacitor C3
must be large enough to keep the peak–to–peak ripple less
than 16% of the average dc output.
7
MC33368
Multiplier
A single quadrant, two input multiplier is the critical
element that enables this device to control power factor. The
ac haversines are monitored at Pin 5 with respect to ground
while the Error Amplifier output at Pin 4 is monitored with
respect to the Voltage Feedback Input threshold. A graph of
the Multiplier transfer curve is shown in Figure 1. Note that
both inputs are extremely linear over a wide dynamic range,
0 to 3.2 V for Pin 5 and 2.5 to 4.0 V for Pin 4. The Multiplier
output controls the Current Sense Comparator threshold as
the ac voltage traverses sinusoidally from zero to peak line.
This has the effect of forcing the MOSFET on–time to track
the input line voltage, thus making the preconverter load
appear to be resistive.
Pin 6 Threshold
[ 0.55
ǒ
V
Pin 4
– V
Ǔ
Pin 3
V
Pin 5
Zero Current Detector
The MC33368 operates as a critical conduction current
mode controller, whereby output switch conduction is
initiated by the Zero Current Detector and terminated when
the peak inductor current reaches the threshold level
established by the Multiplier output. The Zero Current
Detector initiates the next on–time by setting the RS Latch at
the instant the inductor current reaches zero. This critical
conduction mode of operation has two significant benefits.
First, since the MOSFET cannot turn–on until the inductor
current reaches zero, the output rectifier’s reverse recovery
time becomes less critical allowing the use of an inexpensive
rectifier. Second, since there are no deadtime gaps between
cycles, the ac line current is continuous thus limiting the peak
switch to twice the average input current
The Zero Current Detector indirectly senses the inductor
current by monitoring when the auxiliary winding voltage falls
below 1.2 V. To prevent false tripping, 200 mV of hysteresis is
provided. The Zero Current Detector input is internally
protected by two clamps. The upper 10 V clamp prevents
input overvoltage breakdown while the lower –0.7 V clamp
prevents substrate injection. An external resistor must be
used in series with the auxiliary winding to limit the current
through the clamps to 5.0 mA or less.
Current Sense Comparator and RS Latch
The Current Sense Comparator RS Latch configuration
used ensures that only a single pulse appears at the Drive
Output during a given cycle. The inductor current is
converted to a voltage by inserting a ground–referenced
sense resistor R7 in series with the source of output switch.
This voltage is monitored by the Current Sense Input and
compared to a level derived from the Multiplier output. The
peak inductor current under normal operating conditions is
controlled by the threshold voltage of Pin 6 where:
Pin 6 Threshold
I
pk
R7
Abnormal operating conditions occur when the
preconverter is running at extremely low line or if output
voltage sensing is lost. Under these conditions, the Current
Sense Comparator threshold will be internally clamped to
1.5 V. Therefore, the maximum peak switch current is:
+
I
8
pk(max)
With the component values shown in Figure 15, the
Current Sense Comparator threshold, at the peak of the
haversine, varies from 110 mV at 90 Vac to 100 mV at
268 Vac. The Current Sense Input to Drive Output
propagation delay is typically 200 ns.
Timer
A watchdog timer function was added to the IC to
eliminate the need for an external oscillator when used in
stand alone applications. The Timer provides a means to
automatically start or restart the preconverter if the Drive
Output has been off for more than 385 µs after the inductor
current reaches zero.
Undervoltage Lockout and Quickstart
The MC33368 has a 5.0 V internal reference brought out
to Pin 1 and capable of sourcing 10 mA typically. It also
contains an Undervoltage Lockout (UVLO) circuit which
suppresses the Gate output at Pin 11 if the VCC supply
voltage drops below 8.5 V typical.
A Quickstart circuit has been incorporated to optimize
converter startup. During initial startup, compensation
capacitor C1 will be discharged, holding the Error Amplifier
output below the Multiplier’s threshold. This will prevent Drive
Output switching and delay bootstraping of capacitor C4 by
diode D6. If Pin 4 does not reach the multiplier threshold
before C4 discharges below the lower SMPS UVLO
threshold, the converter will hiccup and experience a
significant startup delay. The Quickstart circuit is designed to
precharge C1 to 1.7 V. This level is slightly below the Pin 4
Multiplier threshold, allowing immediate Drive Output
switching.
Restart Delay
A restart delay pin is provided to allow hiccup mode fault
protection in case of a short circuit condition and to prevent
the SMPS from repeatedly trying to restart after the input line
voltage has been removed. When power is first applied, there
is no startup delay, but subsequent cycling of the VCC voltage
will result in delay times that are programmed by an external
resistor and capacitor. The Restart Delay, Pin 2, is a high
impedance, so that an external capacitor can provide delay
times as long as several seconds.
If the SMPS output is short circuited, the transformer
winding, which provides the VCC voltage to the control IC and
the MC33368, will be unable to sustain VCC to the control
circuits. The restart delay capacitor at Pin 2 of the MC33368
prevents the high voltage startup transistor within the IC from
maintaining the voltage on C4. After VCC drops below the
UVLO threshold in the SMPS, the SMPS switching
transistors are held off for the time programmed by the values
of the restart capacitor (C9) and resistor (R8). In this manner,
the SMPS switching transistors are operated at very low duty
cyles, preventing their destruction. If the short circuit fault is
removed, the power supply system will turn on by itself in a
normal startup mode after the restart delay has timed out.
+ 1.5R7V
MOTOROLA ANALOG IC DEVICE DATA
MC33368
Output Switching Frequency Clamp
In normal operation, the MC33368 operates the boost
inductor in the critical mode. That is, the inductor current
ramps to a peak value, ramps down to zero, then immediately
begins ramping positive again. The peak current is
programmed by the multiplier output within the IC. As the
input voltage haversine declines to near zero, the output
switch on–time becomes constant, rather than going to zero
because of the small integrated dc voltage at Pin 5 caused by
C2, R3 and R5. Because of this, the average line current
does not exactly follow the line voltage near the zero
crossings. The Output Switching Frequency Clamp remedies
this situation to improve power factor and minimize EMI
generated in this operating region. The values of R10 and
C7, as shown in Figure 15, program a minimum off–time in
the frequency clamp which overrides the zero current detect
signal, forcing a minimum off–time. This allows discontinuous
conduction operation of the boost inductor in the zero
crossing region, and the average line current more nearly
follows the voltage. The Output Switching Frequency Clamp
function can be disabled by connecting the FC input, Pin 13,
to the VCC supply Pin 12.
For best results, the minimum off–time, determined by
the values of R10 and C7, should be chosen so that
MOTOROLA ANALOG IC DEVICE DATA
ts(min) = t(on) + t(off)fc. Output drive is inhibited when the
voltage at the frequency clamp input is less than 2.0 V. When
the output drive is high, C7 is discharged through an internal
100 µA current source. When the output drive switches low,
C7 is charged through R10. The drive output is inhibited until
the voltage across C7 reaches 2.0 V, establishing a minimim
off–time where:
t
(off)fc
+ * R10 C7 loge
ƪ ǒ Ǔƫ
1
*
2
V
CC
Output
The IC contains a CMOS output driver that was
specifically designed for direct drive of power MOSFETs. The
Gate Output is capable of up to ±1500 mA peak current with
a typical rise and fall time of 50 ns with a 1.0 nF load.
Additional internal circuitry has been added to keep the Gate
Output in a sinking mode whenever the Undervoltage
Lockout is active. This characteristic eliminates the need for
an external gate pull–down resistor. The totem–pole output
has been optimized to minimize cross–conduction current
during high speed operation.
9
MC33368
Table 1. Design Equations
Calculation
Formula
Notes
+ VO IO
2 Ǹ2 P
O
I
+
L(pk)
h Vac
Converter Output Power
P
Peak Indicator Current
ǒ
Inductance
L
P
+
t
Switch Off–Time
t
V
O –Vac
Ǹ2
t
Delay Time
t
+
h
V
+t
Peak Switch Current
R7
2
O
L
+
The off–time t(off) is greatest at the peak of the ac line
voltage and approaches zero at the ac line zero crossings.
Theta (θ) represents the angle of the ac line voltage.
–1
I
P L(pk)
ǒ Ǔ
V
O
V
– 2
CC
V
CC
) t(off)
V
Converter Output
Voltage
Converter Output
Peak–to–Peak
Ripple Voltage
Error Amplifier
Bandwidth
V
O
BW
Set the mulltiplier input voltage VM to 3.0 V at high line.
Empirically adjust VM for the lowest distortion over the ac
line voltage range while guaranteeing startup at minimum
line.
Vac
Ǹǒ
+ Vref
DV O(pp) + IL(pk)
Ǹ2
R5
)1
R3
ǒ Ǔ
ǒ )Ǔ
+
M
R2
R1
2
1 – I IB R1
p
Ǔ
1
f ac C3
+ 2 gpmC1
The delay time is used to override the minimum off–time at
the ac line zero crossings by programming the Frequency
Clamp with C7 and R10.
Set the current sense threshold VCS to 1.0 V for universal
input (85 to 265 Vac) operation and to 0.5 V for fixed input
(92 to 138 Vac, or 184 to 276 Vac) operation. Note that VCS
must be less than 1.4 V.
+ I VCS
L(pk)
Multiplier Input Voltage
The off–time is at a minimum at ac line crossings. This
equation is used to calculate t(off) as Theta approaches
zero.
The minimum switching frequency occurs at the peak of
the ac line voltage. As the ac line voltage traverses from
peak to zero, t(off) approaches zero producing an increase
in switching frequency.
1
(on)
Let the switching cycle t = 40 µs for universal input (85 to
265 Vac) operation and 20 µs for fixed input (92 to
138 Vac, or 184 to 276 Vac) operation.
In theory, the on–time t(on) is constant. In practice, t(on)
tends to increase at the ac line zero crossings due to the
charge on capacitor C5. Let Vac = Vac(LL) for initial t(on)
and t(off) calculations.
(on)
Ǹ 2 Vac ŤSin qŤ
min
(LL)
L
O P
Vac 2
+ – R10 C7 ln
d
f
Vac
2 P
t
(off)
Switching Frequency
h
(LL)
Ǹ 2 VO PO
(on)
+
(off)
Minimum Switch
Off–Time
Ǔ
Calculated at the minimum required ac line voltage for
output regulation. Let the efficiency η = 0.92 for low line
operation.
(LL)
Switch On–Time
t
Calculate the maximum required output power.
O
2
) ESR2
The IIB R1 error term can be minimized with a divider
current in excess of 100 µA.
The calculated peak–to–peak ripple must be less than 16%
of the average dc output voltage to prevent false tripping of
the Overvoltage Comparator. Refer to the Overvoltage
Comparator Text. ESR is the equivalent series resistance
of C3.
The bandwidth is typically set to 20 Hz. When operating at
high ac line, the value of C1 may need to be increased.
NOTE: The following converter characteristics must be chosen:
VO = Desired output voltage.
Vac(LL) = AC RMS minimum required operating line voltage for output regulation.
IO = Desired output current.
∆VO = Converter output peak–to–peak ripple voltage.
Vac = AC RMS operating line voltage.
10
MOTOROLA ANALOG IC DEVICE DATA
MC33368
Figure 15. 80 W Power Factor Controller
1N4006
D4
D2
EMI
Filter
92 to
270 Vrms
D1
C5
1.0
D3
16
Vref
Line
MC33368
Vref
D6
D8 R13
VCC 1N4744 51 1N4934
15 V
R8
10 k
RD
C9
330 µF
2
AGnd
UVLO
Q
8
Timer
R
RS Latch
R
R
S
S
Q
S
Set Dominant
1.5 V
12
Zero
Current
Detect
7 15 V
ZCD
1.2/1.0
T
R4
22 k
Gate
320 µH
MUR130
MTP8N50E
R2
470 k
10
Low
Load Detect
FC
9
Quickstart
LEB
6
Leading Edge
Blanking
CS
Mult
R7
0.1
0.25 W
5.0 V
Reference
5
C2
0.01
R10
10
C7
10 pF
13
Frequency
Clamp
1.08 x Vref
Multiplier
4
1
Comp
3
Vref
C1
0.68
FB
Vref
C6
0.1
VO
D5
C3
220
To VCC
Pin 12
PGnd
R5
1.3 M
Q1
R11
10
11
Overvoltage
Comparator
R3
20 k
C4
100
13/8.0
T: Coilcraft N2881–A
Primary = 62 turns of #22 AWG
Secondary = 5 turns of #22 AWG
Core = Coilcraft PT2510, EE25
Gap = 0.072″ total for a primary inductance (Lp) of 320 µH
R1
10 k
Not Used: D7, C8, R6, R9
Power Factor Controller Test Data
DC Output
AC Line Input
Vrms
Pin
PF
Ifund
Current Harmonic Distortion (% Ifund)
THD
2
3
5
7
VO(pp)
VO
IO
PO
n(%)
90
79.7
0.999
0.89
0.5
0.15
0.09
0.06
0.09
3.0
244.4
0.31
76.01
95.4
100
79.3
0.998
0.79
0.5
0.14
0.09
0.08
0.10
3.0
242.9
0.31
75.54
95.3
110
78.9
0.997
0.72
0.5
0.16
0.13
0.08
0.10
3.0
242.9
0.31
75.30
95.4
120
78.5
0.996
0.66
0.5
0.15
0.12
0.08
0.13
3.0
243.0
0.31
75.57
96.3
130
78.1
0.994
0.60
0.5
0.14
0.12
0.07
0.14
3.0
243.0
0.31
75.57
96.7
138
77.8
0.991
0.57
0.5
0.15
0.14
0.08
0.14
3.0
243.0
0.31
75.57
97.1
Heatsink = AAVID Engineering Inc., 590302B03600, or 593002B03400
MOTOROLA ANALOG IC DEVICE DATA
11
MC33368
Figure 16. 175 W Universal Input Power Factor Controller
1N5406
D2
EMI
Filter
92 to
270 Vrms
C5
1.0
D4
D1
D3
16
Vref
Line
MC33368
Vref
D8 R13
D6
VCC 1N4744 51 1N4934
15 V
R8
1.0 M
RD
C9
2.2
2
AGnd
UVLO
Q
8
Timer
R
RS Latch
R
R
S
S
Q
S
Set Dominant
1.5 V
12
Zero
Current
Detect
7 15 V
ZCD
R4
22 k
6.9 V
1.2/1.0
T
MUR460
Gate
R11
10
11
Overvoltage
Comparator
PGnd
R5
1.3 M
C3
330
To VCC
Pin 12
MTW20N50E
R2
820 k
13
Frequency
Clamp
1.08 x Vref
FC
9
Quickstart
LEB
6
Leading Edge
Blanking
CS
Mult
C2
0.01
R7
0.1
5.0 V
Reference
5
Multiplier
4
Comp
1
C1
2.2
3
Vref
FB
Vref
C6
0.1
VO
D5
Q1
10
Low
Load Detect
R3
10 k
C4
100
13/8.0
T: Coilcraft N2880–A
L = 870 µHy
Primary: 78 turns of #16 AWG
Secondary: 6 turns of #18 AWG
Core: Coilcraft PT4215, EE42–15
Gap: 0.104″ total
Not Used: D7, C7, C8, R6, R9, R10
R1
10 k
Power Factor Controller Test Data
DC Output
AC Line Input
Current Harmonic Distortion (% Ifund)
Vrms
90
Pin
PF
190.4 0.995
Ifund
THD
2
3
5
7
VO(pp)
VO
IO
PO
n(%)
2.11
5.8
0.16
0.32
0.24
0.80
3.6
398.0
0.44
175.9
92.4
120
192.1 0.997
1.60
3.2
0.08
0.17
0.07
0.30
3.6
398.9
0.44
177.1
92.2
138
192.7 0.997
1.40
0.9
0.08
0.24
0.03
0.15
3.6
402.3
0.45
179.0
92.9
180
194.3 0.995
1.08
0.9
0.04
0.18
0.04
0.08
3.6
409.1
0.45
182.9
94.1
240
189.3 0.983
0.80
0.7
0.08
0.21
0.08
0.06
3.6
407.0
0.45
181.1
95.7
268
186.3 0.972
0.71
0.6
0.11
0.32
0.10
0.10
3.6
406.2
0.44
180.4
96.8
Heatsink = AAVID Engineering Inc., 590302B03600
12
MOTOROLA ANALOG IC DEVICE DATA
MC33368
Figure 17. Power Factor Test Setup
Line
2X Step–up
Isolation
Autoformer Transformer
EMI Filter
AC Power
Analyzer
PM 1000
HI
W
115 Vrms
Input
VA
HI
T
PF Vrms Arms
0.1
A
V
VD Acf Ainst Freq HARM
1
0
L.O.
0 to 270 Vac
1.0 Output to
Power Factor
Correction
Circuit
L.O.
Neutral
Voltech
An RFI filter is required for best performance when connecting the preconverter directly to the ac line. The filter attenuates the level of high
frequency switching that appears on the ac line current waveform. Figures 15 and 16 work well with commercially available two stage filters such
as the Delta Electronics 03DPCG6. Shown above is a single stage test filter that can easily be constructed with four ac line rated capacitors and
a common–mode transformer. Coilcraft CMT3–28–2 was used to test Figures 15 and 16. It has a minimum inductance of 28 mH and a maximum
current rating of 2.0 A. Coilcraft CMT4–17–9 was used to test Figure 19. It has a minimum inductance of 17 mH and a maximum current rating of
9.0 A. Circuit conversion efficiency η (%) was calculated without the power loss of the RFI filter.
Figure 18. On/Off Control
D2
92 to
270 Vrms
EMI
Filter
D1
D4
C5
1.0
D3
Line
16
Vref
Vref
MC33368
R8
10 k
15 V
RD
C9
330 µF
UVLO
8
On/Off
Input
5.0 V
Off
0V
On
R
12
Zero
Current
Detect
13/8.0
RS Latch
R
R
S
S
Q
S
Set Dominant
1.5 V
1N4148
Timer
Q
2
AGnd
1.2/1.0
6.9 V
10
13
Leading Edge
Blanking
C1
22
1
VCC
Vref
C6
0.1
MTW14N50E
R2
820 k
R7
0.1
5.0 V
Reference
Comp
C3
330
CS
Mult
4
Q1
LEB
6
Quickstart
Multiplier
R11
10
DC
Out
D5
FC
9
1.08 x Vref
R3
10 k
T
PGnd
Frequency
Clamp
5
7 15 V
ZCD
R4
22 k
11
Low
Load Detect
C2
0.01
C4
100
Gate
Overvoltage
Comparator
R5
1.3 M
R13
51 D6
VCC D8
Vref
10 k
1.0 k
3
FB
R1
10 k
2N3904
1.0 k
MOTOROLA ANALOG IC DEVICE DATA
13
MC33368
Figure 19. 400 W Power Factor Controller
D2
1N5406
D4
D1
D3
EMI
Filter
92 to
270 Vac
C5
1.0
16
Vref
Vref
MC33368
R8
1.0 M
15 V
RD
C9
330 µF
Line
UVLO
Q
2
AGnd
8
Timer
R
1.5 V
12
Zero
Current
Detect
RS Latch
R
R
S
S
Q
S
Set Dominant
13/8.0
1.2/1.0
1.5 V
7 15 V
ZCD
R4
22 k
T
MUR460
D5
Q1
11
C3
330
R11
10
PGnd
R5
1.3 M
13
Frequency
Clamp
1.08 x Vref
R2
820 k
CS
Mult
5.0 V
Reference
5
Multiplier
4
Comp
C1
1.0
1
Vref
C6
0.1
C7
470 pF
LEB
6
Leading Edge
Blanking
C2
0.01
R10
10 k
FC
9
Quickstart
3
400 V
MTW20N50E
Vref
10
Low
Load Detect
14
1N4934
C4
100
Gate
Overvoltage
Comparator
R3
10.5 k
R13
51 D6
1N4744
VCC D8
R9
10
C8
0.001
R7
0.1
FB
Vref
R1
10 k
MOTOROLA ANALOG IC DEVICE DATA
MC33368
Figure 20. Printed Circuit Board and Component Layout
(Circuits of Figures 15 and 16)
D3
DC Output
C6
AC Input
D1
R3 C2
C5
D7
R5
R1
R2
R8
R6
C1
D2
R4
D6
IC1
C9
C7
J
C8
J
D4
R7
C4
ÎÎÎÎÎ
ÎÎÎÎÎ
ÎÎÎÎÎ
ÎÎÎÎÎ
ÎÎÎÎÎ
ÏÏÏ
ÎÎÎÎÎ
R13
R10
R11 J
J
R9
Transformer
D8
Q1
C3
S
D
G
D5
J = Jumper
(Top View)
4.5″
MC33368
3.0″
(Bottom View)
MOTOROLA ANALOG IC DEVICE DATA
15
MC33368
OUTLINE DIMENSIONS
P SUFFIX
PLASTIC PACKAGE
CASE 648–08
(DIP–16)
ISSUE R
–A–
16
9
1
8
NOTES:
1. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.
2. CONTROLLING DIMENSION: INCH.
3. DIMENSION L TO CENTER OF LEADS WHEN
FORMED PARALLEL.
4. DIMENSION B DOES NOT INCLUDE MOLD FLASH.
5. ROUNDED CORNERS OPTIONAL.
B
F
C
L
DIM
A
B
C
D
F
G
H
J
K
L
M
S
S
–T–
SEATING
PLANE
K
H
G
D
M
J
16 PL
0.25 (0.010)
T A
M
M
INCHES
MIN
MAX
0.740
0.770
0.250
0.270
0.145
0.175
0.015
0.021
0.040
0.70
0.100 BSC
0.050 BSC
0.008
0.015
0.110
0.130
0.295
0.305
0_
10 _
0.020
0.040
MILLIMETERS
MIN
MAX
18.80
19.55
6.35
6.85
3.69
4.44
0.39
0.53
1.02
1.77
2.54 BSC
1.27 BSC
0.21
0.38
2.80
3.30
7.50
7.74
0_
10 _
0.51
1.01
D SUFFIX
PLASTIC PACKAGE
CASE 751K–01
(SO–16)
ISSUE O
-A16
M
B
S
9
P
1
M_
0.25 (0.010)
-B-
F
8
G
R X 45 _
C
-TK
NOTES:
1 DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.
2 CONTROLLING DIMENSION: MILLIMETER.
3 DIMENSIONS A AND B DO NOT INCLUDE MOLD
PROTRUSION.
4 MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER
SIDE.
5 DIMENSION D DOES NOT INCLUDE DAMBAR
PROTRUSION. ALLOWABLE DAMBAR
PROTRUSION SHALL BE 0.127 (0.005) TOTAL IN
EXCESS OF THE D DIMENSION AT MAXIMUM
MATERIAL CONDITION.
D 14 PL
0.25 (0.010)
SEATING
PLANE
J
M
T A
S
B
S
DIM
A
B
C
D
F
G
J
K
M
P
R
MILLIMETERS
MIN
MAX
9.80
10.00
3.80
4.00
1.35
1.75
0.35
0.49
0.40
1.25
1.27 BSC
0.19
0.25
0.10
0.25
0_
7_
5.80
6.20
0.25
0.50
INCHES
MIN
MAX
0.368
0.393
0.150
0.157
0.054
0.068
0.014
0.019
0.016
0.049
0.050 BSC
0.008
0.009
0.004
0.009
0_
7_
0.229
0.244
0.010
0.019
Motorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty, representation or guarantee regarding
the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and
specifically disclaims any and all liability, including without limitation consequential or incidental damages. “Typical” parameters which may be provided in Motorola
data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals”
must be validated for each customer application by customer’s technical experts. Motorola does not convey any license under its patent rights nor the rights of
others. Motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other
applications intended to support or sustain life, or for any other application in which the failure of the Motorola product could create a situation where personal injury
or death may occur. Should Buyer purchase or use Motorola products for any such unintended or unauthorized application, Buyer shall indemnify and hold Motorola
and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees
arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that
Motorola was negligent regarding the design or manufacture of the part. Motorola and
are registered trademarks of Motorola, Inc. Motorola, Inc. is an Equal
Opportunity/Affirmative Action Employer.
Mfax is a trademark of Motorola, Inc.
How to reach us:
USA / EUROPE / Locations Not Listed: Motorola Literature Distribution;
P.O. Box 5405, Denver, Colorado 80217. 303–675–2140 or 1–800–441–2447
JAPAN: Nippon Motorola Ltd.; Tatsumi–SPD–JLDC, 6F Seibu–Butsuryu–Center,
3–14–2 Tatsumi Koto–Ku, Tokyo 135, Japan. 81–3–3521–8315
Mfax: [email protected] – TOUCHTONE 602–244–6609
INTERNET: http://www.mot.com/SPS/
ASIA/PACIFIC: Motorola Semiconductors H.K. Ltd.; 8B Tai Ping Industrial Park,
51 Ting Kok Road, Tai Po, N.T., Hong Kong. 852–26629298
16
◊
MC33368/D
MOTOROLA ANALOG IC DEVICE DATA