MAXIM MAX1717EVKIT

19-1636; Rev 0; 2/00
MAX1717 Evaluation Kit
This fully assembled and tested circuit board provides
a digitally adjustable 0.925V to 2V output voltage from a
7V to 24V battery input range. It delivers up to 12A output current with 14.1A peak current. The EV kit operates at 300kHz switching frequency and has superior
line- and load-transient response. Output slew-rate control minimizes battery and inductor surge currents. With
its precision timer circuit, the MAX1717’s output voltage
slew rate can be tailored to a given application, providing “just-in-time” arrival at the new DAC setting.
Ordering Information
PART
TEMP. RANGE
MAX1717EVKIT
0°C to +70°C
IC PACKAGE
24 QSOP
Features
♦ High Speed, Accuracy, and Efficiency
♦ Voltage-Positioned Output
♦ Lowest Output Capacitor Count (4)
♦ Reduces CPU Power Consumption
♦ Fast-Response Quick-PWM™ Architecture
♦ 7V to 24V Input Voltage Range
♦ 0.925V to 2V Output Voltage Range
♦ 12A Load-Current Capability (14.1A peak)
♦ Controlled Input Surge Current During Output
Transition
♦ 300kHz Switching Frequency
♦ No Current-Sense Resistor
♦ VGATE Power-Good/Transition-Complete Indicator
♦ 24-Pin QSOP Package
♦ Low-Profile Components
♦ Fully Assembled and Tested
Component List
DESIGNATION QTY
C1–C4, C20
5
C5, C6, C7
3
or
or
C5, C6, C7, C10
4
DESCRIPTION
10µF, 25V ceramic capacitors (1812)
Taiyo Yuden TMK432BJ106KM or
Tokin C34Y5U1E106Z
220µF, 2.5V, 15mΩ low-ESR
specialty polymer capacitors
Panasonic EEFUE0E221R
or
470µF, 6.3V, 30mΩ low-ESR
tantalum capacitors
Kemet T510X477M006AS
C8
1
10µF, 6.3V ceramic capacitor
Taiyo Yuden JMK325BJ106MN
C9
1
0.1µF ceramic capacitor (1206)
C11, C12
2
0.22µF ceramic capacitors (1206)
C13, C21, C22
0
Not installed
C14
1
470pF ceramic capacitor (1206)
C15
1
1µF ceramic capacitor (1206)
C17, C19, C23,
C24, C25
5
4700pF ceramic capacitors (0805)
DESIGNATION QTY
DESCRIPTION
C18
1
1000pF ceramic capacitor (0805)
D1
1
2A Schottky diode
International Rectifier 10MQ040 or
STMicroelectronics STPS2L25U
D2
1
100mA Schottky diode
Central Semiconductor CMPSH-3
D3
1
200mA switching diode
Central Semiconductor CMPD2838
J1
1
Scope-probe jack
Berg Electronics 33JR135-1
JUA0–JUA4,
JUB0–JUB4
10
2-pin headers
L1
1
1µH power inductor
Sumida CEP125-1R0MC or
Panasonic ETQP6F1R1BFA
N1
1
N-channel MOSFET (SO-8)
International Rectifier IRF7811 or
IRF 7811A
Pentium is a registered trademark of Intel Corp.
Quick-PWM is a trademark of Maxim Integrated Products.
________________________________________________________________ Maxim Integrated Products
1
For free samples and the latest literature, visit www.maxim-ic.com or phone 1-800-998-8800.
For small orders, phone 1-800-835-8769.
Evaluates: MAX1717
General Description
The MAX1717 evaluation kit (EV kit) demonstrates a
high-power, dynamically adjustable notebook CPU
application circuit. The MAX1717 DC-DC converter
steps down high-voltage batteries and/or AC adapters,
generating a precision, low-voltage CPU core VCC rail.
The MAX1717 EV kit meets the Intel mobile Pentium® III
CPU’s transient voltage specification by using voltage
positioning to minimize output capacitor requirements.
Evaluates: MAX1717
MAX1717 Evaluation Kit
Component List (continued)
DESIGNATION QTY
DESCRIPTION
N2, N3
2
N-channel MOSFETs (SO-8)
International Rectifier IRF7805 or
IRF 7811 or IRF 7811A
R1
1
20Ω ±5% resistor (0805)
R2–R6, R9, R10,
12
R22–R26
R11
R12
100kΩ ±5% resistors (0805)
SUPPLIER
PHONE
FAX
Central
Semiconductor
516-435-1110
516-435-1824
Dale-Vishay
402-564-3131
402-563-6418
International
Rectifier
310-322-3331
310-322-3332
Kemet
408-986-0424
408-986-1442
Panasonic
714-373-7939
714-373-7183
1
100Ω ±5% resistor (0805)
1
0.005Ω ±1%, 1W resistor (2512)
Dale WSL-2512-R005F
Sanyo
619-661-6322
619-661-1055
Sumida
847-956-0666
847-956-0702
R13
1
10kΩ ±5% resistor (0805)
Taiyo Yuden
408-573-4150
408-573-4159
R14
1
120kΩ ±5% resistor (0805)
Tokin
408-432-8020
408-434-0375
R15
1
20kΩ ±5% resistor (0805)
R16
1
300kΩ ±5% resistor (0805)
R17
1
200kΩ ±5% resistor (0805)
R18
1
24.9kΩ ±1% resistor (0805)
R19
1
27.4kΩ ±1% resistor (0805)
R20
1
2kΩ ±1% resistor (0805)
R21
1
160kΩ ±5% resistor (0805)
SW1
1
DIP-6 dip switch
U1
1
MAX1717EEG (24-pin QSOP)
None
10
Shunts
None
1
MAX1717 PC board
None
1
MAX1717 data sheet
None
1
MAX1717 EV kit data sheet
Recommended Equipment
• 7V to 24V, >20W power supply, battery, or notebook
AC adapter
• DC bias power supply, 5V at 100mA
• Dummy load capable of sinking 14.1A
• Digital multimeter (DMM)
• 100MHz dual-trace oscilloscope
Quick Start
1) Ensure that the circuit is connected correctly to the
supplies and dummy load prior to applying any
power.
2) Set switches SW1-A (SHDN), SW1-B (SKIP), and
SW1-C (A/B) to the on position. This configures the
EV kit for automatic pulse-skipping operation with the
internal mux in A mode. The DAC code settings
2
Component Suppliers
Note: Please indicate that you are using the MAX1717 when
contacting these component suppliers.
D4–D0 are set to a 1.35V output for the A-mode configuration through installed jumpers JUA4 and JUA1,
and to a 1.6V output for the B-mode configuration
through installed jumpers JUB0, JUB1, JUB2, and
JUB4.
3) Turn on the battery power before turning on the +5V
bias power; otherwise, the output UVLO timer will
time out and the FAULT latch will be set, disabling
the regulator until +5V power is cycled or shutdown
is toggled.
4) Observe the output with the DMM and/or oscilloscope. Look at the LX switching-node and MOSFET
gate-drive signals while varying the load current.
5) Toggle the A/B switch and observe the output voltage transition to the new 1.6V setting. Note: When
driving A/B with the dip switch, the transition may
take longer than expected due to switch bounce.
Detailed Description
This 12A buck-regulator design is optimized for a
300kHz frequency and output voltage settings around
1.35V to 1.6V. At lower output voltages, transient
response degrades slightly and efficiency worsens. At
higher output voltages (approaching 2V), output ripple
increases. At VOUT = 1.6V, inductor ripple is approximately 30%, with a resulting pulse-skipping threshold
at roughly ILOAD = 2A.
Setting the Output Voltage
The MAX1717 uses an internal 5-bit DAC as well as a
unique, proprietary, internal multiplexer that allows two
_______________________________________________________________________________________
MAX1717 Evaluation Kit
Evaluates: MAX1717
different 5-bit codes to be entered using only five pins.
The output voltage can be digitally set from 0.925V to
2V (Table 1). There are three different ways of setting
the output voltage:
• Drive the external VID0–VID4 inputs (no jumpers
installed). The output voltage can be set by driving
VID0–VID4 with open-drain drivers or 3V/5V CMOS
output logic levels (internal multiplexer must be in Amode configuration A/B = high).
• Install jumpers JUA0–JUA4 (A-mode configuration:
SW1-C ON, A/B = high). When JUA0–JUA4 are not
installed, the MAX1717’s D0–D4 inputs are at logic 1
(connected to VCC). When JUA0–JUA4 are installed,
D0–D4 inputs are at logic 0 (connected to GND). In
the A-mode configuration, the output voltage can be
changed during operation by installing and removing
jumpers JUA0–JUA4. As shipped, the EV kit is configured for operation in A mode with jumpers
JUA0–JUA4 set for a 1.35V output (Table 1).
• Install jumpers JUB0–JUB4 (B-mode configuration:
SW1-C OFF, A/B = low). When JUB0–JUB4 are not
installed, a 100kΩ resistor is in series with each of
the D0–D4 inputs, making them a logic 1 in B mode.
When JUB0–JUB4 are installed, the 100kΩ resistors
are shorted, making D0–D4 logic 0 in B mode. As
shipped, the EV kit is configured for operation in B
mode with jumpers JUB0–JUB4 set for 1.6V output
(Table 1). While in the B-mode configuration, the output voltage cannot be changed. A/B, SHDN, or
VBIAS must be cycled to reread the B-mode setting.
Refer to the MAX1717 data sheet for more information.
Table 1. MAX1717 Output Voltage
Adjustment Settings
D4
JUA4
JUB4
D3
JUA3
JUB3
D2
JUA2
JUB2
D1
JUA1
JUB1
D0
JUA0
JUB0
0
0
0
0
0
2
0
0
0
0
1
1.95
0
0
0
1
0
1.90
0
0
0
1
1
1.85
0
0
1
0
0
1.80
0
0
1
0
1
1.75
0
0
1
1
0
1.70
0
0
1
1
1
1.65
0
1
0
0
0
1.60
0
1
0
0
1
1.55
0
1
0
1
0
1.50
0
1
0
1
1
1.45
0
1
1
0
0
1.40
0
1
1
0
1
1.35
0
1
1
1
0
1.30
0
1
1
1
1
Shutdown
1
0
0
0
0
1.275
1
0
0
0
1
1.250
1
0
0
1
0
1.225
1
0
0
1
1
1.200
1
0
1
0
0
1.175
Voltage Positioning
1
0
1
0
1
1.150
The MAX1717 EV kit meets the Intel Mobile Pentium III
CPU’s transient voltage specification by using voltage
positioning to minimize output capacitor requirements.
The output voltage is initially set slightly high (1.25%),
then allowed to regulate lower as the load current
increases. R20 and R21 set the initial output voltage
23mV high, and R12 (5mΩ) causes the output voltage
to drop with increasing load (60mV or about 4% of 1.6V
at 12A).
Setting the output voltage high allows a larger step
down when the output current suddenly increases.
Regulating at the lower output voltage under load
allows a larger step up when the output current suddenly decreases. Allowing a larger step size means
that the output capacitance can be reduced and the
capacitor’s ESR can be increased. If voltage positioning
is not used, one additional output capacitor is required
to meet the same transient specification.
1
0
1
1
0
1.125
1
0
1
1
1
1.100
1
1
0
0
0
1.075
1
1
0
0
1
1.050
1
1
0
1
0
1.025
1
1
0
1
1
1.000
1
1
1
0
0
0.975
1
1
1
0
1
0.950
1
1
1
1
0
0.925
1
1
1
1
1
Shutdown
OUTPUT
VOLTAGE (V)
Note: Shunts installed on jumpers JUA0–JUA4, JUB0–JUB4 =
logic 0.
An additional benefit of voltage positioning is reduced
power consumption at high load currents. Because the
output voltage is lower under load, the CPU draws less
current. The result is lower power dissipation in the
CPU, though some extra power is dissipated in R12. For
_______________________________________________________________________________________
3
Evaluates: MAX1717
MAX1717 Evaluation Kit
a nominal 1.6V, 12A output, reducing the output voltage
2.6% (1.4% - 4%) gives an output voltage of 1.56V and
an output current of 11.69A. Given these values, CPU
power consumption is reduced from 19.2W to 18.23W.
The additional power consumption of R12 is 0.68W, and
the overall power savings is as follows:
19.2 – (18.23 + 0.68) = 0.3W
In effect, 1W of CPU dissipation is saved and the power
supply dissipates much of the savings, but both the net
savings and the transfer of dissipation away from the
hot CPU are beneficial.
Efficiency Measurements and
Effective Efficiency
Testing the power conversion efficiency (POUT/PIN)
fairly and accurately requires more careful instrumentation
than might be expected. One common error is to use
inaccurate DMMs. Another is to use only one DMM and
move it from one location to another to measure the
various input/output voltages and currents. This second
error usually results in changing the exact conditions
applied to the circuit due to series resistance in the
ammeters. It’s best to use four 3-1/2 digit or better
DMMs that have been recently calibrated and monitor
V BATT , V OUT , I BATT , and I LOAD simultaneously.
Connect the VBATT and VOUT meters directly across
the input and output capacitors. Note that it’s inaccurate to test efficiency at the remote VOUT and GND terminals, as this incorporates the parasitic resistance of
the PC board output and ground buses in the measurement (a significant power loss).
Remember to include the power consumed by the +5V
bias supply when making efficiency calculations:
V
× I
OUT
LOAD
Efficiency =
V
× I
+ 5V × I
(
BATT
BATT
) (
BIAS
)
Efficiency performance is greatly impacted by the
choice of MOSFET. The International Rectifier
MOSFETs used in this kit were of leading-edge performance for 12A applications at the time the kit was
designed. However, considering the rapid pace of
MOSFET improvement, the latest offerings should be
evaluated.
4
After obtaining the actual, accurate efficiency data, there
is still some work remaining before an accurate assessment of a voltage-positioned circuit can be made. As discussed in the Voltage Positioning section, a voltage-positioned power supply can dissipate additional power while
reducing overall system power consumption. For this reason, we use the concept of effective efficiency, which
allows the direct comparison of a positioned and nonpositioned circuit’s efficiency. Effective efficiency is defined
as the efficiency required of a nonvoltage-positioned circuit to equal the total dissipation of a voltage-positioned
circuit for a given CPU operating condition.
Calculate effective efficiency as follows:
1) Start with the efficiency data for the positioned circuit
(VIN, IIN, VOUT, IOUT).
2) Calculate the load resistance for each VOUT, IOUT
data point:
RLOAD = VOUT / IOUT
3) Calculate the output current that would exist for each
RLOAD data point in a nonpositioned application:
INP = VNP / RLOAD
where VNP = 1.6V (in this example).
4) Calculate effective efficiency as:
Effective efficiency = (VNP × INP) / (VIN × IIN) = calculated nonpositioned power output divided by the
measured voltage-positioned power input.
5) Plot the efficiency data point at the current INP.
The effective efficiency of the voltage-positioned circuit
will be less than that of the nonpositioned circuit at light
loads (where the voltage-positioned output voltage is
higher than the nonpositioned output voltage) and
greater than that of the nonpositioned circuit at heavy
loads (where the voltage-positioned output voltage is
lower than the nonpositioned output voltage).
Dynamic Output Voltage
Transition Experiment
Observe the output voltage transition between 1.35V
and 1.6V by toggling the SW1-C (A/B) position between
on and off. This EV kit is set to transition the output voltage at 3.75mV/µs. The speed of the transition can be
altered by changing resistor R14 (120kΩ). You may
observe longer-than-expected transitions due to switch
bounce (SW1). To eliminate switch bounce, set SW1-C
(A/B) to the off position, and drive the A/B pad with a
function generator.
During the voltage transition, watch the inductor current
by looking across R12 with a differential scope probe or
_______________________________________________________________________________________
MAX1717 Evaluation Kit
There are two other methods to create an output voltage transition. Select A mode by setting the A/B switch
to the on position (SW1-C). Then either manually
change the JUA0–JUA4 jumpers to a new VID code
setting (Table 1), or remove all JUA0–JUA4 jumpers
and drive the VID0–VID4 PC board test points externally to the desired code settings.
Load-Transient Experiment
One interesting experiment is to subject the output to
large, fast load transients and observe the output with
an oscilloscope. This requires careful instrumentation of
the output using the supplied scope-probe jack.
Accurate measurement of output ripple and load-transient
response invariably requires that ground clip leads be
completely avoided and that the probe hat be removed
to expose the GND shield, so the probe can be
plugged directly into the jack. Otherwise, EMI and
noise pickup will corrupt the waveforms.
Most benchtop electronic loads intended for powersupply testing lack the ability to subject the DC-DC
converter to ultra-fast load transients. Emulating the
supply current di/dt at the CPU VCORE pins requires at
least 10A/µs load transients. One easy method for generating such an abusive load transient is to solder a
MOSFET, such as an MTP3055 or 12N05, directly
across the scope-probe jack. Then drive its gate with a
strong pulse generator at a low duty cycle (≤10%) to
minimize heat stress in the MOSFET. Adjust the highlevel output voltage of the pulse generator to vary the
load current. Alternatively, control the load current with
a load resistor in series with the MOSFET’s drain, and
drive the MOSFET fully on. Remember to include the
expected on-resistance of the MOSFET in the load
resistor calculation.
To determine the load current, you might expect to
insert a meter in the load path, but this method is prohibited here by the need for low resistance and inductance
in the path of the dummy load MOSFET. There are two
easy alternative methods of determining how much
load current a particular pulse-generator amplitude is
causing. The first and best is to observe the inductor
current with a calibrated AC current probe, such as a
Tektronix AM503. In the buck topology, the load current
is equal to the average value of the inductor current.
The second method is to measure the input current
while using a static dummy load of the desired value.
Then, connect the MOSFET dummy load at 100% duty
momentarily, and adjust the gate-drive signal until the
battery current rises to the appropriate level (the MOSFET
load must be well heatsinked for this to work without
causing smoke and flames).
Table 2. Switch SW1-A/SW1-B Functions
(SHDN, SKIP)
SW1-A SW1-B
Off
X
CONNECTION
EFFECT
SKP/SDN connected
to GND through R15
and R17.
Shutdown mode,
VOUT = 0.
On
On
SKP/SDN connected
to VCC through R15.
Output enabled. SKIP
mode operation.
Allows automatic
PWM/PFM switchover
for pulse skipping at
light load for highest
efficiency.
—
Off
SKP/SDN connected
to +2V through R15
and divider
R16/R17.
Output enabled. Lownoise mode. Forced
fixed-frequency PWM
operation.
Table 3. Switch SW1-C Functions (A/B)
SW1-C
CONNECTION
MAX1717 OUTPUT
On
A/B connected
to VCC
Internal VID multiplexer set to A mode.
Off
A/B connected
to GND
Internal VID multiplexer set to B mode.
_______________________________________________________________________________________
5
Evaluates: MAX1717
by inserting a current probe in series with the inductor.
Observe the low, well-controlled inductor current that
accompanies the voltage transition. The same slew rate
and controlled inductor current are used during shutdown and startup, resulting in well-controlled currents
into and out of the battery (input source).
Evaluates: MAX1717
MAX1717 Evaluation Kit
Table 4. Jumpers JU3/JU4/JU5 Functions (Switching-Frequency Selection)
SHUNT LOCATION SHUNT LOCATION
JU3
TON PIN
FREQUENCY
(kHz)
JU4
JU5
Installed
Not Installed
Not Installed
Connected to VCC
Not Installed
Installed
Not Installed
Connected to REF
550
Not Installed
Not Installed
Installed
Connected to GND
1000
Not Installed
Not Installed
Not Installed
Floating
300
200
IMPORTANT: Don’t change the operating frequency without first recalculating component values. The frequency has a significant
effect on the peak current-limit level, MOSFET heating, preferred inductor value, PFM/PWM switchover point, output noise, efficiency,
and other critical parameters.
Table 5. Jumper JU6 Functions (Fixed/Adjustable Current-Limit Selection)
SHUNT POSITION
ILIM PIN
CURRENT-LIMIT THRESHOLD
On
Connected to VCC
100mV
Off
Connected to midpoint of external resistordivider R18/R19. Refer to the Pin Description in
the MAX1717 data sheet for more information
(see Current Limit section).
Adjustable from 50mV to 300mV.
Table 6. Troubleshooting Guide
SYMPTOM
Circuit won’t start when power
is applied.
SOLUTION
Power-supply sequencing: +5V bias supply
was applied first.
Cycle SW1-A (SHDN).
Output overvoltage due to shorted high-side
MOSFET.
Replace the MOSFET.
Output overvoltage due to load recovery
above 2.25V.
Reduce the inductor value, raise the switching
frequency, or add more output capacitance.
Output overload condition.
Remove excessive load.
Broken connection, bad MOSFET, or other
catastrophic problem.
Troubleshoot the power stage. Are the DH and
DL gate-drive signals present? Is the 2V VREF
present?
VBATT power source has poor impedance
characteristic.
Add a bulk electrolytic bypass capacitor
across the benchtop power supply, or substitute
a real battery.
Excessive EMI, poor efficiency
at high input voltages.
Gate-drain capacitance of N2 is causing
shoot-through cross-conduction.
Observe the gate-source voltage of N2 during
the low-to-high LX node transition (this requires
careful instrumentation). Is the gate voltage
being pulled above 1.5V, causing N2 to turn on?
Use a smaller low-side MOSFET or add a BST
resistor (R7).
Poor efficiency at high input
voltages, N1 gets hot.
N1 has excessive gate capacitance.
Use a smaller high-side MOSFET or add more
heatsinking.
Circuit won’t start when RESET
is pressed, +5V bias supply
cycled.
On-time pulses are erratic or
exhibit unexpected changes
in period.
6
POSSIBLE PROBLEM
_______________________________________________________________________________________
SW1-A
"SHDN"
REF
2V
R17
200k
R16
300k
VCC
A/B
4
2
5
JU6
JU3
200k
SW1-B
"SKIP"
SW1-C
1 "A/B" 3
6
MAX1717EV KIT SCHEMATIC
(CONTINUES ON NEXT PAGE)
GND
VBATT
R18
24.9k
1%
JU4
550kHz
C14
470pF
R8
SHORT
R14
120k
TP1
R13
10k
JU5
1MHz
R19
27.4k
1%
10
8
9
6
3
2
16
21
20
19
18
FLOAT = 300kHz
C12
0.22µF
R15
20k
R10
100k
D0
D1
D2
D3
D4
17
ILIM
TON
REF
CC
TIME
U1
R1
20Ω
MAX1717
VCC
VCC
SKP/SDN
A/B
D0
D1
D2
D3
D4
C11
0.22µF
VGATE
GNDS
FBS
FB
GND
DL
LX
DH
BST
VDD V+
VDD
12
11
5
4
13
14
23
24
22
1
C1
10µF
25V
JU8
R4
100k
R21
160k
VCC
C18
1000pF
C9
0.1µF
R7
SHORT
VBATT
C2
10µF
25V
JU9
VCC
4
C15
1µF
R11
100Ω
VDD
C4
10µF
25V
N2
1
2
6
5
VGATE
3
7
REF
R20
2k 1%
4
8
D2
CMPSH-3
C3
10µF
25V
8
3
7
8
3
7
4
C20
10µF
25V
N3
1
2
6
5
N1
1
2
6
5
L1
1µH
FBS
D1
C21
OPEN
C22
OPEN
R12
0.005Ω
C5
470µF
6.3V
C6
470µF
6.3V
C7
470µF
6.3V
D3
CMPD2838
C10
470µF
6.3V
+5V
VBIAS
C13
OPEN
C8
10µF
6.3V
JI - PROBE
SCOPE JACK
VOUT
Evaluates: MAX1717
7V TO 24V
MAX1717 Evaluation Kit
Figure 1. MAX1717 EV Kit Schematic
_______________________________________________________________________________________
7
Evaluates: MAX1717
MAX1717 Evaluation Kit
VCC
R26
100k
JUB4
C25
4700pF
D4
VID4
R2
100k
VCC
JUA4
R25
100k
C24
4700pF
JUB3
R3
100k
VID3
D3
JUA3
VCC
R24
100k
JUB2
C23
4700pF
R5
100k
D2
VID2
JUA2
VCC
R23
100k
JUB1
C19
4700pF
R6
100k
VID1
D1
JUA1
VCC
R22
100k
JUB0
C17
4700pF
R9
100k
D0
VID0
JUA0
Figure 1. MAX1717 EV Kit Schematic (continued)
8
_______________________________________________________________________________________
MAX1717 Evaluation Kit
Evaluates: MAX1717
1.0"
Figure 2. MAX1717 EV Kit Component Placement Guide—
Component Side
1.0"
Figure 4. MAX1717 EV Kit PC Board Layout—Component Side
1.0"
Figure 3. MAX1717 EV Kit Component Placement Guide—
Solder Side
1.0"
Figure 5. MAX1717 EV Kit PC Board Layout—Ground Plane
(Layer 2)
_______________________________________________________________________________________
9
Evaluates: MAX1717
MAX1717 Evaluation Kit
1.0"
Figure 6. MAX1717 EV Kit PC Board Layout—Ground Plane
(Layer 3)
10
1.0"
Figure 7. MAX1717 EV Kit PC Board Layout—Solder Side
______________________________________________________________________________________
MAX1717 Evaluation Kit
Evaluates: MAX1717
NOTES
______________________________________________________________________________________
11
Evaluates: MAX1717
MAX1717 Evaluation Kit
NOTES
Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are
implied. Maxim reserves the right to change the circuitry and specifications without notice at any time.
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© 2000 Maxim Integrated Products
Printed USA
is a registered trademark of Maxim Integrated Products.