19-3211; Rev 0; 1/08 8-String White LED Driver with SMBus for LCD Panel Applications The MAX17061 is a high-efficiency driver for white lightemitting diodes (LEDs). It is designed for large liquidcrystal displays (LCDs) that employ an array of LEDs as the light source. An internal switch current-mode step-up controller drives the LED array, which can be configured for up to eight strings in parallel and 10 LEDs per string. Each string is terminated with ballast that achieves ±1.5% current-regulation accuracy between strings, ensuring even LED brightness. The MAX17061 has a wide inputvoltage range from 4.5V to 26V, and provides a fixed 25mA or adjustable 15mA to 30mA full-scale LED current. The MAX17061 internally generates a DPWM signal for accurate WLED dimming control. The DPWM frequency is resistor programmable, while DPWM duty cycle is controlled directly from an external PWM signal or through a control word through the MAX17061’s SMBus™ interface. This DPWM control provides a dimming range with 8-bit resolution and supports Intel display-power-saving technology (DPST) to maximize battery life. The MAX17061 has multiple features to protect the controller from fault conditions. Separate feedback loops limit the output voltage under any circumstance, ensuring safe operation. Once an open string is detected, the string is disabled while other strings operate normally. The MAX17061 also features short LED detection. The shorted strings are also disabled after a 2ms fault blanking interval. The controller features cycle-bycycle current limit to provide stable operation and softstart capability. If the MAX17061 is in current-limit condition, the step-up converter is latched off after an internal timer expires. A thermal-shutdown circuit provides another level of protection. The MAX17061’s step-up controller features an internal 150mΩ (typ), 45V (max) power MOSFET with local current-sense amplifier for accurate cycle-by-cycle current limit. This architecture greatly simplifies the external circuitry and saves PCB space. Low-feedback voltage at each LED string 625mV (typ) at 25mA LED current helps reduce power loss and improve efficiency. The MAX17061 features selectable switching frequency (500kHz, 750kHz, or 1MHz), which enables a wide variety of applications that can trade off component size for operating frequency. The MAX17061 is available in a thermally enhanced 28-pin, 4mm x 4mm Thin QFN package. Applications Notebook, Subnotebook, and Tablet Computer Displays Automotive Systems Handy Terminals Features o Accurate Dimming Control Using SMBus, PWM Interface o Dimming Range with 8-Bit Resolution o Adjustable DPWM Frequency with 1.5% Accuracy o Up to Eight Parallel Strings Multiple SeriesConnected LEDs o ±1.5% Current Regulation Accuracy Between Strings o Low String Feedback Voltage: 625mV at 25mA LED Current o Full-Scale LED Current Adjustable from 15mA to 30mA, or Preset 25mA o Open and Short LED Protections o Output Overvoltage Protection o 0.15Ω Internal HV Power MOSFET (45V max) o Wide Input-Voltage Range from 4.5V to 26V o 500kHz/750kHz/1MHz Selectable Switching Frequency o Small 28-Pin, 4mm x 4mm, Thin QFN package Ordering Information PART TEMP RANGE PIN-PACKAGE -40oC to +85oC 28 Thin QFN (4mm x 4mm) MAX17061ETI+ +Denotes a lead-free package. Simplified Operating Circuit L1 D1 VOUT VIN VDD IN VCC ISET LX1, 2 PGND1, 2 R1 OV CCV R2 MAX17061 PWM PWMI PWMO FB1 FB2 GND N.C. CLK DATA FB3 OSC FB4 SCL FB5 FB6 SDA FB7 FSET FB8 EP Pin Configuration appears at end of data sheet. SMBus is a trademark of Intel Corp. ________________________________________________________________ Maxim Integrated Products For pricing, delivery, and ordering information, please contact Maxim Direct at 1-888-629-4642, or visit Maxim’s website at www.maxim-ic.com. 1 MAX17061 General Description MAX17061 8-String White LED Driver with SMBus for LCD Panel Applications ABSOLUTE MAXIMUM RATINGS Continuous Power Dissipation (TA = +70°C) 28-Pin Thin QFN (derate 16.9mW/°C above +70°C)...1667mW Operating Temperature Range ...........................-40°C to +85°C Junction Temperature ......................................................+150°C Storage Temperature Range .............................-60°C to +150°C Lead Temperature (soldering, 10s) .................................+300°C IN to GND ..............................................................-0.3V to +28V FB_, LX_ to GND ....................................................-0.3V to +45V PGND_ to GND......................................................-0.3V to +0.3V VCC, VDD, PWMI, SDA, SCL to GND ........................-0.3V to +6V ISET, CCV, PWMO, FSET, OSC, OV to GND ................................................-0.3V to VCC + 0.3V Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. ELECTRICAL CHARACTERISTICS (Circuit of Figure 1, VIN = 12V, CCCV = 0.022µF, RCCV = 5.1kΩ, VISET = VOSC = VDD = VCC, RFSET = 464kΩ, VPWMI = GND, TA = 0°C to +85°C, unless otherwise noted. Typical values are at TA = +25°C.) PARAMETER IN Input Voltage Range CONDITIONS TYP MAX VIN = VCC 4.5 5.5 VCC = open 5.5 26.0 VIN = 26V IN Quiescent Current MAX17061 is enabled at minimum brightness, no load IN Quiescent Current MAX17061 is disabled, VIN = 12V VCC Output Voltage MIN 1.24 VIN = VCC = 5V UNITS V 2 mA 10 µA MAX17061 is enabled, 6V < VIN < 26V, 0 < IVCC < 10mA 4.7 5.0 5.3 MAX17061 is disabled, VIN = 12V 3.90 4.35 4.80 15 40 70 mA 4.00 4.25 4.45 V 0.15 0.3 Ω VCC Current Limit VCC is forced to 4.5V VCC UVLO Threshold Rising edge, typical hysteresis = 85mV V BOOST CONVERTER LX On-Resistance LX Leakage Current Operating Frequency 20mA from LX_ to PGND 1 µA VOSC = VCC 45V on LX_ 0.9 1.0 1.1 MHz VOSC = open 675 750 825 VOSC = GND 450 500 550 VCC 0.4 OSC High-Level Threshold OSC Midlevel Threshold V 1.5 OSC Low-Level Threshold Minimum Duty Cycle PWM mode (Note 1) 10 Pulse skipping, no load (Note 1) 0 Maximum Duty Cycle LX Current Limit 94.0 Duty cycle = 75% (Note 1) kHz 95.5 VCC 2.0 V 0.4 V % 97.0 % 1.6 A 2.1 V CONTROL INPUT SDA, SCL Logic Input-High Level SDA, SCL Logic Input-Low Level PWMI Logic Input-High Level 0.8 2.1 PWMI Logic Input-Low Level 2 _______________________________________________________________________________________ V V 0.8 V 8-String White LED Driver with SMBus for LCD Panel Applications (Circuit of Figure 1, VIN = 12V, CCCV = 0.022µF, RCCV = 5.1kΩ, VISET = VOSC = VDD = VCC, RFSET = 464kΩ, VPWMI = GND, TA = 0°C to +85°C, unless otherwise noted. Typical values are at TA = +25°C.) PARAMETER CONDITIONS MIN TYP MAX UNITS +0.3 µA +1 µA -0.1 +0.1 µA -1 +1 INPUT LEAKAGE PWMI Leakage Current ISET, FSET Leakage Current -0.3 ISET , FSET to VCC OV Leakage Current SDA, SCL Input Bias Current SDA Output Low-Sink Current VSDA = 0.4V OSC Leakage Current 4 µA mA -3 +3 µA LED CURRENT Full-Scale FB_ Output Current ISET = VCC 24.5 25.0 25.5 RISET = 133kΩ 28.8 30.0 31.2 RISET = 200kΩ 19.3 20.0 20.7 RISET = 266kΩ 14.4 15.0 15.6 VCC 0.4 ISET High-Level Threshold ISET Output Voltage Current Regulation Between Strings Minimum FB_ Regulation Voltage V 1.166 -1.5 1.236 1.306 +1.5 IFB_ = 25mA 475 625 910 IFB_ = 30mA 575 750 1100 IFB_ = 20mA 380 500 740 IFB_ = 15mA 285 375 560 Full brightness mA V % mV Maximum FB_ Ripple IFB_ = 20mA (COUT = 1µF, VOSC = VCC) (Note1) 120 200 mVP/P FB_ On-Resistance VFB_ = 50mV (includes 10Ω sense resistor) 17.5 28.4 Ω FB_ Leakage Current VFB_ = 26V, TA = +25°C 1 VFB_ = 45V, TA = +25°C 2.5 4 1.236 1.306 µA FAULT PROTECTION OV Threshold Voltage Rising edge, typical hysteresis = 60mV FB_ Overvoltage Threshold VIN > 5.5V 1.166 V 5.2 5.6 6.0 V FB_ Undervoltage Threshold 130 175 220 mV OV Undervoltage Threshold (Boost Global Fail) 48 84 120 mV Thermal-Shutdown Threshold (Note 1) Overcurrent FAULT Shutdown Timer IPEAK > 3.3A at duty = 0% 88 160 128 168 °C µs FB_ Overvoltage Fault Timer Full brightness 1.7 2 2.3 ms _______________________________________________________________________________________ 3 MAX17061 ELECTRICAL CHARACTERISTICS (continued) MAX17061 8-String White LED Driver with SMBus for LCD Panel Applications ELECTRICAL CHARACTERISTICS (continued) (Circuit of Figure 1, VIN = 12V, CCCV = 0.022µF, RCCV = 5.1kΩ, VISET = VOSC = VDD = VCC, RFSET = 464kΩ, VPWMI = GND, TA = 0°C to +85°C, unless otherwise noted. Typical values are at TA = +25°C.) PARAMETER CONDITIONS MIN TYP MAX UNITS kΩ PWM FILTER PWM Output Impedance DPWM Oscillator Frequency 20 40 60 RFSET = 464kΩ 197 200 203 RFSET = 113kΩ 750 785 820 RFSET = 65kΩ 1.270 1.335 1.400 RFSET = 42kΩ 2 PWMI Input-Frequency Range 5 10 PWMI Full-Range Accuracy PWMI Brightness Setting Hz kHz 100 kHz 5 LSB % PWMI duty cycle = 100% 98 PWMI duty cycle = 50% 48 100 50 52 PWMI duty cycle = 0% 2.6 2.7 2.8 SMBus TIMING SPECIFICATION SMBus Frequency FSMB 10 Bus Free Time TBUF 4.7 100 kHz µs START Condition Hold Time from SCL THD:STA 4 µs START Condition Setup Time from SCL TSU:STA 4.7 µs STOP Condition Setup Time from SCL TSU:STO 4 µs SDA Hold Time from SCL THD:DAT 300 ns SDA Setup Time from SCL TSU:DAT 250 ns SCL Low Period TLOW 4.7 µs SCL High Period THIGH 4 µs ELECTRICAL CHARACTERISTICS (Circuit of Figure 1, VIN = 12V, CCCV = 0.022µF, RCCV = 5.1kΩ, VISET = VOSC = VDD = VCC, RFSET = 464kΩ, VPWMI = GND, TA = -40°C to +85°C, unless otherwise noted. Typical values are at TA = +25°C.) (Note 2) PARAMETER IN Input Voltage Range IN Quiescent Current CONDITIONS MIN TYP 4.5 5.5 VCC = open 5.5 26.0 MAX17061 is enabled at minimum brightness, no load VIN = 26V 2 VIN = VCC = 5V 2 MAX17061 is disabled, VIN = 12V VCC Output Voltage 10 MAX17061 is enabled, 6V < VIN < 26V, 0 < IVCC < 10mA 4.7 5.3 MAX17061 is disabled, VIN = 12V 3.9 4.8 VCC Current Limit VCC is forced to 4.5V VCC UVLO Threshold Rising edge, typical hysteresis = 85mV 4 MAX VIN = VCC UNITS V mA µA V 12 70 mA 4.00 4.45 V _______________________________________________________________________________________ 8-String White LED Driver with SMBus for LCD Panel Applications (Circuit of Figure 1, VIN = 12V, CCCV = 0.022µF, RCCV = 5.1kΩ, VISET = VOSC = VDD = VCC, RFSET = 464kΩ, VPWMI = GND, TA = -40°C to +85°C, unless otherwise noted. Typical values are at TA = +25°C.) (Note 2) PARAMETER CONDITIONS MIN TYP MAX UNITS BOOST CONVERTER LX On-Resistance 20mA from LX_ to PGND LX Leakage Current 45V on LX_ Operating Frequency Ω 1 µA VOSC = VCC 0.89 1.10 MHz VOSC = open 675 825 kHz VOSC = GND 450 VCC 0.4 560 kHz OSC High-Level Threshold OSC Midlevel Threshold 1.5 OSC Low-Level Threshold Maximum Duty Cycle LX Current Limit 0.3 94 Duty cycle = 75% V VCC 2.0 0.4 97 1.6 V V % A CONTROL INPUT SDA, SCL Logic Input-High Level 2.1 SDA, SCL Logic Input-Low Level V 0.8 PWMI Logic Input-High Level 2.1 PWMI Logic Input-Low Level V V 0.8 V -0.3 +0.3 µA +1 µA -0.1 +0.1 µA -1 +1 INPUT LEAKAGE PWMI Leakage Current ISET, FSET Leakage Current ISET , FSET to VCC OV Leakage Current SDA, SCL Input Bias Current SDA Output-Low Sink Current VSDA = 0.4V OSC Leakage Current 4 µA mA -3 +3 µA ISET = VCC 24.5 25.5 RISET = 133kΩ 28.6 31.4 RISET = 200kΩ 19.0 21.0 RISET = 266kΩ 14.3 VCC 0.4 1.166 15.7 1.306 V Full brightness -1.5 +1.5 % IFB_ = 25mA 425 910 IFB_ = 30mA 575 1100 IFB_ = 20mA 380 740 IFB_ = 15mA 285 560 LED CURRENT Full-Scale FB_ Output Current ISET High-Level Threshold ISET Output Voltage Current Regulation Between Strings Minimum FB_ Regulation Voltage mA V mV Maximum FB_ Ripple IFB_ = 20mA (COUT = 1µF, VOSC = VCC) 200 mVP/P FB_ On-Resistance VFB_ = 50mV (includes 10Ω sense resistor) 28.4 Ω _______________________________________________________________________________________ 5 MAX17061 ELECTRICAL CHARACTERISTICS (continued) MAX17061 8-String White LED Driver with SMBus for LCD Panel Applications ELECTRICAL CHARACTERISTICS (continued) (Circuit of Figure 1, VIN = 12V, CCCV = 0.022µF, RCCV = 5.1kΩ, VISET = VOSC = VDD = VCC, RFSET = 464kΩ, VPWMI = GND, TA = -40°C to +85°C, unless otherwise noted. Typical values are at TA = +25°C.) (Note 2) PARAMETER CONDITIONS MIN TYP MAX UNITS FAULT PROTECTION OV Threshold Voltage 1.166 1.306 V FB_ Overvoltage Threshold 5.2 6.0 V FB_ Undervoltage Threshold 130 220 mV OV Undervoltage Threshold (Boost Global Fail) 48 120 mV 88 168 µs 1.6 2.4 ms Overcurrent FAULT Shutdown Timer Rising edge, typical hysteresis = 60mV IPEAK > 3.3A at duty = 0% FB_ Overvoltage Fault Timer PWM FILTER PWM Output Impedance DPWM Oscillator Frequency 20 60 kΩ RFSET = 464kΩ 197 203 kHz RFSET = 113kΩ 750 820 Hz RFSET = 65kΩ 1.27 1.40 kHz 5 100 kHz 5 LSB % PWMI Input Frequency Range PWMI Full-Range Accuracy PWMI duty cycle = 100% PWMI Brightness Setting 98 PWMI duty cycle = 50% 48 52 PWMI duty cycle = 0% 2.6 2.8 100 SMBus TIMING SPECIFICATION SMBus Frequency FSMB 10 Bus Free Time TBUF 4.7 kHz µs START Condition Hold Time from SCL THD:STA 4 µs START Condition Setup Time from SCL TSU:STA 4.7 µs STOP Condition Setup Time from SCL TSU:STO 4 µs SDA Hold Time from SCL THD:DAT 300 ns SDA Setup Time from SCL TSU:DAT 250 ns SCL Low Period TLOW 4.7 µs SCL High Period THIGH 4 µs Note 1: Specifications are guaranteed by design, not production tested. Note 2: Specifications to -40°C are guaranteed by design, not production tested. 6 _______________________________________________________________________________________ 8-String White LED Driver with SMBus for LCD Panel Applications 20 15 10 86 10 13 16 19 0 50 INPUT VOLTAGE (V) 100 150 200 0 250 20 25.8 25.6 30 25 LED CURRENT (mA) 25.4 25.2 25.0 24.8 24.6 60 80 100 LED CURRENT vs. INPUT VOLTAGE MAX17061 toc04 26.0 40 PWMI DUTY CYCLE (%) SMBus BRIGHTNESS SETTING LED CURRENT vs. AMBIENT TEMPERATURE (BRIGHTNESS = 100%) LED CURRENT (mA) SMBus = 128 10 0 0 24.4 SMBus = 0xFF 20 15 10 5 SMBus = 0x1F 24.2 24.0 0 40 60 80 AMBIENT TEMPERATURE (°C) 11 14 INPUT VOLTAGE (V) SUPPLY CURRENT vs. INPUT VOLTAGE SHUTDOWN CURRENT vs. INPUT VOLTAGE 5 5 4 SMBus = 255 3 2 1 8 17 20 10 MAX17061 toc07 20 SHUTDOWN CURRENT (μA) 0 MAX17061 toc06 7 15 5 5 85 SMBus = 255 20 MAX17061 toc05 87 25 LED CURRENT (mA) 25 LED CURRENT (mA) 88 30 MAX17061 toc02 30 MAX17061 toc01 89 SUPPLY CURRENT (mA) BOOST CONVERTER EFFICIENCY (%) 90 LED CURRENT vs. PWMI DUTY CYCLE LED CURRENT vs. SMBus BRIGHTNESS SETTING MAX17061 toc03 BOOST CONVERTER EFFICIENCY vs. INPUT VOLTAGE (BRIGHTNESS = 100%) 8 6 4 2 SMBus = 0 0 0 5 8 11 14 INPUT VOLTAGE (V) 17 20 5 8 11 14 INPUT VOLTAGE (V) 17 20 _______________________________________________________________________________________ 7 MAX17061 Typical Operating Characteristics (Circuit of Figure 1, VIN = 12V, CCCV = 0.022µF, RCCV = 5.1kΩ, VISET = VOSC = VDD = VCC, RFSET = 464kΩ, VPWMI = GND, LEDs = 10 series x 4 parallel strings, TA = +25°C, unless otherwise noted.) MAX17061 8-String White LED Driver with SMBus for LCD Panel Applications Typical Operating Characteristics (continued) (Circuit of Figure 1, VIN = 12V, CCCV = 0.022µF, RCCV = 5.1kΩ, VISET = VOSC = VDD = VCC, RFSET = 464kΩ, VPWMI = GND, LEDs = 10 series x 4 parallel strings, TA = +25°C, unless otherwise noted.) SWITCHING WAVEFORMS (VIN = 7V, BRIGHTNESS = 100%) SWITCHING WAVEFORMS (VIN = 20V, BRIGHTNESS = 100%) MAX17061 toc08 MAX17061 toc09 VLX 20V/div VLX 20V/div 0V 0V IL 200mA/div IL 200mA/div 0mA 0mA 1μs/div 1μs/div STARTUP WAVEFORMS (BRIGHTNESS = 100%) STARTUP WAVEFORMS (SMBus = 0x04) MAX17061 toc10 MAX17061 toc11 VLX 20V/div 0V IL 1A/div 0A VLX 20V/div 0V IL 1A/div 0A VOUT 20V/div 0V VOUT 20V/div 0V VCCV 2V/div 0V VCCV 2V/div 0V 400μs/div 400μs/div LED CURRENT WAVEFORMS (SMBus = 0x80) LED CURRENT WAVEFORMS (SMBus = 0x04) MAX17061 toc12 MAX17061 toc13 VFB1 10V/div 0V VFB1 10V/div 0V ILED 20mA/div 0mA ILED 20mA/div 0mA IL 500mA/div 0mA IL 500mA/div 0mA VOUT 20V/div 0V 0V 2ms/div 8 VOUT 20V/div 2ms/div _______________________________________________________________________________________ 8-String White LED Driver with SMBus for LCD Panel Applications LED-OPEN FAULT PROTECTION (BRIGHTNESS = 100%, LED OPEN ON FB1) LED-SHORT FAULT PROTECTION (BRT = 100%, 2 LEDs SHORT ON FB1) MAX17061 toc14 MAX17061 toc15 VFB1 1V/div VFB1 5V/div 0V IFB2 10V/div 0V VFB2 10V/div 0V 0V VOUT 20V/div IFB1 20mA/div 0V 0mA IFB2 20mA/div 0mA IFB2 20mA/div 0mA 400μs/div 1ms/div LINE TRANSIENT RESPONSE (VIN = 12V→19V, BRIGHTNESS = 100%) LINE TRANSIENT RESPONSE (VIN = 19V→12V, BRIGHTNESS = 100%) MAX17061 toc16 MAX17061 toc17 VOUT 20V/div VOUT 20V/div 0V 0V VIN 10V/div 0V VIN 10V/div 0V IL 1A/div IL 1A/div 0A 0A IFB1 20mA/div IFB1 20mA/div 0mA 0mA 100μs/div 100μs/div LED CURRENT BALANCE vs. INPUT VOLTAGE MAX17061 toc18 LED CURRENT BALANCE (%) 1.0 0.6 0.2 -0.2 -0.6 -1.0 5 8 11 14 INPUT VOLTAGE (V) 17 20 _______________________________________________________________________________________ 9 MAX17061 Typical Operating Characteristics (continued) (Circuit of Figure 1, VIN = 12V, CCCV = 0.022µF, RCCV = 5.1kΩ, VISET = VOSC = VDD = VCC, RFSET = 464kΩ, VPWMI = GND, LEDs = 10 series x 4 parallel strings, TA = +25°C, unless otherwise noted.) MAX17061 8-String White LED Driver with SMBus for LCD Panel Applications Pin Description PIN NAME FUNCTION 1 FB3 LED String 3 Cathode Connection. FB3 is the open-drain output of an internal regulator, which controls current through FB3. FB3 can sink up to 30mA. If unused, connect FB3 to VCC. 2 FB4 LED String 4 Cathode Connection. FB4 is the open-drain output of an internal regulator, which controls current through FB4. FB4 can sink up to 30mA. If unused, connect FB4 to VCC. 3 GND Analog Ground 4, 6, 18 N.C. No Connection 5 FB5 LED String 5 Cathode Connection. FB5 is the open-drain output of an internal regulator, which controls current through FB5. FB5 can sink up to 30mA. If unused, connect FB5 to VCC. 7 FB6 LED String 6 Cathode Connection. FB6 is the open-drain output of an internal regulator, which controls current through FB6. FB6 can sink up to 30mA. If unused, connect FB6 to VCC. 8 FB7 LED String 7 Cathode Connection. FB7 is the open-drain output of an internal regulator, which controls current through FB7. FB7 can sink up to 30mA. If unused, connect FB7 to VCC. 9 FB8 LED String 8 Cathode Connection. FB8 is the open-drain output of an internal regulator, which controls current through FB8. FB8 can sink up to 30mA. If unused, connect FB8 to VCC. 10 OSC Oscillator Frequency-Selection Pin. Connect OSC to VCC to set the step-up converter’s oscillator frequency to 1MHz. Connect OSC to GND to set the frequency to 500kHz. Float OSC to set the frequency to 750kHz. 11 PWMI PWM Signal Input. This PWM signal is used for brightness control in PWM mode or DPST mode. This signal is filtered and its duty cycle is converted into a digital signal to calculate DPWM duty cycle. In PWM mode, the DPWM duty cycle equals the input PWM duty cycle. In DPST mode, the DPWM duty cycle is the input PWM duty cycle multiplied by the SMBus brightness command. 12 PWMO Filtered PWM Signal Output. Connect a capacitor between PWMO and GND. The capacitor forms a lowpass filter with an internal 40kΩ (typ) resistor to filter the PWM signal into an analog signal whose level represents the duty-cycle information of the input PWM signal. DPWM Frequency Adjustment Pin. Connect a resistor from FSET to GND to set the internal DPWM frequency: 13 fDPWM = FSET 109 α × R[Ω] + γ where: α = 10.638 γ = 58509 This DPWM signal directly chops WLED current with the calculated duty cycle for brightness control. 10 14 SDA SMBus Serial-Data Input 15 SCL SMBus Serial-Clock Input 16 LX2 Boost Regulator Internal MOSFET Drain. Connect the inductor and the Schottky diode to LX2 node. LX2 should always be shorted to LX1 externally. 17 LX1 Boost Regulator Internal MOSFET Drain. Connect the inductor and the Schottky diode to LX1 node. LX1 should always be shorted to LX2 externally. 19 PGND2 Boost Regulator Power Ground 20 PGND1 Boost Regulator Power Ground 21 IN Supply Input, 4.5V to 26V. VIN biases the internal 5V linear regulator that powers the device. Bypass IN to GND directly at the pin with a 0.1µF or greater ceramic capacitor. ______________________________________________________________________________________ 8-String White LED Driver with SMBus for LCD Panel Applications PIN NAME 22 VDD Boost Regulator MOSFET Gate Drive Supply. Bypass VDD to GND with a ceramic capacitor of 1µF or greater. 23 VCC 5V Linear Regulator Output. VCC provides power to the MAX17061. Bypass VCC to GND with a ceramic capacitor of 1µF or greater. If VIN is less than or equal to 5.5V, tie VCC to IN to disable internal LDO and use external 5V supply to VCC. 24 CCV Step-Up Converter Compensation Pin. Connect a 0.022µF ceramic capacitor and 5.1kΩ resistor from CCV to GND. When the MAX17061 shuts down, CCV is discharged to 0V through an internal 20kΩ resistor. 25 OV 26 ISET FUNCTION Overvoltage Sense. Connect OV to the center tap of a resistive voltage-divider from VOUT to ground. The detection threshold for voltage limiting at OV is 1.236V (typ). Full-Scale LED Current Adjustment Pin. The resistance from ISET to GND controls the full-scale current in each LED string: ILEDMAX = 20mA x 200kΩ/RISET The acceptable resistance range is 133kΩ < RISET < 266kΩ, which corresponds to full-scale LED current of 30mA > ILEDMAX > 15mA. Connect ISET to VCC for a default full-scale LED current of 25mA. 27 FB1 LED String 1 Cathode Connection. FB1 is the open-drain output of an internal regulator, which controls current through FB1. FB1 can sink up to 30mA. If unused, connect FB1 to VCC. 28 FB2 LED String 2 Cathode Connection. FB2 is the open-drain output of an internal regulator, which controls current through FB2. FB2 can sink up to 30mA. If unused, connect FB2 to VCC. — EP Exposed Backside Pad. Solder to the circuit board ground plane with sufficient copper connection to ensure low thermal resistance. See the PCB Layout Guidelines section. Detailed Description The MAX17061 is a high-efficiency driver for arrays of white LEDs. It contains a fixed-frequency currentmode PWM step-up controller, a 5V linear regulator, dimming control circuit, SMBus interface, internal power MOSFET, and eight regulated current sources (see Figure 2). When enabled, the step-up controller boosts the output voltage to provide sufficient headroom for the current sources to regulate their respective string currents. The MAX17061 features selectable switching frequency (500kHz, 750kHz, or 1MHz), which allows trade-offs between external component size and operating efficiency. The control architecture automatically skips pulses at light loads to improve efficiency and prevents overcharging the output capacitor. WLED brightness is controlled by turning the WLEDs on and off with a DPWM signal. The DPWM frequency can be accurately adjusted with a resistor. The brightness of the LEDs is proportional to the duty cycle of the DPWM signal, which is controlled externally through either a PWM or 2-wire SMBus-compatible interface, or both. When both interfaces are used at the same time, the product of the PWM duty cycle and SMBus command value is used for the dimming control. This DPWM control scheme provides a full dimming range with 8-bit resolution. The MAX17061 has multiple features to protect the controller from fault conditions. Separate feedback loops limit the output voltage in all circumstances. The MAX17061 checks each FB_ voltage during the operation. If one or more strings are open, the corresponding FB_ voltages are pulled below 175mV (typ), and open-circuit fault is detected. As a result, the respective current sources are disabled. When one or more LEDs are shorted and the FB_ voltage exceeds 1.1 x VCC, short fault is detected and the respective current source is disabled. In either LED open or short conditions, the fault strings are disabled while other strings can still operate normally. The controller features cycle-by-cycle current limit to provide stable operation and soft-start protection. In a currentlimit condition, the controller shuts down after a 128µs overcurrent fault timer expires. A thermal-shutdown circuit provides another level of protection. ______________________________________________________________________________________ 11 MAX17061 Pin Description (continued) MAX17061 8-String White LED Driver with SMBus for LCD Panel Applications The MAX17061 includes a 5V linear regulator that provides the internal bias and gate drive for the step-up controller. When an external 5V is available, the internal LDO can be overdriven to decrease power dissipation. Otherwise, connect the IN pin to an input greater than 5.5V. When the input voltage is close to the output voltage, the MAX17061 automatically skips pulses to prevent overcharging the output capacitor. In SKIP mode, the inductor current ramps up for a minimum on-time of approximately 90ns, and then discharges the stored energy to the output. The switch remains off until another pulse is needed to boost the output voltage. Fixed-Frequency Step-Up Controller The MAX17061’s fixed-frequency, current-mode, stepup controller automatically chooses the lowest active FB_ voltage to regulate the output voltage. Specifically, the difference between the lowest FB_ voltage and the current-source control signal plus an offset (VSAT) is integrated at the CCV output. The resulting error signal is compared to the external switch current plus slope compensation to determine the switch on-time. As the load changes, the error amplifier sources or sinks current to the CCV output to deliver the required peakinductor current. The slope-compensation signal is added to the current-sense signal to improve stability at high duty cycles. Internal 5V Linear Regulator VCC and UVLO The MAX17061 includes an internal low-dropout linear regulator (VCC). When VIN is higher than 5.5V, this linear regulator generates a 5V supply to power internal PWM controller, control logic, and MOSFET driver. The VCC voltage drops to 4.35V in shutdown. If VIN is less than or equal to 5.5V, VCC and IN can be tied together and powered from an external 5V supply. There is an internal diode from VCC to IN, so VIN must be greater than VCC (see Figure 3). L1 10μH VIN 7V TO 21V D1 4.7μF 2μF 0.1μF VDD VCC OSC ISET 1μF COUT IN LX1 LX2 PGND1 PGND2 FSET 5.1kΩ CCV 464kΩ R1 2.21MΩ MAX17061 OV 220pF 0.022μF PWM VOUT UP TO 45V R2 61.9kΩ PWMI PWMO FB1 1μF FB2 FB3 FB4 CLK SCL DATA SDA FB5 FB6 VCC FB7 GND FB8 EP Figure 1. Typical Operating Circuit 12 ______________________________________________________________________________________ 8-String White LED Driver with SMBus for LCD Panel Applications IN 1.236V ERROR COMPARATOR 5V LINEAR REGULATOR MAX17061 OUTPUT OVERVOLTAGE COMPARATOR MAX17061 OV VDD LX1, 2 VCC CONTROL AND DRIVER LOGIC CLOCK PGND1, 2 VCC SLOPE COMPENSATION OSCILLATOR OSC 3-LEVEL COMPARATOR CURRENT SENSE FB OVERVOLTAGE COMPARATOR VCC + 0.6V OV FAULT FB8 FB7 FB6 HVC FB5 FB4 ERROR AMPLIFIER FB3 gm CCV ISET LVC FB2 VSAT REF ADJ FB1 REF EN 8-BIT D/A FSET 10Ω DPWM SIGNAL GENERATOR DPWM SETTING PWMO A PWMI MUX "< = 1" D MUX "1" PWM_SEL DIMMING BLOCK DIAGRAM WLED ON/OFF CURRENT SOURCE GND CURRENT SOURCE FB2 CURRENT SOURCE FB3 CURRENT SOURCE FB4 CURRENT SOURCE FB5 CURRENT SOURCE FB6 CURRENT SOURCE FB7 CURRENT SOURCE FB8 PWM_MD 0x03 SDA SCL 0x02 0x01 SMBus INTERFACE 0x00 Figure 2. Control Circuit Block Diagram ______________________________________________________________________________________ 13 MAX17061 8-String White LED Driver with SMBus for LCD Panel Applications The MAX17061 includes power-on reset (POR) and undervoltage lockout (UVLO) features. POR resets the fault latch and sets all the SMBus registers to their POR values. POR occurs when VCC rises above 2.8V (typ). The controller is disabled until VCC exceeds the UVLO threshold of 4.25V (typ). Hysteresis on UVLO is approximately 85mV. The VCC and VDD pins should be bypassed to GND with a minimum 1µF ceramic capacitor. voltage is higher than 3V (typ), the string is considered to be unused. Unused strings should be tied to VCC. In the second phase, each FB_ is precharged by an internal 400µA (typ) current source. If a given FB_ voltage remains lower than 1V (typ), the FB_ is considered to be a short to GND and the device is disabled. After the LED string diagnostic phases are finished, the boost converter starts. The total startup time is less than 10ms, including 4.2ms (typ) soft-start. Shutdown Startup The MAX17061 can be placed into shutdown by clearing bit 0 of the device control register (0x01). When a critical failure is detected, the IC also enters shutdown mode. In shutdown mode, all functions of the IC are turned off including the 5V linear regulator. Only a crude linear regulator remains on, providing a 4.35V (typ) output voltage to VCC, with 1µA current-sourcing capability. The fault/status register is not reset in shutdown. When bit 0 of the device control register (0x01) is set to 1, the MAX17061 exits shutdown mode and starts. The fault/status register is reset at startup. At startup, the MAX17061 checks the OV pin to see if the Schottky diode is open. If the OV voltage is lower than 84mV (typ), the boost converter does not start. After the OV test is done, the MAX17061 performs a diagnostic test of the LED array. The test is divided to two phases; each phase takes approximately 1.024ms. In the first test phase, all FB_ inputs are quickly discharged down to 5.6V (typ) and then continuously discharged by 800µA (typ) current sources. If a given FB_ voltage remains higher than 5.6V (typ), the string is considered to be shorted. Otherwise, if a given FB_ L1 2.2μH VIN 2.8V TO 5.5V 4.7μF D1 2μF 0.1μF EXTERNAL 5V SUPPLY VDD VCC OSC ISET 1μF IN LX1 LX2 PGND1 PGND2 FSET R1 2.21MΩ 5.1kΩ CCV 464kΩ MAX17061 OV 220pF 0.022μF PWM VOUT UP TO 45V R2 61.9kΩ PWMI PWMO FB1 1μF FB2 FB3 FB4 CLK SCL DATA SDA FB5 FB6 VCC FB7 GND EP FB8 Figure 3. Low-Input-Voltage Application Circuit 14 ______________________________________________________________________________________ 8-String White LED Driver with SMBus for LCD Panel Applications OSC PIN CONNECTION SWITCHING FREQUENCY (kHz) GND 500 Open 750 VCC 1000 Frequency Selection A tri-level OSC input sets the internal oscillator frequency for step-up converter, as shown in Table 1. High-frequency (1MHz) operation optimizes the regulator for the smallest component size, at the expense of efficiency due to increased switching losses. Low-frequency (500kHz) operation offers the best overall efficiency but requires larger components and PCB area. Overvoltage Protection To protect the step-up converter when the load is open, or the output voltage becomes excessive for any reason, the MAX17061 features a dedicated overvoltage feedback input (OV). The OV pin is tied to the center tap of a resistive voltage-divider from the high-voltage output. When the OV pin voltage, V OV , exceeds 1.236V, a comparator turns off the internal power MOSFET. This step-up converter switch is reenabled after the VOV drops 60mV (typ) hysteresis below the protection threshold. This overvoltage-protection feature ensures the step-up converter fail-safe operation when the LED strings are disconnected from the output. LED Current Sources Maintaining uniform LED brightness and dimming capability are critical for LCD backlight applications. The MAX17061 is equipped with a bank of eight matched current sources. These specialized current sources are accurate to within ±1.5% between strings and can be switched on and off within 15µs, enabling PWM frequencies of up to 2kHz. All LED full-scale currents are identical and are set through the ISET pin (15mA < ILED < 30mA). When ISET is connected to VCC, the LED fullscale current is set at the 25mA default value. The minimum voltage drop across each current source is approximately 625mV when the LED current is 25mA. The low-voltage drop helps reduce dissipation while maintaining sufficient compliance to control the LED current within the required tolerances. The LED current sources can be disabled by tying the respective FB_ pin to VCC at startup. When the IC is powered up, the controller scans settings for all FB_ pins. If a FB_ pin is not tied to VCC, an internal circuit pulls this pin low, and the controller enables the corresponding current source to regulate the string current. If the FB_ pin is tied to VCC, the controller disables the corresponding current regulator. The current regulator cannot be disabled by connecting the respective FB_ pin to VCC after the IC is powered up. All FB_ pins in use are combined to extract a lowest FB_ voltage (LVC) (see Figure 2). LVC is fed into the step-up converter’s error amplifier and is used to set the output voltage. Current-Source Fault Protection The MAX17061 performs a diagnostic test at startup. Open/short strings are disabled. LED fault open/short is also detected after startup. When one or more strings fails after startup, the corresponding current sources are disabled. The remaining LED strings still operate normally. When a fault is detected, bit 4 or/and bit 5 of the fault/status resister are set (see the Fault/Status Register section). Open-Current Source Protection The MAX17061 step-up converter output voltage is regulated according to the minimum FB_ voltages on all the strings in use. If one or more strings are open, the respective FB_ pins are pulled to ground. For any FB_ lower than 175mV, the corresponding current source is disabled. The unaffected LED strings still operate normally. If all strings in use are open, the MAX17061 shuts down the step-up converter. The MAX17061 can tolerate A slight mismatch (4.4V) between LED strings. When severe mismatches (> 4.4V) or WLED shorts occur, the FB_ voltages will be uneven because mismatched voltage drops across strings. If a given FB_ voltage is higher than 5.6V (typ) after 24µs blanking time when LEDs are turned on, an LED short condition is detected on the respective string. When the short continues for greater than 2ms, the string is disabled. The controller allows the unaffected LED strings to operate normally. The LED shortprotection feature is disabled during the soft-start phase of the step-up converter. Dimming Control The MAX17061 internally generates a DPWM signal for accurate WLED brightness dimming control. The DPWM frequency is adjustable through an external setting resistor and has 1.5% accuracy for RFSET = 464kΩ. The duty cycle of this DPWM signal can be controlled externally through two interfaces: PWM and SMBus. The ISET pin sets the amplitude of the current sources for each LED string (Figure 4). The internal DPWM signal directly controls the duty cycle of these current sources. The resulting current is chopped and synchronized to the DPWM signal. When filtered by the slow response time of the human eye, the overall brightness is modulated in a consistent flicker-free manner. ______________________________________________________________________________________ 15 MAX17061 Table 1. Frequency Selection MAX17061 8-String White LED Driver with SMBus for LCD Panel Applications D= tON tDPWM DPWM DIMMING MODE DPWM D = 6.25% D = 12.5% D = 30% D = 50% tON tDPWM ILEDMAX ILED 0A Figure 4. LED Current Control by DPWM Signal in Dimming Full-Scale LED Brightness in DPWM Dimming Control The full-scale LED current in the DPWM dimming is determined by resistance from the ISET pin to ground: 20mA × 200kΩ ILEDMAX = RISET The acceptable resistance range is 133kΩ < RISET < 266kΩ, which corresponds to full-scale LED current of 30mA > ILEDMAX > 15mA. Connect ISET to VCC for a default full-scale LED current of 25mA. The current source output is pulse-width modulated and synchronized with a DPWM signal to reduce jitter and flicker noise in the display. DPWM Frequency Setting The MAX17061 uses an internal DPWM signal to perform dimming control. The DPWM frequency is specified by an external resistor connected from FSET pin to GND: 109 fDPWM = α × R[Ω] + γ where: α = 10.638 γ = 58509 The adjustable range for the FSET resistor, RFSET, is from 42kΩ to 464kΩ, corresponding to the DPWM frequency of 200Hz to 2kHz. 16 PWMO BUFFER A PWMI DIGITAL MULTIPLIER <=1 D 1 MUX SMBus AND PWM INPUT BLOCK PWM_MD IDENTIFICATION REGISTER 0x03 SDA SCL FAULT/STATUS REGISTER 0x02 DPWM SETTING MUX DEVICE CONTROL REGISTER 0x01 PWM_SEL BACKLIGHT ON/OFF BRIGHTNESS CONTROL REGISTER 0x00 SMBus INTERFACE Figure 5. MAX17061 PWM and SMBus Interface Circuit Dimming Control Interfaces The MAX17061’s dimming control circuit consists of two interfaces: PWM and SMBus. The block diagram of these two input interfaces is shown in Figure 5. The dimming can be performed in three modes: PWM, SMBus, or DPST. In PWM mode, the brightness is adjusted by the PWM signal applied to the PWMI pin. In SMBus mode, the brightness is adjusted by an I 2C command from uplink processor through the 2-wire SMBus. In DPST mode, the brightness is adjusted by the product of the PWM duty cycle and SMBus command value. This DPWM control provides a dimming range with 8-bit resolution down to 2.7% and supports Intel DPST to maximize battery life. ______________________________________________________________________________________ 8-String White LED Driver with SMBus for LCD Panel Applications The MAX17061 uses two multiplexers internally to direct the dimming signal processing (Figure 5). These two multiplexers are controlled by 2 bits of the device control register, PWM_SEL, and PWM_MD, respectively. The PWM_SEL bit selects either the SMBus or the PWM input to control the brightness. The PWM_MD bit selects the mode in which the PWM input is to be interpreted. Table 2 provides a complete setting of the three dimming modes (X means don’t care). In PWM mode, the output LED brightness is solely controlled by the percentage duty cycle of the input signal to PWMI. In SMBus mode, the input of PWMI has no effect on the dimming control, and only the SMBus command to brightness control register adjusts the output brightness. In DPST mode, the overall brightness level is the normalized product of the SMBus command setting and PWM input duty cycle. The PWM signal starts from 100% when operating in DPST mode. Dimming Control Register Descriptions The MAX17061 includes four registers to monitor and control brightness, fault status, identification, and operating mode. The slave address is 0b0101100. Brightness control register: Address is 0x00. This register is both readable and writable for all 8 bits, BRT0–BRT7, which are used to control the LED brightness level. In SMBus dimming mode, an SMBus write byte cycle to register 0x00 sets the output brightness level. The SMBus setting of 0xFF for this register sets the backlight controller to the maximum brightness output, and 0x00 sets the minimum backlight brightness (about 2.7%). The default value for register 0x00 is 0xFF. A write byte cycle to register 0x00 has no effect when the backlight controller is in PWM mode. The SMBus read byte cycle to register 0x00 returns the current brightness level, regardless of the dimming mode. REGISTER 0x00 BRIGHTNESS CONTROL REGISTER DEFAULT VALUE 0xFF BRT7 BRT6 BRT5 BRT4 BRT3 BRT2 BRT1 BRT0 Bit 7 (R/W) Bit 6 (R/W) Bit 5 (R/W) Bit 4 (R/W) Bit 3 (R/W) Bit 2 (R/W) Bit 1 (R/W) Bit 0 Bit field definitions: BIT FIELD DEFINITION Bit [7..0] BRT [7..0] DESCRIPTION 8-bit brightness setting, adjusting brightness levels in 256 steps, default value is 0xFF. Device control register: Address is 0x01. This register is both readable and writable for Bit 0 to Bit 2. Bit 0, also named BL_CTL, is used as ON/OFF control for the output LEDs. Bit 1 and Bit 2, named PWM_SEL and PWM_MD, respectively, control the operating mode of the backlight controller. Bit 3 through Bit 7 are reserved bits. All reserved bits, return zero when read, and are ignored by the controller when written. A value of 1 written to BL_CTL turns on the backlight in 10ms or less after the write cycle completes. A value of zero written to BL_CTL immediately turns off the backlight. REGISTER 0x01 DEVICE CONTROL REGISTER DEFAULT VALUE 0x00 RESERVED RESERVED RESERVED RESERVED RESERVED PWM_MD PWM_SEL BL_CTL Bit 7 Bit 6 Bit 5 Bit 4 Bit 3 Bit 2 (R/W) Bit 1 (R/W) Bit 0 (R/W) Bit field definitions: BIT FIELD DEFINITION Bit 2 PWM_MD Bit 1 PWM_SEL Bit 0 BL_CTL DESCRIPTION PWM mode select (1 = absolute brightness, 0 = % change), default = 0 Brightness MUX select (1 = PWM pin, 0 = SMBus value), default = 0 BL on/off (1 = on, 0 = off), default = 0 ______________________________________________________________________________________ 17 MAX17061 Overvoltage Protection The SMBus interface can be used to adjust the dimming, as well as shut down the MAX17061. Before the MAX17061 receives a turn-on command from the SMBus, it automatically remains off. In this low-power state, most of the control circuits are turned off, and only part of LDO is active to provide a loosely regulated output of about 4.35V on the V CC pin to power the SMBus interface. Even in PWM dimming mode, only the PWMI interface is used for brightness control; the MAX17061 cannot run without the SMBus interface. For sister products without the SMBus interface, contact MAXIM Integrated Products, Inc. MAX17061 8-String White LED Driver with SMBus for LCD Panel Applications Table 2. Operating Modes Selected by Device Control Register Bits 1 and 2 PWM_MD PWM_SEL MODE DPWM DUTY-CYCLE SETTING X 1 PWM mode 1 0 SMBus mode 0 0 DPST mode PWMI input duty cycle SMBus command Product of PWMI input duty cycle and SMBus command Fault/Status Register: Address is 0x02. This register has 6 status bits that allow monitoring the backlight controller’s operating state. Bit 6 and Bit 7 are reserved bits, and Bit 3 is the status indicator or backlight. The other 5 bits are fault indicators. Bit 0 is a logical OR of all fault codes except LED open/short to simplify error detection. All the bits in this register are read only. The reserved bits return a zero when read. REGISTER 0x02 FAULT STATUS REGISTER DEFAULT VALUE 0x00 RESERVED RESERVED 2_CH_SD 1_CH_SD BL_STAT OV_CURR THRM_SHDN FAULT Bit 7 (R) Bit 6 (R) Bit 5 (R) Bit 4 (R) Bit 3 (R) Bit 2 (R) Bit 1 (R) Bit 0 (R) Bit field definitions: BIT FIELD DEFINITION Bit 5 2_CH_SD Bit 4 1_CH_SD One LED output channel is faulted (1 = faulted, 0 = OK) Bit 3 BL_STAT Backlight status (1 = BL on, 0 = BL off) Bit 2 OV_CURR Bit 1 THRM_SHD Bit 0 FAULT DESCRIPTION Two or more LED output channels are faulted (1 = faulted, 0 = OK) Input overcurrent (1 = overcurrent condition, 0 = current OK) Thermal shutdown (1 = thermal fault, 0 = thermal OK) Any fault except LED open/short occurs (logic OR of all fault conditions, 1 = fault condition, 0 = no fault) Identification Register: Address is 0x03. The ID register contains two bit fields to denote the manufacturer and the silicon revision of the controller IC. The bit field widths were chosen to allow up to 32 vendors with up to eight silicon revisions each. This register is read only. REGISTER 0x03 ID REGISTER DEFAULT VALUE 0x80 LED PANEL MFG3 MFG2 MFG1 MFG0 REV2 REV1 REV0 Bit 7 = 1 Bit 6 (R) Bit 5 (R) Bit 4 (R) Bit 3 (R) Bit 2 (R) Bit 1 (R) Bit 0 (R) Bit field definitions: 18 BIT FIELD DEFINITION Bit 7 LED panel DESCRIPTION Bit [6..3] MFG[3..0] Manufacturer ID; see Table 3, default = 0 Bit [2..0] REV[2..0] Silicon rev (revs 0–7 allowed for silicon spins), default = 0 Display panel using LED backlight, bit 7 = 1 ______________________________________________________________________________________ 8-String White LED Driver with SMBus for LCD Panel Applications Thermal Shutdown The MAX17061 includes a thermal-protection circuit. When the local IC temperature exceeds +160°C (typ), the controller and current sources shut down and do not restart until the die temperature drops by 15°C. When thermal shutdown occurs, Bit 1 of fault/status register is set to 1. Table 3. Vendor IDs ID VENDOR 0 Maxim 1 Micro Semi 2 MPS 3 O2 Micro 4 TI All MAX17061 designs should be prototyped and tested prior to production. Table 4 provides a list of power components for the typical applications circuit. Table 5 lists component suppliers. External component value choice is primarily dictated by the output voltage and the maximum load current, as well as maximum and minimum input voltages. Begin by selecting an inductor value. Once L is known, choose the diode and capacitors. Step-Up Converter Current Calculation At light loads, the MAX17061 automatically skips pulses to improve efficiency and prevent overcharging the output capacitor. The output current for the converter SKIP operation can be calculated by the following equation: IO(SKIP) < 5 ST 6 Analog Devices 7–14 Reserved 15 Vendor ID register not implemented VIN2 × TON(MIN)2 × fOSC 2 × L × (VOUT + VDIODE − VIN ) where IO(SKIP) is the output current in SKIP mode, VIN is the input voltage, TON(MIN) is the minimum on-time, and VDIODE is the forward voltage of rectifier diode D. Table 4. Component List SWITCHING FREQUENCY 1MHz 1MHz Nichia NSSW008C 3.2V (typ), 3.5V (max) at 20mA Nichia NSSW008C 3.2V (typ), 3.5V (max) at 20mA Number of WLEDs 10 pcs x 4 strings, 25mA (max) 10 pcs x 8 strings, 25mA (max) Input Voltage 7V to 21V 7V to 21V Inductor 10µH, 1.2A power inductor TDK VLP6810T-100M1R2; Sumida CR6D09HPNP-100MC 10µH, 2.5A power inductor TDK SLF10145T-100M2R5-PF Input Capacitors 4.7µF ±10%, 25V X5R ceramic capacitor (1206) Murata GRM319R61E475KA12D 10µF ±10%, 25V X5R ceramic capacitor (1206) Murata GRM31CR61E106KA Output Capacitor COUT 0.33µF ±10%, 50V X7R ceramic capacitor (1206) (6x) Murata GRM319R71H334K TDK C3216JB1H334K 1µF ±10%, 50V X7R ceramic capacitor (1206) (4x) Murata GRM31MR71H105KA TDK C3216X7R1H105K Diode Rectifier 0.7A, 60V Schottky diode (US-flat) Toshiba CUS04 3A, 60V Schottky diode Nihon EC31QS06 White LED Table 5. Component Suppliers SUPPLIER PHONE WEBSITE Murata 770-436-1300 www.murata.com Nichia 248-352-6575 www.nichia.com Sumida 847-545-6700 www.sumida.com Toshiba 949-455-2000 www.toshiba.com/taec Vishay 203-268-6261 www.vishay.com ______________________________________________________________________________________ 19 MAX17061 Design Procedure The list of ID values for vendors is shown in Table 3. MAX17061 8-String White LED Driver with SMBus for LCD Panel Applications To ensure the stable operation, the MAX17061 includes slope compensation, which sets the minimum inductor value. In continuous-conduction mode (CCM), the minimum inductor value is calculated with the following equation: L CCM(MIN) = (VOUT(MAX) + VDIODE − 2 × VIN(MIN) ) × RS 2 × 24.7mV × fOSC(MIN) where 24.7mV is a scale factor from the slope compensation, the LCCM(MIN) is the minimum inductor value for stable operation in CCM, and RS =12mΩ (typ) is the equivalent sensing scale factor from the controller’s internal current-sense circuit. The controller can also operate in discontinuous conduction mode (DCM). In this mode, the inductor value can be lower, but the peak inductor current is higher than in CCM. In DCM, the maximum inductor value is calculated with the following equation: ⎛ ⎞ VIN(MIN) LDCM(MAX) = ⎜1 − ⎟ ⎝ VOUT(MAX) + VDIODE ⎠ × VIN(MIN)2 × η 2 × fOSC(MAX) × VOUT(MAX) × IOUT(MAX) where the LDCM(MAX) is the maximum inductor value for DCM, η is the nominal regulator efficiency (85%), and IOUT(MAX) is the maximum output current. The output current capability of the step-up converter is a function of current limit, input voltage, operating frequency, and inductor value. Because the slope compensation is used to stabilize the feedback loop, the inductor current limit depends on the duty cycle, and is determined with the following equation: ILIM = 1.9A + 24.7mV × (0.75 − D) RS where 24.7mV is the scale factor from the slope compensation, 1.9A is a typical current limit at 75% duty cycle, and D is the duty cycle. The output current capability depends on the currentlimit value and operating mode. The maximum output current in CCM is governed by the following equation: ⎛ 0.5 × D × VIN ⎞ IOUT _ CCM(MAX) = ⎜ ILIM − fOSC × L ⎟⎠ ⎝ 20 where ILIM is the current limit calculated above, η is the nominal regulator efficiency (85%), and D is the duty cycle. The corresponding duty cycle for this current is: D= VOUT − VIN + VDIODE VOUT − ILIM × RON + VDIODE where VDIODE is the forward voltage of the rectifier diode and RON is the internal MOSFET’s on-resistance (0.15Ω typ). The maximum output current in DCM is governed by the following equation: IOUT _ DCM(MAX) = L × ILIM2 × fOSC × η 2 × (VOUT + VDIODE − VIN ) Inductor Selection The inductance, peak current rating, series resistance, and physical size should all be considered when selecting an inductor. These factors affect the converter’s operating mode, efficiency, maximum output load capability, transient response time, output voltage ripple, and cost. The maximum output current, input voltage, output voltage, and switching frequency determine the inductor value. Very high inductance minimizes the current ripple, and therefore reduces the peak current, which decreases core losses in the inductor and I2R losses in the entire power path. However, large inductor values also require more energy storage and more turns of wire, which increases physical size and I2R copper losses. Low inductor values decrease the physical size, but increase the current ripple and peak current. Finding the best inductor involves the compromises among circuit efficiency, inductor size, and cost. In choosing an inductor, the first step is to determine the operating mode: continuous conduction mode (CCM) or discontinuous conduction mode (DCM). The MAX17061 has a fixed internal slope compensation that requires minimum inductor value. When CCM mode is chosen, the ripple current and the peak current of the inductor can be minimized. If a small-size inductor is required, DCM mode can be chosen. In DCM mode, the inductor value and size can be minimized, but the inductor ripple current and peak current are higher than those in CCM. The controller can be stable, independent of the internal slope compensation mode, but there is a maximum inductor value requirement to ensure the DCM operating mode. ______________________________________________________________________________________ 8-String White LED Driver with SMBus for LCD Panel Applications IIN(DCMAX , )= IOUT(MAX) × VOUT VIN(MIN) × ηMIN 2) Calculate the ripple current at that operating point and the peak current required for the inductor: IRIPPLE = ( VIN(MIN) × VOUT(MAX) − VIN(MIN) L × VOUT(MAX) × fOSC ) Inductor Selection in DCM Operation When DCM operating mode is chosen to minimize the inductor value, the calculations are different from those above in CCM mode. The maximum inductor value for DCM mode is calculated with the following equation: The peak-inductor current in DCM is calculated with following equation: ⎛ ⎞ VIN(MIN) LDCM(MAX) = ⎜1 − ⎟ ⎝ VOUT(MAX) + VDIODE ⎠ × VIN(MIN)2 × η 2 × fOSC(MAX) × VOUT(MAX) × IOUT(MAX) Inductor Selection in CCM Operation 1) Calculate the approximate inductor value using the typical input voltage (VIN), the maximum output current (I OUT(MAX)), the expected efficiency ( ηTYP) taken from an appropriate curve in the Typical Operating Characteristics, and an estimate of LIR based on the above discussion: 2 ⎛ VIN _ MIN ⎞ ⎛ VOUT − VIN _ MIN ⎞ ⎛ ηTYP ⎞ L=⎜ ⎟ ⎟⎜ ⎟ ⎜ ⎝ VOUT ⎠ ⎝ IOUT(MAX) × fOSC ⎠ ⎝ LIR ⎠ The MAX17061 has a minimum inductor value limitation for a stable operation in CCM mode at low input voltage because of the internal fixed-slope compensation. The minimum inductor value for stability is calculated with the following equation: L CCM(MIN) = (VOUT(MAX) + VDIODE − 2 × VIN(MIN) ) × RS 2 × 24.7mV × fOSC(MIN) where 24.7mV is a scale factor from slope compensation, and the RS is the equivalent current-sensing scale factor (12mΩ typ): 1) Choose an available inductor value from an appropriate inductor family. Calculate the maximum DC input current at the minimum input voltage VIN(MIN), using conservation of energy and the expected efficiency at that operating point (ηMIN) taken from an appropriate curve in the Typical Operating Characteristics: IRIPPLE IPEAK = IIN(DCMAX , )+ 2 The inductor’s saturation current rating should exceed I PEAK and the inductor’s DC current rating should exceed IIN(DC,MAX). For good efficiency, choose an inductor with less than 0.1Ω series resistance. Inductor Selection Design Examples: Considering the Typical Operating Circuit with four 10-LED strings and 25mA LED full-scale current, the maximum load current (IOUT(MAX)) is 100mA with a 35.9V output and a minimal input voltage of 7V. Choosing a CCM operating mode with LIR = 1 at 1MHz and estimating efficiency of 85% at this operating point: 2 ⎛ 7V ⎞ ⎛ 35.9V − 7V ⎞ ⎛ 0.85 ⎞ L=⎜ ⎟ ⎜ ⎟⎜ ⎟ = 9.44μH ⎝ 35.9V ⎠ ⎝ 100mA × 1MHz ⎠ ⎝ 1 ⎠ In CCM, the inductor has to be higher than LCCM(MIN): L CCM(MIN) = (35.9V + 0.4V − 2 × 7V) × 12mΩ = 6.0μH 2 × 24.7mV × 0.9MHz A10µH inductor is chosen, which is higher than the minimum L that guarantees stability in CCM. ______________________________________________________________________________________ 21 MAX17061 The equations used here include a constant LIR, which is the ratio of the inductor peak-to-peak ripple current to the average DC inductor current at the full load current. The controller operates in DCM mode when LIR is higher than 2.0, and it works in CCM mode when LIR is lower than 2.0. The best trade-off between inductor size and converter efficiency for step-up regulators generally has an LIR between 0.3 and 0.5. However, depending on the AC characteristics of the inductor core material and ratio of inductor resistance to other power-path resistances, the best LIR can shift up or down. If the inductor resistance is relatively high, more ripples can be accepted to reduce the number of required turns and increase the wire diameter. If the inductor resistance is relatively low, increasing inductance to lower the peak current can reduce losses throughout the power path. If extremely thin high-resistance inductors are used, as is common for LCD panel applications, LIR higher than 2.0 can be chosen for DCM operating mode. Once a physical inductor is chosen, higher and lower values of the inductor should be evaluated for efficiency improvements in typical operating regions. The detail design procedure for CCM can be described as follows: MAX17061 8-String White LED Driver with SMBus for LCD Panel Applications The peak-inductor current at minimum input voltage is calculated as follows: 100mA × 35.9V IPEAK = 7V × 0.85 7V × (35.9V − 7V ) = 0.92A + 2 × 10μH × 35.9V × 0.9MHz Alternatively, choosing a DCM operating mode at 750kHz and estimating efficiency of 85% at this operating point: 7V ⎛ ⎞ LDCM(MAX) = ⎜1− ⎟ ⎝ 35.9V + 0.4V ⎠ × (7V)2 × 0.85 = 5.6μH 2 × 0.825MHz × 35.9V × 100mA A 4.7µH inductor is chosen. The peak inductor current at minimum input voltage is calculated as follows: IPEAK = 100mA × 2 × 35.9V × (35.9V + 0.4V − 7V ) 4.7uH × 0.675MHz × 0.85 × (35.9V + 0.4V ) = 1.47A Output Capacitor Selection The total output voltage ripple has two components: the capacitive ripple caused by the charging and discharging on the output capacitor, and the ohmic ripple due to the capacitor’s equivalent series resistance (ESR): VRIPPLE = VRIPPLE(C) + VRIPPLE(ESR) IOUT(MAX) ⎛ VOUT(MAX) − VIN(MIN) ⎞ VRIPPLE(C) ≈ ⎜ ⎟ COUT ⎝ VOUT(MAX)fOSC ⎠ Overvoltage Protection Determination The OV protection circuit should ensure the circuit safe operation; therefore, the controller should limit the output voltage within the ratings of all MOSFET, diode, and output capacitor components, while providing sufficient output voltage for LED current regulation. The OV pin is tied to the center tap of a resistive voltage-divider (R1 and R2 in Figure 1) from the high-voltage output. When the controller detects the OV pin voltage reaching the threshold VOV_TH, typically 1.23V, OV protection is activated. Hence, the step-up converter output overvoltage protection point is: ⎛ R1 ⎞ VOUT(OVP) = VOV _ TH × ⎜1 + ⎟ ⎝ R2 ⎠ In Figure 1, the output OVP voltage is set to: VOUT(OVP) = 1.236V × (1 + 2.21MΩ ) ≈ 45V 61.9kΩ Input Capacitor Selection and: VRIPPLE(ESR) ≈ IPEAKRESR(COUT) where I PEAK is the peak inductor current (see the Inductor Selection section). The output voltage ripple should be low enough for the FB_ current-source regulation. The ripple voltage should be less than 200mVP-P. For ceramic capacitors, the output voltage ripple is typically dominated by VRIPPLE(C). The voltage rating and temperature characteristics of the output capacitor must also be considered. The actual capacitance of a ceramic capacitor is reduced by DC voltage biasing. Ensure the selected capacitor has enough capacitance at actual DC biasing. 22 Rectifier Diode Selection The MAX17061’s high switching frequency demands a high-speed rectifier. Schottky diodes are recommended for most applications because of their fast recovery time and low forward voltage. The diode should be rated to handle the output voltage and the peak switch current. Make sure that the diode’s peak current rating is at least IPEAK calculated in the Inductor Selection section and that its breakdown voltage exceeds the output voltage. The input capacitor (C IN ) filters the current peaks drawn from the input supply and reduces noise injection into the IC. A 10µF ceramic capacitor is used in the Typical Operating Circuit (Figure 1) because of the high source impedance seen in typical lab setups. Actual applications usually have much lower source impedance since the step-up regulator often runs directly from the output of another regulated supply. In some applications, CIN can be reduced below the values used in the Typical Operating Circuit (Figure 1). Ensure a low-noise supply at IN by using adequate CIN. Alternatively, greater voltage variation can be tolerated on CIN if IN is decoupled from CIN using an RC lowpass filter. ______________________________________________________________________________________ 8-String White LED Driver with SMBus for LCD Panel Applications FB Pin Maximum Voltage The current through each FB_ pin is controlled only during the step-up converter’s on-time. During the converter’s off-time, the current sources are turned off. The output voltage does not discharge and stays high. The MAX17061 disables the FB current source to which the string is shorted. In this case, the step-up converter’s output voltage is always applied to the disabled FB pin. The FB_ pin can withstand 45V. Applications Information LED VFB_ Variation The MAX17061 has accurate (±1.5%) matching for each current source. However, the forward voltage of each white LED can vary up to 25% from part to part. The accumulated voltage difference in each string equates to additional power loss within the IC. For the best efficiency, the voltage difference between strings should be minimized. The difference between lowest voltage string and highest voltage string should be less than 4.8V (typ). Otherwise, the internal LED shortprotection circuit disables the high FB string. PCB Layout Guidelines Careful PCB layout is important for proper operation. Use the following guidelines for good PCB layout: 1) Minimize the area of high current switching loop of rectifier diode, internal MOSFET, and output capacitor to avoid excessive switching noise. 2) Connect high-current input and output components with short and wide connections. The high-current input loop goes from the positive terminal of the input capacitor to the inductor, to the internal MOSFET, then to the input capacitor’s negative terminal. The high-current output loop is from the positive terminal of the input capacitor to the inductor, to the rectifier diode, to the positive terminal of the output capacitors, reconnecting between the output capacitor and input capacitor ground terminals. Avoid using vias in the high-current paths. If vias are unavoidable, use multiple vias in parallel to reduce resistance and inductance. 3) Create a ground island (PGND) consisting of the input and output capacitor ground and negative terminal of the current-sense resistor. Connect all these together with short, wide traces or a small ground plane. Maximizing the width of the powerground traces improves efficiency and reduces output-voltage ripple and noise spikes. Create an analog ground island (AGND) consisting of the overvoltage detection divider ground connection, the ISET and FSET resistor connections, CCV capacitor connections, and the device’s exposed backside pad. Connect the AGND and PGND islands by connecting the GND pins directly to the exposed backside pad. Make no other connections between these separate ground planes. ______________________________________________________________________________________ 23 MAX17061 LED Selection and Bias The series/parallel configuration of the LED load and the full-scale bias current have a significant effect or regulator performance. LED characteristics vary significantly from manufacturer to manufacturer. Consult the respective LED data sheets to determine the range of output voltages for a given brightness and LED current. In general, brightness increases as a function of bias current. This suggests that the number of LEDs could be decreased if higher bias current is chosen; however, high current increases LED temperature and reduces operating life. Improvements in LED technology are resulting in devices with lower forward voltage and while increasing the bias current and light output. LED manufacturers specify LED color at a given LED current. With lower LED current, the color of the emitted light tends to shift toward the blue range of the spectrum. A blue bias is often acceptable for business applications but not for high-image-quality applications such as DVD players. Direct DPWM dimming is a viable solution for reducing power dissipation while maintaining LED color integrity. Careful attention should be paid to switching noise to avoid other display quality problems. Using fewer LEDs in a string improves step-up converter efficiency, and lowers breakdown voltage requirements of the external MOSFET and diode. The minimum number of LEDs in series should always be greater than maximum input voltage. If the diode voltage drop is lower than maximum input voltage, the voltage drop across the current-sense inputs (FB_) increases and causes excess heating in the IC. Between 8 and 12 LEDs in series are ideal for input voltages up to 20V. PGND1 PGND2 N.C. LX1 LX2 SCL 19 18 17 16 15 VDD 22 14 SDA VCC 23 13 FSET CCV 24 12 PWMO 11 PWMI ISET 26 10 OSC FB1 27 9 FB8 FB2 28 8 FB7 OV 25 3 4 5 6 7 FB6 2 FB5 1 N.C. MAX17061ETI+ N.C. Refer to the MAX17061 evaluation kit for an example of proper board layout. 20 FB4 6) Minimize the size of the LX node while keeping it wide and short. Keep the LX node away from the feedback node and ground. If possible, avoid running the LX node from one side of the PCB to the other. Use DC traces as shield if necessary. 21 TOP VIEW GND 5) Place IN pin bypass capacitor as close as possible to the device. The ground connection of the IN bypass capacitor should be connected directly to GND pins with a wide trace. Pin Configuration IN 4) Place the overvoltage detection divider resistors as close as possible to the OV pin. The divider’s center trace should be kept short. Placing the resistors far away causes the sensing trace to become antennas that can pick up switching noise. Avoid running the sensing traces near LX. FB3 MAX17061 8-String White LED Driver with SMBus for LCD Panel Applications THIN QFN 4mm x 4mm Chip Information TRANSISTOR COUNT: 21,800 PROCESS: BiCMOS 24 ______________________________________________________________________________________ 8-String White LED Driver with SMBus for LCD Panel Applications 24L QFN THIN.EPS ______________________________________________________________________________________ 25 MAX17061 Package Information (The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information go to www.maxim-ic.com/packages.) MAX17061 8-String White LED Driver with SMBus for LCD Panel Applications Package Information (continued) (The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information go to www.maxim-ic.com/packages.) Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are implied. Maxim reserves the right to change the circuitry and specifications without notice at any time. Maxim Integrated Products, 120 San Gabriel Drive, Sunnyvale, CA 94086 408-737-7600 ____________________ 26 © 2008 Maxim Integrated Products is a registered trademark of Maxim Integrated Products, Inc.