LTC4081 500mA Li-Ion Charger with NTC Input and 300mA Synchronous Buck DESCRIPTIO U FEATURES Battery Charger: Constant-Current/Constant-Voltage Operation with Thermal Feedback to Maximize Charge Rate Without Risk of Overheating ■ Internal 4.5 Hour Safety Timer for Termination ■ Charge Current Programmable Up to 500mA with 5% Accuracy ■ NTC Thermistor Input for Temperature Qualified Charging ■ C/10 Charge Current Detection Output ■ 5μA Supply Current in Shutdown Mode Switching Regulator: ■ High Efficiency Synchronous Buck Converter ■ 300mA Output Current (Constant-Frequency Mode) ■ 2.7V to 4.5V Input Range (Powered from BAT Pin) ■ 0.8V to V BAT Output Range ■ MODE Pin Selects Fixed (2.25MHz) Constant-Frequency PWM Mode or Low ICC (23μA) Burst Mode® Operation ■ 2μA BAT Current in Shutdown Mode ■ 10-lead, low profile (0.75 mm) 3mm × 3mm DFN package ■ U APPLICATIO S ■ ■ ■ ■ The LTC4081 is a complete constant-current/constantvoltage linear battery charger for a single-cell 4.2V lithium-ion/polymer battery with an integrated 300mA synchronous buck converter. A 3mm × 3mm DFN package and low external component count make the LTC4081 especially suitable for portable applications. Furthermore, the LTC4081 is specifically designed to work within USB power specifications. The ⎯ C⎯ H⎯ R⎯G pin indicates when charge current has dropped to ten percent of its programmed value (C/10). An internal 4.5 hour timer terminates the charge cycle. The full-featured LTC4081 battery charger also includes trickle charge, automatic recharge, soft-start (to limit inrush current) and an NTC thermistor input used to monitor battery temperature. The LTC4081 integrates a synchronous buck converter that is powered from the BAT pin. It has an adjustable output voltage and can deliver up to 300mA of load current. The buck converter also features low-current highefficiency Burst Mode operation that can be selected by the MODE pin. The LTC4081 is available in a 10-lead, low profile (0.75 mm) 3mm × 3mm DFN package. Wireless Headsets Bluetooth Applications Portable MP3 Players Multifunction Wristwatches , LT, LTC and LTM are registered trademarks of Linear Technology Corporation. Burst Mode is a registered trademark of Linear Technology Corporation. All other trademarks are the property of their respective owners. Protected by U.S. Patents, including 6522118. U Buck Efficiency vs Load Current (VOUT = 1.8V) TYPICAL APPLICATIO Li-Ion Battery Charger with 1.8V Buck Regulator 510Ω VCC CHRG EN_BUCK 100k BAT LTC4081 NTC 4.7μF 100k EN_CHRG T 500mA 4.7μF 1OμH + SW 10pF FB VOUT (1.8V/300mA) 806Ω 806k 60 40 20 1M MODE GND PROG 4.2V Li-Ion/ POLYMER BATTERY EFFICIENCY (%) 80 4.7μF 0 0.01 EFFICIENCY (Burst) EFFICIENCY (PWM) 100 POWER LOSS 10 (PWM) POWER LOSS (Burst) 1 POWER LOSS (mW) VCC (3.75V TO 5.5V) 1000 100 VBAT = 3.8V 0.1 VOUT = 1.8V L = 10μH C = 4.7μF 0.01 0.1 1 10 100 1000 LOAD CURRENT (mA) 4081 TA01b 4081 TA01a 4081f 1 LTC4081 U W W W ABSOLUTE AXI U RATI GS (Note 1) VCC , t < 1ms and Duty Cycle < 1% .............. – 0.3V to 7V VCC Steady State ......................................... – 0.3V to 6V BAT, ⎯C⎯H⎯R⎯G .................................................. – 0.3V to 6V ⎯E⎯N⎯_⎯C⎯H⎯R⎯G, PROG, NTC ...................– 0.3V to VCC + 0.3V MODE, EN_BUCK .......................... – 0.3V to VBAT + 0.3V FB ............................................................... – 0.3V to 2V BAT Short-Circuit Duration............................Continuous BAT Pin Current ...................................................800mA PROG Pin Current ....................................................2mA Junction Temperature .......................................... .125°C Operating Temperature Range (Note 2) .. – 40°C to 85°C Storage Temperature Range.................. – 65°C to 125°C PIN CONFIGURATION TOP VIEW 10 SW BAT 1 VCC 2 EN_CHRG 3 PROG 4 7 FB NTC 5 6 CHRG 9 EN_BUCK 11 8 MODE DD PACKAGE 10-LEAD (3mm × 3mm) PLASTIC DFN TJMAX = 110°C, θJA = 43°C/W (NOTE 3) EXPOSED PAD (PIN 11) IS GND, MUST BE SOLDERED TO PCB ORDER INFORMATION LEAD FREE FINISH TAPE AND REEL PART MARKING PACKAGE DESCRIPTION TEMPERATURE RANGE LTC4081EDD#PBF LTC4081EDD#TRPBF LDBX 10-Lead (3mm × 3mm) DFN 0°C to 70°C Consult LTC Marketing for parts specified with wider operating temperature ranges. Consult LTC Marketing for information on non-standard lead based finish parts. For more information on lead free part marking, go to: http://www.linear.com/leadfree/ For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/ ELECTRICAL CHARACTERISTICS The ● denotes specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C, VCC = 5V, VBAT = 3.8V, V⎯E⎯N⎯_⎯C⎯H⎯R⎯G = 0V, VNTC = 0V, VEN_BUCK = VBAT, VMODE = 0V. (Note 2) SYMBOL PARAMETER CONDITIONS VCC Battery Charger Supply Voltage (Note 4) (Note 5) MIN TYP MAX UNITS ● 3.75 5 5.5 V ● 2.7 3.8 4.5 V VBAT Input Voltage for the Switching Regulator ICC Quiescent Supply Current (Charger On, VBAT = 4.5V (Forces IBAT and IPROG = 0), Switching Regulator Off) VEN_BUCK = 0 ● 110 300 μA ICC_SD Supply Current in Shutdown (Both Battery Charger and Switching Regulator Off) ● 5 2 10 μA μA V⎯E⎯N⎯_⎯C⎯H⎯R⎯G = 5V, VEN_BUCK = 0, VCC > VBAT V⎯E⎯N⎯_⎯C⎯H⎯R⎯G = 4V, VEN_BUCK = 0, VCC (3.5V) < VBAT (4V) 4081f 2 LTC4081 ELECTRICAL CHARACTERISTICS The ● denotes specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C, VCC = 5V, VBAT = 3.8V, V⎯E⎯N⎯_⎯C⎯H⎯R⎯G = 0V, VNTC = 0V, VEN_BUCK = VBAT, VMODE = 0V. (Note 2) SYMBOL PARAMETER CONDITIONS MIN IBAT_SD Battery Current in Shutdown (Both Battery Charger and Switching Regulator Off) V⎯E⎯N⎯_⎯C⎯H⎯R⎯G = 5V, VEN_BUCK = 0, VCC > VBAT V⎯E⎯N⎯_⎯C⎯H⎯R⎯G = 4V, VEN_BUCK = 0, VCC (3.5V) < VBAT (4V) VBAT Regulated Output Voltage IBAT = 2mA IBAT = 2mA, 4.3V < VCC < 5.5V ● TYP MAX 0.6 2 5 μA μA 4.179 4.158 4.2 4.2 4.221 4.242 V V ● UNITS Battery Charger VFLOAT IBAT Current Mode Charge Current RPROG = 4k; Current Mode; VEN_BUCK = 0 RPROG = 0.8k; Current Mode; VEN_BUCK = 0 ● ● 90 475 100 500 110 525 mA mA VUVLO_CHRG VCC Undervoltage Lockout Voltage VCC Rising VCC Falling ● ● 3.5 2.8 3.6 3.0 3.7 3.2 V V VPROG PROG Pin Servo Voltage 0.8k ≤ RPROG ≤ 4k ● 0.98 1.0 1.02 V VASD Automatic Shutdown Threshold Voltage (VCC – VBAT), VCC Low to High (VCC – VBAT), VCC High to Low 60 15 82 32 100 45 mV mV tSS_CHRG Battery Charger Soft-Start Time ITRKL Trickle Charge Current VBAT = 2V, RPROG = 0.8k VTRKL Trickle Charge Threshold Voltage VBAT Rising VTRHYS Trickle Charge Threshold Voltage Hysteresis ΔVRECHRG Recharge Battery Threshold Voltage ΔVUVCL1, ΔVUVCL2 (VCC – VBAT) Undervoltage Current Limit Threshold Voltage tTIMER Charge Termination Timer ● Recharge Time ● 180 μs 35 50 65 2.75 2.9 3.05 V 100 150 350 mV VFLOAT – VBAT, 0°C < TA < 85°C 70 100 130 mV IBAT = 0.9 ICHG IBAT = 0.1 ICHG 180 90 300 130 3 4.5 ● mA mV mV 6 hrs 1.5 2.25 3 hrs Low-Battery Charge Time VBAT = 2.5V ● 0.75 1.125 1.5 hrs IC/10 End of Charge Indication Current Level RPROG = 2k (Note 6) ● 0.085 0.1 0.115 TLIM Junction Temperature in ConstantTemperature Mode RON_CHRG Power FET On-Resistance (Between VCC and BAT) ⎯ H ⎯ R ⎯ G ⎯ Pulse Defective Battery Detection C Frequency Defective Battery Detection ⎯C⎯H⎯R⎯G Pulse Frequency Duty Ratio fBADBAT DBADBAT mA/mA 115 °C 700 mΩ VBAT = 2V 2 Hz VBAT = 2V 75 % IBAT = 350mA, VCC = 4V INTC NTC Pin Current VNTC = 2.5V VCOLD Cold Temperature Fault Threshold Voltage Rising Voltage Threshold Hysteresis 0.76 • VCC 0.015 • VCC V V VHOT Hot Temperature Fault Threshold Voltage Falling Voltage Threshold Hysteresis 0.35 • VCC 0.017 • VCC V V VDIS NTC Disable Threshold Voltage Falling Threshold; VCC = 5V Hysteresis fNTC Fault Temperature ⎯C⎯H⎯R⎯G Pulse Frequency Fault Temperature ⎯C⎯H⎯R⎯G Pulse Frequency Duty Ratio DNTC 1 μA 82 50 mV mV 2 Hz 25 % 4081f 3 LTC4081 ELECTRICAL CHARACTERISTICS The ● denotes specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C, VCC = 5V, VBAT = 3.8V, V⎯E⎯N⎯_⎯C⎯H⎯R⎯G = 0V, VNTC = 0V, VEN_BUCK = VBAT, VMODE = 0V. (Note 2) SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS 0.78 0.80 0.82 V 2.25 2.75 Buck Converter ● VFB FB Servo Voltage IFB FB Pin Input Current fOSC Switching Frequency IBAT_NL_CF No-Load Battery Current (Continuous Frequency Mode) No-Load for Regulator, V⎯E⎯N⎯_⎯C⎯H⎯R⎯G = 5V, L = 10μH, C = 4.7μF 1.9 mA IBAT_NL_BM No-Load Battery Current (Burst Mode Operation) No-Load for Regulator, V⎯E⎯N⎯_⎯C⎯H⎯R⎯G = 5V, MODE = VBAT, L = 10μH, C = 4.7μF 23 μA IBAT_SLP Battery Current in SLEEP Mode V⎯E⎯N⎯_⎯C⎯H⎯R⎯G = 5V, MODE = VBAT, VOUT > Regulation Voltage ● 10 15 20 μA VUVLO_BUCK Buck Undervoltage Lockout Voltage VBAT Rising VBAT Falling ● ● 2.6 2.4 2.7 2.5 2.8 2.6 V V RON_P PMOS Switch On-Resistance 0.95 Ω RON_N NMOS Switch On-Resistance 0.85 Ω ILIM_P PMOS Switch Current Limit ILIM_N NMOS Switch Current Limit 700 mA IZERO_CF NMOS Zero Current in Normal Mode 15 mA IPEAK Peak Current in Burst Mode Operation MODE = VBAT 50 100 150 mA IZERO_BM Zero Current in Burst Mode Operation MODE = VBAT 20 35 50 mA tSS_BUCK Buck Soft-Start Time From the Rising Edge of EN_BUCK to 90% of Buck Regulated Output Input High Voltage ⎯E⎯N⎯_⎯C⎯H⎯R⎯G, EN_BUCK, MODE Pin Low to High ● VIL Input Low Voltage E⎯ ⎯N⎯_⎯C⎯H⎯R⎯G, EN_BUCK, MODE Pin High to Low ● VOL Output Low Voltage (⎯C⎯H⎯R⎯G) ISINK = 5mA ● 105 mV IIH Input Current High EN_BUCK, MODE Pins at 5.5V, VBAT = 5V ● –1 1 μA IIL Input Current Low ⎯E⎯N⎯_⎯C⎯H⎯R⎯G, EN_BUCK, MODE Pins at GND ● –1 1 μA R⎯E⎯N⎯_⎯C⎯H⎯R⎯G ⎯E⎯N⎯_⎯C⎯H⎯R⎯G Pin Input Resistance V⎯E⎯N⎯_⎯C⎯H⎯R⎯G = 5V 3.3 MΩ I⎯C⎯H⎯R⎯G ⎯C⎯H⎯R⎯G Pin Leakage Current VBAT = 4.5V, V⎯C⎯H⎯R⎯G = 5V 1 μA VFB = 0.85V –50 ● 1.8 375 50 520 700 400 nA MHz mA μs Logic VIH Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: The LTC4081 is guaranteed to meet performance specifications from 0°C to 85°C. Specifications over the –40°C to 85°C operating temperature range are assured by design, characterization and correlation with statistical process controls. Note 3: Failure to solder the exposed backside of the package to the PC board ground plane will result in a thermal resistance much higher than 43°C/W. 1.2 0.4 V 60 1 ● V 1.45 Note 4: Although the LTC4081 charger functions properly at 3.75V, full charge current requires an input voltage greater than the desired final battery voltage per ΔVUVCL1 specification. Note 5: The 2.8V maximum buck undervoltage lockout (VUVLO_BUCK) exit threshold must first be exceeded before the minimum VBAT specification applies. Note 6: IC/10 is expressed as a fraction of measured full charge current with indicated PROG resistor. 4081f 4 LTC4081 TYPICAL PERFORMANCE CHARACTERISTICS (TA = 25°C, VCC = 5V, VBAT = 3.8V, unless otherwise specified) Battery Regulation (Float) Voltage vs Charge Current 4.21 Battery Regulation (Float) Voltage vs Temperature Battery Regulation (Float) Voltage vs VCC Supply Voltage 4.210 RPROG = 2k 4.25 4.205 4.20 4.20 4.200 4.18 4.17 4.16 4.15 4.15 4.195 FLOAT VOLTAGE (V) FLOAT VOLTAGE (V) FLOAT VOLTAGE (V) 4.19 4.190 4.185 4.180 4.175 0 50 200 150 100 CHARGE CURRENT (mA) 250 4.00 3.90 4.165 4.13 4.05 3.95 4.170 4.14 4.10 4.160 – 50 – 30 3.85 50 30 10 TEMPERATURE (°C) – 10 4081 G01 70 90 4 4.5 5 5.5 VCC SUPPLY VOLTAGE (V) 6 4081 G03 4081 G02 Charge Current vs Temperature with Thermal Regulation (Constant-Current Mode) 250 0.9 1.0 VCC = 6V VBAT = 3V RPROG = 2k VCC = 4V 0.8 IBAT = 350mA RPROG = 2k 0.8 0.7 THERMAL CONTROL LOOP IN OPERATION 100 RDS(ON) (Ω) VPROG (V) 0.6 150 0.6 0.4 0.5 0.4 0.3 0.2 0.2 50 0.1 –25 0 25 50 75 100 125 0 25 0 TEMPERATURE (°C) 50 75 100 125 150 175 200 CHARGE CURRENT (mA) 4081 G04 –10 30 50 10 TEMPERATURE (°C) 70 90 4081 G06 ⎯E⎯N⎯_⎯C⎯H⎯R⎯G Pin Pulldown Resistance vs Temperature 1.7 0.95 0.90 RISING 0.85 0.80 FALLING 0.75 0.70 0.65 0.60 0.55 0.50 –50 0 – 50 – 30 4081 G05 E⎯ ⎯N⎯_⎯C⎯H⎯R⎯G, EN_BUCK and MODE Pin Threshold Voltage vs Temperature PULLDOWN RESISTANCE (MΩ) 0 –50 THRESHOLD VOLTAGE (V) CHARGE CURRENT (mA) 200 Charger FET On-Resistance vs Temperature PROG Pin Voltage vs Charge Current –30 –10 10 30 50 TEMPERATURE (°C) 70 90 4081 G07 1.6 1.5 1.4 1.3 1.2 1.1 1.0 –50 –30 –10 10 30 50 TEMPERATURE (°C) 70 90 4081 G08 4081f 5 LTC4081 TYPICAL PERFORMANCE CHARACTERISTICS (TA = 25°C, VCC = 5V, VBAT = 3.8V, unless otherwise specified) ⎯C⎯H⎯R⎯G Pin Output Low Voltage vs Temperature Normalized Charge Termination Time vs Temperature 80 Buck Oscillator Frequency vs Battery Voltage 1.05 ICHRG = 5mA 2.28 VOLTAGE (mV) 60 50 40 30 20 2.27 1.00 FREQUENCY (MHz) NORMALIZED TIMER PERIOD 70 0.95 0.90 2.26 2.25 2.24 0.85 2.23 10 0 –50 –30 –10 10 30 50 TEMPERATURE (°C) 70 0.80 –50 90 –30 –10 10 30 50 70 2.22 2.5 90 TEMPERATURE (°C) 4081 G09 100 Buck Efficiency vs Load Current (VOUT = 1.5V) 1000 100 100 80 1000 EFFICIENCY (%) 2.1 2.0 40 20 1.9 80 0 0.01 100 POWER LOSS 10 (PWM) 60 1 POWER LOSS (BURST) VBAT = 3.8V 0.1 VOUT = 1.8V L = 10μH C = 4.7μF 0.01 0.1 1 10 100 1000 LOAD CURRENT (mA) 4081 G12 1.810 Burst Mode OPERATION PWM MODE 1.800 1.795 1.790 1.780 2.5 20 0 0.01 No-Load Buck Input Current (Burst Mode Operation) vs Battery Voltage IOUT = 1mA VOUT SET FOR 1.8V 35 Burst Mode OPERATION 30 1.805 PWM MODE 1.800 1.795 1.790 1.785 1.785 3.0 3.5 4.0 BATTERY VOLTAGE (V) 4.5 4081 G14 POWER LOSS 10 (PWM) 1 POWER LOSS (BURST) VBAT = 3.8V 0.1 VOUT = 1.5V L = 10μH C = 4.7μF 0.01 0.1 1 10 100 1000 LOAD CURRENT (mA) 4081 G13a 40 Buck Output Voltage vs Temperature BUCK OUTPUT VOLTAGE (V) BUCK OUTPUT VOLTAGE (V) 1.805 IOUT = 1mA VOUT SET FOR 1.8V 100 4081 G13 Buck Output Voltage vs Battery Voltage 1.810 60 BUCK INPUT CURRENT (μA) FREQUENCY (MHz) VBAT = 2.7V EFFICIENCY (BURST) EFFICIENCY (PWM) POWER LOSS (mW) 2.2 POWER LOSS (mW) EFFICIENCY (BURST) EFFICIENCY (PWM) 80 EFFICIENCY (%) VBAT = 3.8V VBAT = 4.5V 4.5 4081 G11 Buck Efficiency vs Load Current (VOUT = 1.8V) 2.4 1.8 –60 –40 –20 0 20 40 60 TEMPERATURE (°C) 3.5 4.0 BATTERY VOLTAGE (V) 4081 G10 Buck Oscillator Frequency vs Temperature 2.3 3.0 1.780 –50 –30 IOUT = 1mA VOUT = 1.8V L = 10μH 25 20 15 10 5 30 50 –10 10 TEMPERATURE (˚C) 70 90 4081 G15 0 2.5 3.5 3.0 4.0 BATTERY VOLTAGE (V) 4.5 4081 G16 4081f 6 LTC4081 TYPICAL PERFORMANCE CHARACTERISTICS specified) No-Load Buck Input Current (Burst Mode Operation) vs Temperature Buck Main Switch (PMOS) On-Resistance vs Battery Voltage 1.2 1.2 1.0 1.0 20 VBAT = 2.7V 15 10 ON-RESISTANCE (Ω) VBAT = 3.8V 25 0.8 0.6 0.4 0.2 5 30 50 –10 10 TEMPERATURE (˚C) 70 0 2.5 90 0.8 0.6 0.4 0.2 3.0 3.5 4.5 4.0 BATTERY VOLTAGE (V) 0 –50 –30 5.0 4081 G18 30 50 –10 10 TEMPERATURE (°C) 4081 G19 Buck Synchronous Switch (NMOS) On-Resistance vs Battery Voltage 1.2 1.2 1.0 1.0 0.8 0.6 0.4 0.2 90 4081 G20 0.8 0.6 0.4 0.2 0 2.5 3.0 3.5 4.5 4.0 BATTERY VOLTAGE (V) 0 –50 –30 5.0 30 50 –10 10 TEMPERATURE (°C) 70 4081 G21 Maximum Output Current (Burst Mode Operation) vs Battery Voltage 80 L = 10μH MAXIMUM OUTPUT CURRENT (mA) L = 10μH VOUT SET FOR 1.8V 400 300 200 100 2.7 3 90 4081 G22 Maximum Output Current (PWM Mode) vs Battery Voltage 500 70 Buck Synchronous Switch (NMOS) On-Resistance vs Temperature ON-RESISTANCE (Ω) ON-RESISTANCE (Ω) 0 –50 –30 Buck Main Switch (PMOS) On-Resistance vs Temperature VBAT = 4.2V ON-RESISTANCE (Ω) 30 L = 10μH C = 4.7μF VOUT = 1.8V MAXIMUM OUTPUT CURRENT (mA) NO LOAD INPUT CURRENT (μA) 35 (TA = 25°C, VCC = 5V, VBAT = 3.8V, unless otherwise 3.3 3.6 3.9 4.2 4.5 BATTERY VOLTAGE (V) 70 VOUT SET FOR 1.8V 60 50 40 30 20 10 0 2.7 3 3.3 3.6 3.9 4.2 4.5 BATTERY VOLTAGE (V) 4081 G23 4081 G24 4081f 7 LTC4081 TYPICAL PERFORMANCE CHARACTERISTICS specified) (TA = 25°C, VCC = 5V, VBAT = 3.8V, unless otherwise Output Voltage Waveform when Switching Between Burst and PWM Mode (ILOAD = 10mA) Output Voltage Transient Step Response (PWM Mode) Output Voltage Transient Step Response (Burst Mode Operation) VOUT 20mV/DIV AC COUPLED VOUT 50mV/DIV AC COUPLED VOUT 20mV/DIV AC COUPLED ILOAD 250mA/DIV VMODE 5V/DIV ILOAD 50mA/DIV 0mA 0V 0mA 4081 G25 4081 G27 50μs/DIV 50μs/DIV 4081 G26 50μs/DIV Buck VOUT Soft-Start (ILOAD = 50mA) Charger VPROG Soft-Start VOUT 1V/DIV 0V VPROG 200mV/DIV VEN_BUCK 5V/DIV 0V 0V 4081 G28 200μs/DIV 4081 G29 50μs/DIV 4081f 8 LTC4081 U U U PI FU CTIO S BAT (Pin 1): Charge Current Output and Buck Regulator Input. Provides charge current to the battery and regulates the final float voltage to 4.2V. An internal precision resistor divider from this pin sets the float voltage and is disconnected in charger shutdown mode. This pin must be decoupled with a low ESR capacitor for low-noise buck operation. VCC (Pin 2): Positive Input Supply Voltage. This pin provides power to the battery charger. VCC can range from 3.75V to 5.5V. This pin should be bypassed with at least a 1μF capacitor. When VCC is less than 32mV above the BAT pin voltage, the battery charger enters shutdown mode. ⎯ _⎯ C ⎯ H ⎯ R ⎯ G ⎯ (Pin 3): Enable Input Pin for the Battery Charger. E⎯ N Pulling this pin above the manual shutdown threshold (VIH) puts the LTC4081 charger in shutdown mode, thus stopping the charge cycle. In battery charger shutdown mode, the LTC4081 has less than 10μA supply current and less than 5μA battery drain current provided the regulator is not running. Enable is the default state, but the pin should be tied to GND if unused. PROG (Pin 4): Charge Current Program and Charge Current Monitor Pin. Connecting a 1% resistor, RPROG, to ground programs the charge current. When charging in constant-current mode, this pin servos to 1V. In all modes, the voltage on this pin can be used to measure the charge current using the following formula: I BAT = VPROG • 40 0 RPROG NTC (Pin 5): Input to the NTC (negative temperature coefficient) Thermistor Temperature Monitoring Circuit. For normal operation, connect a thermistor from the NTC pin to ground and a resistor of equal value from the NTC pin to VCC. When the voltage at this pin drops below 0.35 • VCC at hot temperatures or rises above 0.76 • VCC at cold, charging is suspended, the internal timer is frozen and the ⎯C⎯H⎯R⎯G pin output will start to pulse at 2Hz. Pulling this pin below 0.016 • VCC disables the NTC feature. There is approximately 3°C of temperature hysteresis associated with each of the input comparator’s thresholds. ⎯ ⎯H⎯R⎯G (Pin 6): Open-Drain Charge Status Output. The C charge status indicator pin has three states: pulldown, high impedance state, and pulsing at 2Hz. This output can be used as a logic interface or as an LED driver. When the battery is being charged, the ⎯C⎯H⎯R⎯G pin is pulled low by an internal N-channel MOSFET. When the charge current drops to 10% of the full-scale current, the ⎯C⎯H⎯R⎯G pin is forced to a high impedance state. When the battery voltage remains below 2.9V for one quarter of the full charge time, the battery is considered defective, and the ⎯C⎯H⎯R⎯G pin pulses at a frequency of 2Hz with 75% duty cycle. When the NTC pin voltage rises above 0.76 • VCC or drops below 0.35 • VCC, the ⎯C⎯H⎯R⎯G pin pulses at a frequency of 2Hz (25% duty cycle). FB (Pin 7): Feedback Pin for the Buck Regulator. A resistor divider from the regulator’s output to the FB pin programs the output voltage. Servo value for this pin is 0.8V. MODE (Pin 8): Burst Mode Enable Pin. Tie this pin high to force the LTC4081 regulator into Burst Mode operation for all load conditions. Tie this pin low to force constantfrequency mode operation for all load conditions. Do not float this pin. EN_BUCK (Pin 9): Enable Input Pin for the Buck Regulator. Pull this pin high to enable the regulator, pull low to shut down. Do not float this pin. SW (Pin 10): Switch Pin for the Buck Regulator. Minimize the length of the metal trace connected to this pin. Place the inductor as close to this pin as possible. GND (Pin 11): Ground. This pin is the back of the Exposed Pad package and must be soldered to the PCB for electrical connection and rated thermal performance. 4081f 9 LTC4081 W BLOCK DIAGRA 2 VCC + 3 EN_CHRG 0.82V CHARGER SHUTDOWN C3 – MP3 MP1 D3 – 115°C + TDIE TA X1 REN X400 D1 PROG 0.1V + – D2 1 + BAT MA C1 R1 CA VA + + – – – MP4 6 1.22V 1V CHRG R2 PULSE LOGIC CHARGER ENABLE 0.1V + 2.9V C2 – BAT BADBAT + VCC C4 3.6V 4 UVLO – PROG RPROG + VCC VCC C5 R9 – RNOM C8 5 VBAT + 80mV TOO COLD SUSPEND + NTC CHARGE CONTROL – LOGIC R10 CHARGER OSCILLATOR – T RNTC C9 COUNTER TOO HOT + R11 + C10 NTC_EN – R12 LINEAR BATTERY CHARGER MP2 + 9 EN_BUCK 0.82V – SYNCHRONOUS BUCK CONVERTER C6 L1 PWM CONTROL AND DRIVE ENABLE BUCK SW CPL MN1 + 0.82V – C7 2.25MHz BUCK OSCILLATOR 11 GND R7 COUT 7 ERROR AMP + MODE – 8 VOUT 10 FB 0.8V R8 4081 BD Figure 1. LTC4081 Block Diagram 4081f 10 LTC4081 U OPERATIO The LTC4081 is a full-featured linear battery charger with an integrated synchronous buck converter designed primarily for handheld applications. The battery charger is capable of charging single-cell 4.2V Li-Ion batteries. The buck converter is powered from the BAT pin and has a programmable output voltage providing a maximum load current of 300mA. The converter and the battery charger can run simultaneously or independently of each other. BATTERY CHARGER OPERATION Featuring an internal P-channel power MOSFET, MP1, the battery charger uses a constant-current/constantvoltage charge algorithm with programmable current. Charge current can be programmed up to 500mA with a final float voltage of 4.2V ±0.5%. The ⎯C⎯H⎯R⎯G open-drain status output indicates when C/10 has been reached. No blocking diode or external sense resistor is required; thus, the basic charger circuit requires only two external components. An internal charge termination timer adheres to battery manufacturer safety guidelines. Furthermore, the LTC4081 battery charger is capable of operating from a USB power source. A charge cycle begins when the voltage at the VCC pin rises above 3.6V and approximately 82mV above the BAT pin voltage, a 1% program resistor is connected from the PROG pin to ground, and the ⎯E⎯N⎯_⎯C⎯H⎯R⎯G pin is pulled below the shutdown threshold (VIL). When the BAT pin approaches the final float voltage of 4.2V, the battery charger enters constant-voltage mode and the charge current begins to decrease. When the current drops to 10% of the full-scale charge current, an internal comparator turns off the N-channel MOSFET driving the ⎯C⎯H⎯R⎯G pin, and the pin becomes high impedance. An internal thermal limit reduces the programmed charge current if the die temperature attempts to rise above a preset value of approximately 115°C. This feature protects the LTC4081 from excessive temperature and allows the user to push the limits of the power handling capability of a given circuit board without the risk of damaging the LTC4081 or external components. Another benefit of the thermal limit is that charge current can be set according to typical, rather than worst-case, ambient temperatures for a given application with the assurance that the battery charger will automatically reduce the current in worst-case conditions. An internal timer sets the total charge time, tTIMER (typically 4.5 hours). When this time elapses, the charge cycle terminates and the ⎯C⎯H⎯R⎯G pin assumes a high impedance state even if C/10 has not yet been reached. To restart the charge cycle, remove the input voltage and reapply it or momentarily force the ⎯E⎯N⎯_⎯C⎯H⎯R⎯G pin above VIH. A new charge cycle will automatically restart if the BAT pin voltage falls below VRECHRG (typically 4.1V). Constant-Current / Constant-Voltage / Constant-Temperature The LTC4081 battery charger uses a unique architecture to charge a battery in a constant-current, constant-voltage and constant-temperature fashion. Figure 1 shows a Simplified Block Diagram of the LTC4081. Three of the amplifier feedback loops shown control the constant-current, CA, constant-voltage, VA, and constant-temperature, TA modes. A fourth amplifier feedback loop, MA, is used to increase the output impedance of the current source pair, MP1 and MP3 (note that MP1 is the internal P-channel power MOSFET). It ensures that the drain current of MP1 is exactly 400 times the drain current of MP3. Amplifiers CA and VA are used in separate feedback loops to force the charger into constant-current or constantvoltage mode, respectively. Diodes D1 and D2 provide priority to either the constant-current or constant-voltage loop, whichever is trying to reduce the charge current the most. The output of the other amplifier saturates low which effectively removes its loop from the system. When in constant-current mode, CA servos the voltage at the PROG pin to be precisely 1V. VA servos its non-inverting input to 1.22V when in constant-voltage mode and the internal resistor divider made up of R1 and R2 ensures that the battery voltage is maintained at 4.2V. The PROG pin voltage gives an indication of the charge current anytime in the charge cycle, as discussed in “Programming Charge Current” in the Applications Information section. 4081f 11 LTC4081 U OPERATIO If the die temperature starts to creep up above 115°C due to internal power dissipation, the transconductance amplifier, TA, limits the die temperature to approximately 115°C by reducing the charge current. Diode D3 ensures that TA does not affect the charge current when the die temperature is below 115°C. In thermal regulation, the PROG pin voltage continues to give an indication of the charge current. In typical operation, the charge cycle begins in constantcurrent mode with the current delivered to the battery equal to 400V/RPROG. If the power dissipation of the LTC4081 results in the junction temperature approaching 115°C, the amplifier (TA) will begin decreasing the charge current to limit the die temperature to approximately 115°C. As the battery voltage rises, the LTC4081 either returns to full constant-current mode or enters constant-voltage mode straight from constant-temperature mode. Battery Charger Undervoltage Lockout (UVLO) An internal undervoltage lockout circuit monitors the VCC input voltage and keeps the battery charger off until VCC rises above 3.6V and approximately 82mV above the BAT pin voltage. The 3.6V UVLO circuit has a built-in hysteresis of approximately 0.6V, and the 82mV automatic shutdown threshold has a built-in hysteresis of approximately 50mV. During undervoltage lockout conditions, maximum battery drain current is 5μA and maximum supply current is 10μA. Undervoltage Charge Current Limiting (UVCL) The battery charger in the LTC4081 includes undervoltage charge current limiting that prevents full charge current until the input supply voltage reaches approximately 300mV above the battery voltage (ΔVUVCL1). This feature is particularly useful if the LTC4081 is powered from a supply with long leads (or any relatively high output impedance). See Applications Information section for further details. Trickle Charge and Defective Battery Detection At the beginning of a charge cycle, if the battery voltage is below 2.9V, the battery charger goes into trickle charge mode, reducing the charge current to 10% of the programmed current. If the low battery voltage persists for one quarter of the total time (1.125 hr), the battery is assumed to be defective, the charge cycle terminates and the ⎯C⎯H⎯R⎯G pin output pulses at a frequency of 2Hz with a 75% duty cycle. If, for any reason, the battery voltage rises above 2.9V, the charge cycle will be restarted. To restart the charge cycle (i.e., when the dead battery is replaced with a discharged battery less than 2.9V), the charger must be reset by removing the input voltage and ⎯ _⎯ C ⎯ H ⎯ R ⎯ G ⎯ pin above reapplying it or temporarily pulling the E⎯ N the shutdown threshold. Battery Charger Shutdown Mode The LTC4081’s battery charger can be disabled by pulling the ⎯E⎯N⎯_⎯C⎯H⎯R⎯G pin above the shutdown threshold (VIH). In shutdown mode, the battery drain current is reduced to about 2μA and the VCC supply current to about 5μA provided the regulator is off. When the input voltage is not present, the battery charger is in shutdown and the battery drain current is less than 5μA. ⎯C⎯H⎯R⎯G Status Output Pin The charge status indicator pin has three states: pulldown, pulsing at 2Hz (see Trickle Charge and Defective Battery Detection and Battery Temperature Monitoring) and high impedance. The pulldown state indicates that the battery charger is in a charge cycle. A high impedance state indicates that the charge current has dropped below 10% of the full-scale current or the battery charger is disabled. When the timer runs out (4.5 hrs), the ⎯C⎯H⎯R⎯G pin is also forced to the high impedance state. If the battery charger is not in constant-voltage mode when the charge current is forced to drop below 10% of the full-scale current by UVCL, ⎯C⎯H⎯R⎯G will stay in the strong pulldown state. Charge Current Soft-Start The LTC4081’s battery charger includes a soft-start circuit to minimize the inrush current at the start of a charge cycle. When a charge cycle is initiated, the charge current ramps from zero to full-scale current over a period of approximately 180μs. This has the effect of minimizing the transient current load on the power supply during start-up. 4081f 12 LTC4081 U OPERATIO Timer and Recharge The LTC4081’s battery charger has an internal charge termination timer that starts when the input voltage is greater than the undervoltage lockout threshold and at least 82mV above BAT, and the battery charger is leaving shutdown. At power-up or when exiting shutdown, the charge time is set to 4.5 hours. Once the charge cycle terminates, the battery charger continuously monitors the BAT pin voltage using a comparator with a 2ms filter time. When the average battery voltage falls below 4.1V (which corresponds to 80%-90% battery capacity), a new charge cycle is initiated and a 2.25 hour timer begins. This ensures that the battery is kept at, or near, a fully charged condition and eliminates the need for periodic charge cycle initiations. The ⎯C⎯H⎯R⎯G output assumes a strong pulldown state during recharge cycles until C/10 is reached or the recharge cycle terminates. When the charger is in Hold mode (battery temperature is either too hot or too cold) the ⎯C⎯H⎯R⎯G pin pulses in a 2Hz, 25% duty cycle frequency unless the charge task is finished or the battery is assumed to be defective. If the NTC pin is grounded, the NTC function will be disabled. SWITCHING REGULATOR OPERATION: The switching buck regulator in the LTC4081 can be turned on by pulling the EN_BUCK pin above VIH. It has two userselectable modes of operation: constant-frequency (PWM) mode and Burst Mode Operation. The constant-frequency mode operation offers low noise at the expense of efficiency whereas the Burst Mode operation offers higher efficiency at light loads at the cost of increased noise, higher output voltage ripple, and less output current. A detailed description of different operating modes and different aspects of operation follow. Operations can best be understood by referring to the Block Diagram. Battery Temperature Monitoring via NTC The battery temperature is measured by placing a negative temperature coefficient (NTC) thermistor close to the battery pack. The NTC circuitry is shown in Figure 2. To use this feature, connect the NTC thermistor, RNTC, between the NTC pin and ground and a resistor, RNOM, from the NTC pin to VCC. RNOM should be a 1% resistor with a value equal to the value of the chosen NTC thermistor at 25°C (this value is 10k for a Vishay NTHS0603NO1N1002J thermistor). The LTC4081 goes into hold mode when the value of the NTC thermistor drops to 0.53 times the value of RNOM, which corresponds to approximately 40°C, and when the value of the NTC thermistor increases to 3.26 times the value of RNOM, which corresponds to approximately 0°C. Hold mode freezes the timer and stops the charge cycle until the thermistor indicates a return to a valid temperature. For a Vishay NTHS0603NO1N1002J thermistor, this value is 32.6k which corresponds to approximately 0°C. The hot and cold comparators each have approximately 3°C of hysteresis to prevent oscillation about the trip point. VCC RNOM 0.76 • VCC 6 NTC T RNTC – + TOO COLD – 0.35 • VCC + TOO HOT + NTC_ENABLE 0.016 • VCC – 4081 F02 Figure 2. NTC Circuit Information 4081f 13 LTC4081 U OPERATIO Constant-Frequency (PWM) Mode Operation The switching regulator operates in constant-frequency (PWM) mode when the MODE pin is pulled below VIL . In this mode, it uses a current mode architecture including an oscillator, an error amplifier, and a PWM comparator for excellent line and load regulation. The main switch MP2 (P-channel MOSFET) turns on to charge the inductor at the beginning of each clock cycle if the FB pin voltage is less than the 0.8V reference voltage. The current into the inductor (and the load) increases until it reaches the peak current demanded by the error amp. At this point, the main switch turns off and the synchronous switch MN1 (N-channel MOSFET) turns on allowing the inductor current to flow from ground to the load until either the next clock cycle begins or the current reduces to the zero current (IZERO) level. Oscillator: In constant-frequency mode, the switching regulator uses a dedicated oscillator which runs at a fixed frequency of 2.25MHz. This frequency is chosen to minimize possible interference with the AM radio band. Error Amplifier: The error amplifier is an internally compensated transconductance (gm) amplifier with a gm of 65 μmhos. The internal 0.8V reference voltage is compared to the voltage at the FB pin to generate a current signal at the output of the error amplifier. This current signal represents the peak inductor current required to achieve regulation. PWM Comparator: Lossless current sensing converts the PMOS switch current signal to a voltage which is summed with the internal slope compensation signal. The PWM comparator compares this summed signal to determine when to turn off the main switch. The switch current sensing is blanked for ~12ns at the beginning of each clock cycle to prevent false switch turn-off. Burst Mode Operation Burst Mode operation can be selected by pulling the MODE pin above VIH. In this mode, the internal oscillator is disabled, the error amplifier is converted into a comparator monitoring the FB voltage, and the inductor current swings between a fixed IPEAK (~100mA) and IZERO (35mA) irrespective of the load current as long as the FB pin voltage is less than or equal to the reference voltage of 0.8V. Once VFB is greater than 0.8V, the control logic shuts off both switches along with most of the circuitry and the regulator is said to enter into SLEEP mode. In SLEEP mode, the regulator only draws about 20μA from the BAT pin provided that the battery charger is turned off. When the output voltage droops about 1% from its nominal value, the regulator wakes up and the inductor current resumes swinging between IPEAK and IZERO. The output capacitor recharges and causes the regulator to re-enter the SLEEP state if the output load remains light enough. The frequency of this intermittent burst operation depends on the load current. That is, as the load current drops further, the regulator turns on less frequently. Thus Burst Mode operation increases the efficiency at light loads by minimizing the switching and quiescent losses. However, the output voltage ripple increases to about 2%. To minimize ripple in the output voltage, the current limits for both switches in Burst Mode operation are reduced to about 20% of their values in the constant-frequency mode. Also the zero current of the synchronous switch is changed to about 35mA thereby preventing reverse conduction through the inductor. Consequently, the regulator can only deliver approximately 67mA of load current while in Burst Mode operation. Any attempt to draw more load current will cause the output voltage to drop out of regulation. Current Limit To prevent inductor current runaway, there are absolute current limits (ILIM) on both the PMOS main switch and the NMOS synchronous switch. These limits are internally set at 520mA and 700mA respectively for PWM mode. If the peak inductor current demanded by the error amplifier ever exceeds the PMOS ILIM, the error amplifier will be ignored and the inductor current will be limited to PMOS ILIM. In Burst Mode operation, the PMOS current limit is reduced to 100mA to minimize output voltage ripple. 4081f 14 LTC4081 U OPERATIO Zero Current Comparator The zero or reverse current comparator monitors the inductor current to the output and shuts off the synchronous rectifier when this current reduces to a predetermined value (IZERO). In fixed frequency mode, this is set to negative 15mA meaning that the regulator allows the inductor current to flow in the reverse direction (from the output to ground through the synchronous rectifier) to a maximum value of 15mA. This is done to ensure that the regulator is able to regulate at very light loads without skipping any cycles thereby keeping output voltage ripple and noise low at the cost of efficiency. However, in Burst Mode operation, IZERO is set to positive 35mA meaning that the synchronous switch is turned off as soon as the current through the inductor to the output decreases to 35mA in the discharge cycle. This preserves the charge on the output capacitor and increases the overall efficiency at light loads. Soft-Start The LTC4081 switching regulator provides soft-start in both modes of operation by slowly charging an internal capacitor. The voltage on this capacitor, in turn, slowly ramps the current limits of both switches from a low value to their respective maximum values over a period of about 400μs. The soft-start capacitor is discharged completely whenever the regulator is disabled. Short-Circuit Protection In the event of a short circuit at the output or during start-up, VOUT will be near zero volts. Since the downward slope of the inductor current is ~VOUT/L, the inductor current may not get a chance to discharge enough to avoid a runaway situation. Because the current sensing is blanked for ~12ns at the beginning of each clock cycle, inductor current can build up to a dangerously high level over a number of cycles even if there is a hard current limit on the main PMOS switch. This is why the switching regulator in the LTC4081 also monitors current through the synchronous NMOS switch and imposes a hard limit on it. If the inductor current through the NMOS switch at the end of a discharge cycle is not below this limit, the regulator skips the next charging cycle thereby preventing inductor current runaway. Switching Regulator Undervoltage Lockout Whenever VBAT is less than 2.7V, an undervoltage lockout circuit keeps the regulator off, preventing unreliable operation. However, if the regulator is already running and the battery voltage is dropping, the undervoltage comparator does not shut down the regulator until VBAT drops below 2.5V. Dropout Operation When the BAT pin voltage approaches VOUT, the duty cycle of the switching regulator approaches 100%. When VBAT is approximately equal to VOUT, the regulator is said to be in dropout. In dropout, the main switch (MP2) stays on continuously with the output voltage being equal to the battery voltage minus the voltage drops across the main switch and the inductor. Global Thermal Shutdown The LTC4081 includes a global thermal shutdown which shuts off the entire device (battery charger and switching regulator) if the die temperature exceeds 160°C. The LTC4081 resumes normal operation once the temperature drops approximately 14°C. 4081f 15 LTC4081 U W U U APPLICATIO S I FOR ATIO BATTERY CHARGER Programming Charge Current The battery charge current is programmed using a single resistor from the PROG pin to ground. The charge current is 400 times the current out of the PROG pin. The program resistor and the charge current are calculated using the following equations: RPROG = 400 • 1V IBAT , IBAT = 400 • 1V RPROG The charge current out of the BAT pin can be determined at any time by monitoring the PROG pin voltage and using the following equation: I BAT = VPROG • 400 RPROG Stability Considerations The LTC4081 battery charger contains two control loops: constant-voltage and constant-current. The constantvoltage loop is stable without any compensation when a battery is connected with low impedance leads. Excessive lead length, however, may add enough series inductance to require a bypass capacitor of at least 1μF from BAT to GND. Furthermore, a 4.7μF capacitor with a 0.2Ω to 1Ω series resistor from BAT to GND is required to keep ripple voltage low when the battery is disconnected. In constant-current mode, the PROG pin voltage is in the feedback loop, not the battery voltage. Because of the additional pole created by PROG pin capacitance, capacitance on this pin must be kept to a minimum. With no additional capacitance on the PROG pin, the battery charger is stable with program resistor values as high as 25k. However, additional capacitance on this node reduces the maximum allowed program resistor. The pole frequency at the PROG pin should be kept above 100kHz. Therefore, if the PROG pin is loaded with a capacitance, CPROG, the following equation should be used to calculate the maximum resistance value for RPROG: RPROG ≤ Average, rather than instantaneous, battery current may be of interest to the user. For example, when the switching regulator operating in low-current mode is connected in parallel with the battery, the average current being pulled out of the BAT pin is typically of more interest than the instantaneous current pulses. In such a case, a simple RC filter can be used on the PROG pin to measure the average battery current as shown in Figure 3. A 10k resistor has been added between the PROG pin and the filter capacitor to ensure stability. Undervoltage Charge Current Limiting (UVCL) USB powered systems tend to have highly variable source impedances (due primarily to cable quality and length). A transient load combined with such impedance can easily trip the UVLO threshold and turn the battery charger off unless undervoltage charge current limiting is implemented. Consider a situation where the LTC4081 is operating under normal conditions and the input supply voltage begins to sag (e.g. an external load drags the input supply down). If the input voltage reaches VUVCL (approximately 300mV above the battery voltage, ΔVUVCL), undervoltage charge current limiting will begin to reduce the charge current in an attempt to maintain ΔVUVCL between VCC and BAT. The LTC4081 will continue to operate at the reduced charge current until the input supply voltage is increased or voltage mode reduces the charge current further. LTC4081 10k PROG GND RPROG CFILTER CHARGE CURRENT MONITOR CIRCUITRY 4081 F03 Figure 3. Isolating Capacitive Load on PROG Pin and Filtering 1 2π • 100kHz • CPROG 4081f 16 LTC4081 U W U U APPLICATIO S I FOR ATIO Operation from Current Limited Wall Adapter USB and Wall Adapter Power By using a current limited wall adapter as the input supply, the LTC4081 can dissipate significantly less power when programmed for a current higher than the limit of the wall adapter. Although the LTC4081 allows charging from a USB port, a wall adapter can also be used to charge Li-Ion batteries. Figure 4 shows an example of how to combine wall adapter and USB power inputs. A P-channel MOSFET, MP1, is used to prevent back conducting into the USB port when a wall adapter is present and Schottky diode, D1, is used to prevent USB power loss through the 1k pulldown resistor. Consider a situation where an application requires a 200mA charge current for a discharged 800mAh Li-Ion battery. If a typical 5V (non-current limited) input supply is available then the peak power dissipation inside the part can exceed 300mW. Typically a wall adapter can supply significantly more current than the current-limited USB port. Therefore, an N-channel MOSFET, MN1, and an extra program resistor can be used to increase the charge current when the wall adapter is present. Now consider the same scenario, but with a 5V input supply with a 200mA current limit. To take advantage of the supply, it is necessary to program the LTC4081 to charge at a current greater than 200mA. Assume that the LTC4081 charger is programmed for 300mA (i.e., RPROG = 1.33kΩ) to ensure that part tolerances maintain a programmed current higher than 200mA. Since the battery charger will demand a charge current higher than the current limit of the input supply, the supply voltage will collapse to the battery voltage plus 200mA times the on-resistance of the internal PFET. The on-resistance of the battery charger power device is approximately 0.7Ω with a 5V supply. The actual on-resistance will be slightly higher due to the fact that the input supply will have collapsed to less than 5V. The power dissipated during this phase of charging is approximately 30mW. That is a ten times improvement over the non-current limited supply power dissipation. 5V WALL ADAPTER (500mA) USB POWER (100mA) Power Dissipation The conditions that cause the LTC4081 battery charger to reduce charge current through thermal feedback can be approximated by considering the total power dissipated in the IC. For high charge currents, the LTC4081 power dissipation is approximately: PD = ( VCC − VBAT ) • IBAT + PD _ BUCK Where PD is the total power dissipated within the IC, VCC is the input supply voltage, VBAT is the battery voltage, IBAT is the charge current and PD_BUCK is the power dissipation due to the regulator. PD_BUCK can be calculated as: ⎛1 ⎞ PD _ BUCK = VOUT • IOUT ⎜ − 1⎟ ⎝η ⎠ BAT D1 2 MP1 1 ICHG SYSTEM LOAD LTC4081 VCC PROG MN1 1k + 4 Li-Ion BATTERY 4k 1k 4081 F04 Figure 4. Combining Wall Adapter and USB Power 4081f 17 LTC4081 U W U U APPLICATIO S I FOR ATIO Where VOUT is the regulated output of the switching regulator, IOUT is the regulator load and η is the regulator efficiency at that particular load. It is not necessary to perform worst-case power dissipation scenarios because the LTC4081 will automatically reduce the charge current to maintain the die temperature at approximately 115°C. However, the approximate ambient temperature at which the thermal feedback begins to protect the IC is: Using the previous example with an ambient temperature of 85°C, the charge current will be reduced to approximately: 115 °C − 85 °C 30 °C I BAT = = = 2 3 2 . 6mA (6V − 3V ) • 43°C / W 129 °C / A Furthermore, the voltage at the PROG pin will change proportionally with the charge current as discussed in the Programming Charge Current section. TA = 115°C – PDθJA VCC Bypass Capacitor TA = 115°C – (VCC – VBAT) • IBAT • θJA if the regulator is off. Many types of capacitors can be used for input bypassing; however, caution must be exercised when using multi-layer ceramic capacitors. Because of the self-resonant and high Q characteristics of some types of ceramic capacitors, high voltage transients can be generated under some start-up conditions, such as connecting the battery charger input to a live power source. Adding a 1Ω series resistor in series with an X5R ceramic capacitor will minimize start-up voltage transients. For more information, refer to Application Note 88. Example: Consider the extreme case when an LTC4081 is operating from a 6V supply providing 250mA to a 3V Li-Ion battery and the regulator is off. The ambient temperature above which the LTC4081 will begin to reduce the 250mA charge current is approximately: TA = 115°C – (6V – 3V) • (250mA) • 43°C/W TA = 115°C – 0.75W • 43°C/W = 115°C – 32.25°C TA = 82.75°C If there is more power dissipation due to the regulator, the thermal regulation will begin at a somewhat lower temperature. In the above circumstances, the LTC4081 can be used above 82.75°C, but the charge current will be reduced from 250mA. The approximate current at a given ambient temperature can be calculated: I BAT = 115 °C − T A ( VCC − VBAT ) • θ JA Thermistors The LTC4081 NTC trip points are designed to work with thermistors whose resistance-temperature characteristics follow Vishay Dale’s “R-T Curve 1.” The Vishay NTHS0603NO1N1002J is an example of such a thermistor. However, Vishay Dale has many thermistor products that follow the “R-T Curve 1” characteristic in a variety of sizes. Furthermore, any thermistor whose ratio of RCOLD to RHOT is about 5 will also work (Vishay Dale R-T Curve 1 shows a ratio of RCOLD to RHOT of 3.266/0.5325 = 6.13). 4081f 18 LTC4081 U W U U APPLICATIO S I FOR ATIO Power conscious designs may want to use thermistors whose room temperature value is greater than 10k. Vishay Dale has a number of values of thermistor from 10k to 100k that follow the “R-T Curve 1.” Using different R-T curves, such as Vishay Dale “R-T Curve 2”, is also possible. This curve, combined with LTC4081 internal thresholds, gives temperature trip points of approximately 0°C (falling) and 40°C (rising), a delta of 40°C. This delta in temperature can be moved in either direction by changing the value of RNOM with respect to RNTC. Increasing RNOM will move both trip points to higher temperatures. To calculate RNOM for a shift to lower temperature for example, use the following equation: RNOM = RCOLD • RNTC at 25 °C 3 . 266 where RCOLD is the resistance ratio of RNTC at the desired cold temperature trip point. If you want to shift the trip points to higher temperatures use the following equation: RNOM = RHOT • RNTC at 25 °C 0 . 5325 where RHOT is the resistance ratio of RNTC at the desired hot temperature trip point. Here is an example using a 100k R-T Curve 2 thermistor from Vishay Dale. The difference between the trip points is 40°C, from before, and we want the cold trip point to be 0°C, which would put the hot trip point at 40°C. The RNOM needed is calculated as follows: RNOM = RCOLD • RNTC at 25 °C 3 . 266 2 . 816 = • 10k = 8 . 62k 3 . 266 The nearest 1% value for RNOM is 8.66k. This is the value used to bias the NTC thermistor to get cold and hot trip points of approximately 0°C and 40°C respectively. To extend the delta between the cold and hot trip points, a resistor, R1, can be added in series with RNTC (see Figure 5). The values of the resistors are calculated as follows: RNOM = RCOLD − RHOT 3 . 266 − 0 . 5325 0 . 5325 ⎛ ⎞ • (RCOLD − RHOT ) − RHOT R1 = ⎜ ⎝ 3 . 266 − 0 . 5325 ⎟⎠ where RNOM is the value of the bias resistor and RHOT and RCOLD are the values of RNTC at the desired temperature trip points. Continuing the example from before with a desired trip point of 50°C: 10k • ( 2.816 − 0.44086 ) RCOLD − RHOT = 3.266 − 0.5325 3.266 − 0.5325 = 8.8k, 8.87k is the nearest 1% value. RNOM = 0.5325 ⎛ ⎞ • ( 2.816 − 0.4086 ) − 0.4086 R1 = 10k • ⎜ ⎝ 3.266 − 0.5325 ⎟⎠ = 604Ω, 604 is the nearest 1% value. VCC RNOM 8.87k 0.76 • VCC 6 – + NTC TOO COLD R1 604Ω – T RNTC 10k 0.35 • VCC + TOO HOT + NTC_ENABLE 0.016 • VCC – 4081 F05 Figure 5. NTC Circuits 4081f 19 LTC4081 U W U U APPLICATIO S I FOR ATIO NTC Trip Point Error SWITCHING REGULATOR When a 1% resistor is used for RHOT, the major error in the 40°C trip point is determined by the tolerance of the NTC thermistor. A typical 100k NTC thermistor has ±10% tolerance. By looking up the temperature coefficient of the thermistor at 40°C, the tolerance error can be calculated in degrees centigrade. Consider the Vishay NTHS0603N01N1003J thermistor, which has a temperature coefficient of –4%/°C at 40°C. Dividing the tolerance by the temperature coefficient, ±5%/(4%/°C) = ±1.25°C, gives the temperature error of the hot trip point. The cold trip point error depends on the tolerance of the NTC thermistor and the degree to which the ratio of its value at 0°C and its value at 40°C varies from 6.14 to 1. Therefore, the cold trip point error can be calculated using the tolerance, TOL, the temperature coefficient of the thermistor at 0°C, TC (in %/°C), the value of the thermistor at 0°C, RCOLD, and the value of the thermistor at 40°C, RHOT. The formula is: Temperature Error(°C) = ⎛ 1+ TOL RCOLD ⎞ − 1⎟ • 100 ⎜⎝ 6.14 • R ⎠ HOT TC For example, the Vishay NTHS0603N01N1003J thermistor with a tolerance of ±5%, TC of –5%/°C and RCOLD/RHOT of 6.13, has a cold trip point error of: ⎛ 1+ 0.05 ⎞ ⎜⎝ 6.14 • 6.13 − 1⎟⎠ • 100 Temperature Error(°C) = −5 = −0.95°C, 1.05°C Setting the Buck Converter Output Voltage The LTC4081 regulator compares the FB pin voltage with an internal 0.8V reference to generate an error signal at the output of the error amplifier. A voltage divider from VOUT to ground (as shown in the Block Diagram) programs the output voltage via FB using the formula: ⎡ R7 ⎤ VOUT = 0 . 8 V • ⎢1 + ⎥ ⎣ R8 ⎦ Keeping the current low (<5μA) in these resistors maximizes efficiency, but making them too low may allow stray capacitance to cause noise problems and reduce the phase margin of the error amp loop. To improve the frequency response, a phase-lead capacitor (CPL) of approximately 10pF can be used. Great care should be taken to route the FB line away from noise sources, such as the inductor or the SW line. Inductor Selection The value of the inductor primarily determines the current ripple in the inductor. The inductor ripple current ΔIL decreases with higher inductance and increases with higher VIN or VOUT: ΔIL = VOUT ⎛ VOUT ⎞ • 1− fOSC • L ⎜⎝ VIN ⎟⎠ 4081f 20 LTC4081 U W U U APPLICATIO S I FOR ATIO Accepting larger values of ΔIL allows the use of low inductances, but results in higher output voltage ripple, greater core losses, and lower output current capability. A reasonable starting point for setting ripple current is ΔIL =0.3 • ILIM, where ILIM is the peak switch current limit. The largest ripple current occurs at the maximum input voltage. To guarantee that the ripple current stays below a specified maximum, the inductor value should be chosen according to the following equation: L≥ VOUT f0 • Δ IL ⎛ VOUT ⎞ • ⎜ 1− ⎟ ⎜⎝ VIN(MAX ) ⎟⎠ For applications with VOUT = 1.8V, the above equation suggests that an inductor of at least 6.8μH should be used for proper operation. Many different sizes and shapes of inductors are available from numerous manufacturers. To maximize efficiency, choose an inductor with a low DC resistance. Keep in mind that most inductors that are very thin or have a very small volume typically have much higher core and DCR losses and will not give the best efficiency. Also choose an inductor with a DC current rating at least 1.5 times larger than the peak inductor current limit to ensure that the inductor does not saturate during normal operation. To minimize radiated noise use a toroid or shielded pot core inductor in ferrite or permalloy materials. Table 1 shows a list of several inductor manufacturers. Table 1. Recommended Surface Mount Inductor Manufacturers Coilcraft www.coilcraft.com Sumida www.sumida.com Murata www.murata.com Toko www.tokoam.com Input and Output Capacitor Selection Since the input current waveform to a buck converter is a square wave, it contains very high frequency components. It is strongly recommended that a low equivalent series resistance (ESR) multilayer ceramic capacitor be used to bypass the BAT pin which is the input for the converter. Tantalum and aluminum capacitors are not recommended because of their high ESR. The value of the capacitor on BAT directly controls the amount of input voltage ripple for a given load current. Increasing the size of this capacitor will reduce the input ripple. To prevent large VOUT voltage steps during transient load conditions, it is also recommended that a ceramic capacitor be used to bypass VOUT. A typical value for this capacitor is 4.7μF. Multilayer Ceramic Chip Capacitors (MLCC) typically have exceptional ESR performance. MLCCs combined with a carefully laid out board with an unbroken ground plane will yield very good performance and low EMI emissions. 4081f 21 LTC4081 U W U U APPLICATIO S I FOR ATIO There are several types of ceramic capacitors with considerably different characteristics. Y5V ceramic capacitors have apparently higher packing density but poor performance over their rated voltage or temperature ranges. Under given voltage and temperature conditions, X5R and X7R ceramic capacitors should be compared directly by case size rather than specified value for a desired minimum capacitance. Some manufacturers provide excellent data on their websites about achievable capacitance. Table 2 shows a list of several ceramic capacitor manufacturers. Table 2. Recommended Ceramic Capacitor Manufacturers Taiyo Yuden www.t-yuden.com AVX www.avxcorp.com Murata www.murata.com TDK www.tdk.com Board Layout Considerations To be able to deliver maximum charge current under all conditions, it is critical that the exposed metal pad on the backside of the LTC4081’s package has a good thermal contact to the PC board ground. Correctly soldered to a 2500mm2 double-sided 1 oz. copper board, the LTC4081 has a thermal resistance of approximately 43°C/W. Failure to make thermal contact between the exposed pad on the backside of the package and the copper board will result in thermal resistance far greater than 43°C/W. Furthermore due to its high frequency switching circuitry, it is imperative that the input capacitor, BAT pin capacitor, inductor, and the output capacitor be as close to the LTC4081 as possible and that there is an unbroken ground plane under the LTC4081 and all of its high frequency components. 4081f 22 LTC4081 U PACKAGE DESCRIPTIO DD Package 10-Lead Plastic DFN (3mm × 3mm) (Reference LTC DWG # 05-08-1699) R = 0.115 TYP 6 0.38 ± 0.10 10 0.675 ±0.05 3.50 ±0.05 1.65 ±0.05 2.15 ±0.05 (2 SIDES) 3.00 ±0.10 (4 SIDES) PACKAGE OUTLINE 1.65 ± 0.10 (2 SIDES) PIN 1 TOP MARK (SEE NOTE 6) (DD) DFN 1103 5 0.25 ± 0.05 0.200 REF 0.50 BSC 2.38 ±0.05 (2 SIDES) 1 0.75 ±0.05 0.00 – 0.05 0.25 ± 0.05 0.50 BSC 2.38 ±0.10 (2 SIDES) BOTTOM VIEW—EXPOSED PAD RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS NOTE: 1. DRAWING TO BE MADE A JEDEC PACKAGE OUTLINE M0-229 VARIATION OF (WEED-2). CHECK THE LTC WEBSITE DATA SHEET FOR CURRENT STATUS OF VARIATION ASSIGNMENT 2. DRAWING NOT TO SCALE 3. ALL DIMENSIONS ARE IN MILLIMETERS 4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE 5. EXPOSED PAD SHALL BE SOLDER PLATED 6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE TOP AND BOTTOM OF PACKAGE 4081f Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights. 23 LTC4081 U TYPICAL APPLICATIO Li-Ion Battery Charger with 1.5V Buck Regulator Buck Efficiency vs Load Current (VOUT = 1.5V) D1 100 R3 510Ω 80 RNOM 100k CHRG EN_BUCK NTC CIN 4.7μF RNTC 100k BAT LTC4081 EN_CHRG T 500mA L1 1OμH CBAT 4.7μF + SW CPL 10pF FB R1 715k MODE GND PROG RPROG 806Ω R2 806k 4.2V Li-Ion/ POLYMER BATTERY VOUT (1.5V/300mA) COUT 4.7μF 4081 TA02a EFFICIENCY (%) VCC EFFICIENCY (Burst) EFFICIENCY (PWM) 100 POWER LOSS 10 (PWM) 60 40 20 0 0.01 POWER LOSS (Burst) 1 POWER LOSS (mW) VCC (3.75V TO 5.5V) 1000 VBAT = 3.8V 0.1 VOUT = 1.5V L = 10μH C = 4.7μF 0.01 0.1 1 10 100 1000 LOAD CURRENT (mA) 4081 TA02b RELATED PARTS PART NUMBER DESCRIPTION COMMENTS Battery Chargers LTC3550 Dual Input USB/AC Adapter Li-Ion Battery Charger Synchronous Buck Converter, Efficiency: 93%, Adjustable Output: 600mA, with Adjustable Output 600mA Buck Converter Charge Current: 950mA Programmable, USB Compatible, Automatic Input Power Detection and Selection LTC3550-1 Dual Input USB/AC Adapter Li-Ion Battery Charger Synchronous Buck Converter, Efficiency: 93%, Output: 1.875V at 600mA, with 600mA Buck Converter Charge Current: 950mA Programmable, USB Compatible, Automatic Input Power Detection and Selection LTC4054 Standalone Linear Li-Ion Battery Charger with Integrated Pass Transistor in ThinSOTTM Thermal Regulation Prevents Overheating, C/10 Termination LTC4061 Standalone Li-Ion Charger with Thermistor Interface 4.2V, ±0.35% Float Voltage, Up to 1A Charge Current, 3mm × 3mm DFN Package LTC4061-4.4 Standalone Li-Ion Charger with Thermistor Interface 4.4V (Max), ±0.4% Float Voltage, Up to 1A Charge Current, 3mm × 3mm DFN Package LTC4062 Standalone Linear Li-Ion Battery Charger with Micropower Comparator Up to 1A Charge Current, Charges from USB Port, Thermal Regulation 3mm × 3mm DFN Package LTC4063 Li-Ion Charger with Linear Regulator Up to 1A Charge Current, 100mA, 125mV LDO, 3mm × 3mm DFN Package LTC4080 Standalone 500mA Charger with 300mA Synchronous Buck For 1-Cell Li-Ion/Polymer Batteries; Trickle Charge; Timer Termination +C/10; Thermal Regulation, Buck Output: 0.8V to VBAT, Buck Input: 2.7V to 5.5V, 3mm × 3mm DFN-10 Package Power Management LTC3405/LTC3405A 300mA (IOUT), 1.5MHz, Synchronous Step-Down 95% Efficiency, VIN: 2.7V to 6V, VOUT = 0.8V, IQ = 20μA, ISD < 1μA, DC/DC Converter ThinSOT Package LTC3406/LTC3406A 600mA (IOUT), 1.5MHz, Synchronous Step-Down 95% Efficiency, VIN: 2.5V to 5.5V, VOUT = 0.6V, IQ = 20μA, ISD < 1μA, DC/DC Converter ThinSOT Package LTC3411 1.25A (IOUT), 4MHz, Synchronous Step-Down DC/DC Converter 95% Efficiency, VIN: 2.5V to 5.5V, VOUT = 0.8V, IQ = 60μA, ISD < 1μA, MS Package LTC3440 600mA (IOUT), 2MHz, Synchronous Buck-Boost DC/DC Converter 95% Efficiency, VIN: 2.5V to 5.5V, VOUT = 2.5V, IQ = 25μA, ISD < 1μA, MS Package LTC4411/LTC4412 Low Loss PowerPathTM Controller in ThinSOT Automatic Switching Between DC Sources, Load Sharing, Replaces ORing Diodes LTC4413 Dual Ideal Diode in DFN 2-Channel Ideal Diode ORing, Low Forward On-Resistance, Low Regulated Forward Voltage, 2.5V ≤ VIN ≤ 5.5V ThinSOT and PowerPath are trademarks of Linear Technology Corporation. 24 Linear Technology Corporation 4081f LT 0707 • PRINTED IN USA 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com © LINEAR TECHNOLOGY CORPORATION 2007