® RT8059 1.5MHz, 1A, High Efficiency PWM Step-Down DC/DC Converter General Description Features The RT8059 is a high efficiency Pulse Width Modulated (PWM) step-down DC/DC converter, capable of delivering 1A output current over a wide input voltage range from 2.8V to 5.5V. The RT8059 is ideally suited for portable electronic devices that are powered by 1-cell Li-ion battery or by other power sources within the range, such as cellular phones, PDAs and handy-terminals. Wide Input Voltage from 2.8V to 5.5V Adjustable Output from 0.6V to VIN 1A Output Current 95% Efficiency No Schottky Diode Required 1.5MHz Fixed Frequency PWM Operation Small TSOT-23-5 Package RoHS Compliant and Halogen Free Internal synchronous rectifier with low RDS(ON) dramatically reduces conduction loss at PWM mode. No external Schottky diode is required in practical applications. The RT8059 automatically turns off the synchronous rectifier when the inductor current is low and enters discontinuous PWM mode. This can increase efficiency in light load condition. The RT8059 enters low dropout mode when normal PWM cannot provide regulated output voltage by continuously turning on the upper P-MOSFET. The RT8059 enters shutdown mode and consumes less than 0.1μA when the EN pin is pulled low. The switching ripple can be easily smoothed out by small package filtering elements due to a fixed operation frequency of 1.5MHz. This along with small TSOT-23-5 package provides small PCB area application. Other features include soft-start, lower internal reference voltage with 2% accuracy, over temperature protection, and over current protection. Ordering Information RT8059 Applications NIC Card Cellular Telephones Personal Information Appliances Wireless and DSL Modems MP3 Players Portable Instruments Pin Configurations (TOP VIEW) FB VIN 5 4 2 3 EN GND LX TSOT-23-5 Marking Information BQ= : Product Code BQ=DNN DNN : Date Code Package Type J5 : TSOT-23-5 Lead Plating System G : Green (Halogen Free and Pb Free) Note : Richtek products are : RoHS compliant and compatible with the current requirements of IPC/JEDEC J-STD-020. Suitable for use in SnPb or Pb-free soldering processes. Copyright © 2016 Richtek Technology Corporation. All rights reserved. DS8059-06 May 2016 is a registered trademark of Richtek Technology Corporation. www.richtek.com 1 RT8059 Typical Application Circuit 4 VIN 2.8V to 5.5V VIN CIN 4.7µF LX L 3 CFF RT8059 1 EN FB VOUT R1 COUT 10µF 5 GND 2 R2 Table 1. Suggested Component Values VOUT (V) R1 (k) R2 (k) CFF (pF) L (H) COUT (F) X5R 16V 0805 1 38.3 56.2 22 to 39 1.5 10 1.2 56 56 15 to 39 1.5 10 1.8 113 56.2 0 to 8.2 2.2 10 2.5 178 56 0 to 12 2.2 10 3.3 249 54.9 0 to 8.2 2.2 10 Note : All the input and output capacitors are the suggusted values, refering to the effective capacitances, subject to any de-rating effect, like a DC Bias. Functional Pin Description Pin No. 1 2 3 4 5 Pin Name EN GND LX VIN FB Pin Function Chip Enable (Active High). Do not leave the EN pin floating. Ground. Switch Node. Power Input. Feedback Input Pin. Copyright © 2016 Richtek Technology Corporation. All rights reserved. www.richtek.com 2 is a registered trademark of Richtek Technology Corporation. DS8059-06 May 2016 RT8059 Function Block Diagram VIN EN RS1 OSC & Shutdown Control Current Limit Detector Slope Compensation Current Sense FB Control Logic PWM Comparator Error Amplifier Driver LX RC COMP Zero Detector UVLO VREF Copyright © 2016 Richtek Technology Corporation. All rights reserved. DS8059-06 May 2016 RS2 GND is a registered trademark of Richtek Technology Corporation. www.richtek.com 3 RT8059 Absolute Maximum Ratings (Note 1) VIN to GND -----------------------------------------------------------------------------------------------------------LX to GND ------------------------------------------------------------------------------------------------------------< 30ns ----------------------------------------------------------------------------------------------------------------- EN, FB to GND ------------------------------------------------------------------------------------------------------ Power Dissipation, PD @ TA = 25°C TSOT-23-5 ------------------------------------------------------------------------------------------------------------ Package Thermal Resistance (Note 2) TSOT-23-5, θJA ------------------------------------------------------------------------------------------------------ Junction Temperature Range ------------------------------------------------------------------------------------- Lead Temperature (Soldering, 10 sec.) ------------------------------------------------------------------------ Storage Temperature Range ------------------------------------------------------------------------------------- ESD Susceptibility (Note 3) HBM (Human Body Mode) ---------------------------------------------------------------------------------------MM (Machine Mode) ----------------------------------------------------------------------------------------------- Recommended Operating Conditions 6.5V −0.3V to (VIN + 0.3V) −5V to 7.5V VIN + 0.6V 0.392W 255°C/W 150°C 260°C −65°C to 150°C 2kV 200V (Note 4) Supply Input Voltage, VIN ------------------------------------------------------------------------------------------ 2.8V to 5.5V Junction Temperature Range -------------------------------------------------------------------------------------- −40°C to 125°C Ambient Temperature Range -------------------------------------------------------------------------------------- −40°C to 85°C Electrical Characteristics (VIN = 3.6V, VOUT = 2.5V, L = 2.2μH, CIN = 4.7μF, COUT = 10μF, TA = 25°C, unless otherwise specified) Parameter Symbol Test Conditions Min Typ Max Unit Quiescent Current IQ IOUT = 0mA, V FB = VREF + 5% -- 78 -- A Shutdown Current ISHDN EN = GND -- 0.1 1 A Reference Voltage VREF 0.588 0.6 0.612 V Adjustable Output Range VOUT (Note 5) VREF -- VIN 0.2 V Adjustable Output Voltage Accuracy VOUT V IN = VOUT +V to 5.5V, 0A < IOUT < 1A, (Note 6) 3 -- 3 % FB Input Current IFB V FB = VIN 50 -- 50 nA P-MOSFET R ON RDS(ON)_P IOUT = 200mA -- 0.28 -- N-MOSFET RON RDS(ON)_N IOUT = 200mA -- 0.25 -- P-Channel Current Limit ILM_P VIN = 2.8V to 5.5V -- 1.5 -- Logic-High V IH VIN = 2.8V to 5.5V 1.5 -- -- Logic-Low V IL VIN = 2.8V to 5.5V -- -- 0.4 -- 2.3 -- V -- 0.2 -- V 1.2 -- 1.5 150 1.8 -- MHz C 100 -- -- % EN Input Threshold Voltage Under Voltage Lockout Threshold V UVLO Under Voltage Lockout Hysteresis VUVLO Oscillator Frequency Thermal Shutdown Temperature fOSC T SD Max. Duty Cycle DMAX Copyright © 2016 Richtek Technology Corporation. All rights reserved. www.richtek.com 4 IOUT = 100mA A V is a registered trademark of Richtek Technology Corporation. DS8059-06 May 2016 RT8059 Note 1. Stresses beyond those listed “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to absolute maximum rating conditions may affect device reliability. Note 2. θJA is measured at TA = 25°C on a low effective thermal conductivity single-layer test board per JEDEC 51-3. Note 3. Devices are ESD sensitive. Handling precaution recommended. Note 4. The device is not guaranteed to function outside its operating conditions. Note 5. Guaranteed by design. Note 6. ΔV = IOUT x RDS(ON) Copyright © 2016 Richtek Technology Corporation. All rights reserved. DS8059-06 May 2016 is a registered trademark of Richtek Technology Corporation. www.richtek.com 5 RT8059 Typical Operating Characteristics Efficiency vs. Load Current Reference Voltage vs. Input Voltage 100 0.620 IOUT = 0.1A 0.615 80 VIN VIN VIN VIN 70 60 = = = = 3.3V, 5.5V, 3.3V, 5.5V, VOUT VOUT VOUT VOUT = = = = 2.5V 2.5V 1.2V 1.2V Reference Voltage (V) Efficiency (%) 90 50 40 30 20 0.610 0.605 0.600 0.595 0.590 0.585 10 0 0.01 0.580 0.1 1 2.5 3 Load Current (A) Reference Voltage vs. Temperature 0.620 VIN = 3.3V, IOUT = 0.1A Output Voltage (V) Reference Voltage (V) 5 5.5 1.220 0.605 0.600 0.595 0.590 0.585 1.215 1.210 1.205 1.200 1.195 1.190 1.185 1.180 0.580 -50 -25 0 25 50 75 100 0 125 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1 Output Current (A) Temperature (°C) Current Limit vs. Temperature Frequency vs. Temperature 2.1 VIN = 3.3V, VOUT = 1.2V, IOUT = 0.3A VIN = 3.3V, VOUT = 1.2V 1.9 1.60 1.55 Current Limit (A) Frequency (MHz) 1 4.5 VIN = 3.3V 1.225 0.610 1.65 4 Output Voltage vs. Output Current 1.230 0.615 1.70 3.5 Input Voltage (V) 1.50 1.45 1.40 1.35 1.30 1.7 1.5 1.3 1.1 0.9 0.7 1.25 0.5 1.20 -50 -25 0 25 50 75 100 Temperature (°C) Copyright © 2016 Richtek Technology Corporation. All rights reserved. www.richtek.com 6 125 -50 -25 0 25 50 75 100 125 Temperature (°C) is a registered trademark of Richtek Technology Corporation. DS8059-06 May 2016 RT8059 Load Transient Response Load Transient Response VIN = 3.3V, VOUT = 1.2V, IOUT = 0.1A to 1A VIN = 3.3V, VOUT = 1.2V, IOUT = 0.5A to 1A VOUT (50mV/Div) VOUT (50mV/Div) IOUT (500mA/Div) IOUT (500mA/Div) Time (100μs/Div) Time (100μs/Div) Switching Switching VIN = 3.3V, VOUT = 1.2V, IOUT = 1A VOUT (5mV/Div) VOUT (5mV/Div) VLX (2V/Div) VLX (2V/Div) IOUT (1A/Div) IOUT (1A/Div) VEN (2V/Div) Time (250ns/Div) Time (250ns/Div) Power On from EN Power Off from EN VIN = 3.3V, VOUT = 1.2V, IOUT = 1A VIN = 3.3V, VOUT = 1.2V, IOUT = 1A VEN (2V/Div) VOUT (500mV/Div) VOUT (500mV/Div) IOUT (1A/Div) IOUT (1A/Div) Time (500μs/Div) Copyright © 2016 Richtek Technology Corporation. All rights reserved. DS8059-06 May 2016 VIN = 3.3V, VOUT = 1.2V, IOUT = 0.5A Time (500μs/Div) is a registered trademark of Richtek Technology Corporation. www.richtek.com 7 RT8059 Applications Information The basic RT8059 application circuit is shown in Typical Application Circuit. External component selection is determined by the maximum load current and begins with the selection of the inductor value and operating frequency followed by CIN and COUT. current is exceeded. This results in an abrupt increase in inductor ripple current and consequent output voltage ripple. Do not allow the core to saturate! Inductor Selection Toroid or shielded pot cores in ferrite or permalloy materials are small and don't radiate energy but generally cost more than powdered iron core inductors with similar characteristics. The choice of which style inductor to use mainly depends on the price vs size requirements and any radiated field/EMI requirements. For a given input and output voltage, the inductor value and operating frequency determine the ripple current. The ripple current ΔIL increases with higher VIN and decreases with higher inductance. V V ∆IL OUT 1 OUT VIN f L Having a lower ripple current reduces the ESR losses in the output capacitors and the output voltage ripple. Highest efficiency operation is achieved at low frequency with small ripple current. This, however, requires a large inductor. A reasonable starting point for selecting the ripple current is ΔIL = 0.4(IMAX). The largest ripple current occurs at the highest VIN. To guarantee that the ripple current stays below a specified maximum, the inductor value should be chosen according to the following equation : VOUT VOUT 1 L f I V L(MAX) IN(MAX) Inductor Core Selection Once the value for L is known, the type of inductor can be selected. High efficiency converters generally cannot afford the core loss found in low cost powdered iron cores, forcing the use of more expensive ferrite or mollypermalloy cores. Actual core loss is independent of core size for a fixed inductor value but it is very dependent on the inductance selected. As the inductance increases, core losses decrease. Unfortunately, increased inductance requires more turns of wire and therefore, results in higher copper losses. Ferrite designs have very low core losses and are preferred at high switching frequencies, so design goals can concentrate on copper loss and preventing saturation. Ferrite core material saturates “hard”, which means that inductance collapses abruptly when the peak design Copyright © 2016 Richtek Technology Corporation. All rights reserved. www.richtek.com 8 Different core materials and shapes will change the size/ current and price/current relationship of an inductor. CIN and COUT Selection The input capacitance, C IN, is needed to filter the trapezoidal current at the source of the top MOSFET. To prevent large ripple voltage, a low ESR input capacitor sized for the maximum RMS current should be used. RMS current is given by : IRMS IOUT(MAX) VOUT VIN VIN 1 VOUT This formula has a maximum at VIN = 2VOUT, where I RMS = I OUT/2. This simple worst-case condition is commonly used for design because even significant deviations do not result in much difference. Note that ripple current ratings from capacitor manufacturers are often based on only 2000 hours of life which makes it advisable to further derate the capacitor, or choose a capacitor rated at a higher temperature than required. Several capacitors may also be paralleled to meet size or height requirements in the design. The selection of COUT is determined by the effective series resistance (ESR) that is required to minimize voltage ripple and load step transients, as well as the amount of bulk capacitance that is necessary to ensure that the control loop is stable. Loop stability can be checked by viewing the load transient response as described in a later section. The output ripple, ΔVOUT, is determined by : 1 ∆VOUT ∆IL ESR 8fCOUT where f is the switching frequency and ΔIL is the inductor ripple current. is a registered trademark of Richtek Technology Corporation. DS8059-06 May 2016 RT8059 The output ripple is highest at maximum input voltage since ΔIL increases with input voltage. Multiple capacitors placed in parallel may be needed to meet the ESR and RMS current handling requirements. Dry tantalum, special polymer, aluminum electrolytic and ceramic capacitors are all available in surface mount packages. Special polymer capacitors offer very low ESR but have lower capacitance density than other types. Tantalum capacitors have the highest capacitance density but it is important to only use types that have been surge tested for use in switching power supplies. Aluminum electrolytic capacitors have significantly higher ESR but can be used in cost-sensitive applications provided that consideration is given to ripple current ratings and long term reliability. Ceramic capacitors have excellent low ESR characteristics but can have a high voltage coefficient and audible piezoelectric effects. The high Q of ceramic capacitors with trace inductance can also lead to significant ringing. The regulator loop response can be checked by looking at the load transient response. Switching regulators take several cycles to respond to a step in load current. When a load step occurs, VOUT immediately shifts by an amount equal to ΔILOAD (ESR), where ESR is the effective series resistance of COUT. ΔILOAD also begins to charge or discharge COUT generating a feedback error signal used by the regulator to return VOUT to its steady-state value. During this recovery time, VOUT can be monitored for overshoot or ringing which would indicate a stability problem. Using Ceramic Input and Output Capacitors Thermal Considerations Higher values, lower cost ceramic capacitors are now becoming available in smaller case sizes. Their high ripple current, high voltage rating and low ESR make them ideal for switching regulator applications. However, care must be taken when these capacitors are used at the input and output. When a ceramic capacitor is used at the input and the power is supplied by a wall adapter through long wires, a load step at the output can induce ringing at the input, VIN. At best, this ringing can couple to the output and be mistaken as loop instability. At worst, a sudden inrush of current through the long wires can potentially cause a voltage spike at VIN large enough to damage the part. For continuous operation, do not exceed absolute maximum junction temperature. The maximum power dissipation depends on the thermal resistance of the IC package, PCB layout, rate of surrounding airflow, and difference between junction and ambient temperature. The maximum power dissipation can be calculated by the following formula : Output Voltage Setting The resistive voltage divider allows the FB pin to sense a fraction of the output voltage as shown in Figure 1. VOUT R1 FB RT8059 R2 GND For adjustable voltage mode, the output voltage is set by an external resistive voltage divider according to the following equation : VOUT VREF (1 R1) R2 where VREF is the internal reference voltage (0.6V typ.) Checking Transient Response PD(MAX) = (TJ(MAX) − TA) / θJA where TJ(MAX) is the maximum junction temperature, TA is the ambient temperature, and θJA is the junction to ambient thermal resistance. For recommended operating condition specifications of the RT8059, the maximum junction temperature is 125°C and TA is the ambient temperature. The junction to ambient thermal resistance, θJA, is layout dependent. For TSOT23-5 packages, the thermal resistance, θJA, is 255°C/W on a standard JEDEC 51-3 single-layer thermal test board. The maximum power dissipation at TA = 25°C can be calculated by the following formula : PD(MAX) = (125°C − 25°C) / (255°C/W) = 0.392W for TSOT-23-5 package Figure 1. Setting Output Voltage Copyright © 2016 Richtek Technology Corporation. All rights reserved. DS8059-06 May 2016 is a registered trademark of Richtek Technology Corporation. www.richtek.com 9 RT8059 Maximum Power Dissipation (W) 1 The maximum power dissipation depends on the operating ambient temperature for fixed T J(MAX) and thermal resistance, θJA. For the RT8059 package, the derating curves in Figure 2 allow the designer to see the effect of rising ambient temperature on the maximum power dissipation. 0.42 0.39 0.36 0.33 0.30 0.27 0.24 0.21 0.18 0.15 0.12 0.09 0.06 0.03 0.00 Layout Considerations Follow the PCB layout guidelines for optimal performance of the RT8059. Keep the trace of the main current paths as short and wide as possible. Place the input capacitor as close as possible to the device pins (VIN and GND). LX node experiences high frequency voltage swings and should be kept in a small area. Keep analog components away from the LX node to prevent stray capacitive noise pick-up. Place the feedback components as close as possible to the FB pin. Single-Layer PCB GND and Exposed Pad must be connected to a strong ground plane for heat sinking and noise protection. 0 25 50 75 100 Ambient Temperature (°C) 125 VIN CIN GND COUT Figure 2. Derating Curves for RT8059 Package VIN 4 3 LX 2 GND 1 EN VOUT L C1 FB R1 VOUT 5 R2 GND Figure 3. PCB Layout Guide Copyright © 2016 Richtek Technology Corporation. All rights reserved. www.richtek.com 10 is a registered trademark of Richtek Technology Corporation. DS8059-06 May 2016 RT8059 Outline Dimension H D L B C b A A1 e Dimensions In Millimeters Dimensions In Inches Symbol Min Max Min Max A 0.700 1.000 0.028 0.039 A1 0.000 0.100 0.000 0.004 B 1.397 1.803 0.055 0.071 b 0.300 0.559 0.012 0.022 C 2.591 3.000 0.102 0.118 D 2.692 3.099 0.106 0.122 e 0.838 1.041 0.033 0.041 H 0.080 0.254 0.003 0.010 L 0.300 0.610 0.012 0.024 TSOT-23-5 Surface Mount Package Richtek Technology Corporation 14F, No. 8, Tai Yuen 1st Street, Chupei City Hsinchu, Taiwan, R.O.C. Tel: (8863)5526789 Richtek products are sold by description only. Richtek reserves the right to change the circuitry and/or specifications without notice at any time. Customers should obtain the latest relevant information and data sheets before placing orders and should verify that such information is current and complete. Richtek cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Richtek product. Information furnished by Richtek is believed to be accurate and reliable. However, no responsibility is assumed by Richtek or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Richtek or its subsidiaries. DS8059-06 May 2016 www.richtek.com 11