EL9110 ® Data Sheet July 15, 2005 Differential Receiver/Equalizer Features The EL9110 is a single channel differential receiver and equalizer. It contains a high speed differential receiver with 5 programmable poles. The outputs of these pole blocks are then summed into an output buffer. The equalization length is set with the voltage on a single pin. The EL9110 also contains a three-statable output, enabling multiple devices to be connected in parallel and used in a multiplexing application. • 150MHz -3dB bandwidth The gain can be adjusted up or down by 6dB using the VGAIN control signal. In addition, a further 6dB of gain can be switched in to provide a matched drive into a cable. FN7305.4 • CAT-5 compensation - 75MHz @ 1000 ft - 125MHz @ 500 ft • 33mA supply current • Differential input range 3.2V • Common mode input range ±4.5V • ±5V supply • Output to within 1.5V of supplies The EL9110 has a bandwidth of 150MHz and consumes just 33mA on ±5V supply. A single input voltage is used to set the compensation levels for the required length of cable. • Available in 16-pin QSOP package The EL9110 is available in the 16-pin QSOP package and is specified for operation over the full -40°C to +85°C temperature range. Applications Ordering Information PART NUMBER • Pb-Free plus anneal available (RoHS compliant) • Twisted-pair receiving/equalizer • KVM (Keyboard/Video/Mouse) • VGA over twisted-pair PACKAGE TAPE & REEL PKG. DWG. # EL9110IU 16-Pin QSOP - MDP0040 EL9110IU-T7 16-Pin QSOP 7” MDP0040 EL9110IU-T13 16-Pin QSOP 13” MDP0040 EL9110IUZ (See Note) 16-Pin QSOP (Pb-free) - MDP0040 EL9110IUZ-T7 (See Note) 16-Pin QSOP (Pb-free) 7” MDP0040 EL9110IUZ-T13 (See Note) 16-Pin QSOP (Pb-free) 13” MDP0040 • Security video Pinout EL9110 (16-PIN QSOP) TOP VIEW CTRL_REF 1 NOTE: Intersil Pb-free plus anneal products employ special Pb-free material sets; molding compounds/die attach materials and 100% matte tin plate termination finish, which are RoHS compliant and compatible with both SnPb and Pb-free soldering operations. Intersil Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020. 1 VCTRL 2 16 CMEXT 15 VS+ VINP 3 14 ENBL VINM 4 13 VSA+ VS- 5 12 VOUT CMOUT 6 11 VSA- VGAIN 7 10 0V LOGIC_REF 8 9 X2 CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright Intersil Americas Inc. 2003, 2005. All Rights Reserved All other trademarks mentioned are the property of their respective owners. EL9110 Absolute Maximum Ratings (TA = 25°C) Supply Voltage between VS+ and VS- . . . . . . . . . . . . . . . . . . . . .12V Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 30mA Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves Pin Voltages . . . . . . . . . . . . . . . . . . . . . . . . . VS- -0.5V to VS+ +0.5V Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C Ambient Operating Temperature . . . . . . . . . . . . . . . .-40°C to +85°C Die Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . 150°C CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typ values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA Electrical Specifications PARAMETER VSA+ = VA+ = +5V, VSA- = VA- = -5V, TA = 25°C, Unless Otherwise Specified DESCRIPTION CONDITIONS MIN TYP MAX UNIT AC PERFORMANCE BW Bandwidth (See Figure 1) 150 MHz SR Slew Rate VIN = -1V to +1V, VG = 0.35, VC = 0, RL = 75 + 75Ω 1.5 V/ns THD Total Harmonic Distortion 10MHz 1VP-P out, VG = 0.35V, X2 gain, VC = 0 -50 dBc DC PERFORMANCE VOS Offset Voltage (bin #1) X2 gain, no equalization -250 Offset Voltage (bin #2) -10 +250 mV CPI9049 mV INPUT CHARACTERISTICS CMIR Common-mode Input Range Common-mode extension off -4/+3.5 V CMIRx Extended CMIR Common-mode extension on ±4.5 V ONOISE Output Noise VG = 0.35, X2 gain, 75 + 75Ω load, VC = 0.6 25 mV RMS CMRR Common-mode Rejection Ratio Measured at 10kHz 60 dB CMRR+ Common-mode Rejection Ratio Measured at 10MHz 50 dB CMBW CM Amplifier Bandwidth 10K || 10pF load 50 MHz CMSLEW CM Slew Rate Measured @ +1V to -1V 100 V/µs CINDIFF Differential Input Capacitance Capacitance VINP to VINM RINDIFF Differential Input Resistance Resistance VINP to VINM CINCM CM Input Capacitance Capacitance VINP = VINM to ground RINCM CM Input Resistance Resistance VINP = VINM to ground +IIN Positive Input Current -IIN VINDIFF 600 fF 2.4 MΩ 1.2 pF 2.8 MΩ DC bias @ VINP = VINM = 0V 1 µA Negative Input Current DC bias @ VINP = VINM = 0V 1 µA Differential Input Range VINP - VINM when slope gain falls to 0.9 3.2 V 1 1 2.5 OUTPUT CHARACTERISTICS VO Output Voltage Swing RL = 150Ω IOUT Output Drive Current RL = 10Ω, VINP = 1V, VINM = 0V, X2 = gain, VG = 0.35 ROUTCM CM Output Resistance at 100kHz DiffGain Differential Gain VC = 0, VG = 0.35, X2 = 5, RL = 75 + 75Ω ISON Supply Current VENBL = 5, VINM = 0 27 34 mA ISOFF Supply Current VENBL = 0, VINM = 0 0.4 0.8 mA PSRR Power Supply Rejection Ratio DC to 100kHz, ±5V supply 50 0.85 ±3.5 V 60 mA 30 Ω 1.0 1.1 SUPPLY 2 60 dB EL9110 Electrical Specifications PARAMETER VSA+ = VA+ = +5V, VSA- = VA- = -5V, TA = 25°C, Unless Otherwise Specified (Continued) DESCRIPTION CONDITIONS MIN TYP MAX UNIT LOGIC CONTROL PINS VHI Logic High Level VIN - VLOGIC ref for guaranteed high level 1.35 VLOW Logic Low Level VIN - VLOGIC ref for guaranteed low level 0.8 V ILOGICH Logic High Input Current VIN = 5V, VLOGIC = 0V 50 µA ILOGICL Logic Low Input Current VIN = 0V, VLOGIC = 0V 15 µA Pin Descriptions PIN NUMBER PIN NAME PIN TYPE PIN FUNCTION 1 CTRL_REF Input Reference voltage for VGAIN and VCTRL pins 2 VCTRL Input Control voltage (0 to 1V) to set equalization 3 VINP Input Positive differential input 4 VINM Input Negative differential input 5 VS- Power -5V to core of chip 6 CMOUT Output Output of common mode voltage present at inputs 7 VGAIN Input Control voltage to set overall gain (0 to 1V) 8 LOGIC_REF Input Reference voltage for all logic signals 9 X2 Logic Input 10 0V 11 VSA- Power -5V to output buffer 12 VOUT Output Single-ended output voltage reference to pin 10 13 VSA+ Power +5V to output buffer 14 ENBL Logic Input 15 VS+ Power 16 CMEXT Logic Input Logic signal; low - gain = 1, high - gain = 2 0V reference for output voltage 3 Logic signal to enable pin; low - disabled, high - enabled +5V to core of chip Logic signal to enable CM range extension; active high V EL9110 Typical Performance Curves 5 -45 THD (dBc) 3 GAIN (dB) -40 VGAIN=0V VCTRL=0V RLOAD=150Ω X2=OFF 1 -1 -3 -50 VGAIN=0V VCTRL=0V VSS=+5V VEE=-5V RLOAD=150Ω X2=OFF INPUT=0dBm -55 -60 -5 1M 10M -65 0.1M 100M 1M FREQUENCY (Hz) 10M 100M FREQUENCY (Hz) FIGURE 1. FREQUENCY RESPONSE FIGURE 2. TOTAL HARMONIC DISTORTION VCTRL=0V VGAIN=0.35V X2=ON CMRR (dBc) 200mV/DIV 100K 2ns/DIV 1M 10M 100M FREQUENCY (Hz) FIGURE 3. RISE TIME GAIN (dB) 2 -20 VGAIN=0.35V VCTRL=0V RLOAD=150Ω X2=ON -40 -PSRR (dB) 4 FIGURE 4. COMMON MODE REJECTION 0 -2 -60 -80 -100 -4 -6 100K VEE=-5V VCTRL=0V VGAIN=0V INPUTS ON GND 1M 10M 100M FREQUENCY (Hz) FIGURE 5. CM AMPLIFIER BANDWIDTH 4 -120 10 100 1K 10K 100K 1M 10M FREQUENCY (Hz) FIGURE 6. PSRR vs FREQUENCY 100M EL9110 Typical Performance Curves (Continued) 0 VCTRL=800mV GAIN (dB) +PSRR (dB) -20 10dB/DIV VCC=5V VCTRL=0V VGAIN=0V INPUTS ON GND -40 -60 -80 VCTRL=0mV 100mV STEP -100 10 100 1K 10K 100K 1M 10M 10M 1M 100M FREQUENCY (Hz) FREQUENCY (Hz) FIGURE 7. PSRR vs FREQUENCY FIGURE 8. GAIN AS THE FUNCTION OF VCTRL JEDEC JESD51-3 LOW EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD 1.4 POWER DISSIPATION (W) 10ns/DIV GROUP DELAY (ns) 100M VCTRL=0mV VCTRL=900mV 1.2 1 791mW 0.8 θJ 0.6 0.4 QS OP 16 58 °C /W A =1 0.2 100mV STEP 1M 10M 0 100M 200M 0 25 FREQUENCY (Hz) 1.8 125 150 FIGURE 10. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE JEDEC JESD51-7 HIGH EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD 1.6 1.4 1.2 1.116W 1 θJ 0.8 0.6 QS OP 16 12 °C /W A =1 0.4 0.2 0 0 25 50 75 85 100 125 150 AMBIENT TEMPERATURE (°C) FIGURE 11. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE 5 75 85 100 AMBIENT TEMPERATURE (°C) FIGURE 9. GROUP DELAY AS THE FUNCTION OF THE FREQUENCY REPONSE CONTROL VOLTAGE (VCTRL) POWER DISSIPATION (W) 50 EL9110 Applications Information Logic Control The EL9110 has three logical input pins, Chip Enable (ENBL), Common Mode Extend (CMEXT), and Switch Gain (X2). The logic circuits all have a nominal threshold of 1.1V above the potential of the logic reference pin. In most applications it is expected that this chip will run from a +5V, 0V, -5V supply system with logic being run between 0V and +5V. In this case the logic reference voltage should be tied to the 0V supply. If the logic is referenced to the -5V rail, then the logic reference should be connected to -5V. The logic reference pin sources about 60µA and this will rise to about 200µA if all inputs are true (positive). The logic inputs all source up to 10µA when they are held at the logic reference level. When taken positive, the inputs sink a current dependent on the high level, up to 50µA for a high level 5V above the reference level. The logic inputs, if not used, should be tied to the appropriate voltage in order to define their state. Control Reference and Signal Reference Analog control voltages are required to set the equalizer and contrast levels. These signals are voltages in the range 0V 1V, which are referenced to the control reference pin. It is expected that the control reference pin will be tied to 0V and the control voltage will vary from 0V to 1V. It is; however, acceptable to connect the control reference to any potential between -5V and 0V to which the control voltages are referenced. The control voltage pins themselves are high impedance. The control reference pin will source between 0µA and 200µA depending on the control voltages being applied. The control reference and logic reference effectively remove the necessity for the 0V rail and operation from ±5V (or 0V and 10V) only is possible. However we still need a further reference to define the 0V level of the single ended output signal. The reference for the output signal is provided by the 0V pin. The output stage cannot pull fully up or down to either supply so it is important that the reference is positioned to allow full output swing. The 0V reference should be tied to a 'quiet ground' as any noise on this pin is transferred directly to the output. The 0V pin is a high impedance pin and draws dc bias currents of a few µA and similar levels of AC current. Common Mode Extension The common mode extension circuitry extends the range of input common mode voltage before the input differential amplifier is overloaded. It does this by reducing the voltage equally at both inputs of the first differential amplifier as the common mode signal rises towards the supply. Similarly, when the common mode input signal goes low, the inputs to the first differential amplifier are raised whilst preserving the 6 differential signal and maintain the amplifier within its common mode operating range. This operation may not always be desirable. A problem occurs because the EL9110 sinks or sources a common mode current though its input pins to create the common mode offset voltage. Assuming the system has been set up so that the differential line has a well-balanced impedance, then a problem will only occur when the common mode impedance to ground is not low. This will occur in systems where the inputs to the EL9110 are AC coupled. In such systems it is recommended that the common mode extension be disabled. In systems where the differential input signal is directly coupled and has its common mode level defined by a low impedance line driver, the common mode extension circuitry can extend the total common mode range by 2V - 3V. Equalizing When transmitting a signal across a twisted pair cable, it is found that the high frequency (above 1MHz) information is attenuated more significantly than the information at low frequencies. The attenuation is predominantly due to resistive skin effect losses and has a loss curve which depends on the resistivity of the conductor, surface condition of the wire and the wire diameter. For the range of high performance twisted pair cables based on 24awg copper wire (Cat 5 etc.) these parameters vary only a little between cable types, and in general cables exhibit the same frequency dependence of loss. (The lower loss cables can be compared with somewhat longer lengths of their more lossy brothers.) This enables a single equalizing law equation to be built into the EL9110. With a control voltage applied between pins 2 and 1, the frequency dependence of the equalization is shown in Figure 8. The equalization matches the cable loss up to about 100MHz. Above this, system gain is rolled off rapidly to reduce noise bandwidth. The roll-off occurs more rapidly for higher control voltages, thus the system (cable + equalizer) bandwidth reduces as the cable length increases. This is desirable, as noise becomes an increasing issue as the equalization increases. The cable loss for 100m, 200m, and 300m of CAT 5 cable, based on manufacturer's loss curves is shown in Figure 13. Thus: • 100m requires VC = 0.2V • 200m requires VC = 0.6V and: • 300m requires VC = 1.0V approximately Contrast By varying the voltage between pins 7 and 1, the gain of the signal path can be changed in the ratio 4:1. The gain change varies almost linearly with control voltage. For normal EL9110 small capacitance differential and common mode capacitance of the input pins of the device makes it possible to connect parallel to the termination resistor. operation it is anticipated the X2 mode will be selected and the output load will be back matched. A unity gain to the output load will then be achieved with a gain control voltage of about 0.35V. This allows the gain to be trimmed up or down by 6dB to compensate for any gain/loss errors that affect the contrast of the video signal. Figure 12 shows an example plot of the gain to the load with gain control voltage. The cable will work as an antenna for all the RF spectrum which is "in the air" where the cable is used. The spectrum, particularly its common mode components, could and will contain high energy level of transients which are above the built-in protection level of the device and easily could damage its inputs. Using a transient protection circuit according to the given application is recommended. 2 1.8 GAIN (V) 1.6 Since the used signal's bandwidth is in the range of 100MHz, for layout and power supply bypassing the roles of RF design should be applied. 1.4 1.2 1 The following picture is taken from the DB9110 demoboard's layout. For better visibility the ground plain is removed. 0.8 0.6 0.4 0 0.2 0.4 0.6 0.8 The ground plane is shown in the following picture. 1 VGAIN FIGURE 12. VARIATION OF GAIN WITH GAIN CONTROL VOLTAGE Circuit and Layout Recommendation The interconnection cable is a transmission line therefore for proper function it should be treated like transmission line, a refection-free termination is necessary. A reflection-free termination is a real "ohmic" resistor with as less as possible reactive parasitic. The traces of the layout, up to the point where of the termination resistor placed, are part of the transmission line which also includes the cable's connector. A connector with a better controlled impedance is an obligation for good picture quality. The termination resistor should be placed close to the inputs of the device's pins (pin 3 and pin 4.) The FIGURE 13. DEMO BOARD LAYOUT The accompanying circuit diagram looks like: R11 330Ω C5 1µF 1 CTRL CMEXT 16 _REF 2 VCTRL R6 R5 R7 R9 VS+ 15 3 VINP ENBL 14 4 VINM VSA+ 13 5 VS- VOUT 12 C7 1µF TP7 6 CMOUT R12 330Ω C8 1nF C10 1µF VSA- 11 7 VGAIN 0V 10 LOGIC _REF X2 9 8 C9 1µF FIGURE 14. CIRCUIT DIAGRAM 7 C11 1nF C6 1nF EL9110 Block Diagram CMOUT CMEXT VS+ VS- COMMON MODE RANGE EXTENDED BIAS CIRCUITRY COMMON MODE RECOVERY DIFFERENTIAL LINE IN X2 LOW FREQ BOOST VSA+ X2/X1 INPUT AMP VINP VINM LOGICREF ENBL CONTRAST VOUT + EQUALIZING BOOST 0V ±6dB RANGE CONTROL ASP VCTRL DIFFERENTIAL TO SINGLE-ENDED VSA- GAIN ASP CTRLREF VGAIN VS- & VSA- connected CONNECTED to -5V TO -5V CONNECTED to +5V TO +5V VS+ & VSA+ connected Typical Application VCTRL 0.1µF 1 CTRL CMEXT 16 _REF 2 VCTRL VS+ 15 3 VINP ENBL 14 4 VINM VSA+ 13 5 VS- VOUT 12 +5V 100 -5V 0.1µF CMOUT +5V 6 CMOUT VSA- 11 7 VGAIN 0V 10 LOGIC 8 _REF X2 9 0.1µF 75 -5V +5V 0.1µF All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems. Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries. For information regarding Intersil Corporation and its products, see www.intersil.com 8