HFA1102 T CT DUC Semiconductor PRO PRODU E T E E L T O U OBS UBSTIT A1109 S F H E , SIBL FA1100 POS H January 1999 File Number 3597.4 600MHz Current Feedback Amplifier with Compensation Pin Features Description • Low Distortion (HD2 at 30MHz) . . . . . . . . . . . . . . . -56dBc The HFA1102 is a high speed wideband current feedback • -3dB Bandwidth . . . . . . . . . . . . . . . . . . . . . . . . . . 600MHz • Compensation Pin for Bandwidth Limiting [ /Title amplifier featuring a compensation pin for bandwidth limiting. (HFA11 Built with Harris’ proprietary complementary bipolar UHF-1 process, it has excellent AC performance and low distortion. 02) /SubBecause the HFA1102 is already unity gain stable, the primary purpose for limiting the bandwidth is to reduce the ject noise (broadband) of the circuit. The bandwidth of the (600MH total HFA1102 may be limited by connecting a capacitor and z Cur- series damping resistor from pin 8 to ground. Typical bandwidths for various values of compensation capacitors rent are shown in the Electrical Specifications section of this Feeddatasheet. back Ampli- A variety of packages and temperature grades are available. See the ordering information below for details. fier with ComPart Number Information pensaPART NUMBER TEMP. PKG. tion Pin) (BRAND) RANGE (oC) PACKAGE NO. /Author HFA1102IB -40 to 85 8 Ld SOIC M8.15 () (H1102I) /KeyHFA11XXEVAL DIP Evaluation Board for High Speed Op Amps words (Harris Pinout HFA1102 Semi(SOIC) conducTOP VIEW tor, single, 8 COMP NC 1 video 7 V+ -IN 2 opera+ 6 OUT +IN 3 tional 5 NC V- 4 amplifier, op amp, high speed video, high slew rate, 5V single supply, 1 • Very Fast Slew Rate . . . . . . . . . . . . . . . . . . . . . . 2000V/µs • Fast Settling Time (0.1%) . . . . . . . . . . . . . . . . . . . . . 11ns • Excellent Gain Flatness - (100MHz) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±0.05dB - (50MHz) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±0.02dB - (30MHz) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±0.01dB • High Output Current . . . . . . . . . . . . . . . . . . . . . . . . . 60mA • Overdrive Recovery . . . . . . . . . . . . . . . . . . . . . . . . <10ns Applications • Low Noise Amplifiers • Video Switching and Routing • Pulse and Video Amplifiers • RF/IF Signal Processing • Flash A/D Driver • Medical Imaging Systems The Op Amps with Fastest Edges INPUT 220MHz SIGNAL OUTPUT (AV = 2) HFA1102 OP AMP 0ns 25ns CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. Copyright © Harris Corporation 1999 HFA1102 Absolute Maximum Ratings Thermal Information Voltage Between V+ and V- . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12V DC Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . VSUPPLY Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5V Output Current (50% Duty Cycle) . . . . . . . . . . . . . . . . . . . . . . 60mA Thermal Resistance (Typical, Note 1) θJA (oC/W) θJC (oC/W) SOIC Package . . . . . . . . . . . . . . . . . . . 170 N/A Maximum Junction Temperature (Plastic Package) . . . . . . . .150oC Maximum Storage Temperature Range . . . . . . . . . . -65oC to 150oC Maximum Lead Temperature (Soldering 10s) . . . . . . . . . . . . 300oC (SOIC - Lead Tips Only) Operating Conditions Temperature Range . . . . . . . . . . . . . . . . . . . . . . . . . . -40oC to 85oC CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. NOTE: 1. θJA is measured with the component mounted on an evaluation PC board in free air. VSUPPLY = ±5V, AV = +1, RF = 510Ω, RL = 100Ω, CCOMP = 0pF, Unless Otherwise Specified Electrical Specifications TEST CONDITIONS TEMP. (oC) MIN TYP MAX UNITS 25 - 2 6 mV Full - - 10 mV Full - 10 - µV/oC 25 40 46 - dB Full 38 - - dB 25 45 50 - dB Full 42 - - dB 25 - 25 40 µA Full - - 65 µA Full - 40 - nA/oC 25 - 20 40 µA/V Full - - 50 µA/V 25 - 12 50 µA Full - - 60 µA Full - 40 - nA/oC 25 - 1 7 µA/V Full - - 10 µA/V 25 - 6 15 µA/V Full - - 27 µA/V Non-Inv. Input Resistance 25 25 50 - kΩ Inv. Input Resistance 25 - 16 30 Ω 25 - 2 - pF Full ±2.5 ±3.0 - V PARAMETER INPUT CHARACTERISTICS Input Offset Voltage Input Offset Voltage Drift ∆VCM = ±2V VIO CMRR ∆VS = ±1.25V VIO PSRR Non-Inv. Input Bias Current +IN = 0V +IBIAS Drift ∆VCM = ±2V +IBIAS CMS Inv. Input Bias Current -IN = 0V -IBIAS Drift ∆VCM = ±2V -IBIAS CMS ∆VS = ±1.25V -IBIAS PSS Input Capacitance Either Input Input Common Mode Range Input Noise Voltage 100kHz 25 - 4 - nV/√Hz +Input Noise Current 100kHz 25 - 18 - pA/√Hz -Input Noise Current 100kHz 25 - 21 - pA/√Hz 500 - kΩ TRANSFER CHARACTERISTICS Open Loop Transimpedance AV = +1, RF = 150Ω, RDAMP = 120Ω, Unless Otherwise Specified 25 2 - HFA1102 VSUPPLY = ±5V, AV = +1, RF = 510Ω, RL = 100Ω, CCOMP = 0pF, Unless Otherwise Specified (Continued) Electrical Specifications TEST CONDITIONS PARAMETER TEMP. (oC) MIN TYP MAX UNITS Linear Phase Deviation DC to 100MHz 25 - 0.6 - Degrees Differential Gain NTSC, RL = 75Ω 25 - 0.03 - % Differential Phase NTSC, RL = 75Ω 25 - 0.03 - Degrees Full 1 - - V/V CCOMP = 0pF 25 - 600 - MHz CCOMP = 1pF 25 - 350 - MHz CCOMP = 3pF 25 - 190 - MHz CCOMP = 7pF 25 - 55 - MHz CCOMP = 0pF 25 - ±0.01 - dB CCOMP = 1pF 25 - ±0.05 - dB CCOMP = 3pF 25 - ±0.10 - dB Gain Flatness To 100MHz 25 - ±0.05 - dB Gain Flatness To 50MHz 25 - ±0.02 - dB 25 ±3.0 ±3.3 - V Full ±2.5 ±3.0 - V 25 50 65 - mA Full 40 60 - mA Minimum Stable Gain Bandwidth Limiting Characteristics -3dB Bandwidth (VOUT = 0.2VP-P, AV = +1) Gain Flatness (To 30MHz) OUTPUT CHARACTERISTICS AV = +2, Unless Otherwise Specified Output Voltage AV = -1 Output Current RL = 50Ω, AV = -1 Closed Loop Output Impedance DC 25 - 0.1 - Ω 2nd Harmonic Distortion 30MHz, VOUT = 2VP-P 25 - -56 - dBc 3rd Harmonic Distortion 30MHz, VOUT = 2VP-P 25 - -80 - dBc 3rd Order Intercept 100MHz 25 - 30 - dBm 1dB Compression 100MHz 25 - 20 - dBm TRANSIENT RESPONSE AV = +1, RF = 150Ω, RDAMP = 120Ω, Unless Otherwise Specified Rise Time VOUT = 2.0V Step 25 - 600 - ps Overshoot VOUT = 2.0V Step 25 - 10 - % Slew Rate AV = +1, VOUT = 5VP-P 25 - 1200 - V/µs AV = +2, VOUT = 5VP-P 25 - 2000 - V/µs 0.1% Settling Time VOUT = 2V to 0V 25 - 11 - ns 0.2% Settling Time VOUT = 2V to 0V 25 - 7 - ns Supply Voltage Range Full ±4.5 - ±5.5 V Supply Current 25 - 21 26 mA Full - - 33 mA POWER SUPPLY CHARACTERISTICS 3 HFA1102 Application Information All current feedback amplifiers require a feedback resistor, even for unity gain applications. The RF, in conjunction with the internal compensation capacitor, sets the dominant pole of the frequency response. Thus, the amplifier's bandwidth is inversely proportional to RF. The HFA1102 design is optimized for a 150Ω RF, at a gain of +1. Decreasing RF in a unity gain application decreases stability, leading to excessive peaking and overshoot. At higher gains the amplifier is more stable, so RF can be decreased in a trade-off of stability for bandwidth. 500Ω 500Ω Optimum Feedback Resistor (RF) VH 50Ω 1 8 2 7 0.1µF 10µF +5 50Ω IN 10µF 3 6 4 5 OUT VL 0.1µF GND GND -5V TOP LAYOUT Bandwidth Limiting The bandwidth of the HFA1102 may be limited by connecting a resistor (RDAMP) and capacitor in series from pin 8 to GND. The series resister is required to damp the interaction between the package parasitics and CCOMP. Typical bandwidths for various values of compensation capacitor are shown in the specification tables. Because the HFA1102 is already unity gain stable, the main reason for limiting the bandwidth is to reduce the total noise (broadband) of the circuit. Additionally, compensating the HFA1102 allows the use of a lower value RF for a given gain. The decreased bandwidth due to CCOMP offsets the bandwidth increase from the lower RF, keeping the amplifier stable. Reducing RF provides the double benefits of reduced DC errors (-IB × RF) and reduced total noise (INI × RF and 4KTRF). VH 1 +IN OUT VL V+ VGND BOTTOM LAYOUT PC Board Layout The frequency performance of this amplifier depends a great deal on the amount of care taken in designing the PC board. The use of low inductance components such as chip resistors and chip capacitors is strongly recommended, while a solid ground plane is a must! Attention should be given to decoupling the power supplies. A large value (10µF) tantalum in parallel with a small value chip (0.1µF) capacitor works well in most cases. An example of a good high frequency layout is the Evaluation Board shown. 600 6 4 CC = 3pF CC = 7pF 0.6 0.06 CC = 0pF 180 CC = 1pF PHASE CC = 3pF CC = 7pF Evaluation Board The HFA1102 may be evaluated using the HFA11XX Evaluation Board which is available from your local sales office (part number HFA11XXEVAL). RDAMP and CCOMP should be connected in series from the socket pin to the GND plane. The trace from pin 8 to the VH connector should be cut near the socket to remove this parallel capacitance.The layout and schematic of the board are shown below: AV = -1 CC = 0pF CC = 1pF 60 135 90 45 0 0.01 0.1 0.3 0.6 1 3 6 10 30 60 100 300 600 FREQUENCY (MHz) FIGURE 2. OPEN LOOP TRANSIMPEDANCE FOR VARIOUS COMPENSATION CAPACITORS PHASE (DEGREES) Care must also be taken to minimize the capacitance to ground seen by the amplifier’s inverting input. The larger this capacitance, the worse the gain peaking, resulting in pulse overshoot and possible instability. To this end, it is recommended that the ground plane be removed under traces connected to pin 2, and connections to pin 2 should be kept as short as possible. FIGURE 1. EVALUATION BOARD SCHEMATIC AND LAYOUT GAIN (kΩ) Terminated microstrip signal lines are recommended at the input and output of the device. Output capacitance, such as that resulting from an improperly terminated transmission line will degrade the frequency response of the amplifier and may cause oscillations. In most cases, the oscillation can be avoided by placing a resistor in series with the output.