MCP16301/MCP16301H Data Sheet

MCP16301/H
High-Voltage Input Integrated Switch Step-Down Regulator
Features
General Description
• Up to 96% Typical Efficiency
• Input Voltage Range:
- 4.0V to 30V (MCP16301)
- 4.7V to 36V (MCP16301H)
• Output Voltage Range: 2.0V to 15V
• 2% Output Voltage Accuracy
• Qualification: AEC-Q100 Rev G, Grade 1
(-40°C to +125°C)
• Integrated N-Channel Buck Switch: 460 m
• Minimum 600 mA Output Current Over All Input
Voltage Range (See Figure 2-6 for Maximum
Output Current vs. VIN):
- up to 1A output current at 3.3V, 5V and 12V
VOUT, SOT-23 package at +25°C ambient
temperature
• 500 kHz Fixed Frequency
• Adjustable Output Voltage
• Low Device Shutdown Current
• Peak Current Mode Control
• Internal Compensation
• Stable with Ceramic Capacitors
• Internal Soft-Start
• Cycle-by-Cycle Peak Current Limit
• Undervoltage Lockout (UVLO): 3.5V
• Overtemperature Protection
• Available Package: SOT-23-6
The MCP16301/H devices are highly integrated,
high-efficiency, fixed-frequency, step-down DC-DC
converters in a popular 6-pin SOT-23 package that
operates from input voltage sources up to 36V.
Integrated features include a high-side switch,
fixed-frequency peak current mode control, internal
compensation, peak current limit and overtemperature
protection. Minimal external components are
necessary to develop a complete step-down DC-DC
converter power supply.
Applications
• PIC® Microcontroller and dsPIC® Digital Signal
Controller Bias Supply
• 24V Industrial Input DC-DC Conversion
• Set-Top Boxes
• DSL Cable Modems
• Automotive
• Wall Cube Regulation
• SLA Battery-Powered Devices
• AC-DC Digital Control Power Source
• Power Meters
• D2 Package Linear Regulator Replacement
- See Figure 5-2
• Consumer
• Medical and Health Care
• Distributed Power Supplies
 2011-2015 Microchip Technology Inc.
High converter efficiency is achieved by integrating the
current-limited, low-resistance, high-speed N-Channel
MOSFET and associated drive circuitry. High
switching frequency minimizes the size of external
filtering components, resulting in a small solution size.
The MCP16301/H devices can supply 600 mA of
continuous current while regulating the output voltage
from 2.0V to 15V. An integrated, high-performance
peak current mode architecture keeps the output
voltage tightly regulated, even during input voltage
steps and output current transient conditions that are
common in power systems.
The EN input is used to turn the device on and off.
While turned off, only a few micro amps of current are
consumed from the input for power shedding and load
distribution applications.
Output voltage is set with an external resistor divider.
The MCP16301/H devices are offered in a
space-saving SOT-23-6 surface mount package.
Package Type
MCP16301/H
6-Lead SOT-23
BOOST 1
6
SW
GND 2
5
VIN
4
EN
VFB
3
DS20005004D-page 1
MCP16301/H
Typical Applications
1N4148
VIN
4.7V to 36V
CBOOST L1
100 nF 15 µH
Boost
VIN
CIN
10 µF
SW
COUT
2 x 10 µF
40V
Schottky
Diode
EN
VOUT
3.3V @ 600 mA
31.6 k
VFB
GND
10 k
1N4148
VIN
6.0V to 36V
CBOOST L1
100 nF 22 µH
Boost
VIN
CIN
10 µF
SW
40V
Schottky
Diode
EN
VOUT
5.0V @ 600 mA
COUT
2 x 10 µF
52.3 k
VFB
GND
10 k
100
VOUT = 5.0V
90
Efficiency (%)
80
70
VOUT = 3.3V
60
50
VIN = 12V
40
30
20
10
0
10
100
1000
IOUT (mA)
DS20005004D-page 2
 2011-2015 Microchip Technology Inc.
MCP16301/H
1.0
ELECTRICAL
CHARACTERISTICS
† Notice: Stresses above those listed under “Maximum
Ratings” may cause permanent damage to the device.
This is a stress rating only and functional operation of
the device at those or any other conditions above those
indicated in the operational sections of this
specification is not intended. Exposure to maximum
rating conditions for extended periods may affect
device reliability.
Absolute Maximum Ratings †
VIN, SW ............................................................... -0.5V to 40V
BOOST – GND ................................................... -0.5V to 46V
BOOST – SW Voltage........................................ -0.5V to 6.0V
VFB Voltage ........................................................ -0.5V to 6.0V
EN Voltage ............................................. -0.5V to (VIN + 0.3V)
Output Short-Circuit Current ................................. Continuous
Power Dissipation ....................................... Internally Limited
Storage Temperature ................................... -65°C to +150°C
Ambient Temperature with Power Applied ... -40°C to +125°C
Operating Junction Temperature.................. -40°C to +150°C
ESD Protection On All Pins:
HBM ................................................................. 3 kV
MM ..................................................................200V
DC CHARACTERISTICS
Electrical Characteristics: Unless otherwise indicated, TA = +25°C, VIN = VEN = 12V, VBOOST – VSW = 3.3V,
VOUT = 3.3V, IOUT = 100 mA, L = 15 µH, COUT = CIN = 2 x 10 µF X7R ceramic capacitors.
Boldface specifications apply over the TA range of -40oC to +125oC.
Parameters
Sym.
Min.
Typ.
Max.
Units
Input Voltage
VIN
4
—
30
V
Note 1 (MCP16301)
4.7
—
36
V
Note 1 (MCP16301H)
Feedback Voltage
VFB
0.784
0.800
0.816
V
Output Voltage Adjust Range
Feedback Voltage
Line Regulation
Conditions
VOUT
2.0
—
15.0
V
VFB/VFB)/VIN
—
0.01
0.1
%/V
IFB
-250
±10
+250
nA
UVLOSTART
—
3.5
4.0
V
VIN Rising (MCP16301)
—
3.5
4.7
V
VIN Rising (MCP16301H)
VIN Falling
Feedback Input Bias Current
Undervoltage Lockout Start
Note 2
VIN = 12V to 30V
Undervoltage Lockout Stop
UVLOSTOP
2.4
3.0
—
V
Undervoltage Lockout
Hysteresis
UVLOHYS
—
0.5
—
V
Switching Frequency
fSW
425
500
550
kHz
Maximum Duty Cycle
DCMAX
90
95
—
%
Minimum Duty Cycle
DCMIN
—
1
—
%
NMOS Switch On Resistance
RDS(ON)
—
0.46
—

VBOOST – VSW = 3.3V
NMOS Switch Current Limit
IN(MAX)
—
1.3
—
A
VBOOST – VSW = 3.3V
Quiescent Current
IQ
—
2
7.5
mA
VBOOST = 3.3V; Note 3
Quiescent Current - Shutdown
IQ
—
7
10
µA
VOUT = EN = 0V
Maximum Output Current
IOUT
600
—
—
mA
Note 1
EN Input Logic High
VIH
1.4
—
—
V
VIL
—
—
0.4
V
IENLK
—
0.05
1.0
µA
EN Input Logic Low
EN Input Leakage Current
Note 1:
2:
3:
IOUT = 200 mA
VIN = 5V; VFB = 0.7V;
IOUT = 100 mA
VEN = 12V
The input voltage should be > output voltage + headroom voltage; higher load currents increase the input
voltage necessary for regulation. See characterization graphs for typical input to output operating voltage
range and UVLOSTART and UVLOSTOP limits.
For VIN < VOUT, VOUT will not remain in regulation.
VBOOST supply is derived from VOUT.
 2011-2015 Microchip Technology Inc.
DS20005004D-page 3
MCP16301/H
DC CHARACTERISTICS (CONTINUED)
Electrical Characteristics: Unless otherwise indicated, TA = +25°C, VIN = VEN = 12V, VBOOST – VSW = 3.3V,
VOUT = 3.3V, IOUT = 100 mA, L = 15 µH, COUT = CIN = 2 x 10 µF X7R ceramic capacitors.
Boldface specifications apply over the TA range of -40oC to +125oC.
Parameters
Sym.
Min.
Typ.
Max.
Units
Soft-Start Time
tSS
—
300
—
µS
Thermal Shutdown Die
Temperature
TSD
—
150
—
C
TSDHYS
—
30
—
C
Die Temperature Hysteresis
Note 1:
2:
3:
Conditions
EN Low to High,
90% of VOUT
The input voltage should be > output voltage + headroom voltage; higher load currents increase the input
voltage necessary for regulation. See characterization graphs for typical input to output operating voltage
range and UVLOSTART and UVLOSTOP limits.
For VIN < VOUT, VOUT will not remain in regulation.
VBOOST supply is derived from VOUT.
TEMPERATURE SPECIFICATIONS
Electrical Specifications: Unless otherwise indicated, TA = +25°C, VIN = VEN = 12V, VBOOST – VSW = 3.3V,
VOUT = 3.3V
Parameters
Sym.
Min.
Typ.
Max.
Units
Operating Junction Temperature Range
TJ
-40
—
+125
°C
Storage Temperature Range
TA
-65
—
+150
°C
Maximum Junction Temperature
TJ
—
—
+150
°C
JA
—
190.5
—
°C/W
Conditions
Temperature Ranges
Steady State
Transient
Package Thermal Resistances
Thermal Resistance, 6L-SOT-23
DS20005004D-page 4
EIA/JESD51-3 Standard
 2011-2015 Microchip Technology Inc.
MCP16301/H
2.0
TYPICAL PERFORMANCE CURVES
Note:
The graphs and tables provided following this note are a statistical summary based on a limited number of
samples and are provided for informational purposes only. The performance characteristics listed herein
are not tested or guaranteed. In some graphs or tables, the data presented may be outside the specified
operating range (e.g., outside specified power supply range) and therefore outside the warranted range.
Note: Unless otherwise indicated, VIN = EN = 12V, COUT = CIN = 2 X 10 µF, L = 15 µH, VOUT = 3.3V, ILOAD = 200 mA,
TA = +25°C.
100
90
VIN = 16V
VIN = 6V
90
VIN = 12V
70
60
VIN = 30V
Efficiency (%)
Efficiency (%)
80
VOUT = 2.0V
50
40
VOUT = 12.0V
70
60
50
30
0
100
200
FIGURE 2-1:
IOUT.
300
400
IOUT (mA)
500
600
2.0V VOUT Efficiency vs.
0
100
200
300
400
IOUT (mA)
100
VIN = 6V
80
VIN = 12V
70
VIN = 30V
60
VOUT = 3.3V
600
VIN = 16V
90
Efficiency (%)
90
500
12V VOUT Efficiency vs.
FIGURE 2-4:
IOUT.
100
Efficiency (%)
80
40
30
VIN = 30V
VIN = 24V
80
70
VOUT = 15.0V
60
50
50
40
40
30
30
0
100
200
300
400
IOUT (mA)
500
0
600
3.3V VOUT Efficiency vs.
FIGURE 2-2:
IOUT.
100
200
300
400
IOUT (mA)
500
600
15V VOUT Efficiency vs.
FIGURE 2-5:
IOUT.
1400
100
VIN = 6V
VOUT = 3.3V
1200
90
VIN = 12V
80
1000
VIN = 30V
70
60
IOUT (mA)
Efficiency (%)
VIN = 30V
VIN = 24V
VOUT = 5.0V
VOUT = 12V
600
50
400
40
200
30
VOUT = 5V
800
0
0
100
FIGURE 2-3:
IOUT.
200
300
400
IOUT (mA)
500
600
5.0V VOUT Efficiency vs.
 2011-2015 Microchip Technology Inc.
6
12
18
24
30
36
VIN (V)
FIGURE 2-6:
vs. VIN.
Maximum Output Current
DS20005004D-page 5
MCP16301/H
Note: Unless otherwise indicated, VIN = EN = 12V, COUT = CIN = 2 X 10 µF, L = 15 µH, VOUT = 3.3V, ILOAD = 200 mA,
TA = +25°C.
1800
Peak Current Limit (mA)
5
IQ (mA)
4
VOUT = 3.3V
IOUT = 0 mA
3
VIN = 6V
2
VIN = 12V
VIN = 30V
1
1600
VIN = 30V
1400
VIN = 12V
1200
VIN = 6V
1000
800
VOUT = 3.3V
0
600
-40 -25 -10
5 20 35 50 65 80 95 110 125
Ambient Temperature (°C)
FIGURE 2-7:
Temperature.
Input Quiescent Current vs.
-40 -25 -10
FIGURE 2-10:
Peak Current Limit vs.
Temperature; VOUT = 3.3V.
510
VIN = 12V
VOUT = 3.3V
IOUT = 200 mA
500
495
TA = 25°C
VDS = 100 mV
500
490
RDSON (m:)
Switching Frequency (kHz)
505
490
485
480
475
470
480
470
460
450
465
440
460
430
420
455
-40
-20
0
20
40
60
80 100
Ambient Temperature (°C)
3
120
FIGURE 2-8:
Switching Frequency vs.
Temperature; VOUT = 3.3V.
95.4
3.5
4
Boost Voltage (V)
4.5
5
Switch RDSON vs. VBOOST.
FIGURE 2-11:
0.802
95.5
VIN = 5V
IOUT = 200 mA
95.3
95.2
95.1
95
VIN = 12V
VOUT = 3.3V
IOUT = 100 mA
0.801
VFB Voltage (V)
Maximum Duty Cycle (%)
5 20 35 50 65 80 95 110 125
Ambient Temperature (°C)
0.800
0.799
0.798
94.9
0.797
94.8
94.7
0.796
-40 -25 -10
5 20 35 50 65 80 95 110 125
Ambient Temperature (°C)
FIGURE 2-9:
Maximum Duty Cycle vs.
Ambient Temperature; VOUT = 5.0V.
DS20005004D-page 6
-40
-20
FIGURE 2-12:
VOUT = 3.3V.
0
20 40 60 80 100 120
Ambient Temperature (°C)
VFB vs. Temperature;
 2011-2015 Microchip Technology Inc.
MCP16301/H
Voltage (V)
Note: Unless otherwise indicated, VIN = EN = 12V, COUT = CIN = 2 X 10 µF, L = 15 µH, VOUT = 3.3V, ILOAD = 200 mA,
TA = +25°C.
3.80
3.70
3.60
3.50
3.40
3.30
3.20
3.10
3.00
2.90
2.80
2.70
2.60
2.50
UVLO Start
VOUT =
20 mV/DIV
AC coupled
VSW =
5V/DIV
UVLO Stop
IL =
20 mA/DIV
-40 -25 -10
FIGURE 2-13:
Temperature.
5 20 35 50 65 80 95 110 125
Ambient Temperature (°C)
Undervoltage Lockout vs.
1 µs/DIV
FIGURE 2-16:
Waveforms.
Heavy Load Switching
5.00
VIN = 12V
VOUT = 3.3V
IOUT = 100 mA
0.65
0.60
0.55
0.50
0.45
0.40
Minimum Input Voltage (V)
0.70
Enable Threshold Voltage (V)
VOUT = 3.3V
IOUT = 600 mA
VIN = 12V
4.70
To Start
4.40
4.10
3.80
To Run
3.50
3.20
-40 -25 -10
FIGURE 2-14:
Temperature.
VOUT
20 mV/DIV
AC coupled
5 20 35 50 65 80 95 110 125
Ambient Temperature (°C)
EN Threshold Voltage vs.
1
10
100
1000
IOUT (mA)
FIGURE 2-17:
Typical Minimum Input
Voltage vs. Output Current.
VOUT = 3.3V
IOUT = 100 mA
VIN = 12V
VOUT = 3.3V
IOUT = 50 mA
VIN = 12V
VOUT
2V/DIV
VSW
5V/DIV
VEN
2V/DIV
IL
100 mA/DIV
1 µs/DIV
FIGURE 2-15:
Waveforms.
Light Load Switching
 2011-2015 Microchip Technology Inc.
100 µs/DIV
µs/
FIGURE 2-18:
Start-Up From Enable.
DS20005004D-page 7
MCP16301/H
Note: Unless otherwise indicated, VIN = EN = 12V, COUT = CIN = 2 X 10 µF, L = 15 µH, VOUT = 3.3V, ILOAD = 200 mA,
TA = +25°C.
VOUT = 3.3V
IOUT = 100 mA
VIN = 12V
VOUT
1V/DIV
VIN
5V/DIV
100 µs/DIV
FIGURE 2-19:
Start-Up from VIN.
VOUT = 3.3V
IOUT = 100 mA to 600
mA
VOUT
AC coupled
100 mV/DIV
IOUT
200 mA/DIV
100 µs/DIV
FIGURE 2-20:
Load Transient Response.
VOUT = 3.3V
IOUT = 100 mA
VIN = 8V to 12V Step
VOUT
AC coupled
100 mV/DIV
VIN
2V/DIV
10 µs/DIV
FIGURE 2-21:
DS20005004D-page 8
Line Transient Response.
 2011-2015 Microchip Technology Inc.
MCP16301/H
3.0
PIN DESCRIPTIONS
The descriptions of the pins are listed in Table 3-1.
TABLE 3-1:
PIN FUNCTION TABLE
MCP16301/H
SOT-23
Symbol
Description
1
BOOST
2
GND
Boost voltage that drives the internal NMOS control switch. A bootstrap capacitor is
connected between the BOOST and SW pins.
Ground pin.
3
VFB
Output voltage feedback pin. Connect VFB to an external resistor divider to set the
output voltage.
4
EN
Enable pin. Logic high enables the operation. Do not allow this pin to float.
5
VIN
Input supply voltage pin for power and internal biasing.
6
SW
Output switch node. This pin connects to the inductor, the freewheeling diode and the
bootstrap capacitor.
3.1
Boost Pin (BOOST)
The high side of the floating supply used to turn the
integrated N-Channel MOSFET on and off is
connected to the boost pin.
3.2
Ground Pin (GND)
The ground or return pin is used for circuit ground
connection. The length of the trace from the input cap
return, output cap return and GND pin should be made as
short as possible to minimize the noise on the GND pin.
3.3
Feedback Voltage Pin (VFB)
The VFB pin is used to provide output voltage regulation
by using a resistor divider. The VFB voltage will be
0.800V typical with the output voltage in regulation.
3.4
Enable Pin (EN)
The EN pin is a logic-level input used to enable or
disable device switching and to lower the quiescent
current while disabled. A logic high (> 1.4V) will enable
the regulator output. A logic low (< 0.4V) will ensure
that the regulator is disabled.
 2011-2015 Microchip Technology Inc.
3.5
Power Supply Input Voltage Pin
(VIN)
Connect the input voltage source to VIN. The input
source should be decoupled to GND with a
4.7 µF-20 µF capacitor, depending on the impedance
of the source and output current. The input capacitor
provides AC current for the power switch and a stable
voltage source for the internal device power. This
capacitor should be connected as close as possible to
the VIN and GND pins. For lighter load applications, a
1 µF X7R (or X5R, for limited temperature range, -40 to
+85°C) ceramic capacitor can be used.
3.6
Switch Pin (SW)
The Switch Node pin is connected internally to the
N-Channel switch and externally to the SW node
consisting of the inductor and Schottky diode. The SW
node can rise very fast as a result of the internal switch
turning on. The external Schottky diode should be
connected close to the SW node and GND.
DS20005004D-page 9
MCP16301/H
NOTES:
DS20005004D-page 10
 2011-2015 Microchip Technology Inc.
MCP16301/H
4.0
DETAILED DESCRIPTION
4.1
Device Overview
The MCP16301/H devices are high-input voltage
step-down regulators, capable of supplying 600 mA to
a regulated output voltage from 2.0V to 15V. Internally,
the trimmed 500 kHz oscillator provides a fixed
frequency, while the peak current mode control
architecture varies the duty cycle for output voltage
regulation. An internal floating driver is used to turn the
high-side integrated N-Channel MOSFET on and off.
The power for this driver is derived from an external
boost capacitor whose energy is supplied from a fixed
voltage ranging from 3.0V to 5.5V, typically the input or
output voltage of the converter. For applications with an
output voltage outside of this range, such as 12V, the
boost capacitor bias can be derived from the output
using a simple Zener diode regulator.
4.1.1
INTERNAL REFERENCE VOLTAGE
(VREF)
An integrated precise 0.8V reference combined with an
external resistor divider sets the desired converter
output voltage. The resistor divider range can vary
without affecting the control system gain. High-value
resistors consume less current, but are more
susceptible to noise.
4.1.2
4.1.4
ENABLE INPUT
Enable input, (EN), is used to enable and disable the
device. If disabled, the MCP16301/H devices consume
a minimal current from the input. Once enabled, the
internal soft start controls the output voltage rate of rise,
preventing high-inrush current and output voltage
overshoot.
4.1.5
SOFT START
The internal reference voltage rate of rise is controlled
during start-up, minimizing the output voltage overshoot and the inrush current.
4.1.6
UNDERVOLTAGE LOCKOUT
An integrated Undervoltage Lockout (UVLO) prevents
the converter from starting until the input voltage is high
enough for normal operation. The converter will typically
start at 3.5V and operate down to 3.0V. Hysteresis is
added to prevent starting and stopping during start-up,
as a result of loading the input voltage source.
4.1.7
OVERTEMPERATURE
PROTECTION
Overtemperature protection limits the silicon die
temperature to +150°C by turning the converter off. The
normal switching resumes at +120°C.
INTERNAL COMPENSATION
All control system components necessary for stable
operation over the entire device operating range are
integrated, including the error amplifier and inductor
current slope compensation. To add the proper amount
of slope compensation, the inductor value changes
along with the output voltage (see Table 5-1).
4.1.3
EXTERNAL COMPONENTS
External components consist of:
•
•
•
•
•
•
input capacitor
output filter (inductor and capacitor)
freewheeling diode
boost capacitor
boost blocking diode
resistor divider.
The selection of the external inductor, output capacitor,
input capacitor and freewheeling diode is dependent
upon the output voltage and the maximum output
current.
 2011-2015 Microchip Technology Inc.
DS20005004D-page 11
MCP16301/H
VIN
BG
REF
CIN
VOUT
VREG
Boost
Precharge
SS OTEMP
VREF
RTOP
+
Amp
-
FB
RBOT
RCOMP
EN
VOUT
S
-
+
-
HS
Drive
SW
Schottky
Diode
PWM
Latch
Comp
+
Boost Diode
CBOOST
500 kHz OSC
C OUT
R
Precharge
Overtemp
CS
+
+
CCOMP
VREF
BOOST
SHDN all blocks
GND
RSENSE
Slope
Comp
GND
FIGURE 4-1:
4.2
4.2.1
MCP16301/H Block Diagram.
Functional Description
STEP-DOWN OR BUCK
CONVERTER
The MCP16301/H devices are non-synchronous
step-down or buck converters, capable of stepping
input voltages ranging from 4V to 30V (MCP16301) or
36V (MCP16301H) down to 2.0V to 15V for VIN > VOUT.
The integrated high-side switch is used to chop or
modulate the input voltage using a controlled duty cycle
for output voltage regulation. High efficiency is
achieved by using a low-resistance switch, low forward
drop diode, low equivalent series resistance (ESR), an
inductor and a capacitor. When the switch is turned on,
a DC voltage is applied to the inductor (VIN – VOUT),
resulting in a positive linear ramp of inductor current.
When the switch turns off, the applied inductor voltage
is equal to -VOUT, resulting in a negative linear ramp of
inductor current (ignoring the forward drop of the
Schottky diode).
For steady-state, continuous inductor current
operation, the positive inductor current ramp must
equal the negative current ramp in magnitude. While
operating in steady state, the switch duty cycle must be
equal to the relationship of VOUT/VIN for constant
output voltage regulation, under the condition that the
inductor current is continuous or never reaches zero.
For discontinuous inductor current operation, the
steady-state duty cycle will be less than VOUT/VIN to
maintain voltage regulation. The average of the
DS20005004D-page 12
chopped input voltage or SW node voltage is equal to
the output voltage, while the average of the inductor
current is equal to the output current.
IL
VOUT
SW
VIN
+
-
Schottky
Diode
L
COUT
IL
IOUT
0
VIN
SW
VOUT
on
on
on
off
off
Continuous Inductor Current Mode
IL
0
IOUT
VIN
SW
on
on
off
off
on
Discontinuous Inductor Current Mode
FIGURE 4-2:
Step-Down Converter.
 2011-2015 Microchip Technology Inc.
MCP16301/H
4.2.2
PEAK CURRENT MODE CONTROL
The MCP16301/H devices integrate a Peak Current
Mode Control architecture, resulting in superior AC
regulation while minimizing the number of voltage loop
compensation components, and their size, for
integration. Peak Current Mode Control takes a small
portion of the inductor current, replicates it, and
compares this replicated current sense signal to the
output of the integrated error voltage. In practice, the
inductor current and the internal switch current are
equal during the switch-on time. By adding this peak
current sense to the system control, the step-down
power train system is reduced from a 2nd order to a 1st
order. This reduces the system complexity and
increases its dynamic performance.
For Pulse-Width Modulation (PWM) duty cycles that
exceed 50%, the control system can become bimodal
where a wide pulse followed by a short pulse repeats
instead of the desired fixed pulse width. To prevent this
mode of operation, an internal compensating ramp is
summed into the current shown in Figure 4-1.
4.2.3
PULSE-WIDTH MODULATION
(PWM)
The internal oscillator periodically starts the switching
period, which, for MCP16301, occurs every 2 µs or
500 kHz. With the integrated switch turned on, the
inductor current ramps up until the sum of the current
sense and slope compensation ramp exceeds the
integrated error amplifier output. The error amplifier
output slews up or down to increase or decrease the
inductor peak current feeding into the output LC filter. If
the regulated output voltage is lower than its target, the
inverting error amplifier output rises. This results in an
increase in the inductor current to correct the errors in
the output voltage.
The fixed-frequency duty cycle is terminated when the
sensed inductor peak current, summed with the
internal slope compensation, exceeds the output
voltage of the error amplifier. The PWM latch is reset by
turning off the internal switch and preventing it from
turning on until the beginning of the next cycle. An
overtemperature signal, or boost cap undervoltage,
can also reset the PWM latch to asynchronously
terminate the cycle.
4.2.4
HIGH-SIDE DRIVE
The MCP16301/H devices feature an integrated
high-side N-Channel MOSFET for high-efficiency
step-down power conversion. An N-Channel MOSFET
is used for its low resistance and size (instead of a
P-Channel MOSFET). The N-Channel MOSFET gate
must be driven above its source to fully turn on the
transistor. A gate-drive voltage above the input is
necessary to turn on the high-side N-Channel. The
high-side drive voltage should be between 3.0V and
5.5V. The N-Channel source is connected to the
inductor and Schottky diode, or switch node.
When the switch is off, the inductor current flows
through the Schottky diode, providing a path to
recharge the boost cap from the boost voltage source:
typically the output voltage for 3.0V to 5.0V output
applications. A boost-blocking diode is used to prevent
current flow from the boost cap back into the output
during the internal switch-on time. Prior to start-up, the
boost cap has no stored charge to drive the switch. An
internal regulator is used to precharge the boost cap.
Once precharged, the switch is turned on and the
inductor current flows. When the switch turns off, the
inductor current free-wheels through the Schottky
diode, providing a path to recharge the boost cap.
Worst-case conditions for recharge occur when the
switch turns on for a very short duty cycle at light load,
limiting the inductor current ramp. In this case, there is
a small amount of time for the boost capacitor to
recharge. For high input voltages there is enough precharge current to replace the boost cap charge. For
input voltages above 5.5V typical, the MCP16301/H
devices will regulate the output voltage with no load.
After starting, the MCP16301/H devices will regulate
the output voltage until the input voltage decreases
below 4V. See Figure 2-17 for device range of operation over input voltage, output voltage and load.
4.2.5
ALTERNATIVE BOOST BIAS
For 3.0V to 5.0V output voltage applications, the boost
supply is typically the output voltage. For applications
with 3.0V < VOUT < 5.0V, an alternative boost supply
can be used.
Alternative boost supplies can be from the input, input
derived, output derived or an auxiliary system voltage.
For low voltage output applications with unregulated
input voltage, a shunt regulator derived from the input
can be used to derive the boost supply. For
applications with high output voltage or regulated high
input voltage, a series regulator can be used to derive
the boost supply.
 2011-2015 Microchip Technology Inc.
DS20005004D-page 13
MCP16301/H
Boost Diode
C1
VZ = 5.1V
BOOST
RSH
CB
EN
VIN
L
MCP16301/H
VOUT
SW
2V
VIN
12V
COUT
FW Diode
CIN
RTOP
FB
GND
RBOT
3.0V to 5.5V External Supply
Boost Diode
BOOST
CB
EN
L
2V
VIN
12V
VOUT
MCP16301/H SW
VIN
COUT
FW Diode
CIN
GND
RTOP
FB
RBOT
FIGURE 4-3:
Shunt and External Boost Supply.
Shunt Boost Supply Regulation is used for low-output
voltage converters operating from a wide ranging input
source. A regulated 3.0V to 5.5V supply is needed to
provide high-side drive bias. The shunt uses a Zener
diode to clamp the voltage within the 3.0V to 5.5V
range using the resistance shown in Figure 4-3.
To calculate the shunt resistance, the boost drive
current can be estimated using Equation 4-1.
DS20005004D-page 14
IBOOST_TYP for 3.3V Boost Supply = 0.6 mA
IBOOST_TYP for 5.0V Boost Supply = 0.8 mA
EQUATION 4-1:
BOOST CURRENT
I BOOST = I BOOST_TYP  1.5 mA
 2011-2015 Microchip Technology Inc.
MCP16301/H
To calculate the shunt resistance, the maximum IBOOST
and IZ currents are used at the minimum input voltage
(Equation 4-2).
EQUATION 4-2:
SHUNT RESISTANCE
V INMIN – V Z
R SH = -----------------------------I Boost + I Z
VZ and IZ can be found on the Zener diode
manufacturer’s data sheet (typical IZ = 1 mA).
Boost Diode VZ = 7.5V
BOOST
CB
EN
L
VIN
12V
VIN
15V to 36V
VOUT
MCP16301/H SW
COUT
FW Diode
CIN
RTOP
FB
GND
RBOT
Boost Diode
BOOST
VZ = 7.5V
CB
EN
L
2V
VIN
12V
VOUT
MCP16301/H SW
VIN
COUT
FW Diode
CIN
GND
RTOP
FB
RBOT
FIGURE 4-4:
Series Regulator Boost Supply.
Series regulator applications use a Zener diode to drop
the excess voltage. The series regulator bias source
can be input or output voltage derived, as shown in
Figure 4-4. For proper circuit operation, the boost
supply must remain between 3.0V and 5.5V at all
times.
 2011-2015 Microchip Technology Inc.
DS20005004D-page 15
MCP16301/H
NOTES:
DS20005004D-page 16
 2011-2015 Microchip Technology Inc.
MCP16301/H
5.0
APPLICATION INFORMATION
5.1
Typical Applications
The MCP16301/H step-down converters operate over
a wide input voltage range, up to 36V maximum.
Typical applications include generating a bias or VDD
voltage for the PIC® microcontroller product line, digital
control system bias supply for AC-DC converters, 24V
industrial input and similar applications.
5.2
Adjustable Output Voltage
Calculations
To calculate the resistor divider values for the
MCP16301/H devices, Equation 5-1 can be used.
RTOP is connected to VOUT, RBOT is connected to GND
and both are connected to the VFB input pin.
EQUATION 5-1:
R TOP
V OUT
= R BOT   ------------- – 1
 V FB

EXAMPLE 5-1:
VOUT
=
3.3V
VFB
=
0.8V
RBOT
=
10 k
RTOP
=
31.25 k (standard value = 31.6 k)
VOUT
=
3.328V (using standard value)
EXAMPLE 5-2:
VOUT
=
5.0V
VFB
=
0.8V
RBOT
=
10 k
RTOP
=
52.5 k (standard value = 52.3 k)
VOUT
=
4.98V (using standard value)
The transconductance error amplifier gain is controlled
by its internal impedance. The external divider resistors
have no effect on system gain, so a wide range of
values can be used. A 10 k resistor is recommended
as a good trade-off for quiescent current and noise
immunity.
 2011-2015 Microchip Technology Inc.
5.3
General Design Equations
The step-down converter duty cycle can be estimated
using Equation 5-2 while operating in Continuous
Inductor Current mode. This equation also counts the
forward drop of the freewheeling diode and internal
N-Channel MOSFET switch voltage drop. As the load
current increases, the switch voltage drop and diode
voltage drop increase, requiring a larger PWM duty
cycle to maintain the output voltage regulation. Switch
voltage drop is estimated by multiplying the switch
current times the switch resistance or RDSON.
EQUATION 5-2:
CONTINUOUS INDUCTOR
CURRENT DUTY CYCLE
 V OUT + V Diode 
D = ------------------------------------------------------ V IN –  I SW  R DSON  
The MCP16301/H devices feature an integrated slope
compensation to prevent the bimodal operation of the
PWM duty cycle. Internally, half of the inductor current
down slope is summed with the internal current sense
signal. For the proper amount of slope compensation,
it is recommended to keep the inductor down-slope
current constant by varying the inductance with VOUT,
where K = 0.22V/µH.
EQUATION 5-3:
K = V OUT  L
For VOUT = 3.3V,
recommended.
TABLE 5-1:
an
inductance
of
15 µH
is
RECOMMENDED INDUCTOR
VALUES
VOUT
K
LSTANDARD
2.0V
0.20
10 µH
3.3V
0.22
15 µH
5.0V
0.23
22 µH
12V
0.21
56 µH
15V
0.22
68 µH
DS20005004D-page 17
MCP16301/H
5.4
Input Capacitor Selection
5.6
The step-down converter input capacitor must filter the
high input ripple current as a result of pulsing or
chopping the input voltage. The input voltage pin of the
MCP16301/H devices is used to supply voltage for the
power train and as a source for internal bias. A low
equivalent series resistance (ESR), preferably a
ceramic capacitor, is recommended. The necessary
capacitance is dependent upon the maximum load
current and source impedance. Three capacitor
parameters to keep in mind are the voltage rating,
equivalent series resistance and the temperature
rating. For wide temperature range applications, a
multi-layer X7R dielectric is mandatory, while for
applications with limited temperature range, a
multi-layer X5R dielectric is acceptable. Typically, input
capacitance between 4.7 µF and 10 µF is sufficient for
most applications. For applications with 100 mA to
200 mA load, a 1 µF X7R capacitor can be used,
depending on the input source and its impedance.
The input capacitor voltage rating should be a minimum
of VIN plus margin. Table 5-2 contains the
recommended range for the input capacitor value.
5.5
Output Capacitor Selection
The output capacitor helps in providing a stable output
voltage during sudden load transients, and reduces the
output voltage ripple. As with the input capacitor, X5R
and X7R ceramic capacitors are well suited for this
application.
The MCP16301/H devices are internally compensated,
so the output capacitance range is limited. See
Table 5-2 for the recommended output capacitor range.
The amount and type of output capacitance and
equivalent series resistance will have a significant
effect on the output ripple voltage and system stability.
The range of the output capacitance is limited due to
the integrated compensation of the MCP16301/H
devices.
Inductor Selection
The MCP16301/H devices are designed to be used
with small surface mount inductors. Several
specifications should be considered prior to selecting
an inductor. To optimize system performance, the
inductance value is determined by the output voltage
(Table 5-1) so the inductor ripple current is somewhat
constant over the output voltage range.
EQUATION 5-4:
INDUCTOR RIPPLE
CURRENT
V
L
 IL = -----L-  t ON
EXAMPLE 5-3:
VIN = 12V
VOUT = 3.3V
IOUT = 600 mA
EQUATION 5-5:
INDUCTOR PEAK
CURRENT
 IL
I LPK = -------- + I OUT
2
Inductor ripple current = 319 mA
Inductor peak current = 760 mA
An inductor saturation rating minimum of 760 mA is
recommended. Low ESR inductors result in higher
system efficiency. A trade-off between size, cost and
efficiency is made to achieve the desired results.
The output voltage capacitor voltage rating should be a
minimum of VOUT, plus margin.
Table 5-2 contains the recommended range for the
input and output capacitor value:
TABLE 5-2:
CAPACITOR VALUE RANGE
Parameter
Min
CIN
2.2 µF
none
COUT
20 µF
none
DS20005004D-page 18
Max
 2011-2015 Microchip Technology Inc.
MCP16301/H
Size
WxLxH
(mm)
ME3220
15
0.52
0.90
3.2x2.5x2.0
LPS4414
15
0.440
0.92
4.3x4.3x1.4
LPS6235
15
0.125
2.00
6.0x6.0x3.5
MSS6132
15
0.135
1.56
6.1x6.1x3.2
Part Number
Value
(µH)
ISAT (A)
MCP16301/H RECOMMENDED
3.3V INDUCTORS
DCR ()
TABLE 5-3:
Coilcraft®
MSS7341
15
0.057
1.78
7.3x7.3x4.1
ME3220
15
0.520
0.8
2.8x3.2x2.0
LPS3015
15
0.700
0.61
3.0x3.0x1.4
Würth Elektronik Group®
744025
15
0.400 0.900 2.8x2.8x2.8
744031
15
0.255 0.450 3.8x3.8x1.65
744042
15
0.175
0.75
5.7
Freewheeling Diode
The freewheeling diode creates a path for inductor
current flow after the internal switch is turned off. The
average diode current is dependent upon output load
current at duty cycle (D). The efficiency of the converter
is a function of the forward drop and speed of the
freewheeling diode. A low forward drop Schottky diode
is recommended. The current rating and voltage rating
of the diode is application dependent. The diode
voltage rating should be a minimum of VIN, plus margin.
For example, a diode rating of 40V should be used for
an application with a maximum input of 30V. The
average diode current can be calculated using
Equation 5-6.
EQUATION 5-6:
DIODE AVERAGE
CURRENT
I D1AVG =  1 – D   I OUT
4.8x4.8x1.8
EXAMPLE 5-4:
Coiltronics®
SD12
15
0.48
SD18
15
0.266 0.831 5.2x5.2x1.8
0.692 5.2x5.2x1.2
SD20
15
0.193 0.718 5.2x5.2x2.0
SD3118
15
0.51
0.75
3.2x3.2x1.8
SD52
15
0.189
0.88
5.2x5.5.2.0
Sumida® Corporation
IOUT
= 0.5A
VIN
= 15V
VOUT
= 5V
D
= 5/15
ID1AVG
= 333 mA
CDPH4D19F
15
0.075
0.66
5.2x5.2x2.0
A 0.5A to 1A diode is recommended.
CDRH3D161H
15
0.328
0.65
4.0x4.0x1.8
TABLE 5-4:
VLF30251
15
0.5
0.47
2.5x3.0x1.2
VLF4012A
15
0.46
0.63
3.5x3.7x1.2
VLF5014A
15
0.28
0.97
4.5x4.7x1.4
B82462G4332M
15
0.097
1.05
6x6x2.2
®
TDK-EPC
App
FREEWHEELING DIODES
Manufacturer
Part
Number
Rating
12 VIN
600 mA
DFLS120L-7
Diodes
Incorporated®
24 VIN
100 mA
Diodes
Incorporated
B0540Ws-7
40V, 0.5A
18 VIN
600 mA
Diodes
Incorporated
B130L-13-F
30V, 1A
5.8
20V, 1A
Boost Diode
The boost diode is used to provide a charging path from
the low-voltage gate drive source, while the switch
node is low. The boost diode blocks the high voltage of
the switch node from feeding back into the output
voltage when the switch is turned on, forcing the switch
node high.
A standard 1N4148 ultra-fast diode is recommended
for its recovery speed, high voltage blocking capability,
availability and cost. The voltage rating required for the
boost diode is VIN.
For low boost voltage applications, a small Schottky
diode with the appropriately rated voltage can be used
to lower the forward drop, increasing the boost supply
for gate drive.
 2011-2015 Microchip Technology Inc.
DS20005004D-page 19
MCP16301/H
5.9
Boost Capacitor
The boost capacitor is used to supply current for the
internal high-side drive circuitry that is above the input
voltage. The boost capacitor must store enough energy
to completely drive the high-side switch on and off. A
0.1 µF X5R or X7R capacitor is recommended for all
applications. The boost capacitor maximum voltage is
5.5V, so a 6.3V or 10V rated capacitor is
recommended. In case of a noise-sensitive application,
an additional resistor in series with the boost capacitor,
that will reduce the high-frequency noise associated
with switching power supplies, can be added. A typical
value for the resistor is 82.
5.10
EXAMPLE 5-5:
VIN
= 10V
VOUT
= 5V
IOUT
= 0.4A
Efficiency
= 90%
Total System Dissipation
= 222 mW
LESR
= 0.15
PL
= 24 mW
Diode VF
= 0.50
D
= 50%
PDiode
= 125 mW
Thermal Calculations
The MCP16301/H devices are available in a SOT-23-6
package. By calculating the power dissipation and
applying the package thermal resistance (JA), the
junction temperature is estimated. The maximum
continuous junction temperature rating for the
MCP16301/H devices is +125°C.
To quickly estimate the internal power dissipation for
the switching step-down regulator, an empirical
calculation using measured efficiency can be used.
Given the measured efficiency, the internal power
dissipation is estimated by Equation 5-7. This power
dissipation includes all internal and external
component losses. For a quick internal estimate,
subtract the estimated Schottky diode loss and inductor
ESR loss from the PDIS calculation in Equation 5-7.
EQUATION 5-7:
TOTAL POWER
DISSIPATION ESTIMATE
OUT  I OUT
V
----------------------------- Efficiency- –  V OUT  I OUT  = PDis
The difference between the first term, input power, and
the second term, power delivered, is the total system
power dissipation. The freewheeling Schottky diode
losses are determined by calculating the average diode
current and multiplying by the diode forward drop. The
inductor losses are estimated by PL = IOUT2 x LESR.
EQUATION 5-8:
DIODE POWER
DISSIPATION ESTIMATE
P Diode = V F    1 – D   I OUT 
DS20005004D-page 20
MCP16301/H internal power dissipation estimate:
PDIS - PL - PDIODE = 73 mW
JA
= 198°C/W
Estimated Junction
Temperature Rise
= +14.5°C
5.11
PCB Layout Information
Good printed circuit board layout techniques are
important to any switching circuitry, and switching
power supplies are no different. When wiring the
switching high-current paths, short and wide traces
should be used. Therefore, it is important that the input
and output capacitors be placed as close as possible to
the MCP16301/H devices to minimize the loop area.
The feedback resistors and feedback signal should be
routed away from the switching node and the switching
current loop. When possible, ground planes and traces
should be used to help shield the feedback signal and
minimize noise and magnetic interference.
A good MCP16301/H layout starts with CIN placement.
CIN supplies current to the input of the circuit when the
switch is turned on. In addition to supplying
high-frequency switch current, CIN also provides a
stable voltage source for the internal MCP16301/H
circuitry. Unstable PWM operation can result if there
are excessive transients or ringing on the VIN pin of the
MCP16301/H devices. In Figure 5-1, CIN is placed
close to pin 5. A ground plane on the bottom of the
board provides a low resistive and inductive path for
the return current. The next priority in placement is the
freewheeling current loop formed by D1, COUT and L,
while strategically placing COUT return close to CIN
return. Next, CB and DB should be placed between the
boost pin and the switch node pin SW. This leaves
space close to the VFB pin of the MCP16301/H devices
to place RTOP and RBOT. RTOP and RBOT are routed
away from the Switch node so noise is not coupled into
the high-impedance VFB input.
 2011-2015 Microchip Technology Inc.
MCP16301/H
Bottom Plane is GND
MCP16301/H
Bottom Trace
RBOT RTOP 10 Ohm
EN
C
1 B DB
REN
VIN
VOUT
D1
L
2 x CIN
GND
COUT
COUT
4
BOOST
EN
GND
DB
1
CB
REN
VIN
5
4V to 30V
CIN
MCP16301/H
Value
CIN
10 µF
COUT
2 x 10 µF
L
15 µH
RTOP
31.6 k
RBOT
10 k
D1
B140
DB
1N4148
CB
100 nF
FIGURE 5-1:
6
VIN
COUT
10 Ohm
D1
GND
2
Component
SW
VOUT
3.3V
L
FB
3
RTOP
RBOT
*Note: The 10 resistor is used with network analyzer, to measure
system gain and phase.
MCP16301/H SOT-23-6 Recommended Layout, 600 mA Design.
 2011-2015 Microchip Technology Inc.
DS20005004D-page 21
MCP16301/H
Bottom Plane is GND
MCP16301/H
RBOT
RTOP
DB
VIN
VOUT
CB
REN
L
CIN
GND
GND
D1
4
COUT
GND
BOOST
EN
DB
1
CB
REN
VIN
4V to 30V
CIN
5
VIN
MCP16301/H
Value
CIN
1 µF
COUT
10 µF
L
15 µH
RTOP
31.6 k
RBOT
10 k
D1
PD3S130
CB
100 nF
REN
1 M
FIGURE 5-2:
DS20005004D-page 22
6
COUT
D1
GND
Component
SW
VOUT
3.3V
L
FB
RTOP
3
2
RBOT
MCP16301/H SOT-23-6 D2 Recommended Layout, 200 mA Design.
 2011-2015 Microchip Technology Inc.
MCP16301/H
6.0
TYPICAL APPLICATION CIRCUITS
Boost Diode
BOOST
CB
EN
L
MCP16301/H
VIN
3.3V
VIN
6V to 30V
VOUT
SW
COUT
FW Diode
CIN
GND
RTOP
FB
RBOT
Component
Value
Manufacturer
Yuden®
Part Number
Comment
CIN
2 x 4.7 µF
Taiyo
Co., Ltd.
UMK325B7475KM-T Cap. 4.7 µF 50V Ceramic X7R 1210 10%
COUT
2 x 10 µF
Taiyo Yuden
Co., Ltd.
JMK212B7106KG-T Cap. 10 µF 6.3V Ceramic X7R 0805 10%
15 µH
Coilcraft®
L
MSS6132-153ML
MSS6132 15 µH Shielded Power Inductor
RTOP
31.6 k
Panasonic®-ECG
ERJ-3EKF3162V
Res. 31.6 k 1/10W 1% 0603 SMD
RBOT
10 k
Panasonic-ECG
ERJ-3EKF1002V
Res. 10.0 k 1/10W 1% 0603 SMD
FW Diode
B140
Diodes
Incorporated®
B140-13-F
Boost Diode
1N4148
Diodes
Incorporated
1N4448WS-7-F
CB
100 nF
AVX® Corporation
0603YC104KAT2A
FIGURE 6-1:
Diode Schottky 40V 1A SMA
Diode Switch 75V 200 mW SOD-323
Cap. 0.1 µF 16V Ceramic X7R 0603 10%
Typical Application 30V VIN to 3.3V VOUT.
 2011-2015 Microchip Technology Inc.
DS20005004D-page 23
MCP16301/H
Boost Diode
BOOST
CB
EN
15V to 30V
VIN
DZ
L
MCP16301/H
VOUT
12V
SW
VIN
COUT
FW Diode
CIN
GND
RTOP
FB
RBOT
Component
Value
Manufacturer
Yuden®
Part Number
Comment
CIN
2 x 4.7 µF
Taiyo
Co., Ltd.
UMK325B7475KM-T Cap. 4.7 uF 50V Ceramic X7R 1210 10%
COUT
2 x 10 µF
Taiyo Yuden
Co., Ltd.
JMK212B7106KG-T
Cap. Ceramic 10 µF 25V X7R 10% 1206
L
56 µH
Coilcraft®
MSS6132-153ML
MSS7341 56 µH Shielded Power Inductor
RTOP
140 k
Panasonic®-ECG
ERJ-3EKF3162V
Res. 140 k 1/10W 1% 0603 SMD
RBOT
10 k
Panasonic-ECG
ERJ-3EKF1002V
Res. 10.0 k 1/10W 1% 0603 SMD
FW Diode
B140
Diodes
Incorporated®
B140-13-F
Boost Diode
1N4148
Diodes
Incorporated
1N4448WS-7-F
CB
100 nF
AVX® Corporation
0603YC104KAT2A
Cap. 0.1 µF 16V Ceramic X7R 0603 10%
DZ
7.5V Zener
Diodes
Incorporated
MMSZ5236BS-7-F
Diode Zener 7.5V 200 mW SOD-323
FIGURE 6-2:
DS20005004D-page 24
Diode Schottky 40V 1A SMA
Diode Switch 75V 200 mW SOD-323
Typical Application 15V – 30V Input; 12V Output.
 2011-2015 Microchip Technology Inc.
MCP16301/H
DZ
Boost Diode
BOOST
CB
EN
L
VIN
VOUT
MCP16301/H SW
12V
2V
VIN
COUT
FW Diode
CIN
GND
RTOP
FB
RBOT
Component
Value
Manufacturer
CIN
10 µF
Yuden®
Taiyo
Co., Ltd.
COUT
22 µF
Taiyo Yuden
Co., Ltd.
JMK316B7226ML-T
L
10 µH
Coilcraft®
MSS4020-103ML
RTOP
15 k
Panasonic®-ECG
ERJ-3EKF1502V
Res. 15.0 k 1/10W 1% 0603 SMD
RBOT
10 k
Panasonic-ECG
ERJ-3EKF1002V
Res. 10.0 k 1/10W 1% 0603 SMD
FW Diode
PD3S
Diodes
Incorporated®
PD3S120L-7
Boost Diode
1N4148
Diodes
Incorporated
1N4448WS-7-F
CB
100 nF
AVX® Corporation
0603YC104KAT2A
Cap. 0.1 µF 16V Ceramic X7R 0603 10%
DZ
7.5V Zener
Diodes
Incorporated
MMSZ5236BS-7-F
Diode Zener 7.5V 200 mW SOD-323
FIGURE 6-3:
Part Number
Comment
EMK316B7106KL-TD Cap. Ceramic 10 µF 16V X7R 10% 1206
Cap. Ceramic 22 µF 6.3V X7R 1206
10 µH Shielded Power Inductor
Diode Schottky 1A 20V POWERDI323
Diode Switch 75V 200 mW SOD-323
Typical Application 12V Input; 2V Output at 600 mA.
 2011-2015 Microchip Technology Inc.
DS20005004D-page 25
MCP16301/H
Boost Diode
DZ
CZ
BOOST
RZ
CB
EN
VIN
L
2.5V
VIN
10V to 16V
VOUT
MCP16301/H SW
COUT
FW Diode
CIN
GND
RTOP
FB
RBOT
Component
Value
Manufacturer
CIN
10 µF
Yuden®
Taiyo
Co., Ltd.
COUT
22 µF
Taiyo Yuden
Co., Ltd.
JMK316B7226ML-T
L
12 µH
Coilcraft®
LPS4414-123MLB
LPS4414 12 µH Shielded Power Inductor
21.5 k
Panasonic®-ECG
ERJ-3EKF2152V
Res. 21.5 k 1/10W 1% 0603 SMD
Res. 10.0 k 1/10W 1% 0603 SMD
RTOP
Part Number
Comment
TMK316B7106KL-TD Cap. Ceramic 10 µF 25V X7R 10% 1206
Cap. Ceramic 22 µF 6.3V X7R 1206
10 k
Panasonic-ECG
ERJ-3EKF1002V
DFLS120
Diodes
Incorporated®
DFLS120L-7
Boost Diode
1N4148
Diodes
Incorporated
1N4448WS-7-F
CB
100 nF
AVX® Corporation
0603YC104KAT2A
Cap. 0.1 µF 16V Ceramic X7R 0603 10%
DZ
7.5V Zener
Diodes
Incorporated
MMSZ5236BS-7-F
Diode Zener 7.5V 200 mW SOD-323
CZ
1 µF
Taiyo Yuden
Co., Ltd.
LMK107B7105KA-T
Cap. Ceramic 1.0 µF 10V X7R 0603
RZ
1 k
Panasonic-ECG
ERJ-8ENF1001V
RBOT
FW Diode
FIGURE 6-4:
DS20005004D-page 26
Diode Schottky 20V 1A POWERDI123
Diode Switch 75V 200 mW SOD-323
Res. 1.00 k 1/4W 1% 1206 SMD
Typical Application 10V to 16V VIN to 2.5V VOUT.
 2011-2015 Microchip Technology Inc.
MCP16301/H
Boost Diode
EN
BOOST
CB
REN
L
MCP16301/H
VIN
4V to 30V
VOUT
3.3V
SW
VIN
COUT
FW Diode
CIN
GND
RTOP
FB
RBOT
Component
Value
Manufacturer
CIN
1 µF
Yuden®
Taiyo
Co., Ltd.
GMK212B7105KG-T Cap. Ceramic 1.0 µF 35V X7R 0805
COUT
10 µF
Taiyo Yuden
Co., Ltd.
JMK107BJ106MA-T
L
15 µH
Coilcraft®
LPS3015-153MLB
Inductor Power 15 µH 0.61A SMD
31.6 k
Panasonic®-ECG
ERJ-2RKF3162X
Res. 31.6 k 1/10W 1% 0402 SMD
RBOT
10 k
Panasonic-ECG
ERJ-3EKF1002V
Res. 10.0 k 1/10W 1% 0603 SMD
FW Diode
B0540
Diodes
Incorporated®
B0540WS-7
Diode Schottky 0.5A 40V SOD323
Boost Diode
1N4148
Diodes
Incorporated
1N4448WS-7-F
Diode Switch 75V 200 mW SOD-323
CB
100 nF
TDK® Corporation
C1005X5R0J104M
Cap. Ceramic 0.10 µF 6.3V X5R 0402
REN
10 M
Panasonic-ECG
ERJ-2RKF1004X
RTOP
FIGURE 6-5:
Part Number
Comment
Cap. Ceramic 10 µF 6.3V X5R 0603
Res. 1.00 M 1/10W 1% 0402 SMD
Typical Application 4V to 30V VIN to 3.3V VOUT at 150 mA.
 2011-2015 Microchip Technology Inc.
DS20005004D-page 27
MCP16301/H
NOTES:
DS20005004D-page 28
 2011-2015 Microchip Technology Inc.
MCP16301/H
7.0
PACKAGING INFORMATION
7.1
Package Marking Information
6-Lead SOT-23
Legend: XX...X
Y
YY
WW
NNN
e3
*
Note:
Example
Part Number
Code
MCP16301T-I/CHY
HTNN
MCP16301T-E/CH
JYNN
MCP16301HT-E/CH
AAANY
MCP16301HT-I/CH
AAAPY
HT25
Customer-specific information
Year code (last digit of calendar year)
Year code (last 2 digits of calendar year)
Week code (week of January 1 is week ‘01’)
Alphanumeric traceability code
Pb-free JEDEC® designator for Matte Tin (Sn)
This package is Pb-free. The Pb-free JEDEC designator ( e3)
can be found on the outer packaging for this package.
In the event the full Microchip part number cannot be marked on one line, it will
be carried over to the next line, thus limiting the number of available
characters for customer-specific information.
 2011-2015 Microchip Technology Inc.
DS20005004D-page 29
MCP16301/H
/$ !$%$
0".!1
!!$
20
&$$"$
$$
,33... 3
0
b
4
N
E
E1
PIN 1 ID BY
LASER MARK
1
2
3
e
e1
D
A
A2
c
φ
L
A1
L1
4$!
!5 $!
6% 9&2!
55##
6
6
67
8
2$
)*+
7%$!"5"2$
*+
7-:$
;
""200!!
<
;
)
$"&&
;
)
7-="$
#
;
""20="$
#
;
<
7-5$
;
/$5$
5
;
/$
$
5
)
;
<
/$
>
;
>
5"0!!
<
;
5"="$
9
;
)
!!"#"$%" "&!
$%!!"&!
$%!!!$'"
!"$
#()
*+, *! !$'$-%!..$%$$!
!"
. +<*
DS20005004D-page 30
 2011-2015 Microchip Technology Inc.
MCP16301/H
Note:
For the most current package drawings, please see the Microchip Packaging Specification located at
http://www.microchip.com/packaging
 2011-2015 Microchip Technology Inc.
DS20005004D-page 31
MCP16301/H
6-Lead Plastic Small Outline Transistor (CHY) [SOT-23]
Note:
For the most current package drawings, please see the Microchip Packaging Specification located at
http://www.microchip.com/packaging
b
4
N
E
E1
PIN 1 ID BY
LASER MARK
1
2
3
e
e1
D
A
A2
c
φ
L
A1
L1
Units
Dimension Limits
Number of Pins
MILLIMETERS
MIN
N
NOM
MAX
6
Pitch
e
0.95 BSC
Outside Lead Pitch
e1
1.90 BSC
Overall Height
A
0.90
–
Molded Package Thickness
A2
0.89
–
1.45
1.30
Standoff
A1
0.00
–
0.15
Overall Width
E
2.20
–
3.20
Molded Package Width
E1
1.30
–
1.80
Overall Length
D
2.70
–
3.10
Foot Length
L
0.10
–
0.60
Footprint
L1
0.35
–
0.80
Foot Angle
I
0°
–
30°
Lead Thickness
c
0.08
–
0.26
Lead Width
b
0.20
–
0.51
Notes:
1. Dimensions D and E1 do not include mold flash or protrusions. Mold flash or protrusions shall not exceed 0.127 mm per side.
2. Dimensioning and tolerancing per ASME Y14.5M.
BSC: Basic Dimension. Theoretically exact value shown without tolerances.
Microchip Technology Drawing C04-028B
DS20005004D-page 32
 2011-2015 Microchip Technology Inc.
MCP16301/H
6-Lead Plastic Small Outline Transistor (CHY) [SOT-23]
Note:
For the most current package drawings, please see the Microchip Packaging Specification located at
http://www.microchip.com/packaging
 2011-2015 Microchip Technology Inc.
DS20005004D-page 33
MCP16301/H
NOTES:
DS20005004D-page 34
 2011-2015 Microchip Technology Inc.
MCP16301/H
APPENDIX A:
REVISION HISTORY
Revision D (April 2015)
The following is the list of modifications:
1.
2.
3.
4.
5.
Updated the Features section.
Updated the input voltage and resistor values in
the Typical Applications section.
Added Figure 2-6.
Updated Examples 5-1 and 5-2.
Updated the RTOP value in Figures 5-1, 5-2, 6-1
and 6-5.
Revision C (November 2013)
The following is the list of modifications:
1.
2.
3.
Added new device to the family (MCP16301H)
and related information throughout the
document.
Added package markings and drawings for the
MCP16301H device.
Updated the Product Identification System
section.
Revision B (November 2012)
The following is the list of modifications:
1.
2.
3.
4.
5.
Added Extended Temperature characteristic.
Added 6-lead SOT-23 package version
(CH code).
Updated the following characterization charts:
Figures 2-7, 2-8, 2-9, 2-10, 2-12, 2-13 and 214.
Updated Section 7.0, Packaging Information.
Updated the Product Identification System
section.
Revision A (May 2011)
• Original Release of this Document.
 2011-2015 Microchip Technology Inc.
DS20005004D-page 35
MCP16301/H
NOTES:
DS20005004D-page 36
 2011-2015 Microchip Technology Inc.
MCP16301/H
PRODUCT IDENTIFICATION SYSTEM
To order or obtain information, e.g., on pricing or delivery, refer to the factory or the listed sales office.
PART NO.
X
-X
/XXX
Device
Tape
and Reel
Temperature
Range
Package
Device:
MCP16301T:
High-Voltage Step-Down Regulator,
Tape and Reel
MCP16301HT: High-Voltage Step-Down Regulator,
Tape and Reel
Temperature Range:
E
I
Package:
CH = Plastic Small Outline Transistor (SOT-23), 6-lead
CHY*= Plastic Small Outline Transistor (SOT-23), 6-lead
*Y
= -40C to +125C
= -40C to +85C
(Extended)
(Industrial)
Examples:
a)
MCP16301T-I/CHY:
b)
MCP16301T-E/CH:
c)
MCP16301HT-E/CH:
Step-Down Regulator,
Tape and Reel,
Industrial Temperature,
6LD SOT-23 package
Step-Down Regulator,
Tape and Reel,
Extended Temperature,
6LD SOT-23 package
Step-Down Regulator,
Tape and Reel,
Extended Temperature,
6LD SOT-23 package
= Nickel palladium gold manufacturing designator.
 2011-2015 Microchip Technology Inc.
DS20005004D-page 37
MCP16301/H
NOTES:
DS20005004D-page 38
 2011-2015 Microchip Technology Inc.
Note the following details of the code protection feature on Microchip devices:
•
Microchip products meet the specification contained in their particular Microchip Data Sheet.
•
Microchip believes that its family of products is one of the most secure families of its kind on the market today, when used in the
intended manner and under normal conditions.
•
There are dishonest and possibly illegal methods used to breach the code protection feature. All of these methods, to our
knowledge, require using the Microchip products in a manner outside the operating specifications contained in Microchip’s Data
Sheets. Most likely, the person doing so is engaged in theft of intellectual property.
•
Microchip is willing to work with the customer who is concerned about the integrity of their code.
•
Neither Microchip nor any other semiconductor manufacturer can guarantee the security of their code. Code protection does not
mean that we are guaranteeing the product as “unbreakable.”
Code protection is constantly evolving. We at Microchip are committed to continuously improving the code protection features of our
products. Attempts to break Microchip’s code protection feature may be a violation of the Digital Millennium Copyright Act. If such acts
allow unauthorized access to your software or other copyrighted work, you may have a right to sue for relief under that Act.
Information contained in this publication regarding device
applications and the like is provided only for your convenience
and may be superseded by updates. It is your responsibility to
ensure that your application meets with your specifications.
MICROCHIP MAKES NO REPRESENTATIONS OR
WARRANTIES OF ANY KIND WHETHER EXPRESS OR
IMPLIED, WRITTEN OR ORAL, STATUTORY OR
OTHERWISE, RELATED TO THE INFORMATION,
INCLUDING BUT NOT LIMITED TO ITS CONDITION,
QUALITY, PERFORMANCE, MERCHANTABILITY OR
FITNESS FOR PURPOSE. Microchip disclaims all liability
arising from this information and its use. Use of Microchip
devices in life support and/or safety applications is entirely at
the buyer’s risk, and the buyer agrees to defend, indemnify and
hold harmless Microchip from any and all damages, claims,
suits, or expenses resulting from such use. No licenses are
conveyed, implicitly or otherwise, under any Microchip
intellectual property rights.
Trademarks
The Microchip name and logo, the Microchip logo, dsPIC,
FlashFlex, flexPWR, JukeBlox, KEELOQ, KEELOQ logo, Kleer,
LANCheck, MediaLB, MOST, MOST logo, MPLAB,
OptoLyzer, PIC, PICSTART, PIC32 logo, RightTouch, SpyNIC,
SST, SST Logo, SuperFlash and UNI/O are registered
trademarks of Microchip Technology Incorporated in the
U.S.A. and other countries.
The Embedded Control Solutions Company and mTouch are
registered trademarks of Microchip Technology Incorporated
in the U.S.A.
Analog-for-the-Digital Age, BodyCom, chipKIT, chipKIT logo,
CodeGuard, dsPICDEM, dsPICDEM.net, ECAN, In-Circuit
Serial Programming, ICSP, Inter-Chip Connectivity, KleerNet,
KleerNet logo, MiWi, MPASM, MPF, MPLAB Certified logo,
MPLIB, MPLINK, MultiTRAK, NetDetach, Omniscient Code
Generation, PICDEM, PICDEM.net, PICkit, PICtail,
RightTouch logo, REAL ICE, SQI, Serial Quad I/O, Total
Endurance, TSHARC, USBCheck, VariSense, ViewSpan,
WiperLock, Wireless DNA, and ZENA are trademarks of
Microchip Technology Incorporated in the U.S.A. and other
countries.
SQTP is a service mark of Microchip Technology Incorporated
in the U.S.A.
Silicon Storage Technology is a registered trademark of
Microchip Technology Inc. in other countries.
GestIC is a registered trademarks of Microchip Technology
Germany II GmbH & Co. KG, a subsidiary of Microchip
Technology Inc., in other countries.
All other trademarks mentioned herein are property of their
respective companies.
© 2011-2015, Microchip Technology Incorporated, Printed in
the U.S.A., All Rights Reserved.
ISBN: 978-1-63277-328-9
QUALITY MANAGEMENT SYSTEM
CERTIFIED BY DNV
== ISO/TS 16949 ==
 2011-2015 Microchip Technology Inc.
Microchip received ISO/TS-16949:2009 certification for its worldwide
headquarters, design and wafer fabrication facilities in Chandler and
Tempe, Arizona; Gresham, Oregon and design centers in California
and India. The Company’s quality system processes and procedures
are for its PIC® MCUs and dsPIC® DSCs, KEELOQ® code hopping
devices, Serial EEPROMs, microperipherals, nonvolatile memory and
analog products. In addition, Microchip’s quality system for the design
and manufacture of development systems is ISO 9001:2000 certified.
DS20005004D-page 39
Worldwide Sales and Service
AMERICAS
ASIA/PACIFIC
ASIA/PACIFIC
EUROPE
Corporate Office
2355 West Chandler Blvd.
Chandler, AZ 85224-6199
Tel: 480-792-7200
Fax: 480-792-7277
Technical Support:
http://www.microchip.com/
support
Web Address:
www.microchip.com
Asia Pacific Office
Suites 3707-14, 37th Floor
Tower 6, The Gateway
Harbour City, Kowloon
China - Xiamen
Tel: 86-592-2388138
Fax: 86-592-2388130
Austria - Wels
Tel: 43-7242-2244-39
Fax: 43-7242-2244-393
China - Zhuhai
Tel: 86-756-3210040
Fax: 86-756-3210049
Denmark - Copenhagen
Tel: 45-4450-2828
Fax: 45-4485-2829
India - Bangalore
Tel: 91-80-3090-4444
Fax: 91-80-3090-4123
France - Paris
Tel: 33-1-69-53-63-20
Fax: 33-1-69-30-90-79
India - New Delhi
Tel: 91-11-4160-8631
Fax: 91-11-4160-8632
Germany - Dusseldorf
Tel: 49-2129-3766400
Atlanta
Duluth, GA
Tel: 678-957-9614
Fax: 678-957-1455
Hong Kong
Tel: 852-2943-5100
Fax: 852-2401-3431
Australia - Sydney
Tel: 61-2-9868-6733
Fax: 61-2-9868-6755
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Tel: 86-10-8569-7000
Fax: 86-10-8528-2104
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Tel: 512-257-3370
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Tel: 86-28-8665-5511
Fax: 86-28-8665-7889
Boston
Westborough, MA
Tel: 774-760-0087
Fax: 774-760-0088
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Tel: 86-23-8980-9588
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Fax: 630-285-0075
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Tel: 216-447-0464
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Tel: 248-848-4000
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Tel: 281-894-5983
Indianapolis
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Tel: 317-773-8323
Fax: 317-773-5453
Los Angeles
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Tel: 949-462-9523
Fax: 949-462-9608
New York, NY
Tel: 631-435-6000
San Jose, CA
Tel: 408-735-9110
Canada - Toronto
Tel: 905-673-0699
Fax: 905-673-6509
China - Dongguan
Tel: 86-769-8702-9880
China - Hangzhou
Tel: 86-571-8792-8115
Fax: 86-571-8792-8116
Germany - Munich
Tel: 49-89-627-144-0
Fax: 49-89-627-144-44
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Tel: 91-20-3019-1500
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Tel: 81-6-6152-7160
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Germany - Pforzheim
Tel: 49-7231-424750
Italy - Milan
Tel: 39-0331-742611
Fax: 39-0331-466781
Japan - Tokyo
Tel: 81-3-6880- 3770
Fax: 81-3-6880-3771
Italy - Venice
Tel: 39-049-7625286
Korea - Daegu
Tel: 82-53-744-4301
Fax: 82-53-744-4302
Netherlands - Drunen
Tel: 31-416-690399
Fax: 31-416-690340
China - Hong Kong SAR
Tel: 852-2943-5100
Fax: 852-2401-3431
Korea - Seoul
Tel: 82-2-554-7200
Fax: 82-2-558-5932 or
82-2-558-5934
China - Nanjing
Tel: 86-25-8473-2460
Fax: 86-25-8473-2470
Malaysia - Kuala Lumpur
Tel: 60-3-6201-9857
Fax: 60-3-6201-9859
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Tel: 86-532-8502-7355
Fax: 86-532-8502-7205
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Tel: 60-4-227-8870
Fax: 60-4-227-4068
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Tel: 86-21-5407-5533
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Philippines - Manila
Tel: 63-2-634-9065
Fax: 63-2-634-9069
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Tel: 86-24-2334-2829
Fax: 86-24-2334-2393
Singapore
Tel: 65-6334-8870
Fax: 65-6334-8850
China - Shenzhen
Tel: 86-755-8864-2200
Fax: 86-755-8203-1760
Taiwan - Hsin Chu
Tel: 886-3-5778-366
Fax: 886-3-5770-955
China - Wuhan
Tel: 86-27-5980-5300
Fax: 86-27-5980-5118
Taiwan - Kaohsiung
Tel: 886-7-213-7828
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Tel: 86-29-8833-7252
Fax: 86-29-8833-7256
Poland - Warsaw
Tel: 48-22-3325737
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Tel: 34-91-708-08-90
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Tel: 46-8-5090-4654
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Tel: 44-118-921-5800
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Tel: 886-2-2508-8600
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Thailand - Bangkok
Tel: 66-2-694-1351
Fax: 66-2-694-1350
01/27/15
DS20005004D-page 40
 2011-2015 Microchip Technology Inc.