Total Power Conversion Solutions for Computer Motherboards Using HIP6017, HIP6019 Controller ICs ® Application Note April 1998 AN9800.1 Author: Bogdan M. Duduman Introduction The evaluation board features a 5-bit DAC-controlled synchronous buck converter targeted at the microprocessor core voltage, an adjustable standard buck converter (HIP6019EVAL1 only) supplying the I/O circuitry, an adjustable linear controller aimed at the GTL bus, and an adjustable linear regulator with built-in pass element to provide power to the clock generator. The HIP6017 is ideally suited for PC applications employing an ATX power supply, while the HIP6019 addresses the same need in PCs using a PS2 power supply or in situations where the 3.3V output of the ATX supply does not provide adequate regulation or transient response. Table 1 summarizes the target design parameters of the four on-board regulator blocks (three in case of HIP6017EVAL1). The four core regulator reference designs presented in Table 2 share much common circuitry and the same printed circuit board. They highlight the operation of the HIP6017/HIP6019 controllers in an embedded motherboard application environment and the difference amongst paired designs resides in the step load capability for given output regulation limits (see Table 1 for such regulation limit examples). While design examples 1 and 2 conform to the stringent requirements of Intel’s converter design guidelines, design examples 1A and 2A account for the practical experience of PC system designers. In contrast to the conservative worst-case specifications published by Intel, practical experience of PC system designers reveals 1 microprocessor core currents 30% lower than the theoretical absolute maximum levels. This experience reflects in the design of the core regulator, as shown in examples 1A and 2A. The design engineer is encouraged to modify the board according to his own experience or specifications, and the evaluation platform is laid out to accommodate this. The core regulator of HIP6017/HIP6019EVAL1 ships populated as design example 1A. +5V +12V THIS BLOCK INCLUDED IN HIP6019 ONLY Keeping pace with today’s high-performance desktop PC architectures, the HIP6017 and HIP6019 controller/regulator ICs respond to the need for increased integration and reduced system-level costs. The Intersil HIP6017 and HIP6019 are complex controllers that integrate one and two, respectively, switching regulators, a linear controller, and a linear regulator in a single 28-lead SOIC package. The switching converters employ voltage-mode control architecture and high circuit performance is insured by the use of high Gain - Bandwidth Product (GBWP) error amplifiers, high-accuracy references, a programmable free-running oscillator, and adaptable shootthrough protection. The ICs offer a full range of protection features including over-current, over-voltage, as well as fault condition signaling and shutdown. All these combined features make the HIP6017 and HIP6019 ideal as total microprocessor point-of-use power supply solution providers [1, 2]. Figure 1 presents a simple block diagram of the HIP6017/HIP6019 application circuit. ADJUSTABLE SYNCHRONOUS BUCK CONTROLLER + DAC + ADJUSTABLE STANDARD BUCK CONTROLLER ADJUSTABLE LINEAR CONTROLLER VID0 VID1 VID2 VID3 VID4 + ADJUSTABLE LINEAR REGULATOR + FIGURE 1. HIP6017/HIP6019 EVAL1 BLOCK DIAGRAM Quick Start Evaluation The inputs of both evaluation platforms will accept either standard power supplies or an ATX-style power supply. The outputs can be exercised using either resistive loads, electronic loads, or the Intel Slot 1 EMT tool. Shielded scope probe test points on the dynamic outputs (core, I/O, and GTL bus) allow for accurate inspection of the output power quality. Before proceeding, please consult Table 1 for the evaluation board’s design envelope characteristics. AUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright © Intersil Americas Inc. 2002. All Rights Reserved Application Note 9800 TABLE 1. HIP6017/HIP6019EVAL1 DESIGN PARAMETERS NOMINAL VOLTAGE (V) STATIC TOLERANCE (±,%) DYNAMIC TOLERANCE (±,%) NOMINAL CURRENT (A) MAXIMUM CURRENT (A) MAXIMUM CURRENT STEP (A) MAXIMUM SLEW RATE (A/μs) VCC_CORE 2.8 2.14 4.28 10 14.2 9.5 30 VCC_L2 3.3 5.0 5.0 5 8 7 1 VCC_VTT 1.5 9.0 9.0 1 4 3 8 VCC_CLK 2.5 4 4 0.1 0.2 N/A N/A OUTPUT TABLE 2. HIP6017/HIP6019EVAL1 CORE REGULATOR DESIGN EXAMPLES REF. DES. EXAMPLE 1 VOUT = 2.8V IOUT = 14.2A IOUT_STEP = 13.5A EXAMPLE 1A VOUT = 2.8V IOUT = 14.2A IOUT_STEP = 9.5A EXAMPLE 2 VOUT = 2.0V IOUT = 16.0A IOUT_STEP = 15.6A EXAMPLE 2A VOUT = 2.0V IOUT = 16.0A IOUT_STEP = 11.0A MOSFETs Q1 Q2 HUF76139 HUF76139 HUF76139 HUF76139 HUF76143 HUF76143 HUF76143 HUF76143 OCSET RESISTOR R2 1.3kΩ 1.3kΩ 1.1kΩ 1.1kΩ OUTPUT INDUCTOR L3 2.9μH (9T of 16AWG on T60-52 core) 2.9μH (9T of 16AWG on T60-52 core) 2.2μH (7T of 16AWG on T68-52A core) 2.2μH (7T of 16AWG on T68-52A core) INPUT CAPACITORS C1-13 4 (EEUFA1A10) 4 (EEUFA1A10) 9 (EEUFA1A10) 8 (EEUFA1A10) OUTPUT CAPACITORS C24-36 9 (EEUFA1A10) 7 (EEUFA1A10) 11 (EEUFA1A10) 8 (EEUFA1A10) OFFSET RESISTOR R9 732kΩ 732kΩ 432kΩ 432kΩ COMPONENT DESCRIPTION On either board, if using an Intel Slot 1 EMT Tool, the core regulator VID jumpers located on the evaluation board are in parallel with the ones located on the tool itself, so remember to de-populate one set of jumpers completely and use the other set to dial-in the desired output voltage. HIP6017EVAL1 The easiest way to power this board is by using an ATX-type computer power supply. Simply plug the appropriate supply connector into the on-board receptacle (J2), connect the outputs (VCC_CLK, VCC_CORE, and VCC_VTT) to the desired loads, and power-up the board. If using standard laboratory power supplies, make sure the power-up sequence follows this order: 3.3V supply, followed by the 5V and 12V supplies in no particular order. This sequence is required by the IC’s sophisticated monitoring and protection circuitry. HIP6019EVAL1 Similarly, the easiest way to power this board is also by using an ATX-type PC power supply. Plug the appropriate output connector into the evaluation board’s input receptacle (J2), connect the desired output loads, and power-up. If using standard laboratory equipment, the input supplies (5V and 12V) do not require any special sequencing. 2 HIP6017/HIP6019EVAL1 Reference The evaluation board is designed to simultaneously meet all the applicable criteria outlined in Table 1 (HIP6017EVAL1 does not provide the 3.3V I/O voltage). The following section highlights some of the most important features of this system’s power solution. ATX Power Supply Control Interface JP5 allows control of the power supply. By placing the jumper in the 1-2 position, the PS-ON (output enable) input of the ATX supply is connected to ground, thus unconditionally enabling the outputs. Placing the jumper in the 2-3 position connects the supply control pin to the drain of Q5 (see Figure 2). When ATX supply is turned on, the 5V stand-by output turns Q5 on and enables the power supply outputs. If FAULT/RT pin goes high, Q6 latches on, thus turning off Q5 and disabling the power supply outputs. Cycling power off and then back on re-enables the power supply. The sole purpose of this circuit is to exemplify a possible interface between the control circuit’s FAULT output and an ATX power supply. In case of an over-voltage event, this circuit disables the input supply much faster than its internal short-circuit protection, thus minimizing any risks of power supply failure. Application Note 9800 Over-Current Protection FAULT/RT ATX CONNECTOR 9 5VSB R26 5.1K J2 JP5 14 3, 5, 7, 13 15, 16, 17 PS-ON 3 2 GND 1 R27 5.1K CR3 1N4148 Q5 Q6 1/2 RF1K49154 1/2 RF1K49154 FIGURE 2. ATX POWER SUPPLY CONTROL CIRCUIT Lossless Output Voltage Droop with Load The switching regulators on the HIP6017/HIP6019EVAL1 boards implement output voltage droop functions, where the output voltage sags proportionately with the output current. Although not necessary for proper circuit operation, this method takes advantage of the static regulation limits to improve the dynamic regulation by expanding the available headroom for transient edge output excursion. In such practical applications, compared to a non-droop implementation, this translates to fewer output capacitors or better regulation for the same type and number of capacitors. Figure 3 details the output voltage characteristics of a converter with 2.3% droop compared to a non-droop implementation. 2.832V WITHOUT DROOP 2.800V 2.768V OUTPUT VOLTAGE WITH DROOP 0.5A OUTPUT CURRENT 14.2A FIGURE 3. OUTPUT VOLTAGE DROOP AT 2.8V DAC SETTING In contrast to droop implementation involving a resistive element placed in the output current path, this method does not involve the additional power loss introduced by the resistor. By moving the voltage regulation point ahead of the output inductor (at the PHASE node), droop becomes equal to the average voltage drop across the output inductor’s DC resistance as well as any distributed resistance. To insure symmetric output voltage excursions about the set voltage in response to load transients, the output voltage is offset above the nominal level by half the calculated droop. 3 The switching regulators within HIP6017 and HIP6019 employ a lossless current sensing technique based on the upper MOSFET’s rDS(ON). During the ON-time of the upper MOSFET, its drain-to-source voltage is compared with a user-adjustable voltage created by an internal current source across ROCSET (i.e., R1, R2 in the schematic). When the MOSFET’s drain-to-source voltage exceeds the preset threshold, the regulator immediately shuts down all outputs and initiates a soft-start cycle. If the condition persists, the third shutdown latches the chip off. Cycling the bias voltage OFF and ON resets the protection circuitry. The linear regulator outputs employ a different method of over-current detection. Given the relatively large rDS(ON) of the pass devices, a short-circuit condition usually translates into a dip in the output voltage. If the output voltage (as sensed at the feedback pin) dips below approximately 75% of the set point, this undervoltage is interpreted as an overcurrent event and the control IC reacts accordingly, shutting down all outputs and cycling the soft-start. The internal regulator is protected by an additional internal output current mirror. Output current exceeding the preset threshold (see data sheet) generates a similar response. Any over-current event on any output is reported by the toggle of the PGOOD output. Over-Voltage Protection Both switching regulator outputs are protected against overvoltage events. The VCC_L2 regulator (standard buck, HIP6019EVAL1 only) has a threshold internally set at 4.3V. The microprocessor core regulator (synchronous buck) has a voltage-tracking over-voltage threshold set at 115% (typically) of the DAC setting. In case of an over-voltage event, the microprocessor core regulator attempts to regulate the output voltage at the over-voltage threshold. Both switching regulators report the overvoltage condition through a high output on the FAULT/RT pin. In addition to the normal over-voltage operation, the microprocessor core regulator has another very useful protection feature presented in Figures 4 and 5. In case of a power-up sequence with a shorted upper MOSFET, and bias voltage above 4V (typically), an independent functional block acts upon the lower gate driver, regulating the core voltage to around 1.3V until the controller bias voltage reaches power-on threshold, at which point normal operation resumes, core voltage is regulated to 115% of the DAC setting (2.8V in this case), and fault condition is reported on the FAULT/RT pin. Application Note 9800 Printed Circuit Board VDAC = 2.8V +12VIN 1 4 FAULT/RT +5VIN 3 VCC_CORE 2 The practical implementation of the circuit is done on a twoounce, four-layer printed circuit board. The two internal layers are dedicated for ground and power planes. The layout is compact and several additional footprints are provided for increased evaluation flexibility. The component side of the board contains an embedded serpentine resistor (approx. 200mΩ) series with the drain of Q4. This resistor is not necessary for the proper operation of the circuit; its role is simply to share the power dissipation which otherwise would be dissipated entirely by Q4. Contact Intersil technical support at 1-888-INTERSIL for board layout Gerber files. Power MOSFETs CH1 10.0V CH3 1.00V CH2 1.00V CH4 10.0V M20.0ms CH2 2.02V FIGURE 4. START-UP SEQUENCE WITH SHORTED Q1 (ATX CONTROL CIRCUIT BY-PASSED) Figure 4 exemplifies operation of the evaluation board without the help of the control circuit shown in Figure 2, the ATX supply being shut down by its internal over-current protection circuitry. Proper operation of this protection feature is contingent, however, on the 12V bias voltage being sufficiently high to turn on the lower MOSFET and the lower MOSFET being a logic-level type. The circuit has been tested with several ATX supplies, and they all produced acceptable bias voltage for the operation of the protection circuitry and the on-board logic-level UltraFET™ MOSFETs. VDAC = 2.8V The power transistors utilized by HIP6017/HIP6019EVAL1 belong to Intersil’ newest line of 30V UltraFET MOSFETs. Featuring reduced rDS(ON) and low trr and Qrr, these transistors allow for elimination of the traditional lower MOSFET anti-parallel schottky. HIP6017/HIP6019EVAL1 Performance Efficiency Figure 6 displays the laboratory-measured efficiency of the HIP6017EVAL1 reference design versus load current, for 5V input and 100 linear feet per minute (LFM) of airflow. Due to the fact that the linear regulators efficiency is not a figure of merit for the application circuit, the efficiency results were obtained based on loading of the switching regulator output only. 95 +12VIN EXAMPLE 1A (VCC_CORE = 2.8V) 1 4 CONVERTER EFFICIENCY (%) PS_ON +5VIN 3 VCC_CORE 93 91 89 87 2 CH1 10.0V CH3 1.00V M 20.0ms CH2 CH2 1.00V CH4 5.00V 2.02V FIGURE 5. START-UP SEQUENCE WITH SHORTED Q1 (ATX CONTROL CIRCUIT ACTIVE) Figure 5 depicts the same start-up scenario, this time with the ATX supply control interface enabled. As seen in the oscilloscope capture, as soon as power-on reset (POR) thresholds are detected, the HIP6019 detects the overvoltage condition and reports it on the FAULT/RT pin. In turn, the control circuit shuts down the ATX supply by generating a logic high at the PS-ON input. 4 85 0 3 6 9 12 SWITCHING CONVERTER OUTPUT CURRENT (A) 15 FIGURE 6. HIP6017EVAL1 MEASURED CONVERTER EFFICIENCY Similarly, Figure 7 displays the efficiency obtained in the HIP6019EVAL1 circuit. Since this evaluation platform contains two switching regulators, both switching regulator outputs were simultaneously loaded and measured. The efficiency curve in Figure 7 represents a composite result of the overall circuit efficiency plotted against total converter output power. UltraFET™ is a trademark of Intersil Corporation. Application Note 9800 95 CONVERTER EFFICIENCY (%) EXAMPLE1 (VCC_CORE = 2.8V) 93 91 89 87 should be at least 1.25 to 1.5 times the maximum input voltage. High frequency decoupling (highly recommended) is implemented through the use of ceramic capacitors in parallel with the bulk aluminum capacitor filtering. The switching converter’s input RMS current is dependent on the input and output voltages as well as the output current. Figure 9 shows this approximate relationships for five different levels of current. Based on the linearity of the relationship, the graph results can be interpolated for additional levels of output current. For output voltages ranging from 2 to 3V, a good approximation of the input RMS current is 1/2 the output current. 0 40 20 60 100 80 COMBINED SWITCHING CONVERTERS OUTPUT POWER (W) FIGURE 7. HIP6019EVAL1 MEASURED CONVERTER EFFICIENCY Load Transient Response Channel 4 of the oscilloscope captures presented in Figure 8 details the core voltage regulation of a HIP6019EVAL1 in response to a 12A output step load transient (larger than the 9.5A design point) as provided by an Intel Slot 1 Test Tool. All other outputs are subjected to the maximum transient loading conditions and all channels are vertically offset by the nominal output voltage settings as described in Table 1. APPROXIMATE INPUT RMS CURRENT (A) 10 85 VIN = 5V IOUT = 18A IOUT = 16A 8 IOUT = 14A IOUT = 12A 6 IOUT = 10A 4 2 0 0 1 2 3 OUTPUT VOLTAGE (V) 4 5 FIGURE 9. SWITCHING CONVERTER RMS INPUT CURRENT 1 4 VCC_L2 Using the above graph and the capacitor RMS current rating, a minimum number of input capacitors can be easily determined. If the time-averaged load is different than the maximum load, the number of input capacitors may be cautiously scaled down. VCC_CORE VCC_VTT 2 3 VCC_CLK CH1 50.0mV BW CH2 50.0mV BW CH3 50.0mV BW CH4 50.0mV BW M 100μs CH2 FIGURE 8. HIP6019EVAL1 OUTPUT TRANSIENT RESPONSE HIP6017/HIP6019EVAL1 Modifications Input Capacitors Selection In a DC/DC converter employing an input inductor, the input RMS current is supplied entirely by the input capacitors. The number of input capacitors is usually determined by their maximum RMS current rating. The voltage rating at maximum ambient temperature of the input capacitors 5 Output Voltages The synchronous buck converter supplying the microprocessor core voltage is controlled by the internal DAC. Output voltage can be adjusted by selecting the appropriate VID jumper combination. For more information please refer to the HIP6019 data sheet which contains a very comprehensive table detailing all the VID combinations and the resultant output voltages. Noteworthy is the fact the HIP6019 can be operated with or without pull-up resistors on the VID lines. If droop implementation is desired, the no-load output voltage can be determined from the following equation: R4 + R8 V VCC – CORE = V DAC • ⎛ 1 + ----------------------⎞ , where ⎝ R9 ⎠ (EQ. 1) VDAC = DAC-set output voltage target. In case of the standard buck regulator, as well as the linear regulator and controller, output voltage adjustment is based Application Note 9800 For the standard buck regulator: R3 + R5 V VCC – L2 = V REF • ⎛ 1 + ----------------------⎞ ⎝ R6 ⎠ (EQ. 2) For the linear controller: R11 V VCC – VTT = V REF • ⎛ 1 + -----------⎞ ⎝ R12⎠ (EQ. 3) for the linear regulator: 100 REGULATOR PHASE MARGIN (DEGREES) on the chip’s internal bandgap voltage reference. Simple resistor value changes allow for outputs as low as 2.7V or as high as 4.2V. The steady-state DC output voltages can be set using the following equations: 90 80 70 60 1000μF 562μF 316μF 178μF 100μF 56μF 32μF 18μF 10μF 50 40 30 20 10 0 R13 V VCC – CLK = V REF • ⎛ 1 + -----------⎞ , where ⎝ R14⎠ Note the fact that since the internal regulator draws its input power from the FB2 pin, VVCC_CLK cannot exceed the voltage set by the user for the VVCC_L2 output. Similarly, VVCC_VTT cannot be set higher than its input source (VVCC_L2 in HIP6019EVAL1, and +3.3V in HIP6017EVAL1.) Output Capacitors Selection Selection of the output capacitors should take into account all the component parasitics. Table 2 offers some recommendations for the core regulator based on the output requirements. Sizing the output capacitor for the internal linear regulator is a somewhat different procedure, mainly due to the fact that the stability of this regulator depends on the characteristics of this output capacitor. The output capacitance and ESR determine the loop stability, and Figure 10 helps quantify the tradeoff between the type of capacitor used and the resulting regulator loop phase margin. As with any other design, the selection should be made in such a way as to provide a minimum of 45 degrees of phase margin (selection should be made above the dotted line). Additionally, the selected output capacitor should be able to keep the output voltage within desired regulation limits when subjected to typical load transients. 6 0.4 0.6 0.8 1.0 OUTPUT CAPACITOR ESR (Ω) (EQ. 4) VREF = HIP6019 internal reference voltage (typically 1.265V). 0.2 FIGURE 10. VCC_CLK REGULATOR LOOP PHASE MARGIN vs OUTPUT CAPACITOR CHARACTERISTICS Conclusion The HIP6019EVAL1 board lends itself to a wide variety of high-power DC-DC microprocessor converter designs. The built-in flexibility allows the designer to quickly modify for applications with various requirements, the printed circuit board being laid out to accommodate the necessary components for operation at currents up to 19A. References For Intersil documents available on the internet, see web site http://www.intersil.com. [1] HIP6019 Data Sheet, Intersil Corporation, FN4490. [2] HIP6017 Data Sheet, Intersil Corporation, FN4496. Application Note 9800 HIP6017EVAL1 Schematic +12VIN F1 +5VIN L1 1μH 15A GND F2 GND SPARE + C17 SPARE R1 GND C16 1μF C1-13 4x1000μF VCC C15 1μF 1000pF R2 28 GND2 C18 9 TP1 23 PWRGOOD OCSET1 1.3K 8 PGOOD SPARE JP6 TP5 R25 +3.3VIN Q3 SPARE NC L2 VCC_L2 NC Q1 HUF76139S3S 27 UGATE1 PHASE1 26 1 2 SPARE + C23 1000μF R3 SPARE CR2 SPARE 25 24 VIN2 R5 C37 SPARE R20 0 0 C49 V33 C38 R21 Q4 HUF75307D3S TP6 VCC_VTT + R7 FB3 1.87K + C24-36 7x1000μF R4 4.99K VSEN1 C40 R8 FB1 5 19 16 12 VID0 SPARE SPARE C42 R10 R9 0.01μF 150K 732K 0.68μF R23 SPARE JP0 VID1 JP1 VID2 JP2 VID3 JP3 VID4 JP4 TP7 SS 14 13 R22 C50 C41 COMP1 C48 0.039μF 17 VID[0] VID[1] VID[2] VID[3] VID[4] GND R24 GND TP9 SPARE 5V 5VSB 9 14 3, 5, 7, 13 15, 16, 17 VCC_VTT VCC_L2 B113 B117 B121 6 FAULT / RT ATX 1, 2, 11 MOTHERBOARD CONNECTOR A1 A3 B5 B9 R14 10K +5VIN J2 18 3 FB2 10K 4, 6 19, 20 10 7 VCC_CORE 2.9μH 2.21K 4 R13 12V PGND 11 R12 10K VOUT2 L3 Q2 HUF76139S3S 10pF R11 +12VIN 21 LGATE1 C39 GATE3 C47 270μF HIP6017 10K CR1 SPARE SPARE SPARE C43-46 4x1000μF + 22 20 TP8 VCC_CLK 10 U1 SPARE SPARE SPARE R6 SPARE NC 15 TP4 3.3V JP7 R26 5.1K VCC_L2 +5VIN 1N4148 PS-ON JP5 GND VCC_CORE Q5 Q6 1/2 RF1K49154 GND VCC5 1/2 RF1K49154 VCC5 PWRGOOD VID[0] VID[1] VID[2] VID[3] VID[4] B13, B17, B25, B29, B33, B37 A2, A6, A10, A14, A18, A22, B109 B45, B49, B53, B57, B65, B69 A26,A30, A34, A38, A42, A46, B73, B77, B85, B89, B93, B97 A50, A54, A58, A62, A66, A70, B105 A74, A78, A82, A86, A90, A94 J1 A98, A102, A106, A110, A114, A118 7 R27 5.1K CR3 A12 B120 A120 A119 B119 A121 SLOT 1 EDGE CONNECTOR Application Note 9800 HIP6019EVAL1 Schematic +12VIN F1 +5VIN L1 1μH 15A F2 + C17 GND GND 1000pF R1 OCSET2 1.3K C18 1000pF R2 28 9 VCC_L2 UGATE2 TP3 L2 PWRGOOD OCSET1 1.3K 8 PGOOD PHASE2 Q1 HUF76139S3S 27 UGATE1 PHASE1 26 1 2 TP4 10K L3 5.2μH + C19-23 5x1000μF R3 4.99K VSEN2 FB2 3.32K R21 C49 0.68μF R20 C38 + R7 C39 5.11K 220K 0.1μF R11 FB3 1.87K 10K R14 10K 3, 5, 7, 13 15, 16, 17 J2 VCC_VTT VCC_L2 B113 B117 B121 3.3V C40 R8 FB1 2.21K C41 COMP1 7 18 6 5 19 16 12 VID0 SPARE SPARE C42 R10 R9 0.01μF 150K 732K 0.68μF R23 SPARE JP0 VID1 JP1 VID2 JP2 VID3 JP3 VID4 JP4 TP7 SS 14 13 R22 C50 C48 0.039μF 17 VID[0] VID[1] VID[2] VID[3] VID[4] GND GND TP9 JP7 R26 5.1K VCC_L2 R27 5.1K CR3 +5VIN 1N4148 PS-ON JP5 GND VCC_CORE Q5 Q6 1/2 RF1K49154 GND VCC5 1/2 RF1K49154 VCC5 PWRGOOD VID[0] VID[1] VID[2] VID[3] VID[4] B13, B17, B25, B29, B33, B37 A2, A6, A10, A14, A18, A22, B109 B45, B49, B53, B57, B65, B69 A26,A30, A34, A38, A42, A46, B73, B77, B85, B89, B93, B97 A50, A54, A58, A62, A66, A70, B105 A74, A78, A82, A86, A90, A94 J1 A98, A102, A106, A110, A114, A118 8 R4 4.99K 5VSB 9 ATX 1, 2, 11 MOTHERBOARD CONNECTOR A1 A3 B5 B9 SPARE + C24-36 7x1000μF VSEN1 R24 5V 14 PGND 11 FAULT / RT 4, 6 19, 20 21 3 FB4 +5VIN 12V HIP6019 4 R13 +12VIN 10 22 R12 10K VOUT4 C47 270μF 10 U1 LGATE1 VCC_CORE 2.9μH CR1 Q2 SPARE HUF76139S3S 10pF GATE3 C43-46 4x1000μF + 15 20 R6 TP8 VCC_CLK COMP2 24 10pF SPARE SPARE SPARE Q4 HUF75307D3S TP6 VCC_VTT 25 CR2 MBR2535CTL R5 C37 TP5 R25 Q3 HUF76137S3S TP2 TP1 23 JP6 +3.3VIN C14-15 2x1μF VCC 15A GND C16 1μF C1-13 4x1000μF A12 B120 A120 A119 B119 A121 SLOT 1 EDGE CONNECTOR Application Note 9800 Bill of Materials for HIP6017EVAL1 REF PART # DESCRIPTION PACKAGE C1-4, 23, 28-34, 43-46 EEUFA1A10 Aluminum Capacitor, 10V, 1000μF Radial 8x20 C5-13, 19-22, 24-27, 35, 36 Spare Aluminum Capacitor Radial 8x20 C14 Spare Ceramic Capacitor 1206 C15, 16 1206YZ105MAT1A Ceramic Capacitor, X7S, 16V, 1.0μF 1206 C17, 37-39, 49, 50 Spare Ceramic Capacitor 0805 C18 1000pF Ceramic Ceramic Capacitor, X7R, 25V C40 0.68μF Ceramic C41 QTY VENDOR 16 Panasonic 3 AVX 0805 1 Various Ceramic Capacitor, X7R, 16V 1206 1 AVX 10pF Ceramic Ceramic Capacitor, X7R, 25V 0805 1 Various C42 0.01μF Ceramic Ceramic Capacitor, X7R, 16V 0805 1 Various C47 6MV270GX Aluminum Capacitor, 6.3V, 270μF Radial 6.3x11 1 Sanyo C48 0.039μF Ceramic Ceramic Capacitor, X7R, 16V 0805 1 Various CR1 Spare Schottky Rectifier DO215AB CR2 Spare Schottky Rectifier D2-PAK CR3 1N4148 Silicon Rectifier, 100mA, 75V DO35 1 Motorola F1 251015A Miniature Fuse, 15A Axial 1 Littelfuse J1 71796-0005 145251-1 Slot 1 Edge Connector 1 Molex AMP J2 39-29-9203 20-pin Mini-Fit, Jr.TM Header Connector 1 Molex JP6, R5, 20 0Ω Shorting Resistor 0805 3 Various JP7 16AWG Jumper, Ni-plated Copper Conductor L1 PO720 1μH Inductor, 7T of 16AWG on T50-52 Core Wound Toroid 18x18x9 1 Pulse L2 Spare Inductor Wound Toroid 20x20x10 L3 PO716 2.9μH Inductor, 9T of 16AWG on T60-52 Core Wound Toroid 20x20x10 1 Pulse Q1, Q2 HUF76139S3S UltraFET™ MOSFET, 30V, 7.5mΩ TO-263 2 Intersil Q3 Spare MOSFET TO-263 Q4 HUF75307D3S UltraFET™ MOSFET, 55V, 90mΩ TO-252 1 Intersil Q5, 6 RF1K49154 MegaFET MOSFET, 60V, VGS(MIN) = 2V, 130mΩ SO-8 1 Intersil R1, 3, 6, 7, 21-24 Spare Resistor 0805 R2 1.3kΩ Resistor, 5%, 0.1W 0805 1 Various R4 4.99kΩ Resistor, 1%, 0.1W 0805 1 Various R8 2.21kΩ Resistor, 1%, 0.1W 0805 1 Various R9 732kΩ Resistor, 1%, 0.1W 0805 1 Various R10 150kΩ Resistor, 5%, 0.1W 0805 1 Various R11 1.87kΩ Resistor, 1%, 0.1W 0805 1 Various R12-14, 25 10kΩ Resistor, 1%, 0.1W 0805 4 Various R26, 27 5.1kΩ Resistor, 5%, 0.1W 0805 2 Various 9 Application Note 9800 Bill of Materials for HIP6017EVAL1 REF (Continued) PART # DESCRIPTION PACKAGE QTY VENDOR +5VIN, +12VIN, +3.3VIN, GND, VCC_CORE, VCC_CLK, VCC_L2, VCC_VTT 1514-2 Terminal Post 14 Keystone TP1,4, 7-9 SPCJ-123-01 Test Point 6 Jolo TP3 Spare Test Point TP2,5,6 1314353-00 Test Point, Scope Probe 3 Tektronics U1 HIP6017CB Dual PWM and Dual Linear Controller 1 Intersil SOIC-28 Bill of Materials for HIP6019EVAL1 REF PART # DESCRIPTION PACKAGE C1-4, 19-23, 28-34, 43-46 EEUFA1A102 Aluminum Capacitor, 10V, 1000μF Radial 8x20 C5-13, 24-27, 35, 36 Spare Aluminum Capacitor Radial 8x20 C14-16 1206YZ105MAT1A Ceramic Capacitor, X7S, 16V, 1.0μF C17-18 1000pF Ceramic C37, C40 QTY VENDOR 20 Panasonic 1206 3 AVX Ceramic Capacitor, X7R, 25V 0805 2 Various 0.68μF Ceramic Ceramic Capacitor, X7R, 16V 1206 2 AVX C38, 41 10pF Ceramic Ceramic Capacitor, X7R, 25V 0805 2 Various C39 0.1μF Ceramic Ceramic Capacitor, X7R, 16V 0805 1 Various C42 0.01μF Ceramic Ceramic Capacitor, X7R, 16V 0805 1 Various C47 6MV270GX Aluminum Capacitor, 6.3V, 270μF Radial 6.3x11 1 Sanyo C48 0.039μF Ceramic Ceramic Capacitor, X7R, 16V 0805 1 Various C49-50 Spare Ceramic Capacitor 0805 CR1 Spare Schottky Rectifier DO215AB CR2 MBR2535CTL Schottky Rectifier, 25A, 35V D2-PAK 1 Motorola CR3 1N4148 Silicon Rectifier, 100mA, 75V DO35 1 Motorola F1, 2 251015A Miniature Fuse, 15A Axial 2 Littelfuse J1 71796-0005 145251-1 Slot 1 Edge Connector 1 Molex AMP J2 39-29-9203 20-pin Mini-Fit, Jr. Header Connector 1 Molex JP6, 7 Spare Jumper L1 PO720 1μH Inductor, 7T of 16AWG on T50-52 Core Wound Toroid 18x18x9 1 Pulse L2 PO743 5.2μH Inductor, 13T of 16AWG on T60-52 Core Wound Toroid 20x20x10 1 Pulse L3 PO716 2.9μH Inductor, 9T of 16AWG on T60-52 Core Wound Toroid 20x20x10 1 Pulse Q1, Q2 HUF76139S3S UltraFET MOSFET, 30V, 7.5mΩ TO-263 2 Intersil Q3 HUF76137S3S UltraFET MOSFET, 30V, 9mΩ TO-263 1 Intersil Q4 HUF75307D3S UltraFET MOSFET, 55V, 90mΩ TO-252 1 Intersil Q5, 6 RF1K49154 MegaFET MOSFET, 60V, VGS(MIN) = 2V, 130mΩ SO-8 1 Intersil 10 Application Note 9800 Bill of Materials for HIP6019EVAL1 REF (Continued) PART # DESCRIPTION PACKAGE QTY VENDOR R1, 2 1.3kΩ Resistor, 5%, 0.1W 0805 2 Various R3, 4 4.99kΩ Resistor, 1%, 0.1W 0805 2 Various R5 3.32kΩ Resistor, 1%, 0.1W 0805 1 Various R6 5.11kΩ Resistor, 1%, 0.1W 0805 1 Various R7 220kΩ Resistor, 5%, 0.1W 0805 1 Various R8 2.21kΩ Resistor, 1%, 0.1W 0805 1 Various R9 732kΩ Resistor, 1%, 0.1W 0805 1 Various R10 150kΩ Resistor, 5%, 0.1W 0805 1 Various R11 1.87kΩ Resistor, 1%, 0.1W 0805 1 Various R12-14, 25 10kΩ Resistor, 1%, 0.1W 0805 4 Various R20-24 Spare Resistor 0805 R26, 27 5.1kΩ Resistor, 5%, 0.1W 0805 2 Various +5VIN, +12VIN, GND, VCC_CORE, VCC_CLK, VCC_L2, VCC_VTT 1514-2 Terminal Post 12 Keystone TP1, 3, 4, 7-9 SPCJ-123-01 Test Point 6 Jolo TP2, 5, 6 1314353-00 Test Point, Scope Probe 3 Tektronics U1 HIP6019CB Dual PWM and Dual Linear Controller 1 Intersil SOIC-28 All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems. Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries. For information regarding Intersil Corporation and its products, see www.intersil.com 11