PDF Circuit Note

Circuit Note
CN-0382
Devices Connected/Referenced
Circuits from the Lab® reference designs are engineered and
tested for quick and easy system integration to help solve today’s
analog, mixed-signal, and RF design challenges. For more
information and/or support, visit www.analog.com/CN0382.
AD7124-4
Low Power, 24-Bit, Sigma-Delta ADC with
PGA and Reference
AD5421
16-Bit, Loop Powered, 4 mA to 20 mA DAC
AD5700
Low Power HART Modem
ADuM1441
SPI Isolator
ADP162
Ultralow Quiescent Current, 150 mA,
CMOS Linear Regulator
ADG5433
High Voltage Latch-Up Proof, Triple SPDT
Switches
Isolated 4 mA to 20 mA/HART Temperature and Pressure Industrial Transmitter
Using a Low Power, Precision, 24-Bit, Sigma-Delta ADC
EVALUATION AND DESIGN SUPPORT
Circuit Evaluation Board
DEMO-AD7124-DZ Evaluation Board
Design and Integration Files
Schematics, Layout Files, Bill of Materials, Code Examples
CIRCUIT FUNCTION AND BENEFITS
The circuit shown in Figure 1 is an isolated smart industrial
field instrument that interfaces to many types of analog sensors
such as temperature (Pt100, Pt1000, and thermocouple) or
bridge pressure sensors. The instrument communicates via a
4 mA to 20 mA analog output and a highway addressable
remote transducer (HART®) interface. HART is a digital 2-way
communication in which a 1 mA peak-to-peak frequency shift
keyed (FSK) signal is modulated on top of the standard 4 mA to
20 mA analog current signal. The HART interface allows
features such as remote calibration, fault interrogation, and
transmission of process variables, which are necessary in
applications such as temperature and pressure control.
The circuit uses the AD7124-4, an ultralow power, precision
24-bit, Σ-Δ analog-to-digital converter (ADC), which includes
all the features needed for temperature and pressure systems.
The circuit also includes the AD5421, a 16-bit, 4 mA to 20 mA,
loop powered digital-to-analog converter (DAC); the AD5700,
the industry’s lowest power and smallest footprint HARTcompliant IC modem; the ADuM1441, which provides ultralow
power serial peripheral interface (SPI) isolation; the ADG5433
CMOS switch; and the ADP162 low power, 3.3 V regulator in
the isolated power circuitry.
Rev. 0
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environment at room temperature. However, you are solely responsible for testing the circuit and
determining its suitability and applicability for your use and application. Accordingly, in no event shall
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CN-0382
Circuit Note
AVDD_ISOL
ADG5433
DVDD_ISOL
ADP162A
1000Z
1.5Ω
10Ω
1µF
1µF
S1B
D1
OUT IN
1µF
NC
S1A
10µF
EN
GND
S2B
D2
S2A
IGND
GND
IGND
DGND
EP
VSS
10Ω
VDD_9V
REGOUT
10µF
EN IN3 IN2 IN1
10µF
AD5421
DGND DGND
DVDD_3.3V
DVDD_3.3V
FAULT
SDIN
100kHz
SDO
SYNC
DC-DC_ENABLE
10Ω
LOOP–
CIN
L*
LOOP–
*0.3Ω AT DC
1kΩ AT 100MHz
0.068µF
0.22µF
AVDD_ISOL DVDD_ISOL
IGND
LOOP+
4700pF
1MΩ
VLOOP
DVDD
DGND
PRIMARY
SENSOR
SIMULATION
L*
REGIN
20MΩ
SCLK
DGND
VDD
DVDD_ISOL DVDD_3.3V
DGND
0.01µF
68kΩ
AIN0
GND1
0.1µF
AIN1
DIN
SCLK
68kΩ
NTC
10kΩ
0.1µF
AIN2
DOUT/RDY
AIN3
AVDD_ISOL
0.01µF
100Ω
1kΩ
IGND
470Ω
0.1µF
1kΩ
VIC
VOC
VOD
VID
DGND
MICROCONTROLLER
SPI
DVDD_3.3V
EN2
GND2
DGND
UART_RX
ADuM1441
AIN6
UART_TX
UART
IGND
REFIN1(+)
5.6kΩ
J5-1
VOB
GND1
AD7124-4
0.01µF
1kΩ
VOA
VIB
EN1
0.01µF
5.6kΩ
GND2
VIA
DGND
PROGRAMMING/
DEBUG INTERFACE
REFIN1(–)
0.01µF
CD
TXD
J5-2
J5-3
0.01µF
J5-4
J5-5
0.1µF
1kΩ
J5-6
0.01µF
1kΩ
470Ω
1.2MΩ
XTAL2
AD5700 REF
1µF
300pF
1.2MΩ
150pF
VCC
AIN7
PSW
AVSS
DVDD_3.3V
DGND
470Ω
HART_VDD
1µF
DGND
13355-001
0.01µF
J5-8
150kΩ
ADC_IP
AIN5
J5-7
470Ω
HART_OUT
XTAL1
AIN4
1kΩ
RTS
THERMISTOR
TEMPERATURE
SENSOR
SPI
CS
0.01µF
1kΩ
IGND
UART
VDD2
HART_IN
VRES 1kΩ
VDD1
RXD
1MΩ
IOVDD
HART_OUT
0.01µF
REFOUT AVDD
IGND
Figure 1. 4 mA to 20 mA, Loop Powered Field Instrument with HART Interface (Simplified Schematic: All Connections and Decoupling Not Shown)
CIRCUIT DESCRIPTION
Analog Front-End Interface
The AD7124-4 is a low power, low noise, completely integrated
analog front end for high precision measurement applications.
The device contains a low noise, 24-bit, Σ-Δ analog-to-digital
converter (ADC), and can be configured to have four
differential inputs or seven single-ended or pseudo differential
inputs. The on-chip low noise gain stage ensures that signals of
small amplitude can be interfaced directly to the ADC.
One of the major advantages of the AD7124-4 is that it gives the
user the flexibility to employ one of three integrated power
modes. The current consumption, range of output data rates,
and rms noise can be tailored with the power mode selected.
The device also offers a multitude of filter options, ensuring that
the user has the highest degree of flexibility.
The AD7124-4 can achieve simultaneous 50 Hz and 60 Hz
rejection when operating at an output data rate of 25 SPS
(single-cycle settling).
The AD7124-4 establishes the highest degree of signal chain
integration. The device contains a precision, low noise, low
drift internal band gap reference, and also accepts an external
differential reference, which can be internally buffered. Other
key integrated features include programmable low drift excitation
current sources, burnout currents, and a bias voltage generator,
which sets the common-mode voltage of a channel to AVDD/2.
The low-side power switch enables the user to power down
bridge sensors between conversions, ensuring the absolute
minimal power consumption of the system. The device also
allows the user the option of operating with either an internal
clock or an external clock.
Rev. 0 | Page 2 of 13
Circuit Note
CN-0382
The AD7124-4 also has extensive diagnostic functionality
integrated as part of its comprehensive feature set. These
diagnostics include a cyclic redundancy check (CRC), signal
chain checks, and serial interface checks, which lead to a more
robust solution. These diagnostics reduce the need for external
components to implement diagnostics, resulting in reduced
board space needs, reduced design cycle times, and cost savings.
The failure modes effects and diagnostic analysis (FMEDA) of a
typical application has shown a safe failure fraction (SFF)
greater than 90% according to IEC 61508.
Sensor Input
The circuit supports 3-wire and 4-wire RTDs, thermocouples,
and pressure transducers via the 8-pin connector. The AD7124-4
has all the building blocks needed to interface to these sensors.
For all the sensor types connected, the ADC is used in mid power
mode. The post filter is used because it enables simultaneous
50 Hz and 60 Hz rejection when converting at 25 SPS. When a
sensor is connected to the circuit, the ADC is configured to suit
the sensor type connected. An internal full-scale and offset
calibration can also be performed to minimize the offset error
and full-scale error, the calibrations being initiated by a UART
or HART command.
The AD7124-4 has numerous diagnostics on-chip, which
ensure a robust design. In this circuit, open-wire detection
ensures that the sensors are connected, the power-on reset
(POR) in the status register is monitored so that the user is
informed when a power-on reset occurs. The error register is
read for each conversion, and its contents are sent via HART
along with the sensor result.
RTD
A resistive temperature detector (RTD) can measure temperature
from −200°C to +600°C. Typical RTDs are Pt100 and Pt1000
and are made of platinum. A Pt100 is used with this circuit.
4-Wire RTD
Figure 2 shows how a 4-wire Pt100 RTD connects to the circuit.
J5-3
RREF
1kΩ
10nF
1kΩ
10nF
1kΩ
0.1µF
100Ω
IOUT1
REF(+)
REF(–)
10nF
10nF
J5-4
RTD
J5-5
AIN(+)
1kΩ
0.1µF
1kΩ
10nF
AIN(–)
J5-8
470Ω
13355-002
The integrated channel sequencer allows several channels to be
enabled simultaneously, and the AD7124-4 sequentially
converts on each enabled channel, simplifying communication
with the device. As many as 16 channels can be enabled at any
time; a channel being defined as an analog input or a diagnostic
such as a power supply check or a reference check. This unique
feature allows diagnostics to be interleaved with conversions.
The AD7124-4 also supports per channel configuration. The
device allows eight configurations or setups. Each configuration
consists of gain, filter type, output data rate, buffering, and
reference source. The user can assign any of these setups on a
channel by channel basis.
Figure 2. 4-Wire RTD
One of the on-chip excitation currents of the AD7124-4 excites
the Pt100. The maximum resistance of the Pt100 is 313.71 Ω (at
600°C). If the excitation current is programmed to 250 µA, the
maximum voltage generated across the Pt100 is
250 µA × 313.71 Ω = 78.43 mV
With the programmable gain array (PGA) programmed to a
gain of 16, the maximum voltage seen at the modulator input is
78.43 mV × 16 = 1.25 V
A 5.6 kΩ precision resistor (0.05%, 10 ppm/°C) generates the
reference voltage. The value of the reference resistor, RREF, is
chosen so that the voltage generated across it has a minimum
value of 1.25 V in this circuit, that is, the voltage seen at the
modulator input due to the analog input is less than or equal to
the reference voltage. The 250 µA current that supplies the
Pt100 also flows through the 5.6 kΩ resistor, resulting in a
ratiometric configuration. Therefore, any variation of the
excitation current has no effect on the performance of the
circuit. The voltage generated across the precision resistor is
5.6 kΩ × 250 µA = 1.4 V
Antialiasing filters are included on the analog input and
reference input. These filters prevent any interference at
multiples of the modulator sampling frequency aliasing into the
band of interest. To ensure that these filters and the external
resistors do not cause gain errors, the reference buffers are
enabled. The analog input buffers are enabled automatically
because these buffers are enabled when the PGA is used. The
reference buffers require some headroom (100 mV within the
power supply rails). Therefore, a 470 Ω resistor was included on
the low side to allow this headroom.
The 250 µA excitation current requires 370 mV of headroom.
The voltage seen on this pin is (470 + 5600 + 313.71) Ω ×
250 µA = 1.6 V, which is acceptable.
The AIN4 and AIN5 pins are used as the AINP and AINM
analog input.
Rev. 0 | Page 3 of 13
CN-0382
Circuit Note
The 1 kΩ resistors on the connector pins have a dual purpose:
they make up the antialias filters, and they also protect the analog
inputs if an overvoltage occurs (due to miswiring, for example).
The Circuit Note CN-0381 provides further detail on
interfacing 4-wire Pt100 sensors to the AD7124-4 and
linearizing or post-processing the conversions.
The circuit shown in Figure 1 also supports a 4-wire Pt1000
RTD. The circuit connections are the same as those used for the
Pt100. The ADC configuration used is described previously in
this section, but with the PGA gain set to 1.
3-Wire RTD
Figure 3 shows how a 3-wire Pt100 RTD connects to the circuit.
RREF
10nF
1kΩ
10nF
1kΩ
100Ω
The Circuit Note CN-0383 provides further detail on
interfacing 3-wire Pt100 sensors to the AD7124-4 and
linearizing or post-processing the conversions.
IOUT0
REF(+)
The circuit shown in Figure 1 also supports a 3-wire Pt1000
RTD. The circuit connections are the same as used for the
Pt100. The ADC configuration used is as described previously
in this section, but with the PGA gain set to 1.
0.1µF
REF(–)
10nF
10nF
J5-4
RTD
1kΩ
J5-5
1kΩ
AIN(+)
Thermocouple
0.1µF
AIN(–)
10nF
100Ω
J5-6
1kΩ
The 250 µA excitation current requires 370 mV of headroom.
The voltage seen on this pin is (470 Ω × 2 × 250 µA) + (5600 +
313.71) Ω × 250 µA = 1.713 V, which is acceptable.
Figure 4 shows how a thermocouple connects to the circuit.
IOUT1
J5-3
1kΩ
J5-8
13355-003
470Ω
100Ω
VBIAS
10nF
J5-4
Figure 3. 3-Wire RTD
The AD7124-4 has two matched excitation currents. Both are
used with the 3-wire RTD so that lead wire compensation can
be performed. Because the Pt100 has a maximum resistance is
313.71 Ω (at 600 °C), the excitation currents are programmed to
250 µA. The reference resistor, RREF, is connected on the top
side. Therefore, one 250 µA excitation current (IOUT0) is
output on Pin AIN6, flows through the 5.6 kΩ precision
reference resistor (0.05%, 10ppm/°C ), and then through the
Pt100. The second 250 µA current (IOUT1) is output on pin
AIN7. This current generates a voltage due to the lead
resistance, which is in opposition to the lead resistance voltage
generated due to the current on AIN6. Therefore, the error due
to the lead resistance is minimized.
The voltage generated across the 5.6 Ωk reference resistor is
250 µA × 5.6 kΩ = 1.4 V
The maximum voltage generated across the Pt100 is
250 µA Ω 313.71 Ω = 78.43 mV
With the PGA programmed to a gain of 16, the voltage seen at
the modulator of the AD7124-4 is
78.43 mV × 16 = 1.25 V
This voltage is within range because it is less than the reference
voltage.
1kΩ
10nF
1kΩ
10nF
0.1µF
J5-5
AIN(+)
AIN(–)
13355-004
J5-3
1kΩ
Antialiasing filters are included on the analog input and
reference input. These filters prevent any interference at
multiples of the modulator sampling frequency from aliasing
into the band of interest. To ensure that these filters and the
external resistors do not cause gain errors, the reference buffers
are enabled. The analog input buffers are enabled automatically
because these buffers are enabled when the PGA is used. The
reference buffers require some headroom (100 mV within the
power supply rails). Therefore, a 470 Ω resistor was included on
the low side to allow this headroom.
Figure 4. T-Type Thermocouple
A thermocouple consists of a connection of two different types
of wire. A voltage is generated, which is dependent on
temperature. For example, a T-type thermocouple generates a
voltage of 40 µV typically when a 1°C change in temperature
occurs.
The thermocouple voltage must be biased to a voltage. The
AD7124-4 contains a VBIAS source that biases the thermocouple
to (AVDD − AVSS)/2. The bias voltage is enabled on the AIN6
channel and applied to the thermocouple, as shown in Figure 4.
The bias voltage can also be enabled on the AINM pin of the
analog input. However, the external R and C values must be
limited in this case, because there is a difference between the
bias voltage seen on AINM and the filtered version seen on
AINP; this difference is sufficiently high that it affects the
conversion result.
The thermocouple measurement is an absolute measurement,
the internal 2.5 V reference being used for the conversion. A
T-type thermocouple is used. This thermocouple can measure
temperatures from −200°C to +400°C, leading to a voltage range
of −8 mV to +16 mV being generated by the thermocouple. The
PGA is set to 128.
Rev. 0 | Page 4 of 13
Circuit Note
CN-0382
For the cold junction compensation, an NTC thermistor is used
(10 kΩ, 1%, 3435 K).
The Circuit Note CN-0384 provides further detail on interfacing
thermocouple sensors to the AD7124-4 and linearizing or postprocessing the conversions.
REFOUT
0.01µF
1kΩ
0.01µF
Pressure Sensor
AIN(–)
IGND
Figure 5. Thermistor
The internal reference supplies the thermistor, the gain being
set to 1 for this conversion. A resistor, RREF, is used on the low
side of the thermistor. This is a precision 5.6 kΩ resistor (0.05%,
10 ppm/°C). The voltage across the thermistor VNTC is
VNTC =
A voltage excited pressure sensor is connected as shown in
Figure 6 while a current-excited pressure sensor is connected as
shown in Figure 7. A Honeywell pressure sensor (Honeywell
S&C 24PCDFA6D) is used.
J5-1
1kΩ
224
1kΩ
AIN(+)
0.1µF
J5-5
AIN(–)
1kΩ
10nF
1kΩ
10nF
100Ω
J5-6
REF(–)
J5-8
470Ω
VNTC × R REF
VREF − VNTC
Figure 6. Voltage Excited Pressure Sensor
10nF
100Ω
1kΩ
IOUT0
10nF
Combining these equations,
RREF
ADCCODE × RREF
1kΩ
REF(+)
0.1µF
J5-3
1kΩ
FSCODE − ADCCODE
where:
ADCCODE is the code read from the AD7124-4.
RREF = 5.6 kΩ.
FSCODE is the full-scale code from the AD7124-4 (224).
REF(–)
10nF
10nF
J5-4
1kΩ
AIN(+)
0.1µF
J5-5
1kΩ
AIN(–)
10nF
J5-8
The resistance is then converted to temperature in the
microcontroller using a look-up table based on the thermistor
equation:
1
R
ln NTC
 R0
β
REF(+)
10nF
J5-4
where:
RREF = 5.6 kΩ.
VREF is the reference voltage.
T=
10nF 100Ω
J5-2
VREF × ADCCODE
The resistance of the thermistor, RNTC, is
RNTC =
AVDD
0.1µF
where:
VREF is the reference voltage.
ADCCODE is the code read from the AD7124-4.
224 is the maximum code from ADC.
R NTC =
470Ω
13355-006
0.1µF
13355-005
RREF
AIN(+)
1kΩ
470Ω
13355-007
NTC
10kΩ
100 mV of headroom. This resistor also protects the circuit
because it limits the current if miswiring occurs.
Figure 7. Current Excited Pressure Sensor
For the voltage excited architecture, AVDD (3.3 V) excites the
sensor. If AVDD is used to excite the load cell, the excitation
voltage can be used directly as the ADC reference. Note that a
resistor was added on the high side and the low side of the
sensor to ensure that the headroom requirements of the
AD7124-4 buffers are met. A gain of 16 is used.


 1
+
T0
where:
T is the temperature recorded by thermistor (K).
R0 = 10 kΩ.
β = 3435 K.
T0 = 298.15 K.
The resulting temperature in °C is T − 273.15.
The 5.6 kΩ resistor also provides headroom for the analog input
because the analog input buffers are enabled, and they require
For the current excited mode, both of the 100 µA excitation
currents of the AD7124-4 are directed to Pin AIN6, resulting in
a 200 µA excitation current for the sensor. Again, the gain is set
to 16. A 5.6 kΩ precision resistor generates the reference. This
arrangement results in a ratiometric configuration, that is, any
deviation in the excitation current value has no effect on the
system accuracy.
Rev. 0 | Page 5 of 13
CN-0382
Circuit Note
The circuit board includes the option to connect the sensor low
side to GND or to the power switch of the AD7124-4.
As previously stated, the analog inputs and reference inputs
have antialias filters to reject any interference that occur at
multiples of the ADC sampling frequencies. The series resistors
also limit the current if an overvoltage occurs.
Primary Sensor Simulation
The circuit includes a resistor network and potentiometer that
allows sensor simulation (primary sensor simulation circuit
shown in Figure 1). Using the potentiometer, the voltage
applied between AIN0 (AINP) and AIN1 (AINM) can be varied
from approximately −0.09 V to approximately +1.36 V. This
circuit uses the internal reference for the conversions; the
AD7124-4 gain is set to 1, and the analog input buffers are
enabled. This configuration allows the user to evaluate the
circuit without needing to connect an external sensor.
Digital Data Processing, Algorithm, and Communications
The demonstration software (included in the CN-0382 Design
Support Package) performs the initialization and configuration,
processes data from the analog inputs, controls the analog
output, and performs the HART communication. All the
sensors mentioned require linearization or compensation. This
linearization is performed in the software. See the Circuit Note
CN-0381, Circuit Note CN-0383, and Circuit Note CN-0384 for
further details on the RTD and thermocouple sensors and the
linearization required.
Analog Output
The AD5421 integrates a low power, precision, 16-bit DAC with
a 4 mA to 20 mA, loop powered output driver and provides all
functions required for the field instrument analog output.
The AD5421 interfaces with the microcontroller via the SPI
interface.
The AD5421 also includes a range of diagnostic functions
related to the 4 mA to 20 mA loop. The auxiliary ADC can
measure the voltage across the instruments loop terminals via
the 20 MΩ/1 MΩ resistive divider connected to the VLOOP pin.
The ADC can also measure the chip temperature via the
integrated sensor. The microcontroller can configure and read
all the diagnostics of the AD5421; however, the AD5421 can
also operate autonomously.
As an example, if the communication between the controller
and the AD5421 fails, the AD5421 automatically sets its analog
output to a 3.2 mA alarm current after a defined period. This
alarm current indicates to the host that the field instrument
failed to operate.
The software controls any change of the output current from
one value to another to prevent disturbance of the HART
communication.
HART Communication
The AD5700 integrates a complete HART FSK modem. The
modem connects to the microcontroller via a standard UART
interface, complemented by request to send (RTS) and carrier
detect (CD) signals.
The HART output is scaled to the required amplitude by the
0.068 µF/0.22 µF capacitive divider and coupled to the AD5421
CIN pin, where it is combined with the DAC output to drive and
modulate the output current.
The HART input is coupled from LOOP+ via a simple passive
RC filter to the AD5700 ADC_IP pin. The RC filter operates as
the first stage band-pass filter for the HART demodulator and
also improves the system electromagnetic immunity, which is
important for robust applications working in harsh industrial
environments.
The AD5700 low power oscillator generates the clock for the
HART modem with a 3.6864 MHz external crystal connected
directly to the XTAL1 and XTAL2 pins.
Output Protection
A transient voltage suppressor (TVS) protects the 4 mA to
20 mA HART interface from overvoltage. Select the TVS
voltage rating so that the AD5421 absolute maximum voltage of
60 V on the REGIN pin is not exceeded. Note that the TVS
leakage current can affect the current output accuracy;
therefore, pay attention to the leakage current at a given loop
voltage and temperature range when selecting this component.
An external depletion-mode FET can be used with the AD5421
to increase the loop voltage maximum.
The circuit is protected against reversed polarity by a pair of
diodes in series with loop output.
The ferrite beads in series with the loop together with the
4700 pF capacitor improve the system EMC performance. Do
not use a higher capacitance across the loop terminals because
of the HART network specifications.
The 4.7 V, low leakage, Zener diode protects the AD5421 on-chip,
50 Ω loop sense resistor in the event of an accidental external
voltage between the AD5421 COM pin and LOOP− pin (for
example, when debugging the circuit).
Power Supplies and Power Management
The complete field instrument circuitry, including the sensor
drive current, must operate on the limited amount of power
available from the 4 mA to 20 mA loop. This is a common
challenge in any loop powered field instrument design. The
circuit in Figure 1 provides an example of delivering both a low
power and high performance solution. All integrated circuits
used in the application are designed for low power, and the
circuit leverages their integrated features to deliver a flexible
power management structure and an optimum loop powered
solution.
Rev. 0 | Page 6 of 13
Circuit Note
CN-0382
The AD5421 is powered by the 4 mA to 20 mA loop voltage and
provides a regulated low voltage for the rest of the circuit. The
AD5421 REGOUT voltage is pin programmable from 1.8 V to
12 V depending on circuit requirements. The circuit in Figure 1
uses the 9 V supply voltage option. The sensor side is isolated
from the 4-20 mA loop using a simple push-pull, dc-to-dc
converter. The ADG5433 is clocked from the microcontroller
and generates 9 V non-overlapping square waves, which drive a
transformer. The transformer works in voltage ratio 2:1. The
4.5 V on the secondary side is rectified and regulated by the
ADP162 to generate a low noise 3.3 V supply for the AD7124-4.
Both the analog and digital 3.3 V supplies of the AD7124-4 are
supplied by the ADP162 regulator. However, a filter (L1/R19) is
included to prevent noise from the digital circuitry being fed
into the analog sections.
The AD5421 supplies the 3.3 V logic supply on the loop side.
This supply is used directly by the microcontroller and the
AD5700.
The REGOUT RC filter (10 µF/10 Ω/10 µF) helps to prevent any
interference coming from the loop affecting the analog
circuitry. It also prevents any interference generated by the
circuit, specifically by the controller and the digital circuitry,
from coupling back to the loop, which is important for a reliable
HART communication.
The AD5700 HART modem is supplied through an additional
RC filter (470 Ω/1 µF). This filter is very important in the loop
powered application because it prevents current noise from the
AD5700 from coupling to the 4 mA to 20 mA loop output,
which would otherwise affect the HART communication. The
AD5700 modem uses the external crystal with 8.2 pF capacitors
to ground on the XTAL1 and XTAL2 pins, which is the option
using the least possible power.
One of the major advantages of the AD7124-4 is that it gives the
user the flexibility to employ one of three integrated power
modes. The current consumption, range of output data rates,
and rms noise can be tailored with the power mode selected.
Therefore, for 4 mA to 20 mA or portable equipment, the low
or mid power mode is the optimum choice. For process control
systems where power consumption is not a concern, the full
power mode can be used, which leads to lower noise. For this
loop powered circuit, the mid power mode is used. See the
AD7124-4 data sheet for further information on the power
modes.
The PSW ground switch pin of the AD7124-4 controls the
excitation/power supply when the pressure transducer is
connected. The switch is off by default at the instrument power
up. This default allows the system to be fully configured,
including appropriate power modes, before turning on the
sensor, and thus minimizes any possible power-up spikes on the
4 mA to 20 mA loop output.
When an RTD sensor is connected, it is supplied from the
programmable current source of the AD7124-4, and therefore,
its power is fully controlled by the software. Similarly, for
thermocouple sensors, the bias voltage and absolute reference
are embedded in the AD7124-4 and therefore software
controlled.
Software
The microcontroller interfaces to the AD7124-4 and AD5421
using SPI interfaces. It communicates with the AD5700 via a
UART interface, UART0. Software is downloaded to the
microcontroller via the second UART interface on the
microcontroller, UART1.
On start-up, the microcontroller configures all three devices,
the AD7124-4 being configured for a T-type thermocouple. The
AD7124-4 is operated in continuous conversion mode.
Therefore, its DOUT/RDY pin is connected to an interrupt on
the microcontroller also. Each time a conversion is available
from the ADC, an interrupt to the microcontroller is generated
and the conversion is read. The microcontroller then linearizes
and processes the data. The result is sent to the AD5421 DAC
for transmission on the 4 mA to 20 mA loop. The software used
to demonstrate the functionality and performance of the circuit
is contained in the CN-0382 Design Support Package. The
software supports all the sensor types mentioned in this circuit
note. Documentation on how to alter the software for the
different sensor types and details on downloading the software
to the microcontroller are also provided in the CN-0382 Design
Support Package.
The code example includes a basic HART slave command
response to demonstrate the hardware function and capability.
However, the code example does not include the protocol layers
of the HART communication.
COMMON VARIATIONS
The AD7124-4 has a high performance and very flexible analog
front-end, with four differential or seven pseudo differential
analog input pins and extra pins for voltage reference and low
side power switch. It allows direct interface to multiple analog
sensors of varying types, such as any resistive bridge sensors,
resistive temperature sensors, or thermocouples. Therefore, do
not limit the field instrument solution to the sensor types listed
in this circuit note only, because it can be used for almost any
sensor field instrument.
The AD7124-8 can be used as an alternative to the AD7124-4.
Both the AD7124-4 and AD7124-8 have the same performance.
However, the AD7124-8 offers 8 differential or 15 pseudo
differential inputs, and therefore is suitable for applications that
require a high channel count.
The AD5421 can be connected via the protection directly to the
loop. Alternatively, a depletion mode N-channel MOSFET can
be connected between the AD5421 and the loop power supply,
as shown in Figure 8. The use of the additional MOSEFT in this
configuration keeps the voltage drop across the AD5421 at
approximately 12 V, lowers the power dissipated in the AD5421
package, and therefore improves the 4 mA to 20 mA analog
output accuracy. It also increases the maximum voltage allowed
Rev. 0 | Page 7 of 13
CN-0382
Circuit Note
For applications that are not loop powered, the AD5410, AD5420,
AD5422, or AD5755 are good choices for the 4 mA to 20 mA
DAC.
in the loop to the level of the MOSFET rating. The additional
MOSFET has no effect on the HART communication.
L
LOOP+
Finally, there are a wide choice of isolator products that can be
used instead of the ADuM1441: the ADuM1440, ADuM1442,
ADuM1445, ADuM1446, ADuM1447, ADuM1240,
ADuM1241, ADuM1245, and ADuM1246.
DN2540
BSP129
AD5421
REGIN
DRIVE
4700pF
200kΩ
20MΩ
VLOOP
COM
CIRCUIT EVALUATION AND TEST
TVS
40V
LOW-LEAKAGE
Circuit Hardware
1MΩ
L
The circuit shown in Figure 1 is built on the DEMO-AD7124-DZ
printed circuit board (PCB) shown in Figure 9.
LOOP–
LOOP–
13355-008
4.7V
LOW-LEAKAGE TO
HART
INPUT
FILTER
Figure 8. MOSEFT Connected to the AD5421 Loop Power Supply
The AD5700 is used with a 3.6864 MHz crystal in this circuit,
which is the configuration achieving the lowest power
consumption. Alternatively, the AD5700-1, with an integrated
0.5% precision internal oscillator, can be used. The internal
oscillator increases the modem power supply current by 225 μA
maximum, compared to the crystal oscillator; however, because
no external crystal is needed, this option provides both cost
savings and reduced board area requirements.
The DEMO-AD7124-DZ circuit board includes additional
features for easy system evaluation. The RTD, thermocouple, or
pressure sensor can be connected via the 8-pin connector, J5.
There are test points for HART RTS and CD. The 4-pin
connector allows code to be downloaded to the microcontroller.
The CN-0382 Design Support Package also includes a full field
instrument C-code example for 3-wire and 4-wire Pt100 and
Pt1000 RTDs, thermocouples, and voltage/current excited
pressure sensors, which enables complete verification and
evaluation of all hardware blocks and features of the circuit, and
a limited verification of the HART interface functionality. For
detailed information about HART interface specifications and
resources, contact the Hart Communication Foundation.
J5-1
J5-2
J5-3
J5-4
J5-6
4mA TO 20mA
LOOP CONNECTOR
J5-7
J5-8
Figure 9. DEMO-AD7124-DZ Printed Circuit Board
Rev. 0 | Page 8 of 13
13355-009
J5-5
Circuit Note
CN-0382
Circuit Power Consumption
For ease of in-circuit measurement, the circuit has numerous
test points to measure the current. The REGOUT pin and DVDD
pins of the AD5421 include a 10 Ω resistor in their path. The
output of the ADP162 has a similar 10 Ω resistor in its path.
There are test points on each side of the 10 Ω resistors. This
setup allows the voltage drop across each resistor to be
measured, and the current to be calculated without interrupting
the supply current or disturbing the circuit.
The circuit is configured as follows:
•
•
Microcontroller core clock = 1 MHz
AD7124-4 and the analog circuitry operating in the
relevant mode per individual sensor type
AD5421 operating and updating loop output current at a
rate of 10 SPS
HART communicating, periodically responding to master
request to read all device variables
Figure 10 shows the performance of the system when connected
to a 4-wire RTD. A B Grade Pt100 sensor is used. The AD7124-4
configuration is as follows:
•
•
•
•
•
•
•
•
Power mode: mid power mode
Filter: post filter, 25 SPS
Excitation current: enabled on AIN6 and set to 250 µA
Gain = 16
Polarity: unipolar
Reference buffers enabled
RTD connected to the AIN4/AIN5 channel
Reference: REFIN1 with 5.6 kΩ reference resistor
connected across the REFIN1 terminals
AD7124-4 internal offset and full-scale calibration was
performed on power-up
•
1.5
Table 1. Circuit Current Consumption
AD5421
Internal
(mA)
DVDD
3.3 V
(mA)
REGOUT
9.0 V
(mA)
Total Off
Loop
(mA)
Isolated
3.3 V
(mA)
0.28
0.28
0.28
0.28
0.63
0.63
0.63
0.63
0.82
1.00
1.12
0.89
1.73
1.91
2.03
1.80
0.48
0.84
1.08
0.61
0.28
0.28
0.63
0.63
1.16
0.98
2.07
1.89
1.15
0.79
Pt100
0.5
ERROR (°C)
Mode
Simulation
RTD 4-wire
RTD 3-wire
TC
Pressure
V Mode
I Mode
NO CALIBRATION
1.0
0
–0.5
–1.0
Table 1 shows the power supply current for each of the
individual blocks: the AD5421 itself (estimation, verified by
placing the AD5421 into a minimum loop current), the
circuitry supplied from DVDD 3.3 V (the microcontroller, the
HART modem, and the primary side of the SPI isolation), and
the primary 9 V side of the isolated power supply. These
components together sum into the total current taken off the
loop for the circuit itself, before adding the variable current
component to make the 4 mA to 20 mA output. The Isolated
3.3 V column is the current from the isolated 3.3 V, which
supplies the sensor, the AD7124-4, and the secondary side of
the SPI isolation.
–1.5
0
20
40
60
RTD TEMPERATURE (°C)
80
100
13355-010
•
•
Sensor Input Performance
4-Wire RTD
Figure 10. 4-Wire RTD Measurement
The conversions read from the ADC were linearized within the
microcontroller. The temperature forced on the Pt100 sensor
was swept from 0°C to 100°C while the circuit board was held at
25°C. Figure 10 shows the accuracy of the demonstration. The
measured accuracy of the demonstration is within the specified
accuracy of a B Grade Pt100 sensor.
The circuit with all relevant analog and digital blocks, including
the input sensor, consumes a power supply current well within
the budget allowed at the minimum 4 mA loop output current.
Rev. 0 | Page 9 of 13
CN-0382
Circuit Note
3-Wire RTD
Thermocouple
Figure 11 shows the performance of the system when connected
to a 3-wire RTD. A B Grade Pt100 is used. The AD7124-4
configuration is as follows:
Figure 12 shows the performance of the system when connected
to a T-type thermocouple. The AD7124-4 configuration is as
follows:
•
•
•
•
•
•
•
•
•
•
•
•
Power mode: mid power mode
Filter: post filter, 25 SPS
Excitation Current IOUT0: enabled on AIN6 and set to
250 µA
Excitation Current IOUT1: enabled on AIN7 and set to
250 µA
Gain = 16
Polarity: unipolar
Reference buffers enabled
RTD connected to the AIN4/AIN5 channel
Reference: REFIN1 with 5.6 kΩ reference resistor
connected across the REFIN1 terminals
AD7124-4 internal offset and full-scale calibration
performed on power-up
Power mode: mid-power mode
Thermocouple configuration
• Gain = 128
• Channel: AIN4/AIN5
• Internal reference enabled
• Filter: post filter, 25 SPS
• Polarity: bipolar
AD7124-4 internal offset and full-scale calibration
performed on power-up
Cold junction configuration
• Gain = 1
• Filter: fast settling Sinc3, 44.44 SPS
• Channel: AIN2/AIN3
• Internal reference selected
• Analog input buffers enabled
• Polarity: unipolar
•
•
1.5
GAIN AND OFFSET CALIBRATION, 25°C
1.0
The full-scale error of the AD7124-4 is factory calibrated at a
gain of 1; therefore, no additional calibrations were performed.
Pt100
ERROR (°C)
0.5
2.0
CALIBRATIONS AT 25°C
0
1.5
1.0
–1.5
0
20
40
60
80
RTD TEMPERATURE (°C)
100
13355-011
–1.0
ERROR (°C)
–0.5
0.5
0
–0.5
–1.0
Figure 11. 3-Wire RTD Measurement
THERMOCOUPLE
ERROR BAND
–1.5
–2.0
0
20
40
60
80
THERMOCOUPLE TEMPERATURE (°C)
100
13355-012
The temperature forced on the Pt100 sensor was swept from
0°C to 100°C while the circuit board was held at 25°C. The
conversions read from the ADC were linearized within the
microcontroller. The resulting error between the forced
temperature and the temperature measured by the circuit board
is shown. An internal offset and full-scale calibration were
performed at 25°C prior to the temperature sweep. Following
the calibration, the 3-wire Pt100 is well within the envelope
allowed for a B Grade Pt100. Figure 11 shows the accuracy of
the demonstration. The measured accuracy of the
demonstration is within the specified accuracy of a B Grade
Pt100 sensor.
Figure 12. T-Type Thermocouple Measurement (Cold Junction at Ambient)
In Figure 12, the cold junction was held at 25°C, and the
thermocouple was swept from 0°C to 100°C. The conversions
read from the ADC were processed and linearized within the
microcontroller.
A T-type thermocouple has an accuracy of 1°C or 0.75%,
whichever is greater. The thermistor also adds some error. The
thermistor used in the circuit has an accuracy of 1% or 1°C,
whichever is greater. Figure 12 shows the difference between
the forced temperature and the measured temperature. The
results are well within specification for the
thermocouple/thermistor combination.
Rev. 0 | Page 10 of 13
Circuit Note
CN-0382
2.0
•
•
•
Power mode: mid power mode
Filter: post filter, 25 SPS
Excitation current: both excitation currents enabled on
AIN6 and set to 100 µA, resulting in a total current of
200 µA
Gain = 16
Polarity: bipolar
Reference buffers enabled
Sensor connected to the AIN4/AIN5 channel
Reference: REFIN1 with 5.6 kΩ reference resistor
connected across the REFIN1 terminals.
CALIBRATIONS AT 25°C
•
•
•
•
•
1.0
0.5
0
–0.5
–1.0
The performance summary is shown in Table 2, and the signal
plots are shown in Figure 14 to Figure 17.
10
20
30
40
50
60
COLD JUNCTION TEMPERATURE (°C)
70
80
Figure 13. T-Type Thermocouple Measurement (Cold Junction Swept and
Thermocouple Held at Ambient)
Pressure
With a pressure sensor connected, noise tests were performed.
The level of noise is the main factor that can be influenced by
the interaction of the analog front end with the rest of the
circuitry on the board. Therefore, tests were performed to focus
on the noise and related resolution performance of the system.
The demonstration was configured to transmit data, expressed
as pressure in kPa, over the HART communication. One
hundred samples were captured, and a basic data analysis to
quantify the performance was completed. The first test was
performed with a standard pressure sensor (Honeywell
24PCDFA6D) connected. A second test was performed with the
input signal generated by a shorted input.
The testing was performed with the sensor being excited with a
current source and with a voltage. In voltage mode, the
AD7124-4 configuration is as follows:
Power mode: mid power mode
Filter: post filter, 25 SPS
Gain = 16
Polarity: bipolar
Reference buffers enabled
Sensor connected to the AIN4/AIN5 channel
Reference: REFIN2, the reference being provided by the
sense resistors of the pressure sensor.
Table 2. Pressure Sensor: Noise and Resolution
Parameter
Full Scale
Noise RMS
Peak-to-Peak
Noise
Effective (RMS)
Resolution
Noise-Free
(Peak-toPeak)
Resolution
Voltage Mode
Pressure Shorted
Sensor
Input
391.47
391.47
0.66
0.61
3.5
3.2
Current Mode
Pressure Shorted
Sensor
Input
438.45
438.45
1.76
1.69
11.1
9.8
Unit
kPa
Pa
Pa
19.2
19.3
17.9
18
Bits
16.8
16.9
15.3
15.4
Bits
1.5575
1.5570
1.5565
Rev. 0 | Page 11 of 13
1.5560
1.5555
1.5550
1.5545
1.5540
1.5535
1.5530
0
10
20
30
40
50
60
70
80
90
SAMPLES
Figure 14. Voltage Mode—Pressure Sensor Input Waveform
100
13355-014
0
PRESSURE (kPa)
THERMOCOUPLE
AND THERMISTOR
ERROR BAND
–1.5
–2.0
•
•
•
•
•
•
•
In current excitation mode, the AD7124-4 configuration is as
follows:
1.5
13355-013
THERMOCOUPLE TEMEPERATURE ERROR (°C)
The measurements were repeated with the thermocouple held
at 25°C and the cold junction swept from 0°C to 80°C (see
Figure 13). The system had an overall accuracy of 1.75°C, which
can be improved by using a more accurate cold junction such as
a Pt100 sensor.
CN-0382
Circuit Note
–0.062
–0.0230
–0.0235
–0.064
PRESSURE (kPa)
PRESSURE (kPa)
–0.0240
–0.0245
–0.0250
–0.0255
–0.066
–0.068
–0.070
–0.0260
–0.072
0
10
20
30
40
50
60
70
80
90
100
SAMPLES
Figure 15. Voltage Mode—Shorted Input Waveform
1.368
1.364
1.362
1.360
1.358
1.356
1.354
20
30
40
50
60
70
80
90
100
SAMPLES
13355-016
PRESSURE (kPa)
1.366
10
0
10
20
30
40
50
60
SAMPLES
70
80
90
Figure 17. Current Mode—Shorted Input Waveform
1.370
0
–0.074
Figure 16. Current Mode—Pressure Sensor Input Waveform
Rev. 0 | Page 12 of 13
100
13355-017
–0.0270
13355-015
–0.0265
Circuit Note
CN-0382
LEARN MORE
Circuit Note CN-0209. Fully Programmable Universal Analog
Front End for Process Control Applications. Analog Devices.
CN-0382 Design Support Package:
www.analog.com/CN0382-DesignSupport
Duff, Matthew and Joseph Towey. Two Ways to Measure
Temperature Using Thermocouples Feature Simplicity, Accuracy,
and Flexibility. Analog Dialogue 44-10. Analog Devices.
Cantrell, Mark. AN-0971 Application Note. Recommendations
for Control of Radiated Emissions with isoPower Devices.
Analog Devices.
Kester, Walt. “Temperature Sensors,” Chapter 7 in Sensor Signal
Conditioning. Analog Devices, 1999.
AN-615 Application Note. Peak-to-Peak Resolution Versus
Effective Resolution. Analog Devices.
AN-892 Application Note. Temperature Measurement Theory
and Practical Techniques. Analog Devices.
AN-0970 Application Note. RTD Interfacing and Linearization
Using an ADuC706x Microcontroller. Analog Devices.
Circuit Note CN-0325. PLC/DCS Universal Analog Input Using
Either 4 or 6 Pin Terminal Block. Analog Devices.
Circuit Note CN-0376. Channel-to-Channel Isolated
Temperature Input (Thermocouple/RTD) for PLC/DCS
Applications. Analog Devices.
Circuit Note CN-0381. Completely Integrated 4-Wire RTD
Measurement System Using a Low Power, Precision, 24-Bit,
Sigma-Delta ADC. Analog Devices.
Circuit Note CN-0383. Completely Integrated 3-Wire RTD
Measurement System Using a Low Power, Precision, 24-Bit,
Sigma-Delta ADC. Analog Devices.
Circuit Note CN-0384. Completely Integrated Thermocouple
Measurement System Using a Low Power, Precision, 24-Bit,
Sigma-Delta ADC. Analog Devices.
HART® Communication Foundation
MS-2644 Technical Article. Ultralow Power Opening
Applications to High Speed Isolation. Analog Devices.
Data Sheets and Evaluation Boards
MT-031 Tutorial. Grounding Data Converters and Solving the
Mystery of “AGND” and “DGND”. Analog Devices.
AD5421 Data Sheet and Evaluation Board
MT-101 Tutorial. Decoupling Techniques. Analog Devices.
ADG5433 Data Sheet
Circuit Note CN-0172. 3-Channel Thermocouple Temperature
Measurement System with 0.25 ° C Accuracy, Analog Devices.
ADuM1441 Data Sheet
Circuit Note CN-0206. Thermocouple Temperature Measurement
System with Less Than 500 µA Current Drain. Analog Devices.
REVISION HISTORY
AD7124-4 Data Sheet and Evaluation Board
AD5700 Data Sheet and Evaluation Board
ADP162 Data Sheet
7/15—Revision 0: Initial Version
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registered trademarks are the property of their respective owners.
CN13355-0-7/15(0)
Rev. 0 | Page 13 of 13