NCP3065, NCV3065 Up to 1.5 A Constant Current Switching Regulator for LEDs The NCP3065 is a monolithic switching regulator designed to deliver constant current for powering high brightness LEDs. The device has a very low feedback voltage of 235 mV (nominal) which is used to regulate the average current of the LED string. In addition, the NCP3065 has a wide input voltage up to 40 V to allow it to operate from 12 Vac or 12 Vdc supplies commonly used for lighting applications as well as unregulated supplies such as Lead Acid batteries. The device can be configured in a controller topology with the addition of an external transistor to support higher LED currents beyond the 1.5A rated switch current of the internal transistor. The NCP3065 switching regulator can be configured in Step-Down (Buck) and Step-Up (boost) topologies with a minimum number of external components. http://onsemi.com MARKING DIAGRAMS 8 3065 ALYWG G 1 SOIC-8 D SUFFIX CASE 751 1 Features •Integrated 1.5 A Switch •Input Voltage Range from 3.0 V to 40 V •Low Feedback Voltage of 235 mV •Cycle-by-Cycle Current Limit •No Control Loop Compensation Required •Frequency of Operation Adjustable up to 250 kHz •Operation with All Ceramic Output Capacitors or No Output Capacitance •Analog and Digital PWM Dimming Capability •Internal Thermal Shutdown with Hysteresis •Automotive Version Available Applications •Automotive and Marine Lighting •High Power LED Driver •Constant Current Source •Low Voltage LED Lighting NC SWC Ipk SWE CT Vin FB GND Vin R 3065 ALYW G G 1 DFN-8 MN SUFFIX CASE 488 = = = = = = Specific Device Code Assembly Location Wafer Lot Year Work Week Pb-Free Package ORDERING INFORMATION D Cout 22 mF See detailed ordering and shipping information in the package dimensions section on page 15 of this data sheet. LED Cluster D -LED Vth = 0.235 V Cin 220 mF 8 D L NCP3065 1 (Note: Microdot may be in either location) +LED Rs NCP3065 AWL YYWWG PDIP-8 P, P1 SUFFIX CASE 626 NCP3065 A L, WL Y, YY W, WW G or G (Landscape, Path, Solar, MR16 Replacement) 0.15 W 8 CT 2.2 nF Rsense 0.68 W Figure 1. Typical Buck Application Circuit © Semiconductor Components Industries, LLC, 2007 July, 2007 - Rev. 0 1 Publication Order Number: NCP3065/D NCP3065, NCV3065 1 Switch Collector Switch Emitter 2 8 N.C. 7 Ipk Sense Timing Capacitor 3 6 GND 4 5 ÇÇ ÇÇ ÇÇ ÇÇ Switch Collector Switch Emitter Timing Capacitor VCC GND Comparator Inverting Input (Top View) EP Flag Ç Ç Ç Ç (Top View) NOTE: N.C. Ipk Sense VCC Comparator Inverting Input EP Flag must be tied to GND Pin 4 on PCB Figure 2. Pin Connections Figure 3. Pin Connections NCP3065 8 1 TSD N.C. Switch Collector SET dominant R Q S 7 COMPARATOR + Ipk Sense 2 S Switch Emitter Q SET dominant R 0.2 V OSCILLATOR 6 3 Timing Capacitor CT +VCC COMPARATOR 0.235 V REFERENCE REGULATOR + - 5 4 GND Comparator Inverting Input Figure 4. Block Diagram PIN DESCRIPTION Pin No. Pin Name 1 Switch Collector 2 Switch Emitter 3 Timing Capacitor 4 GND 5 Comparator Inverting Input 6 VCC 7 Ipk Sense 8 N.C. Description Internal Darlington switch collector Internal Darlington switch emitter Timing Capacitor Oscillator Input, Timing Capacitor Ground pin for all internal circuits Inverting input pin of internal comparator Voltage supply Peak Current Sense Input to monitor the voltage drop across an external resistor to limit the peak current through the circuit Pin not connected http://onsemi.com 2 NCP3065, NCV3065 MAXIMUM RATINGS (measured vs. pin 4, unless otherwise noted) Rating Symbol Value Unit VCC (Pin 6) VCC 0 to +40 V Comparator Inverting Input (Pin 5) VCII -0.2 to +VCC V Darlington Switch Collector (Pin 1) VSWC 0 to +40 V Darlington Switch Emitter (Pin 2) (Transistor OFF) VSWE -0.6 to +VCC V Darlington Switch Collector to Emitter (Pins 1-2) VSWCE 0 to +40 V Darlington Switch Current ISW 1.5 A Ipk Sense (Pin 7) VIPK -0.2 to VCC + 0.2 V VTCAP -0.2 to +1.4 V PDIP-8 (Note 5) Thermal Resistance Junction-to-Air RqJA 100 SOIC-8 (Note 5) Thermal Resistance Junction-to-Air RqJA 180 DFN-8 (Note 5) Thermal Resistance Junction-to-Air Thermal Resistance Junction-to-Case RqJA RqJC 78 14 Storage Temperature Range TSTG -65 to +150 °C TJ(MAX) +150 °C Timing Capacitor (Pin 3) Power Dissipation and Thermal Characteristics °C/W °C/W °C/W Maximum Junction Temperature Operating Junction Temperature Range (Note 3) NCP3065, NCV3065 °C TJ -40 to +125 Stresses exceeding Maximum Ratings may damage the device. Maximum Ratings are stress ratings only. Functional operation above the Recommended Operating Conditions is not implied. Extended exposure to stresses above the Recommended Operating Conditions may affect device reliability. 1. This device series contains ESD protection and exceeds the following tests: Pin 1-8: Human Body Model 2000 V per AEC Q100-002; 003 or JESD22/A114; A115 Machine Model Method 200 V 2. This device contains latch-up protection and exceeds 100 mA per JEDEC Standard JESD78. 3. The relation between junction temperature, ambient temperature and Total Power dissipated in IC is TJ = TA + Rq • PD 4. The pins which are not defined may not be loaded by external signals 5. 1 oz copper, 1 in2 copper area http://onsemi.com 3 NCP3065, NCV3065 ELECTRICAL CHARACTERISTICS (VCC = 5.0 V, TJ = -40°C to +125°C, unless otherwise specified) Conditions Symbol Min Typ Max Unit (VPin 5 = 0 V, CT = 2.2 nF, TJ = 25°C) fOSC 110 150 190 kHz Discharge to Charge Current Ratio (Pin 7 to VCC, TJ = 25°C) IDISCHG / ICHG 5.5 6.0 6.5 - Capacitor Discharging Current (Pin 7 to VCC, TJ = 25°C) IDISCHG 1650 mA Capacitor Charging Current (Pin 7 to VCC, TJ = 25°C) ICHG 275 mA Current Limit Sense Voltage (TJ = 25°C) (Note 7) VIPK(Sense) (ISW = 1.0 A, TJ = 25°C) (Note 6) Characteristic OSCILLATOR Frequency 165 185 235 mV VSWCE(DROP) 1.0 1.3 V (VCE = 40 V) IC(OFF) 0.01 100 mA TJ = 25°C VTH 235 mV ±5 % OUTPUT SWITCH (Note 6) Darlington Switch Collector to Emitter Voltage Drop Collector Off-State Current COMPARATOR Threshold Voltage TJ = 0 to +85°C Threshold Voltage Line Regulation Input Bias Current TJ = -40°C to +125°C VTH -10 +10 % (VCC = 3.0 V to 40 V) REGLiNE -6.0 6.0 mV (Vin = Vth) ICII in -1000 1000 nA (VCC = 5.0 V to 40 V, CT = 2.2 nF, Pin 7 = VCC, VPin 5 > Vth, Pin 2 = GND, remaining pins open) ICC 7.0 mA -100 TOTAL DEVICE Supply Current Thermal Shutdown Threshold 160 °C Hysteresis 10 °C 6. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient temperature as possible. 7. The VIPK(Sense) Current Limit Sense Voltage is specified at static conditions. In dynamic operation the sensed current turn-off value depends on comparator response time and di/dt current slope. See the Operating Description section for details. 8. NCV prefix is for automotive and other applications requiring site and change control. http://onsemi.com 4 NCP3065, NCV3065 450 190 400 180 FREQUENCY (Hz) FREQUENCY (kHz) 350 300 250 200 150 170 160 150 140 100 130 50 120 0 110 0 1 2 3 4 5 6 7 8 9 10 11 12 1314 1516 1718 1920 3 7 12 16 21 25 29 34 38 40 Ct, CAPACITANCE (nF) VCC, SUPPLY VOLTAGE (V) Figure 5. Oscillator Frequency vs. Oscillator Timing Capacitor Figure 6. Oscillator Frequency vs. Supply Voltage 2.4 1.25 VCC = 5.0 V IE = 1 A VCC = 5.0 V IC = 1 A 1.20 VOLTAGE DROP (V) 2.2 VOLTAGE DROP (V) CT = 2.2 nF TJ = 25°C 2.0 1.8 1.6 1.4 1.15 1.10 1.05 1.2 1.0 -50 0 50 100 1.0 -50 150 50 100 150 TJ, JUNCTION TEMPERATURE (°C) TJ, JUNCTION TEMPERATURE (°C) Figure 7. Emitter Follower Configuration Output Darlington Switch Voltage Drop vs. Temperature Figure 8. Common Emitter Configuration Output Darlington Switch Voltage Drop vs. Temperature 1.5 2.0 1.9 1.4 VCC = 5.0 V TJ = 25°C 1.7 1.6 1.5 1.4 1.3 1.2 1.1 1.0 0.9 0.8 1.2 0.7 1.1 1.0 0.6 0.5 0 VCC = 5.0 V TJ = 25°C 1.3 VOLTAGE DROP (V) 1.8 VOLTAGE DROP (V) 0 0.5 1.0 0 1.5 0.5 1.0 IE, EMITTER CURRENT (A) IC, COLLECTOR CURRENT (A) Figure 9. Emitter Follower Configuration Output Darlington Switch Voltage Drop vs. Emitter Current Figure 10. Common Emitter Configuration Output Darlington Switch Voltage Drop vs. Collector Current http://onsemi.com 5 1.5 0.25 0.30 Vipk(sense), CURRENT LIMIT SENSE VOLTAGE (V) Vth, COMPARATOR THRESHOLD VOLTAGE (V) NCP3065, NCV3065 0.245 0.24 0.235 0.23 0.225 0.22 -50 -30 -10 10 30 50 70 90 110 130 150 0.28 0.26 0.24 0.22 0.20 0.18 0.16 0.14 0.12 0.10 -40 -25 -10 TJ, JUNCTION TEMPERATURE (°C) 5 20 ICC, SUPPLY CURRENT (mA) 65 80 95 110 125 Figure 12. Current Limit Sense Voltage vs. Temperature 6.0 5.5 5.0 4.5 4.0 3.5 CT = 2.2 nF Pin 5, 7 = VCC Pin 2 = GND 3.0 2.5 2.0 8.0 50 TJ, JUNCTION TEMPERATURE (°C) Figure 11. Comparator Threshold Voltage vs. Temperature 3.0 35 13 18 23 28 33 38 43 VCC, SUPPLY VOLTAGE (V) Figure 13. Standby Supply Current vs. Supply Voltage http://onsemi.com 6 NCP3065, NCV3065 INTRODUCTION comparator value, the output switch cycle is inhibited. When the load current causes the output voltage to fall below the nominal value feedback comparator enables switching immediately. Under these conditions, the output switch conduction can be enabled for a partial oscillator cycle, a partial cycle plus a complete cycle, multiple cycles, or a partial cycle plus multiple cycles. The NCP3065 is a monolithic power switching regulator optimized for LED Driver applications. Its flexible architecture enables the system designer to directly implement a step-up or step-down topology with a minimum number of external components for driving LEDs. A representative block diagram is shown in Figure 4. OPERATING DESCRIPTION The NCP3065 operates as a fixed oscillator frequency output voltage ripple gated regulator. In general, this mode of operation is somewhat analogous to a capacitor charge pump and does not require dominant pole loop compensation for converter stability. The typical operating waveforms are shown in Figure 14. The output voltage waveform shown is for a step-down converter with the ripple and phasing exaggerated for clarity. During initial converter startup, the feedback comparator senses that the output voltage level is below nominal. This causes the output switch to turn on and off at a frequency and duty cycle controlled by the oscillator, thus pumping up the output filter capacitor. When the feedback voltage level reaches nominal Oscillator The oscillator frequency and off-time of the output switch are programmed by the value of the timing capacitor CT. Capacitor CT is charged and discharged by a 1 to 6 ratio internal current source and sink, generating a positive going sawtooth waveform at Pin 3. This ratio sets the maximum tON/(tON+tOFF) of the switching converter as 6/(6+1) or 85.7% (typical). The oscillator peak and valley voltage difference is 500 mV typically. To calculate the CT capacitor value for required oscillator frequency, use the equations found in Figure 22. An online NCP3065 design tool can be found at www.onsemi.com, which adds in selecting component values. 1 Feedback Comparator Output 0 1 IPK Comparator Output 0 Timing Capacitor, CT On Output Switch Off Nominal Output Voltage Level Output Voltage Startup Operation Figure 14. Typical Operating Waveforms http://onsemi.com 7 NCP3065, NCV3065 Peak Current Sense Comparator LED Dimming Under normal conditions, the output switch conduction is initiated by the Voltage Feedback comparator and terminated by the oscillator. Abnormal operating conditions occur when the converter output is overloaded or when feedback voltage sensing is lost. Under these conditions, the Ipk Current Sense comparator will protect the Darlington output Switch. The switch current is converted to a voltage by inserting a fractional ohm resistor, RSC, in series with VCC and the Darlington output switch. The voltage drop across RSC is monitored by the Current Sense comparator. If the voltage drop exceeds 200 mV (nom) with respect to VCC, the comparator will set the latch and terminate the output switch conduction on a cycle-by-cycle basis. This Comparator/Latch configuration ensures that the Output Switch has only a single on-time during a given oscillator cycle. The COMP pin of the NCP3065 is used to provide dimming capability. In digital input mode the PWM input signal inhibits switching of the regulator and reduces the average current through the LEDs. In analog input mode a PWM input signal is RC filtered and the resulting voltage is summed with the feedback voltage thus reduces the average current through the LEDs. Figure 15 illustrated the linearity of the digital dimming function with a 200 Hz digital PWM. For further information on dimming control refer to application note AND8298. 24 Vin, Vf = 3.6 V 600 I1 di/dt slope Vipk(sense) 24 Vin, Vf = 7.2 V 700 ILED (mA) Real Vturn-off on Rs Resistor 800 Io I through the Darlington Switch 500 12 Vin, Vf = 3.6 V 400 300 200 100 t_delay 0 0 10 20 30 40 50 60 70 80 90 100 DUTY CYCLE (%) The VIPK(Sense) Current Limit Sense Voltage threshold is specified at static conditions. In dynamic operation the sensed current turn-off value depends on comparator response time and di/dt current slope. Real Vturn-off on Rsc resistor Figure 15. No Output Capacitor Operation A constant current buck regulator such as the NCP3065 focuses on the control of the current through the load, not the voltage across it. The switching frequency of the NCP3065 is in the range of 100-300 kHz which is much higher than the human eye can detect. This allows us to relax the ripple current specification to allow higher peak to peak values. This is achieved by configuring the NCP3065 in a continuous conduction buck configuration with low peak to peak ripple thus eliminating the need for an output filter capacitor. The important design parameter is to keep the peak current below the maximum current rating of the LED. Using 15% peak to peak ripple results in a good compromise between achieving max average output current without exceeding the maximum limit. This saves space and reduces part count for applications that require a compact footprint. (Example: See Figure 17) See application note AND8298 for more information. Vturn_off + Vipk(sense) ) Rsc @ (t_delay @ dińdt) Typical Ipk comparator response time t_delay is 350 ns. The di/dt current slope is dependent on the voltage difference across the inductor and the value of the inductor. Increasing the value of the inductor will reduce the di/dt slope. It is recommended to verify the actual peak current in the application at worst conditions to be sure that the max peak current will never get over the 1.5A Darlington Switch Current max rating. Thermal Shutdown Internal thermal shutdown circuitry is provided to protect the IC in the event that the maximum junction temperature is exceeded. When activated, typically at 165°C, the Darlington Output Switch is disabled. The temperature sensing circuit is designed with some hysteresis. The Darlington Switch is enabled again when the chip temperature decreases under the low threshold. This feature is provided to prevent catastrophic failures from accidental device overheating. It is not intended to be used as a replacement for proper heatsinking. Output Switch The output switch is designed in a Darlington configuration. This allows the application designer to operate at all conditions at high switching speed and low voltage drop. The Darlington Output Switch is designed to switch a maximum of 40 V collector to emitter voltage and current up to 1.5 A. http://onsemi.com 8 NCP3065, NCV3065 APPLICATIONS Figure 16 gives the relevant design equations for the key parameters. Additionally, a complete application design aid for the NCP3065 can be found at www.onsemi.com. Figures 16 through 24 show the simplicity and flexibility of the NCP3065. Two main converter topologies are demonstrated with actual test data shown below each of the circuit diagrams. (See Notes 9, 10, 11) ton toff Step-Down Step-Up Vout ) VF Vin * VSWCE * Vout Vout ) VF * Vin Vin * VSWCE ton toff ton toff ton fǒton ) 1Ǔ fǒton ) 1Ǔ t t off off *6 CT + 381.6 @ 10 * 343 @ 10 *12 fosc CT ǒ Ǔ IL(avg) Iout t Iout on ) 1 toff Ipk (Switch) DI IL(avg) ) L 2 DI IL(avg) ) L 2 RSC 0.20 Ipk(Switch) 0.20 Ipk(Switch) L * Vout ǒVin * VSWCE Ǔton DIL ǒVin *DIVLSWCEǓton Vripple(pp) DIL Vout I out Ǹǒ 1 8fCO VTH Ǔ 2 t I [ on out ) DIL @ ESR CO ) (ESR) 2 ǒRR2 ) 1Ǔ VTH 1 V refńR sense ǒRR2 ) 1Ǔ 1 V refńR sense 9. VSWCE - Darlington Switch Collector to Emitter Voltage Drop, refer to Figures 7, 8, 9 and 10. 10. VF - Output rectifier forward voltage drop. Typical value for 1N5819 Schottky barrier rectifier is 0.4 V. 11. The calculated ton/toff must not exceed the minimum guaranteed oscillator charge to discharge ratio. The Following Converter Characteristics Must Be Chosen: Vin - Nominal operating input voltage. Vout - Desired output voltage. Iout - Desired output current. DIL - Desired peak-to-peak inductor ripple current. For maximum output current it is suggested that DIL be chosen to be less than 10% of the average inductor current IL(avg). This will help prevent Ipk (Switch) from reaching the current limit threshold set by RSC. If the design goal is to use a minimum inductance value, let DIL = 2(IL(avg)). This will proportionally reduce converter output current capability. f - Maximum output switch frequency. Vripple(pp) - Desired peak-to-peak output ripple voltage. For best performance the ripple voltage should be kept to a low value since it will directly affect line and load regulation. Capacitor CO should be a low equivalent series resistance (ESR) electrolytic designed for switching regulator applications. Figure 16. Design Equations http://onsemi.com 9 NCP3065, NCV3065 NTF2955 Q4 MMBT3904LT1G Q5 R15 6x 1R0 ±1%R 0R10 R1 J2 R2 R3 R4 R5 R6 R7 1206 1206 1206 1206 1206 1206 1206 1 +VIN C4 J3 U1 8 N.C. SWC 1 7 SWE 2 IPK 6 3 VCC TCAP 5 COMP GND 4 + D2 +VAUX +LED C1 1208 0.1 mF C3 1.8 nF D1 + C6 NU MBRS140LT3G R14 NU R9 BC807-LT1G 470 mH 15 k C5 Q1 J6 R8 CT 1 GND J4 1 J1 1 L1 NCP3065 SOIC8 C2 220 mF / 50 V 0.1 mF MMSD4148 1k 100 pF J5 1 R10 0805 10 k 1k R12 RSENSE ±1% R13 NU Q2 -LED J7 1 GND R11 BC817-LT1G 1 ON/OFF Figure 17. Buck Demo Board with External Switch Application Schematic efficiency with 1 and 2 LEDs and output currents of 350mA and 700 mA. Additional data and design information can be found of this design in Application Note AND8298. This design illustrates the NCP3065 being used as a PFET controller, the design has been optimized for continuous current operation with low ripple which allows the output filter capacitor to be eliminated. Figure 20 illustrates the Value of Components Name Value Name Value C1, C4 100 nF, Ceramic Capacitor, 1206 Q5 MMBT3904LT1G, SOT23 C2 220 mF, 50 V, Electrolytic Capacitor R1 100 mW, 0.5 W C3 1.8 nF, Ceramic Capacitor, 0805 R8 15 k, resistor 0805 C5 100 pF, Ceramic Capacitor, 0805 R9 10 kW, resistor 0805 D1 1 A, 40 V Schottky Rectifier R10, R15 1 kW, resistor 0805 D2 MMSD4148 R11 1.2 kW, resistor 0805 L1 470 mH, DO5022P-474ML Coilcraft Inductor R12 RSENSE ±1%, 1206 Q4 NTF2955, P-MOSFET, SOT223 U1 NCP3065, SOIC8 NOTE: RSENSE is used to select LED output current, for 350 mA use 680 mW, for 700 mA use 330 mW and for 1000 mA use 220 mW Test Results (without output capacitor) Test Condition Results Line Regulation Vin = 9 V to 35 V, Io = 350 mA 12 mA Load Regulation Vin = 12 V, Io = 350 mA, Vo = 3 V to 8 V 13 mA Output Ripple Vin = 9 V to 35 V, Io = 350 mA < 15% IO Efficiency Vin = 12 V, Io = 350 mA, VOUT = 3 to 8 V > 75% http://onsemi.com 10 NCP3065, NCV3065 88 84 EFFICIENCY (%) VOUT = 7.2 V, No Output Cap 80 76 72 68 VOUT = 3.6 V, No Output Cap 64 60 4 8 12 16 20 24 28 32 36 VIN, INPUT VOLTAGE (V) Figure 19. Efficiency vs. Input Voltage for the 1.5 A Buck Demo Board at Iout = 700 mA, TA = 255C, Without Output Capacitor Figure 18. 1.5 A Buck Demoboard Layout 88 88 84 84 VOUT = 7.2 V, Output Cap 100 mF VOUT = 7.2 V, Output Cap 100 mF EFFICIENCY (%) EFFICIENCY (%) 80 76 72 68 64 VOUT = 3.6 V, Output Cap 100 mF 80 76 72 VOUT = 3.6 V, Output Cap 100 mF 68 64 60 56 60 4 8 12 16 20 24 28 32 36 4 8 12 16 20 24 28 32 36 VIN, INPUT VOLTAGE (V) VIN, INPUT VOLTAGE (V) Figure 20. Efficiency vs. Input Voltage for the 1.5 A Buck Demo Board at Iout = 350 mA, TA = 255C, with 100 mF Output Capacitor Figure 21. Efficiency vs. Input Voltage for the 1.5 A Buck Demo Board at Iout = 700 mA, TA = 255C, with 100 mF Output Capacitor http://onsemi.com 11 NCP3065, NCV3065 L1 6x 1R0 ±1%R 0R15 R1 R2 R3 R4 R5 100 mH R6 R7 J2 1 C5 +VIN J4 + C3 220 mF / 50 V 0.1 mF 1 U1 8 N.C. SWC 7 SWE IPK 6 VCC TCAP 5 COMP GND 4 NCP3065 J1 1 +VOUT D1 C2 C4 2.2 nF + C1 100 mF / 50 V 0.1 mF J5 1 1k0 +VAUX 2 3 R8 GND J6 1 MBRS140LT3G 1 GND R9 -LED RSENSE D2 BC807-LT1G Q1 Q2 MM3Z36VT1G R11 NU J7 R10 1 ON/OFF 1k2 BC817-LT1G Figure 22. Boost Demo Board Application Schematic Value of Components Name Value Name Value C1 100 mF/50 V, Electrolytic Capacitor Q2 BC817-LT1G, SOT23 C2, C5 100 nF, Ceramic Capacitor, 1206 R1 150 mW, resistor 0.5 W C3 220 mF/50 V, Electrolytic Capacitor R8 1 k, resistor 0805 C4 2.2 nF, Ceramic Capacitor, 0805 R9 Load current sense resistor, 1206 D1 MBRS140LT3G, Schottky diode R10 1.2 k, resistor 0805 D2 MMSZ36VT1G, Zener diode U1 NCP3065, SOIC8 L1 100 mH, DO3340P-104ML Coilcraft Inductor Test Results Test Condition Results Line Regulation Vin = 10 V to 20 V, Vo = 22 V, IOAVG = 350 mA 25 mA Output Ripple Vin = 8 V to 20 V, Vo = 22 V, IOAVG = 350 mA 50 mA Efficiency Vin = 10 to 20 V, IOAVG = 350 mA > 83 % http://onsemi.com 12 J3 1 NCP3065, NCV3065 95 93 EFFICIENCY (%) 91 89 87 85 83 81 79 77 75 8 10 12 14 16 18 20 VIN, INPUT VOLTAGE (V) Figure 24. Efficiency vs. Input Voltage for the Boost Demo Board at IOUT = 350 mA, VOUT = 22 V (6xLED with VF = 3.6 V), TA = 255C Figure 23. Boost Demoboard Layout http://onsemi.com 13 22 NCP3065, NCV3065 MTB30P06V Q4 MMBT3904LT1G Q5 R15 6x 1R0 ±1%R 0R04 R1 R2 J2 R3 R4 R5 R6 U1 8 N.C. SWC 1 7 SWE 2 IPK 6 3 VCC TCAP 5 COMP GND 4 R7 1206 1206 1206 1206 1206 1206 1 +VIN C4 J3 + C7 + 1 mF / 50 V C2 220 mF / 50 V 0.1 mF +VAUX 15 k C3 1.8 nF C5 R14 NU L1 +LED C1 1206 0.1 mF D1 C6 220 mF / 50 V J5 1 R10 1k R16 0R15 ±1% R13 NU Q2 + 100 pF 0805 10 k 0805 Q1 R8 CT MBRS140LT3G R9 J1 1 PF0504.223NL NCP3065 SOIC8 0.1 mF BC807-LT1G D2 C8 1 GND J4 1 MMSD4148 1k R12 0R15 ±1% J6 -LED J7 1 GND R11 1 1k2 ON/OFF 0805 BC817-LT1G Figure 25. Buck Demoboard with External Switch Application Schematic Value of Components Name Value Name Value C1 100 mF, 50 V, Electrolytic Capacitor Q4 MTB30P06V, P-MOS transistor C1, C4, C8 100 nF, Ceramic Capacitor, 1206 Q5 MMBT3904LT1G C2, C6 220 mF, 50 V, Electrolytic Capacitor R1 40 mW, Resistor 0.5 W C3 2.2 nF, Ceramic Capacitor, 0805 R8 6k8, Resistor 0805 C5 100 pF, Ceramic Capacitor, 0805 R9 10k, Resistor 0805 C7 1 mF / 50 V, Ceramic Capacitor, 1206 R10 1k, Resistor 0805 D1 MBRS540LT3G, Schottky Diode R11 1k2, Resistor 0805 D2 MMSD4148T1G, Diode R12, R16 150 mW, Resistor 0.5 W L1 22 mH U1 NCP3065, SOIC8 Q2 BC817-LT1G, SOT23 Test Results Test Condition Results Line Regulation Vin = 8 V to 35 V, Io = 3000 mA < 6% Output Ripple Vin = 12 V, Io = 3000 mA < 6% Efficiency Vin = 12 V, Io = 3000 mA > 78% Short Circuit Current Vin = 12 V, Rload = 0.15 W http://onsemi.com 14 NCP3065, NCV3065 EFFICIENCY (%) 90 88 86 84 82 80 78 76 74 72 70 68 66 8 10 12 14 16 18 20 22 24 26 28 30 32 34 36 VIN, INPUT VOLTAGE (v) Figure 27. Efficiency vs. Input Voltage for the 3A Buck Demo Board at IOUT = 3 A, VOUT = 4 V, TA = 255C Figure 26. 3 A Buck Demoboard Layout ORDERING INFORMATION Package Shipping† NCP3065MNTXG DFN-8 (Pb-Free) 4000 Units / Tape & Reel NCP3065PG PDIP-8 (Pb-Free) 50 Units / Rail NCP3065DR2G SOIC-8 (Pb-Free) 2500 Units / Tape & Reel NCV3065MNTXG DFN-8 (Pb-Free) 4000 Units / Tape & Reel NCV3065PG PDIP-8 (Pb-Free) 50 Units / Rail NCV3065DR2G SOIC-8 (Pb-Free) 2500 Units / Tape & Reel Device †For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging Specifications Brochure, BRD8011/D. http://onsemi.com 15 NCP3065, NCV3065 PACKAGE DIMENSIONS 8 LEAD PDIP CASE 626-05 ISSUE L 8 5 -B1 4 F -A- NOTE 2 L C J -TN SEATING PLANE D H NOTES: 1. DIMENSION L TO CENTER OF LEAD WHEN FORMED PARALLEL. 2. PACKAGE CONTOUR OPTIONAL (ROUND OR SQUARE CORNERS). 3. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. M K G 0.13 (0.005) M T A M B M http://onsemi.com 16 DIM A B C D F G H J K L M N MILLIMETERS MIN MAX 9.40 10.16 6.10 6.60 3.94 4.45 0.38 0.51 1.02 1.78 2.54 BSC 0.76 1.27 0.20 0.30 2.92 3.43 7.62 BSC --10_ 0.76 1.01 STYLE 1: PIN 1. 2. 3. 4. 5. 6. 7. 8. AC IN DC + IN DC - IN AC IN GROUND OUTPUT AUXILIARY VCC INCHES MIN MAX 0.370 0.400 0.240 0.260 0.155 0.175 0.015 0.020 0.040 0.070 0.100 BSC 0.030 0.050 0.008 0.012 0.115 0.135 0.300 BSC --10_ 0.030 0.040 NCP3065, NCV3065 PACKAGE DIMENSIONS SOIC-8 NB CASE 751-07 ISSUE AH NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DIMENSION A AND B DO NOT INCLUDE MOLD PROTRUSION. 4. MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER SIDE. 5. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.127 (0.005) TOTAL IN EXCESS OF THE D DIMENSION AT MAXIMUM MATERIAL CONDITION. 6. 751-01 THRU 751-06 ARE OBSOLETE. NEW STANDARD IS 751-07. -XA 8 5 S B 0.25 (0.010) M Y M 1 4 K -YG C N DIM A B C D G H J K M N S X 45 _ SEATING PLANE -Z- 0.10 (0.004) H M D 0.25 (0.010) M Z Y S X J S SOLDERING FOOTPRINT* 1.52 0.060 7.0 0.275 4.0 0.155 0.6 0.024 1.270 0.050 SCALE 6:1 mm Ǔ ǒinches *For additional information on our Pb-Free strategy and soldering details, please download the ON Semiconductor Soldering and Mounting Techniques Reference Manual, SOLDERRM/D. http://onsemi.com 17 MILLIMETERS MIN MAX 4.80 5.00 3.80 4.00 1.35 1.75 0.33 0.51 1.27 BSC 0.10 0.25 0.19 0.25 0.40 1.27 0_ 8_ 0.25 0.50 5.80 6.20 INCHES MIN MAX 0.189 0.197 0.150 0.157 0.053 0.069 0.013 0.020 0.050 BSC 0.004 0.010 0.007 0.010 0.016 0.050 0 _ 8 _ 0.010 0.020 0.228 0.244 NCP3065, NCV3065 PACKAGE DIMENSIONS 8 PIN DFN, 4x4 CASE 488AF-01 ISSUE B A D 8X L ÇÇ Ç ÇÇ Ç ÇÇ Ç 8X B PIN ONE IDENTIFICATION K 1 8 E b 2X 0.15 C 0.10 C 8X 0.08 C SEATING PLANE A1 8X NOTE 3 D2 4 5 0.15 C 2X E2 0.05 C ÇÇÇ Ç ÇÇÇ Ç DIM A A1 A3 b D D2 E E2 e K L e 0.10 C A B TOP VIEW NOTES: 1. DIMENSIONS AND TOLERANCING PER ASME Y14.5M, 1994. 2. CONTROLLING DIMENSION: MILLIMETERS. 3. DIMENSION b APPLIES TO PLATED TERMINAL AND IS MEASURED BETWEEN 0.25 AND 0.30 MM FROM TERMINAL. 4. COPLANARITY APPLIES TO THE EXPOSED PAD AS WELL AS THE TERMINALS. BOTTOM VIEW MILLIMETERS MIN MAX 0.80 1.00 0.00 0.05 0.20 REF 0.25 0.35 4.00 BSC 1.91 2.21 4.00 BSC 2.09 2.39 0.80 BSC 0.20 --0.30 0.50 A (A3) C SIDE VIEW SOLDERING FOOTPRINT* 4.30 8X 2.21 ÇÇ ÇÇ ÇÇ ÇÇ ÇÇ ÇÇ 2.39 1 8X 0.35 DIMENSIONS: MILLIMETERS ÇÇ ÇÇ ÇÇ ÇÇ ÇÇ ÇÇ 0.63 0.40 0.80 PITCH 2.75 *For additional information on our Pb-Free strategy and soldering details, please download the ON Semiconductor Soldering and Mounting Techniques Reference Manual, SOLDERRM/D. ON Semiconductor and are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice to any products herein. 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