SPT7863 10-BIT, 40 MSPS, 160 mW A/D CONVERTER TECHNICAL DATA AUGUST 21, 2001 FEATURES APPLICATIONS • • • • • • • • • • • All high-speed applications where low power dissipation is required • Video imaging • Medical imaging • Radar receivers • IR imaging • Digital communications Monolithic 40 MSPS converter 160 mW power dissipation On-chip track-and-hold Single +5 V power supply TTL/CMOS outputs 5 pF input capacitance Low cost Tri-state output buffers High ESD protection: 3,500 V minimum Selectable +3 V or +5 V logic I/O GENERAL DESCRIPTION The SPT7863 is a 10-bit monolithic, low-cost, ultralowpower analog-to-digital converter capable of minimum word rates of 40 MSPS. The on-chip track-and-hold function assures very good dynamic performance without the need for external components. The input drive requirements are minimized due to the SPT7863’s low input capacitance of only 5 pF. SPT7863 is pin-compatible with an entire family of 10-bit, CMOS converters (SPT7835/40/50/55/60/61), which simplifies upgrades. The SPT7863 has incorporated proprietary circuit design and CMOS processing technologies to achieve its advanced performance. Inputs and outputs are TTL/CMOS-compatible to interface with TTL/CMOS logic systems. Output data format is straight binary. Power dissipation is extremely low at only 160 mW typical at 40 MSPS with a power supply of +5.0 V. The digital outputs are +3 V or +5 V, and are user selectable. The The SPT7863 is available in 28-lead SOIC and 32-lead small (7 mm square) TQFP packages over the commercial temperature range. BLOCK DIAGRAM ADC Section 1 AIN 1:16 Mux T/H AutoZero CMP 11-Bit SAR D10 Overrange 11 D9 (MSB) 11 CLK In .. . P2 Timing P15 and Control Enable P16 .. . ADC Section 15 .. . 11 .. . ADC Section 2 ADC Section 16 T/H Data Valid D8 DAC P1 AutoZero CMP 11 11-Bit SAR D7 11 11-Bit 16:1 Mux/ Error Correction D6 D5 D4 D3 11 D2 DAC D1 Ref In Reference Ladder VREF D0 (LSB) ABSOLUTE MAXIMUM RATINGS (Beyond which damage may occur)1 25 °C Supply Voltages AVDD ...................................................................... +6 V DVDD ..................................................................... +6 V Output Digital Outputs ................................................... 10 mA Temperature Operating Temperature ................................ 0 to 70 °C Junction Temperature ........................................ 175 °C Lead Temperature, (soldering 10 seconds) ....... 300 °C Storage Temperature ............................ –65 to +150 °C Input Voltages Analog Input .............................. –0.5 V to AVDD +0.5 V VREF .............................................................. 0 to AVDD CLK Input ............................................................... VDD AVDD – DVDD .................................................. ±100 mV AGND – DGND .............................................. ±100 mV Note: 1. Operation at any Absolute Maximum Rating is not implied. See Electrical Specifications for proper nominal applied conditions in typical applications. ELECTRICAL SPECIFICATIONS TA=TMIN to TMAX, AVDD=DVDD=OVDD=+5.0 V, VIN=0 to 4 V, ƒS=40 MSPS, VRHS=4.0 V, VRLS=0.0 V, unless otherwise specified. PARAMETERS TEST CONDITIONS TEST LEVEL Resolution DC Accuracy Integral Linearity Error (ILE) Differential Linearity Error (DLE) No Missing Codes Analog Input Input Voltage Range Input Resistance Input Capacitance Input Bandwidth Offset Gain Error MIN SPT7863 TYP MAX 10 UNITS Bits 51% duty cycle VI VI VI (Small Signal) ±1.0 ±0.5 Guaranteed VI IV V V V V VRLS 50 V kΩ pF MHz LSB % 600 Ω MHz 5.0 ±2.0 ±0.2 VI V 300 100 IV IV V V V 0 3.0 1.0 Reference Settling Time VRHS VRLS V V Conversion Characteristics Maximum Conversion Rate Minimum Conversion Rate Pipeline Delay (Latency) Aperture Delay Time Aperture Jitter Time VI IV IV V V 500 150 4.0 90 75 2.0 AVDD 5.0 Clock Cycles Clock Cycles 4.0 30 MHz MHz Clock Cycles ns ps (p-p) 9.2 8.7 Bits Bits 57 54 dB dB 12 55 V V V mV mV 15 20 40 2 VI V VI V VRHS 250 Reference Input Resistance Bandwidth Voltage Range VRLS VRHS VRHS – VRLS ∆(VRHF – VRHS) ∆(VRLS – VRLF) Dynamic Performance Effective Number of Bits (ENOB) ƒIN = 3.58 MHz ƒIN = 10 MHz Signal-to-Noise Ratio (SNR) (without Harmonics) ƒIN = 3.58 MHz ƒIN = 10 MHz LSB LSB SPT7863 2 8/21/01 ELECTRICAL SPECIFICATIONS TA=TMIN to TMAX, AVDD=DVDD=OVDD=+5.0 V, VIN=0 to 4 V, ƒS=40 MSPS, VRHS=4.0 V, VRLS=0.0 V, unless otherwise specified. PARAMETERS Dynamic Performance Total Harmonic Distortion (THD) ƒIN = 3.58 MHz ƒIN = 10 MHz Signal-to-Noise and Distortion (SINAD) ƒIN = 3.58 MHz ƒIN = 10 MHz Spurious Free Dynamic Range Differential Phase Differential Gain TEST CONDITIONS TEST LEVEL ƒIN = 3.580 MHz Inputs Logic 1 Voltage Logic 0 Voltage Maximum Input Current Low Maximum Input Current High Input Capacitance Digital Outputs Logic 1 Voltage Logic 0 Voltage tRISE tFALL Output Enable to Data Output Delay IOH = 0.5 mA IOL = 1.6 mA 15 pF load 15 pF load 20 pF load, TA = +25 °C 50 pF load over temp. Power Supply Requirements Voltages OVDD DVDD AVDD Currents AIDD DIDD Power Dissipation TEST LEVEL CODES All electrical characteristics are subject to the following conditions: All parameters having min/max specifications are guaranteed. The Test Level column indicates the specific device testing actually performed during production and Quality Assurance inspection. Any blank section in the data column indicates that the specification is not tested at the specified condition. LEVEL I II III IV V VI MIN SPT7863 TYP VI V 64 67 62 VI V V V V 54 57 54 70 ±0.3 ±0.3 VI VI VI VI VI 2.0 MAX dB dB dB dB dB Degree % 0.8 +10 +10 –10 –10 +5 VI VI V V V V 3.5 IV IV IV VI VI VI 3.0 4.75 4.75 0.4 10 10 10 22 5.0 5.0 17 16 160 UNITS 5.0 5.25 5.25 21 21 210 V V µA µA pF V V ns ns ns ns V V V mA mA mW TEST PROCEDURE 100% production tested at the specified temperature. 100% production tested at TA = +25 °C, and sample tested at the specified temperatures. QA sample tested only at the specified temperatures. Parameter is guaranteed (but not tested) by design and characterization data. Parameter is a typical value for information purposes only. 100% production tested at TA = +25 °C. Parameter is guaranteed over specified temperature range. SPT7863 3 8/21/01 SPECIFICATION DEFINITIONS APERTURE DELAY DIFFERENTIAL LINEARITY ERROR (DLE) Aperture delay represents the point in time, relative to the rising edge of the CLOCK input, that the analog input is sampled. Error in the width of each code from its theoretical value. (Theoretical = VFS/2N) INTEGRAL LINEARITY ERROR (ILE) APERTURE JITTER Linearity error refers to the deviation of each individual code (normalized) from a straight line drawn from –FS through +FS. The deviation is measured from the edge of each particular code to the true straight line. The variations in aperture delay for successive samples. CLOCK DUTY CYCLE Ratio of positive clock time (tCH) to total clock period (tCLK) times 100%. t Duty Cycle = CH X 100% tCLK OUTPUT DELAY Time between the clock’s triggering edge and output data valid. OVERVOLTAGE RECOVERY TIME DIFFERENTIAL GAIN (DG) The time required for the ADC to recover to full accuracy after an analog input signal 125% of full scale is reduced to 50% of the full-scale value. A signal consisting of a sine wave superimposed on various DC levels is applied to the input. Differential gain is the maximum variation in the sampled sine wave amplitudes at these DC levels. SIGNAL-TO-NOISE RATIO (SNR) The ratio of the fundamental sinusoid power to the total noise power. Harmonics are excluded. DIFFERENTIAL PHASE (DP) A signal consisting of a sine wave superimposed on various DC levels is applied to the input. Differential phase is the maximum variation in the sampled sine wave phases at these DC levels. SIGNAL-TO-NOISE AND DISTORTION (SINAD) The ratio of the fundamental sinusoid power to the total noise and distortion power. EFFECTIVE NUMBER OF BITS (ENOB) TOTAL HARMONIC DISTORTION (THD) SINAD = 6.02N + 1.76, where N is equal to the effective number of bits. N= The ratio of the total power of the first 9 harmonics to the power of the measured sinusoidal signal. SINAD – 1.76 6.02 SPURIOUS FREE DYNAMIC RANGE (SFDR) The ratio of the fundamental sinusoidal amplitude to the single largest harmonic or spurious signal. INPUT BANDWIDTH Small signal (50 mV) bandwidth (3 dB) of analog input stage. SPT7863 4 8/21/01 Figure 1A – Timing Diagram 1 1 11 13 9 3 17 ANALOG IN 7 5 15 CLOCK IN SAMPLING CLOCK (Internal) INVALID VALID DATA OUTPUT 1 2 3 4 5 DATA VALID Figure 1B – Timing Diagram 2 tCLK tC tCH tCL CLOCK IN DATA OUTPUT Data 0 Data 1 Data 3 Data 2 tOD DATA VALID tS tCH tS tCL Table I – Timing Parameters DESCRIPTION PARAMETERS MIN tC tCLK ns Clock Period tCLK 25 ns Clock to Output Delay (15 pF Load) tOD 17 ns tS 10 ns Conversion Time Clock to DAV TYP MAX UNITS SPT7863 5 8/21/01 Figure 2 – Typical Interface Circuit Ref In (+4 V) DAV VRHF VRHS VRLS VRLF VIN VIN SPT7863 SPT7860 VCAL CLK IN 3.3/5 DGND D4 Interfacing Logics D3 D2 D1 D0 CLK AVDD D10 D9 D8 D7 D6 D5 DVDD AGND EN DGND* DVDD 3.3/5 Enable/Tri-State (Enable = Active Low) +A5 L1 AGND +A5 + 10 µF +5 V Analog +5 V Analog RTN 3.3/5 DGND *To reduce the possibility of latch-up, avoid connecting the DGND pins of the ADC to the digital ground of the system. + 10 µF +5 V Digital RTN +5 V Digital NOTES: 1) L1 is to be located as closely to the device as possible. 2) All capacitors are 0.1 µF surface-mount unless otherwise specified. 3) L1 is a 10 µH inductor or a ferrite bead. TYPICAL INTERFACE CIRCUIT OPERATING DESCRIPTION Very few external components are required to achieve the stated device performance. Figure 2 shows the typical interface requirements when using the SPT7863 in normal circuit operation. The following sections provide descriptions of the major functions and outline critical performance criteria to consider for achieving the optimal device performance. The general architecture for the CMOS ADC is shown in the block diagram. The design contains 16 identical successive approximation ADC sections, all operating in parallel, a 16-phase clock generator, an 11-bit 16:1 digital output multiplexer, correction logic, and a voltage reference generator that provides common reference levels for each ADC section. POWER SUPPLIES AND GROUNDING The high sample rate is achieved by using multiple SAR ADC sections in parallel, each of which samples the input signal in sequence. Each ADC uses 16 clock cycles to complete a conversion. The clock cycles are allocated as shown in table II. Fairchild suggests that both the digital and the analog supply voltages on the SPT7863 be derived from a single analog supply as shown in figure 2. A separate digital supply should be used for all interface circuitry. Fairchild suggests using this power supply configuration to prevent a possible latch-up condition on powerup. SPT7863 6 8/21/01 Table II – Clock Cycles Clock 1 2 3 4 5-15 16 Figure 3 – Ladder Force/Sense Circuit Operation Reference zero sampling Auto-zero comparison Auto-calibrate comparison Input sample 11-bit SAR conversion Data transfer AGND + VRHF VRHS The 16-phase clock, which is derived from the input clock, synchronizes these events. The timing signals for adjacent ADC sections are shifted by one clock cycle so that the analog input is sampled on every cycle of the input clock by exactly one ADC section. After 16 clock periods, the timing cycle repeats. The latency from analog input sample to the corresponding digital output is 12 clock cycles. VRLS + VRLF VIN • Since only 16 comparators are used, a huge power savings is realized. • The auto-zero operation is done using a closed loop system that uses multiple samples of the comparator’s response to a reference zero. • The auto-calibrate operation, which calibrates the gain of the MSB reference and the LSB reference, is also done with a closed loop system. Multiple samples of the gain error are integrated to produce a calibration voltage for each ADC section. • Capacitive displacement currents, which can induce sampling error, are minimized since only one comparator samples the input during a clock cycle. • The total input capacitance is very low since sections of the converter that are not sampling the signal are isolated from the input by transmission gates. All capacitors are 0.01 µF Figure 4 – Reference Ladder +4.0 V External Reference 90 mV VRHS (+3.91 V) R/2 R R R R=30 W (typ) All capacitors are 0.01 µF R VOLTAGE REFERENCE R The SPT7863 requires the use of a single external voltage reference for driving the high side of the reference ladder. It must be within the range of 3 V to 5 V. The lower side of the ladder is typically tied to AGND (0.0 V), but can be run up to 2.0 V with a second reference. The analog input voltage range will track the total voltage difference measured between the ladder sense lines, VRHS and VRLS. R VRLS (0.075 V) VRLF (AGND) 0.0 V Force and sense taps are provided to ensure accurate and stable setting of the upper and lower ladder sense line voltages across part-to-part and temperature variations. By using the configuration shown in figure 3, offset and gain errors of less than ±2 LSB can be obtained. 75 mV R/2 (chip cap preferred) to minimize high-frequency noise injection. If this simplified configuration is used, the following considerations should be taken into account. The reference ladder circuit shown in figure 4 is a simplified representation of the actual reference ladder with force and sense taps shown. Due to the actual internal structure of the ladder, the voltage drop from VRHF to VRHS is not equivalent to the voltage drop from VRLF to VRLS. In cases where wider variations in offset and gain can be tolerated, VREF can be tied directly to VRHF, and AGND can be tied directly to VRLF as shown in figure 4. Decouple force and sense lines to AGND with a .01 µF capacitor SPT7863 7 8/21/01 Typically, the top side voltage drop for VRHF to VRHS will equal: Upon powerup, the SPT7863 begins its calibration algorithm. In order to achieve the calibration accuracy required, the offset and gain adjustment step size is a fraction of a 10-bit LSB. Since the calibration algorithm is an oversampling process, a minimum of 10,000 clock cycles are required. This results in a minimum calibration time upon powerup of 250 µsec (for a 40 MHz clock). Once calibrated, the SPT7863 remains calibrated over time and temperature. VRHF – VRHS = 2.25 % of (VRHF – VRLF) (typical), and the bottom side voltage drop for VRLS to VRLF will equal: VRLS – VRLF = 1.9 % of (VRHF – VRLF) (typical). Figure 4 shows an example of expected voltage drops for a specific case. VREF of 4.0 V is applied to VRHF, and VRLF is tied to AGND. A 90 mV drop is seen at VRHS (= 3.91 V), and a 75 mV increase is seen at VRLS (= 0.075 V). Since the calibration cycles are initiated on the rising edge of the clock, the clock must be continuously applied for the SPT7863 to remain in calibration. ANALOG INPUT INPUT PROTECTION VIN is the analog input. The input voltage range is from VRLS to VRHS (typically 4.0 V) and will scale proportionally with respect to the voltage reference. (See voltage reference section.) All I/O pads are protected with an on-chip protection circuit shown in figure 6. This circuit provides ESD robustness to 3.5 kV and prevents latch-up under severe discharge conditions without degrading analog transition times. The drive requirements for the analog inputs are very minimal when compared to most other converters due to the SPT7863’s extremely low input capacitance of only 5 pF and very high input resistance in excess of 50 kΩ. Figure 6 – On-Chip Protection Circuit VDD The analog input should be protected through a series resistor and diode clamping circuit as shown in figure 5. 120 W Figure 5 – Recommended Input Protection Circuit +V Analog 120 W AVDD Pad D1 Buffer ADC 47 W D2 POWER SUPPLY SEQUENCING CONSIDERATIONS All logic inputs should be held low until power to the device has settled to the specific tolerances. Avoid power decoupling networks with large time constants that could delay VDD power to the device. V D1 = D2 = Hewlett-Packard HP5712 or equivalent CALIBRATION The SPT7863 uses an auto-calibration scheme to ensure 10-bit accuracy over time and temperature. Gain and offset errors are continually adjusted to 10-bit accuracy during device operation. This process is completely transparent to the user. SPT7863 8 8/21/01 CLOCK INPUT DIGITAL OUTPUTS The SPT7863 is driven from a single-ended TTL-input clock. Because of the aggressive design of the SPT7863, its clock duty cycle ranges from 40% to 51% (see figure 7 – DLE vs Clock Duty Cycle). Operation beyond 51% duty cycle may result in missing codes. The digital outputs (D0–D10) are driven by a separate supply (OVDD) ranging from +3 V to +5 V. This feature makes it possible to drive the SPT7863’s TTL/CMOScompatible outputs with the user’s logic system supply. The format of the output data (D0–D9) is straight binary. (See table III.) The outputs are latched on the rising edge of CLK. These outputs can be switched into a tri-state mode by bringing EN high. Figure 7 – DLE vs Clock Duty Cycle 2.0 1.8 Table III – Output Data Information 1.6 ANALOG INPUT OVERRANGE OUTPUT CODE D10 D9–D0 +F.S. + 1/2 LSB 1 11 1111 1111 +F.S. –1/2 LSB 0 1 1 1 1 1 1 1 1 1Ø +1/2 F.S. 0 ØØ ØØØØ ØØØØ +1/2 LSB 0 00 0000 000Ø 0.0 V 0 00 0000 0000 (Ø indicates the flickering bit between logic 0 and 1.) 1.4 1.2 1.0 0.8 LSB 0.6 0.4 0.2 0.0 0.2 OVERRANGE OUTPUT The OVERRANGE OUTPUT (D10) is an indication that the analog input signal has exceeded the positive fullscale input voltage by 1 LSB. When this condition occurs, D10 will switch to logic 1. All other data outputs (D0 to D9) will remain at logic 1 as long as D10 remains at logic 1. This feature makes it possible to include the SPT7863 in higher resolution systems. 0.4 0.6 0.8 1.0 1.2 38 40 42 44 46 48 50 Clock Duty Cycle (%) 52 54 56 EVALUATION BOARD Figure 8 – ILE vs Clock Duty Cycle LSB 2.8 2.4 2.0 1.6 1.2 0.8 0.4 0.0 0.4 0.8 1.2 1.6 2.0 2.4 2.8 38 The EB7863 evaluation board is available to aid designers in demonstrating the full performance of the SPT7863. This board includes a reference circuit, clock driver circuit, output data latches, and an on-board reconstruction of the digital data. An application note describing the operation of this board, as well as information on the testing of the SPT7863, is also available. Contact the factory for price and availability. 40 42 44 46 48 50 Clock Duty Cycle (%) 52 54 56 SPT7863 9 8/21/01 PACKAGE OUTLINES 28-Lead SOIC SYMBOL A B C D E F G H I 28 I H 1 INCHES MIN MAX 0.699 0.709 0.005 0.011 0.050 typ 0.018 typ 0.0077 0.0083 0.090 0.096 0.031 0.039 0.396 0.416 0.286 0.292 MILLIMETERS MIN MAX 17.75 18.01 0.13 0.28 1.27 typ 0.46 typ 0.20 0.21 2.29 2.44 0.79 0.99 10.06 10.57 7.26 7.42 INCHES MIN MAX 0.346 0.362 0.272 0.280 0.346 0.362 0.272 0.280 0.031 typ 0.012 0.016 0.053 0.057 0.002 0.006 0.037 0.041 0.007 0° 7° 0.020 0.030 MILLIMETERS MIN MAX 8.80 9.20 6.90 7.10 8.80 9.20 6.90 7.10 0.80 BSC 0.30 0.40 1.35 1.45 0.05 0.15 0.95 1.05 0.17 0° 7° 0.50 0.75 A F B C D H G E 32-Lead TQFP G H A B C SYMBOL A B C D E F G H I J K L D I J E F K L SPT7863 10 8/21/01 PIN ASSIGNMENTS AGND PIN FUNCTIONS 28 1 D10 2 27 D9 VRHS 3 26 D8 VRHF N/C VRLS 5 VRLF 6 VIN 7 AGND VCAL Analog Ground VRHF Reference High Force VRHS Reference High Sense VRLS Reference Low Sense 24 D6 VRLF Reference Low Force VCAL Calibration Reference VIN Analog Input AVDD Analog VDD DVDD Digital VDD 23 D5 SOIC Function AGND D7 25 4 Name 22 OVDD 8 21 OGND 9 20 D4 DGND Digital Ground AVDD 10 19 D3 CLK Input Clock ƒCLK = FS (TTL) DVDD 11 18 D2 17 D1 DGND 12 CLK 13 16 D0 DAV 14 15 EN D9 D8 27 26 25 28 D10 AGND 30 29 31 VRHF 32 AGND VRLS VRHS VRLF 1 24 D7 VIN 2 23 D6 AGND 3 22 D5 AGND 4 21 OVDD TQFP VCAL 5 20 OGND AVDD 6 19 D4 AVDD 7 18 D3 DVDD 8 17 D2 EN Output Enable D0–9 Tri-State Data Output, (D0=LSB) D10 Tri-State Output Overrange DAV Data Valid Output OVDD Digital Output Supply OGND Digital Output Ground N/C No Connect D1 EN 16 14 CLK DAV 15 D0 13 11 DGND DVDD DGND 12 9 10 ORDERING INFORMATION PART NUMBER TEMPERATURE RANGE PACKAGE TYPE SPT7863SCS 0 to +70 °C 28L SOIC SPT7863SCT 0 to +70 °C 32L TQFP DISCLAIMER FAIRCHILD SEMICONDUCTOR RESERVES THE RIGHT TO MAKE CHANGES WITHOUT FURTHER NOTICE TO ANY PRODUCTS HEREIN TO IMPROVE RELIABILITY, FUNCTION OR DESIGN. FAIRCHILD DOES NOT ASSUME ANY LIABILITY ARISING OUT OF THE APPLICATION OR USE OF ANY PRODUCT OR CIRCUIT DESCRIBED HEREIN; NEITHER DOES IT CONVEY ANY LICENSE UNDER ITS PATENT RIGHTS, NOR THE RIGHTS OF OTHERS. LIFE SUPPORT POLICY FAIRCHILD'S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT OF FAIRCHILD SEMICONDUCTOR CORPORATION. As used herein: 1. Life support devices or systems are devices or systems which, (a) are intended for surgical implant into the body, or (b) support or sustain life, and whose failure to perform, when properly used in accordance with instructions for use provided in the labeling, can be reasonably expected to result in a significant injury to the user. 2. A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness. www.fairchildsemi.com © Copyright 2002 Fairchild Semiconductor Corporation SPT7863 11 8/21/01