SEMTECH SX1213IWLTRT

SX1213 Receiver
Ultra-Low Power Integrated UHF Receiver
ADVANCED COMMUNICATIONS & SENSING
General Description
Features
The SX1213 is a low cost single-chip receiver
operating in the frequency ranges from 300MHz to
510MHz. The SX1213 is optimized for very low power
consumption (3mA). It incorporates a baseband
demodulator with data rates up to 200 kb/s. Data
handling features include a sixty-four byte FIFO,
packet handling, CRC and data whitening processing.
Its highly integrated architecture allows for minimum
external component count whilst maintaining design
flexibility. All major RF communication parameters are
programmable and most of them may be dynamically
set. It complies with European (ETSI EN 300-220
V2.1.1) and North American (FCC part 15.247 and
15.249) regulatory standards.
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Ordering Information
Delivery
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Table 1: Ordering Information
Part number
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Low Rx power consumption: 3mA
Good reception sensitivity: down to -104 dBm at
25 kb/s in FSK, -110 dBm at 2kb/s in OOK
Packet handling feature with data whitening and
CRC processing
RSSI (Received Signal Strength Indicator) range
from Rx noise floor to 0 dBm
Bit rates up to 200 kb/s, NRZ coding
On-chip frequency synthesizer
FSK and OOK modulation
Incoming sync word recognition
Built-in Bit-Synchronizer for incoming data and
clock synchronization and recovery
5 x 5 mm TQFN package
Optimized Circuit Configuration for Low-cost
applications
Pin to pin compatible with SX1212 Transceiver
Applications
Minimum Order
Quantity / Multiple
SX1213IWLTRT
Tape & Reel
3000 pieces
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ƒ TQFN-32 package – Operating range [-40;+85°C]
ƒ T refers to Lead Free packaging
ƒ This device is WEEE and RoHS compliant
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ƒ
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Wireless alarm and security systems
Wireless sensor networks
Automated Meter Reading
Home and building automation
Industrial monitoring and control
Remote Wireless Control
Application Circuit Schematic
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SX1213
ADVANCED COMMUNICATIONS & SENSING
Table of Contents
1. General Description ................................................................... 5
1.1. Simplified Block Diagram................................................... 5
1.2. Pin Diagram ....................................................................... 6
1.3. Pin Description................................................................... 7
2. Electrical Characteristics............................................................ 8
2.1. ESD Notice ........................................................................ 8
2.2. Absolute Maximum Ratings ............................................... 8
2.3. Operating Range ............................................................... 8
2.4. Chip Specification .............................................................. 8
2.4.1. Power Consumption .................................................. 8
2.4.2. Frequency Synthesis................................................. 9
2.4.3. Receiver .................................................................. 10
2.4.4. Digital Specification ................................................. 11
3. Architecture Description ........................................................... 12
3.1. Power Supply Strategy .................................................... 12
3.2. Frequency Synthesis Description .................................... 13
3.2.1. Reference Oscillator................................................ 13
3.2.2. CLKOUT Output ...................................................... 13
3.2.3. PLL Architecture...................................................... 14
3.2.4. PLL Tradeoffs.......................................................... 14
3.2.5. Voltage Controlled Oscillator................................... 15
3.2.6. PLL Loop Filter ........................................................ 16
3.2.7. PLL Lock Detection Indicator .................................. 16
3.2.8. Frequency Calculation ............................................ 16
3.3. Receiver Description........................................................ 18
3.3.1. Architecture ............................................................. 18
3.3.2. LNA and First Mixer ................................................ 19
3.3.3. IF Gain and Second I/Q Mixer................................. 19
3.3.4. Channel Filters ........................................................ 19
3.3.5. Channel Filters Setting in FSK Mode ...................... 20
3.3.6. Channel Filters Setting in OOK Mode ..................... 21
3.3.7. RSSI ........................................................................ 21
3.3.8. Fdev Setting in Receive Mode ................................ 23
3.3.9. FSK Demodulator.................................................... 23
3.3.10. OOK Demodulator................................................. 23
3.3.11. Bit Synchronizer .................................................... 26
3.3.12. Alternative Settings ............................................... 27
3.3.13. Data Output ........................................................... 27
4. Operating Modes...................................................................... 28
4.1. Modes of Operation ......................................................... 28
4.2. Digital Pin Configuration vs. Chip Mode .......................... 28
5. Data Processing....................................................................... 29
5.1. Overview.......................................................................... 29
5.1.1. Block Diagram ......................................................... 29
5.1.2. Data Operation Modes ............................................ 29
5.2. Control Block Description ................................................ 30
5.2.1. SPI Interface ........................................................... 30
5.2.2. FIFO ........................................................................ 32
5.2.3. Sync Word Recognition........................................... 34
5.2.4. Packet Handler........................................................ 35
5.2.5. Control..................................................................... 35
5.3. Continuous Mode ............................................................ 36
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5.3.1. General Description .................................................36
5.3.2. Rx Processing ..........................................................37
5.3.3. Interrupt Signals Mapping ........................................37
5.3.4. uC Connections........................................................38
5.3.5. Continuous Mode Example ......................................38
5.4. Buffered Mode ..................................................................39
5.4.1. General Description .................................................39
5.4.2. Rx Processing ..........................................................39
5.4.3. Interrupt Signals Mapping ........................................40
5.4.4. uC Connections........................................................41
5.4.5. Buffered Mode Example...........................................41
5.5. Packet Mode.....................................................................42
5.5.1. General Description .................................................42
5.5.2. Packet Format..........................................................42
5.5.3. Rx Processing ..........................................................44
5.5.4. Packet Filtering ........................................................44
5.5.5. DC-Free Data Mechanisms......................................46
5.5.6. Interrupt Signal Mapping ..........................................47
5.5.7. uC Connections........................................................47
5.5.8. Packet Mode Example .............................................48
5.5.9. Additional Information ..............................................48
6. Configuration and Status Registers ..........................................49
6.1. General Description..........................................................49
6.2. Main Configuration Register - MCParam..........................49
6.3. Interrupt Configuration Parameters - IRQParam ..............51
6.4. Receiver Configuration parameters - RXParam ...............53
6.5. Sync Word Parameters - SYNCParam.............................54
6.6. Oscillator Parameters - OSCParam .................................55
6.7. Packet Handling Parameters – PKTParam ......................56
7. Application Information .............................................................57
7.1. Crystal Resonator Specification .......................................57
7.2. Software for Frequency Calculation .................................57
7.2.1. GUI ...........................................................................57
7.2.2. .dll for Automatic Production Bench .........................57
7.3. Switching Times and Procedures .....................................57
7.3.1. Optimized Receive Cycle .........................................58
7.3.2. Receiver Frequency Hop Optimized Cycle ..............59
7.4. Reset of the Chip..............................................................60
7.4.1. POR .........................................................................60
7.4.2. Manual Reset ...........................................................60
7.5. Reference Design.............................................................61
7.5.1. Application Schematic..............................................61
7.5.2. PCB Layout ..............................................................61
7.5.3. Bill Of Material..........................................................62
7.5.4. Ordering Information for Tools .................................63
8. Packaging Information ..............................................................63
8.1. Package Outline Drawing .................................................63
8.2. PCB Land Pattern.............................................................64
8.3. Tape & Reel Specification ................................................64
9. Revision History ........................................................................65
10. Contact Information.................................................................65
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SX1213
ADVANCED COMMUNICATIONS & SENSING
Index of Figures
Figure 1: SX1213 Simplified Block Diagram .................................. 5
Figure 2: SX1213 Pin Diagram ...................................................... 6
Figure 3: SX1213 Detailed Block Diagram .................................. 12
Figure 4: Power Supply Breakdown............................................. 13
Figure 5: Frequency Synthesizer Description .............................. 14
Figure 6: LO Generator ................................................................ 14
Figure 7: Loop Filter ..................................................................... 16
Figure 8: Receiver Architecture ................................................... 18
Figure 9: FSK Receiver Setting ................................................... 18
Figure 10: OOK Receiver Setting ................................................ 18
Figure 11: Active Channel Filter Description................................ 19
Figure 12: Butterworth Filter's Actual BW .................................... 21
Figure 13: Polyphase Filter's Actual BW...................................... 21
Figure 14: RSSI Dynamic Range ................................................. 22
Figure 15: RSSI IRQ Timings ...................................................... 23
Figure 16: OOK Demodulator Description ................................... 24
Figure 17: Floor Threshold Optimization...................................... 25
Figure 18: BitSync Description..................................................... 26
Figure 19: SX1213’s Data Processing Conceptual View ............. 29
Figure 20: SPI Interface Overview and uC Connections ............. 30
Figure 21: Write Register Sequence ............................................ 31
Figure 22: Read Register Sequence............................................ 32
Figure 23: Read Bytes Sequence (ex: 2 bytes) ........................... 32
Figure 24: FIFO and Shift Register (SR)...................................... 33
Figure 25: FIFO Threshold IRQ Source Behavior........................ 34
Figure 26: Sync Word Recognition .............................................. 34
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Figure 27: Continuous Mode Conceptual View.............................36
Figure 28: Rx Processing in Continuous Mode.............................37
Figure 29: uC Connections in Continuous Mode ..........................38
Figure 30: Buffered Mode Conceptual View .................................39
Figure 31: Rx Processing in Buffered Mode (FIFO size=16,
Fifo_fill_method=0).............................................................40
Figure 32: uC Connections in Buffered Mode...............................41
Figure 33: Packet Mode Conceptual View....................................42
Figure 34: Fixed Length Packet Format........................................43
Figure 35: Variable Length Packet Format ...................................44
Figure 36: CRC Implementation ...................................................46
Figure 37: Manchester Decoding..................................................46
Figure 38: Data Whitening Implementation...................................47
Figure 39: uC Connections in Packet Mode .................................47
Figure 40: Optimized Rx Cycle .....................................................58
Figure 41: Rx Hop Cycle...............................................................59
Figure 42: POR Timing Diagram...................................................60
Figure 43: Manual Reset Timing Diagram ....................................60
Figure 44: Reference Design Circuit Schematic ...........................61
Figure 45: Reference Design‘s Stackup .......................................62
Figure 46: Reference Design Layout (top view)............................62
Figure 47: Package Outline Drawing ............................................63
Figure 48: PCB Land Pattern........................................................64
Figure 49: Tape & Reel Dimensions .............................................64
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SX1213
ADVANCED COMMUNICATIONS & SENSING
Index of Tables
Table 1: Ordering Information ........................................................ 1
Table 2: SX1213 Pinouts ............................................................... 7
Table 3: Absolute Maximum Ratings ............................................. 8
Table 4: Operating Range.............................................................. 8
Table 5: Power Consumption Specification ................................... 8
Table 6: Frequency Synthesizer Specification............................... 9
Table 7: Receiver Specification.................................................... 10
Table 8: Digital Specification (1) .................................................. 11
Table 9: MCParam_Freq_band and MCParam_Subband Setting
.......................................................................................... 15
Table 10: Operating Modes ......................................................... 28
Table 11: Pin Configuration vs. Chip Mode ................................. 28
Table 12: Data Operation Mode Selection................................... 30
Table 13: Config vs. Data SPI Interface Selection....................... 31
Table 14: Status of FIFO when Switching Between Different
Modes of the Chip ............................................................. 34
Table 15: Interrupt Mapping in Continuous Rx Mode .................. 37
Table 16: Relevant Configuration Registers in Continuous Mode
(data processing related only)............................................38
Table 17: Interrupt Mapping in Buffered Rx and Stby Modes .......40
Table 18: Relevant Configuration Registers in Buffered Mode (data
processing related only) .....................................................41
Table 19: Interrupt Mapping in Rx and Stby in Packet Mode........47
Table 20: Relevant Configuration Registers in Packet Mode (data
processing related only) .....................................................48
Table 21: Registers List ................................................................49
Table 22: MCParam Register Description ....................................49
Table 23: IRQParam Register Description....................................51
Table 24: RXParam Register Description .....................................53
Table 25: SYNCParam Register Description ................................54
Table 26: OSCParam Register Description ..................................55
Table 27: PKTParam Register Description ...................................56
Table 28: Crystal Resonator Specification....................................57
Table 29: Reference Design BOM ................................................62
Table 30: Tools Ordering Information ...........................................63
Acronyms
BOM
BR
BW
CCITT
CP
CRC
DAC
DDS
DLL
ERP
ETSI
FCC
Fdev
FIFO
FS
FSK
GUI
IC
ID
IF
IRQ
ITU
LFSR
LNA
Bill Of Materials
Bit Rate
Bandwidth
Comité Consultatif International
Téléphonique et Télégraphique - ITU
Charge Pump
Cyclic Redundancy Check
Digital to Analog Converter
Direct Digital Synthesis
Dynamically Linked Library
Equivalent Radiated Power
European Telecommunications Standards
Institute
Federal Communications Commission
Frequency Deviation
First In First Out
Frequency Synthesizer
Frequency Shift Keying
Graphical User Interface
Integrated Circuit
IDentificator
Intermediate Frequency
Interrupt ReQuest
International Telecommunication Union
Linear Feedback Shift Register
Low Noise Amplifier
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Rev.2 – July 1 , 2009
LO
LSB
MSB
NRZ
NZIF
OOK
PA
PCB
PFD
PLL
POR
RBW
RF
RSSI
Rx
SAW
SPI
SR
Stby
Tx
uC
VCO
XO
XOR
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Local Oscillator
Least Significant Bit
Most Significant Bit
Non Return to Zero
Near Zero Intermediate Frequency
On Off Keying
Power Amplifier
Printed Circuit Board
Phase Frequency Detector
Phase-Locked Loop
Power On Reset
Resolution BandWidth
Radio Frequency
Received Signal Strength Indicator
Receiver
Surface Acoustic Wave
Serial Peripheral Interface
Shift Register
Standby
Transmitter
Microcontroller
Voltage Controlled Oscillator
Crystal Oscillator
eXclusive OR
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SX1213
ADVANCED COMMUNICATIONS & SENSING
This product datasheet contains a detailed description of the SX1213 performance and functionality. Please consult
the Semtech website for the latest updates or errata.
1. General Description
The SX1213 is a single chip FSK and OOK receiver capable of operation in the 300 to 510 MHz license free ISM
frequency bands. It complies with both the relevant European and North American standards, EN 300-220 V2.1.1
(June 2006 release) and FCC Part 15 (10-1-2006 edition). A unique feature of this circuit is its extremely low
current consumption in full active mode of only 3mA (typ). The SX1213 is available in a 5x5 mm TQFN-32 package.
1.1. Simplified Block Diagram
Figure 1: SX1213 Simplified Block Diagram
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SX1213
ADVANCED COMMUNICATIONS & SENSING
1.2. Pin Diagram
The following diagram shows the pins arrangement of the QFN package, top view.
Figure 2: SX1213 Pin Diagram
Notes:
ƒ yyww refers to the date code
ƒ ------ refers to the lot number
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SX1213
ADVANCED COMMUNICATIONS & SENSING
1.3. Pin Description
Table 2: SX1213 Pinouts
Number
0
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
17
18
19
20
21
22
23
24
25
26
27
28
Name
GND
TEST5
TEST1
VR_VCO
VCO_M
VCO_P
LF_M
LF_P
TEST6
TEST7
XTAL_P
XTAL_M
TEST0
TEST8
NSS_CONFIG
NSS_DATA
MISO
MOSI
SCK
CLKOUT
DATA
IRQ_0
IRQ_1
PLL_LOCK
TEST2
TEST3
VDD
VR_1V
VR_DIG
Type
I
I/O
I/O
O
I/O
I/O
I/O
I/O
I/O
I/O
I/O
I/O
I
I/O
I
I
O
I
I
O
O
O
O
O
I/O
I/O
I
O
O
29
30
31
32
NC
TEST4
RFI
NC
I/O
I
-
Description
Exposed ground pad
Connect to GND
Connect to GND
Regulated supply of the VCO
VCO tank
VCO tank
PLL loop filter
PLL loop filter
Connect to GND
Connect to GND
Crystal connection
Crystal connection
Connect to GND
POR. Do not connect if unused
SPI CONFIG enable
SPI DATA enable
SPI data output
SPI data input
SPI clock input
Clock output
NRZ data output (Continuous mode)
Interrupt output
Interrupt output
PLL lock detection output
Connect to GND
Connect to GND
Supply voltage
Regulated supply of the analog circuitry
Regulated supply of digital circuitry
Connect to GND
Connect to GND
RF input
Connect to GND
Note: pin 13 (Test 8) can be used as a manual reset trigger. See section 7.4.2 for details on its use.
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SX1213
ADVANCED COMMUNICATIONS & SENSING
2. Electrical Characteristics
2.1. ESD Notice
The SX1213 is a high performance radio frequency device. It satisfies:
ƒ Class 2 of the JEDEC standard JESD22-A114-B (Human Body Model), except on pins 3-4-5-27-28-31-where it
satisfies Class 1A.
ƒ Class III of the JEDEC standard JESD22-C101C (Charged Device Model) on all pins.
It should thus be handled with all the necessary ESD precautions to avoid any permanent damage.
2.2. Absolute Maximum Ratings
Stresses above the values listed below may cause permanent device failure. Exposure to absolute maximum
ratings for extended periods may affect device reliability.
Table 3: Absolute Maximum Ratings
Symbol
VDDmr
Tmr
Pmr
Description
Supply voltage
Storage temperature
Input level
Min
-0.3
-55
-
Max
3.7
125
0
Min
2.1
-40
-
Max
3.6
+85
0
Unit
V
°C
dBm
2.3. Operating Range
Table 4: Operating Range
Symbol
VDDop
Trop
ML
Description
Supply Voltage
Temperature
Input Level
Unit
V
°C
dBm
2.4. Chip Specification
Conditions: Temp = 25 °C, VDD = 3.3 V, crystal frequency = 12.8 MHz, carrier frequency = 315 or 434 MHz,
modulation FSK, data rate = 25 kb/s, Fdev = 50 kHz, fc = 100 kHz, unless otherwise specified.
2.4.1. Power Consumption
Table 5: Power Consumption Specification
Symbol
Description
Supply current in sleep
mode
Supply current in standby
mode, CLKOUT disabled
IDDSL
IDDST
IDDFS
Supply current in FS mode
IDDR
Supply current in receiver
mode
(1)
Conditions
Min
Typ
Max
Unit
-
0.1
2
µA
Crystal oscillator running
-
65
95
µA
Frequency synthesizer
running
-
1.3
1.7
mA
-
3.0
3.5
mA
Information from design and characterization
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SX1213
ADVANCED COMMUNICATIONS & SENSING
2.4.2. Frequency Synthesis
Table 6: Frequency Synthesizer Specification
Symbol
Description
Conditions
FR
Frequency ranges
Programmable (may
require
specific BOM)
BR_F
BR_O
FDA
XTAL
Bit rate (FSK)
Bit rate (OOK)
Frequency deviation (FSK)
Crystal oscillator frequency
Frequency synthesizer
step
Oscillator wake-up time
Frequency synthesizer
wake-up time at most
10 kHz away from the
target
FSTEP
TS_OSC
TS_FS
Frequency synthesizer hop
time at most 10 kHz away
from the target
TS_HOP
((1)
Min
300
320
350
390
430
470
1.56
1.56
33
9
Typ
50
12.8
Max
330
350
390
430
470
510
200
32
200
15
Unit
MHz
MHz
MHz
MHz
MHz
MHz
Kb/s
Kb/s
kHz
MHz
-
2
-
kHz
-
1.5
5
ms
From Stby mode
-
500
800
µs
200 kHz step
1 MHz step
-
180
200
-
µs
µs
5 MHz step
-
250
-
µs
7 MHz step
-
260
-
µs
12 MHz step
-
290
-
µs
20 MHz step
-
320
-
µs
27 MHz step
-
340
-
µs
NRZ
NRZ
Variable, depending on the
frequency.
From Sleep mode(1)
Information from design and characterization
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SX1213
ADVANCED COMMUNICATIONS & SENSING
2.4.3. Receiver
On the following table, fc and fo describe the bandwidth of the active channel filters as described in section
3.3.4.2. All sensitivities are measured receiving a PN15 sequence, for a BER of 0.1.%
ƒ
Table 7: Receiver Specification
Symbol
Description
RFS_F
Conditions
434 MHz, BR=25 kb/s, Fdev
=50 kHz, fc=100 kHz
RFS_O
Sensitivity (OOK)
CCR
Co-channel rejection
Adjacent channel
rejection
ACR
BI
Blocking immunity
RXBW_F(1,2)
RXBW_O(1,2)
IIP3
(1)
TS_RE
TS_RE2(1)
Receiver bandwidth in
FSK mode
Receiver bandwidth in
OOK mode
rd
Input 3 order intercept
point
Receiver wake-up time
Receiver wake-up time
TS_RE_HOP
Receiver hop time from
Rx ready to Rx ready with
a frequency hop
TS_RSSI
DR_RSSI
RSSI sampling time
RSSI dynamic Range
(2)
Typ
Max
Unit
-
-104
-
dBm
-
-110
-
dBm
-
-12
-
dBc
-
27
-
dB
-
52
-
dB
-
57
-
dB
-
-48
-
dBm
-
-37
-
dBm
-
-33
-
dBm
50
-
250
kHz
50
-
400
kHz
-
-28
-
dBm
-
280
600
400
400
460
480
520
550
600
70
500
900
1/Fdev
-
Sensitivity (FSK)
434 MHz, 2kb/s NRZ
fc-fo=50 kHz, fo=50 kHz
(1)
Min
Modulation as wanted signal
Offset = 300 kHz, unwanted
tone is not modulated
Offset = 600 kHz, unwanted
tone is not modulated
Offset = 1.2 MHz, unwanted
tone is not modulated
Offset = 1 MHz,
unmodulated
Offset = 2 MHz,
unmodulated, no SAW
Offset = 10 MHz,
unmodulated, no SAW
Single side BW
Polyphase Off
Single side BW
Polyphase On
Interferers at 1MHz and
1.950 MHz offset
From FS to Rx ready
From Stby to Rx ready
200 kHz step
1MHz step
5MHz step
7MHz step
12MHz step
20MHz step
27MHz step
From Rx ready
Ranging from sensitivity
µs
µs
µs
µs
µs
µs
µs
µs
µs
s
dB
Information from design and characterization
This reflects the whole receiver bandwidth, as described in sections 3.3.4.1 and 3.3.4.2
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SX1213
ADVANCED COMMUNICATIONS & SENSING
2.4.4. Digital Specification
Conditions: Temp = 25 °C, VDD = 3.3 V, crystal frequency = 12.8 MHz, unless otherwise specified.
Table 8: Digital Specification (1)
Symbol
VIH
VIL
VOH
VOL
SCK_CONFIG
SCK_DATA
T_DATA
T_MOSI_C
T_MOSI_D
T_NSSC_L
T_NSSD_L
T_NSSC_H
T_NSSD_H
(1)
Description
Digital input level high
Digital input level low
Digital output level high
Digital output level low
SPI Config. clock frequency
SPI data clock frequency
DATA hold and setup time
MOSI setup time for SPI Config.
MOSI setup time for SPI Data.
NSS_CONFIG low to SCK rising edge.
SCK falling edge to NSS_CONFIG high.
NSS_DATA low to SCK rising edge.
SCK falling edge to NSS_DATA high.
NSS_CONFIG rising to falling edge.
NSS_DATA rising to falling edge.
Conditions
Imax=1mA
Imax=-1mA
Min
0.8*VDD
0.9*VDD
2
250
312
Typ
-
Max
0.2*VDD
0.1*VDD
6
1
-
Unit
V
V
V
V
MHz
MHz
µs
ns
ns
500
-
-
ns
625
-
-
ns
500
625
-
-
ns
ns
Information from design and characterization
Note: on pin 10 (XTAL_P) and 11 (XTAL_N), maximum voltages of 1.8V can be applied.
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SX1213
ADVANCED COMMUNICATIONS & SENSING
3. Architecture Description
This section describes in depth the architecture of this ultra low-power receiver:
RSSI
OOK
demod
BitSync
LNA
RFI
Control
FSK
demod
LO2 Rx
NSS_CONFIG
NSS_DATA
CLKOUT
DATA
LO1 Rx
TEST(8:0)
LO1 Rx
XTAL_P
XO
XTAL_M
IRQ_0
IRQ_1
MOSI
MISO
SCK
PLL_LOCK
I LO2 Rx
Q
Frequency Synthesizer
LO
Generator
VR_1V
VR_DIG
VCO_P
VCO_M
VR_VCO
LF_M
LF_P
Figure 3: SX1213 Detailed Block Diagram
3.1. Power Supply Strategy
To provide stable sensitivity and linearity characteristics over a wide supply range, the SX1213 is internally
regulated. This internal regulated power supply structure is described below:
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SX1213
ADVANCED COMMUNICATIONS & SENSING
1ųF
Y5V
Vbat
VDD – Pin 26
2.1 – 3.6V
External Supply
Reg_top
1.4 V
Biasing :
-SPI
-Config. Registers
-POR
Reg_dig
1.0 V
Biasing analog
blocks
Biasing digital
blocks
Biasing :
-VCO circuit
-Ext. VCO
tank
VR_VCO
Pin 3
VR_DIG
Pin 28
VR_1V
Pin 27
1ųF
Y5V
Reg_VCO
0.85 V
220nF
X7R
100nF
X7R
Figure 4: Power Supply Breakdown
To ensure correct operation of the regulator circuit, the decoupling capacitor connection shown in Figure 4 is
required. These decoupling components are recommended for any design.
3.2. Frequency Synthesis Description
The frequency synthesizer of the SX1213 is a fully integrated integer-N type PLL. The PLL circuit requires only five
external components for the PLL loop filter and the VCO tank circuit.
3.2.1. Reference Oscillator
The SX1213 embeds a crystal oscillator, which provides the reference frequency for the PLL. The recommended
crystal specification is given in section 7.1.
3.2.2. CLKOUT Output
The reference frequency, or a sub-multiple of it, can be provided on CLKOUT (pin 19) by activating the bit
OSCParam_Clkout_on. The division ratio is programmed through bits OSCParam_Clkout_freq. The two
applications of the CLKOUT output are:
ƒ To provide a clock output for a companion uC, thus saving the cost of an additional oscillator. CLKOUT can be
made available in any operation mode, except Sleep mode, and is automatically enabled at power-up.
ƒ To provide an oscillator reference output. Measurement of the CLKOUT signal enables simple software
trimming of the initial crystal tolerance.
Note: To minimize the current consumption of the SX1213, ensure that the CLKOUT signal is disabled when
unused.
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3.2.3. PLL Architecture
The crystal oscillator (XO) forms the reference oscillator of an Integer-N Phase Locked Loop (PLL), whose
operation is discussed in the following section. Figure 5 shows a block schematic of the SX1213 PLL. Here the
crystal reference frequency and the software controlled dividers R, P and S determine the output frequency of the
PLL.
÷75.(Pi+1)+Si
LO
PFD
÷(Ri+1)
XO
Vtune
Fcomp
XT_M
LF_P
XT_P
LF_M
VCO_P
VCO_M
VR_VCO
Figure 5: Frequency Synthesizer Description
The VCO tank inductors are connected on an external differential input. Similarly, the loop filter is also located
externally. However, there is an internal 8pF capacitance at VCO input that should be subtracted from the desired
loop filter capacitance.
The output signal of the VCO is used as the input to the local oscillator (LO) generator stage, illustrated in Figure 6.
The VCO frequency is subdivided and used in a series of up (down) conversions for transmission (reception).
LO1 Rx
LO
VCO Output
Receiver
LOs
I
LO2 Rx
÷8
90°
Q
Figure 6: LO Generator
3.2.4. PLL Tradeoffs
With an integer-N PLL architecture, the following criterion must be met to ensure correct operation:
ƒ The comparison frequency, Fcomp, of the Phase Frequency Detector (PFD) input must remain higher than six
times the PLL bandwidth (PLLBW) to guarantee loop stability and to reject harmonics of the comparison
frequency Fcomp. This is expressed in the inequality:
PLLBW ≤
ƒ
ƒ
Fcomp
6
However the PLLBW has to be sufficiently high to allow adequate PLL lock times
Because the divider ration R determines Fcomp, it should be set close to 119, leading to Fcomp≈100 kHz
which will ensure suitable PLL stability and speed.
With the recommended Bill Of Materials (BOM) of the reference design of section 7.5.3, the PLL prototype is the
following:
ƒ 64 ≤ R ≤ 169
ƒ S < P+1
ƒ PLLBW = 15 kHz nominal
ƒ Startup times and reference frequency spurs as specified.
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3.2.5. Voltage Controlled Oscillator
The integrated VCO requires only two external tank circuit inductors. As the input is differential, the two inductors
should have the same nominal value. The performance of these components is important for both the phase noise
and the power consumption of the PLL. It is recommended that a pair of high Q factor inductors is selected. These
should be mounted orthogonally to other inductors (in particular the LNA biasing inductor) to reduce spurious
coupling between the LNA input and VCO.
For best performance wound type inductors, with tight tolerance, should be used as described in section 7.5.3.
3.2.5.1. SW Settings of the VCO
To guarantee the optimum operation of the VCO over the SX1213’s frequency and temperature ranges, the
following settings should be programmed into the SX1213:
300MHz - 330MHz
Freq_band [MHz]
320MHz - 350MHz
39nH
L1 and L2
st
nd
33 nH
rd
th
st
nd
rd
th
Subbband
1 quarter
2
quarter
3 quarter
4 quarter
1 quarter
2
quarter
3 quarter
4 quarter
fo [MHz]
303.75MHz
311.25MHz
318.75MHz
326.25MHz
323.75MHz
331.25MHz
338.75MHz
346.25MHz
Freq_band [MHz]
350MHz - 390MHz
L1 and L2
27nH
st
nd
390MHz - 430MHz
22nH
rd
th
st
nd
rd
th
Subbband
1 quarter
2
quarter
3 quarter
4 quarter
1 quarter
2
quarter
3 quarter
4 quarter
fo [MHz]
355.00MHz
365.00MHz
375.00MHz
385.00MHz
395.00MHz
405.00MHz
415.00MHz
425.00MHz
Freq_band [MHz]
430MHz - 470MHz
L1 and L2
18nH
st
nd
470MHz - 510MHz
15nH
rd
th
st
nd
rd
th
Subbband
1 quarter
2
quarter
3 quarter
4 quarter
1 quarter
2
quarter
3 quarter
4 quarter
fo [MHz]
435.00MHz
445.00MHz
455.00MHz
465.00MHz
475.00MHz
485.00MHz
495.00MHz
505.00MHz
Table 9: MCParam_Freq_band and MCParam_Subband Setting
3.2.5.2. Trimming the VCO Tank by Hardware and Software
To ensure that the frequency band of operation may be accurately addressed by the R, P and S dividers of the
synthesizer, it is necessary to ensure that the VCO is correctly centered. Note that for the reference design (see
section 7.5) no centering is necessary. However, any deviation from the reference design may require the
optimization procedure, outlined below, to be implemented. This procedure is simplified thanks to the built-in VCO
trimming feature which is controlled over the SPI interface. This tuning does not require any RF test equipment,
and can be achieved by simply measuring Vtune, the voltage between pins 6 (LFM) and 7 (LFP).
The VCO is centered if the voltage is within the range:
50 ≤ Vtune(mV ) ≤ 150mV
If this inequality is not satisfied then adjust the Trim_band bits from 11 (default value) to 00 whilst monitoring Vtune.
This allows the VCO voltage to be trimmed by adding additional capacitance to the VCO tank. Should the desired
voltage range be inaccessible, the voltage may be adjusted further by changing the tank circuit inductance value.
Note that an increase in capacitance will result in a decrease of Vtune (approximately ~60 mV per step).
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Note for mass production: The VCO capacitance is piece to piece dependant. As such, the optimization proposed
above should be verified on several prototypes, to ensure that the population is centered on 100 mV.
3.2.6. PLL Loop Filter
To adequately reject spurious components arising from the comparison frequency Fcomp, an external 2nd order
loop filter is employed.
RL1
LF_M
CL2
CL1
LF_P
Figure 7: Loop Filter
Following the recommendations made in section 3.2.4, the loop filter proposed in the reference design’s bill of
material on section 7.5.3 should be used. The loop filter settings are frequency band independent and are hence
relevant to all implementations of the SX1213.
3.2.7. PLL Lock Detection Indicator
The SX1213 also features a PLL lock detect indicator. This is useful for optimizing power consumption, by adjusting
the synthesizer wake up time (TS_FS), since the PLL startup time is lower than specified under nominal conditions.
The lock status can be read on bit IRQParam_PLL_lock, and must be cleared by writing a “1” to this same register.
In addition, the lock status can be reflected in pin 23 PLL_LOCK, by setting the bit IRQParam_Enable_lock_detect.
3.2.8. Frequency Calculation
As shown in Figure 5 the PLL structure comprises three different dividers, R, P and S, which set the output
frequency through the LO. A second set of dividers is also available to allow rapid switching between a pair of
frequencies: R1/P1/S1 and R2/P2/S2. These six dividers are programmed by six bytes of the register MCParam
from addresses 6 to 11.
3.2.8.1. FSK Mode
The following formula gives the relationship between the local oscillator, and R, P and S values, when using FSK
modulation.
9
Flo
8
9 Fxtal
[75(P + 1) + S )]
Frf , fsk =
8 R +1
Frf , fsk =
3.2.8.2. OOK Mode
Due to the low intermediate frequency (Low-IF) architecture of the SX1213 the frequency should be configured so
as to ensure the correct low-IF receiver baseband center frequency, IF2.
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9
Flo − IF 2
8
9 Fxtal
[75(P + 1) + S )] − IF 2
Frf , ook =
8 R +1
Frf , ook =
Note that from Section 3.3.4, it is recommended that IF2 be set to 100 kHz.
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3.3. Receiver Description
The SX1213 is set to receive mode when MCParam_Chip_mode = 011.
Second downconversion
First downconversion
RSSI
OOK
demod
Bit
synchronizer
FSK
demod
LO2 Rx
LNA
Control logic
-Pattern recognition
-FIFO handler
-SPI interface
-Packet handler
LO1 Rx
Baseband, IF2 in OOK
IF1
RF
Figure 8: Receiver Architecture
3.3.1. Architecture
The SX1213 receiver employs a super-heterodyne architecture. Here, the first IF is 1/9th of the RF frequency
(approximately 100MHz). The second down-conversion down-converts the I and Q signals to base band in the
case of the FSK receiver (Zero IF) and to a low-IF (IF2) for the OOK receiver.
Second
down-conversion
LO2
Rx
First
down-conversion
0
IF1
≈100MHz
IF2=0
in FSK
mode
Image
frequency
LO1 Rx
Channel
Image
frequency
LO1 Rx
Channel
Frequencyl
Figure 9: FSK Receiver Setting
First
down-conversion
Second
down-conversion
0
IF2<0
in FSK
mode
equal to fo
IF1
≈100MHz
LO2 Rx
Frequency
Figure 10: OOK Receiver Setting
After the second down-conversion stage, the received signal is channel-select filtered and amplified to a level
adequate for demodulation. Both FSK and OOK demodulation are available. Finally, an optional Bit Synchronizer
(BitSync) is provided, to be supply a synchronous clock and data stream to a companion uC in Continuous mode,
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or to fill the FIFO buffers with glitch-free data in Buffered mode. The operation of the receiver is now described in
detail.
Note: Image rejection is achieved by the SAW filter.
3.3.2. LNA and First Mixer
The performance of this amplifier is such that the Noise Figure (NF) of the receiver can be estimated to be ≈7 dB.
3.3.3. IF Gain and Second I/Q Mixer
Following the LNA and first down-conversion, there is an IF amplifier whose gain can be programmed from 13.5 dB to 0 dB in 4.5 dB steps, via the register MCParam_IF_gain. The default setting corresponds to 0 dB gain,
but lower values can be used to increase the RSSI dynamic range. Refer to section 3.3.7 for additional information.
3.3.4. Channel Filters
The second mixer stages are followed by the channel select filters. The channel select filters have a strong
influence on the noise bandwidth and selectivity of the receiver and hence its sensitivity. Each filter comprises a
passive and active section.
3.3.4.1. Passive Filter
Each channel select filter features a passive second-order RC filter, with a bandwidth programmable through the
bits RXParam_PassiveFilt. As the wider of the two filters, its effect on the sensitivity is negligible, but its bandwidth
has to be setup instead to optimize blocking immunity. The value entered into this register sets the single side
bandwidth of this filter. For optimum performance it should be set to 3 to 4 times the cutoff frequency of the active
Butterworth (or polyphase) filter described in the next section.
3 * Fc ButterfFilt ≤ BW passive, filter ≤ 4 * Fc ButterFilt
3.3.4.2. Active Filter
The ’fine’ channel selection is performed by an active, third-order, Butterworth filter, which acts as a low-pass filter
for the zero-IF configuration (FSK), or a complex polyphase filter for the Low-IF (OOK) configuration. The
RXParam_PolypFilt_on bit enables/disables the polyphase filter.
Low-pass filter for FSK ( RXParam_PolyFilt_on=’’0’’)
-fC
0
fC
frequency
Polyphase filter for OOK ( RXParam_PolyFilt_on=’’1’’ )
Canceled side of
the polyphase filter
-fC
-fo
0
frequency
Figure 11: Active Channel Filter Description
As can be seen from Figure 11, the required bandwidth of this filter varies between the two demodulation modes.
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ƒ
FSK mode: The 99% energy bandwidth of an FSK modulated signal is approximated to be:
BR ⎤
⎡
BW99%, FSK = 2 * ⎢ Fdev +
2 ⎥⎦
⎣
The bits RXParam_ButterFilt set fc, the cutoff frequency of the filter. As we are in a Zero-IF configuration, the FSK
lobes are centered around the virtual “DC” frequency. The choice of fc should be such that the modulated signal
falls in the filter bandwidth, anticipating the Local Oscillator frequency drift over the operating temperature and
aging of the device:
2 * fc > BW99%,FSK + LOdrifts
Please refer to the charts in section 3.3.5 for an accurate overview of the filter bandwidth vs. setting.
ƒ
OOK mode: The 99% energy bandwidth of an OOK modulated signal is approximated to be:
BW99%,OOK =
2
= 2.BR
Tbit
The bits RXParam_PolypFilt_center set fo, the center frequency of the polyphase filter when activated. fo should
always be chosen to be equal to the low Intermediate Frequency of the receiver (IF2). This is why, in the GUI
described in section 7.2.1 of this document, the low IF frequency of the OOK receiver denoted IF2 has been
replaced by fo.
The following setting is recommended:
fo = 100kHz
RXParam _ PolypFilt ="0011"
The value stored in RXParam_ButterFilt determines fc, the filter cut-off frequency. So the user should set fc
according to:
2 * ( fc − fo ) > BW 99%,OOK + LO drifts
Again, fc as a function of RXParam_ButterFilt is given in the section 3.3.6.
3.3.5. Channel Filters Setting in FSK Mode
Fc, the 3dB cutoff frequency of the Butterworth filter used in FSK reception, is programmed through the bit
RXParam_ButterFilt. However, the whole receiver chain influences this cutoff frequency. Thus the channel select
and resultant filter bandwidths are summarized in the following chart:
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Actual
BW
Butterworth Filter's BW, FSK
Theoretical
BW
450
400
Fc (3dB Cutoff) [kHz]
350
300
250
200
150
100
50
0
0
2
4
6
8
10
12
14
16
Val (RXParam_ButterFilt) [d]
Figure 12: Butterworth Filter's Actual BW
Error! Reference source not found. suggests filter settings in FSK mode, along with the corresponding passive
filter bandwidth and the accepted tolerance on the crystal reference.
3.3.6. Channel Filters Setting in OOK Mode
The center frequency, fo, is always set to 100kHz. The following chart shows the receiver bandwidth when
changing RXParam_Butterfilt bits, whilst the polyphase filter is activated.
Actual
BW
Polyphase Filter's BW, OOK
Theoretical
BW
450
400
Fc-Fo with Fo=100 kHz [kHz]
350
300
250
200
150
100
50
0
0
2
4
6
8
10
Val (RXParam_ButterFilt [d]
RXParam_PolypFilt="0011"
12
14
16
Figure 13: Polyphase Filter's Actual BW
Error! Reference source not found. suggests a few filter settings in OOK mode, along with the corresponding
passive filter bandwidth and the accepted tolerance on the crystal reference.
3.3.7. RSSI
After filtering, the In-phase and Quadrature signals are amplified by a chain of 11 amplifiers, each with 6dB gain.
The outputs of these amplifiers are used to evaluate the Received Signal Strength (RSSI).
3.3.7.1. Resolution and Accuracy
Whilst the RSSI resolution is 0.5 dB, the absolute accuracy is not expected to be better than +/- 3dB due to process
and external component variation. Higher accuracy whilst performing absolute RSSI measurements will require
additional calibration.
3.3.7.2. Acquisition Time
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In OOK mode, the RSSI evaluates the signal strength by sampling I(t) and Q(t) signals 16 times in each period of
the chosen IF2 frequency (refer to section 3.3.1). In FSK mode, the signals are sampled 16 times in each Fdev
period, Fdev being the frequency deviation of the companion transmitter. An average is then performed over a
sliding window of 16 samples. Hence, the RSSI output register RXParam_RSSI is updated 16 times in each Fdev
or IF2 period.
The following settings should be respected:
ƒ FSK Mode: Ensure that the Fdev parameter (as described in MCParam_Fdev) remains consistent with the
actual frequency deviation of the companion transmitter.
ƒ OOK reception: Ensure that the Fdev parameter (as described in MCParam_Fdev) is equal with the frequency
of I(t) and Q(t) signals, i.e. the second Intermediate Frequency, IF2, of the receiver (Note that this equals Fo,
the center frequency of the polyphase filter).
3.3.7.3. Dynamic Range
The dynamic range of the RSSI is over 70 dB, extending from the nominal sensitivity level. The IF gain setting
available in MCParam_IF_gain is used to achieve this dynamic range:
RSSI Response
180
160
140
RSSI_Val [0.5dB/bit]
120
100
80
60
40
20
0
-120
-100
-80
-60
-40
-20
0
Pin [dBm]
IF_Gain=00
IF_Gain=01
IF_Gain=10
IF_Gain=11
Figure 14: RSSI Dynamic Range
The RSSI response versus input signal is independent of the receiver filter bandwidth. However in the absence of
any input signal, the minimum value directly reflects upon the noise floor of the receiver, which is dependant on the
filter bandwidth of the receiver.
3.3.7.4. RSSI IRQ Source
The SX1213 can also be used to detect a RSSI level above a pre-configured threshold. The threshold is set in
IRQParam_RSSI_irq_thresh and the IRQ status stored in IRQParam_RSSI_irq (cleared by writing a “1”).
An interrupt can be mapped to the IRQ0 or IRQ1 pins via bits IRQParam_Rx_stby_irq0 or
IRQParam_Rx_stby_irq1. Figure 15 shows the timing diagram of the RSSI interrupt source, with
IRQParam_RSSI_irq_thresh set to 28.
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RXParam_RSSI_val(7:0)
24 26 27 30 25 20 20 20 18 22 33 20 22 34 33
IRQParam_RSSI_irq
Clear interrupt
Figure 15: RSSI IRQ Timings
3.3.8. Fdev Setting in Receive Mode
The effect of the Fdev setting is different between FSK and OOK modes:
3.3.8.1. FSK Rx Mode
In FSK mode the Fdev setting, as configured by MCParam_Freq_Dev, sets sampling frequencies on the receiver.
The user should make it consistent with the frequency deviation of the FSK signal that is received.
3.3.8.2. OOK Rx Mode
The frequency deviation Fdev, as described above, sets the sampling rate of the RSSI block. It is therefore
necessary to set Fdev to the recommended low-IF frequency, IF2, of 100 kHz:
Fdev = IF 2 = 100kHz
MCParam _ Freq _ dev ="00000011"
3.3.9. FSK Demodulator
The FSK demodulator provides data polarity information, based on the relative phase of the input I and Q signals at
the baseband. Its outputs can be fed to the Bit Synchronizer to recover the timing information. The user can also
use the raw, unsynchronized, output of the FSK demodulator in Continuous mode.
The FSK demodulator of the SX1213 operates most effectively for FSK signals with a modulation index greater
than or equal to two:
β=
2 * Fdev
≥2
BR
3.3.10. OOK Demodulator
The OOK demodulator performs a comparison of the RSSI output and a threshold value. Three different threshold
modes are available, programmed through the RXParam_OOK_thresh_type register.
The recommended mode of operation is the “Peak” threshold mode, illustrated below in Figure 16:
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RSSI
(dB)
‘’Peak -6dB’’ Threshold
‘’Floor’’ threshold defined by
MCParam_OOK_floor_thresh
Noise floor of
receiver
Time
Zoom
Decay in dB as defined in
RXPAram_OOK_thresh_step
Fixed 6dB difference
Period as defined in
RXParam_OOK_thresh_dec_period
Figure 16: OOK Demodulator Description
In peak threshold mode the comparison threshold level is the peak value of the RSSI, reduced by 6dB. In the
absence of an input signal or during the reception of a logical “0”, the acquired peak value is decremented by one
RXPAram_OOK_thresh_step every RXParam_OOK_thresh_dec_period.
When the RSSI output is null for a long time (for instance after a long string of “0” received, or if no transmitter is
present), the peak threshold level will continue falling until it reaches the “Floor Threshold” that is programmed
through the register MCParam_OOK_floor_thresh.
The default settings of the OOK demodulator lead to the performance stated in the electrical specification.
However, in applications in which sudden signal drops are awaited during a reception, the three parameters shall
be optimized accordingly.
3.3.10.1. Optimizing the Floor Threshold
MCParam_OOK_floor_thres determines the sensitivity of the OOK receiver, as it sets the comparison threshold for
weak input signals (i.e. those close to the noise floor). Significant sensitivity improvements can be generated if
configured correctly.
Note that the noise floor of the receiver at the demodulator input depends on:
ƒ The noise figure of the receiver.
ƒ The gain of the receive chain from antenna to base band.
ƒ The matching - including SAW filter.
ƒ The bandwidth of the channel filters.
It is therefore important to note that the setting of MCParam_OOK_floor_thresh will be application dependant. The
following procedure is recommended to optimize MCParam_OOK_floor_thresh.
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Set SX1210 in OOK Rx mode
Adjust Bit Rate, Channel filter BW
Default RXParam_OOK_thresh setting
No input signal
Continuous Mode
Monitor DATA pin (pin 20)
Increment
MCParam_OOK_floor_thres
Glitch activity
on DATA ?
Optimization complete
Figure 17: Floor Threshold Optimization
The new floor threshold value found during this test should be the value used for OOK reception with those receiver
settings.
Note that if the output signal on DATA is logic “1”, the value of MCParam_OOK_floor_thres is below the noise floor
of the receiver chain. Conversely, if the output signal on DATA is logic “1”, the value of MAParam_floor_thres is
several dB above the noise floor.
3.3.10.2. Optimizing OOK Demodulator Response for Fast Fading Signals
A sudden drop in signal strength can cause the bit error rate to increase. For applications where the expected
signal drop can be estimated the following OOK demodulator parameters RXParam_OOK_thresh_step and
RXParam_OOK_thresh_dec_period can be optimized as described below for a given number of threshold
decrements per bit RXParam_OOK_thresh_dec_period:
ƒ 000 Æ once in each chip period (d)
ƒ 001 Æ once in 2 chip periods
ƒ 010 Æ once in 4 chip periods
ƒ 011 Æ once in 8 chip periods
ƒ 100 Æ twice in each chip period
ƒ 101 Æ 4 times in each chip period
ƒ 110 Æ 8 times in each chip period
ƒ 111 Æ 16 times in each chip period
For each decrement of RXParam_OOK_thresh_step:
ƒ 000 Æ 0.5 dB (d)
ƒ 001 Æ 1.0 dB
ƒ 010 Æ 1.5 dB
ƒ 011 Æ 2.0 dB
ƒ 100 Æ 3.0 dB
ƒ 101 Æ 4.0 dB
ƒ 110 Æ 5.0 dB
ƒ 111 Æ 6.0 dB
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3.3.10.3. Alternative OOK Demodulator Threshold Modes
In addition to the Peak OOK threshold mode, the user can alternatively select two other types of threshold
detectors:
ƒ Fixed threshold: The value is selected through the MCParam_OOK_floor_thresh register (refer to section
3.3.10.1 for further information concerning optimization of the floor threshold).
ƒ Average threshold: Data supplied by the RSSI block is averaged with the following cutoff frequency:
RXParam _ OOK _ cutoff = 00 ⇒ Fcutoff =
RXParam _ OOK _ cutoff = 11 ⇒ Fcutoff =
BR
8 *π
BR
32 * π
In the first example, the higher cut-off frequency enables a sequence of up to 8 consecutive “0” or “1” to be
supported, whilst the lower cut-off frequency presented in the second example allows for the correct reception of up
to 32 consecutive “0” or “1”.
3.3.11. Bit Synchronizer
The Bit Synchronizer (BitSync) is a block that provides a clean and synchronized digital output, free of glitches.
Raw demodulator
output
(FSK or OOK)
DATA
BitSync Output
To pin DATA and
DCLK in continuous
mode
DCLK
IRQ_1
Figure 18: BitSync Description
The BitSync can be disabled through the bits RXParam_Bitsync_off, and by holding pin IRQ1 low. However, for
optimum receiver performance, its use when running Continuous mode is strongly advised. With this option a
DCLK signal is present on pin IRQ_1.
The BitSync is automatically activated in Buffered and Packet modes. The bit synchronizer bit-rate is controlled by
MCParam_BR. For a given bit rate, this parameter is determined by:
BR =
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For proper operation, the Bit Synchronizer must first receive three bytes of alternating logic value preamble, i.e.
“0101” sequences. After this startup phase, the rising edge of DCLK signal is centered on the demodulated bit.
Subsequent data transitions will preserve this centering.
This has two implications:
ƒ Firstly, if the Bit Rates of Transmitter and Receiver are known to be the same, the SX1213 will be able to
receive an infinite unbalanced sequence (all “0s” or all ”1s”) with no restriction.
ƒ If there is a difference in Bit Rate between Tx and Rx, the amount of adjacent bits at the same level that the
BitSync can withstand can be estimated as:
NumberOfBits =
1 BR
*
2 ΔBR
This implies approximately 6 consecutive unbalanced bytes when the Bit Rate precision is 1%, which is easily
achievable (crystal tolerance is in the range of 50 to 100 ppm).
3.3.12. Alternative Settings
Bit Synchronizer and Active channel filter settings are a function of the reference oscillator crystal frequency, FXTAL.
Settings other than those programmable with a 12.8 MHz crystal can be obtained by selection of the correct
reference oscillator frequency. Please contact your local Semtech representative for further details.
3.3.13. Data Output
After OOK or FSK demodulation, the baseband signal is made available to the user on pin 20, DATA, when
Continuous mode is selected.
In Buffered and Packet modes, the data is retrieved from the FIFO through the SPI interface.
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4. Operating Modes
This section summarizes the settings for each operating mode of the SX1213, and explains the functionality
available and the timing requirements for switching between modes.
4.1. Modes of Operation
Table 10: Operating Modes
Mode
Sleep
Standby
MCParam_Chip_mode
000
001
FS
Receive
Active blocks
SPI, POR
SPI, POR, Top regulator, digital regulator, XO, CLKOUT (if activated through
OSCParam_Clkout)
Same + VCO regulator, all PLL and LO generation blocks
Same as FS mode + LNA, first mixer, IF amplifier, second mixer set, channel
filters, baseband amplifiers and limiters, RSSI, OOK or FSK demodulator,
BitSync and all digital features if enabled
010
011
4.2. Digital Pin Configuration vs. Chip Mode
Table 11 describes the state of the digital IOs in each of the above described modes of operation, regardless of the
data operating mode.
Table 11: Pin Configuration vs. Chip Mode
Chip
……….Mode
Sleep
mode
Standby
mode
FS mode
Receive
mode
Comment
NSS_CONFIG
Input
Input
Input
Input
NSS_CONFIG has the priority over
NSS_DATA
NSS_DATA
Input
Input
Input
Input
MISO
Input
Input
Input
Input
MOSI
SCK
IRQ_0
IRQ_1
DATA (3)
CLKOUT
Input
Input
High-Z
High-Z
High-Z
High-Z
Input
Input
Output (1)
Output (1)
High-Z
Output
Input
Input
Output (1)
Output (1)
High-Z
Output
PLL_LOCK
High-Z
Output (4)
Output (4)
Input
Input
Output
Output
Output
Output
Output
(4)
Pin
Output only if NSS_CONFIG or
NSSDATA=’0’
Notes:
(1): High-Z if Continuous mode is activated, else Output
(2): Valid logic states must be applied to inputs at all times to avoid unwanted leakage currents
(3): Tie to Vss (or Vdd) when not in active receive mode.
(4): Output if PLL_lock_en = 1, else High-Z
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5. Data Processing
5.1. Overview
5.1.1. Block Diagram
Figure 19, illustrates the SX1213 data processing circuit. Its role is to interface the data from the demodulator and
the uC access points (SPI, IRQ and DATA pins). It also controls all the configuration registers.
The circuit contains several control blocks which are described in the following paragraphs.
SX1213
Rx
DATA
IRQ_0
CONTROL
Rx
Data
IRQ_1
SPI
SYNC
RECOG.
PACKET
HANDLER
FIFO
(+SR)
Tx
CONFIG
DATA
NSS_DATA
SCK
MOSI
MISO
Figure 19: SX1213’s Data Processing Conceptual View
The SX1213 implements several data operation modes, each with their own data path through the data processing
section. Depending on the data operation mode selected, some control blocks are active whilst others remain
disabled.
5.1.2. Data Operation Modes
The SX1213 has three different data operation modes selectable by the user:
ƒ Continuous mode: each bit received is accessed in real time at the DATA pin. This mode may be used if
adequate external signal processing is available.
ƒ Buffered mode: each byte received is stored in a FIFO and accessed via the SPI bus. uC processing overhead
is hence significantly reduced compared to Continuous mode operation. The packet length is unlimited.
ƒ Packet mode (recommended): user only retrieves payload bytes to/from the FIFO. Sync word is automatically
detected and stripped off while optional CRC check and DC free data decoding can be performed. The uC
processing overhead is hence reduced further compared to Buffered mode. The maximum payload length is
limited to the maximum FIFO limit of 64 bytes
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Table 12: Data Operation Mode Selection
MCParam_Data_mode
00
01
1x
Data Operation Mode
Continuous
Buffered
Packet
Each of these data operation modes is described fully in the following sections.
5.2. Control Block Description
5.2.1. SPI Interface
5.2.1.1. Overview
As illustrated in the Figure 20 below, the SX1213’s SPI interface consists of two sub blocks:
ƒ
ƒ
SPI Config: used in all data operation modes to read and write the configuration registers which control all the
parameters of the chip (operating mode, bit rate, etc...)
SPI Data: used in Buffered and Packet mode to read data bytes from the FIFO. (FIFO interrupts can be used to
manage the FIFO content.)
SX1213
Config.
Registers
SPI
CONFIG
(slave)
NSS_CONFIG
MOSI
MISO
SCK
NSS_CONFIG
MOSI
MISO
SCK
NSS_DATA
µC
FIFO
SPI
DATA
(slave)
(master)
NSS_DATA
Figure 20: SPI Interface Overview and uC Connections
Both interfaces are configured in slave mode whilst the uC is configured as the master. They have separate
selection pins (NSS_CONFIG and NSS_DATA) but share the remaining pins:
ƒ SCK (SPI Clock): clock signal provided by the uC
ƒ MOSI (Master Out Slave In): data input signal provided by the uC
ƒ MISO (Master In Slave Out): data output signal provided by the SX1213
As described below, only one interface can be selected at a time with NSS_CONFIG having the priority:
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Table 13: Config vs. Data SPI Interface Selection
NSS_DATA
0
0
1
1
NSS_CONFIG
0
1
0
1
SPI Interface
Config
Data
Config
None
The following paragraphs describe how to use each of these interfaces.
5.2.1.2. SPI Config
ƒ Write Register
To write a value into a configuration register the timing diagram below should be carefully followed by the uC.
The register’s new value is effective from the rising edge of NSS_CONFIG.
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
NSS_CONFIG (In)
SCK (In)
New value at
address A1
MOSI (In)
start
rw
A(4) A(3) A(2) A(1) A(0) stop D(7) D(6) D(5) D(4) D(3) D(2) D(1) D(0)
Current value at
address A1*
Address = A1
MISO (Out)
HZ
x
x
x
x
x
x
x
x
D(7) D(6) D(5) D(4) D(3) D(2) D(1)
D(0)
HZ
* when writing the new value at address A1, the current content of A1 can be read by the uC.
(In)/(Out) refers to SX1210 side
Figure 21: Write Register Sequence
Note that when writing more than one register successively, it is not compulsory to toggle NSS_CONFIG back high
between two write sequences. The bytes are alternatively considered as address and value. In this instance, all
new values will become effective on rising edge of NSS_CONFIG.
ƒ Read Register
To read the value of a configuration register the timing diagram below should be carefully followed by the uC.
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1
2
start
rw
3
4
5
6
7
8
9
10
11
12
13
14
15
16
x
x
x
x
x
x
x
x
NSS_CONFIG (In)
SCK (In)
MOSI (In)
A(4) A(3) A(2) A(1) A(0) stop
Current value at
address A1
Address = A1
MISO (Out)
HZ
x
x
x
x
x
x
x
D(7) D(6) D(5) D(4) D(3) D(2) D(1)
x
HZ
D(0)
Figure 22: Read Register Sequence
Note that when reading more than one register successively, it is not compulsory to toggle NSS_CONFIG back
high between two read sequences. The bytes are alternatively considered as address and value.
5.2.1.3. SPI Data
To read bytes from the FIFO the timing diagram below should be carefully followed by the uC.
1
2
3
4
5
6
7
8
x
x
x
x
x
1
2
3
x
x
x
4
5
6
7
8
x
x
x
x
NSS_DATA (In)
SCK (In)
x
MOSI (In)
x
x
x
2nd byte read
st
1 byte read
MISO (Out) HZ
D1(7)
D1(6) D1(5)
D1(4) D1(3)
x
D1(2) D1(1) D1(0)
HZ
D2(7) D2(6)
D2(5)
D2(4)
D2(3)
D2(2)
D2(1)
D2(0)
HZ
Figure 23: Read Bytes Sequence (ex: 2 bytes)
Note that it is compulsory to toggle NSS_DATA back high between each byte read.
5.2.2. FIFO
5.2.2.1. Overview and Shift Register (SR)
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In Buffered and Packet modes of operation, data that have been received are stored in a configurable FIFO (First
In First Out) device. It is accessed via the SPI Data interface and provides several interrupts for transfer
management.
The FIFO is 1 byte (8 bits) wide hence it only performs byte (parallel) operations, whereas the demodulator
functions serially. A shift register is therefore employed to interface the two devices. In Rx the shift register gets bit
by bit data from the demodulator and writes them byte by byte to the FIFO. This is illustrated in figure below.
FIFO
byte1
byte0
8
Data Rx
SR (8bits)
1
MSB
LSB
Figure 24: FIFO and Shift Register (SR)
5.2.2.2. Size Selection
The FIFO width is programmable, to 16, 32, 48 or 64 bytes via MCParam_Fifo_size
5.2.2.3. Interrupt Sources and Flags
All interrupt sources and flags are configured in the IRQParam section of the configuration register, with the
exception of Fifo_threshold :
ƒ /Fifoempty: /Fifoempty interrupt source is low when byte 0, i.e. whole FIFO, is empty. Otherwise it is high. Note
that when retrieving data from the FIFO, /Fifoempty is updated on NSS_DATA falling edge, i.e. when
/Fifoempty is updated to low state the currently started read operation must be completed. In other words,
/Fifoempty state must be checked after each read operation for a decision on the next one (/Fifoempty = 1:
more byte(s) to read; /Fifoempty = 0: no more byte to read).
ƒ Write_byte: Write_byte interrupt source goes high for 1 bit period each time a new byte is transferred from the
SR to the FIFO (i.e. each time a new byte is received)
ƒ Fifofull: Fifofull interrupt source is high when the last FIFO byte, i.e. the whole FIFO, is full. Otherwise it is low.
ƒ Fifo_overrun_clr: Fifo_overrun_clr flag is set when a new byte is written by the SR while the FIFO is already
full. Data is lost and the flag should be cleared by writing a 1, note that the FIFO will also be cleared.
ƒ Fifo_threshold: Fifo_threshold interrupt source’s behavior can be programmed via MCParam_Fifo_thresh (B
value). This behavior is illustrated in Figure 25.
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IRQ source
1
0
B
B+1
# of bytes in FIFO
Rx & Stby
Figure 25: FIFO Threshold IRQ Source Behavior
5.2.2.4. FIFO Clearing
Table 14 below summarizes the status of the FIFO when switching between different modes
Table 14: Status of FIFO when Switching Between Different Modes of the Chip
From
Stby
Rx
Any
To
Rx
Stby
Sleep
FIFO Status
Cleared
Not cleared
Cleared
Comments
In Packet & Buffered modes FIFO can be read in Stby after Rx
5.2.3. Sync Word Recognition
5.2.3.1. Overview
Sync word recognition (also called Pattern recognition in previous products) is activated by setting
RXParam_Sync_on. The bit synchronizer must also be activated.
The block behaves like a shift register; it continuously compares the incoming data with its internally programmed
Sync word and asserts the Sync IRQ source on each occasion that a match is detected. This is illustrated in Figure
26.
Rx DATA
Bit N-x =
(NRZ)
Sync_value[x]
Bit N-1 =
Bit N =
Sync_value[1] Sync_value[0]
DCLK
SYNC
Figure 26: Sync Word Recognition
During the comparison of the demodulated data, the first bit received is compared with bit 7 (MSB) of byte at
address 22 and the last bit received is compared with bit 0 (LSB) of the last byte whose address is determined by
the length of the Sync word.
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When the programmed Sync word is detected the user can assume that this incoming packet is for the node and
can be processed accordingly.
5.2.3.2. Configuration
ƒ
ƒ
ƒ
Size: Sync word size can be set to 8, 16, 24 or 32 bits via RXParam_Sync_size.
Error tolerance: The number of errors tolerated in the Sync word recognition can be set to 0, 1, 2 or 3 via
RXParam_Sync_tol.
Value: The Sync word value is configured in SYNCParam_Sync_value.
5.2.4. Packet Handler
The packet handler is the block used in Packet mode. Its functionality is fully described in section 5.5.
5.2.5. Control
The control block configures and controls the full chip’s behavior according to the settings programmed in the
configuration registers.
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5.3. Continuous Mode
5.3.1. General Description
As illustrated in Figure 27, in Continuous mode the NRZ data from the demodulator is directly accessed by the uC
on the DATA pin (20). The SPI Data, FIFO and packet handler are thus inactive.
SX1213
Rx
DATA
IRQ_0
IRQ_1(DCLK)
CONTROL
Data
Rx
SPI
SYNC
RECOG.
NSS_CONFIG
CONFIG
SCK
MOSI
MISO
Datapath
Figure 27: Continuous Mode Conceptual View
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5.3.2. Rx Processing
If the bit synchronizer is disabled, the raw demodulator output is made directly available on DATA pin and no DCLK
signal is provided.
Conversely, if the bit synchronizer is enabled, synchronous cleaned data and clock are made available respectively
on DATA and IRQ_1 pins. DATA is sampled on the rising edge of DCLK and updated on the falling edge as
illustrated in Figure 28.
DATA (NRZ)
DCLK
Figure 28: Rx Processing in Continuous Mode
Note that in Continuous mode it is always recommended to enable the bit synchronizer to clean the DATA signal
even if the DCLK signal is not used by the uC. (bit synchronizer is automatically enabled in Buffered and Packet
mode).
5.3.3. Interrupt Signals Mapping
The tables below give the description of the interrupts available in Continuous mode.
IRQ_0
Rx_stby_irq_0
00 (d)
01
1x
IRQ_1
Rx
Sync
RSSI
DCLK
Table 15: Interrupt Mapping in Continuous Rx Mode
Note: In Continuous mode, no interrupt is available in Stby mode
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5.3.4. uC Connections
SX1213
DATA
IRQ_0
IRQ_1 (DCLK)
NSS_CONFIG
uC
SCK
MOSI
MISO
Figure 29: uC Connections in Continuous Mode
Note that some connections may not be needed depending on the application:
ƒ IRQ_0: if Sync and RSSI interrupts are not used. In this case, leave floating.
ƒ IRQ_1: DCLK connection is not compulsory. In this case, leave floating.
ƒ MISO: if no read register access is needed. In this case, pull-up to VDD through a 100 kΩ resistor.
In addition, NSS_DATA pin (unused in continuous mode) should be pulled-up to VDD through a 100 kΩ resistor.
Please refer to Table 11 for SX1213’s pins configuration
5.3.5. Continuous Mode Example
ƒ
Configure all data processing related registers listed below appropriately. In this example we assume that both
Bit synchronizer and Sync word recognition are on.
Table 16: Relevant Configuration Registers in Continuous Mode (data processing related only)
Description
MCParam
IRQParam
RXParam
SYNCParam
ƒ
ƒ
ƒ
ƒ
ƒ
Data_mode_x
Rx_stby_irq_0
Sync_on
Sync_size
Sync_tol
Sync_value
Defines data operation mode (Æ Continuous)
Defines IRQ_0 source in Rx mode
Enables Sync word recognition
Defines Sync word size
Defines the error tolerance on Sync word recognition
Defines Sync word value
Program Rx interrupts: IRQ_0 mapped to Sync (Rx_stby_irq_0=”00”) and IRQ_1 mapped to DCLK (Bit
synchronizer enabled)
Go to Rx mode (note that Rx is not ready immediately, see Figure 40)
Wait for Sync interrupt
Get all packet bits on DATA pin synchronously with DCLK signal provided on IRQ_1
Go to Sleep mode
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5.4. Buffered Mode
5.4.1. General Description
As illustrated in Figure 30, for Buffered mode operation the NRZ data from the demodulator is not directly accessed
by the uC but stored in the FIFO and accessed via the SPI Data interface. This frees the uC for other tasks
between processing data from the SX1213, furthermore it simplifies software development and reduces uC
performance requirements (speed, reactivity). Note that in this mode the packet handler stays inactive.
An important feature is also the ability to empty the FIFO in Stby mode, ensuring low power consumption and
adding greater software flexibility.
SX1213
IRQ_0
CONTROL
IRQ_1
Rx
Data
SPI
SYNC
RECOG.
NSS_CONFIG
CONFIG
FIFO
(+SR)
DATA
NSS_DATA
SCK
MOSI
MISO
Datapath
Figure 30: Buffered Mode Conceptual View
Note that Bit Synchronizer is automatically enabled in Buffered mode. The Sync word recognition must be enabled
(RXParam_Sync_on=1) independently of the FIFO filling method selected (IRQParam_Fifo_fill_method).
5.4.2. Rx Processing
After entering Rx in Buffered mode, the chip requires the uC to retrieve the received data from the FIFO. The FIFO
will actually start being filled with received bytes either; when a Sync word has been detected (in this case only the
bytes following the Sync word are filled into the FIFO) or when the Fifo_fill bit is asserted by the user - depending
on the state of bit, IRQParam_Fifo_fill_method.
In Buffered mode, the packet length is not limited i.e. as long as Fifo_fill is set, the received bytes are shifted into
the FIFO.
The uC software must therefore manage the transfer of the FIFO contents by interrupt and ensure reception of the
correct number of bytes. (In this mode, even if the remote transmitter has stopped, the demodulator will output
random bits from noise)
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When the FIFO is full, Fifofull IRQ source is asserted to alert the uC, that at that time, the FIFO can still be unfilled
without data loss. If the FIFO is not unfilled, once the SR is also full (i.e. 8 bits periods later) Fifo_overrun_clr is
asserted and SR’s content is lost.
Figure 31 illustrates an Rx processing with a 16 bytes FIFO size and Fifo_fill_method=0. Please note that in the
illustrative example of section 5.4.5, the uC does not retrieve any byte from the FIFO through SPI Data, causing
overrun.
Data Rx
(to SR) “noisy” data
Preamble
Sync
b0
b1
b2
b3
b4
b5
b6
b7
b8
b9
b10
b11 b12 b13 b14 b15 b16
Start condition
(Cf. Fifo_fill_method)
/Fifoempty
Fifofull
Fifo_overrun_clr
Write_byte
15
FIFO
0
b0
b1
b2
b3
b4
b5
b6
b7
b8
b9
b10
b11
b12
b13
b14
b15
Figure 31: Rx Processing in Buffered Mode (FIFO size=16, Fifo_fill_method=0)
5.4.3. Interrupt Signals Mapping
The tables below describe the interrupts available in Buffered mode.
IRQ_0
IRQ_1
Rx_stby_irq_x
00 (d)
01
10
11
00 (d)
01
10
11
Rx
Write_byte
/Fifoempty
Sync
Fifofull
RSSI
Fifo_threshold
Stby
/Fifoempty
Fifofull
Fifo_threshold
Table 17: Interrupt Mapping in Buffered Rx and Stby Modes
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5.4.4. uC Connections
SX1213
IRQ_0
IRQ_1
uC
NSS_CONFIG
NSS_DATA
SCK
MOSI
MISO
Figure 32: uC Connections in Buffered Mode
Note that depending upon the application, some uC connections may not be needed:
ƒ IRQ_0: if none of the relevant IRQ sources are used. In this case, leave floating.
ƒ IRQ_1: if none of the relevant IRQ sources are used. In this case, leave floating.
In addition, DATA pin (unused in buffered mode) should be pulled-up to VDD through a 100 kΩ resistor.
Please refer to Table 11 for the SX1213’s pin configuration.
5.4.5. Buffered Mode Example
ƒ
Configure all data processing related registers listed below appropriately. In this example we assume Sync
word recognition is on and Fifo_fill_method=0.
Description
MCParam
IRQParam
RXParam
SYNCParam
Data_mode_x
Fifo_size
Fifo_thresh
Rx_stby_irq_0
Rx_stby_irq_1
Fifo_fill_method
Fifo_fill
Sync_size
Sync_tol
Sync_value
Defines data operation mode (ÆBuffered)
Defines FIFO size
Defines FIFO threshold
Defines IRQ_0 source in Rx & Stby modes
Defines IRQ_1 source in Rx & Stby modes
Defines FIFO filling method
Controls FIFO filling status
Defines Sync word size
Defines the error tolerance on Sync word detection
Defines Sync word value
Table 18: Relevant Configuration Registers in Buffered Mode (data processing related only)
ƒ
ƒ
ƒ
ƒ
ƒ
ƒ
Program Rx/Stby interrupts: IRQ_0 mapped to /Fifoempty (Rx_stby_irq_0=10) and IRQ_1 mapped to
Fifo_threshold (Rx_stby_irq_1=01). Configure Fifo_thresh to an appropriate value (ex: to detect packet end if
its length is known)
Go to Rx mode (note that Rx is not ready immediately, Cf section 7.3.1).
Wait for Fifo_threshold interrupt (i.e. Sync word has been detected and FIFO filled up to the defined threshold).
If it is packet end, go to Stby (SR’s content is lost).
Read packet bytes from FIFO until /Fifoempty goes low (or correct number of bytes is read).
Go to Sleep mode.
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5.5. Packet Mode
5.5.1. General Description
Similar to Buffered mode operation, in Packet mode the NRZ data from the demodulator is not directly accessed by
the uC but stored in the FIFO and accessed via the SPI Data interface.
In addition, the SX1213’s packet handler performs several packet oriented tasks such as Preamble and Sync word
extraction, CRC check, dewhitening of data, address filtering, etc. This simplifies still further software and reduces
uC overhead by performing these repetitive tasks within the RF chip itself.
Another important feature is ability to empty the FIFO in Stby mode, ensuring optimum power consumption and
adding more flexibility for the software.
SX1213
IRQ_0
CONTROL
IRQ_1
Data
Rx
SPI
SYNC
RECOG.
NSS_CONFIG
PACKET
HANDLER
FIFO
(+SR)
CONFIG
DATA
NSS_DATA
SCK
MOSI
MISO
Datapath
Figure 33: Packet Mode Conceptual View
Note that Bit Synchronizer and Sync word recognition are automatically enabled in Packet mode.
5.5.2. Packet Format
Two types of packet formats are supported: fixed length and variable length, selectable by the
PKTParam_Pkt_format bit. The maximum size of the payload is limited by the size of the FIFO selected (16, 32, 48
or 64 bytes).
5.5.2.1. Fixed Length Packet Format
In applications where the packet length is fixed in advance, this mode of operation may be of interest to minimize
RF overhead (no length byte field is required). All nodes should be programmed with the same packet length value.
The length of the payload is set by the PKTParam_Payload_length register and is limited by the size of the FIFO
selected.
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The length stored in this register relates only to the payload which includes the message and the optional address
byte. In this mode, the payload must contain at least one byte, i.e. address or message byte.
An illustration of a fixed length packet is shown in Figure 34. It contains the following fields:
ƒ Preamble (1010...).
ƒ Sync word (Network ID).
ƒ Optional Address byte (Node ID).
ƒ Message data.
ƒ Optional 2-bytes CRC checksum.
Optional DC free data decoding
CRC checksum calculation
Preamble
1 to 4 bytes
Sync Word
1 to 4 bytes
Address
byte
Message
0 to (FIFO size) bytes
CRC
2-bytes
Payload/FIFO
Fields processed and removed by the packet handler
Optional User provided fields which are part of the payload
Message part of the payload
Figure 34: Fixed Length Packet Format
5.5.2.2. Variable Length Packet Format
This mode is necessary in applications where the length of the packet is not known in advance and can vary over
time. It is then necessary for the transmitter to send the length information together with each packet in order for
the receiver to operate properly.
In this mode the length of the payload, indicated by the length byte in Figure 35, is given by the first byte of the
FIFO and is limited only by the size (width of 8bits) of the FIFO selected. Note that the length byte itself is not
included in its calculation. In this mode, the payload must contain at least 2 bytes, i.e. length + address or message
byte.
An illustration of a variable length packet is shown in Figure 35. It contains the following fields:
ƒ Preamble (1010...).
ƒ Sync word (Network ID).
ƒ Length byte
ƒ Optional Address byte (Node ID).
ƒ Message data.
ƒ Optional 2-bytes CRC checksum.
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Optional DC free data decoding
CRC checksum calculation
Preamble
1 to 4 bytes
Sync Word
1 to 4 bytes
Length
byte
Address
byte
Message
0 to (FIFO size - 1) bytes
CRC
2-bytes
Payload/FIFO
Fields processed and removed by the packet handler
Optional User provided fields which are part of the payload
Message part of the payload
Figure 35: Variable Length Packet Format
5.5.3. Rx Processing
In Rx mode the packet handler extracts the user payload to the FIFO by performing the following operations:
ƒ Receiving the preamble and stripping it off.
ƒ Detecting the Sync word and stripping it off.
ƒ Optional DC-free decoding of data.
ƒ Optionally checking the address byte.
ƒ Optionally checking CRC and reflecting the result on CRC_status bit and CRC_OK IRQ source.
Only the payload (including optional address and length fields) is made available in the FIFO.
Payload_ready and CRC_OK interrupts (the latter only if CRC is enabled) can be generated to indicate the end of
the packet reception.
By default, if the CRC check is enabled and fails for the current packet, then the FIFO is automatically cleared and
neither of the two interrupts are generated and new packet reception is started. This autoclear function can be
disabled via PKTParam_CRC_autoclr bit and, in this case, even if CRC fails, the FIFO is not cleared and only
Payload_ready IRQ source is asserted.
Once fully received, the payload can also be fully or partially retrieved in Stby mode via
PKTParam_Fifo_stby_access. At the end of the reception, although the FIFO automatically stops being filled, it is
still up to the user to explicitly exit Rx mode if required. (e.g. go to Stby to get payload). FIFO must be empty for a
new packet reception to start.
5.5.4. Packet Filtering
SX1213’s packet handler offers several mechanisms for packet filtering ensuring that only useful packets are made
available to the uC, reducing significantly system power consumption and software complexity.
5.5.4.1. Sync Word Based
Sync word filtering/recognition is automatically enabled in Packet mode. It is used for identifying the start of the
payload and also for network identification. As previously described, the Sync word recognition block is configured
(size, error tolerance, value) via RXParam_Sync_size, RXParam_Sync_tol and SYNCParam configuration
registers. This information is used to filter packets in Rx.
Every received packet which does not start with this locally configured Sync word is automatically discarded and no
interrupt is generated.
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When the Sync word is detected, payload reception automatically starts and Sync IRQ source is asserted.
5.5.4.2. Address Based
Address filtering can be enabled via the PKTParam_Adrs_filt bits. It adds another level of filtering, above Sync
word, typically useful in a multi-node networks where a network ID is shared between all nodes (Sync word) and
each node has its own ID (address).
Three address based filtering options are available:
ƒ Adrs_filt = 01: Received address field is compared with internal register Node_Adrs. If they match then the
packet is accepted and processed, otherwise it is discarded.
ƒ Adrs_filt = 10: Received address field is compared with internal register Node_Adrs and the constant 0x00. If
either is a match, the received packet is accepted and processed, otherwise it is discarded. This additional
check with a constant is useful for implementing broadcast in a multi-node networks.
ƒ Adrs_filt = 11: Received address field is compared with internal register Node_Adrs and the constants 0x00 &
0xFF. If any of the three matches, then the received packet is accepted and processed, otherwise it is
discarded. These additional checks with constants are useful for implementing broadcast commands of all
nodes.
Please note that the received address byte, as part of the payload, is not stripped off the packet and is made
available in the FIFO.
5.5.4.3. Length Based
In variable length Packet mode, PKTParam_Payload_length must be programmed with the maximum length
permitted. If received length byte is smaller than this maximum then the packet is accepted and processed,
otherwise it is discarded.
Please note that the received length byte, as part of the payload, is not stripped off the packet and is made
available in the FIFO.
To disable this function the user should set the value of the PKTParam_Payload_length to the value of the FIFO
size selected.
5.5.4.4. CRC Based
The CRC check is enabled by setting bit PKTParam_CRC_on. It is used for checking the integrity of the message.
ƒ On your Tx side a two byte CRC checksum should be calculated on the payload part of the packet and
appended to the end of the message.
ƒ On SX1213 (Rx side) the checksum is calculated on the received payload and compared with the two
checksum bytes received. The result of the comparison is stored in the PKTParam_CRC_status bit and
CRC_OK IRQ source.
By default, if the CRC check fails then the FIFO is automatically cleared and no interrupt is generated. This filtering
function can be disabled via PKTParam_CRC_autoclr bit and in this case, even if CRC fails, the FIFO is not
cleared and only Payload_ready interrupt goes high. Please note that in both cases, the two CRC checksum bytes
are stripped off by the packet handler and only the payload is made available in the FIFO.
The CRC is based on the CCITT polynomial as shown in Figure 36. This implementation also detects errors due to
leading and trailing zeros.
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data input
X15
CRC Polynomial =X16 + X12 + X5 + 1
X14
X13
X12
X11
X5
***
X4
X0
***
Figure 36: CRC Implementation
5.5.5. DC-Free Data Mechanisms
Two techniques are supported by the SX1213 packet handler: Manchester decoding and data whitening. Please
note that only one of the two methods should be enabled at a time.
5.5.5.1. Manchester Decoding
Manchester decoding is enabled by setting bit PKTParam_Manchester_on and can only be used in Packet mode.
The NRZ data to Manchester codes ‘1’ as “10” and ‘0’ as “01”.
In this case, the maximum chip rate is the maximum bit rate given in the specifications section and the actual bit
rate is half the chip rate.
Manchester decoding is only applied to the payload and CRC checksum while preamble and Sync word are kept
NRZ. However, the chip rate from preamble to CRC is the same and defined by MCParam_BR (Chip Rate = Bit
Rate NRZ = 2 x Bit Rate Manchester).
Manchester decoding is thus made transparent for the user, who still retrieves NRZ data from the FIFO.
1/BR ...Sync
RF chips @ BR
User/NRZ bits
Manchester OFF
User/NRZ bits
Manchester ON
1/BR
...
1
1
1
0
1
0
0
1
0
0
1
Payload...
0
1
1
0
1
0
...
...
1
1
1
0
1
0
0
1
0
0
1
0
0
1
0
...
...
1
1
1
0
1
0
0
1
0
1
0
1
1
1
t
...
Figure 37: Manchester Decoding
5.5.5.2. Data Dewhitening
Another technique called whitening or scrambling is widely used for randomizing the user data before radio
transmission. The data is whitened using a random sequence on the Tx side and de-whitened on the SX1213 (Rx
side) using the same sequence. Comparing to Manchester technique it has the advantage of keeping NRZ datarate
i.e. actual bit rate is not halved.
SX1213 supported whitening algorithm is given in Figure 38. This figure provides you with the random sequence to
be X-ORed with the actual payload.
The de-whitening process is enabled by setting bit PKTParam_Whitening_on. The data is de-whitened by the
SX1213 receiver side by XORing with the same random sequence as the Tx.
Payload de-whitening is thus made transparent for the user, who still retrieves NRZ data from the FIFO.
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L F S R P o ly n o m ia l = X 9 + X 5 + 1
X8
X7
X6
X5
X4
X3
X2
X1
X0
W h ite n e d d a ta
T ra n sm it d a ta
Figure 38: Data Whitening Implementation
5.5.6. Interrupt Signal Mapping
Tables below give the description of the interrupts available in Packet mode.
Table 19: Interrupt Mapping in Rx and Stby in Packet Mode
IRQ_0
IRQ_1
Rx_stby_irq_x
00 (d)
01
10
11
00 (d)
01
10
11
Rx
Payload_ready
Write_byte
/Fifoempty
Sync or Adrs_match*
CRC_OK
Fifofull
RSSI
Fifo_threshold
Stby
/Fifoempty
Fifofull
Fifo_threshold
*The latter if Address filtering is enabled
5.5.7. uC Connections
SX1213
IRQ_0
IRQ_1
NSS_CONFIG
NSS_DATA
SCK
MOSI
MISO
uC
Figure 39: uC Connections in Packet Mode
Note that depending upon the application, some uC connections may not be needed:
ƒ IRQ_0: if none of the relevant IRQ sources are used. In this case, leave floating.
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ƒ IRQ_1: if none of the relevant IRQ sources are used. In this case, leave floating.
In addition, DATA pin (unused in packet mode) should be pulled-up to VDD through a 100 kΩ resistor.
Please refer to Table 11 for the SX1213’s pin configuration.
5.5.8. Packet Mode Example
ƒ
Configure all data processing related registers listed below appropriately. In this example we assume CRC is
enabled with autoclear on.
Table 20: Relevant Configuration Registers in Packet Mode (data processing related only)
Description
MCParam
IRQParam
RXParam
SYNCParam
PKTParam
Data_mode_x
Fifo_size
Fifo_thresh
Rx_stby_irq_0
Rx_stby_irq_1
Sync_size
Sync_tol
Sync_value
Manchester_on
Payload_length
Node_adrs
Pkt_format
Whitening_on
CRC_on
Adrs_filt
CRC_autoclr
Defines data operation mode (ÆPacket)
Defines FIFO size
Defines FIFO threshold
Defines IRQ_0 source in Rx & Stby modes
Defines IRQ_1 source in Rx & Stby modes
Defines Sync word size
Defines the error tolerance on Sync word detection
Defines Sync word value
Enables Manchester decoding
Length in fixed format, max length in variable format
Defines node address for address filtering
Defines packet format (fixed or variable length)
Enables de-whitening process
Enables CRC calculation/check
Enables and defines address filtering
Enables FIFO autoclear if CRC failed
Rx Mode:
ƒ Program Rx/Stby interrupts: IRQ_0 mapped to /Fifoempty (Rx_stby_irq_0=10) and IRQ_1 mapped to CRC_OK
(Rx_stby_irq_1=00)
ƒ Go to Rx (note that Rx is not ready immediately, see section 7.3.1
ƒ Wait for CRC_OK interrupt
ƒ Go to Stby
ƒ Read payload bytes from FIFO until /Fifoempty goes low.
ƒ Go to Sleep mode
5.5.9. Additional Information
It is not possible to receive multiple packets. Once a packet has been received and filled into the FIFO all its
content needs to be read i.e. the FIFO must be empty for a new packet reception to be initiated.
The Payload_ready interrupt goes high when the last payload byte is available in the FIFO and remains high until
all its data are read. Similar behavior is applicable to Adrs_match and CRC_OK interrupts.
The CRC result is available in the CRC_status bit as soon as the CRC_successful and Payload_ready interrupt
sources are triggered. In Rx mode, CRC_status is cleared when the complete payload has been read from the
FIFO. If the payload is read in Stby mode, then CRC_status is cleared when the user goes back to Rx mode and a
new Sync word is detected.
The Fifo_fill_method and Fifo_fill bits don’t have any meaning in the Packet mode and should be set to their default
values only.
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6. Configuration and Status Registers
6.1. General Description
Table 21 sums-up the control and status registers of the SX1213:
Table 21: Registers List
Name
MCParam
IRQParam
RXParam
SYNCParam
Reserved
OSCParam
PKTParam
Size
12 x 8
4x8
6x8
4x8
1x8
1x8
4x8
Address
0 - 11
12 - 15
16 - 21
22 – 25
26
27
28 - 31
Description
Main parameters
Interrupt registers
Receiver parameters
Pattern
Do not change default value : “01111110”
Crystal oscillator parameters
Packet handler parameters
6.2. Main Configuration Register - MCParam
The detailed description of the MCParam register is given in Table 22.
Table 22: MCParam Register Description
Name
Bits
Address
(d)
RW
Chip_mode
7-5
0
r/w
Freq_band
4-2
0
r/w
Subbband
1-0
0
r/w
Data_mode
7-6
1
r/w
FSK_OOK_ctrl
5-4
1
r/w
OOK_thresh_type
3-2
1
r/w
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Description
Transceiver mode:
000 Æ sleep mode - Sleep
001 Æ stand-by mode - Stby (d)
010 Æ frequency synthesizer mode - FS
011 Æ receive mode - Rx
Frequency band:
000 Æ 300-330 MHz
001 Æ 320-350 MHz
010 Æ 350-390 MHz
011 Æ 390-430 MHz
100 Æ 430-470 MHz (d)
101 Æ 470-510 MHz
Frequency Sub-band:
00 -> 1st quarter of the selected band (d)
01 -> 2nd quarter of the selected band
10 -> 3rd quarter of the selected band
11 -> 4th quarter of the selected band
Data operation mode:
00 -> continuous mode (d)
01 -> buffered mode
1X -> packet handling mode
RxTx modulation scheme:
00 -> Reset
01 -> OOK
10 -> FSK (d)
11 -> Direct mode of transmitter (internal). Reserved (external)
OOK demodulator threshold type:
00 Æ fixed threshold mode
01 Æ peak mode (d)
10 Æ average mode
11 Æ reserved
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IF_gain
1-0
1
r/w
Freq_dev
7-0
2
r/w
Gain on the IF chain:
00 Æ maximal gain (0dB) (d)
01 Æ -4.5 dB
10 Æ -9dB
11 Æ -13.5 dB
Single side frequency deviation in FSK Transmit mode:
Refer to sections Error! Reference source not found. and Error! Reference
source not found.
Fdev =
f XTAL
, 0 ≤ D ≤ 255, where D is the value in the register.
32 ⋅ (D + 1)
(d): D = “00000011” => Fdev = 100 kHz
C coefficient of the bit rate
BR_C
7-0
3
r/w
Bit Rate =
f XTAL
, 0 ≤ C ≤ 255, where C is the value in the register.
2 ⋅ (C + 1).(D + 1)
(d): C = “0000111” => Bit Rate = 25 kb/s NRZ
D coefficient of the bit rate
BR_D
7-0
4
r/w
Res
7-6
5
r/w
Low_power_rx
5
5
r/w
Trim_band
2-1
5
r/w
RF_frequency
0
5
r/w
R1
7-0
6
r/w
P1
7-0
7
r/w
S1
7-0
8
r/w
R2
7-0
9
r/w
P2
7-0
10
r/w
S2
7-0
11
r/w
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Rev.2 – July 1 , 2009
Bit Rate =
f XTAL
, 15 ≤ D ≤ 255, where D is the value in the register.
2 ⋅ (C + 1).(D + 1)
(d): D = “0001111” => Bit Rate = 25 kb/s NRZ
Reserved
(d): “0”
Enables the low power mode of the receiver by reducing the bias current
of the LNA.
0 -> Low power mode disabled (d)
1 -> Low power mode enabled
VCO trimming:
00 -> Add VCO trimming capacitor of weight 3
01 -> Add VCO trimming capacitor of weight 2
10 -> Add VCO trimming capacitor of weight 1
11 -> No additional VCO trimming capacitor (d)
Selection between the two RF frequencies defined by the
SynthRi, SynthPi, and SynthSi registers:
0 -> frequency 1 for R1,P1,S1 (d)
1 -> frequency 2 for R2,P2,S2
R counter, active when RPS_select=”0”
(d):6Bh; default values of R1, P1, S1 generate 434.0 MHz in FSK mode
P counter, active when RPS_select=”0”
(d): 2Ah; default values of R1, P1, S1 generate 434.0 MHz in FSK mode
S counter, active when RPS_select=”0”
(d): 1Eh; default values of R1, P1, S1 generate 434.0 MHz in FSK mode
R counter, active when RPS_select=”1”
(d): 77h; default values of R2, P2, S2 generate 435.0 MHz in FSK mode
P counter, active when RPS_select=”1”
(d): 2Fh; default values of R2, P2, S2 generate 435.0 MHz in FSK mode
S counter, active when RPS_select=”1”
(d): 19h; default values of R2, P2, S2 generate 435.0 MHz in FSK mode
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6.3. Interrupt Configuration Parameters - IRQParam
The detailed description of the IRQParam register is given in Table 23.
Table 23: IRQParam Register Description
Name
Bits
Fifo_size
Fifo_thresh
Rx_stby_irq_0
Address
(d)
RW
7-6
12
r/w
5-0
12
r/w
7-6
13
r/w
Description
Configures the size of the FIFO:
00 -> 16 bytes (d)
01 -> 32 bytes
10 -> 48 bytes
11 -> 64 bytes
Number of bytes to be written in the FIFO to activate the
Fifo_threshold interrupts
Actual number of bytes = B + 1, where B is the value in the register.
(d): B = 001111 => Number of bytes = 16
IRQ_0 source in Rx and Standby modes:
If Data_mode(1:0) = 00 (Continuous mode):
00 Æ Sync (d)
01 Æ RSSI
10 Æ Sync
11 Æ Sync
If Data_mode(1:0) = 01 (Buffered mode):
00 Æ - (d)
01 Æ Write_byte
10 Æ /Fifoempty*
11 Æ Sync
If Data_mode(1:0) = 1x (Packet mode):
00 Æ Payload_ready (d)
01 Æ Write_byte
10 Æ /Fifoempty*
11 Æ Sync or Adrs_match (the latter if address filtering is enabled)
*also available in Standby mode (Cf sections 5.4.3 and 5.5.6)
IRQ_1 source in Rx and Standby modes:
r/w
If Data_mode(1:0) = 00 (Continuous mode):
xx Æ DCLK
If Data_mode(1:0) = 01 (Buffered mode):
00 Æ - (d)
01 Æ Fifofull*
10 Æ RSSI
11 Æ Fifo_threshold*
If Data_mode(1:0) = 1x (Packet mode):
00 Æ CRC_ok (d)
01 Æ Fifofull*
10 Æ RSSI
11 Æ Fifo_threshold*
13
r
13
r
*also available in Standby mode (Cf sections 5.4.3 and 5.5.6)
Reserved default 0d
Fifofull IRQ source
Goes high when FIFO is full.
/Fifoempty IRQ source
Goes low when FIFO is empty
Rx_stby_irq_1
5-4
13
Res
3-2
13
Fifofull
1
/Fifoempty
0
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Fifo_overrun_clr
0
13
r/w/
c
Fifo_fill_method
7
14
r/w
Goes high when an overrun error occurred. Writing a 1 clears flag and FIFO
FIFO filling method (Buffered mode only):
0 Æ Automatically starts when a sync word is detected (d)
1 Æ Manually controlled by Fifo_fill
FIFO filling status/control (Buffered mode only):
ƒ
Fifo_fill
6
Fifo_fill_method
7
14
14
r/w/
c
r/w
ƒ
6
14
r/w/
c
Res
5
14
Fifo_overrun_clr
4
13
Res
3
14
r/w
RSSI_irq
2
14
r/w/
c
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r
r/w/
c
If Fifo_fill_method = ‘1’:
0 Æ Stop filling the FIFO
1 Æ Start filling the FIFO
FIFO filling method (Buffered mode only):
0 Æ Automatically starts when a sync word is detected (d)
1 Æ Manually controlled by Fifo_fill
FIFO filling status/control (Buffered mode only):
ƒ
Fifo_fill
If Fifo_fill_method = ‘0’: (d)
Goes high when FIFO is being filled (sync word has been detected)
Writing ‘1’ clears the bit and waits for a new sync word (if Fifo_overrun_clr=0)
If Fifo_fill_method = ‘0’: (d)
Goes high when FIFO is being filled (sync word has been detected)
Writing ‘1’ clears the bit and waits for a new sync word (if Fifo_overrun_clr=0)
ƒ
If Fifo_fill_method = ‘1’:
0 Æ Stop filling the FIFO
1 Æ Start filling the FIFO
reserved
Goes high when an overrun error occurred.
Writing a 1 anytime clears flag (if set) and launches a new Rx or Tx process
(d): “0”, should be set to “1”.
Note: “0” disables the RSSI IRQ source. It can be left enabled at any time, and
the user can choose to map this interrupt to IRQ0/IRQ1 or not.
RSSI IRQ source:
Goes high when a signal above RSSI_irq_thresh is detected
Writing ‘1’ clears the bit
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6.4. Receiver Configuration parameters - RXParam
The detailed description of the RXParam register is given in Table 24.
Table 24: RXParam Register Description
Name
Bits
Address (d)
RW
PassiveFilt
7-4
16
r/w
ButterFilt
3-0
16
r/w
Description
Typical single sideband bandwidth of the passive low-pass filter.
PassiveFilt = 0000 Æ 65 kHz
0001 Æ 82 kHz
0010 Æ 109 kHz
0011 Æ 137 kHz
0100 Æ 157 kHz
0101 Æ 184 kHz
0110 Æ 211 kHz
0111 Æ 234 kHz
1000 Æ 262 kHz
1001 Æ 321 kHz
1010 Æ 378 kHz (d)
1011 Æ 414 kHz
1100 Æ 458 kHz
1101 Æ 514 kHz
1110 Æ 676 kHz
1111 Æ 987 kHz
Sets the receiver bandwidth. For BW information please refer to
sections 3.3.5 (FSK) and 3.3.6 (OOK).
f c = f 0 + 200kHz.
f xtal MHz 1 + Val ( ButterFilt )
.
12.8MHz
8
(d): “0011” => fC = 200 kHz
Central frequency of the polyphase filter (100kHz recommended):
PolypFilt_center
7-4
17
r/w
Res
3-0
17
r/w
PolypFilt_on
7
18
r/w
Bitsync_off
6
18
r/w
Sync_on
5
18
r/w
Sync_size
4-3
18
r/w
Sync_tol
2-1
18
r/w
Res
0
18
r/w
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f 0 = 200kHz.
Fxtal MHz 1 + Val ( PolypFilt _ center )
.
12.8MHz
8
(d):“0011” => f0 = 100 kHz
Reserved
(d): “1000”
Enable of the polyphase filter, in OOK Rx mode:
0 Æ off (d)
1 Æ on
Bit synchronizer: control in Continuous Rx mode:
0 Æ on (d)
1 Æ off
Sync word recognition:
0 Æ off (d)
1 Æ on
Sync word size:
00 Æ 8 bits
01 Æ 16 bits
10 Æ 24 bits
11 Æ 32 bits (d)
Number of errors tolerated in the Sync word recognition:
00 Æ 0 error (d)
01 Æ 1 error
10 Æ 2 errors
11 Æ 3 errors
Reserved
(d):”0”
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Name
Bits
Address (d)
RW
Res
7-0
19
r/w
RSSI_val
7-0
20
r
OOK_thresh_step
7-5
21
r/w
OOK_thresh_dec
_period
4-2
21
r/w
OOK_avg_thresh
_cutoff
1-0
21
r/w
Description
Reserved
(d): “00000111”
RSSI output, 0.5 dB / bit
Note: READ-ONLY (not to be written)
Size of each decrement of the RSSI threshold in the OOK demodulator
000 Æ 0.5 dB (d)
100 Æ 3.0 dB
001 Æ 1.0 dB
101 Æ 4.0 dB
010 Æ 1.5 dB
110 Æ 5.0 dB
011 Æ 2.0 dB
111 Æ 6.0 dB
Period of decrement of the RSSI threshold in the OOK demodulator:
000 Æ once in each chip period (d)
001 Æ once in 2 chip periods
010 Æ once in 4 chip periods
011 Æ once in 8 chip periods
100 Æ twice in each chip period
101 Æ 4 times in each chip period
110 Æ 8 times in each chip period
111 Æ 16 times in each chip period
Cutoff frequency of the averaging for the average mode of the OOK
threshold in demodulator
00 Æ fC ≈ BR / 8.π (d)
01 Æ Reserved
10 Æ Reserved
11 Æ fC ≈ BR / 32.π
6.5. Sync Word Parameters - SYNCParam
The detailed description of the SYNCParam register is given in Table 25.
Table 25: SYNCParam Register Description
Name
Sync_value(31:24)
Bits
7-0
Address (d)
22
Sync_value(23:16)
7-0
23
Sync_value(15:8)
7-0
24
Sync_value(7:0)
7-0
25
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RW
r/w
Description
1st Byte of Sync word
(d): “00000000”
2nd Byte of Sync word (only used if Sync_size ≠ 00)
(d): “00000000”
3rd Byte of Sync word (only used if Sync_size = 1x)
(d): “00000000”
4th Byte of Sync word (only used if Sync_size = 11)
(d): “00000000”
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ADVANCED COMMUNICATIONS & SENSING
6.6. Oscillator Parameters - OSCParam
The detailed description of the OSCParam register is given in Table 26.
Table 26: OSCParam Register Description
Name
Bits
RW
Description
7
Address
(d)
27
Clkout_on
r/w
6-2
27
r/w
Clkout control
0 Æ Disabled
1 Æ Enabled, Clk frequency set by Clkout_freq (d)
Frequency of the signal provided on CLKOUT:
fclkout = f xtal if Clkout_freq = “00000”
Clkout_freq
fclkout =
Res
1-0
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27
r/w
f xtal
otherwise
2 ⋅ Clkout _ freq
(d): 01111 (= 427 kHz)
Reserved
(d): “00”
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ADVANCED COMMUNICATIONS & SENSING
6.7. Packet Handling Parameters – PKTParam
The detailed description of the PKTParam register is given in Table 27.
Table 27: PKTParam Register Description
Name
Bits
RW
Description
7
Address
(d)
28
Manchester_on
r/w
Payload_length
6-0
28
r/w
Node_adrs
7-0
29
r/w
Pkt_format
7
30
r/w
Res
Whitening_on
6-5
4
30
30
r/w
r/w
CRC_on
3
30
r/w
Adrs_filt
2-1
30
r/w
CRC_status
0
30
r
CRC_autoclr
7
31
r/w
Res
6-0
31
r/w
Enable Manchester decoding:
0 Æ off (d)
1 Æ on
If Pkt_format=0, payload length.
If Pkt_format=1, max length
(d): “0000000”
Node’s local address for filtering of received packets.
(d): 00h
Packet format:
0 Æ fixed length (d)
1 Æ variable length
(d) : “10”
Dewhitening process:
0 Æ off (d)
1 Æ on
CRC calculation/check:
0 Æ off
1 Æ on (d)
Address filtering of received packets:
00 Æ off (d)
01 Æ Node_adrs accepted, else rejected.
10 Æ Node_adrs & 0x00 accepted, else rejected.
11 Æ Node_adrs & 0x00 & 0xFF accepted, else rejected.
CRC check result for current packet (READ ONLY):
0 Æ Fail
1 Æ Pass
FIFO auto clear if CRC failed for current packet:
0Æ on (d)
1Æ off
Reserved
(d): “0000000” recommended to set to “1000000”
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ADVANCED COMMUNICATIONS & SENSING
7. Application Information
7.1. Crystal Resonator Specification
Table 28 shows the crystal resonator specification for the crystal reference oscillator circuit of the SX1213. This
specification covers the full range of operation of the SX1213 and is employed in the reference design (see section
7.5.3).
Table 28: Crystal Resonator Specification
Name
Fxtal
Cload
Rm
Co
ΔFxtal
ΔFxtal(ΔT)
Description
Nominal frequency
Load capacitance for Fxtal
Motional resistance
Shunt capacitance
Calibration tolerance at 25+/-3°C
Stability over temperature range [-40°C ; +85°C]
ΔFxtal(Δt)
Ageing tolerance in first 5 years
Min.
9
10
1
-15
-20
-2
Typ.
12.800
15
-
Max.
15
16.5
100
7
+15
+20
-
+2
Unit
MHz
pF
ohms
pF
ppm
ppm
ppm/year
Note that the initial frequency tolerance, temperature stability and ageing performance should be chosen in
accordance with the target operating temperature range and the receiver bandwidth selected.
7.2. Software for Frequency Calculation
The R1, P1, S1, and R2, P2, S2 dividers are configured over the SPI interface and programmed by 8 bits each, at
addresses 6 to 11. The frequency pairs may hence be switched in a single SPI cycle.
7.2.1. GUI
To aid the user with calculating appropriate R, P and S values, software is available to perform the frequency
calculation. The SX1213 PLL frequency Calculator Software can be downloaded from the Semtech website.
7.2.2. .dll for Automatic Production Bench
The Dynamically Linked Library (DLL) used by the software to perform these calculations is also provided, free of
charge, to users, for inclusion in automatic production testing. Key benefits of this are:
ƒ No hand trimming of the reference frequency required: the actual reference frequency of the Device Under Test
(DUT) can be easily measured (e.g. from the CLKOUT output of the SX1213) and the tool will calculate the
best frequencies to compensate for the crystal initial error.
ƒ Channel plans can be calculated and stored in the application’s memory, then adapted to the actual crystal
oscillator frequency.
7.3. Switching Times and Procedures
As an ultra-low power device, the SX1213 can be configured for low minimum average power consumption. To
minimize consumption the following optimized transitions between modes are shown.
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ADVANCED COMMUNICATIONS & SENSING
7.3.1. Optimized Receive Cycle
The lowest-power Rx cycle is the following:
SX1213
IDD
IDDR
3.0mA typ.
IDDFS
1.3mA typ.
IDDST
65uA typ.
IDDSL
100nA typ.
Time
Rx
time
SX1210 can be put in
Any other mode
Wait
TS RE
Receiver is ready :
-RSSI sampling is valid after a 1/Fdev period
-Received data is valid
Wait
TS FS
Set SX1210 in Rx mode
Wait for Receiver settling
Wait
TS OSC
Set SX1210 in FS mode
Wait for PLL settling
Set SX1210 in Standby mode
Wait for XO settling
Figure 40: Optimized Rx Cycle
Note: If the lock detect indicator is available on an external interrupt pin of the companion uC, it can be used to
optimize TS_FS, without having to wait the maximum specified TS_FS.
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SX1213
ADVANCED COMMUNICATIONS & SENSING
7.3.2. Receiver Frequency Hop Optimized Cycle
SX1213
IDD
IDDR
3mA typ
IDDFS
1.3mA typ.
Time
Wait
TS RE
SX1210 is now ready
for data reception
Wait
TS HOP
Set SX1210 back in Rx mode
1. Set R2/P2/S2
2. Set SX1210 in FS mode, change
MCParam_Band if needed, then switch
from R1/P1/S1 to R2/P2/S2
SX1210 is in Rx mode
On channel 1 (R1/P1/S1)
Figure 41: Rx Hop Cycle
Note: it is also possible to move from one channel to the other one without having to switch off the receiver. This
method is faster, and overall draws more current. For timing information, please refer to TS_RE_HOP on Table 7.
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ADVANCED COMMUNICATIONS & SENSING
7.4. Reset of the Chip
A power-on reset of the SX1213 is triggered at power up. Additionally, a manual reset can be issued by controlling
pin 13.
7.4.1. POR
If the application requires the disconnection of VDD from the SX1213, despite of the extremely low Sleep Mode
current, the user should wait for 10 ms from of the end of the POR cycle before commencing communications over
the SPI bus. Pin 13 (TEST8) should be left floating during the POR sequence.
VDD
Pin 13
(output)
Undefined
Wait for
10 ms
Chip is ready from
this point on
Figure 42: POR Timing Diagram
Please note that any CLKOUT activity can also be used to detect that the chip is ready.
7.4.2. Manual Reset
A manual reset of the SX1213 is possible even for applications in which VDD cannot be physically disconnected.
Pin 13 should be pulled high for a hundred microseconds, and then released. The user should then wait for 5 ms
before using the chip.
VDD
Pin 13
(input)
High-Z
> 100 us
Wait for
5 ms
’’1’’
High-Z
Chip is ready from
this point on
Figure 43: Manual Reset Timing Diagram
Please note that while pin 13 is driven high, an over current consumption of up to ten milliamps can be seen on
VDD.
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ADVANCED COMMUNICATIONS & SENSING
7.5. Reference Design
SX1212 Transceiver module is provided to perform the SX1213 evaluation, it is the receiver part of SX1212
Transceiver with compatible pinout and same receiver performances. SX1212 reference design is given as an
example below. However it is possible to reduce the BOM on SX1213 (refer to Table 29: Reference Design BOM).
7.5.1. Application Schematic
Figure 44: Reference Design Circuit Schematic
The reference design area is represented by the dashed rectangle. C12 is a DC blocking capacitor which protects
the SAW filter. It has been added for debug purposes could be removed for a direct antenna connection if there is
no DC bias is expected at the antenna port. Please note that for SX1213 C10 can be replaced a 5.4nH inductor, L4
by a 0Ohm, L3, C4, R1, C8 and C11 are not used. SAW filter is optional on most application (refer toTable 29:
Reference Design BOM)
7.5.2. PCB Layout
As illustrated in figures below, the layout has the following characteristics:
ƒ very compact (9x19mm) => can be easily inserted even on very small PCBs
ƒ standard PCB technology (2 layers, 1.6mm, std via & clearance) => low cost
ƒ Its performance is quasi-insensitive to dielectric thickness => minimal design effort to transfer to other PCB
technologies (thickness, # of layers, etc...)
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ADVANCED COMMUNICATIONS & SENSING
The layers description is illustrated in Figure 45:
Signal (35um)
Isolation (FR4, 1.6mm)
Ground plane
Figure 45: Reference Design‘s Stackup
The layout itself is illustrated in Figure 46. Please contact Semtech for Gerber files.
Figure 46: Reference Design Layout (top view)
7.5.3. Bill Of Material
Ref
U1
Q1
Value
315MHz
433MHz
SX1213
12.8 MHz
Tol (+/-)
Techno
Transceiver IC
15 ppm at 25°C
AT-cut
20 ppm over -40/+85°C
2ppm/year max
R2
6k8
1%
C1
1uF
15%
X5R
C2
100 nF
10%
X7R
C3
100 nF
10%
X7R
C5
100 nF
10%
X7R
C6
10 nF
10%
X7R
C7
680 pF
5%
NPO
C9
22 pF
5%
NPO
L1, L2
39 nH
18 nH
2%
Wire wound
L3
47 nH
5%
Monolithic
U2
315 MHz
434 MHz SAW Filter
C12*
47pF
5%
NPO
*Not part of the ref. design (not required for direct antenna connection).
Size
Comment
TQFN-32
5.0*3.2 mm
Fundamental, Cload=15 pF
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
3.8*3.8 mm
0402
Loop filter
VDD decoupling
Top regulator decoupling
Digital regulator decoupling
VCO regulator decoupling
Loop Filter
Loop Filter
DC block
VCO tank inductors
LNA bias inductor
Optional
DC block
Table 29: Reference Design BOM
Note: for battery powered applications, a high value capacitance should be implemented in parallel with C1
(typically 10 µF) to offer a low impedance voltage source during startup sequences.
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SX1213
ADVANCED COMMUNICATIONS & SENSING
7.5.4. Ordering Information for Tools
The modules described in section 7.5 can be ordered through your Semtech representative for evaluation purpose:
Table 30: Tools Ordering Information
Part Number
SM1212E433
SM1212E315
SX1212SKA315
SX1212SKA433
Description
2 layer RF module, 433 MHz band (Transceiver is used to evaluate the receiver)
2 layer RF module, 315 MHz band (Transceiver is used to evaluate the receiver)
USB evaluation kit, including antennas
USB evaluation kit, including antennas
8. Packaging Information
8.1. Package Outline Drawing
SX1213 is available in a 32-lead TQFN package as shown in Figure 47 below.
A
D
B
DIM
PIN 1
INDICATOR
(LASER MARK)
E
A2
A
SEATING
PLANE
aaa C
A
A1
A2
b
D
D1
E
E1
e
L
N
aaa
bbb
DIMENSIONS
MILLIMETERS
INCHES
MIN NOM MAX MIN NOM MAX
- .031
.028
.000
.002
- (.008) .007 .010 .012
.193 .197 .201
.142 .146 .150
.193 .197 .201
.142 .146 .150
.020 BSC
.012 .016 .020
32
.003
.004
0.80
0.70
0.05
0.00
- (0.20) 0.18 0.25 0.30
4.90 5.00 5.10
3.60 3.70 3.80
4.90 5.00 5.10
3.60 3.70 3.80
0.50 BSC
0.30 0.40 0.50
32
0.08
0.10
C
A1
D1
LxN
E/2
E1
2
1
N
bxN
e/2
e
bbb
C A B
D/2
NOTES:
1. CONTROLLING DIMENSIONS ARE IN MILLIMETERS (ANGLES IN DEGREES).
2. COPLANARITY APPLIES TO THE EXPOSED PAD AS WELL AS THE TERMINALS.
Figure 47: Package Outline Drawing
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ADVANCED COMMUNICATIONS & SENSING
8.2. PCB Land Pattern
K
(C)
H
G
DIM
C
G
H
K
P
X
Y
Z
Z
Y
X
DIMENSIONS
INCHES
MILLIMETERS
(.197)
(5.00)
4.20
.165
3.70
.146
3.70
.146
0.50
.020
.012
0.30
.031
0.80
.228
5.80
P
NOTES:
1. CONTROLLING DIMENSIONS ARE IN MILLIMETERS (ANGLES IN DEGREES).
2. THIS LAND PATTERN IS FOR REFERENCE PURPOSES ONLY.
CONSULT YOUR MANUFACTURING GROUP TO ENSURE YOUR
COMPANY'S MANUFACTURING GUIDELINES ARE MET.
3. THERMAL VIAS IN THE LAND PATTERN OF THE EXPOSED PAD
SHALL BE CONNECTED TO A SYSTEM GROUND PLANE.
FAILURE TO DO SO MAY COMPROMISE THE THERMAL AND/OR
FUNCTIONAL PERFORMANCE OF THE DEVICE.
4. SQUARE PACKAGE - DIMENSIONS APPLY IN BOTH " X " AND " Y " DIRECTIONS.
Figure 48: PCB Land Pattern
8.3. Tape & Reel Specification
Direction of Feed
Carrier Tape
Tape
Width(W)
Pocket
Pitch (P)
Ao/Bo
12
8
5.25
+/-0.3
+/-0.1
+/-0.2
Notes:
*all dimensions in mm
*single sprocket holes
Reel
Ko
Reel
Size
Reel
Width
Min.Trail
er Length
Min.
Leader
Length
QTY per
Reel
1.10
+/-0.1
330.2
12.4
400
400
3000
Figure 49: Tape & Reel Dimensions
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ADVANCED COMMUNICATIONS & SENSING
9. Revision History
ƒ
Revision 2.0: Final datasheet supersedes preliminary.
10. Contact Information
Semtech Corporation
Advanced Communication and Sensing Products Division
200 Flynn Road, Camarillo, CA 93012
Phone (805) 498-2111 Fax: (805) 498-3804
© Semtech 2009
All rights reserved. Reproduction in whole or in part is prohibited without the prior written consent of the copyright owner.
The information presented in this document does not form part of any quotation or contract, is believed to be accurate and
reliable and may be changed without notice. No liability will be accepted by the publisher for any consequence of its use.
Publication thereof does not convey nor imply any license under patent or other industrial or intellectual property rights.
Semtech. assumes no responsibility or liability whatsoever for any failure or unexpected operation resulting from misuse,
neglect improper installation, repair or improper handling or unusual physical or electrical stress including, but not limited to,
exposure to parameters beyond the specified maximum ratings or operation outside the specified range.
SEMTECH PRODUCTS ARE NOT DESIGNED, INTENDED, AUTHORIZED OR WARRANTED TO BE SUITABLE FOR
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