STMICROELECTRONICS VIPER100SP

VIPer100/SP
- VIPer100A/ASP
®
SMPS PRIMARY I.C.
TYPE
VIPer100/SP
VIPer100A/ASP
VDSS
620V
700V
■ ADJUSTABLE
In
3A
3A
RDS(on)
2.5 Ω
2.8 Ω
SWITCHING FREQUENCY UP
TO 200 kHz
■ CURRENT MODE CONTROL
■ SOFT START AND SHUT DOWN CONTROL
■ AUTOMATIC BURST MODE OPERATION IN
STAND-BY CONDITION ABLE TO MEET
“BLUE ANGEL” NORM (<1w TOTAL POWER
CONSUMPTION)
■ INTERNALLY TRIMMED ZENER REFERENCE
■ UNDERVOLTAGE LOCK-OUT WITH
HYSTERESIS
■ INTEGRATED START-UP SUPPLY
■ AVALANCHE RUGGED
■ OVERTEMPERATURE PROTECTION
■ LOW STAND-BY CURRENT
■ ADJUSTABLE CURRENT LIMITATION
10
PENTAWATT HV
PENTAWATT HV
(022Y)
1
PowerSO-10™
DESCRIPTION
VIPer100™/100A, made using VIPower M0
Technology, combines on the same silicon chip a
state-of-the-art PWM circuit together with an
optimized high voltage avalanche rugged Vertical
Power MOSFET (620V or 700V / 3A).
Typical applications cover off line power supplies
with a secondary power capability of 50 W in wide
range condition and 100W in single range or with
doubler configuration. It is compatible from both
primary or secondary regulation loop despite
using around 50% less components when
compared with a discrete solution. Burst mode
operation is an additional feature of this device,
offering the possibility to operate in stand-by
mode without extra components.
BLOCK DIAGRAM
DRAIN
OSC
ON/OFF
OSCILLATOR
SECURITY
LATCH
UVLO
LOGIC
VDD
R/S
FF
Q
S
PWM
LATCH
S
R1 FF Q
R2 R3
OVERTEMP.
DETECTOR
0.5 V
+
_
1.7 µ s
DELAY
250 ns
BLANKING
4.5 V
FC00231
+
COMP
May 2003
1 V/A
CURRENT
AMPLIFIER
ERROR
_ AMPLIFIER
13 V
0.5V
_
+ +
_
SOURCE
1/23
1
VIPer100/SP - VIPer100A/ASP
ABSOLUTE MAXIMUM RATING
Symbol
Parameter
Continuous Drain-Source Voltage (Tj=25 to 125°C)
for VIPer100/SP
for VIPer100A/ASP
VDS
ID
VDD
VOSC
VCOMP
ICOMP
Vesd
ID(AR)
Ptot
Tj
Tstg
Maximum Current
Supply Voltage
Voltage Range Input
Voltage Range Input
Maximum Continuous Current
Electrostatic Discharge (R =1.5kΩ; C=100pF)
Avalanche Drain-Source Current, Repetitive or Not Repetitive
(Tc=100°C; Pulse width limited by Tj max; δ < 1%)
for VIPer100/SP
for VIPer100A/ASP
Power Dissipation at Tc=25ºC
Junction Operating Temperature
Storage Temperature
Value
Unit
-0.3 to 620
V
-0.3 to 700
Internally limited
0 to 15
0 to VDD
0 to 5
±2
4000
V
A
V
V
V
mA
V
2
A
1.4
A
82
Internally limited
-65 to 150
W
°C
°C
THERMAL DATA
Symbol
Rthj-case
Rthj-amb.
Parameter
Thermal Resistance Junction-case
Thermal Resistance Ambient-case
Max
Max
PENTAWATT HV
1.4
60
PowerSO-10™ (*)
1.4
50
Unit
°C/W
°C/W
(*) When mounted using the minimum recommended pad size on FR-4 board.
CONNECTION DIAGRAMS (Top View)
PENTAWATT HV
PENTAWATT HV (022Y)
PowerSO-10™
CURRENT AND VOLTAGE CONVENTIONS
IDD
ID
VDD
IOSC
DRAIN
OSC
13V
+
COMP SOURCE
VDD
VDS
ICOMP
VOSC
VCOMP
FC00020
2/23
1
VIPer100/SP - VIPer100A/ASP
ORDERING NUMBERS
PENTAWATT HV
VIPer100
PENTAWATT HV (022Y)
VIPer100 (022Y)
PowerSO-10™
VIPer100SP
VIPer100A
VIPer100A (022Y)
VIPer100ASP
PINS FUNCTIONAL DESCRIPTION
DRAIN PIN:
Integrated Power MOSFET drain pin. It provides
internal bias current during start-up via an
integrated high voltage current source which is
switched off during normal operation. The device
is able to handle an unclamped current during its
normal operation, assuring self protection against
voltage surges, PCB stray inductance, and
allowing a snubberless operation for low output
power.
source, and can easily be connected to the
output of an optocoupler. Note that any
overvoltage due to regulation loop failure is still
detected by the error amplifier through the VDD
voltage, which cannot overpass 13V. The
output voltage will be somewhat higher than the
nominal one, but still under control.
COMP PIN:
This pin provides two functions :
SOURCE Pin:
Power MOSFET source pin. Primary side circuit
common ground connection.
VDD Pin:
This pin provides two functions :
- It corresponds to the low voltage supply of the
control part of the circuit. If VDD goes below 8V,
the start-up current source is activated and the
output power MOSFET is switched off until the
VDD voltage reaches 11V. During this phase,
the internal current consumption is reduced,
the VDD pin is sourcing a current of about 2mA
and the COMP pin is shorted to ground. After
that, the current source is shut down, and the
device tries to start up by switching again.
- This pin is also connected to the error amplifier,
in order to allow primary as well as secondary
regulation configurations. In case of primary
regulation, an internal 13V trimmed reference
voltage is used to maintain VDD at 13V. For
secondary regulation, a voltage between 8.5V
and 12.5V will be put on VDD pin by transformer
design, in order to stuck the output of the
transconductance amplifier to the high state.
The COMP pin behaves as a constant current
3/23
1
- It is the output of the error transconductance
amplifier, and allows for the connection of a
compensation network to provide the desired
transfer function of the regulation loop. Its
bandwidth can be easily adjusted to the
needed value with usual components value. As
stated
above,
secondary
regulation
configurations are also implemented through
the COMP pin.
- When the COMP voltage is going below 0.5V,
the shut-down of the circuit occurs, with a zero
duty cycle for the power MOSFET. This feature
can be used to switch off the converter, and is
automatically activated by the regulation loop
(whatever is the configuration) to provide a
burst mode operation in case of negligible
output power or open load condition.
OSC PIN:
An Rt-Ct network must be connected on that pin to
define the switching frequency. Note that despite
the connection of Rt to VDD, no significant
frequency change occurs for VDD varying from 8V
to 15V. It provides also a synchronisation
capability, when connected to an external
frequency source.
VIPer100/SP - VIPer100A/ASP
AVALANCHE CHARACTERISTICS
Symbol
ID(AR)
E(AR)
Parameter
Avalanche Current, Repetitive or Not Repetitive
(pulse widht limited by Tj max; δ < 1%)
for VIPer100/SP
for VIPer100A/ASP
(see fig.12)
Single Pulse Avalanche Energy
(starting Tj =25ºC, I D=ID(ar))
(see fig.12)
Max Value
Unit
2
A
1.4
A
60
mJ
ELECTRICAL CHARACTERISTICS (Tj=25°C; VDD=13V, unless otherwise specified)
POWER SECTION
Symbol
BVDSS
IDSS
RDS(on)
Parameter
Drain-Source Voltage
Off-State Drain Current
Static Drain-Source
On Resistance
tf
Fall Time
tr
Rise Time
Coss
Output Capacitance
Test Conditions
ID=1mA; VCOMP=0V
for VIPer100/SP
for VIPer100A/ASP (see fig.5)
Min
Typ
Max
Unit
620
V
700
V
VCOMP=0V; Tj=125°C
VDS=620V for VIPer100/SP
VDS=700V for VIPer100A/ASP
ID=2A
for VIPer100/SP
for VIPer100A/ASP
ID=2A; Tj=100°C
for VIPer100/SP
for VIPer100A/ASP
1
mA
1
mA
2.0
2.5
Ω
2.3
2.8
Ω
4.5
Ω
5.0
ID=0.2A; VIN=300V (1)
(See fig. 3)
100
Ω
ns
ID=0.4A; VIN=300V (1)
(See fig. 3)
VDS=25V
50
ns
150
pF
(1) On Inductive Load, Clamped.
SUPPLY SECTION
Symbol
Parameter
Test Conditions
IDDch
Start-Up Charging
Current
IDD0
Operating Supply Current VDD=12V; FSW=0kHz
(see fig. 2)
IDD1
IDD2
VDDoff
VDDon
VDDhyst
Operating Supply Current
Operating Supply Current
Undervoltage Shutdown
Undervoltage Reset
Hysteresis Start-up
Min
VDD=5V; VDS=35V
(see fig. 2 and fig. 15)
VDD=12V; Fsw=100kHz
VDD=12V; Fsw=200kHz
(See fig. 2)
(See fig. 2)
(See fig. 2)
7.5
2.4
Typ
-2
Max
Unit
mA
12
16
mA
15.5
19
8
11
3
9
12
mA
mA
V
V
V
4/23
VIPer100/SP - VIPer100A/ASP
ELECTRICAL CHARACTERISTICS (continued)
OSCILLATOR SECTION
Symbol
FSW
VOSCIH
VOSCIL
Parameter
Oscillator Frequency
Total Variation
Test Conditions
RT=8.2KΩ; CT=2.4nF
VDD=9 to 15V;
with RT± 1%; CT± 5%
(see fig. 6 and fig. 9)
Min
Typ
Max
Unit
90
100
110
kHz
Oscillator Peak Voltage
Oscillator Valley Voltage
7.1
3.7
V
V
ERROR AMPLIFIER SECTION
Symbol
VDDREG
∆VDDreg
Parameter
VDD Regulation Point
Total Variation
Test Conditions
ICOMP=0mA
(see fig. 1)
Tj=0 to 100°C
GBW
Unity Gain Bandwidth
From Input =VDD to Output = VCOMP
COMP pin is open
(see fig. 10)
AVOL
Gm
Open Loop Voltage Gain
DC Transconductance
Output Low Level
Output High Level
Output Low Current
Capability
Output High Current
Capability
VCOMPLO
VCOMPHI
ICOMPLO
ICOMPHI
COMP pin is open
VCOMP=2.5V
ICOMP=-400µA; VDD=14V
ICOMP=400µA; VDD=12V
(see fig. 10)
(see fig. 1)
Min
12.6
Typ
13
2
150
45
1.1
52
1.5
0.2
4.5
Max
13.4
1.9
Unit
V
%
kHz
dB
mA/V
V
V
VCOMP=2.5V; VDD=14V
-600
µA
VCOMP=2.5V; VDD=12V
600
µA
PWM COMPARATOR SECTION
Symbol
HID
VCOMPoff
IDpeak
td
tb
ton(min)
Parameter
∆VCOMP / ∆IDPEAK
VCOMP Offset
Peak Current Limitation
Current Sense Delay to
Turn-Off
Blanking Time
Minimum On Time
Test Conditions
VCOMP=1 to 3 V
IDPEAK=10mA
VDD=12V; COMP pin open
Min
0.7
3
ID=1A
Typ
1
0.5
4
Max
1.3
5.3
250
Unit
V/A
V
A
ns
250
350
360
1200
ns
ns
Typ
0.5
1.7
Max
Unit
V
µs
SHUTDOWN AND OVERTEMPERATURE SECTION
Symbol
VCOMPth
tDISsu
Ttsd
Thyst
5/23
Parameter
Restart Threshold
Disable Set Up Time
Thermal Shutdown
Temperature
Thermal Shutdown
Hysteresis
Test Conditions
Min
(see fig. 4)
(see fig. 4)
(See fig. 8)
(See fig. 8)
140
5
170
°C
40
°C
VIPer100/SP - VIPer100A/ASP
Figure 2: Undervoltage Lockout
Figure 1: VDD Regulation Point
ICOMP
IDD
Slope =
Gm in mA/V
ICOMPHI
IDD0
VDD
0
VDDhyst
ICOMPLO
VDDoff
VDS= 35 V
Fsw = 0
VDDon VDD
IDDch
VDDreg
FC00150
Figure 3: Transition Time
FC00170
Figure 4: Shut Down Action
VOSC
ID
t
VCOMP
10% Ipeak
VDS
tDISsu
t
t
VCOMPth
90% VD
ID
10% VD
t
tf
t
tr
ENABLE
FC00160
ENABLE
DISABLE
FC00060
Figure 5: Breakdown Voltage Vs. Temperature
Figure 6: Typical Frequency Variation
FC00180
1.15
FC00190
(%)
BVDSS
(Normalized)
1
0
1.1
-1
-2
1.05
-3
1
-4
0.95
-5
0
20
40 60 80 100 120
Temperature (°C)
0
20
40 60 80 100 120 140
Temperature (°C)
6/23
VIPer100/SP - VIPer100A/ASP
Figure 7: Start-Up Waveforms
Figure 8: Overtemperature Protection
TJ
Ttsc
Ttsd-Thyst
t
Vdd
Vddon
Vddoff
t
Id
t
Vcomp
t
SC10191
7/23
VIPer100/SP - VIPer100A/ASP
Figure 9: Oscillator
For Rt >1.2KΩ
and
Ct ≥ 15nF if FSW ≤ 40KHz
VDD
Rt
OSC
2.3
550
F SW = ------------ ⋅  1 – ----------------------
R t Ct 
Rt – 150
FC00050
Ct
Forbidden area
880
Ct(nF) =
22nF
Fsw(kHz)
15nF
Forbidden area
40kHz
Fsw
Oscillator frequency vs Rt and Ct
FC00030
1,000
Ct = 1.5 nF
500
Ct = 2.7 nF
Frequency (kHz)
Ct
~360Ω
CLK
300
Ct = 4.7 nF
200
Ct = 10 nF
100
50
30
1
2
3
5
10
20
30
50
Rt (kΩ)
8/23
1
VIPer100/SP - VIPer100A/ASP
Figure 10: Error Amplifier Frequency Response
FC00200
60
RCOMP = +∞
Voltage Gain (dB)
RCOMP = 270k
40
RCOMP = 82k
RCOMP = 27k
20
RCOMP = 12k
0
(20)
0.001
0.01
0.1
1
10
Frequency (kHz)
100
1,000
Figure 11: Error Amplifier Phase Response
FC00210
200
RCOMP = +∞
150
RCOMP = 270k
Phase (°)
RCOMP = 82k
RCOMP = 27k
100
RCOMP = 12k
50
0
(50)
0.001
0.01
0.1
1
10
Frequency (kHz)
100
1,000
9/23
1
VIPer100/SP - VIPer100A/ASP
Figure 12: Avalanche Test Circuit
L1
1mH
2
VDD
1
3
DRAIN
OSC
13V
BT1
0 to 20V
+
COMP
BT2
12V
C1
47uF
16V
Q1
2 x STHV102FI in parallel
R1
SOURCE
5
4
47
GENERATOR INPUT
500us PULSE
U1
VIPer100
R2
1k
R3
100
FC00195
10/23
1
VIPer100/SP - VIPer100A/ASP
Figure 13: Off Line Power Supply With Auxiliary Supply Feedback
F1
BR1
TR2
C1
TR1
D2
AC IN
L2
+Vcc
D1
R9
C2
C7
C9
R1
C3
GND
D3
C10
R7
C4
R2
VDD
DRAIN
-
U1
VIPer100
OSC
13V
+
COMP SOURCE
C5
C6
C11
R3
FC00081
Figure 14: Off Line Power Supply With Optocoupler Feedback
F1
BR1
TR2
C1
TR1
D2
AC IN
L2
+Vcc
D1
R9
C2
C7
C9
R1
C3
GND
D3
C10
R7
C4
R2
VDD
DRAIN
-
U1
OSC
13V
VIPer100
+
COMP SOURCE
C5
C11
C6
R3
R6
ISO1
R4
C8
U2
R5
FC00091
11/23
1
VIPer100/SP - VIPer100A/ASP
OPERATION DESCRIPTION:
CURRENT MODE TOPOLOGY:
The current mode control method, like the one
integrated in the VIPer100/100A uses two control
loops - an inner current control loop and an outer
loop for voltage control. When the Power
MOSFET output transistor is on, the inductor
current (primary side of the transformer) is
monitored with a SenseFET technique and
converted into a voltage VS proportional to this
current. When VS reaches VCOMP (the amplified
output voltage error) the power switch is switched
off. Thus, the outer voltage control loop defines
the level at which the inner loop regulates peak
current through the power switch and the primary
winding of the transformer.
Excellent open loop D.C. and dynamic line
regulation is ensured due to the inherent input
voltage feedforward characteristic of the current
mode control. This results in an improved line
regulation, instantaneous correction to line
changes and better stability for the voltage
regulation loop.
Current mode topology also ensures good
limitation in the case of short circuit. During a first
phase the output current increases slowly
following the dynamic of the regulation loop. Then
it reaches the maximum limitation current
internally set and finally stops because the power
supply on VDD is no longer correct. For specific
applications the maximum peak current internally
set can be overridden by externally limiting the
voltage excursion on the COMP pin. An integrated
blanking filter inhibits the PWM comparator output
for a short time after the integrated Power
MOSFET is switched on. This function prevents
anomalous or premature termination of the
switching pulse in the case of current spikes
caused by primary side capacitance or secondary
side rectifier reverse recovery time.
STAND-BY MODE
Stand-by operation in nearly open load condition
automatically leads to a burst mode operation
allowing voltage regulation on the secondary side.
The transition from normal operation to burst
mode operation happens for a power PSTBY given
by :
P
STBY
2
1
= --- L I STBY F
SW
2 P
Where:
LP is the primary inductance of the transformer.
FSW is the normal switching frequency.
ISTBY is the minimum controllable current,
corresponding to the minimum on time that the
device is able to provide in normal operation. This
current can be computed as :
( t b + td )V IN
I STBY = -------------------------------L
P
tb + td is the sum of the blanking time and of the
propagation time of the internal current sense and
comparator, and represents roughly the minimum
on time of the device. Note that PSTBY may be
affected by the efficiency of the converter at low
load, and must include the power drawn on the
primary auxiliary voltage.
As soon as the power goes below this limit, the
auxiliary secondary voltage starts to increase
above the 13V regulation level forcing the output
voltage of the transconductance amplifier to low
state (VCOMP < VCOMPth). This situation leads to
the shutdown mode where the power switch is
maintained in the off state, resulting in missing
cycles and zero duty cycle. As soon as VDD gets
back to the regulation level and the VCOMPth
threshold is reached, the device operates again.
The above cycle repeats indefinitely, providing a
burst mode of which the effective duty cycle is
much lower than the minimum one when in normal
operation. The equivalent switching frequency is
also lower than the normal one, leading to a
reduced consumption on the input mains lines.
This mode of operation allows the VIPer100/100A
to meet the new German "Blue Angel" Norm with
less than 1W total power consumption for the
system when working in stand-by. The output
voltage remains regulated around the normal
level, with a low frequency ripple corresponding to
the burst mode. The amplitude of this ripple is low,
because of the output capacitors and of the low
output current drawn in such conditions.The
normal operation resumes automatically when the
power get back to higher levels than PSTBY.
HIGH
VOLTAGE
START-UP
CURRENT
SOURCE
An integrated high voltage current source provides
a bias current from the DRAIN pin during the startup phase. This current is partially absorbed by
internal control circuits which are placed into a
standby mode with reduced consumption and also
provided to the external capacitor connected to the
VDD pin. As soon as the voltage on this pin
reaches the high voltage threshold VDDon of the
UVLO logic, the device turns into active mode and
starts switching.
12/23
VIPer100/SP - VIPer100A/ASP
The start up current generator is switched off, and
the converter should normally provide the needed
current on the VDD pin through the auxiliary
winding of the transformer, as shown on figure 15.
In case of abnormal condition where the auxiliary
winding is unable to provide the low voltage supply
current to the VDD pin (i.e. short circuit on the
output of the converter), the external capacitor
discharges itself down to the low threshold voltage
VDDoff of the UVLO logic, and the device get back
to the inactive state where the internal circuits are
in standby mode and the start up current source is
activated. The converter enters a endless start up
cycle, with a start-up duty cycle defined by the
ratio of charging current towards discharging when
the VIPer100/100A tries to start. This ratio is fixed
by design to 2 to 15, which gives a 12% start up
duty cycle while the power dissipation at start up is
approximately 0.6 W, for a 230 Vrms input voltage.
This low value of start-up duty cycle prevents the
stress of the output rectifiers and of the
transformer when in short circuit.
The external capacitor CVDD on the VDD pin must
be sized according to the time needed by the
converter to start up, when the device starts
switching. This time tSS depends on many
parameters, among which transformer design,
output capacitors, soft start feature and
compensation network implemented on the COMP
pin. The following formula can be used for defining
the minimum capacitor needed:
IDD t SS
C VDD > -------------------------V DDhy st
where:
IDD is the consumption current on the VDD pin
when switching. Refer to specified IDD1 and IDD2
values.
tSS is the start up time of the converter when the
device begins to switch. Worst case is generally at
full load.
VDDhyst is the voltage hysteresis of the UVLO
logic. Refer to the minimum specified value.
Soft start feature can be implemented on the
COMP pin through a simple capacitor which will be
also used as the compensation network. In this
case, the regulation loop bandwidth is rather low,
because of the large value of this capacitor. In
case a large regulation loop bandwidth is
mandatory, the schematics of figure 16 can be
used. It mixes a high performance compensation
network together with a separate high value soft
start capacitor. Both soft start time and regulation
loop bandwidth can be adjusted separately.
If the device is intentionally shut down by putting
the COMP pin to ground, the device is also
performing start-up cycles, and the VDD voltage is
oscillating between VDDon and VDDoff.
This voltage can be used for supplying external
functions, provided that their consumption doesn’t
exceed 0.5mA. Figure 17 shows a typical
application of this function, with a latched shut
down. Once the "Shutdown" signal has been
activated, the device remains in the off state until
the input voltage is removed.
Figure 15: Behaviour of the high voltage current source at start-up
VDD
2 mA
VDDon
VDDoff
3 mA
VDD
15 mA
DRAIN
1 mA 15 mA
CVDD
Ref.
t
Auxiliary primary
winding
UNDERVOLTAGE
LOCK OUT LOGIC
VIPer100
SOURCE
Start up duty cycle ~ 12%
FC00100
13/23
VIPer100/SP - VIPer100A/ASP
TRANSCONDUCTANCE ERROR AMPLIFIER
The VIPer100/100A includes a transconductance
error amplifier. Transconductance Gm is the
change in output current (ICOMP) versus change in
input voltage (VDD). Thus:
G
∂I COMP
-----------------------=
m
∂V DD
The output impedance ZCOMP at the output of this
amplifier (COMP pin) can be defined as:
∂V COMP
∂V COMP
1
Z COMP = --------------------------- = --------- × --------------------------G
∂V DD
∂I COMP
m
This last equation shows that the open loop gain
AVOL can be related to Gm and ZCOMP:
AVOL = Gm x ZCOMP
where Gm value for VIPer100/100A is 1.5 mA/V
typically.
Gmis well defined by specification, but ZCOMP and
therefore AVOL are subject to large tolerances. An
impedance Z can be connected between the
COMP pin and ground in order to define more
accurately the transfer function F of the error
amplifier, according to the following equation, very
similar to the one above:
F(S) = Gm x Z(S)
The error amplifier frequency response is reported
in figure 10 for different values of a simple
resistance connected on the COMP pin. The
unloaded transconductance error amplifier shows
an internal ZCOMP of about 330 KΩ. More complex
impedance can be connected on the COMP pin to
Figure 16: Mixed Soft Start and Compensation
achieve different compensation laws. A capacitor
will provide an integrator function, thus eliminating
the DC static error, and a resistance in series
leads to a flat gain at higher frequency, insuring a
correct phase margin. This configuration is
illustrated on figure 18.
As shown in figure 18 an additional noise filtering
capacitor of 2.2 nF is generally needed to avoid
any high frequency interference.
It can be also interesting to implement a slope
compensation when working in continuous mode
with duty cycle higher than 50%. Figure 19 shows
such a configuration. Note that R1 and C2 build
the classical compensation network, and Q1 is
injecting the slope compensation with the correct
polarity from the oscillator sawtooth.
EXTERNAL CLOCK SYNCHRONIZATION:
The OSC pin provides a synchronisation
capability, when connected to an external
frequency source. Figure 20 shows one possible
schematic to be adapted depending the specific
needs. If the proposed schematic is used, the
pulse duration must be kept at a low value (500ns
is sufficient) for minimizing consumption. The
optocoupler must be able to provide 20mA through
the optotransistor.
PRIMARY PEAK CURRENT LIMITATION
The primary IDPEAK current and, as resulting
effect, the output power can be limited using the
simple circuit shown in figure 21. The circuit based
on Q1, R1 and R2 clamps the voltage on the
Figure 17: Latched Shut Down
D2
U1
VIPER100
VDD
D3
U1
VIPER100
R1
DRAIN
OSC
13V
VDD
R3
+
COMP
13V
AUXILIARY
WINDING
DRAIN
-
OSC
D1
C4
Q2
SOURCE
+
COMP SOURCE
R3
R1
R2
R2
+ C3
C1
R4
+ C2
Shutdown
FC00131
Q1
D1
FC00110
14/23
VIPer100/SP - VIPer100A/ASP
COMP pin in order to limit the primary peak
current of the device to a value:
– 0.5
V
COMP
IDPEAK = ------------------------------------H ID
where:
R1 + R2
V COMP = 0.6 × ---------------------R2
OVER-TEMPERATURE PROTECTION:
Over-temperature protection is based on chip
temperature sensing. The minimum junction
temperature at which over-temperature cut-out
occurs is 140ºC while the typical value is 170ºC.
The device is automatically restarted when the
junction temperature decreases to the restart
temperature threshold that is typically 40ºC below
the shutdown value (see figure 8).
The suggested value for R1+R2 is in the range of
220KΩ.
Figure 18: Typical Compensation Network
Figure 19: Slope Compensation
U1
VIPER100
VDD
R2
DRAIN
R1
U1
V IP E R 1 00
-
OSC
13V
VD D
+
COMP
D RA IN
-
O SC
SOURCE
13 V
+
COMP
S O U RC E
C2
C2
R1
Q1
C3
C1
C1
R3
F C 00141
FC00121
Figure 20: External Clock Sinchronisation
Figure 21: Current Limitation Circuit Example
U1
V IP E R 1 0 0
VDD
U1
VIPER100
VDD
D R A IN
-
OSC
1 3V
+
COM P
DRAIN
S OURC E
-
OSC
13V
+
COMP
SOURCE
R1
10 kΩ
Q1
R2
FC00220
F C 0 0 2 40
15/23
VIPer100/SP - VIPer100A/ASP
Figure 22: Input Voltage Surges Protection
R1
D1
(Optional)
R2
39R
Auxilliary winding
C1
Bulk capacitor
VDD
C2
22nF
DRAIN
OSC
13V
+
VIPerXX0
COMP SOURCE
ELECTRICAL OVER STRESS RUGGEDNESS
The VIPer may be submitted to electrical over
stress caused by violent input voltage surges or
lightning. Following the enclosed Layout
Considerations chapter rules is the most of the
time sufficient to prevent catastrophic damages,
however in some cases the voltage surges
coupled through the transformer auxiliary winding
can overpass the VDD pin absolute maximum
rating voltage value. Such events may trigger the
VDD internal protection circuitry which could be
damaged by the strong discharge current of the
VDD bulk capacitor. The simple RC filter shown in
figure 22 can be implemented to improve the
application immunity to such surges.
16/23
VIPer100/SP - VIPer100A/ASP
Figure 23: Recommended Layout
T1
D1
C7
D2
7RVHFRQGDU\
ILOWHULQJDQGORDG
R1
VDD
DRAIN
-
C1
OSC
13V
)URPLQSXW
C5
+
COMP
GLRGHVEULGJH
SOURCE
U1
VIPerXX0
R2
C6
C2
C3
ISO1
C4
FC00500
LAYOUT CONSIDERATIONS
Some simple rules insure a correct running of
switching power supplies. They may be classified
into two categories:
- To minimise power loops: the way the switched
power current must be carefully analysed and
the corresponding paths must present the
smallest inner loop area as possible. This
avoids radiated EMC noises, conducted EMC
noises by magnetic coupling, and provides a
better efficiency by eliminating parasitic
inductances, especially on secondary side.
- To use different tracks for low level signals and
power ones. The interferences due to a mixing
of signal and power may result in instabilities
and/or anomalous behaviour of the device in
case of violent power surge (Input overvoltages,
output short circuits...).
In case of VIPer, these rules apply as shown on
figure 23. The loops C1-T1-U1, C5-D2-T1, C7-D1T1 must be minimised. C6 must be as close as
possible from T1. The signal components C2,
ISO1, C3 and C4 are using a dedicated track to be
connected directly to the source of the device.
17/23
1
VIPer100/SP - VIPer100A/ASP
PowerSO-10™ MECHANICAL DATA
mm.
DIM.
MIN.
A
A (*)
A1
B
B (*)
C
C (*)
D
D1
E
E2
E2 (*)
E4
E4 (*)
e
F
F (*)
H
H (*)
h
L
L (*)
α
α (*)
inch
TYP
3.35
3.4
0.00
0.40
0.37
0.35
0.23
9.40
7.40
9.30
7.20
7.30
5.90
5.90
MAX.
MIN.
3.65
3.6
0.10
0.60
0.53
0.55
0.32
9.60
7.60
9.50
7.60
7.50
6.10
6.30
0.132
0.134
0.000
0.016
0.014
0.013
0.009
0.370
0.291
0.366
0.283
0.287
0.232
0.232
1.35
1.40
14.40
14.35
0.049
0.047
0.543
0.545
1.80
1.10
8º
8º
0.047
0.031
0º
2º
TYP.
MAX.
0.144
0.142
0.004
0.024
0.021
0.022
0.0126
0.378
0.300
0.374
300
0.295
0.240
0.248
1.27
0.050
1.25
1.20
13.80
13.85
0.053
0.055
0.567
0.565
0.50
0.002
1.20
0.80
0º
2º
0.070
0.043
8º
8º
(*) Muar only POA P013P
B
0.10 A B
10
H
E
E2
E4
1
SEATING
PLANE
e
B
DETAIL "A"
h
A
C
0.25
D
= D1 =
=
=
SEATING
PLANE
A
F
A1
A1
L
DETAIL "A"
α
P095A
18/23
VIPer100/SP - VIPer100A/ASP
PENTAWATT HV MECHANICAL DATA
DIM.
mm.
MIN.
TYP
inch
MAX.
MIN.
TYP.
MAX.
A
4.30
4.80
0.169
0.189
C
1.17
1.37
0.046
0.054
D
2.40
2.80
0.094
0.11
E
0.35
0.55
0.014
0.022
F
0.60
0.80
0.024
0.031
G1
4.91
5.21
0.193
0.205
G2
7.49
7.80
0.295
0.307
H1
9.30
9.70
0.366
H2
0.382
10.40
10.05
H3
0.409
10.40
0.396
0.409
L
15.60
17.30
6.14
0.681
L1
14.60
15.22
0.575
0.599
L2
21.20
21.85
0.835
0.860
L3
22.20
22.82
0.874
0.898
L5
2.60
3
0.102
0.118
L6
15.10
15.80
0.594
0.622
L7
6
6.60
0.236
0.260
M
2.50
3.10
0.098
0.122
M1
4.50
5.60
0.177
0.220
R
0.50
0.02
V4
Diam
90° (typ)
3.65
3.85
0.144
0.152
P023H3
19/23
1
VIPer100/SP - VIPer100A/ASP
PENTAWATT HV 022Y (VERTICAL HIGH PITCH) MECHANICAL DATA
DIM.
mm.
MIN.
inch
TYP
MAX.
MIN.
TYP.
MAX.
A
4.30
4.80
0.169
0.189
C
1.17
1.37
0.046
0.054
D
2.40
2.80
0.094
0.110
E
0.35
0.55
0.014
0.022
F
0.60
0.80
0.024
0.031
G1
4.91
5.21
0.193
0.205
G2
7.49
7.80
0.295
0.307
H1
9.30
9.70
0.366
0.382
H3
10.05
10.40
0.396
0.409
L
16.42
17.42
0.646
0.686
L1
14.60
15.22
0.575
0.599
L3
20.52
21.52
0.808
0.847
H2
10.40
0.409
L5
2.60
3.00
0.102
0.118
L6
15.10
15.80
0.594
0.622
L7
6.00
6.60
0.236
0.260
M
2.50
3.10
0.098
0.122
M1
5.00
5.70
0.197
0.224
R
0.50
V4
90°
Diam.
0.020
90°
3.70
3.90
0.146
0.154
L
L1
E
A
M
M1
C
D
R
Resin between
leads
L6
L7
V4
H2
H3
H1
G1
G2
F
DIA
L5
L3
20/23
1
VIPer100/SP - VIPer100A/ASP
PowerSO-10™ SUGGESTED PAD LAYOUT
TUBE SHIPMENT (no suffix)
14.6 - 14.9
CASABLANCA
B
10.8- 11
MUAR
C
6.30
C
A
A
0.67 - 0.73
10
9
1
9.5
2
3
B
0.54 - 0.6
All dimensions are in mm.
8
7
4
5
1.27
Base Q.ty Bulk Q.ty Tube length (± 0.5)
6
Casablanca
Muar
50
50
1000
1000
532
532
A
B
C (± 0.1)
10.4 16.4
4.9 17.2
0.8
0.8
TAPE AND REEL SHIPMENT (suffix “13TR”)
REEL DIMENSIONS
Base Q.ty
Bulk Q.ty
A (max)
B (min)
C (± 0.2)
F
G (+ 2 / -0)
N (min)
T (max)
600
600
330
1.5
13
20.2
24.4
60
30.4
All dimensions are in mm.
TAPE DIMENSIONS
According to Electronic Industries Association
(EIA) Standard 481 rev. A, Feb. 1986
Tape width
Tape Hole Spacing
Component Spacing
Hole Diameter
Hole Diameter
Hole Position
Compartment Depth
Hole Spacing
W
P0 (± 0.1)
P
D (± 0.1/-0)
D1 (min)
F (± 0.05)
K (max)
P1 (± 0.1)
All dimensions are in mm.
24
4
24
1.5
1.5
11.5
6.5
2
End
Start
Top
No components
Components
No components
cover
tape
500mm min
Empty components pockets
saled with cover tape.
500mm min
User direction of feed
21/23
1
VIPer100/SP - VIPer100A/ASP
PENTAWATT HV TUBE SHIPMENT (no suffix)
B
C
Base Q.ty
Bulk Q.ty
Tube length (± 0.5)
A
B
C (± 0.1)
50
1000
532
18
33.1
1
All dimensions are in mm.
A
22/23
1
VIPer100/SP - VIPer100A/ASP
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of use of such information nor for any infringement of patents or other rights of third parties which may results from its use. No license is
granted by implication or otherwise under any patent or patent rights of STMicroelectronics. Specifications mentioned in this publication are
subject to change without notice. This publication supersedes and replaces all information previously supplied. STMicroelectronics products
are not authorized for use as critical components in life support devices or systems without express written approval of STMicroelectronics.
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23/23
1