LM4854 1.9W Monaural, 85mW Stereo Headphone Audio Amplifier General Description The unity-gain stable LM4854 is both a mono differential output (for bridge-tied loads, or BTL) audio power amplifier and a single-ended (SE) stereo headphone amplifier. Operating on a single 5V supply, the mono BTL mode delivers 1.1W (typ) to an 8Ω load, 1.7W (typ) to a 4Ω load (Note 1) at 1% THD+N. In SE stereo mode, the amplifier will deliver 85mW to 32Ω loads. The LM4854 features a new circuit topology that suppresses output transients (’click and pops’) and eliminates SE-mode output coupling capacitors, saving both component and board space costs. The LM4854 has three inputs: one pair for a two-channel stereo signal and the third for a single-channel mono input. The LM4854 is designed for PDA, cellular telephone, notebook, and other handheld portable applications. It delivers high quality output power from a surface-mount package and requires few external components. Other features include an active-low micropower shutdown mode, an "instant-on" low power standby mode, and thermal shutdown protection. The LM4854 is available in the very space-efficient 12-lead micro SMD, exposed-DAP LLP for higher power applications, and TSSOP packages. Note 1: An LM4854LD that has been properly mounted to a circuit board will deliver 1.7W (typ) into a 4Ω load. Key Specifications j LLP BTL output power (RL = 3.2Ω and THD+N = 1%) VDD = 3.0V 1.0W (typ) VDD = 5.0V 1.9W (typ) j LLP BTL output power (RL = 4Ω and THD+N = 1%) VDD = 3.0V 900mW (typ) VDD = 5.0V 1.7W (typ) j LLP BTL output power (RL = 8Ω and THD+N = 1%) VDD = 3.0V 380mW (typ) VDD = 5.0V 1.1W (typ) j SE output power (RL = 32Ω and THD+N = 1.0%) VDD = 3.0V 32mW (typ) VDD = 5.0V 93mW (typ) j Micropower shutdown supply current VDD = 3.0V 0.005µA (typ) VDD = 5.0V 0.05µA (typ) j Standby supply current VDD = 3.0V 16µA (typ) VDD = 5.0V 27µA (typ) j PSRR (f = 1kHz, 3.0V ≤ VDD ≤ 5.0V, (Fig. 1)) BTL 60dB (typ) SE 66dB (typ) Features n Fast 0.1ms (typ) and 1.0ms (max) turn-on and turn-off time n Eliminates SE amplifier output coupling capacitors n Advanced "click and pop" suppression circuitry n Stereo headphone amplifier mode n Low-power standby and ultra-low current micropower shutdown modes n Thermal shutdown protection circuitry n 2.4V to 5.5V operation n Unity-gain stable n Gain set with external resistors n Space-saving micro SMD package, exposed-DAP LLP, and TSSOP Applications n n n n PDAs Notebook computers Cellular phones Handheld portable electronic devices Boomer ® is a registered trademark of National Semiconductor Corporation. © 2003 National Semiconductor Corporation DS200382 www.national.com LM4854 1.9W Monaural, 85mW Stereo Headphone Audio Amplifier April 2003 LM4854 Typical Application 20038201 FIGURE 1. Typical Audio Amplifier Application Circuit (Pin out shown for the 12-pin large bump micro SMD IBL package. Consult the "Connection Diagrams" for the LLP or MT package pin out.) www.national.com 2 LM4854 Connection Diagrams 20038202 Top View (Bump-side down) Order Number LM4854IBL See NS Package Number BLA12BAB Micro SMD Marking 20038203 Top View X - Date Code T - Die Traceability G - Boomer Family 54 - LM4854IBL LM4854IBL Pin Designation Pin (Bump) Number Pin Function A1 L-IN B1 GND C1 R-IN D1 MONO-IN A2 L-OUT B2 BYPASS C2 HP-SENSE D2 R-OUT A3 SHUTDOWN B3 VDD C3 BTL-OUT D3 STANDBY 3 www.national.com LM4854 Connection Diagrams 200382A5 Top View U - Fab Code Z - Plant Code XY - Date Code TT - Die Tracebility Bottom Line - Part Number 20038204 Top View Order Number LM4854LD See NS Package Number LDA14A 200382A6 Top View Z - Plant Code XY - Date Code TT - Die Traceability Bottom 2 lines - Part Number 20038205 Top View Order Number LM4854MT See NS Package Number MTC14 www.national.com 4 Infrared (15 sec.) (Notes 2, See AN-540 "Surface Mounting and their Effects on Product Reliability" for other methods of soldering surface-mount devices. 3) If Military/Aerospace specified devices are required, please contact the National Semiconductor Sales Office/ Distributors for availability and specifications. Supply Voltage Thermal Resistance 6.0V Storage Temperature Input Voltage θJA (typ) — BLA12BAB −65˚C to +150˚C −0.3V to VDD + 0.3V Power Dissipation(Note 4) Internally Limited ESD Susceptibility (Note 5) All pins except Pin C3 (IBL), Pin11 (LD/MT) Pin C3 (IBL), Pin 11 (LD/MT) 220˚C 121˚C/W θJC (typ) — LDA14A 3˚C/W θJA (typ) — LDA14A 42˚C/W (Note 7) θJC (typ) — MTC14 40˚C/W θJA (typ) — MTC14 109˚C/W 2000V Operating Ratings (Note 3) 8000V ESD Susceptibility(Note 6) 200V Junction Temperature (TJ) 150˚C Temperature Range TMIN ≤ TA ≤ TMAX Solder Information −40˚C ≤ TA ≤ +85˚C 2.4V ≤ VDD ≤ 5.5V Supply Voltage Small Outline Package Vapor Phase (60 sec.) 215˚C Electrical Characteristics for Entire Amplifier (VDD = 5V) The following specifications apply for circuit shown in Figure 1, unless otherwise specified. Limits apply for TA = 25˚C. Symbol Parameter Conditions LM4854 Typical (Note 8) IDD Quiescent Power Supply Current Limit (Notes 9, 10) Units (Limits) VIN = 0V; IO = 0A, No Load 5.0 12 mA max) VIN = 0V; IO = 0A, 8Ω Load 6.5 15 mA (max) 27 35 µA (max) ISTBY Standby Quiescent Power Supply Current VSTANDBY = GND ISD Shutdown Quiescent Power Supply Current VSHUTDOWN = GND 0.05 0.2 µA (max) VOS Output Offset Voltage 8Ω Load 2.0 40 mV (max) PSRR Power Supply Rejection Ratio CBYPASS = 1.0µF, RSOURCE = 10Ω VRIPPLE = 200mVp-p sinewave BTL, RL = 8Ω, RIN = 10Ω fIN = 217Hz fIN = 1kHz SE, RL = 32Ω, RIN = 10Ω fIN = 217Hz fIN = 1kHz CBYPASS = 1.0µF 61 63 dB dB 68 71 dB dB 200 ms tRSH Return-from-Shutdown Time tRST Return-from-Standby Time 1.0 ms(max) VIH Shutdown or Standby Logic High Treshold 1.4 V (min) VIL Shutdown or Standby Logic Low Treshold 0.4 V (max) 0.1 5 www.national.com LM4854 Absolute Maximum Ratings LM4854 Electrical Characteristics Bridged-Mode Operation (VDD = 5V) The following specifications apply for for the circuit shown in Figure 1 and a measurement bandwith of 20Hz to 80kHz, unless otherwise specified. Limits apply for TA = 25˚C. Symbol Parameter Conditions LM4854 Typical (Note 8) Output Power (Note 11) PO THD+N S/N Total Harmonic Distortion+Noise Signal-to-Noise Ratio Limit (Notes 9, 10) Units (Limits) THD = 1% (max); f = 1kHz (Note12) RL = 3.2Ω (LM4854LD) RL = 4Ω (LM4854LD) RL = 8Ω 1.9 1.7 1.1 THD = 10% (max); f = 1kHz (Note12) RL = 3.2Ω (LM4854LD) RL = 4Ω (LM4854LD) RL = 8Ω 2.3 2.1 1.3 W W W 20Hz ≤ fIN ≤ 20kHz RL = 4Ω, PO = 1.0W (LM4854LD) RL = 8Ω, PO = 400mW 0.3 0.18 % % fIN = 1kHz RL = 4Ω, PO = 1.5W (LM4854LD) RL = 8Ω, PO = 50mW 0.1 0.08 % % 90 dB fIN = 1kHz, CBYPASS = 1.0µF PO = 900mW, RL = 8Ω 1.0 W W W (min) Electrical Characteristics : SE Operation (VDD = 5V) The following specifications apply for for the circuit shown in Figure 1 and a measurement bandwith of 20Hz to 80kHz, unless otherwise specified. Limits apply for TA = 25˚C. Symbol Parameter Output Power (Note 11) PO Conditions THD+N THD+N THD+N THD+N = = = = 1.0%, f = 1kHz, RL = 32Ω 10%, f = 1kHz, RL = 32Ω 1.0%, f = 1kHz, RL = 16Ω 10%, f = 1kHz, RL = 16Ω LM4854 Typical (Note 8) Limit (Notes 9, 10) 93 105 170 200 85 140 Units (Limits) mW(min) mW mW(min) mW THD+N Total Harmonic Distortion+Noise 20Hz ≤ fIN ≤ 20kHz RL = 32Ω, PO = 50mW 0.3 % VOUT Output Voltage Swing THD = 1.0%, RL = 5kΩ 4.0 VP-P XTALK Channel Separation fIN = 1kHz, CBYPASS = 1.0µF, RL = 32Ω 55 dB S/N Signal-to-Noise Ratio fIN = 1kHz, CBYPASS = 1.0µF PO = 50mW, RL = 32Ω 90 dB Electrical Characteristics for Entire Amplifier (VDD = 3.0V) The following specifications apply for circuit shown in Figure 1, unless otherwise specified. Limits apply for TA = 25˚C. Symbol Parameter Conditions LM4854 Typical (Note 8) Limit (Notes 9, 10) Units (Limits) IDD Quiescent Power Supply Current VIN = 0V, IO = 0A, 8Ω Load 4.0 10 mA (max) ISTBY Standby Quiescent Power Supply Current VSTANDBY = GND 16.0 20.0 µA (max) ISD Shutdown Current VSHUTDOWN = GND 0.005 0.02 µA (max) VOS Output Offset Voltage 8 Ω Load 2.0 40 mV (max) www.national.com 6 LM4854 Electrical Characteristics for Entire Amplifier (VDD = 3.0V) (Continued) The following specifications apply for circuit shown in Figure 1, unless otherwise specified. Limits apply for TA = 25˚C. Symbol Parameter Conditions LM4854 Typical (Note 8) PSRR Power Supply Rejection Ratio CBYPASS = 1.0µF, RSOURCE = 10Ω VRIPPLE = 200mVp-p sinewave BTL, RL = 8Ω, RIN = 10Ω fIN = 217Hz fIN = 1kHz SE, RL = 32Ω, RIN = 10Ω fIN = 217Hz fIN = 1kHz CBYPASS = 1.0µF Limit (Notes 9, 10) Units (Limits) 62 62 dB dB 68 72 dB dB 200 ms tRSH Return-from-Shutdown Time tRST Return-from-Standby Time 1.0 ms(max) VIH Shutdown or Standby Logic High Treshold 1.4 V (min) VIL Shutdown or Standby Logic Low Treshold 0.4 V (max) 0.1 Electrical Characteristics : Bridged-Mode Operation (VDD = 3.0V) (Notes 4, 9) The following specifications apply for for the circuit shown in Figure 1 and a measurement bandwith of 20Hz to 80kHz, unless otherwise specified. Limits apply for TA = 25˚C. Symbol Parameter Conditions LM4854 Typical (Note 8) PO THD+N S/N Output Power (Note11) Total Harmonic Distortion+Noise Signal-to-Noise Ratio Limit (Notes 9, 10) Units (Limits) THD = 1% (max); f = 1kHz (Note11) RL = 4Ω (LM4854LD) RL = 8Ω 1.0 380 THD = 10% (max); f = 1kHz (Note11) RL = 4Ω (LM4854LD) RL = 8Ω 1.1 530 W mW 20Hz ≤ fIN ≤ 20kHz RL = 4Ω, PO = 800mW (LM4854LD) RL = 8Ω, PO = 150mW 0.3 0.21 % % fIN = 1kHz RL = 4Ω, PO = 500mW (LM4854LD) RL = 8Ω, PO = 150mW 0.1 0.075 % % 90 dB fIN = 1kHz, CBYPASS = 1.0µF PO = 900mW, RL = 8Ω 7 350 W mW (min) www.national.com LM4854 Electrical Characteristics : SE Operation (VDD = 3.0V) (Notes 4, 9) The following specifications apply for for the circuit shown in Figure 1 and a measurement bandwith of 20Hz to 80kHz, unless otherwise specified. Limits apply for TA = 25˚C. Symbol PO Parameter Output Power (Note 11) Conditions THD+N THD+N THD+N THD+N = = = = 1.0%, f = 1kHz, RL = 32Ω 10%, f = 1kHz, RL = 32Ω 1.0%, f = 1kHz, RL = 16Ω 10%, f = 1kHz, RL = 16Ω LM4854 Typical (Note 8) Limit (Notes 9, 10) 32 60 57 100 27 38 Units (Limits) mW(min) mW mW (min) mW THD+N Total Harmonic Distortion+Noise 20Hz ≤ fIN = ≤ 20kHz RL = 32Ω, PO = 30mW 0.3 % VOUT Output Voltage Swing THD = 0.5%, RL = 5kΩ 2.4 VP-P XTALK Channel Separation fIN = 1kHz, CBYPASS = 1.0µF, RL = 32Ω 55 dB S/N Signal-to-Noise Ratio fIN = 1kHz, CBYPASS = 1.0µF PO = 30mW, RL = 32Ω TBD dB Note 2: All voltages are measured with respect to the GND pin unless other wise specified. Note 3: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is functional but do not guarantee specific performance limits. Electrical Characteristics state DC and AC electrical specifications under particular test conditions that guarantee specific performance limits. This assumes that the device is within the Operating Ratings. Specifications are not guaranteed for parameters where no limit is given, however, the typical value is a good indication of device performance. Note 4: The maximum power dissipation must be derated at elevated temperatures and is dictated by TJMAX, θJA, and the ambient temperature, TA. The maximum allowable power dissipation is PDMAX = (TJMAX - TA)/θJA or the number given in Absolute Maximum Ratings, whichever is lower. For the LM4854, see power derating currents for more information. Note 5: Human body model, 100pF discharged through a 1.5kΩ resistor. Note 6: Machine Model, 220pF-240pF discharged through all pins. Note 7: The given θJA is for an LM4854 packaged in an LDA14A with the Exposed-DAP soldered to an exposed 2in2 area of 1oz printed circuit board copper. Note 8: Typicals are measured at 25˚C and represent the parametric norm. Note 9: Limits are guaranteed to National’s AOQL (Average Outgoing Quality Level). Note 10: Datasheet minimum and maximum specification limits are guaranteed by design, test, or statistical analysis. Note 11: Output power is measured at the amplifier’s package pins. Note 12: When driving 4Ω loads and operating on a 5V supply, the LM4854LD must be mounted to a circuit board that has a minimum of 2.5in2 of exposed, uninterrupted copper area connected to the LLP package’s exposed DAP. www.national.com 8 LM4854 External Components Description See Figure 1. Components Functional Description 1. Ri This is the inverting input resistance that, along with Rf, sets the closed-loop gain. Input resistance Ri and input capacitance Ci form a high pass filter. The filter’s cutoff frequency is fc = 1/2πRiCi. 2. Ci This is the input coupling capacitor. It blocks DC voltage at the amplifier’s inverting input. Ci and Ri create a highpass filter. The filter’s cutoff frequency is fc = 1/2πRiCi. Refer to the Application Information section, SELECTING EXTERNAL COMPONENTS, for an explanation of determining Ci’s value. 3. Rf This is the feedback resistance that, along with Ri, sets the closed-loop gain. 4. Cs The supply bypass capacitor. Refer to the POWER SUPPLY BYPASSING section for information about properly placing, and selecting the value of, this capacitor. 5. CB This capacitor filters the half-supply voltage present on the BYPASS pin. Refer to the Application Information section, SELECTING EXTERNAL COMPONENTS, for information about properly placing, and selecting the value of, this capacitor.. Typical Performance Characteristics THD+N vs Frequency THD+N vs Frequency 200382D8 VDD 200382D9 LM4854LD = 5V, RL = 4Ω (BTL), POUT = 1000mW VDD THD+N vs Frequency LM4854LD = 5V, RL = 4Ω (BTL), POUT = 400mW THD+N vs Frequency 200382C0 200382B8 VDD = 5V, RL = 8Ω (BTL), POUT = 400mW VDD = 5V, RL = 16Ω (SE), POUT = 50mW 9 www.national.com LM4854 Typical Performance Characteristics (Continued) THD+N vs Frequency THD+N vs Frequency 200382B9 200382E0 VDD = 5V, RL = 32Ω (SE), POUT = 50mW VDD THD+N vs Frequency LM4854LD = 3V, RL = 4Ω (BTL), POUT = 150mW THD+N vs Frequency 200382B7 200382B5 VDD = 3V, RL = 8Ω (BTL), POUT = 150mW www.national.com VDD = 3V, RL = 16Ω (SE), POUT = 30mW 10 LM4854 Typical Performance Characteristics (Continued) THD+N vs Frequency THD+N vs Output Power 200382B6 200382E1 VDD = 3V, RL = 32Ω (SE), POUT = 30mW LM4854LD VDD = 5V, RL = 4Ω (BTL), at (from top to bottom at 200mW) 20kHZ, 20Hz, 1kHz THD+N vs Output Power THD+N vs Output Power 200382C4 200382C6 VDD = 5V, RL = 16Ω (SE), at (from top to bottom at 30mW) 20kHz, 20Hz, 1kHz VDD = 5V, RL = 8Ω (BTL), at (from top to bottom at 0.2W) 20kHz, 20Hz, 1kHz 11 www.national.com LM4854 Typical Performance Characteristics (Continued) THD+N vs Output Power THD+N vs Output Power 200382C5 200382E2 VDD = 5V, RL = 32Ω (SE), at (from top to bottom at 20mW) 20kHz, 20Hz, 1kHz LM4854LD VDD = 3V, RL = 4Ω (BTL), at (from top to bottom at 200mW) 20kHz, 20Hz, 1kHz THD+N vs Output Power THD+N vs Output Power 200382C1 200382C3 VDD = 3V, RL = 16Ω (SE), at (from top to bottom at 20mW) 20kHz, 20Hz, 1kHz VDD = 3V, RL = 8Ω (BTL), at (from top to bottom at 0.02W) 20kHz, 20Hz, 1kHz www.national.com 12 LM4854 Typical Performance Characteristics (Continued) THD+N vs Output Power Output Power vs Power Supply Voltage 200382A8 200382C2 VDD = 3V, RL = 32Ω (SE), at (from top to bottom at 20mW) 20kHz, 20Hz, 1kHz RL = 8Ω (BTL), fIN = 1kHz, at (from top to bottom at 4V) 10% THD+N, 1% THD+N Output Power vs Power Supply Voltage PSRR vs Frequency 200382A7 200382E3 RL = 16Ω (BTL), fIN = 1kHz, at (from top to bottom at 4V): 10% THD+N, 1% THD+N VDD 13 LM4854LD = 5V, RL = 4Ω (BTL), RSOURCE = 10Ω www.national.com LM4854 Typical Performance Characteristics (Continued) PSRR vs Frequency PSRR vs Frequency 200382B4 200382B2 VDD = 5V, RL = 8Ω (BTL), RSOURCE = 10Ω VDD = 5V, RL = 16Ω (SE), RSOURCE = 10Ω PSRR vs Frequency PSRR vs Frequency 200382E4 200382B3 VDD = 5V, RL = 32Ω (SE), RSOURCE = 10Ω www.national.com VDD 14 LM4854LD = 3V, RL = 4Ω (BTL), RSOURCE = 10Ω LM4854 Typical Performance Characteristics (Continued) PSRR vs Frequency PSRR vs Frequency 200382B1 200382A9 VDD = 3V, RL = 8Ω (BTL), RSOURCE = 10Ω VDD = 3V, RL = 16Ω (SE), RSOURCE = 10Ω PSRR vs Frequency Amplifier Power Dissipation vs Load Power Dissipation 200382D1 200382B0 LM4854IBL/MT, VDD = 5V, RL = 8Ω (BTL), fIN = 1kHz VDD = 3V, RL = 32Ω (SE), RSOURCE = 10Ω 15 www.national.com LM4854 Typical Performance Characteristics (Continued) Amplifier Power Dissipation vs Load Power Dissipation Amplifier Power Dissipation vs Load Power Dissipation 200382C7 200382C8 LM4854IBL/MT, VDD = 5V, (from top to bottom at 0.04W): RL = 16Ω (SE), RL = 32Ω (SE), fIN = 1kHz, both channels driven and loaded LM4854IBL/MT, VDD = 3V, RL = 8Ω (BTL), fIN = 1kHz Power Dissipation Derating Curves Power Dissipation Derating Curve 200382E9 200382E6 LM4854LD, VDD = 5V, RL = 8Ω (BTL), fIN = 1kHz, (from top to bottom at 120˚C): 4in2 copper plane heatsink area 1in2 copper plane heatsink area www.national.com LM4854IBL, VDD = 5V, RL = 8Ω (BTL), fIN = 1kHz 16 LM4854 Typical Performance Characteristics (Continued) Power Dissipation Derating Curve Amplifier Power Dissipation vs Load Power Dissipation 200382C9 200382E7 LM4854MT, VDD = 5V, RL = 8Ω (BTL), fIN = 1kHz LM4854IBL/MT, VDD = 3V, (from top to bottom at 0.02W): RL = 16Ω (SE), RL = 32Ω (SE), fIN = 1kHz, both channels driven and loaded Output Power vs Load Resistance Output Power vs Load Resistance 200382D2 200382D3 LM4854IBL/MT, BTL Load, (from top to bottom at 12Ω): VDD = 5V, THD+N = 10%; VDD = 5V, THD+N = 1% VDD = 3V, THD+N = 10% VDD = 3V, THD+N = 1% LM4854IBL/MT, SE Load (both channels driven and loaded), fIN = 1kHz, (from top to bottom at 12Ω): VDD = 5V, THD+N = 10%; VDD = 5V, THD+N = 1% VDD = 3V, THD+N = 10% VDD = 3V, THD+N = 1% 17 www.national.com LM4854 Typical Performance Characteristics (Continued) Channel-to-Channel Crosstalk vs Frequency Channel-to-Channel Crosstalk vs Frequency 200382D4 200382D5 VDD = 5V, RL = 16Ω (SE) A = Left channel driven, right channel measured B = Right channel driven, left channel measured VDD = 5V, RL = 32Ω (SE) A = Left channel driven, right channel measured B = Right channel driven, left channel measured Channel-to-Channel Crosstalk vs Frequency Channel-to-Channel Crosstalk vs Frequency 200382D6 200382D7 VDD = 3V, RL = 16Ω (SE) A = Left channel driven, right channel measured B = Right channel driven, left channel measured VDD = 3V, RL = 32Ω (SE) A = Left channel driven, right channel measured B = Right channel driven, left channel measured Headphones driven by the LM4854 operate in a manner very similar to a BTL load. The same DC voltage is applied to each input terminal on a headphone speaker. This results in no net DC current flow through the speaker. AC current flows through a headphone speaker as an audio signal’s output amplitude increases on one of the speaker’s terminal. When operating as a headphone amplifier, the headphone jack sleeve is not connected to circuit ground, but to VDD/2. Using the headphone output jack as a line-level output will place the LM4854’s one-half supply voltage on a plug’s sleeve connection. Driving a portable notebook computer or audio-visual display equipment is possible. This presents no difficulty when the external equipment uses capacitively coupled inputs. For the very small minority of equipment that is DC-coupled, the LM4854 monitors the current supplied by Application Information ELIMINATING OUTPUT COUPLING CAPACITORS Typical single-supply audio amplifiers that can switch between driving bridge-tied-load (BTL) speakers and singleended (SE) headphones use a coupling capacitor on each SE output. This capacitor blocks the half-supply voltage to which the output amplifiers are typically biased and couples the audio signal to the headphones. The signal returns to circuit ground through the headphone jack’s sleeve. The LM4854 eliminates these coupling capacitors. When the LM4854 is configured to drive SE loads, AMP2 is internally configured to apply VDD/2 to a stereo headphone jack’s sleeve. This voltage equals the quiescent voltage present on the Amp1 and Amp3 outputs that drive the headphones. www.national.com 18 tecting the LM4854 and the external equipment. For more information, see the section titled ’Single-Ended Output Power Performance and Measurement Considerations’. (Continued) the amplifier that drives the headphone jack’s sleeve. If this current exceeds 500mAPK, the amplifier is shutdown, pro- 20038207 FIGURE 2. Typical Audio Amplifier Application Circuit EXPOSED-DAP MOUNTING CONSIDERATIONS The LM4854’s exposed-DAP (die attach paddle) package (LD) provides a low thermal resistance between the die and the PCB to which the part is mounted and soldered. This allows rapid heat transfer from the die to the surrounding PCB copper area heatsink, copper traces, ground plane, and finally, surrounding air. The result is a low voltage audio power amplifier that produces 1.7W dissipation in a 4Ω load at ≤ 1% THD+N and over 1.9W in a 3Ω load at 10% THD+N. This high power is achieved through careful consideration of necessary thermal design. Failing to optimize thermal design may compromise the LM4854’s high power performance and activate unwanted, though necessary, thermal shutdown protection. The LD package must have its DAP soldered to a copper pad on the PCB. The DAP’s PCB copper pad is then, ideally, connected to a large plane of continuous unbroken copper. This plane forms a thermal mass, heat sink, and radiation area. Place the heat sink area on either outside plane in the case of a two-sided or multi-layer PCB. (The heat sink area can also be placed on an inner layer of a multi-layer board. The thermal resistance, however, will be higher.) Connect the DAP copper pad to the inner layer or backside copper heat sink area with 6 (3 X 2) (LD) vias. The via diameter should be 0.012in - 0.013in with a 1.27mm pitch. Ensure efficient thermal conductivity by plugging and tenting the vias with plating and solder mask, respectively. Best thermal performance is achieved with the largest practical copper heat sink area. If the heatsink and amplifier share the same PCB layer, a nominal 2.5in2 (min) area is necessary for 5V operation with a 4Ω load. Heatsink areas not placed on the same PCB layer as the LM4854 should be 5in2 (min) for the same supply voltage and load resistance. The last two area recommendations apply for 25˚C ambient temperature. Increase the area to compensate for ambient temperatures above 25˚C. In all circumstances and under all conditions, the junction temperature must be held below 150˚C to prevent activating the LM4854’s thermal shutdown protection. The LM4854’s power de-rating curve in the Typical Performance Characteristics shows the maximum power dissipation versus temperature. Example PCB layouts for the exposed-DAP TSSOP and LD packages are shown in the Demonstration Board Layout section. Further detailed and specific information concerning PCB layout and fabrication and mounting an LD (LLP) is found in National Semiconductor’s AN1187. 19 www.national.com LM4854 Application Information LM4854 Application Information typical single-ended configuration forces a single-supply amplifier’s half-supply bias voltage across the load. This increases internal IC power dissipation and may permanently damage loads such as speakers. (Continued) PCB LAYOUT AND SUPPLY REGULATION CONSIDERATIONS FOR DRIVING 3Ω AND 4Ω LOADS Power dissipated by a load is a function of the voltage swing across the load and the load’s impedance. As load impedance decreases, load dissipation becomes increasingly dependent on the interconnect (PCB trace and wire) resistance between the amplifier output pins and the load’s connections. Residual trace resistance causes a voltage drop, which results in power dissipated in the trace and not in the load as desired. For example, 0.1Ω trace resistance reduces the output power dissipated by a 4Ω load from 1.7W to 1.6W. The problem of decreased load dissipation is exacerbated as load impedance decreases. Therefore, to maintain the highest load dissipation and widest output voltage swing, PCB traces that connect the output pins to a load must be as wide as possible. POWER DISSIPATION Power dissipation is a major concern when successful single-ended or bridged amplifier. states the maximum power dissipation point ended amplifier operating at a given supply driving a specified output load. PDMAX-SE = (VDD)2/(2π2 RL): Single-Ended PDMAX-MONOBTL = 4(VDD)2/(2π2 RL): Bridge Mode (3) The maximum power dissipation point given by Equation (3) must not exceed the power dissipation given by Equation (4): BRIDGE CONFIGURATION EXPLANATION As shown in Figure 2, the LM4854 consists of three operational amplifiers. In mono mode, AMP1 and AMP2 operate in series to drive a speaker connected between their outputs. In stereo mode, AMP1 and AMP3 are used to drive stereo headphones or other SE load. In mono mode, external resistors RfL and RiL set the closedloop gain of AMP1, whereas two internal 20kΩ resistors set AMP2’s gain at -1. The LM4854 drives a load, such as a speaker, connected between the two amplifier outputs, L-OUT and BTL-OUT. Figure 2 shows that AMP1’s output serves as AMP2’s input. This results in both amplifiers producing signals identical in magnitude, but 180˚ out of phase. Taking advantage of this phase difference, a load is placed between L-OUT and BTLOUT and driven differentially (commonly referred to as "bridge mode"). This results in a differential,or BTL, gain of: PDMAX’ = (TJMAX - TA)/ θJA (4) The LM4854’s TJMAX = 150˚C. In the IBL package, the LM4854’s θJA is 121˚C/W. The LM4854’s TJMAX = 150˚C. In the LD package soldered to a DAP pad that expands to a copper area of 2.0in2 on a PCB, the LM4854’s θJA is 42˚C/W. In the MT package, the LM4854’s θJA is 109˚C/W. At any given ambient temperature TA, use Equation (4) to find the maximum internal power dissipation supported by the IC packaging. Rearranging Equation (4) and substituting PDMAX for PDMAX’ results in Equation (5). This equation gives the maximum ambient temperature that still allows maximum stereo power dissipation without violating the LM4854’s maximum junction temperature. (1) TA = TJMAX - PDMAX-MONOBTLθJA Bridge mode amplifiers are different from single-ended amplifiers that drive loads connected between a single amplifier’s output and ground. For a given supply voltage, bridge mode has a distinct advantage over the single-ended configuration: its differential output doubles the voltage swing across the load. Theoretically, this produces four times the output power when compared to a single-ended amplifier under the same conditions. This increase in attainable output power assumes that the amplifier is not current limited and that the output signal is not clipped. To ensure minimum output signal clipping when choosing an amplifier’s closedloop gain, refer to the Audio Power Amplifier Design section. Another advantage of the differential bridge output is no net DC voltage across the load. This is accomplished by biasing AMP1’s and AMP2’s outputs at half-supply. This eliminates the coupling capacitor that single supply, single-ended amplifiers require. Eliminating an output coupling capacitor in a www.national.com (2) However, a direct consequence of the increased power delivered to the load by a bridge amplifier is higher internal power dissipation for the same conditions. The LM4854 has two operational amplifiers driving a mono bridge load. The maximum internal power dissipation operating in the bridge mode is twice that of a single-ended amplifier. From Equation (3), assuming a 5V power supply and an 8Ω load, the maximum BTL-mode power dissipation is 317mW. Poor power supply regulation adversely affects maximum output power. A poorly regulated supply’s output voltage decreases with increasing load current. Reduced supply voltage causes decreased headroom, output signal clipping, and reduced output power. Even with tightly regulated supplies, trace resistance creates the same effects as poor supply regulation. Therefore, making the power supply traces as wide as possible helps maintain full output voltage swing. AVD = 2(Rf/Ri) designing a Equation (2) for a singlevoltage and (5) For a typical application with a 5V power supply and an 8Ω load, the maximum ambient temperature that allows maximum stereo power dissipation without exceeding the maximum junction temperature is approximately 73˚C for the IBL package. TJMAX = PDMAX-MONOBTLθJA + TA (6) Equation (6) gives the maximum junction temperature TJMAX. If the result violates the LM4854’s 150˚C, reduce the maximum junction temperature by reducing the power supply voltage or increasing the load resistance. Further allowance should be made for increased ambient temperatures. The above examples assume that a device is a surface mount part operating around the maximum power dissipation point. Since internal power dissipation is a function of output 20 CONTROLLING STANDBY AND MICROPOWER SHUTDOWN (Continued) power, higher ambient temperatures are allowed as output power or duty cycle decreases. If the result of Equation (3) is greater than that of Equation (4), then decrease the supply voltage, increase the load impedance, or reduce the ambient temperature. If these measures are insufficient, a heat sink can be added to reduce θJA. The heat sink can be created using additional copper area around the package, with connections to the ground pin(s), supply pin and amplifier output pins. External, solder attached SMT heatsinks such as the Thermalloy 7106D can also improve power dissipation. When adding a heat sink, the θJA is the sum of θJC, θCS, and θSA. (θJC is the junction-to-case thermal impedance, θCS is the case-to-sink thermal impedance, and θSA is the sink-toambient thermal impedance.) Refer to the Typical Performance Characteristics curves for power dissipation information at lower output power levels. POWER SUPPLY BYPASSING There are a few methods to control standby or micro-power shutdown. These include using a single-pole, single-throw switch (SPST), a microprocessor, or a microcontroller. When using a switch, connect a 100kΩ pull-up resistor between the STANDBY or SHUTDOWN pin and VDD and the SPST switch between the STANDBY or SHUTDOWN pin and GND. Select normal amplifier operation by opening the switch. Closing the switch applies GND to the STANDBY or SHUTDOWN pins, activating micro-power shutdown. The switch and resistor guarantee that the STANDBY or SHUTDOWN pins will not float. This prevents unwanted state changes. In a system with a microprocessor or a microcontroller, use a digital output to apply the active-state voltage to the STANDBY or SHUTDOWN pin. HEADPHONE (SINGLE-ENDED) AMPLIFIER OPERATION Previous single-supply amplifiers that were designed to drive both BTL and SE loads used a SE (or headphone) "sense" input. This input typically required two external resistors to bias the sense input to a preset voltage that selected BTL operation. The LM4854 has a unique headphone sense circuit that eliminates the external resistors. The amplifier has an internal comparator that monitors the voltage present on the R-OUT pin. It compares this voltage against the voltage on the HP-SENSE pin. When these voltages are equal, BTL mode is selected and AMP3 is shutdown and its output has a very high impedance. When the comparator’s input signals are different, (a typical ∆V of 200mV), the comparator’s output switches and activates the SE (headphone) mode. AMP3 changes from shutdown state to an active state and, along with AMP1, drives a stereo load. AMP2 drives the headphone jack sleeve. Figure 3 shows the suggested headphone jack electrical connections. The jack is designed to mate with a three-wire plug. The plug’s tip should carry a stereo signal’s leftchannel information. The ring adjacent to the tip should each carry the right-channel signal and the ring furthest from the tip provides the return to AMP2. A switch can replace the headphone jack contact pin. When the switch shorts the HP-SENSE pin to R-OUT, the bridge-connected speaker is driven by AMP1 and AMP2. AMP3 is shutdown, its output in a high-impedance state. When the switch opens, the LM4854 operates in SE stereo mode. If headphone drive is not needed, short the HP-SENSE pin to the R-OUT pin. The LM4854’s unique headphone sense circuit requires a dual switch headphone jack. A five-terminal headphone jack, such as the Switchcraft 35RAPC4BH3, is shown in Figure 2. For applications that require an SPDIF interface in the stereo headphone jack, use a Foxconn 2F1138-TJ-TR. As with any power amplifier, proper supply bypassing is critical for low noise performance and high power supply rejection. Applications that employ a 5V regulator typically use a 10µF in parallel with a 0.1µF filter capacitors to stabilize the regulator’s output, reduce noise on the supply line, and improve the supply’s transient response. However, their presence does not eliminate the need for a local 1.0µF tantalum bypass capacitance connected between the LM4854’s supply pins and ground. Do not substitute a ceramic capacitor for the tantalum. Doing so may cause oscillation. Keep the length of leads and traces that connect capacitors between the LM4854’s power supply pin and ground as short as possible. Connecting a 1µF capacitor, CB, between the BYPASS pin and ground improves the internal bias voltage’s stability and improves the amplifier’s PSRR. The PSRR improvements increase as the bypass pin capacitor value increases. Too large, however, increases turn-on time and can compromise the amplifier’s click and pop performance. The selection of bypass capacitor values, especially CB, depends on desired PSRR requirements, click and pop performance (as explained in the section, Proper Selection of External Components), system cost, and size constraints. STANDBY The LM4854 features a low-power, fast turn-on standby mode. Applying a logic-low to the STANDBY pin act actives the standby mode. When this mode is active, the power supply current decreases to a nominal value of 30µA and the amplifier outputs are muted. Fast turn-on is assured because all bias points remain at the same voltage as when the part is in fully active operation. The LM4854 returns to fully active operation in 100µs (typ) after the input voltage on the STANDBY pin switches from a logic low to a logic high. MICRO-POWER SHUTDOWN The LM4854 features an active-low micro-power shutdown mode. When active, the LM4854’s micro-power shutdown feature turns off the amplifier’s bias circuitry, reducing the supply current. The logic threshold is typically VDD/2. The low 0.1µA typical shutdown current is achieved by applying a voltage to the SHUTDOWN pin that is as near to GND as possible. A voltage that is greater than GND may increase the shutdown current. 21 www.national.com LM4854 Application Information LM4854 Application Information (Continued) 200382E8 FIGURE 4. The PCDN042 provides additional ESD protection beyond the 8000V shown in the Absolute Maximum Ratings for the AMP2 output 20038212 FIGURE 3. Headphone Circuit SELECTING EXTERNAL COMPONENTS Input Capacitor Value Selection Figure 4 shows an optional resistor connected between the amplifier output that drives the headphone jack sleeve and ground. This resistor provides a ground path that supressed power supply hum. This hum may occur in applications such as notebook computers in a shutdown condition and connected to an external powered speaker. The resistor’s 100Ω value is a suggested starting point. Its final value must be determined based on the tradeoff between the amount of noise suppression that may be needed and minimizing the additional current drawn by the resistor (25mA for a 100Ω resistor and a 5V supply). Amplifying the lowest audio frequencies requires high value input coupling capacitor (Ci in Figure 2). A high value capacitor can be expensive and may compromise space efficiency in portable designs. In many cases, however, the speakers used in portable systems, whether internal or external, have little ability to reproduce signals below 150Hz. Applications using speakers with this limited frequency response reap little improvement by using large input capacitor. The LM4854’s advanced output transient suppression circuitry has eliminated the need to select the input capacitor’s value in relation to the BYPASS capacitor’s value as was necessary in some previous Boomer amplifiers. The value of CI is now strictly determined by the desired low frequency response. As shown in Figure 2, the input resistor (Ri) and the input capacitor (Ci) produce a high pass filter cutoff frequency that is found using Equation (7). Single-Ended Output Power Performance and Measurement Considerations The LM4854 delivers clean, low distortion SE output power into loads that are greater than 10Ω. As an example, output power for 16Ω and 32Ω loads are shown in the Typical Performance Characteristic curves. For loads less than 10Ω, the LM4854 can typically supply 180mW of low distortion power. However, when higher dissipation is desired in loads less than 10Ω, a dramatic increase in THD+N may occur. This is normal operation and does not indicate that proper functionality has ceased. When a jump from moderate to excessively high distortion is seen, simply reducing the output voltage swing will restore the clean, low distortion SE operation. The dramatic jump in distortion for loads less than 10Ω occurs when current limiting circuitry activates. During SE operation, AMP2 (refer to Figure 2) drives the headphone sleeve. An on-board circuit monitors this amplifier’s output current. The sudden increase in THD+N is caused by the current limit circuitry forcing AMP2 into a high-impedance output mode. When this occurs, the output waveform has discontinuities that produce large amounts of distortion. It has been observed that as the output power is steadily increased, the distortion may jump from 5% to greater than 35%. Indeed, 10% THD+N may not actually be achievable. fc = 1 / (2πRiCi) As an example when using a speaker with a low frequency limit of 150Hz, Ci, using Equation (7) is 0.063µF. The 1.0µF Ci shown in Figure 2 allows the LM4854 to drive high efficiency, full range speaker whose response extends below 30Hz. Bypass Capacitor Value Selection Besides minimizing the input capacitor size, careful consideration should be paid to value of CB, the capacitor connected to the BYPASS pin. Since CB determines how fast the LM4854 settles to quiescent operation, its value is critical when minimizing turn-on pops. The slower the LM4854’s outputs ramp to their quiescent DC voltage (nominally VDD/ 2), the smaller the turn-on pop. Choosing CB equal to 1.0µF along with a small value of Ci (in the range of 0.1µF to 0.39µF), produces a click-less and pop-less shutdown function. As discussed above, choosing Ci no larger than necessary for the desired bandwidth helps minimize clicks and pops. CB’s value should be in the range of 5 times to 7 times the value of Ci. This ensures that output transients are eliminated when power is first applied or the LM4854 resumes operation after shutdown. ESD Protection As stated in the Absolute Maximum Ratings, the AMP2 output pin has a maximum ESD susceptibility rating of 8000V. For higher ESD voltages, the addition of a PCDN042 dual transil (from California Micro Devices), as shown in Figure 4, will provide additional protection. www.national.com (7) 22 LM4854 Application Information (Continued) OPTIMIZING CLICK AND POP REDUCTION PERFORMANCE (8) The LM4854 contains circuitry that eliminates turn-on and shutdown transients ("clicks and pops") and transients that could occur when switching between BTL speakers and single-ended headphones. For this discussion, turn-on refers to either applying the power supply voltage or when the micro-power shutdown mode is deactivated. As the VDD/2 voltage present at the BYPASS pin ramps to its final value, the LM4854’s internal amplifiers are configured as unity gain buffers and are disconnected from the L-OUT, BTL-OUT, and R-OUT pins. An internal current source charges the capacitor connected between the BYPASS pin and GND in a controlled, linear manner. Ideally, the input and outputs track the voltage applied to the BYPASS pin. The gain of the internal amplifiers remains unity until the voltage on the bypass pin reaches VDD/2. Once the voltage on the bypass pin is stable and after a fixed nominal delay of 120ms, the device becomes fully operational and the amplifier outputs are reconnected to their respective output pins. Although the BYPASS pin current cannot be modified, changing the size of CB alters the device’s turn-on time. There is a linear relationship between the size of CB and the turn-on time. Here are some typical turn-on times for various values of CB: CB (µF) TON (ms) 0.01 120 0.1 130 0.22 140 0.47 160 1.0 200 2.2 300 VDD = VOUTPEAK + VODTOP + VODBOT The Output Power vs. Supply Voltage graph for an 8Ω load indicates a minimum supply voltage of 4.6V. The commonly used 5V supply voltage easily meets this. The additional voltage creates the benefit of headroom, allowing the LM4854 to produce peak output power in excess of 1W without clipping or other audible distortion. The choice of supply voltage must also not create a situation that violates of maximum power dissipation as explained above in the Power Dissipation section. After satisfying the LM4854’s power dissipation requirements, the minimum differential gain needed to achieve 1W dissipation in an 8Ω load is found using Equation (10). (10) Thus, a minimum gain of 2.83 allows the LM4854’s to reach full output swing and maintain low noise and THD+N performance. For this example, let AVD = 3. The amplifier’s overall gain is set using the input (Ri) and feedback (Rf) resistors. With the desired input impedance set at 20kΩ, the feedback resistor is found using Equation (11). Rf / Ri = AVD / 2 (11) The value of Rf is 30kΩ. The nominal output power is 1.13W. TThe last step in this design example is setting the amplifier’s -3dB frequency bandwidth. To achieve the desired ± 0.25dB pass band magnitude variation limit, the low frequency response must extend to at least one-fifth the lower bandwidth limit and the high frequency response must extend to at least five times the upper bandwidth limit. The gain variation for both response limits is 0.17dB, well within the ± 0.25dB-desired limit. The results are an (12) fL = 100Hz / 5 = 20Hz In order eliminate "clicks and pops", all capacitors must be discharged before turn-on. Rapidly switching VDD may not allow the capacitors to fully discharge, which may cause "clicks and pops". AUDIO POWER AMPLIFIER DESIGN Audio Amplifier Design: Driving 1W into an 8Ω Load The following are the desired operational parameters: 1WRMS • Power Output: 8Ω • Load Impedance 1VRMS • Input Level: • Input Impedance: • Bandwidth: (9) and an fL = 20kHz x 5 = 100kHz 20kΩ 100Hz - 20kHz ± 0.25dB (13) As mentioned in the SELECTING EXTERNAL COMPONENTS section, Ri and Ci create a highpass filter that sets the amplifier’s lower bandpass frequency limit. Find the coupling capacitor’s value using Equation (14). The design begins by specifying the minimum supply voltage necessary to obtain the specified output power. One way to find the minimum supply voltage is to use the Output Power vs Supply Voltage curve in the Typical Performance Characteristics section. Another way, using Equation (8), is to calculate the peak output voltage necessary to achieve the desired output power for a given load impedance. To account for the amplifier’s dropout voltage, two additional voltages, based on the Dropout Voltage vs Supply Voltage in the Typical Performance Characteristics curves, must be added to the result obtained by Equation (8). The result is Equation (9). Ci = 1 / (2πRifL) The result is 1 / ( 2π x 20kΩ x 20Hz) = 0.397µF (14) (15) Use a 0.39µF capacitor, the closest standard value. 23 www.national.com LM4854 Application Information through 12 show the recommended two-layer PC board layout that is optimized for the TSSOP-packaged LM4854 and associated external components. Figures 13 through 17 show the recommended four-layer PC board layout that is optimized for the LLP-packaged LM4854 and associate external components. (Continued) The product of the desired high frequency cutoff (100kHz in this example) and the differential gain AVD, determines the upper passband response limit. With AVD = 3 and fH = 100kHz, the closed-loop gain bandwidth product (GBWP) is 300kHz. This is less than the LM4854’s 3.5MHz GBWP. With this margin, the amplifier can be used in designs that require more differential gain while avoiding performance restricting bandwidth limitations. These circuits are designed for use with an external 5V supply and 8Ω(min) speakers.These circuit boards are easy to use. Apply 5V and ground to the board’s VDD and GND pads, respectively. Connect a speaker between the board’s L-OUT and BTL-OUT or headphones to the headphone jack (L-OUT and R-OUT outputs). RECOMMENDED PRINTED CIRCUIT BOARD LAYOUT Figures 5 through 9 show the recommended four-layer PC board layout that is optimized for the micro SMD-packaged LM4854 and associated external components. Figures 10 Demonstration Board Layout 20038221 20038223 FIGURE 5. Recommended microSMD PC Board Layout: Component-Side SilkScreen FIGURE 7. Recommended microSMD PC Board Layout: Upper Inner-Layer Layout 20038222 20038224 FIGURE 6. Recommended microSMD PC Board Layout: Component-Side Layout www.national.com FIGURE 8. Recommended microSMD PC Board Layout: Lower Inner-Layout Layer 24 LM4854 Demonstration Board Layout (Continued) 20038228 FIGURE 12. Recommended MT PC Board Layout: Bottom-Side Layout 20038225 FIGURE 9. Recommended MM PC Board Layout: Bottom_Side Layout 20038229 FIGURE 13. Recommended LD PC Board Layout: Component-Side SilkScreen 20038226 FIGURE 10. Recommended MT PC Board Layout: Component-Side SilkScreen 20038230 FIGURE 14. Recommended LD PC Board Layout: Component-Side Layout 20038227 FIGURE 11. Recommended MT PC Board Layout: Component-Side Layout 25 www.national.com LM4854 Demonstration Board Layout (Continued) 20038231 FIGURE 15. Recommended LD PC Board Layout: Upper Inner-Layer Layout 20038232 FIGURE 16. Recommended LD PC Board Layout: Lower Inner-Layer Layout 20038233 FIGURE 17. Recommended LD PC Board Layout: Bottom-Side Layout www.national.com 26 LM4854 Physical Dimensions inches (millimeters) unless otherwise noted TSSOP Package Order Number LM4854MT NS Package Number MTC14 27 www.national.com LM4854 Physical Dimensions inches (millimeters) unless otherwise noted (Continued) 14-Lead LLP Package Order Number LM4854LD NS Package Number LDA14A www.national.com 28 LM4854 1.9W Monaural, 85mW Stereo Headphone Audio Amplifier Physical Dimensions inches (millimeters) unless otherwise noted (Continued) 12-Bump micro SMD Package Order Number LM4854IBL, LM4854IBLX NS Package Number BLA12BAB X1 = 1.539 ± 0.03 X2 = 1.996 ± 0.03 X3 = 0.945 ± 0.10 LIFE SUPPORT POLICY NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT AND GENERAL COUNSEL OF NATIONAL SEMICONDUCTOR CORPORATION. As used herein: 1. Life support devices or systems are devices or systems which, (a) are intended for surgical implant into the body, or (b) support or sustain life, and whose failure to perform when properly used in accordance with instructions for use provided in the labeling, can be reasonably expected to result in a significant injury to the user. National Semiconductor Americas Customer Support Center Email: [email protected]om Tel: 1-800-272-9959 www.national.com National Semiconductor Europe Customer Support Center Fax: +49 (0) 180-530 85 86 Email: [email protected] Deutsch Tel: +49 (0) 69 9508 6208 English Tel: +44 (0) 870 24 0 2171 Français Tel: +33 (0) 1 41 91 8790 2. A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness. National Semiconductor Asia Pacific Customer Support Center Fax: +65-6250 4466 Email: [email protected] Tel: +65-6254 4466 National Semiconductor Japan Customer Support Center Fax: 81-3-5639-7507 Email: [email protected] Tel: 81-3-5639-7560 National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications.