ETC AN-18

®
TOPSwitch Flyback
Transformer Construction
Guide
®
Application Note AN-18
Introduction
Ferrite Core Manufacturer’s Catalogs
This application note is a design and construction guide for
margin wound or triple insulated wire wound flyback
transformers suitable for use with TOPSwitch. Margin wound
and triple insulated wire transformer designs are derived in
Appendix B for a 12 V, 15 W universal input power supply with
secondary regulation, using the step-by-step procedure
developed in application note AN-16. It is assumed that the
reader is already familiar with TOPSwitch and the fundamental
principles of flyback power supplies. This information can be
found in the TOPSwitch data sheets, and application notes
AN-14 and AN-16. More details on flyback transformer theory
and design can be found in AN-17.
Ferrite core manufacturers publish catalogs supplying core
dimensions and electrical characteristics used in transformer
design. Some manufacturers also provide additional engineering
information for the more popular core sizes, such as AL vs. gap
and core loss curves. The catalogs for the manufacturers listed
in Appendix A supply basic electrical data for common US,
Asian, and European core types. For core sizes common to
several manufacturers, the electrical characteristics given by
one core manufacturer can be used for a core of the same
physical dimensions from another manufacturer.
Required Reference Materials:
Bobbin manufacturer's catalogs are used to provide mechanical
dimensions for transformer design. The bobbin manufacturers
in Appendix A offer a wide variety of bobbin styles for standard
ferrite core sizes in materials suitable for high volume production.
Many ferrite core manufacturers also carry bobbins for their
standard core sizes.
This application note, AN-16, and AN-17 provide the necessary
techniques for design and construction of flyback transformers
for TOPSwitch applications. In addition, the following reference
materials are required to provide dimensional and electrical
data for cores, bobbins, and wire. Sources for these reference
materials are listed in Appendix A.
Bobbin Manufacturer’s Catalogs
PRIMARY
SECONDARY
BIAS
PI-1907-061896
Figure 1. Typical Flyback Transformer Using EE Core.
July 1996
AN-18
Wire Table
Insulating Materials
A wire table provides dimensional and electrical characteristics
for magnet wire, and is used to select appropriate wire sizes for
transformer design. There are three major wire sizing systems:
AWG, SWG and metric. All wire sizes used in this application
note are based on AWG sizing. A wire table is provided in
Appendix A with data on AWG wire sizes from 18 gauge
through 44 gauge. SWG and metric equivalents to AWG wire
sizes are also shown. A wire table is also available in
reference 5. Wire tables can be obtained from some of the
magnet wire manufacturers listed in Appendix A.
A common insulating material used in transformers is polyester
or Mylar, available in sheet or tape form. This material is also
manufactured as an adhesive tape that is particularly useful in
transformer construction. US manufacturers of this tape
include 3M, Tesa, and CHR. For creepage margins in
transformers, it is desirable to use a thick tape so that the
required build for a margin can be achieved using relatively few
layers. Several manufacturers make a polyester film/mat tape
that is useful for this application.
Magnet Wire
Transformer Construction Materials
The following paragraphs describe the basic materials needed
to construct switching power supply transformers.
Ferrite Cores
Appropriate ferrite materials for 100KHz flyback transformers
are TDK PC40, Philips 3C85, Siemens N67, Thomson B2,
Tokin 2500 or other similar materials. A wide variety of core
shapes are available. E cores are the best choice for transformer
cores for reasons of low cost, wide availability, and lower
leakage inductance. Other core shapes and styles such as the
ETD, EER and EI are also usable. A chart of suitable ferrite core
types for various power levels and transformer construction
types can be found in Appendix A.
Bobbins
Bobbins for off-line flyback transformers should be chosen
with regard to the safety creepage distances required by the
applicable safety regulations. Particular areas of consideration
are the total creepage distance from primary pins to secondary
pins through the core, and the creepage distance from primary
pins to the secondary winding area. With some bobbin styles,
extra insulation may be necessary to meet the creepage
requirements. Bobbins should preferably be made from
thermosetting materials such as phenolic resin in order to
withstand soldering temperatures without deformation.
Polybutylene or polyethylene terphthalate (PBT, PET) and
polyphenylene sulfide (PPS) are also acceptable materials,
though more sensitive to high temperatures than phenolic
resins. Nylon should be avoided if possible, as it melts easily
at the temperatures required to effectively terminate the
transformer windings to the pins on the bobbin. If Nylon
bobbins are used, they should be made with glass reinforced
resin with a temperature rating of 130˚C.
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Some typical domestic manufacturers of magnet wire are
Belden, Phelps Dodge, and Rea. The preferred insulation for
magnet wire is a nylon/polyurethane coating. This coating
burns off in contact with molten solder, allowing the transformer
to be terminated by dip tinning in a solder pot. This type of
insulated magnet wire is available from almost all manufacturers
under various trade names: Solderon, Nyleze, Beldsol, etc. The
insulating coating should be “heavy” or “double” to better
withstand the stress of handling and the winding process.
Ordinary enameled wire or polyimide wire insulation should
not be used, as these types of insulation must be stripped
mechanically or with chemical stripping agents in order to
terminate the wire to the transformer pins.
Triple Insulated Wire
Triple insulated wire can be used to simplify and reduce the size
of transformers where safety isolation is required. The type of
triple insulated wire useful for transformer construction consists
of a solid wire core with three distinct and separable layers of
insulation. Three manufacturers of triple insulated wire are
listed in Appendix A.
Sleeving
Insulating tubing is used to insulate the start and finish leads of
windings in a margin wound transformer. The tubing should be
recognized by the applicable safety agencies, with a minimum
wall thickness of 0.4 mm to meet thickness requirements for
reinforced insulation. The tubing should also be heat resistant,
so that it does not melt when exposed to the temperatures
required to solder the transformer lead wires to the pins on the
bobbin. Materials commonly used for sleeving include Teflon
tubing or polyolefin heat shrink tubing.
AN-18
Varnish
Many transformer manufacturers impregnate their finished
transformers with a suitable electrical varnish. By filling the
voids inside the transformer, the varnish improves heat transfer
from the windings to the environment, and enhances the voltage
withstand capability of the transformer insulation. It also locks
the core and windings in place to help prevent audible noise and
protects the finished transformer from moisture. One
disadvantage of varnish impregnation is that it adds a slow extra
step to transformer construction. Some manufacturers of
electrical varnishes are listed in Appendix A.
SECONDARY
REINFORCED
INSULATION
BIAS
MARGIN
PRIMARY
(Z WOUND)
(a) MARGIN WINDING
ALTERNATE
PRIMARY
WINDING
Transformer Construction Methods
In order to meet international safety regulations, a transformer
for use in an off-line power supply must have adequate insulation
between the primary and secondary windings. For transformers
using standard cores and bobbins, there are two basic transformer
insulation methods: margin wound construction and triple
insulated wire construction.
(b) C WINDING
PI-1828-041696
Figure 2. Margin Wound Transformer Cross Section.
Margin Wound Construction
International safety regulations require the following for
transformers using magnet wire:
• Reinforced insulation between primary and secondary
windings.
• Guaranteed creepage distance between primary and
secondary windings where reinforced insulation is not
used.
A cross-section of a typical margin wound transformer designed
to meet these requirements is shown in Figure 2.
The creepage distance required between primary and secondary
windings by safety regulations is typically 2.5 to 3 mm for
supplies with 115 VAC input, and 5 to 6 mm for 230 VAC or
universal input supplies. This creepage distance is maintained
by physical barriers called margins. In most practical transformer
designs, these margins are built up on each side of the bobbin
using electrical tape, with the windings placed between them as
shown in Figure 2. The total minimum creepage distance
between primary and secondary windings is equal to twice the
margin width M, as shown in Figure 3. This sets the minimum
margin width at one half the required creepage distance, or 1.25
to 1.5 mm for 115 VAC input supplies, and 2.5 to 3 mm for 230
VAC or universal input supplies.
The necessary reinforced insulation between primary and
secondary windings is provided using three layers of electrical
tape, any two of which can withstand the full safety test voltage,
which is 2000 VRMS for 115 VAC input supplies, and 3000
CREEPAGE
DISTANCE
M
M
SECONDARY
WINDING
}
}
REINFORCED
INSULATION
PRIMARY AND
BIAS WINDINGS
PI-1867-053196
Figure 3. Interwinding Creepage Distance for Margin Wound
Transformers.
VRMS for 230 VAC input supplies. The tape layers should
cover the entire width of the bobbin from flange to flange, as
shown in Figure 2. A polyester film tape with a base film
thickness of at least 0.025mm is sufficient for use in this
application. The secondary windings are effectively "boxed in"
by the margins and the reinforced insulation, isolating them
from the primary. Since the start and finish leads of each
winding pass through the margins to reach the transformer pins,
they may require extra insulation to maintain the integrity of the
margin insulation. Insulating tubing with a wall thickness of at
least 0.4 mm is used to cover all start and finish leads of a margin
wound transformer to meet this requirement. This insulation
should extend from the transformer pin to inside of the margin
barrier, as shown in Figure 4.
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3
AN-18
Use of margin winding techniques allows the construction of a
transformer with ordinary magnet wire and readily available
insulating materials. However, the necessity for margins, start
and finish sleeving, and reinforced insulation results in a
complex and labor-intensive transformer. The margins waste
space inside the transformer, making it necessary to use a much
larger core and bobbin size than could be used if the margins
were not required. One alternative to margin wound construction
is the use of triple insulated wire.
Transformer Construction Techniques
Figure 7 shows four styles of transformer construction for both
primary and secondary regulated flyback power supplies, using
margin wound and triple insulated wire techniques. These four
styles are sufficient for almost all switching power supply
requirements. The following paragraphs describe the
considerations involved in selecting a particular construction
style for an application, as well as additional considerations for
reducing EMI, stray capacitance, and leakage inductance.
Triple Insulated Wire Construction
Winding Sequence
Triple insulated wire (Figure 5) has three separate layers of
insulation, any two of which can withstand a safety hipot test
voltage of 3000 VRMS. Triple insulated wire thus satisfies the
requirements for a reinforced insulation per VDE/IEC
regulations, and can be used to construct a transformer without
the creepage margins required in a design using conventional
magnet wire. A cross-section of a triple insulated wire
transformer design is shown in Figure 6. The triple insulated
wire design uses magnet wire for primary and bias windings,
with a triple insulated secondary. This is generally the most
cost effective and space-efficient way to utilize the benefits of
triple insulated wire, as it is larger in diameter and more costly
Figure 7 shows optimum winding sequencing for transformers
for primary and secondary regulation schemes using margin
wound and triple insulated wire construction. The factors
involved in determining optimum winding sequencing and
insulation placement are discussed below.
Solid Wire Core
3 Separate
Insulation
Layers
Margin
Margin
PI-1795-030895
Insulating
Sleeving
Figure 5. Triple Insulated Wire.
PI-1810-032896
Figure 4. Use of Insulating Sleeving.
than the equivalent size of magnet wire. The secondary winding
will usually require fewer turns of larger diameter wire than the
primary, so the cost and space impact of the triple insulated wire
is minimized. In a triple insulated wire design, the full width of
the transformer bobbin is usable, due to the reinforced insulation
provided by the triple insulated wire. A transformer using a
triple insulated wire design will generally be 1/2 to 2/3 of the
size of a transformer of the same power capability using a
magnet wire design. Leakage inductance varies inversely with
the width of the transformer windings, so leakage inductance
for a triple insulated wire transformer will usually be less than
that of an equivalent margin wound design, due to more
efficient use of space on the transformer bobbin.
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SECONDARY
(INSULATED)
BIAS
(ALTERNATE
LOCATION)
BIAS (MAGNET
WIRE)
PRIMARY
(MAGNET
WIRE)
PI-1678-091395
Figure 6. Triple Insulated Wire Wound Transformer Cross Section.
AN-18
PRIMARY FINISH LEAD
(WITH SLEEVING)
PRIMARY FINISH LEAD
(WITH SLEEVING)
PIN
PIN
REINFORCED
INSULATION
SECONDARY
PRIMARY BIAS
PRIMARY FINISH
PRIMARY START
BASIC
INSULATION
PRIMARY BIAS
REINFORCED
INSULATION
SECONDARY
PRIMARY FINISH
PRIMARY START
BASIC
INSULATION
MARGIN (4x)
MARGIN (6x)
PI-1800-030896
PI-1799-030896
Figure 7A. Margin Wound Secondary Regulated Transformer.
Figure 7B. Margin Wound Primary Regulated Transformer.
PRIMARY FINISH LEAD
(WITHOUT SLEEVING)
PRIMARY FINISH LEAD
(WITHOUT SLEEVING)
REINFORCED
INSULATION
BASIC
INSULATION
PIN
TRIPLE INSULATED
SECONDARY
PRIMARY BIAS
PRIMARY FINISH
PRIMARY START
PI-1801-030896
REINFORCED
INSULATION
BASIC
INSULATION
PIN
PRIMARY BIAS
TRIPLE INSULATED
SECONDARY
PRIMARY FINISH
PRIMARY START
PI-1802-030896
Figure 7C. Triple Insulated Secondary Regulated Transformer.
Figure 7D. Triple Insulated Primary Regulated Transformer.
Primary Winding
In all the transformer construction styles depicted in Figure 7,
the primary winding (or a portion of it) is always the first or
innermost winding on the bobbin. This keeps the mean length
of wire per turn as short as possible, reducing the primary
winding parasitic capacitance. Also, if the primary winding is
the innermost winding on the transformer, it will be shielded by
the other transformer windings, helping to reduce noise coupling
from the primary winding to adjacent components. The driven
end of the primary winding (the end connected to the TOPSwitch
drain) should be at the start of the winding. This allows the half
of the primary winding with the largest voltage excursion to be
shielded by other windings or by the second half of the primary
winding, reducing EMI coupled from the primary side of the
transformer to other parts of the supply. The primary winding
should be designed for two winding layers or less. This
minimizes the primary winding capacitance and the leakage
inductance of the transformer. Adding a layer of tape between
primary layers can reduce the primary winding capacitance by
a factor of four. This is especially important for low power
applications using TOP200 and TOP210 to prevent spurious
triggering of the TOPSwitch current limit by the initial current
spike generated when TOPSwitch turns on and discharges the
transformer winding capacitance.
Primary Bias Winding
The optimum placement of the primary bias winding will
depend on whether the power supply uses a primary referenced
or secondary referenced regulation scheme. If the power supply
is regulated from the secondary side, the bias winding should be
placed between the primary and secondary, as shown in Figures
7A and 7 C. When placed between the primary and secondary,
the bias winding acts as an EMI shield connected to the primary
return, reducing the conducted EMI generated by the power
supply. In margin wound designs for secondary regulated
supplies, placing the primary bias winding between the primary
and secondary also minimizes the number of margins and
reinforced insulation layers in the transformer.
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5
AN-18
For power supplies using a primary regulation scheme, the bias
winding should be the outermost winding on the transformer, as
shown in Figures 7B and 7D. This maximizes the coupling of
the primary bias winding with the secondary, and minimizes
coupling to the primary, improving the output regulation of the
supply in two ways. With better coupling to the secondary, the
bias winding responds more accurately to output voltage changes,
improving regulation. Also, the resultant poor coupling of the
bias winding to the primary helps to improve regulation by
reducing peak charging of the bias output due to the primary
leakage spike. If the bias winding is only loosely coupled to the
primary, the leakage spike can be filtered by using a small
resistor in series with the primary bias winding, improving the
load regulation of the supply. This is discussed in greater detail
in design note DN-8.
The primary bias winding should ideally form one complete
layer across the width of the bobbin. If the bias winding has
relatively few turns, this can be accomplished by increasing the
size of the wire used in the bias winding, or using multiple
parallel strands of wire. Increasing the fill factor of the bias
winding in this manner improves the shielding capability of the
winding in the case of the secondary regulated supply, and
improves the secondary to bias coupling in the case of the
primary regulated supply.
Secondary Windings
If a transformer has multiple secondary windings, the highest
power secondary should be the closest to the primary of the
transformer, in order to reduce leakage inductance. If a secondary
winding has relatively few turns, the turns should be spaced so
that they traverse the entire width of the winding area, for
improved coupling. Using multiple parallel strands of wire will
also help to increase the fill factor and coupling for secondaries
with few turns. For multiple output secondary regulated supplies,
auxiliary outputs with tight regulation requirements should be
wound directly on top of the regulated secondary to improve
coupling.
Multiple Output Winding Techniques
Instead of providing separate windings for each output in a
multiple output supply, a common technique for winding
multiple output secondaries with the same polarity sharing a
common return is to stack the secondaries, as shown in Figure
8. This arrangement will improve the load regulation of the
auxiliary outputs in a multiple output supply, and reduce the
total number of secondary turns. The windings for the lowest
voltage output provide the return and part of the winding turns
for the next higher voltage output. The turns of both the lowest
output and the next higher output provide turns for succeeding
outputs. For the two output stacked winding example shown in
Figure 8, the relation between output voltages V1 and V2 is
given below:
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
 N + N2  
V2 =  (V1 + VD1 ) ×  1
 − VD 2
 N1  

VD1 and VD2 are the rectifier forward voltage drops for D1 and
D2, respectively. N 1 and N2 are the winding turns for the V1 and
V2 outputs.
The wire for each output must be sized to accommodate its
output current plus the sum of the output currents of all the
outputs stacked on top of it.
Insulation Requirements
Figure 7, in addition to showing optimum winding sequencing,
also shows placement of basic and reinforced insulation to meet
safety requirements and to improve consistency of the finished
transformer.
For the margin wound secondary regulated transformer
(Figure 7A), basic insulation (1 layer of electrical tape) is used
between primary layers and between the primary and the bias
winding. A layer of tape can also be useful between secondary
windings to provide a smooth winding surface from one winding
layer to the next. Reinforced insulation (three layers of tape) is
used between the primary bias winding and the secondary. A
three layer finish wrap completes the reinforced insulation for
the secondary. There are four margins in this transformer: two
for the primary and bias windings, and two for the secondary
windings. Insulating sleeving is used on the start and finish
leads of all windings. In Figures 7A and 7B sleeving is shown
only on the primary finish lead for purposes of clarity. In
practice, sleeving is used on the start and finish leads of all
windings. The sleeving should extend as shown from the inside
edge of the margin to the transformer pin.
For the margin wound primary regulated transformer
(Figure 7B), basic insulation is used between primary winding
layers. As in the secondary regulated transformer, a layer of
tape can be used between secondary windings to smooth the
winding surface. Reinforced insulation is required between the
primary and secondary windings, between the secondary and
primary bias windings, and as a finish wrap on top of the
primary bias winding. In this transformer, there are three pairs
of margins: one pair for the primary winding, one pair for the
secondary winding, and one pair for the bias winding. Start and
finish of each winding are sleeved as described above.
For the triple insulated secondary regulated transformer
(Figure 7C), basic insulation is used between primary layers,
between primary and bias, and between bias and secondary.
The insulation reduces the capacitance of the primary winding
AN-18
D2
V2
I2
V+
N2
I2
NP
TOPSwitch
Drain
D1
I1
V1
N1
I1+I2
COMMON
RETURN
PI-1798-030896
Figure 8. Stacked Secondary Windings for Multiple Outputs.
and smooths the surface between windings. The finish wrap of
three layers is more for cosmetic reasons than for safety. There
are no margins and no sleeving.
In the triple insulated primary regulated transformer
(Figure 7D), basic insulation is used between primary layers,
between primary and secondary, and between secondary and
bias. A three layer outer wrap is required on the outside for
reinforced insulation. Again, no margins or sleeving are
required.
Reducing Leakage Inductance
The winding order in a transformer has a large effect on the
leakage inductance. Transformer windings should be arranged
in concentric fashion for minimum leakage inductance. Offset
or split bobbin construction (shown in Figure 9) should be
avoided, as these techniques will result in high leakage inductance
and unacceptable primary clamp circuit dissipation.
In a multiple output transformer, the secondary with the highest
output power should be placed closest to the primary for the best
coupling and lowest leakage. For higher power applications
(40 watts and above), a split primary “sandwich” construction
is recommended to minimize leakage inductance. Using a split
primary will in general cut the leakage inductance to half that of
a transformer with a single primary winding. Split primary
construction for secondary regulated transformers is shown for
the margin wound and triple insulated case in Figures 10A and
10B. A split winding construction is not recommended for
primary regulated designs, as it will result in poor load regulation.
High power secondary windings consisting of only a few turns
should be spaced across the width of the bobbin window instead
of being bunched together, in order to maximize coupling to the
primary. Using multiple parallel strands of wire is an additional
technique of increasing the fill factor and coupling of a winding
with few turns. In such cases, the wire size may be determined
more by the requirement for a good fill factor rather than the
RMS current rating of the wire. Where cost permits, using foil
windings is also a good way of increasing coupling, although
this method is usually practical only for low voltage, high
current secondary windings.
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7
AN-18
MARGIN
SECONDARY
BIAS
BIAS
MARGIN PRIMARY
PRIMARY
SECONDARY
OFFSET WINDING CONSTRUCTION
(NOT RECOMMENDED)
SPLIT BOBBIN CONSTRUCTION
(NOT RECOMMENDED)
PI-1829-041696
Figure 9. Offset and Split Bobbin Construction Techniques (Not Recommended).
EMI Reduction Techniques
The following transformer construction techniques help to
reduce EMI:
• Make the primary winding the innermost winding on the
bobbin.
• The start of the primary winding should be connected to the
TOPSwitch drain.
• For a secondary regulated transformer design, place the
bias winding between primary and secondary to act as a
shield.
Additional EMI/RFI reduction techniques include shielding
between primary and secondary windings, and the addition of
a “flux band” to reduce the stray field around the transformer.
Shields are placed between the primary and secondary of a
transformer to reduce the capacitive coupling of common mode
noise between primary and secondary. The shield can be
referenced either to the primary high voltage supply or to the
primary return. Typical shielded transformer constructions are
shown in Figure 11. The most economical form of shield is a
wire shield. This type of shield can be added to the transformer
with very few extra steps, since it consists of a winding
traversing the full width of the bobbin. One end of the shield
winding is terminated to the primary return or primary V+
supply, while the other end of the winding is left floating,
insulated with tape, and buried inside the transformer instead of
being terminated to a pin. The wire size used for a wire shield
is a compromise between a large size to minimize the number
of shield turns, and a relatively small wire size for ease of
termination. 24-27 AWG wire is a reasonable compromise for
small to medium size transformers.
In some cases, the stray magnetic field around a switching
power supply transformer can interfere with adjacent circuitry
and contribute to EMI. To reduce this stray field, a copper “flux
PRIMARY FINISH LEAD
(WITH SLEEVING)
PIN
REINFORCED
INSULATION
BASIC
INSULATION
PRIMARY SECOND 1/2 FINISH
PRIMARY SECOND 1/2 START
SECONDARY
PRIMARY BIAS
SLEEVING
PRIMARY BIAS
PRIMARY FIRST 1/2 FINISH
MARGIN (6x)
PRIMARY FIRST 1/2 START
PI-1803-030896
Figure 10A. Margin Wound Secondary Regulated Transformer
with Split Primary.
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REINFORCED
INSULATION
PRIMARY SECOND
1/2 FINISH
PRIMARY
SECOND 1/2 START
PIN
PRIMARY FINISH LEAD
(WITHOUT SLEEVING)
TRIPLE INSULATED
SECONDARY
BASIC
INSULATION
PRIMARY FIRST 1/2 FINISH
PRIMARY FIRST 1/2 START
PI-1804-030896
Figure 10B. Triple Insulated Secondary Regulated Transformer
with Split Primary.
AN-18
TRANSFORMER SHIELD PLACEMENT
Insulated Wire Transformer
SECONDARY
BIAS
SHIELD
PRIMARY
Margin Wound Transformer
}
SECONDARY
TAPE
MARGINS
SHIELD
BIAS
PRIMARY
PI-1814-032796
Figure 11. Transformer Shield Placement.
band” can be added around the outside of the transformer, as
shown in Figure 12. The “flux band” acts as a shorted turn for
stray flux outside the magnetic circuit formed by the transformer
windings and core. Opposing currents are induced in the flux
band by the stray fields, partially canceling their influence. If
necessary, the flux band can also be connected to primary return
to help reduce electrostatically coupled interference. If a flux
band is used, care must be taken to make sure that there is
sufficient total creepage distance from the primary pins to the
secondary pins through the flux band. Refer to AN-15 for more
information on EMI reduction techniques.
Transformer Construction
Two transformer design and construction examples are shown
in Appendix B for margin wound and triple insulated
transformers for use with TOPSwitch. The design procedure for
the two examples utilizes computer spreadsheet techniques
described in application notes AN-16 and AN-17. The detailed
step-by-step flyback power supply design procedure for using
the spreadsheet is shown in AN-16, while the spreadsheet itself
is described in detail in AN-17. The paragraphs below describe
the procedures needed to apply the information generated by
the power supply design spreadsheet to a practical transformer
design. These procedures are used to complete the two design
examples in Appendix B. In this application note, two completed
spreadsheet design examples are presented. Information derived
from these spreadsheets is used in the construction examples.
the information required to specify a transformer can be read
directly from the completed spreadsheet. Other parameters
must be calculated using numbers from the spreadsheet and
information from other sources, such as a wire table. The
spreadsheet parameters listed below provide information used
to specify a transformer. The number in parentheses indicates
the cell location in the spreadsheet.
• Core Type (B23)
• Bobbin Physical Winding Width (BW) (B27)
• Safety Margin Width (M) (B28)
• Number of Primary Layers (L) (B29)
• Number of Secondary Turns (NS) (B30)
• Primary Inductance (LP) (D44)
• Primary Number of Turns (NP) (D45)
COPPER
FOIL
STRAP
Spreadsheet Parameters Used for
Transformer Specification
Once a power supply design spreadsheet has been completed
and optimized, information from the spreadsheet can be used to
complete a specification for transformer construction. Much of
PI-1648-111695
Figure 12. Transformer Flux Band.
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9
AN-18
Once the transformer parameters have been determined from a
spreadsheet design, the following steps are required to determine
the remaining information needed for transformer construction:
• Calculate and select wire sizes using spreadsheet
information and wire table
• Pick transformer construction style
• Determine insulating tape sizes
• Determine insulating sleeving size
• Choose method of core gapping
Wire Sizes
Wire sizes for the primary, secondary, and bias windings are
determined from the information provided by the power supply
design spreadsheet. Some extra steps may be necessary to
determine the wire size for a given winding. The wire size
selection process is described below.
Primary Wire Size
The power supply design spreadsheet calculates the insulated
wire diameter for the primary based on the number of primary
turns, the number of winding layers, and the available winding
space on the bobbin. The calculated maximum insulated wire
diameter is shown in cell (D53) of the spreadsheet. The
spreadsheet uses this value to choose an AWG wire size that
comes closest to fitting the bobbin. If the wire size falls between
two standard AWG wire gauges, the spreadsheet will
automatically round down the primary wire size to the next
smaller wire gauge. The resulting primary AWG wire size is
displayed in cell (D56) of the spreadsheet. The spreadsheet
calculates the current capacity of the primary wire (CMA) in
circular mils per ampere and displays the result in cell (D58).
The CMA value should be between 200 to 500 circular mils per
ampere for a practical design. If the CMA is not within these
limits, the design should be adjusted to bring the primary CMA
within limits.
Wire Size vs. Frequency
In some cases, the wire size determined by the spreadsheet will
be too large for use at 100KHz. The wire size that can be
effectively used in a power transformer depends on the operating
frequency. High frequency currents tend to flow close to the
surface of a conductor rather than its interior. This phenomenon
is called the skin effect. The penetration of AC current into a
10
A
7/96
Secondary Wire Size
The minimum secondary bare wire cross-sectional area is
determined by the spreadsheet from the secondary RMS current,
and is sized for the same current capacity (CMA) as the primary
winding. The resulting minimum wire area (in circular mils) is
displayed in cell (C66) of the spreadsheet, and is used by the
spreadsheet to calculate a secondary wire size. If the secondary
wire size falls between two standard AWG sizes, the spreadsheet
will automatically round the wire size up to the next larger
AWG size. The resulting secondary AWG wire size is displayed
in cell (D67) of the spreadsheet. In many cases, the wire size
picked by the spreadsheet will be too large to satisfy the size
requirements for 100 KHz operation described above. In these
cases, it will be necessary to use several parallel strands of
MAXIMUM AWG vs. FREQUENCY
40
PI-1906-061768
Transformer Construction Steps
conductor varies as the square root of the frequency, so for a
higher frequency, currents will flow closer to the surface of the
conductor and leave the interior relatively unutilized. The
result is a higher effective resistance for AC current versus DC
current. To minimize the AC copper losses in a transformer, no
conductor should be used that has a thickness greater than 2
times the skin depth at the operating frequency of the supply. A
graph of usable wire gauge as a function of frequency is shown
in Figure 13. At 100 KHz, the nominal operating frequency of
TOPSwitch, 26 AWG is the largest wire size that allows full
utilization of the cross-section of the wire. High current windings
at 100 KHz should be constructed using several strands of 26
AWG or smaller wire rather one large diameter conductor, in
order to allow full utilization of the conductor. This is usually
more of a concern for selecting the wire size for a secondary
output winding than for a primary winding.
Full
Utilization
35
AWG Wire Gauge
• Bias Winding Turns (NB) (D46)
• Gapped Core Inductance Coefficient (ALG) (C47)
• Primary Wire Gauge (AWG ) (D56)
• Primary Winding Current Capacity (CMA) (D58)
• Secondary Circular Mils (CMS) (C66)
• Secondary RMS Current (ISRMS) (D62)
• Secondary Wire Gauge (AWGS) (D67)
30
Partial
Utilization
25
20
15
104
105
106
Frequency (Hz)
Figure 13. Skin Depth vs. Frequency.
107
AN-18
26 AWG or smaller wire to construct a secondary winding that
satisfies both the CMS requirement and the 100KHz maximum
wire size requirement. The total bare area of the paralleled
secondary conductors should be close to the CMS value calculated
by the spreadsheet in cell (C66). If the total bare area is greater
than or equal to the calculated value, the wire size for the
paralleled secondary winding can be used without further
checking. If the total bare area is less than the calculated value
from cell (C66), the current capacity should be checked to make
sure that it remains within the design limits. The current
capacity of the paralleled wires can be calculated from the
formula:
CMAS =
N × CM
ISRMS
CMAS is the current capacity of the parallel secondary winding
in circular mils per ampere, N is the number of strands in the
secondary winding, CM is the bare area of a single secondary
conductor in circular mils (from the wire table in Appendix A),
and ISRMS is the secondary RMS current from cell (D62) of the
spreadsheet.
Choosing a Transformer Construction Type
The transformer construction types shown in Figures 7 and 10
are optimized for margin wound and triple insulated wire
transformer designs for both secondary and primary regulated
power supply designs. These construction types are suitable for
the majority of TOPSwitch flyback supply applications. These
figures should be used as examples for specifying the order of
the transformer windings and the placement of the margins and
insulating sleeving (if used), and insulating tape. The
construction type is chosen on the basis of the supply regulation
scheme (primary or secondary) and insulation type (margin
wound or triple insulated wire). Applications requiring the
lowest transformer cost but not the smallest possible transformer
size can use a margin wound transformer. Applications requiring
the smallest possible transformer size should use a triple insulated
wire design.
The construction types shown in Figure 10 are low-leakage split
primary designs, and should be used if the output power of the
supply is greater than 40W. These designs can also be used to
increase efficiency for a lower power supply, but will be higher
cost than a design with a one piece primary winding.
Choosing Insulation Tape Width
Bias Winding Design
The wire size for the bias winding will be determined mainly by
space-filling considerations rather than current capacity, as
described in the previous sections on transformer construction.
The wire size of the bias winding should be selected to form as
complete a layer as possible. Usually, it will be necessary to use
a parallel bifilar winding in order to fill the largest possible
space with a manageable wire size. In the Appendix A wire
table, turns per centimeter (TC) values are given for AWG wire
sizes. This data can be used to select a bias winding wire size for
a bifilar winding for a given number of turns and available
bobbin width. The required TC value can be calculated from the
equation:
2 × N B × 10
TC =
BW − (2 × M )
TC is the turns per centimeter capability of the bias winding. NB
is the number of bias turns from cell (D46) of the spreadsheet,
BW is the bobbin physical winding width in mm from cell (B27)
of the spreadsheet, and M is the margin width in mm from cell
(B28). Once the required TC is calculated, a wire size is
selected from the Appendix A wire table with a TC greater than
or equal to the calculated value. The largest recommended wire
size is 24 AWG, for ease of winding and termination. If the wire
size used does not form one complete layer, the winding turns
should be wound evenly across the width of the bobbin winding
area.
For a margin wound transformer construction, three different
insulation tape widths are required. A tape width equal to the
width of the bobbin from flange to flange (BW) is required for
reinforced insulation. This information can be read directly
from cell (B27) of the spreadsheet. A tape width equal to the
width of the bobbin minus the width of the margins is needed for
basic insulation between winding layers and adjacent primary
or secondary windings. This width can be calculated with the
equation:
WTB = BW − (2 × M )
WTB is the width of the basic insulation tape, BW is the width of
the bobbin from cell (B27) of the spreadsheet, and M is the
margin width from cell (B28). The third tape width required is
for the margin layers on each side of the bobbin. The width of
this tape is picked to satisfy applicable safety regulations and
entered in cell (B28). Triple insulated wire transformers require
one size of tape for basic insulation, with a width equal to BW.
Insulating Sleeving
In margin wound transformer designs, insulating sleeving is
required on all winding start and finish leads, so that the primary
to secondary isolation provided by the margins is preserved.
The sleeving should have a wall thickness of at least 0.4 mm.
Sleeving for this purpose can be obtained in sizes equivalent to
AWG wire sizes. Usually one size of sleeving, equal to the
A
7/96
11
AN-18
largest wire size, is sufficient for a transformer design. This size
of sleeving can then be used for all other wire sizes in the
transformer. Sleeving is not required for triple insulated wire
designs.
Transformer Gapping , Primary Inductance Tolerance
In standard practice, transformer cores for flyback transformer
applications are gapped to a specified value of ALG rather than
a precise gap length. The center value of ALG can be read from
cell (C47) of the spreadsheet. ALG is customarily specified to a
tolerance of +/- 5-6%. The gap length shown in cell (D 51) of
the spreadsheet is useful mainly for checking transformer peak
flux density and for determining the practicality of the design,
and should not be used in a transformer specification.
Transformer gaps smaller than 0.051 mm (0.002 in) should be
avoided, as it is difficult to maintain tolerance on this small a
gap. Transformer primary inductance tolerance should be
specified at +/- 10% to +/- 15%. Tighter tolerances offer no
performance advantages, and can be unnecessarily costly.
• Transformer parts list, including:
Core part number and ALG
Bobbin part number
All wire types and sizes used
All insulating tape types and widths
Insulating sleeving type and size (if used)
Varnish type (if used)
• Transformer specifications:
Primary inductance and tolerance
Primary leakage inductance and tolerance (determined
from prototype)
Applicable safety standards, or hipot test voltage and
minimum creepage distances
• Detailed construction drawing and instructions (optional)
Design Summary
For high volume transformer applications, the transformer core
is commonly gapped by grinding down the center leg of one of
the ferrite core halves to introduce a single air gap in the
magnetic path of the core. An alternate technique for small
production runs and prototypes is to use non-conducting spacers
between the core halves. If spacers are chosen rather than
grinding the core center leg, the spacer thickness should be half
the value used for the center leg gap, as the magnetic path is
divided twice by the spacers: once at the core center leg, and
once at the core outer legs.
1) Load Design Spreadsheet with Application Variables and
TOPSwitch Variables per instructions in AN-16.
Completion of Transformer Specification
4) From spreadsheet values and Appendix A wire table,
calculate primary, secondary, and bias wire sizes.
Once the above information has been determined, there is
sufficient information to complete a specification for
construction of the transformer. The specification should contain
the following information:
• Transformer schematic, showing all windings, order of
windings, pin assignments, dots indicating winding starts,
turns of each winding, and wire types and sizes
2) Choose a core from Appendix A, and determine core and
bobbin parameters needed for spreadsheet from
manufacturer’s catalog data. Load these values into
the spreadsheet.
3) Complete spreadsheet per AN-16 procedure and iterate
until all parameters meet recommended design limits.
5) Pick a transformer construction style depending on supply
regulation scheme (primary or secondary) and insulation
type (margin wound or triple insulated).
6) Calculate tape widths needed for transformer insulation.
7) Pick insulation sleeving size (if necessary).
8) Complete transformer specification using spreadsheet
values and information from steps 4-7.
12
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7/96
AN-18
Appendix A
Appendix A contains a wire table (Table 1) and a table of
suggested core sizes (Table 2) for use in the flyback transformer
design and construction procedures described in this document.
Also included is a list of manufacturers for transformer
construction materials. Electrical and mechanical data on the
cores listed in Table 2 can be obtained from the ferrite core
manufacturers listed in this appendix. These manufacturers
also carry a selection of bobbins for their more popular core
sizes. Additional sources for transformer bobbins are also listed
in this appendix.
AWG
SWG
Metric
Wire
Wire
Size
Size
Size
(mm)
cm210 -3
CIR-MIL
Turns/cm
Turns/Inch
18
19
1.00
8.228
1624
9.13
23.2
19
20
0.900
6.531
1289
10.19
25.9
20
21
0.800
5.188
1024
11.37
28.9
0.750
4.116
812.3
12.75
32.4
21
Bare Wire Cross-Sectional
Area (CM)
TC
22
22
0.700
3.243
640.1
14.25
36.2
23
23
0.600
2.588
510.8
15.82
40.2
24
24
0.550
2.047
404.0
17.63
44.8
0.450
1.623
320.4
19.80
50.3
25
26
28
0.400
1.280
252.8
22.12
56.2
27
29
0.350
1.021
201.6
24.44
62.1
28
30
0.320
0.8046
158.8
27.32
69.4
0.280
0.6470
127.7
30.27
76.9
0.250
0.5067
100.0
33.93
86.2
31
0.220
0.4013
79.21
37.48
95.2
32
0.200
0.3242
64.00
41.45
105.3
33
0.180
0.2554
50.41
46.33
117.7
34
0.160
0.2011
39.69
52.48
133.3
35
0.140
0.1589
31.36
58.77
149.3
29
30
33
36
39
0.130
0.1266
25.00
65.62
166.7
37
41
0.110
0.1026
20.25
71.57
181.8
38
42
0.100
0.08107
16.00
80.35
204.1
39
43
0.090
0.06207
12.25
91.57
232.6
40
44
0.080
0.04869
9.61
103.6
263.2
41
45
0.070
0.03972
7.84
115.7
294.1
42
46
0.060
0.03166
6.25
131.2
333.3
43
0.02452
4.84
145.8
370.4
44
0.0202
4.00
157.4
400.0
Table 1 Wire Table.
A
7/96
13
AN-18
Output Power
0-10W
FERRITE CORES
Triple Insulated Wire Construction
Margin Wound Construction
EPC17
EEL16
EFD15
EF20
EE16 or EI16
EEL19
EF16
EPC25
E187
EFD25
EE19 or EI19
10-20W
EE19 or EI19
EEL19
EPC19
EPC25
EF20
EFD25
EFD20
EF25
EE22 or EI22
20-30W
EPC25
EPC30
EFD25
EFD30
E24/25
EF30
EI25
EI30
EF25
ETD29
EI28
EER28
EI28
EI30
EF30
ETD29
EI30
EER28
ETD29
EER28L
EER28
EER35
EER28L
EER28L
ETD34
ETD34
EI35
EER35
EER35
ETD39
ETD34
EER35
EI35
ETD39
EER35
EER40
E21
E21
30-50W
50-70W
70-100W
Table 2 Ferrite Core Selection Table for Transformer Construction.
14
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AN-18
Transformer Material Vendors
EIS, 41444 Christy Street, Fremont, CA 94538 (510) 490-5855
(510) 490-2956 (FAX)
The contact numbers below are listed for information purposes
only. Please refer to local authorized representatives and
distributors for pricing and ordering information.
Tesa Tape Inc. 5825 Carnegie Bl., Charlotte, NC 28209
(704) 554-0707 (800) 852-8831 (FAX)
Ferrite Cores
Magnet Wire
TDK Corporation, of America, 1600 Feehanville Dr. Mount
Prospect IL 60056 (847) 803-6100 (847) 803-6296 (FAX)
Belden Wire and Cable Company, P.O. Box 1980, Richmond,
IN 47375 (317) 983-5200 (317) 983-5656 (FAX)
Siemens Matsushita Components, Special Products Division,
186 Wood Ave, South Iselin, NJ 08830 (908) 906-4300
(908) 632-2830 (FAX)
MWS Wire Industries 31200 Cedar Valley Dr., Westlake
Village, CA 90404 (818) 991-8553 (818) 706-0911 (FAX)
Philips Components, Discrete Products Division, Magnetic
Products, 1033 Kings Highway, Saugerties, NY 12477
(914) 246-2811 (914) 246-0486 (FAX)
Phelps Dodge Magnet Wire, 2131 S. Coliseum Blvd. Fort
Wayne, IN 46803 (219) 421-5400 (219) 421-5564 (FAX)
Rea Magnet Wire Co., Inc. 3600 E. Pontiac St. Fort Wayne, IN
46896 (219) 424-4252 (219) 421-7349 (FAX)
Tokin America, Inc.,155 Nicholson Lane, San Jose, CA 95134
(408) 432-8020 (408) 434-0375 (FAX)
Triple Insulated Wire
Thomson Passive Components Corporation, 2211-H
Distribution Center Drive, Charlotte, NC 28269
(704) 597-0766 (704) 597-0553 (FAX)
Furukawa Electric America, Inc. 200 Westpark Drive, Suite
190, Peachtree City, GA 30269 (770) 487-1234
(770) 487-9910 (FAX)
Bobbins
Furukawa Electric Co. Ltd. 6-1, Marunouchi 2-chome, Chiyodaku, Tokyo 100, Japan (PH) 81-3-3286-3226
(FAX) 81-3-3286-3747
Many of the ferrite core vendors above offer compatible bobbins
for their cores. Additional bobbin suppliers are listed below:
Yih Hwa Enterprises Co., Ltd., 2 Floor, No. 2, Alley 4, Lane
222 Lien Cheng Rd. Chung Ho City, Taipei, Taiwan, R.O.C.
886-2-2483366 886-2-2406919 (FAX)
Taiwan Shu Lin Enterprise Co., Ltd., 760 Chung Cheng Road,
Chung Ho City, Taipei Tsien, Taiwan, R.O.C. 886 2 2231500
886 2 2224646 (FAX)
Rubudue Wire Company 5150 E. La Palma Av., Suite 108
Anaheim Hills, CA 92807 (714) 693-5512
(714) 693-5515 (FAX)
Belden Wire and Cable B.V., Edisonstraat 9, P.O. Box 9, NL
5900 AA Venlo, Netherlands (PH) 31 773 878 442 (
FAX) 31 773 878 448
Transformer Varnishes
B&B Products Corp., 2190 Ironwood Crest Dr., Tucson, AZ
85745 (520) 743-3389 (520) 743-8000 (FAX)
Miles-Platts, Inc. 901 Touhy Av., Elk Grove Village, IL 60007
(847) 364-0363 (847) 364-0614 (FAX)
John C. Dolph, Co. Box 267, Monmouth Junction, NJ 08852
(908) 329-2333 (908) 329-1143 (FAX)
Schenectady Chemicals, Inc. Box 1046, Schenectady, NY
12301 (518) 370-4200 (518) 382-8129 (FAX)
Insulating Materials
3M Electrical Specialties Division, Bldg. 130-4N-40, 3M Austin
Center, P.O. Box 2963, Austin TX 78769 (800) 364-3577
(800) 713-6329
P.D. George, 9 Ohio River Boulevard, Sewickley, PA 15143
(800) 999-5700 (412) 741-8892
Epoxylite Corp., 9400 Toledo Way, P.O. Box 19671, Irvine,
CA 92713 (714) 951-3231 (714) 472-0980 (FAX)
CHR/Furon, 407 East St., P.O. Box 1911, New Haven, CT
06509 (203) 777-3631 (203) 787-1725 (FAX)
A
7/96
15
AN-18
Appendix B
transformer with an EF20 core. The power supply design shown
in Figure 1 was used as a starting point for both transformer
design/construction examples. Target specifications for this
power supply design are shown in Table 2. Specifications and
selected component values from Table 2 are loaded into the
application variables section of the spreadsheets. Table 3 shows
TOPSwitch and output rectifier operating conditions used in the
TOPSwitch variable section of the spreadsheets. Since both of
the transformer designs are for the same power supply, the
values loaded into the application variables section and
TOPSwitch variable section for both spreadsheets are exactly
the same, with the exception of the value used for reflected
output voltage (VOR, cell B16). For the triple insulated wire
transformer design shown in Table 6, VOR is adjusted to a value
slightly lower than the default value recommended in AN-16 in
order to reduce the number of primary turns. This is discussed
in the paragraphs devoted to the triple insulated wire design
example.
Transformer Construction Examples
Two transformer design and construction examples using margin
wound and triple insulated wire construction techniques are
described below. These designs are based on the 12V, 15W
universal input power supply shown in Figure 1. The design
procedure for the two examples utilizes computer spreadsheet
techniques described in application notes AN-16 and AN-17.
The detailed step-by-step flyback power supply design procedure
for using the spreadsheet is shown in AN-16. Two completed
spreadsheet design examples are shown in this appendix
(Table 1 and Table 6). Information derived from these
spreadsheets is used in the construction examples.
Spreadsheet Input Parameters
Two power supply design spreadsheets are shown in Tables 1
and 6. Table 1 details a power supply design utilizing a margin
wound transformer with an EF25 core. Table 6 shows a design
for the same power supply utilizing a triple insulated wire
The transformer construction variables in the design spreadsheet
are determined by the core, bobbin and transformer construction
type, and are therefore different for the two design examples.
D2
MBR360
T1
L1
3.3 µH
9,10
L2
22 mH
VR2
1N6001B
11 V
2
6,7
5
C5
47 µF
10 V
C6
0.1 µF
X2
C3
120 µF
25 V
U2
NEC2501-H
D1
UF4005
C1
47 µF
400 V
R2
68 Ω
C2
680 µF
25 V
VR1
P6KE200
BR1
600 V
PO = 15 W
R1
39 Ω
1
VO = 12 V
RTN
D3
1N4148
VB = 12 V
IB = 10 mA
4
DRAIN
F1
3.15 A
L
SOURCE
CONTROL
U1
TOP201YAI
C4
0.1 µF
C7
1.0 nF
Y1
N
J1
VIN = 85-265 VAC
50/60 Hz
Figure 1. Typical TOPSwitch Power Supply for 12V, 15W Output.
16
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PI-1809-031896
AN-18
A
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
17
18
19
20
21
22
23
24
25
26
27
28
29
30
31
32
33
34
35
36
37
38
39
40
41
42
43
44
45
46
47
48
49
50
51
52
53
54
55
56
57
58
59
60
61
62
63
64
65
66
67
68
69
70
71
72
73
74
75
76
77
78
79
80
81
82
B
C
INPUT
ENTER APPLICATION VARIABLES
VACMIN
85
VACMAX
265
fL
50
fS
100000
VO
12
PO
15
n
0.8
Z
0.5
VB
12
tC
3
CIN
47
D
OUTPUT
E
Volts
Volts
Hertz
Hertz
Volts
Watts
Volts
mSeconds
uFarads
ENTER TOPSWITCH VARIABLES
VOR
135
VDS
10
VD
0.4
VDB
0.7
KRP
0.60
Volts
Volts
Volts
Volts
F
Minimum AC Input Voltage
Maximum AC Input Voltage
AC Mains Frequency
TOPSwitch Switching Frequency
Output Voltage
Output Power
Efficiency Estimate
Loss Allocation Factor
Bias Voltage
Bridge Rectifier Conduction Time Estimate
Input Filter Capacitor
Reflected Output Voltage
TOPSwitch on-state Drain to Source Voltage
Output Winding Diode Forward Voltage Drop
Bias Winding Diode Forward Voltage Drop
Ripple to Peak Current Ratio (0.4 < KRP < 1.0)
ENTER TRANSFORMER CORE/CONSTRUCTION VARIABLES
EF25
AE
0.525
cm^2
LE
5.75
cm
AL
1800
nH/T^2
BW
15.1
mm
M
3
mm
L
2
NS
6
Core Type
Core Effective Cross Sectional Area
Core Effective Path Length
Ungapped Core Effective Inductance
Bobbin Physical Winding Width
Safety Margin Width (Half the Primary to Secondary Creepage Distance)
Number of Primary Layers
Number of Secondary Turns
DC INPUT VOLTAGE PARAMETERS
VMIN
VMAX
9 4 Volts
3 7 5 Volts
Minimum DC Input Voltage
Maximum DC Input Voltage
CURRENT WAVEFORM SHAPE PARAMETERS
DMAX
IAVG
IP
IR
IRMS
0.62
0.20
0.46
0.28
0.26
Duty Cycle at Minimum DC Input Voltage (VMIN)
Average Primary Current
Peak Primary Current
Primary Ripple Current
Primary RMS Current
TRANSFORMER PRIMARY DESIGN PARAMETERS
LP
NP
NB
ALG
441
BM
BAC
761
ur
1569
LG
BWE
18.2
OD
INS
0.05
DIA
AWG
CM
64
CMA
1884 uHenries
65
6
nH/T^2
2 5 3 7 Gauss
Gauss
0 . 1 1 mm
mm
0.28 mm
mm
0.23 mm
3 2 AWG
Cmils
2 4 5 Cmils/Amp
TRANSFORMER SECONDARY DESIGN PARAMETERS
ISP
5.03
ISRMS
2.25
IO
1.25
IRIPPLE
1.87
CMS
AWGS
DIAS
ODS
INSS
550
Amps
Amps
Amps
Amps
Amps
Amps
Amps
Amps
Primary Inductance
Primary Winding Number of Turns
Bias Winding Number of Turns
Gapped Core Effective Inductance
Maximum Flux Density (2000 < BM < 3000)
AC Flux Density for Core Loss Curves (0.5 X Peak to Peak)
Relative Permeability of Ungapped Core
Gap Length (Lg >> 0.051 mm)
Effective Bobbin Width
Maximum Primary Wire Diameter including insulation
Estimated Total Insulation Thickness (= 2 * film thickness)
Bare conductor diameter
Primary Wire Gauge (Rounded to next smaller standard AWG value)
Bare conductor effective area in circular mils
Primary Winding Current Capacity (200 < CMA < 500)
Peak Secondary Current
Secondary RMS Current
Power Supply Output Current
Output Capacitor RMS Ripple Current
Cmils
2 2 AWG
0.65 mm
1.52 mm
mm
Secondary Bare Conductor minimum circular mils
Secondary Wire Gauge (Rounded up to next larger standard AWG value)
Secondary Minimum Bare Conductor Diameter
Secondary Maximum Insulated Wire Outside Diameter
Maximum Secondary Insulation Wall Thickness
VOLTAGE STRESS PARAMETERS
VDRAIN
PIVS
PIVB
6 7 8 Volts
4 6 Volts
4 7 Volts
Maximum Drain Voltage Estimate (Includes Effect of Leakage Inductance)
Output Rectifier Maximum Peak Inverse Voltage
Bias Rectifier Maximum Peak Inverse Voltage
ADDITIONAL OUTPUTS
VX
12
VDX
0.7
NX
PIVX
Volts
Volts
6.15
4 7 Volts
Auxiliary Output Voltage
Auxiliary Diode Forward Voltage Drop
Auxiliary Number of Turns
Auxiliary Rectifier Maximum Peak Inverse Voltage
0.44
Table 1. Design Spreadsheet for 15W Margin Wound Transformer.
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17
AN-18
APPLICATION VARIABLES
(INPUT TO TABLE 1 AND TABLE 6 SPREADSHEETS)
DESCRIPTION
SYMBOL
VALUE
SOURCE
CELL #
Minimum AC Input Voltage
VACMIN
85 VAC
Supply Specification
B3
Maximum AC Input Voltage
VACMAX
265 VAC
Supply Specification
B4
AC Mains Frequency
fL
50 Hz
Supply Specification
B5
TOPSwitch Switching
Frequency
fS
100,000 Hz
AN-16 Default Value
B6
Output Voltage
VO
12 V
Supply Specification
B7
Output Power
PO
15 W
Supply Specification
B8
Estimated Efficiency
η
0.8
AN-16 Default Value
B9
Loss Allocation Factor
Z
0.5
AN-16 Default Value
B10
Bias Voltage
VB
12 V
Supply Specification
B11
Bridge Rectifier
Conduction Time Estimate
tC
3 msec
AN-16 Default Value
B12
Input Filter Capacitor (C1)
CIN
47 µF
AN-16 Default Value
B13
Table 2. Application Variables for Design Spreadsheets for Figure 1 Power Supply .
The spreadsheets for the two designs diverge at this point. The
following paragraphs will describe completed construction
examples; first for the margin wound design, then the triple
insulated wire design.
Margin Wound Construction Example
In order to carry the margin wound example to completion, the
remainder of the design parameters needed to complete the
Table 1 spreadsheet input section are described. The construction
example is then completed with the information from the
spreadsheet.
Determining Transformer Construction Variables
In order to complete the input portion of the Table 1 spreadsheet,
information is needed for the transformer/core construction
variable section. Table 4 shows the transformer core/construction
variables chosen for this margin wound transformer construction
example. The EF25 core is chosen from the transformer core
chart in Appendix A as representative for the power level and
construction type. Dimensional and electrical characteristics
for the core and a compatible bobbin are shown in
Figures 2 and 3. The core electrical parameters necessary for
18
A
7/96
the spreadsheet design are Ae, Le, and AL, and are loaded into
spreadsheet cells (B24), (B25), and (B26) respectively. A
margin width (M) of 3 mm (0.118 in) is chosen for the margin
wound design to meet international safety regulations for
universal input voltage range, and loaded into cell (B28). The
number of primary layers (B29) is set at 2 to optimize the core
size and to reduce the transformer leakage inductance and stray
capacitance.
The variable BW (Bobbin Physical Winding Width), required
for the transformer design spreadsheet, represents the width of
the bobbin available for winding. This value can be read directly
from many bobbin specifications. However, in some cases it is
not given directly, and must be calculated from the minimum
total bobbin width and the maximum width of the bobbin end
flanges. The EF25 bobbin drawing shown in Figure 3 does not
show a value for BW. Instead, the total bobbin width (WT) and
flange width (WF) are given, including tolerances. BW can be
calculated from these values using the equation:
[
BW = WT ( MIN ) − 2 × WF ( MAX )
]
AN-18
TOPSwitch VARIABLES
(INPUT TO TABLE 1 AND TABLE 6 SPREADSHEETS)
DESCRIPTION
SYMBOL
VALUE
SOURCE
CELL #
Reflected Output Voltage
VOR
135 V*/130V**
*AN-16 Default Value
**(See Text)
B16
TOPSwitch Drain to Source
Voltage with MOSFET on
V DS
10 V
AN-16 Default Value
B17
Output Diode (D2)
Forward Voltage Drop
VD
0.4 V
Estimated
B18
Bias Diode (D3)
Forward Voltage Drop
V DB
0.7 V
Estimated
B19
Primary Current Ripple
to Peak Ratio
K RP
0.6
Optimized Through
Iteration
B20
Table 3. TOPSwitch Variables for Design Spreadsheets.
WT(MIN) is the minimum total bobbin width, and WF(MAX) is the
maximum flange width. For the bobbin in Figure 3, WT(MIN) is
16.7 mm and WF(MAX) is 0.8 mm. For these values, BW is:
BW = 16.7 − (2 × 0.8) = 15.1mm
Primary Wire Size
From cell (D56) of the Table 1 spreadsheet, the wire size is
given as 32 AWG. The primary winding current capacity is
given in cell (D58) as 245 circular mils/ampere, and meets the
current capacity guideline of 200-500 circular mils/ampere.
This wire size is also suitable for use at 100 KHz, as its diameter
is smaller than twice the 100KHz skin depth, as shown by
Figure 13.
This BW value is entered into cell B27 of the spreadsheet.
The optimum number of secondary turns, NS (B30), for a
transformer design is a function of the power supply input
voltage range, the desired KRP, and the effective core crosssectional area Ae. Using the spreadsheet, it is a simple matter to
iterate the value for NS until a design is reached that fits on the
desired transformer core and bobbin and results in satisfactory
values for primary winding current capacity (CMA), Gap
Length (LG), and maximum flux density (BM). Suggested starting
values for NS in terms of volts per turn are found in AN-16. For
this design using the EF25 core, the optimum NS after iteration
is 6 turns. At this point the spreadsheet design is complete, and
the transformer construction example can proceed using the
output data from the completed and optimized spreadsheet.
Margin Wound Example Completion
The parameters needed to specify the margin wound transformer
design are shown in Table 5. The spreadsheet parameters from
Table 1 are used to determine the transformer wire size, tape
sizes, and sleeving size.
Secondary Wire Size
Looking at cell (B66) of the spreadsheet, a secondary bare wire
area of 550 circular mils is required to make the secondary
CMA equal to the primary CMA. From cell (D67) of the
Table 1 spreadsheet, the closest AWG wire size that can satisfy
this requirement with a single wire is 22 AWG. This wire size
is too large for use at 100KHz, and several parallel wires, size
26 AWG or smaller, should be used instead to allow full
utilization of the wire cross-sectional area. From the wire table
in Appendix A, it can be seen that two parallel strands of 26
AWG wire (CM of 252.8 circular mils per wire) have a total
bare wire area of 505.6 circular mils, which is within 10% of
the required CM of 550 circular mils. The current capacity of
the parallel winding can be calculated from the formula:
CMAS =
N × CM
ISRMS
CMAS is the current capacity of the secondary winding in
circular mils per ampere, N is the number of strands in the
A
7/96
19
AN-18
TRANSFORMER CONSTRUCTION VARIABLES
(INPUT TO TABLE 1 SPREADSHEET)
DESCRIPTION
SYMBOL
VALUE
SOURCE
CELL #
Core Type
-
EF25
Core Specifications
B23
Core Effective Cross
Sectional Area
Ae
0.525 cm2
Core Specifications
B24
Core Effective Path Length
Le
5.75 cm
Core Specifications
B25
Core Ungapped
Inductance Coefficient
AL
1800 nH/T2
Core Specifications
B26
Bobbin Physical
Winding Width
BW
15.1 mm
Calculated from Bobbin
Specifications
B27
Margin Width
M
3 mm
Default Value from
AN-16
B28
Number of Primary
Winding Layers
L
2
Default Value from
AN-16
B29
Number of
Secondary Turns
NS
6t
See Text
B30
Table 4. Transformer Construction Variables for EF25 Margin Wound Transformer Design.
7.5
-0.5
Figure 2. EF25 Core.
A
7/96
le = 5.75 cm
AL= 1800 nH/T2
-0.6
All Dimensions are in mm
20
Ae =0.525 cm2
17.8 max
17.5
+0.8
-0.7
+0.8
PI-1796-030896
3.5 -0.5
25
17
-0.3
0.7 ±0.1
17.3
-0.25
7.7
+0.15
Electrical
Characteristics
7.5
(WT)
27.5 -0.3
All Dimensions are in mm
Figure 3. EF25 Bobbin.
(WF)
0.7 ±0.1
9.4
-0.25
+0.5
7.7 +0.2
8.7
-0.5
2.2 -0.1
12.8
0.7
PI-1797-030896
AN-18
MARGIN WOUND DESIGN TRANSFORMER CONSTRUCTION
PARAMETERS FROM TABLE 1 SPREADSHEET
DESCRIPTION
SYMBOL
VALUE
CELL #
Core Type, Material
-
EF25, Siemens N67
Part# B66317-G-X130
-
Bobbin Type
-
EF25, 10 PIN, Siemens PIN
B66208-A 1110-T1
-
Number of Primary Turns
NP
65 T
D45
Number of Secondary Turns
NS
6T
B30
Number of Bias Winding Turns
NB
6T
D46
Primary Wire Size
AWG
32 AWG
D56
Secondary Wire Size
AWGS
26 AWG
D67 (See Text)
Bias Winding Wire Size
AWGB
24 AWG
See Text
Core Gapped Inductance
Coefficient
ALG
441 nH/T2 ±5%
C47
Primary Inductance
LP
1884 µH +/-10%
D44
Reinforced Insulation
Tape Width
BW
15.1 mm
B27
Basic Insulation
Tape Width
WTB
9.1 mm
See Text
Margin Tape Width
M
3 mm
B28
Sleeving Size
-
24 AWG
See Text
Table 5. Construction Parameters for Margin Wound Design Example.
secondary winding, CM is the bare area of a single secondary
conductor in circular mils (from the wire table in Appendix A),
and ISRMS is the secondary RMS current from cell (D62) of the
spreadsheet. 26 AWG wire has a bare area of 252.8 circular
mils. Two parallel strands of 26 AWG wire have a current
capacity of:
CMAS =
2 × 252.8
= 224.7 circular mils/ampere
2.25
This value is close to the primary current capacity (within
10%), and satisfies the CMA design limits.
A
7/96
21
AN-18
Bias Wire Size
The bias winding wire size is chosen to fill as much of the
bobbin width as possible. Since there are usually relatively few
primary bias winding turns, this is best accomplished by using
a bifilar winding rather than a large diameter wire, effectively
doubling the number of physical turns. The required TC can be
calculated as follows:
2 × N B × 10
2 × 6 × 10
=
BW − (2 × M ) 15.1 − (2 × 3)
= 13.2turns / cm
TC =
From the wire table in Appendix A, the closest wire size with
TC greater than or equal to 13.2 turns/cm is 22 AWG, with a TC
of 14.25 turns/cm. This is too large a wire size to use with an
EF25 core and bobbin. As a compromise, 24 AWG wire is used
instead. This wire size will not completely cover the available
bobbin width, but is an acceptable compromise for the sake of
manufacturability. Since the output current of this winding is
10 mA or less, there is no need to consider the current capacity
of the wire or high frequency skin effect. The wire size in this
case is determined by space-filling requirements rather than
current capacity.
Transformer Construction Style
Since this transformer is a margin wound design for a secondary
regulated application, appropriate construction styles are
Figures 7A and 10A. Because this design is for a 15W
application, the split primary winding shown in Figure 10A is
not necessary, and more cost effective single section primary
design of Figure 7A should be used.
22
A
7/96
Tape Sizes
For a margin wound design, three sizes of tape are required for
reinforced insulation, basic insulation, and margins. The tape
width required for the reinforced insulation layers on this
transformer is equal to BW. From cell (B27) of the Table 1
spreadsheet, this is 15.1 mm. The width WTB of the basic
insulation tape is calculated as:
WTB = BW − (2 × M ) = 15.1 − (2 × 3) = 9.1mm
The margin tape width (M) is read from cell (B28) of the
spreadsheet, and is set at 3 mm to meet international safety
regulations for creepage distance for universal input.
Insulating Sleeving Size
The insulating sleeving size required for this transformer deign
is equivalent to the largest wire size in the transformer, or
24 AWG. The sleeving should have a wall thickness of at least
0.4 mm to meet international safety regulations.
Gapped Core Inductance Coefficient
The ALG for this transformer design is given in cell (C47) of the
design spreadsheet, and should be used as the center value for
specifying the core ALG on the transformer specification.
Finished Margin Wound Transformer Design
The information required to assemble a transformer specification
for the margin wound transformer example is summarized in
Table 5. A completed transformer schematic diagram and parts
list are shown in Figure 4. A construction drawing is shown in
Figure 5.
AN-18
Pin 1
Primary
65T
#32 AWG
Pin 9, 10
Bifilar
SPECIFICATIONS
12V Secondary
6T
Primary Inductance - 1884 µH ±15%
2x #26 AWG
Leakage Inductance < 45 µH
Pin 6, 7
Pin 2
Pin 4
Bifilar
Primary Bias
6T
2x #24 AWG
Pin 5
PARTS LIST FOR EF25 TRANSFORMER DESIGN EXAMPLE
Item Amt.
Description
Part #
Manufacturer
1
1pr.
Core, EF25 N67 Mat'l
B66317-G-X167*
Siemens
2
1ea.
Bobbin, EF25, 10 pin
B66208-A1110-T1
Siemens
3
A/R
Wire, 32 AWG Heavy Nyleze
4
A/R
Wire, 24 AWG Heavy Nyleze
5
A/R
Wire, 26 AWG Heavy Nyleze
6
A/R
Tape, Polyester 3.0 mm wide
#44
3M
7
A/R
Tape, Polyester 9.1 mm wide
#1296
3M
8
A/R
Tape, Polyester 15.1 mm wide
#1296
3M
9
A/R
Tubing, Teflon, 24 AWG, 0.4 mm
minimum wall thickness
*Gap for ALG of 441 nH/T2 ± 5%
PI-1805-031196
Figure 4. Parts List for EF25 Transformer Design Example.
A
7/96
23
AN-18
MARGIN WOUND TRANSFORMER CONSTRUCTION
6,7
9,10
4
5
MARGINS
1
2
WINDING INSTRUCTIONS
Margins
Two-layer "C" Wound Primary
Basic Insulation
Primary Bias
(Bifilar)
Reinforced Insulation
Margins
Parallel Bifilar Secondary
Apply 3mm tape margins as shown.
Start at pin 2. Wind 33 turns of 32 AWG heavy nyleze
magnet wire from left to right. Apply 1 layer of polyester
tape, 9.1 mm wide, for basic insulation. Continue
winding 32 turns from right to left. Finish at pin 1.
Sleeve start and finish leads.
Apply 1 layer of 9.1 mm wide tape for basic
insulation.
Start at pin 5. Wind 6 bifilar turns of 24 AWG heavy
nyleze magnet wire in a single layer, from left to right.
Finish at pin 4. Sleeve start and finish leads.
Apply 3 layers of 15.1 mm wide polyester film tape,
for reinforced insulation.
Apply 3 mm tape margins as shown.
Start at pins 9 & 10. Wind 6 bifilar turns of 26 AWG
heavy nyleze magnet wire in 1 layer from left to right.
Finish at pins 6 & 7. Sleeve start and finish leads.
Outer Insulation
Apply 3 layers of 15.1 mm wide tape for outer
insulation.
Final Assembly
Assemble and secure core halves.
Impregnate uniformly with varnish.
PI-1806-030896
Figure 5. EF25 Margin Wound Construction Example.
24
A
7/96
AN-18
Triple Insulated Wire Construction Example
In the following paragraphs, the design parameters needed to
complete the Table 6 spreadsheet input section will be described.
A triple insulated wire transformer construction example will
then be completed with the information from the spreadsheet.
Determining Transformer Construction Variables
In order to complete the input portion of the Table 6 spreadsheet,
information is needed for the transformer/core construction
variable section. Table 7 shows the transformer core/construction
variables chosen for the triple insulated transformer construction
example. The EF20 core was chosen from the transformer core
chart in Appendix A. Dimensional and electrical characteristics
for the core and a compatible bobbin are shown in Figures 6 and
7. The core electrical parameters necessary for the spreadsheet
design are Ae , Le, and AL, and are loaded into spreadsheet cells
(B24), (B25), and (B26), respectively. Margin width (M) was
set to zero for the triple insulated wire design and loaded into
cell (B28). The number of primary layers (B29) is set at 2 to
optimize the core size and to reduce the transformer leakage
inductance and stray capacitance. BW (Bobbin Physical Winding
Width) is calculated as in the margin wound example, since it
is not directly available from the Figure 7 bobbin drawing.
WT(MIN) is 13.4 mm and WF(MAX) is 0.7 mm, so BW for the EF20
bobbin is:
[
BW = WT ( MIN ) − 2 × WF ( MAX )
]
= 13.45 − (2 × 0.7) ≅ 12.0 mm
This BW value is entered into cell (B27) of the Table 6
spreadsheet. The optimum number of secondary turns, NS
(B30), is determined as 9 turns after iteration. The number of
primary layers (B29) is set at 2 to optimize the core size and to
reduce the transformer leakage inductance and stray capacitance.
Completion of Triple Insulated Wire Transformer
Example
Information necessary to specify the triple insulated wire
transformer example is shown in Table 8. The entries in
Table 8 were taken directly from the Table 6 spreadsheet or
calculated from the spreadsheet values. Unlike the Table 1
spreadsheet design for the EF25 transformer, the Table 6
spreadsheet requires one additional iteration cycle to optimize
the primary wire size. This iteration cycle and the remaining
steps in the transformer design are described below.
Adjusting Primary Wire Size and CMA
The design spreadsheet adjusts the primary wire size to the
closest AWG value that will fit within the available bobbin
width. In some cases the AWG wire size given by the spreadsheet
may result in a CMA value outside of the desired range of
200-500 circular mils/ampere. The CMA and resulting AWG
values in the spreadsheet are dependent variables and cannot be
adjusted directly. The number of primary turns in the spreadsheet
cannot be manipulated directly, as it is a function of the number
of secondary turns. Gross adjustments can be made indirectly
to the primary CMA value by changing the number of secondary
turns (NS) or the core size (see AN-16). Adjusting the number
of secondary turns changes the number of primary turns
proportionally to maintain the reflected output voltage, VOR , at
its specified value. Changing the core size changes the available
bobbin width (BW). The spreadsheet will change the primary
wire size to fill the available bobbin width using the specified
number of primary winding layers.
In some cases, changing the number of secondary turns results
either in too large a change in primary wire size or has a
deleterious effect on other parameters, such as maximum flux
density or transformer gap length. Also, it may not be desirable
to change the core size for reasons of cost, availability, or size
constraints. The following techniques are useful for fine
adjustment of the AWG and CMA of the primary winding
without changing the core/bobbin size or the number of
secondary turns:
• To reduce the primary wire size to a slightly smaller value,
adjust the number of primary layers to a value less than the
default value of 2 layers in increments of 0.1 layer (for
example, try 1.9 layers, 1.8 layers, etc.).
• To increase the primary wire size to a slightly larger value,
adjust the reflected voltage VOR downward in increments
of 1-2 volts. This will slightly reduce the number of
primary turns. Maximum duty cycle (DMAX) will be reduced
slightly, LG will become smaller and BM will rise slightly.
Do not adjust the reflected primary voltage more than 10%
below the maximum recommended value suggested in
AN-16. If more adjustment is needed, reduce the number
of secondary turns instead or use a larger core size.
Initially, the Table 6 spreadsheet used the default value of 135V
for VOR in cell (B16). For NS = 9 turns, this resulted in NP = 96
turns, and a primary wire size of 33 AWG, which for this design,
is slightly too small (CMA of 196 circular mils/ampere) to
satisfy the CMA requirement of 200-500 circular mils/ampere.
Adjusting the number of primary turns by reducing the secondary
turns resulted in a transformer design with a maximum flux
density larger than the design limit of 3000 Gauss. To avoid this
condition, the number of primary turns was instead reduced
from 98 turns to 94 turns by reducing VOR from 135V to 130V
in small steps. This allowed the primary wire size, AWG (D56),
to change from 33 AWG to 32 AWG and brought the primary
winding CMA (D58) up to 243 circular mils/ampere. Maximum
duty cycle and maximum flux density were only slightly
affected by this change.
A
7/96
25
AN-18
A
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
17
18
19
20
21
22
23
24
25
26
27
28
29
30
31
32
33
34
35
36
37
38
39
40
41
42
43
44
45
46
47
48
49
50
51
52
53
54
55
56
57
58
59
60
61
62
63
64
65
66
67
68
69
70
71
72
73
74
75
76
77
78
79
80
81
82
B
C
INPUT
ENTER APPLICATION VARIABLES
VACMIN
85
VACMAX
265
fL
50
fS
100000
VO
12
PO
15
n
0.8
Z
0.5
VB
12
tC
3
CIN
47
D
OUTPUT
E
Volts
Volts
Hertz
Hertz
Volts
Watts
Volts
mSeconds
uFarads
ENTER TOPSWITCH VARIABLES
VOR
130
VDS
10
VD
0.4
VDB
0.7
KRP
0.60
Volts
Volts
Volts
Volts
F
Minimum AC Input Voltage
Maximum AC Input Voltage
AC Mains Frequency
TOPSwitch Switching Frequency
Output Voltage
Output Power
Efficiency Estimate
Loss Allocation Factor
Bias Voltage
Bridge Rectifier Conduction Time Estimate
Input Filter Capacitor
Reflected Output Voltage
TOPSwitch on-state Drain to Source Voltage
Output Winding Diode Forward Voltage Drop
Bias Winding Diode Forward Voltage Drop
Ripple to Peak Current Ratio (0.4 < KRP < 1.0)
ENTER TRANSFORMER CORE/CONSTRUCTION VARIABLES
EF20
AE
0.335
cm^2
LE
4.49
cm
AL
1470
nH/T^2
BW
12
mm
M
0
mm
L
2
NS
9
Core Type
Core Effective Cross Sectional Area
Core Effective Path Length
Ungapped Core Effective Inductance
Bobbin Physical Winding Width
Safety Margin Width (Half the Primary to Secondary Creepage Distance)
Number of Primary Layers
Number of Secondary Turns
DC INPUT VOLTAGE PARAMETERS
VMIN
VMAX
9 4 Volts
3 7 5 Volts
Minimum DC Input Voltage
Maximum DC Input Voltage
CURRENT WAVEFORM SHAPE PARAMETERS
DMAX
IAVG
IP
IR
IRMS
0.61
0.20
0.47
0.28
0.26
Duty Cycle at Minimum DC Input Voltage (VMIN)
Average Primary Current
Peak Primary Current
Primary Ripple Current
Primary RMS Current
TRANSFORMER PRIMARY DESIGN PARAMETERS
LP
NP
NB
ALG
205
BM
BAC
814
ur
1568
LG
BWE
24
OD
INS
0.05
DIA
AWG
CM
64
CMA
1829 uHenries
94
9
nH/T^2
2 7 1 2 Gauss
Gauss
0 . 1 8 mm
mm
0.25 mm
mm
0.21 mm
3 2 AWG
Cmils
2 4 3 Cmils/Amp
TRANSFORMER SECONDARY DESIGN PARAMETERS
ISP
4.91
ISRMS
2.22
IO
1.25
IRIPPLE
1.84
CMS
AWGS
DIAS
ODS
INSS
540
Amps
Amps
Amps
Amps
Amps
Amps
Amps
Amps
Primary Inductance
Primary Winding Number of Turns
Bias Winding Number of Turns
Gapped Core Effective Inductance
Maximum Flux Density (2000 < BM < 3000)
AC Flux Density for Core Loss Curves (0.5 X Peak to Peak)
Relative Permeability of Ungapped Core
Gap Length (Lg >> 0.051 mm)
Effective Bobbin Width
Maximum Primary Wire Diameter including insulation
Estimated Total Insulation Thickness (= 2 * film thickness)
Bare conductor diameter
Primary Wire Gauge (Rounded to next smaller standard AWG value)
Bare conductor effective area in circular mils
Primary Winding Current Capacity (200 < CMA < 500)
Peak Secondary Current
Secondary RMS Current
Power Supply Output Current
Output Capacitor RMS Ripple Current
Cmils
2 2 AWG
0.65 mm
1.33 mm
mm
Secondary Bare Conductor minimum circular mils
Secondary Wire Gauge (Rounded up to next larger standard AWG value)
Secondary Minimum Bare Conductor Diameter
Secondary Maximum Insulated Wire Outside Diameter
Maximum Secondary Insulation Wall Thickness
VOLTAGE STRESS PARAMETERS
VDRAIN
PIVS
PIVB
6 6 8 Volts
4 8 Volts
4 9 Volts
Maximum Drain Voltage Estimate (Includes Effect of Leakage Inductance)
Output Rectifier Maximum Peak Inverse Voltage
Bias Rectifier Maximum Peak Inverse Voltage
ADDITIONAL OUTPUTS
VX
12
VDX
0.7
NX
PIVX
Volts
Volts
9.22
4 9 Volts
Auxiliary Output Voltage
Auxiliary Diode Forward Voltage Drop
Auxiliary Number of Turns
Auxiliary Rectifier Maximum Peak Inverse Voltage
0.34
Table 6. Design Spreadsheet for 15 W Triple Insulated Wire Transformer.
26
A
7/96
AN-18
TRANSFORMER CONSTRUCTION VARIABLES
(INPUT TO TABLE 6 SPREADSHEET)
DESCRIPTION
SYMBOL
VALUE
SOURCE
CELL #
Core Type
-
EF20
Core Specification
B23
Core Effective Cross
Sectional Area
Ae
0.335 cm2
Core Specification
B24
Core Effective Path Length
Le
4.49 cm
Core Specification
B25
Core Ungapped
Inductance Coefficient
AL
1470 nH/T2
Core Specification
B26
Bobbin Physical Winding Width
BW
12.0 mm
Calculated from Bobbin
Specification
B27
Margin Width
M
0
Default Value from
AN-16
B28
Number of Primary
Winding Layers
L
2
Default Value from
AN-16
B29
Number of
Secondary Turns
NS
9t
See Text
B30
Table 7. Transformer Construction Variables for EF20 Triple Insulated Wire Design.
-0.4
14.6 max
5.9
-0.4
Ae = 0.335 cm2
le = 4.49 cm
AL = 1470 nH/T2
3.5 -0.5
20.4
-0.8
+0.6
14.1
-0.5
(WF)
13.7
-0.25
0.6 ±0.1
13.9
-0.25
6.1
+0.15
Electrical
Characteristics
5.9
(WT)
22 -0.3
0.6 ±0.1
7.6
-0.15
+0.5
6.1 +0.2
7
2 -0.1
10.2
0.45
All Dimensions are in mm
Figure 6. EF20 Core.
PI-1821-040296
All Dimensions are in mm
PI-1822-040296
Figure 7. EF20 Bobbin.
A
7/96
27
AN-18
TRIPLE INSULATED WIRE TRANSFORMER CONSTRUCTION
PARAMETERS FROM TABLE 6 SPREADSHEET
DESCRIPTION
SYMBOL
VALUE
CELL #
Core Type, Material,
Part #
-
EF20, Siemens N67
Part# B66311-G-X130
-
Bobbin Type,
Part #
-
EF20, 10 PIN, Siemens PIN
B66206-A 1110-T1
-
Number of Primary Turns
NP
94 turns
D45
Number of Secondary Turns
NS
9 turns
B30
Number of Bias Winding Turns
NB
9 turns
D46
Primary Wire Size
AWG
32 AWG
D56
Secondary Wire Size
AWGS
26 AWG Triple Insulated
D67 (See Text)
Bias Winding Wire Size
AWGB
24 AWG
See Text
Core Gapped Inductance
Coefficient
ALG
205 nH/T2 ±5%
C47
Primary Inductance
LP
1829 µH +/-10%
D44
Reinforced Insulation
Tape Width
BW
N/A
B27
12.0 cm
See Text
Basic Insulation
Tape Width
Margin Tape Width
M
N/A
B28
Sleeving Size
-
N/A
N/A
Table 8. Construction Parameters for Triple Insulated Wire Design Example.
Secondary Wire Size
From cell ( B66) of the Table 6 spreadsheet, a secondary bare
wire area of 540 circular mils is required to make the secondary
CMA equal the primary CMA. From cell (D67), the closest
AWG wire size that can satisfy this requirement with a single
wire is calculated as 22 AWG. This wire size is too large for use
at 100KHz, and several smaller parallel wires should be used
instead to allow full utilization of the wire cross-sectional area.
From the wire table in Appendix A, it can be seen that two
parallel strands of 26 AWG triple insulated wire (CM of 252.8
circular mils per wire) have a total bare wire area of 505.6
circular mils, which is within 10% of the required CM of 540
28
A
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circular mils. The current capacity of the parallel winding can
be calculated from the formula:
CMAS =
N × CM
ISRMS
CMAS is the current capacity of the secondary winding in
circular mils per ampere, N is the number of strands in the
secondary winding, CM is the bare area of a single secondary
conductor in circular mils (from the wire table in Appendix A),
and ISRMS is the secondary RMS current from cell (D62) of the
AN-18
spreadsheet. 26 AWG wire has a bare area of 252.8 circular
mils. Two parallel strands of 26 AWG triple insulated wire have
a current capacity of:
2 × 252.8
CMAS =
= 224.7 circular mils/ampere
2.25
This value is within 10% of the primary CMA of 243 circular
mils/ampere, and satisfies the CMA limit of 200-500 circular
mils per ampere.
Bias Wire Size
The bias winding wire size is chosen to fill as much of the
bobbin width as possible. Since there are usually relatively few
turns on the primary bias winding, this is best accomplished by
using a bifilar winding rather than a large diameter wire,
effectively doubling the number of physical turns. The required
TC to fill a single layer can be calculated as follows:
TC =
2 × N B × 10
2 × 9 × 10
=
BW − (2 × M ) 12 − (2 × 0)
= 15turns / cm
From the wire table, the closest wire size with a TC greater than
or equal to this value is 23 AWG, with a TC of 15.82 turns/cm.
This wire is too large to use with a small bobbin. A compromise
is to use the next smallest size, 24 AWG, which will not fill the
bobbin width completely, but is easier to terminate to the
bobbin pins. Since the output current of this winding is 10 mA
or less, there is no need to consider the current capacity of the
wire. The wire size in this case is determined by fill factor
requirements rather than current capacity.
Transformer Construction Style
Since this transformer is a triple insulated wire design for a
secondary regulated application, appropriate construction styles
are Figure 7B and 10B. Because this design is for a 15W
application, a split primary winding as shown in Figure 10B is
not necessary, and the more cost effective single section primary
design of Figure 7B should be used.
Tape Sizes
Since this is a triple insulated design, one size of tape is required
for basic insulation, with a width equal to BW. From cell (B27)
of the Table 6 spreadsheet, this is 12.0 mm.
Insulating Sleeving Size
Since this is a triple insulated wire design, no sleeving is
required
Gapped Core Inductance Coefficient
The ALG for this transformer design is given in cell (C47) of the
design spreadsheet, and should be used as the center value for
specifying the core ALG on the transformer specification.
Finished Triple Insulated Wire Transformer Design
The information required to assemble a transformer specification
for the triple insulated wire transformer example is summarized
in Table 8. A completed transformer schematic diagram and
parts list are shown in Figure 8. A construction drawing is
shown in Figure 9.
A
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29
AN-18
Pin 1
Primary
94T
#32 AWG
Pin 9, 10
Bifilar
SPECIFICATIONS
12V Secondary
9T
2x #26 AWG Primary Inductance - 1829 µH ±15%
Leakage Inductance < 40 µH
Triple Insulated
Pin 6, 7
Pin 2
Pin 4
Bifilar
Primary Bias
9T
2x #24 AWG
Pin 5
PARTS LIST FOR EF20 TRANSFORMER DESIGN EXAMPLE
Item Amt.
Description
Part #
Manufacturer
1
1pr.
Core, EF20 N67 Mat'l
B66311-G-X167
Siemens*
2
1ea.
Bobbin, EF20, 10 pin
B66206-A1110-T1
Siemens
3
A/R
Wire, 32 AWG Heavy Nyleze
4
A/R
Wire, 24 AWG Heavy Nyleze
5
A/R
Wire, 26 AWG Triple Insulated
6
A/R
Tape, Polyester 12.0 mm wide
#1296
3M
*Gap for ALG of 205 nH/T2 ±5%
PI-1815-040896
Figure 8. Parts List for EF20 Transformer Design Example.
30
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AN-18
TRIPLE INSULATED TRANSFORMER CONSTRUCTION
6,7
9,10
4
5
1
2
WINDING INSTRUCTIONS
Two-layer "C" Wound Primary
Basic Insulation
Start at pin 2. Wind 47 turns of 32 AWG heavy nyleze
wire from left to right. Apply 1 layer of polyester film
tape, 12.0 mm wide, for basic insulation. Continue
winding 47 turns from right to left. Finish at pin 1.
Apply 1 layer of 12.0 mm wide tape for basic
insulation.
Primary Bias
(Bifilar)
Start at pin 5. Wind 9 bifilar turns of 24 AWG heavy
nyleze wire in a single layer, from left to right. Finish at
pin 4.
Basic Insulation
Apply 1 layer of 12.0 mm wide tape for basic insulation.
Parallel Bifilar Triple
Insulated Secondary
Start at pin 9 & 10. Wind 9 bifilar turns of 26 AWG
triple insulated wire in approximately 1 layer from
left to right. Finish at pin 6 & 7.
Outer Insulation
Apply 3 layers of 12.0 mm wide tape for outer
insulation.
Final Assembly
Assemble and secure core halves.
Impregnate uniformly with varnish.
PI-1816-032896
Figure 9. EF20 Triple Insulated Design Example.
A
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31
AN-18
References
1) Power Integrations, Inc., AN-15, "Power Supply Design
Techniques for EMI and Safety"
2) Power Integrations, Inc., AN-16, "TOPSwitch Flyback
Fundamentals"
3) Power Integrations, Inc., AN-17, “Flyback Transformer
Design for TOPSwitch Power Supplies”
4) Power Integrations, Inc. DN-8, “Simple Bias Supplies Using
the TOP200”
5) Col. William McLyman, Transformer and Inductor Design
Handbook, New York, Marcel Dekker, Inc., 1978
6) Col. William McLyman, Magnetic Core Selection for
Transformers and Inductors, New York, Marcel Dekker, Inc.,
1982
7) Abraham I. Pressman, Switching Power Supply Design (2nd
ed.), New York, McGraw-Hill, Inc., 1991
8) Ferdinand C. Geerlings, “SMPS Power Inductor and
Transformer Design, Part 1”, Powerconversion International,
November/December 1979, pp. 45-52
9) Ferdinand C. Geerlings, “SMPS Power Inductor Design and
Transformer Design, Part 2”, Powerconversion International,
January/February 1980, pp. 33-40
10) Coilcraft, Inc., Technical Note Number 8110, “V.D.E.
Transformer Safety Requirements”
Power Integrations reserves the right to make changes to its products at any time to improve reliability or manufacturability.
Power Integrations does not assume any liability arising from the use of any device or circuit described herein, nor does it
convey any license under its patent rights or the rights of others.
PI Logo and TOPSwitch are registered trademarks of Power Integrations, Inc.
©Copyright 1994, Power Integrations, Inc. 477 N. Mathilda Avenue, Sunnyvale, CA 94086
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