ETC DRM064

Single Phase On-Line
UPS Using MC9S12E128
Designer Reference Manual
HCS12
Microcontrollers
DRM064
Rev. 0
09/2004
freescale.com
Single Phase On-Line UPS Using MC9S12E128
Designer Reference Manual
by: Ivan Feno, Pavel Grasblum and Petr Stekl
Freescale Semiconductor Czech System Laboratories
Roznov pod Radhostem, Czech Republic
To provide the most up-to-date information, the revision of our documents on the World Wide Web will be
the most current. Your printed copy may be an earlier revision. To verify you have the latest information
available, refer to:
http://freescale.com/
The following revision history table summarizes changes contained in this document. For your
convenience, the page number designators have been linked to the appropriate location.
Revision History
Date
Revision
Level
09/2004
0
Description
Initial release
Page
Number(s)
N/A
Single Phase On-Line UPS Using MC9S12E128
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Single Phase On-Line UPS Using MC9S12E128
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Freescale Semiconductor
Contents
Chapter 1
Introduction
1.1
1.2
1.2.1
1.2.2
1.2.3
1.3
Application Outline . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
The UPS Topologies and Features . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Passive Standby UPS Topology . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Line-Interactive UPS Topology . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
On-Line UPS Topology . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
MC9S12E128 Advantages and Features . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
13
13
14
15
16
17
Chapter 2
System Description
2.1
2.2
System Concept. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 19
System Specification . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 22
Chapter 3
UPS Control
3.1
3.1.1
3.1.2
3.1.3
3.1.4
3.1.5
3.1.6
Control Techniques . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Battery Charger Control . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Power Factor Correction Control . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
dc/dc Step-Up Converter Control . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Output Inverter Control. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
PI and PID Controller . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Phase-Locked Loop (PLL) Algorithm . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
25
25
27
28
30
32
33
Chapter 4
Hardware Design
4.1
4.2
4.2.1
4.2.2
4.2.3
4.2.4
4.2.5
4.2.6
4.2.7
4.3
4.3.1
4.4
4.4.1
4.4.2
4.5
System Configuration. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Battery Charger . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Operational Description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Battery Charger Topology . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Flyback Converter Operation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Design of Flyback Converter . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Voltage and Current Sensing, Current Limitation. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Main Line Detection . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Battery Charger Algorithm . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Auxiliary Power Supplies . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Auxiliary SMPS Design Considerations . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
dc/dc Step-Up Converter . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
dc/dc Converter Operational Description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
dc/dc Converter Design Considerations. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Power Factor Correction and Output Inverter . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
35
36
36
37
39
39
41
41
41
42
45
47
47
50
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4.5.1
4.5.2
4.5.3
4.5.4
PFC Booster Operational Description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
PFC Booster Design Considerations . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Output Inverter Operational Description. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Output Inverter Design Considerations . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
61
64
68
71
Chapter 5
Software Design
5.1
5.2
5.2.1
5.2.2
5.2.3
5.2.4
5.2.5
5.2.6
5.2.7
5.2.8
5.2.9
5.2.10
5.2.11
5.2.12
5.2.13
5.2.14
5.2.15
5.3
5.3.1
5.3.2
5.3.3
5.3.4
5.4
5.4.1
Introduction . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Data Flow . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Software Variables and Defined Constants . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Process PLL Algorithm. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Process RMS Correction . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Process Mains Line Detection . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Process Ramp . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Process Sine Wave Reference . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Process Button Processing . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Process LED Processing . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Process Application State Machine . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Process PFC Control . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Process Sine Wave Reference (PFC) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Process dc Bus Scaling . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Process dc/dc Step-Up Control . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Process Inverter Control . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Process Battery Charge Control . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Main Software Flowchart . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Initialization of Peripherals and Variables . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Periodic Interrupts . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Event Interrupts . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Interrupt Time Execution and MCU Load Estimation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Software Constant Calculations . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
PI and PID Controller Constants . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
73
73
73
76
76
76
76
76
76
76
76
77
78
78
78
78
78
78
78
80
83
83
85
85
Chapter 6
Tests and Measurements
6.1
6.2
6.3
6.3.1
6.3.2
6.3.3
6.3.4
6.3.5
6.3.6
6.3.7
Test Equipment . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Load Parameters . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Test Results . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Overall Efficiency at Linear Load . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Overall Efficiency at Non-linear Load. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Output Frequency Measurement . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Output Voltage THD. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Power Factor Measurement. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Response on Step Load. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Summary . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
87
87
88
88
89
90
91
92
92
95
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Chapter 7
System Set-Up and Operation
7.1
7.1.1
7.2
7.2.1
7.2.2
7.2.3
7.2.4
7.3
7.3.1
7.3.2
7.3.3
Hardware Setup . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 97
Setting of Mains Line System. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 99
Software Setup . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 100
Application Software Files . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 100
Application PC Master Software Control Files . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 100
Application Build. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 101
Programming the MCU . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 102
Application Control . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 102
On-line Operation. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 102
Battery Operation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 103
Remote Operation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 104
Appendix A. Schematics
A.1
A.2
A.3
A.4
A.5
A.6
Schematics of Power Stage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Schematics of User Interface . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Schematics of Input Filter . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Parts List of UPS Power Stage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Parts List of User Interface . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Parts List of Input Filter . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
105
115
117
119
123
124
Appendix B. References
Appendix C. Glossary
Single Phase On-Line UPS Using MC9S12E128
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Single Phase On-Line UPS Using MC9S12E128
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Figures
1-1
1-2
1-3
2-1
2-2
2-3
2-4
2-5
2-6
3-1
3-2
3-3
3-4
3-5
3-6
3-7
3-8
3-9
3-10
4-1
4-2
4-3
4-4
4-5
4-6
4-7
4-8
4-9
4-10
4-11
4-12
4-13
4-14
4-15
4-16
4-17
4-18
4-19
4-20
4-21
4-22
5-1
Passive Standby UPS Topology . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Line-Interactive UPS Topology . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
On-Line UPS Topology . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
System Concept of UPS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
UPS Power Stage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Input Filter . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
User Interface . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
MC9S12E128 Controller Board. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Overall View of the UPS Demo . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Battery Charger Algorithm. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
PFC Control Algorithm . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Hysteresis Control of Input Current . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Push-Pull Converter PWM Patterns . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
dc/dc Step-Up Converter Control Algorithm . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Sine Wave Modulation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Inverter Control Algorithm . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Simulated PID Controller Response on Input Step . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Quality Control of Non-Linear Load. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Calculation of Phase Difference . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
System Concept of UPS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
UPS Power Stage Block Schematic . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Battery Charger Schematics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Battery Charger Transformer Winding Layout. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
3-Stage Charging Algorithm . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Auxiliary SMPSs . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Isolated Flyback Converter for Drivers . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Flyback Power Transformer Layout of Windings. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
dc/dc Converter Schematic . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
dc/dc Converter Simulation Model Schematic. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Simulated Magnetizing Voltage and Magnetic Charge . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Simulated Primary Winding Current . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Simulated Secondary Winding Current . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Simulated Drain-to-Source and Gate-to-Source MOSFETs Voltages. . . . . . . . . . . . . . . . . .
dc/dc Power Transformer Layout of Windings . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Inverter MOSFET Power Analysis. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Rectifier Diode Voltage and Current Waveform . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Secondary Voltage and Rectified Current Waveforms . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
PFC Power Stage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
PFC Current Controller . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Output Inverter Power Circuit . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Inverter IGBT Gate Drive Circuitry . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Main Data Flow . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
14
15
16
19
20
20
21
21
22
26
27
28
28
29
30
31
31
32
34
35
36
38
40
41
42
44
47
48
49
51
53
54
55
56
58
59
61
62
63
69
70
74
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
9
Figures
5-2
5-3
5-4
5-5
5-6
5-7
5-8
5-9
6-1
6-2
6-3
6-4
6-5
6-6
6-7
6-8
6-9
6-10
6-11
6-12
6-13
6-14
7-1
7-2
7-3
7-4
7-5
7-6
7-7
7-8
7-9
7-10
7-11
7-12
7-13
7-14
7-15
7-16
Application State Machine. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 77
Background Loop . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 79
Structure of PMF Interrupt. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 80
Structure of ATD Conversion Complete Interrupt . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 81
TIM0 CH4 Input Capture Interrupt. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 82
Structure of TIM0 CH5 Output Compare Interrupt . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 82
Structure of TIM0 CH6 Output Compare Interrupt . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 83
CPU Load of UPS Application. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 84
Non-Linear Load . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 87
Overall Efficiency at Linear Load. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 88
Output Voltage and Current at Linear Load . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 88
Overall Efficiency at Non-linear Load . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 89
Output Voltage and Current at Non-linear Load . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 89
Output Frequency in Synchronized Mode . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 90
Output Frequency in Free-running Mode . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 90
Output Voltage and Current at Non-linear Load — Detail . . . . . . . . . . . . . . . . . . . . . . . . . . . 91
Output Voltage and Current at Non-linear Load . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 91
Power Factor Measurement . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 92
Load Step from 20% to 100% . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 93
Load Step from 20% to 100% — Detail. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 93
Load Step from 100% to 20% . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 94
Load Step from 100% to 20% — Detail. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 94
UPS Demo . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 98
UPS Input and Outputs . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 99
UPS Serial Ports and External Battery Connector . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 99
Execute Make Command . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 101
UPS User Interface . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 103
UPS Project in FreeMaster . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 104
Block Schematic . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 106
Auxiliary Power Supplies. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 107
Battery Charger . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 108
Control Board Interface . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 109
dc/dc Step-Up Converter. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 110
Analog Sensing Circuits . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 111
PFC and Inverter IGBT Drivers . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 112
PFC and Inverter . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 113
PFC Current Control Circuit . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 114
UPS User Interface . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 116
Single Phase On-Line UPS Using MC9S12E128
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Freescale Semiconductor
Tables
2-1
4-1
4-2
4-3
4-4
4-5
4-6
4-7
4-8
4-9
4-10
4-11
4-12
4-13
4-14
5-1
5-2
5-3
6-1
A-1
A-2
A-3
On-Line UPS Specification . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 23
Battery Charger Parameters . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 37
Input Design Parameters of Flyback Converter . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 39
Required Parameters of Flyback Transformer . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 40
Measured Values on the Sample . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 40
dc/dc Converter Specifications . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 47
dc/dc Transformer Specification . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 56
Digital PFC Specifications . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 61
PFC Inductor Parameters . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 66
Design Parameters for Core P/N: T175-8/90 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 66
dc-bus Capacitor Parameters . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 68
Output Inverter Specifications . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 68
MKP 338 4 X2 Capacitor Reference Data . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 71
Output Filter Inductor Parameters . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 72
Design Parameters for Core P/N: T175-8/90 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 72
Software Variables . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 75
Execution Time of Periodic Interrupts . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 84
Size of UPS Application Code . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 84
Summary of Measured Parameters . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 95
Parts List of UPS Power Stage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 119
Parts List of User Interface . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 123
Parts List of Input Filter . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 124
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
Freescale Semiconductor Internal Use Only
Draft For Review - September 30, 2004
11
Tables
Single Phase On-Line UPS Using MC9S12E128
12
Freescale Semiconductor Internal Use Only
Draft For Review - September 30, 2004
Freescale Semiconductor
Chapter 1
Introduction
1.1 Application Outline
This reference design describes the design of a single phase on-line uninterruptable power supply (UPS).
UPSs are used to protect sensitive electrical equipment such as computers, workstations, servers, and
other power-sensitive systems.
This reference design focuses on the digital control of key parts of the UPS system. It includes control of
a power factor correction (PFC), a dc/dc step-up converter, a battery charger, and an output inverter. The
dc/dc converter and the output inverter are fully digitally controlled. The PFC and the battery charger are
implemented by a mixed approach, where an MCU controls the signals for PFC current and battery
current demands. The digital control is based on Freescale Semiconductor’s MC9S12E128
microcontroller, which is intended for UPS applications.
The reference design incorporates both hardware and software parts of the system including hardware
schematics.
1.2 UPS Topologies and Features
UPSs are divided into several categories according to their features, which come from the hardware
topologies used. The three basic categories are:
• Passive standby UPS
• Line-interactive UPS
• On-line UPS
The category of the UPS defines the basic behaviors of the UPS, mainly the quality of the output voltage
and the capability to eliminate different failures on the power line (power sags, surge, under voltage, over
voltage, noise, frequency variation, and so on).
NOTE
Although specific tools, suppliers, and methods are mentioned in this
document, Freescale Semiconductor does not recommend or endorse any
particular methodology, tool, or vendor.
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
13
Introduction
1.2.1 Passive Standby UPS Topology
The common topology of the passive standby UPS is depicted in Figure 1-1.
LINE FILTER
BATTERY
CHARGER
AC
~
=
DC
=
DC
SWITCH
AC
~
INVERTER
+
-
Normal operation
Backup operation
BATTERY
Figure 1-1. Passive Standby UPS Topology
During normal operation, while the mains line (the power cord for the ac line) is available, the load is
directly connected to the mains. The battery is charged by the charger, if necessary. If a power failure
occurs, the switch switches to the opposite position, and the load is powered from the batteries. An
inverter converts the battery dc voltage level to an ac mains level. The inverter generates a square wave
output.
The advantage of passive standby topology is its low cost and high efficiency. The disadvantage is limited
protection against power failures. Because the load is connected to the mains line through the filter only,
the load is saved against short sags and surges.
Single Phase On-Line UPS Using MC9S12E128
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Freescale Semiconductor
UPS Topologies and Features
1.2.2 Line-Interactive UPS Topology
The improved topology, called line-interactive, is showed in Figure 1-2. The functionality of the
line-interactive UPS is similar to passive standby topology. During normal operation, the load is
connected directly to the mains line (the power cord to the ac line). Besides the input filter, there is a
transformer with taps connected between the mains line and the load. The transformer usually has three
taps. It ensures that the output voltage can be increased or decreased relative to the mains line by
typically 10 to 15%.
The features of the line-interactive topology are similar to passive standby UPSs. The cost is still quite
low and efficiency is high. The protection against power failures is improved by the possibility of keeping
the output voltage within limits during under voltage or over voltage using the tap transformer.
BYPASS
AVR
LINE FILTER
BATTERY
CHARGER
AC
~
=
DC
=
DC
AC
~
SWITCH
INVERTER
+
-
Normal operation
Backup operation
BATTERY
Figure 1-2. Line-Interactive UPS Topology
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
15
Introduction
1.2.3 On-Line UPS Topology
Another topology, called on-line, is shown in Figure 1-3. This topology is also called double conversion.
This name arises from the operating principle of an on-line UPS. When the UPS works in normal operation
mode, while the mains line (or the power cord for the ac line) is available, the input voltage is rectified to
the dc bus. The power factor correction ensures a sinusoidal current in phase with the input voltage. Then
the UPS behaves as a resistive load. The output inverter converts the dc bus voltage back to a pure
sinusoidal voltage.
The dc/dc converter is connected to the dc bus and converts the battery voltage to the dc bus level. The
converter is activated during a power failure, and delivers the energy stored in the batteries to the dc bus.
The dc bus voltage is again converted to a pure sine voltage.
A battery charger is used to charge the batteries. The charger can be powered from the mains line or from
the dc bus.
BYPASS
RECTIFIER
PFC
IN
DC
=
BATTERY
CHARGER
OUT
AC
AC
~
~
DC
=
=
DC
INVERTER
=
DC
DC-DC
CONVERTER
+
-
Normal operation
Backup operation
BATTERY
Figure 1-3. On-Line UPS Topology
As can be seen, the complexity of the on-line UPS is much greater than the other two topologies
described in this section. This means that the cost is higher, and the efficiency is lower due to double
conversion.
However, the on-line UPS brings a much higher quality of delivered energy. The UPS generates a pure
sine wave output with tight limits (typically ±2%). Besides the power failures eliminated by previous
topologies, the on-line UPS avoids all the failures relating to frequency disturbance, such as frequency
variation, harmonic distortion, line noise, or other shape distortions.
Single Phase On-Line UPS Using MC9S12E128
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Freescale Semiconductor
MC9S12E128 Advantages and Features
1.3 MC9S12E128 Advantages and Features
The MC9S12E Family is a 112-/80-pin low-cost 16-bit MCU family very suitable for UPS, SMPS, and
motor control applications. All members of the MC9S12E Family contain on-chip peripherals including a
16-bit central processing unit (HCS12 CPU), up to 256K bytes of Flash EEPROM, up to 16K bytes of
RAM, three asynchronous serial communications interface modules (SCI), a serial peripheral interface
(SPI), an inter-IC bus (IIC), three 4-channel 16-bit timer modules (TIM), a 6-channel 15-bit pulse-width
modulator with fault protection module (PMF), a 6-channel 8-bit pulse width modulator (PWM), a
16-channel 10-bit analog-to-digital converter (ATD), and two 1-channel 8-bit digital-to-analog converters
(DAC).
The basic features of the key peripherals dedicated for UPS applications are listed below:
• Two 1-channel digital-to-analog converters (DAC) with 8-bit resolution
• Analog-to-digital converter (ATD)
– 16-channel module with 10-bit resolution
– External conversion trigger capability
• Three 4-channel timers (TIM)
– Programmable input capture or output compare channels
– Simple PWM mode
– Counter modulo reset
– External event counting
– Gated time accumulation
• 6 PWM channels (PWM)
– Programmable period and duty cycle
– 8-bit 6-channel or 16-bit 3-channel
– Separate control for each pulse width and duty cycle
– Center-aligned or left-aligned outputs
– Programmable clock select logic with a wide range of frequencies
– Fast emergency shutdown input
• 6-channel pulse width modulator with fault protection (PMF)
– Three independent 15-bit counters with synchronous mode
– Complementary channel operation
– Edge and center aligned PWM signals
– Programmable dead time insertion
– Integral reload rates from 1 to 16
– Four fault protection shut down input pins
– Three current sense input pins
The MC9S12E Family is powerful enough to control on-line and line-interactive UPS topologies. The
passive standby topology can be controlled by a simpler MCU (from the HC08 Family).
Digital control has many advantages over separate analog control. Digital control is more flexible and
allows easier tuning and changing of the UPS parameters. The intercommunication and interaction
between all modules can implemented very efficiently because all modules are controlled by a single
MCU.
The UPS control area is very wide. Each topology can be implemented by different circuits. The circuits
may differ by different control requirements. This reference design shows one of the ways to implement
digital control of an on-line UPS. The design mainly focuses on low cost. A low-cost 16-bit MCU is used
with simple analog circuits. Using a mixed approach to battery charging can also be cheaper than full
digital control, depending on chosen circuit topology.
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
17
Introduction
Single Phase On-Line UPS Using MC9S12E128
18
Freescale Semiconductor
Chapter 2
System Description
2.1 System Concept
The system concept of the UPS is shown in Figure 2-1. Input consists of a rectifier (D1, D5) and a power
factor correction (L1, D2, Q2). The power factor correction is controlled by a mixed approach. The dc-bus
voltage control loop of PFC is controlled by the MCU. The output of the voltage controller defines the
amplitude of the input current. Based on the required amplitude, the MCU generates a current reference
signal. The current reference signal inputs to an external logic, which performs current controller working
in hysteresis mode.
DC-AC
PFC
L1
D1
D2
KBU8J
IN
-
Q1
+
+
Q2
D3
C1
IN
C2
+
Q3
D4
GND
OUT
D5
Filter
OUT
DC-DC Converter
D6
D7
L2
D8
L3
Q4
T1
GND
Q5
Charger
(Flyback
Converter)
BT1
GND
D9
GND
Figure 2-1. System Concept of UPS
Output is provided by an output inverter (Q1, Q3, D3, D4). The inverter converts the dc bus voltage back
to a sinusoidal voltage using pulse-width modulation. The output inverter is fully controlled by the MCU
and generates a pure sinusoidal waveform, free of any disturbance.
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
19
System Description
The battery BT1 supplies a load during the backup mode. There are two 12-V batteries connected in
serial. The battery voltage level 24-V is converted to ±390-V by the dc/dc step-up converter (Q4, Q5,
D6-D9, L2, L3, and T1) using a push-pull topology fully controlled by the MCU.
The last part of a UPS is a battery charger. The battery charger maintains a fully charged battery. It uses
a flyback topology controlled by a mixed approach. The flyback converter is controlled by a dedicated
circuit and the required output voltage and current limit are set by the MCU. A dedicated circuit is used
due to the lower cost compared to direct MCU control. Where a different battery charger topology is used,
there is still enough MCU power to provide digital control.
Figure 2-2. UPS Power Stage
The UPS consists of four PCBs. Most components are situated on the power stage (see Figure 2-2).
These are all the power components (diodes, transistors, inductors, capacitors, relays, and so on) and
analog sensing circuits. The power stage is connected to the mains line (power cord for the ac line)
through an input line filter, realized on the next PCB (Figure 2-3).
Figure 2-3. Input Filter
Single Phase On-Line UPS Using MC9S12E128
20
Freescale Semiconductor
System Concept
Figure 2-4 shows the user interface PCB. It includes two buttons (ON/OFF, BYPASS), four status LEDs
(on-line, on-battery, bypass, and error), and six LEDs indicating output power or remaining battery
capacity. There are also two serial RS232 ports, which can used for communication with the PC. The user
interface provides an extension of the serial ports, which are implemented on the MC9S12E128 controller
board.
Figure 2-4. User Interface
Figure 2-5. MC9S12E128 Controller Board
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
21
System Description
Figure 2-5 shows a controller board for the MC9S12E128. The MC9S12E128 controller board is designed
as a versatile development card for developing real-time software and hardware products to support a
new generation of applications in UPS, servo and motor control, and many others.
The power of the 16-bit MC9S12E128, combined with Hall-effect/quadrature encoder interface, circuitry
for automatic current profiling, over-current logic and over-voltage logic, and two isolated RS232
interfaces, makes the MC9S12E128 controller board ideal for developing and implementing many motor
controlling algorithms, UPS, SMPS, as well as for learning the architecture and instruction set of the
MC9S12E128 processor.
For more detailed information on the MC9S12E128 controller board, see [33].
An overall view of the assembled UPS is shown in Figure 2-6.
Figure 2-6. Overall View of the UPS Demo
2.2 System Specification
The UPS is designed to meet the features and parameters mentioned in Table 2-1.
Single Phase On-Line UPS Using MC9S12E128
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Freescale Semiconductor
System Specification
Table 2-1. On-Line UPS Specification
Features
Parameters
Single Phase On-Line UPS using MC9S12E128
Architecture and Concept
The UPS should be a regenerative 1-phase online type UPS with an automatic bypass
feature when self check fails or is overloaded. The UPS is controlled manually from a front
panel switch and from PC application software.
On-line: If the input power is available, the UPS supplies a load and eliminates all possible
defects on the line (online double conversion)
Battery: If the input power is not available, the UPS supplies a load from batteries. The
backup time is given by battery capacity.
Functional Modes
Bypass: The UPS directly connects its output and input, so the load is directly connected to
the input line. The transition to this mode is set manually or automatically during overload or
fault
Fault: If any fault is detected, the UPS signals fault, and if it is possible, the bypass is
activated.
45 to 65 Hz Operating Frequency Range
120 V (at 25% of load) — 280 V Operating Voltage Range for nominal mains 230 V
Input
85 V to 135 V Operating Voltage Range for nominal mains 110 V
Power factor at input > 0.95 at nominal voltage
Conversion efficiency > 85% at nominal output power
Number of output ports 6 in 2 segments
Output voltage selectable 110/120/200/220/230/240 V
Output power 725 – 750 VA at 230 V mains input voltage
Output
Output power 325 – 350 VA at 110 V mains input voltage
Output waveform: true sine wave < 5% THD
Output frequency 50/60 Hz +/-0.3%
Output load regulation +/-2% (at steady state and linear load)
Battery
Communication
Battery 2*12 V
Battery 7.2 Ah
2x RS232 port for communication with host PC with opto-isolation implemented on
MC9S12E128 Controller Board
4 LED indicators (on-line, battery, bypass, fault)
Visual Interface
battery level gauge 6 levels (<5/20/40/60/80/100%)
load level gauge 6 levels (20/40/60/80/100/>100%)
Control Interface
2x buttons for user control (on/off, bypass)
Fault
Audible warning
Overload
low battery
lasts 5 minute
Implementation
Coding in C language according to ANSI C standard for software running on MCUs
Coding in assembler if needed for software running on MCUs
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
23
System Description
Single Phase On-Line UPS Using MC9S12E128
24
Freescale Semiconductor
Chapter 3
UPS Control
3.1 Control Techniques
Generally, a UPS consists of several different converters. So the control techniques differ with the
converter topologies used. The presented implementation of on-line UPS includes following topologies:
• Battery charger: flyback converter (mixed control)
• PFC: boost converter (mixed control)
• dc/dc step up converter: push-pull converter (full digital control)
• Output inverter: half bridge inverter (full digital control)
3.1.1 Battery Charger Control
The battery charger uses a flyback converter topology. As described in Chapter 4 Hardware Design, the
flyback converter is controlled by a dedicated circuit in order to reduce cost. The interface between the
flyback converter and the MCU incorporates one digital output, which allows the setting of two output
voltage levels, and an analog output, which sets the current limit.
Using a dedicated circuit greatly simplifies the control algorithm. The functionality of the converter itself is
ensured by the dedicated circuit. Therefore, the battery charger software focuses on the charging
algorithm, whose software block diagram is shown in Figure 3-1.
The algorithm reads the current flowing to the batteries. The current value is compared with the maximal
and float thresholds. If the value is close to the maximal value, the battery charger state is set to bulk
charging and the output voltage level is set to the higher value (PU7 set to logic 1). If the actual current
value is between the maximal and float thresholds, the battery charger is considered to be in the
absorption state. The output voltage is still kept at a high level. As soon as the current value reaches the
float threshold, the battery charger goes to the float state, and the output voltage is set to the lower level.
The current limit is set during initialization, according to the number of batteries and their capacity.
The control algorithm is called every 50 ms.
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
25
UPS Control
MC9S12E128
Output Voltage
PU7
Charging Current Limit
PWM10
yes
IBAT = Imax
no
Bulk mode
Set HV level
yes
IBAT > 0.05C
no
Absorption mode
Set HV level
Float mode
Set LV level
Battery Voltage
AN03
AN02
Battery current
Figure 3-1. Battery Charger Algorithm
Single Phase On-Line UPS Using MC9S12E128
26
Freescale Semiconductor
Control Techniques
3.1.2 Power Factor Correction Control
The control algorithm of the PFC is depicted in Figure 3-2. The algorithm includes two control loops. The
inner control loop maintains a sinusoidal input current. The outer loop controls the dc bus voltage. The
result of the outer control loop is the desired amplitude of the input current.
MC9S12E128
PFC ENABLE
PU8
DA0
UREQ +
PI Controller
+
-
SIN REFERENCE
SINUS
GENERATION
IOC04
Zero Cross
PLL LOCK
FAULT1
FAULT0
F
I
L
T
E
R
Top DC Overvoltage
Bottom Overvoltage
AN07
Top DC Bus Voltage
AN08
Bottom DC Bus Voltage
Figure 3-2. PFC Control Algorithm
The current control loop is partially performed by an external circuit. This control technique is also called
“indirect PFC control”. The external circuit compares the actual input current with a sine wave reference.
If the actual current crosses the lower border of sine waveform, the PFC transistor is switched on. As soon
as the input current reaches the upper border, the PFC transistor is switched off. The resulting input
current can be seen in Figure 3-3. Maximal switching frequency (50 kHz) corresponds to the hysteresis
defined by resistors R664 and R675. (see Figure 4-20)
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
27
UPS Control
Sine
Reference
Hysteresis
Levels
Input current
Figure 3-3. Hysteresis Control of Input Current
The software part of the current loop generates the sine wave reference. The sine wave reference is
synchronized to be in phase with the input voltage. The sine wave generator is calculated every 50 µs.
The sine waveform is generated directly by the D/A converter within the range of the voltage reference.
The voltage control loop is fully implemented by software. The sensed dc bus voltage is compared with
the required dc bus voltage, 390 V. The difference inputs to the PI controller. The PI controller output
directly defines the amplitude of the input current. The PI controller constants were experimentally tuned
to get an aperiodic responds to the input step. The constants are P = 100 and T I = 0.016 s. The voltage
control loop is calculated every 1 ms.
The two hardware faults are immediately able to disable the PWM outputs in case of a dc bus over
voltage. The digital output, PU8, enables/disables the external logic providing the current loop.
3.1.3 dc/dc Step-Up Converter Control
The dc/dc converter uses push-pull topology, which requires the PWM signals as shown in Figure 3-4.
These signals can be generated by one pair of PMF outputs with the following configuration:
• even output is set to positive polarity
• odd output is set to negative polarity
• duty cycle of even output is set to X%
• duty cycle of odd output is set to 100 - X%
where X is a value from 0 to 50% – dead time
The required PWM patterns are shown in Figure 3-4.
PWM 4
PWM 3
Figure 3-4. Push-Pull Converter PWM Patterns
Single Phase On-Line UPS Using MC9S12E128
28
Freescale Semiconductor
Control Techniques
The control algorithm is depicted in Figure 3-5. Both dc bus voltages pass the digital filter, and their sum
is compared with the required value of the dc bus voltage. Based on the error, the PI controller sets the
desired duty cycle of the switching transistors.
During mains line operation, the required value of the dc bus is set to 720 V (2 x 360 V). Because the dc
bus is kept by the PFC at 780 V (2 x 390 V), the dc/dc converter is automatically switched off. In case of
mains failure, the dc bus voltage will start to fall. As soon as the voltage reaches the value 720 V, the
dc/dc converter is activated. At 720 V, there is still 20 V reserve in amplitude to generate a maximum
output voltage of 240 V RMS. As soon as the operation from batteries is recognized, the required value
of the dc bus voltage is increased back to 780 V.
The PI controller maintains the constant voltage on the dc bus independent of the load until the mains is
restored or the battery is fully discharged. If the battery is discharged, the UPS output is deactivated and
UPS stays in STANDBY ON BATTERY mode. After 1 minute, the UPS is switched off.
The PI controller constants were experimentally tuned in the same way as the PFC. The constants are
P = 39 and TI = 0.0033 s. The control loop is calculated every 1 ms.
MC9S12E128
PMF3
Output Transistors
UREQ
PMF4
+
-
PI Controller
FAULT1
FAULT0
+
+
F
I
L
T
E
R
Top DC Overvoltage
Bottom DC Overvoltage
AN07
Top DC Bus Voltage
AN08
Bottom DC Bus Voltage
Figure 3-5. dc/dc Step-Up Converter Control Algorithm
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
29
UPS Control
3.1.4 Output Inverter Control
The output inverter is implemented by two IGBT transistors in half bridge topology. The inverter is fully
digitally controlled and generates a pure sine wave voltage.
The sine waveform is generated using the pulse-width modulation technique. The sine reference is stored
in a look-up table. The table values are periodically taken from the table, and then multiplied by the
required amplitude. The resulting value gives the duty cycle of the PWM output. The pointer to the table
is incremented by a value, which corresponds to the desired output frequency. All values over one period
give sinusoidal modulated square wave output (see Figure 3-6). If such a signal passes through a LC
filter, the pure sine wave voltage is generated on the inverter output.
+DCBUS
-DCBUS
Figure 3-6. Sine Wave Modulation
The control algorithm can be seen in Figure 3-7. The main control loop comprises of the PID controller
and a feed forward control technique. The required value entering the PID controller is generated by a
sine wave generator, optionally synchronized with input voltage. The same value is added directly to the
output of the PID controller. It is called the feed forward technique, and it improves the responds of control
loop. The amplitude of the sine wave reference is corrected by RMS correction, which keeps the RMS
value of the output voltage independent of any load. The RMS correction uses the PI controller. The PI
constants were experimentally tuned, and set to P = 0 and TI = 0.00936.
The PID controller was tuned using simulation in MATLAB. The results of the simulation can be seen in
Figure 3-8 and Figure 3-9, with P = 0.6, TI = 0, TD = 0.00071 s, and N = 31. The value N represents the
filter level of D portion EQ 3-5.
The result of the PID controller, including feed forward, is scaled relative to actual dc bus voltage. Then
the exact duty cycle is set to the PMF module.
Single Phase On-Line UPS Using MC9S12E128
30
Freescale Semiconductor
Control Techniques
Figure 3-7. Inverter Control Algorithm
Figure 3-8. Simulated PID Controller Response on Input Step
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
31
UPS Control
Figure 3-9. Quality Control of Non-Linear Load
3.1.5 PI and PID Controller
The PI controller in a continuous time domain is expressed by following equation:
1 t
u ( t ) = K e ( t ) + ----- ∫ e ( τ ) dτ
TI 0
(EQ 3-1)
Similarly, the PID controller can be expressed as:
1 t
d
u ( t ) = K e ( t ) + ----- ∫ e ( τ ) dτ + T D ----- e ( t )
TI 0
dt
(EQ 3-2)
In a Laplace domain it can be written as:
1
u ( s ) = K e ( s ) + -------- e ( s )
sT I
(EQ 3-3)
1
u ( s ) = K e ( s ) + -------- e ( s ) + sT D e ( s )
sT I
(EQ 3-4)
To improve the response of the PID controller to noisy signals, the derivative portion is often replaced by
a derivative portion with filter:
sT D
sTD ≈ ------------------sT
1 + --------DN
(EQ 3-5)
For implementation of algorithms on MCU the equations EQ 3-3 and EQ 3-4 have to be expressed in
discrete time domain like:
u ( kh ) = P ( kh ) + I ( kh ) + D ( kh )
(EQ 3-6)
Single Phase On-Line UPS Using MC9S12E128
32
Freescale Semiconductor
Control Techniques
where
P ( kh ) = K ⋅ e ( kh )
(EQ 3-7)
Kh
I ( kh ) = I ( kh – h ) + ------- e ( kh )
TI
(EQ 3-8)
TD
KT D N
D ( kh ) = --------------------- D ( kh – h ) – --------------------- e ( kh – h )
T D + Nh
T D + Nh
(EQ 3-9)
e ( kh ) = w ( kh ) – m ( kh )
(EQ 3-10)
and
e(kh)
=
Input error in step kh
w(kh)
=
Desired value in step kh
m(kh)
=
Measured value in step kh
u(k)
=
Controller output in step kh
P(kh)
=
Proportional output portion in step kh
I(kh)
=
Integral output portion in step kh
D(kh)
=
Derivative output portion in step kh
TI
=
Integral time constant
T, h
=
Sampling time
K
=
Controller gain
t
=
Time
s
=
Laplace variable
N
=
Filter constant
3.1.6 Phase-Locked Loop (PLL) Algorithm
The PLL algorithm provides synchronization with the mains line. This synchronization is necessary for the
PFC algorithm and can be optionally used for the inverter output.
The algorithm consists of two parts:
• Frequency lock
• Phase lock
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
33
UPS Control
The PLL algorithm measures a period from last two zero crossing signals. Because calculation of the
phase increment to the sine wave table requires a division instruction EQ 3-11, the phase over one-half
period is calculated instead:
T
Phase Increment = 32767 ----------------Period
(EQ 3-11)
where
T
=
period of sine wave algorithm (50 µs)
32767
=
180º in sine wave look up table
Period
=
measured period of main line voltage
If phase increment just corresponds to the measured period we should get a phase of 180º. If there is
some difference, the phase increment must be adjusted (see Figure 3-10). Based on the sign of the phase
difference, the phase increment is incremented or decremented by the value which is equal to the phase
difference multiplied by the PLL constant.
If the phase difference falls below some limit for last 20 periods, the PLL is locked to the line frequency
and a frequency locked status bit is set.
Actual Period
Zerocrossing
Signal
Actual
Phase
180º
0º
Actual Phase
Increment
Phase
Difference
Figure 3-10. Calculation of Phase Difference
Now the PLL is running with the same frequency as the mains line, but the phase is still different. As soon
as the frequency status bit is set, the actual phase is adjusted to 0º or 180º according to the previous
polarity of the input voltage. The polarity of the input voltage is sensed in the middle of each period.
Single Phase On-Line UPS Using MC9S12E128
34
Freescale Semiconductor
Chapter 4
Hardware Design
4.1 System Configuration
The single phase on-line UPS reference design is 750 VA UPS representing an on-line topology. The
UPS comprises four PCBs (power stage, user interface, input filter, and controller board). The power
stage together with the MC9S12E128 controller board is shown in Figure 1-2
Figure 4-1. System Concept of UPS
The UPS reference design provides both a ready-to-use hardware and a ready-made software
development platform for an on-line UPS, under 1000 VA output power, and controlled by a single 16-bit
MCU.
The UPS power stage consists of several system blocks shown as:
• Battery Charger
• Auxiliary Power Supplies
• Control Board Interface
• dc/dc Step-Up Converter
• PFC + Inverter
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
35
Hardware Design
J101
PSH02_02P
J100
J104
J103
1
2
J102
Auxiliary Power Supplies
+VBAT
-5V_TOP
GND_TOP
+15V_TOP
-5V_BOT
GND_BOT
+15V_BOT
+VBAT
GND_PFC
+15V_PFC
FUSE AUTO 40A
+5V_A
+5V_D
+15V
3
4
+5V_REF
1
2
GNDA
GND
/POWER_EN
POWER_EN
F101
Battery Charger
L
J105
L
N
F102
+5V_A
+5V_A
GNDA
GND
6.3A/fast
GNDA
/POWER_ON
GND
F100
+VBAT
-VBAT
+15V
+5V_D
+5V_A
+15V_TOP
-5V_TOP
-5V_BOT
GND_BOT
+15V_PFC
GNDA
VBAT
IBAT
J106
GND_TOP
+15V_BOT
GND
HV_BAT_LEVEL
IBAT_CONTROL
2A/fast
N
+VBAT
-VBAT
GND_PFC
+5V_REF
-5V_TOP
GND_TOP
+15V_TOP
-5V_BOT
GND_BOT
+15V_BOT
GND_PFC
+15V_PFC
+5V_A
+5V_D
+15V
L1
L2
N
PE
PE MH100
GNDA
GND
+5V_REF
PFC+Inverter
PE CONNECTION
PWM_TOP
PWM_BOT
J107
Control Board Interface
OUT1
OUT2
N_OUT
DCB_POS
DCB_NEG
RLY_IN
RLY_BYPASS
RLY_OUT1
RLY_OUT2
FAULT0
FAULT1
AD2
AD3
J108
FAN_PWM
V_DCB_TOP
V_DCB_BOT
V_IN
I_IN
V_OUT_TOP
V_OUT_BOT
I_OUT
TEMP
+5V_D
+5V_A
+15V
PWM10
PWM12
TIM14
TIM15
TIM16
TIM17
DIV1
DIV2
UNI-3 PFC_EN
PFC_ZC
GND
GNDA
GND
+5V_D
+5V_A
+15V
DA0
DA1
GNDA
J109
FAN+
FAN-
J110
1
2
AD1
AD4
UNI-3_PWM2
AD5
UNI-3_PWM3
AD6
UNI-3_PWM4
UNI-3 PHAIS UNI-3_PWM5
UNI-3 PHCIS
UNI-3 DCBI UNI-3 PFC_EN
UNI-3 DCBV UNI-3 SERIAL
PSH02_02P
J111
1
2
PSH02_02P
UNI-3 BEMFZCA
UNI-3 BEMFZCC
UNI-3 BEMFZCB
UNI-3 PFC_ZC
DA0
DA1
Fault1
Fault0
DC-DC Step Up
GND
GNDA
GND
GNDA
+VBAT
-VBAT
+VBAT
-VBAT
DCB_POS
DCB_NEG
PWM4
PWM5
Figure 4-2. UPS Power Stage Block Schematic
4.2 Battery Charger
4.2.1 Operational Description
The battery charger is intended for charging the UPS batteries and supplying all UPS control circuits. The
battery charger provides a three-state charging algorithm fully controlled by the MCU. Its operating
parameters are listed in Table 4-1.
Single Phase On-Line UPS Using MC9S12E128
36
Freescale Semiconductor
Battery Charger
Table 4-1. Battery Charger Parameters
Input voltage
80 to 280 V / 50 to 60 Hz
Output voltage
High voltage level
Low voltage level
29.4 V
27.4 V
Max. value
Absorption - float threshold
1.8 A
0.36 A
Output current
NOTE
The output values are set to the values recommended by the battery
manufacturer. The current limits can be set to any value by SW.
4.2.2 Battery Charger Topology
The battery charger uses a flyback topology, frequently used for its simplicity for output power below
100 W. The charger consists of a flyback converter, battery voltage and current sensing, current
limitation, and mains line voltage detection. The schematic of the battery charger is shown in
Figure 4-3.The flyback converter uses the dedicated circuit TOP249 for control, which incorporates a
MOSFET transistor and control circuit in one package. Using this dedicated circuit allows connection of
the control signals to the secondary side of the flyback converter without galvanic isolation. The second
advantage of the solution is that UPS power is independent of MCU control, and the UPS is able to run
without batteries.
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
37
C302
220uF/450V
+
D302
B250R
D303
P6KE200
C301
+
L
4.7nF
T300
1
R302
1M
9
R306
1M
5
R303
24k
D304
-
6
D305
BYV26C
+VBAT
47uH
LINE_OK
R301
68k
1N4148
TR02/MC145
29.4V @ Q4 ON
27.4V @ Q4 OFF
L300
13
7
N
TP300
Vbat
D301
BYW29E-200
R304
39k
C303
220uF/50V
100nF
C304
R305
1k8
220uF/50V
100u/50
+
+
R307
620
+
C306
C305
R309
2k4
5.05V @ 39V
VBAT
D
7
GND_TR
2
CONTROL
F
4
L301
47uH
L
TOP249Y
R300
0.1
C
1
ISO300
SFH615A-2
4
X
GND_CH
1
3
C316
100n
R315
7.5k
IBAT1
R329
1K
R313
27R
5 3
sense
U300
R312
200
G
D300
1N4148
S
-VBAT
GND
IBAT2
GNDA
2
R314
HV_BAT_LEVEL
100
+
C307
47uF/10V
C315
100n
Q301
MMBF0201NLT1
sense
R311
33k
R310
5K6
R308
3K6
R331
100
IBAT2
5
MC33502
U301B
7
8
3
2
+
-
100k
U301A
MC33502
220n
Q300
8
BC847
U302
TL431ACD
GND
C314
N/P
R323
1k
GND_CH
R326
3k9
IBAT
R324
1k
IBAT_CONTROL
LINE_OK
R327
560
C311
C310
470nF
GND
4.875V @ 2.34A
GND
R318
1
100K
R325
33K
GND_CH
1
C300
R320
R322
220
D309
5V1
100nF
C308
4
6
+
R319
1k6
R321
1k6
+5V_A
C309
470nF
-
IBAT1
R317
33K
6
R316
220
C312
D307
10nF/100V
BAV103
470nF
R328
C313
D308
BAV103
100nF/100V
GND
/POWER_ON
68K
D
R330
10k
GND
GND_TR
Figure 4-3. Battery Charger Schematics
G
Q302 S
MMBF0201NLT1
GND
Battery Charger
4.2.3 Flyback Converter Operation
The flyback converter consists of the transformer T300, the MOSFET transistor U300 include control
circuit and the feedback circuit (R303, R305, R309, R312, Q301, ISO300, and U302).
When the MOSFET transistor (U300) is switched on, the magnetic field energy is accumulated in the
magnetic core of the transformer T300. During this time the output diodes (D301, D304) are reverse
biased. As soon as the transistor is switched off, the accumulated magnetic field energy is released
through the forward biased output diodes (D301, D304) to the output capacitors (C304, C305), and
through the output filter (L300, L301, C306) to the load.
The output voltage is sensed by the divider (R303, R305, R309, R312). The voltage from the divider is
compared with the internal reference of U302. The U302 creates the control signal—the current flowing
through the opto coupler (ISO300)—which galvanically isolates the primary and secondary side of the
flyback converter.
The control signal is connected to the control pin of the control circuit (U300). According to the control
signal, the duty cycle of the MOSFET transistor (U300) is set. The MOSFET transistor is switched with a
fixed frequency of 66 kHz.
The resistor R312 can be shorted by the transistor Q301. This allows setting the output voltage to either
29.4 or 27.4 V by the MCU.
4.2.4 Design of Flyback Converter
The design of flyback converter using TOP249 is described in detail in [10], [11] and [12]. The following
input parameters were considered during the converter design:
Table 4-2. Input Design Parameters of Flyback Converter
Input voltage
80 to 280 V / 50 to 60 Hz
Max. output voltage
29.4 V
Max. output current
1.8 A
Switching frequency
66 kHz
The calculated parameters of the flyback transformer are specified in Table 4-3. The measured values on
the manufactured sample are listed in Table 4-4. To decrease leakage inductance, the interleaved
winding layout is used for the primary winding. The complete transformer winding layout is shown in
Figure 4-4.
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
39
Hardware Design
2.5kV insulation layer
20T Cu f 4x0.315mm
2.5kV insulation layer
12T Cu f 3x0.56mm
2.5kV insulation layer
5T Cu f 2x0.315mm
2.5kV insulation layer
20T Cu f 4x0.315mm
L4
L3
L2
L1
14
Core
ETD29/16/10 N87 B66358-G-X187
ETD29/16/10 N87 B66358-G500-X187
Coil former
B66359-J1014-T1
Yoke
B66359-A2000
8
L3
1pcs
1pcs
1pcs
2pcs
L1
(EPCOS components)
L4
L2
1
7
Figure 4-4. Battery Charger Transformer Winding Layout
Table 4-3. Required Parameters of Flyback Transformer
Magnetizing inductance referred to the primary
328 mH + 3 0 – 20%
Magnetizing inductance referred to the secondary
31µH + 30 – 20%
Total leakage inductance referred to the primary
<3.5 µH
Primary dc resistance
<0.1 Ω
Secondary dc resistance
<0.001Ω
Test Voltage primary-to-secondary
2.5k V ac
Table 4-4. Measured Values on the Sample
Pin #
L [µH]
@1kHz, 1V
L [µH]
@100kHz, 1V
ESR [Ohm]
@100kHz, 1V
DCR [Ohm]
L [µH] @100kHz, 1V
pin # 9 and 13 shorted
1-6
331.2
330.5
2.142
0.095
2.88
5-7
5.2
5.22
0.061
0.018
-
9-13
29.8
29.74
0.194
0.0005
-
Single Phase On-Line UPS Using MC9S12E128
40
Freescale Semiconductor
Battery Charger
4.2.5 Voltage and Current Sensing, Current Limitation
The battery voltage is sensed by the divider (R304, R307, and R310). The divider scales the maximum
measurable battery voltage of 39 V to the A/D converter range of 5 V. The battery current is sensed as
the voltage drops on resistor R300. The voltage drop is amplified by U301B to get 5 V at 2.4 A.
The current limitation is provided by U301A. The U301A compares the actual battery current with the limit,
which is set by the MCU. The MCU generates a PWM signal, which is filtered to the analog value.
4.2.6 Main Line Detection
The mains line detection ensures that the UPS is internally switched on (STANDBY ON LINE state) if the
mains line is available. The detection circuit detects the functionality of the flyback converter, and if the
mains line is detected, the power supplies are switched on. The detection circuit consists of rectified
diodes D307, D308, and transistor Q302.
4.2.7 Battery Charger Algorithm
There are many algorithms (constant voltage, constant current, two stage, three stage, etc.), that can be
used for charging lead acid batteries. The algorithms differ by the complexity of battery charger
implementation and by influence on the battery life.
Because the battery charger is controlled by the MCU, any battery charger algorithm can be implemented.
The UPS reference design uses the three stage charging algorithm (see Figure 4-5).
Figure 4-5. 3-Stage Charging Algorithm
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
41
Hardware Design
As the name of algorithm suggests, charging consists of three stages. The charging starts with the current
limit 0.25 of battery capacity. The battery charger works in current mode until the battery voltage reaches
the high level voltage (2.45 V/cell). This stage is called bulk charging. As soon as the battery voltage
reaches the high level, the current starts to fall, and the absorption stage begins. Once the battery current
falls under 0.05 of battery capacity, the battery charge voltage is set to the low level (2.28 V/cell). The last
stage is called the float stage.
NOTE
The voltage levels and current thresholds come from the battery
manufacturer. The values may also vary with the temperature if
temperature measurement is implemented.
4.3 Auxiliary Power Supplies
Signal circuits, control circuits, digital circuits, and driving circuits are supplied by auxiliary SMPSs
(Figure 4-6). Since the drive circuits have to be galvanically isolated from each other, a small isolated
flyback converter (Figure 4-7) is used to generate separate voltage sources for all power semiconductor
drivers.
U202
LM2575-5
R212
33k
TP204
+5V_D
4
1
+5V_D
L202
2
470uH
1
+VBAT
5
D
R213
C215
220uF/10V
C216
22uF/50V
D211
KA3528LSGT
G
100
GND
GND
U200
LM2575-15
GND
TP200
+15V
4
1
+15V
L203
2
680uH
D213
1N5819
+
12
+
R214
2.4k
R215
20K
5
3
GND
1
GND
C218
22uF/50V
2
Q200 S
MMBF0201NLT1
GND
1
POWER_EN
R200
510
+
D210
1N5819
+
2
3
/POWER_EN
R216
1.8K
D214
KA3528LSGT
2
C217
220uF/10V
GND
+15V
3
10uH
+
C219
22u/20V
GNDA
C221
100nF
U203
MC78L05ACP
VIN
VO
GND
L205
GND
1
GND
TP207
+5V_A
+5V_A
GND
GND
TP208
Vref
L200
+5V_REF
10uH
C200
100nF
2
GND
GNDA
+
C220
22u/20V
GNDA
Figure 4-6. Auxiliary SMPSs
Single Phase On-Line UPS Using MC9S12E128
42
Freescale Semiconductor
Auxiliary Power Supplies
Supply voltages for the microcontroller and other digital circuits (+5V_D) are generated by U202. U200 is
used to stabilize +15V for the flyback converter, relays, dc/dc MOSFETs drivers, and cooling fans and it
is used as a down-converter for U203 in order to lower the power loss dissipated by U203. The IC supplies
5 V for op amps, comparators, and the heatsink temperature sensor. The output voltage is further filtered
and used as a reference for the signal and control circuits. In order to switch-on and switch-off all the
control and signal circuits, U200 and U202 are controllable by POWER_EN and /POWER_EN signals.
POWER_EN signal is driven by the microcontroller to control the switch-off process. /POWER_EN signal
is grounded when the “ON” button is depressed. All the power supplies are put into an operational state,
the micro starts to execute the program, and the POWER_EN signal is then put into the active state to
hold the supplies operational even when the button is released.
Figure 4-7 shows the isolated flyback converter schematic that provides the inverter and PFC drivers with
a power supply. MOSFET Q201 is driven by UC3843 in a classic current-mode configuration without the
feedback loop. The supply is designed to deliver constant power to the output while access power is
dissipated in zener diodes D202-D203, D206-D207, and D209 in case of drivers-in-standby. Respective
zener diodes are used specifically to split the secondary voltage to 5-V and 15-V levels.
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
43
C201
T1
R201
TP201
+15V_TOP
220
D201
100pF
12
+15V_TOP
LL4448
1
+15V
11
C204
L201
47nF
330u
R202
R203
15k
1
2
3
4
1
R206
8.2k
2
+ C206
330uF
U201
COMP
VFB
ISENSE
RT/CT
VREF
VCC
OUT
GND
R207
GND
GND
GND
GND
Q201
NTF3055
S
1k
C212
100pF
GND
GND_TOP
D203
BZV55/5V1
+
C203
100uF/10V
8z.
7
2
6z.
C208
100pF
R205
D205
TP202
+15V_BOT
220
+15V_BOT
LL4448
TR01/MC145
100pF
C213
-5V_BOT
LL4448
R211
TP203
+15V_PFC
220
D208
+
C214
220uF/25V
GND_PFC
TP211
GND_BOT
TP212
GND_BOT
D207
-5V_BOT
BZV55/5V1
+ C210
100uF/10V
100pF
Figure 4-7. Isolated Flyback Converter for Drivers
D206
BZV55/15V
+ C207
220uF/25V
R210
1.8
GND
TP210
-5V_TOP
-5V_TOP
C205
6
R204
220
5
R209
C209
100nF
D1
G
33
C211
100pF
GND
D
MMBD914LT1
8
7
6
5
UC3843
R208
8.2k
GND
D204
15k
8
5z.
TP209
GND_TOP
D202
BZV55/15V
+ C202
220uF/25V
8z.
+15V_PFC
TP213
D209
GND_PFC
BZV55/15V
GND_PFC
Auxiliary Power Supplies
4.3.1 Auxiliary SMPS Design Considerations
Auxiliary SMPS design (Figure 4-6) follows producer general considerations for LM2575 and 78L05
switched and linear regulators.
Because the isolated flyback converter is based on a standard UC384X IC, the design is focused on
transformer design. The transformer is used as an energy reservoir. During the switch-on the energy is
accumulated, and during the switch off the energy is delivered to the output capacitor and the load.
Respective output voltages are 2 x 20-V for HCPL315J output inverter driver - generated by L2 and L3
(+15 and –5 V are good driving margins in 800-V application), and 15-V for HCPL3150 PFC driver generated by L4 (single supply 15 V is sufficient for 400-V application). First, the output power is defined.
When driver circuits with HCPL315J and HCPL3150 drivers are considered, a value of 1.2 W is obtained.
When efficiency is considered, a value of 2 W is obtained. For such power, a switching frequency 300 kHz
is chosen. Let’s consider a 0.5 maximum duty. It means that during half of the switching period, all energy
for the whole cycle must be accumulated in the transformer.
The average necessary input charge is given by EQ 4-1. When we consider the triangular shape of the
transformer primary current, we get EQ 4-2 for the charge taken by the transformer.
P IN
Q = I AV ⋅ T = --------- ⋅ T
V IN
(EQ 4-1)
t ON ⋅ I P
Q = ∫ i dt = ---------------2
(EQ 4-2)
Because the voltage is equal, the equality of these charges also provides equal energies. When we
compare both equations, we get
P IN
t ON ⋅ I 1P
-------- ⋅ T = ------------------V IN
2
(EQ 4-3)
Rearranging EQ 4-3 we get EQ 4-4 for the peak primary current:
P IN T
2 3.3µ
I PP = 2 ⋅ --------- ⋅ -------- = 2 ⋅ ------ ⋅ ----------- = 586mA
15 1.5µ
V IN t O N
(EQ 4-4)
The peak secondary current for a 20-V output is calculated using EQ 4-6 (all the output power is
considered), and the secondary winding inductance L2 is then given by EQ 4-7.
V IN
15
L 1 = --------- dt = ------------- ⋅ 1.5µ = 38µH
di
0.586
(EQ 4-5)
P OUT T
1.6 3.3µ
I 1P = 2 ⋅ ------------- ⋅ ---------- = 2 ⋅ ------- ⋅ ----------- = 293mA
20 1.8µ
V OU T t O FF
(EQ 4-6)
V OU T
20
L 2 = ------------- dt = ------------- ⋅ 1.8µ = 123µH
di
0.293
(EQ 4-7)
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
45
Hardware Design
Let’s choose a RM8 core made from N97 ferrite material, with Ae = 64mm 2 and AL = 3300 nH. Respective
winding turns are as follows:
N1 =
L
------P- =
AL
38µ
--------------- = 3.4 ≈ 4t
3300n
(EQ 4-8)
N2 =
L
------S- =
AL
123µ
--------------- = 6.1 ≈ 6t
3300n
(EQ 4-9)
Therefore, N1 primary to N2 secondary ratio is given as follows:
N
4
p = ------1 = --- = 0.667
6
N2
(EQ 4-10)
For supplying the PFC driver, 15-V supply voltage is necessary and the turns ratio between both
secondaries is used to calculate the number of turns for the PFC driver.
15
15
N 4 = ------ ⋅ N 2 = ------ ⋅ 6 = 4.5t
20
20
(EQ 4-11)
Rounding the number up or down would cause large unbalanced secondary voltages. Secondary turns
are then scaled to obtain appropriate secondary-to-secondary ratio. Afterwards, primary turns are also
altered. In this case, N2 = 8t gives exact value of N 4 = 6t as follows:
15
15
N 4 = ------ ⋅ N 2 = ------ ⋅ 8 = 6t
20
20
(EQ 4-12)
Now, the primary turns are scaled to maintain primary-to-secondary ratio:
N 1 = p ⋅ N 2 = 0.667 ⋅ 8 = 5.34 ≈ 5t
(EQ 4-13)
To maintain a discontinued conduction mode, the switching frequency has to be also altered to the value
of 200 kHz. And the maximum flux has to be checked - simulation shows flux of amplitude 160 mT.
Figure 4-8 shows the layout of the windings on the transformer bobbin.
Single Phase On-Line UPS Using MC9S12E128
46
Freescale Semiconductor
dc/dc Step-Up Converter
2.5kV insulation layer
6T Cu f 0.25mm
2.5kV insulation layer
8T Cu f 0.25mm
2.5kV insulation layer
8T Cu f 0.25mm
2.5kV insulation layer
5T Cu f 0.25mm
L4
L3
L2
L1
Core
Coil former
Clamp
RM8 N97
12
7
L3
L2
L1
L4
1
B65811-J-R97
B65812-C1512-T1
B65812-A2203
6
1set
1pcs
2pcs
(EPCOS components)
Figure 4-8. Flyback Power Transformer Layout of Windings
4.4 dc/dc Step-Up Converter
4.4.1 dc/dc Converter Operational Description
A dc/dc converter is intended for dc bus supply when the UPS run from batteries. Parameter
specifications are listed in Table 4-5. The converter transforms the battery voltage of 24 V to a dc bus
voltage of +400 V, –400 V. Low-cost considerations led to push-pull topology as shown in Figure 4-9. The
circuit consists of a push-pull inverter (Q500-Q503), power transformer T500, bridge rectifier (D500,
D502, D504, D505) and filter L501, L502. The rectifier directly supplies the dc bus voltage +400,–400V.
Table 4-5. dc/dc Converter Specifications
Parameter
Value
Input voltage nominal
24 V
Input voltage minimal
21 V
Input voltage maximal
30 V
Output voltage nominal
+390 V -390 V
Output voltage minimal
+350 V -350 V
Output power nominal
580 W
Output current nominal
0.74 A
Input current nominal
27 A
Switching frequency
50 kHz
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
47
L501
+Bat
MUR180
1
2
FFPF05U120STU
D500
680u/50V
1
D504
D505
10
L503
330u
MC33152D
NC
8
OutA
7
2 InA
1
5
1
1
2
R505
2
R506
47uF
C510
C508
1n
1
2
GND_BAT
100n
C500
GND_BAT
GND_BAT
Q501 Q500
NTP45N06 NTP45N06
D
D
G
G
S
Q502 Q503
NTP45N06 NTP45N06
D
D
G
S
U501
8 NC
G1
S
2
R500
VCC
MC33152D
NC
1
2
7 OutA
InA
2
2
5 OutB
InB
4
TP502
PWM_5
10
S
1
R507
GND
GND
GND_BAT
GND_BAT
GND_BAT
GND_BAT
GND_BAT
Figure 4-9. dc/dc Converter Schematic
PWM5
R509
10k
10
10
3
1
2
R508
10k
OutB
4 InB
L500
330u
1
C507
1n
GND_BAT
10
PWM4
1
R503
100R/1W
2
6
GND_BAT
VCC
T500
TR03/MC145
9
1
1
100n
C511
DCB_POS
+15V
2
GND_BAT
+OUT
650u/1A
2
+
2
C506
22n/400V
18
4
6
100R/1W
R504
2
2
D503 L502
FFPF05U120STU
1
47uF
C509
1
GND
13
15
FFPF05U120STU
+15V
U500
1 NC
2
MUR180
GND_BAT
TP501
PWM_4
1
FFPF05U120STU
D502
2
R502
1k/5W
+
2
2
2
680u/50V
680u/50V
2
R501
1k/5W
1
DCB_NEG
C501
22n/400V
6
-VBAT
2
2
C502 + C503 + C504 + C505 + C512 + C513 +
-OUT
3
1
680u/50V
1
1
1
+VBAT
1
680u/50V 680u/50V
650u/1A
D501
1
The converter performance and features are analyzed by simulation with the model shown in Figure 4-10.
Chokes and Rectifier Snubbers
Rectifier Model
mur2100e/ON
DC Bus
mur2100e/ON
L16
1
C5
Power Transformer Model
D1
10p
1
2
L7
4700 2
R3
2
10u
10p
C4
R20
20n
D7
L10
20n
9.98m
K_Linear
COUPLING = 1
1
2
2
30.8u
L3
1
L1
L15
26.7n
2
30.8u
2
20n
V2
S
M3
20
R11 NTP45N06
0
L8
R4
2
10u
R7
20m
R15
L12
20n
0.5
R16
20n
R17
1
4700
C3
1
100
R10 M1
1
R23
2
L11
2n
2u
V1
R1
5m R14
Implementation = 1
1
2
2
23.2
2
2
L18
2n
2u
Inverter Model
C2
1n
1n
NTP45N06
M2
C10
10p
R19
1
1000
4700
D3
C6
10p
10p
mur2100e/ON
NTP45N06 NTP45N06
20
R12
L17
2
560u
mur2100e/ON
R9
0.3
Current Sensing
R13
20
0
V3
S
K K2
D1N4149
D12
K_Linear
COUPLING = 1
0
1
1
L20
1.6m
L19
80u
80m
2
2
R25
R27
D6
3
C11
5p
R26
1k
220
D1N4149
D9
R24
22
D1N4149
C12
10n
D10
D1N4149
D11
D1N4149
Figure 4-10. dc/dc Converter Simulation Model Schematic
R6
2
0
50m
L14
20n
mur2100e/ON
D4
Implementation = 2
20
V5
22n
D8
1
R2
5m
M4
390
C8
2k
100
C1
50m
V4
R28
524meg
0
9.98m
26.7n
L21
22n
390
L6
L4
1
R5
C7
2k
1
1
1000
mur2100e/ON
R22
2
15n
1
1
1
C9
10p
R21
1
1
L2
L13
4700 2
L5
K K1
2
0.3
D2
R18
L9
0.5
R8
2
560u
1
R29
524meg
Hardware Design
The inverter is supplied by a set of a low-ESR capacitors, C502-C505 and C512-C513, to lower the
battery bus ripple current and hence the EMI signature of the converter input. Inverter MOSFETs
Q500-Q503 are driven by MC33152 drivers. MOSFETs drain voltage ringing is damped by RC cells
R504-C507 and R503-C508. Because of the voltage source character of the inverter, the rectifier has to
be a current type, which is why smoothing chokes L501 and L502 are used. Over voltage spikes across
the rectifier diodes, due to the diodes reverse-recovery and transformer leakage, are clamped by RCD
snubbers consisting of a R501- C501- D501 for the positive side, and R502 - C506 - D503 for the negative
side.
4.4.2 dc/dc Converter Design Considerations
4.4.2.1 Power Transformer
The first task in power transformer design is to choose an appropriate transformer core. Based on
manufacturer power-handling-capability core tables the core size is selected. Subsequently, the
maximum core flux density travel ∆B must be determined from the core manufacturer data sheet, and then
an approximate number of turns can be calculated. Since the number of turns is usually an integer, the
number is rounded and the real flux density travel is calculated. If ∆B is below a maximum limit with
respect to the switching frequency (core material dependent), winding turns and the cross-sectional areas
are calculated for all respective windings.
For 580W output, an ETD44 core is selected. Now, the integral of the Faraday induction law EQ 4-14
gives the relation for the magnetic charge put into the core EQ 4-15:
dψ
dφ
dB
u i = ------- = N ------ = N ⋅ S ------dt
dt
dt
(EQ 4-14)
where
ui
=
induced voltage
ψ
=
linkage flux in the core
N
=
number of turns
Φ
=
flux in the core
Β
=
flux density in the core
∫
u i dt = N ⋅ S ⋅ ∆B
(EQ 4-15)
where
∆Β
=
flux density travel
S
=
core cross-sectional area
Single Phase On-Line UPS Using MC9S12E128
50
Freescale Semiconductor
dc/dc Step-Up Converter
Initially, the magnetic charge has to be calculated. Since the induced voltage during an active part of the
converter operational cycle is constant and it equals the input voltage, the magnetic charge in the core is
given by EQ 4-16.
∫
u i dt = V IN ⋅ δ ⋅ T
(EQ 4-16)
where
VIN
=
input voltage
δ
=
switching duty cycle
T
=
switching period (f = 50kHz)
–6
∫
u i dt = 24 ⋅ 0.45 ⋅ 20 ×10 = 216 µVs
(EQ 4-17)
Simulation results can also be used to obtain the magnetic charge. Figure 4-11 shows simulated
magnetizing voltage and magnetic charge. Magnetic charge is obtained by the time integral of the
magnetizing voltage. Peak-to-peak reading of the magnetic charge is 218 µV.
Rearranging EQ 4-15, the number of primary turns can be calculated:
u dt
–6
∫ i
216 ×10
- = 3.12 t
--------------N1 =
= ---------------------------------S ⋅ ∆B 173 ×10–6 ⋅ 0.4
1
40V
2
100u
20V
0
0V
-100u
-20V
-200u
-40V
(EQ 4-18)
>>
-300u
15us
1
20us
V(L1:1,L1:2)
2
25us
S(V(L1:1,L1:2))
30us
35us
40us
45us
Time
Figure 4-11. Simulated Magnetizing Voltage and Magnetic Charge
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
51
Hardware Design
Let’s choose 3 turns. However, the flux density travel ∆B has to be checked:
u dt
–6
∫ i
216 ×10
- = 416 mT
∆B = -------------- = ----------------------------S ⋅ N 1 173 ×10–6 ⋅ 3
(EQ 4-19)
From EPCOS Siferit N97 specification (FAL0625-W @60°C), the core power loss is 10 W, indicating a
good core utilization. However, forced convection should be considered. The negative loss temperature
coefficient of the N97 material is advantageous since it contributes to a temperature stability of the core
(FAL0624-N).
Now, the number of turns of the secondaries can be calculated. For primary to secondary ratio and a
forward type of converter, equation EQ 4-20 is valid:
V OU T
p = ---------------------------------V IN ⋅ η ⋅ δ MA X
(EQ 4-20)
For efficiency η = 0.93 and maximum duty δ(MAX) = 0.98, EQ 4-20 yields
V OUT
350
p = ----------------------------------- = ------------------------------------ = 18.47
V IN ⋅ η ⋅ δ MAX 21 ⋅ 0.93 ⋅ 0.97
(EQ 4-21)
Primary to secondary ratio is rounded to 18, and the secondary winding number of turns yields
N 2 = p ⋅ N 1 = 18 ⋅ 3 = 54t
(EQ 4-22)
Once the winding turns are determined, the cross sectional area of a winding can be calculated. For the
ETD44 core, winding current density can be selected in the range 5-10A/mm 2. Let J = 8A/mm2. Primary
cross-sectional area is given by EQ 4-23
I
2
19.1
S 1 = ----1 = ---------- = 2.39 mm
J
8
(EQ 4-23)
where
Ι1
=
nominal primary winding current obtained by integrating the square of the simulated
winding current (Figure 4-12).
Single Phase On-Line UPS Using MC9S12E128
52
Freescale Semiconductor
dc/dc Step-Up Converter
1
60A
2
915m
40A
910m
20A
905m
0A
900m
-20A
>>
895m
2.2965ms
2.3000ms
1
-I(R1)
2
2.3040ms
2.3080ms
S(I(R1)*I(R1))
2.3120ms
2.3160ms
2.3200ms
2.3240ms
2.3280ms
Time
Figure 4-12. Simulated Primary Winding Current
Secondary cross-sectional area is given by EQ 4-24:
I
2
0.74
S 2 = ---2- = ---------- = 0.093 mm
J
8
(EQ 4-24)
where
Ι2
=
nominal secondary winding current obtained by integrating the square of the simulated
winding current (Figure 4-13).
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
53
Hardware Design
1
1.5A
2
1.300m
1.0A
1.296m
0.5A
1.292m
-0.0A
1.288m
-0.5A
1.284m
-1.0A
1.280m
-1.5A
>>
1.276m
2.2965ms 2.3000ms
1
-I(R3)
2
2.3040ms
2.3080ms
S(I(R3)*I(R3))
2.3120ms
2.3160ms
2.3200ms
2.3240ms
2.3280ms
Time
Figure 4-13. Simulated Secondary Winding Current
For a 50kHz switching frequency the skin effect depth is given by EQ 4-25:
0.066
0.066
δ = ------------- = --------------------- = 295 µm
3
f
50 ×10
(EQ 4-25)
In this case the best solution for the primary is the use of a copper foil. An ETD44 bobbin has a width of
30 mm. Because of the necessary creepage, the foil width is set to 25 mm. Based on the result of
EQ 4-23, the foil thickness yields 100 µm and has excellent skin performance when compared with skin
depth at the current switching frequency.
From the result of EQ 4-24, the secondary winding wire diameter yields 0.338 mm. The nearest wire
diameter in production is 0.315mm. A wire with a larger diameter is not helpful any more because of the
increased ac resistance due to the skin effect.
The primary winding of the push-pull converter transformer uses a center-tapped windings as well as the
secondary windings. As the power transformer is a part of the push-pull converter, there are some
restrictions required, especially with respect to the leakage inductance. With inverter transistor turn-off,
the drain voltage in push-pull is not clamped by the circuit topology itself. For ideal case (zero leakage),
the drain voltage is clamped through the transformer coupling when the rectifier diodes are re-opened.
Single Phase On-Line UPS Using MC9S12E128
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Freescale Semiconductor
dc/dc Step-Up Converter
60V
40V
20V
0V
9.458us
9.600us
V(M1:d)
V(M2:d)
9.800us
V(M3:g)
10.000us
V(M2:g)
10.200us
10.400us
10.600us
10.800us
Time
Figure 4-14. Simulated Drain-to-Source and Gate-to-Source MOSFETs Voltages
However, when leakage is non-zero, coupling between the primary and the secondary is not so close and
the transformer acts more than an inductive load. As a result, inverter transistors receive voltage spikes
and ringing at the drain voltage, usually leading to the use of MOSFETs with a higher break-down drain
voltage (Figure 4-14). Due to the necessity to decrease the leakage inductance, an interleaved winding
layout has to be used, as seen in Figure 4-15.
Single Phase On-Line UPS Using MC9S12E128
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Hardware Design
2.5kV insulation layer
29T Cu f 0.315mm
2.5kV insulation layer
29T Cu f 0.315mm
2.5kV insulation layer
3T Cu stripe 25x0.15mm
500V insulation layer
3T Cu stripe 25x0.15mm
2.5kV insulation layer
29T Cu f 0.315mm
2.5kV insulation layer
29T Cu f 0.315mm
L6
L5
L4
L3
L2
L1
18
Core
ETD44/22/15 N97 B66365-G-X197 2pcs
Coil former
B66366-B1018-T1 1pcs
Yoke
B66366-A2000
2pcs
10
L6
L2
L1
L4
(EPCOS components)
L5
L3
1
9
Figure 4-15. dc/dc Power Transformer Layout of Windings
The transformer specification is presented by Table 4-6. The magnetizing inductance values are obtained
from the manufacturer. The AL constant, total leakage, is obtained initially from numeric parametric
simulation results, and afterwards is verified experimentally on the sample. Resistance values are
measured values. Test voltages come from general standards defined for the inductive components used
in SMPS. Measurements on the sample show that it is possible to achieve a relative leakage less than
0.6%.
Table 4-6. dc/dc Transformer Specification
2.5mH+30-20%
Magnetizing inductance referred to the secondary
Magnetizing inductance referred to the primary
30µH+30-20%
Total leakage inductance referred to the secondary
<20uH
Primary DC resistance
<1mOhm
Secondary DC resistance
<0.6Ohm
Test Voltage secondary-to-secondary and primary-to-secondary
2kV AC
Test Voltage primary-to-primary
150V AC
4.4.2.2 Inverter MOSFETs
As mentioned above, MOSFETs voltage rating is given by voltage spikes that can possibly occur during
MOSFET switch-off. Of course it depends on the input voltage, load conditions, and transformer
properties. For push-pull a number of twice the input voltage is usually sufficient. The current rating of the
MOSFETs (chip size) is always a compromise because a small chip has large RDS(ON) that causes high
conduction losses. On the other hand, a large chip has low RDS(ON), but the chip capacitances are higher,
and, in the case of hard-switched topologies, the energy stored in the capacitances is not recovered in
the switching process, but instead, energy is dissipated in the chip. This is especially the case in
applications where the supply voltage is greater than 200 V.
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Freescale Semiconductor
dc/dc Step-Up Converter
The primary factor for chip selection are the effective drain current and the switching frequency. Then a
suitable device is selected. Power loss components are calculated and compared with the designed
maximum power loss per package.
Simulation results (Figure 4-12) show a value of 19.1 A (transistor and primary winding currents are the
same). Dynamically, a current level as high as 50 to 60 A is observed when a load transient occurs and
the regulator attempts to hold the output voltage level. Of course the transistor has to withstand such
conditions for a number of milliseconds.
A couple of ON Semi’s twin NTP45N06 could be a solution. RDS(ON) for the transistor is 26 mΩ. If a single
NTP45N06 switches the current with an effective value of 19.1 A, conduction losses are as high as 9.5 W.
To lower the conduction losses and to ensure the transistor switching robustness in dynamic conditions,
let’s consider the twin NTP45N06 which decrease overall conduction losses to the half (power loss per
package decreases to a quarter - 2.4 W). However, the switching and the capacitance losses have to be
considered, due to the increased overall chip area, and hence the overall chip capacitance.
Switching losses are given by EQ 4-26 (ref. [2]).
I SW
P SW = V D S ⋅ ( Q G D + Q GS2 ) ⋅ f SW ⋅ -------IG
(EQ 4-26)
3 30
- = 0.72 W
P SW = 24 ⋅ ( 3nC + 15nC ) ⋅ 50 ×10 ⋅ -----0.9
(EQ 4-27)
where
VDS
=
drain-to-source voltage at the switching instance
QGD
=
“miller part” of the gate charge
QGS2
=
“post-threshold voltage” gate charge
fSW
=
switching frequency
ISW
=
drain current at the instant of switch off
IG
=
available mean driver current
Note that VDS can reach a level close to 60V as depending on the particular duty cycle, input voltage, and
output load conditions. The same is true for ISW parameter, and the loss value can be impacted.
CAUTION
If the output load conditions or large transformer leakage cause over
voltage spikes at the drain and the maximum drain voltage is reached, the
voltage is clamped by MOSFET internal avalanche process (see
Figure 4-14 — fourth wave oscillation on green waveform). If the energy of
the spikes is high enough, chip temperature will exceed the maximum limit
and the semiconductor structure is destroyed. Please always observe the
drain-to-source voltage when testing the prototype. If this is the case,
increase the MOSFET voltage class or redesign the power transformer in
order to decrease the leakage.
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Hardware Design
Turn-on capacitance losses PCAP for the NTP45N06 are given by EQ 4-28.
1
2
P CAP = f SW ⋅ W CAP = f SW ⋅ --- ⋅ C OSS ( EFF ) ⋅ V D S
2
(EQ 4-28)
1
3
– 12
2
P CAP = 50 ×10 × --- ⋅ 380 ×10 ⋅ 60 = 34 mW
2
(EQ 4-29)
where
fSW
=
switching frequency
WCAP
=
capacitance energy (see ref. [1])
COSS(EFF) =
effective output capacity of the MOSFET (see ref. [2])
The sum of the switching and the capacitance losses is less than 0.8W per transistor at nominal
conditions, resulting in 1.6 W for the single NTP45N06 solution and 3.2W for the twin solution. When all
the loss contributions are compared, prevalence of the conduction losses is clear. The twin NTP45N06
solution results in an overall loss of 3.2W per package (the conduction component is 2.4 W, the switching
component 0.8W). Therefore, the twin solution doesn’t contribute significantly to lower a converter
efficiency. Power loss 3.2 W per package means moderate package utilization for TO220, with a good
power loss margin.
The power losses can also be calculated by simulation of the model. Figure 4-16 shows the MOSFET
instantaneous power and energy obtained by instantaneous power integration. The average power is
then calculated by the definition of the power - the energy loss referred to the switching period.
1
400W
2
8.04m
200W
8.00m
0W
7.96m
>>
-200W
7.92m
2.208ms
1
W(M3)
2.212ms
2
S(W(M3))
2.216ms
2.220ms
2.224ms
2.228ms
2.232ms
Time
Figure 4-16. Inverter MOSFET Power Analysis
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Freescale Semiconductor
dc/dc Step-Up Converter
The use of a single transistor with a higher rated drain current is also possible, however, the copper lead
utilization is rather high even though manufacturers define the value around 75 A as a limit for TO220
package leads.
4.4.2.3 Rectifier Diodes
Rated diode voltage is given by the voltage waveform applied to the diode. However, diode voltage
waveforms are different from that of the MOSFETs since the rectifier diodes are placed in a different
topology. As the rectifier is current-loaded there is no natural clamp for over voltage spikes at the instant
of a diode reverse recovery. That is why a suitable snubber has to be implemented in order to cut-off the
excess energy that could possibly overheat the diode chip by internal avalanche.
As dc/dc converter nominal output voltage is 2x390V (Figure 4-18 shows secondary voltage of the power
transformer), and during dynamic conditions it can reach 2 x 420 V, the possibility of selecting the diode
voltage rating is constrained. Figure 4-17 shows waveforms of the rectifier diode voltage and current. In
this case, diodes with a break-down voltage of 1200V are selected.
1
0.5KV
2
1.5A
1.0A
0V
0.5A
-0.5KV
0A
>>
-1.0KV
-0.5A
2.3075ms 2.3100ms
1
V(D1:1,D1:2)
2
2.3150ms
I(D1)
2.3200ms
2.3250ms
2.3300ms
Time
Figure 4-17. Rectifier Diode Voltage and Current Waveform
When choosing the rectifier current rating, similarly as with the MOSFETs, the anode effective current and
switching frequency have to be considered. Simulation results for the nominal anode effective current
shows a value of 0.54 A and a 1.3 W power loss. Because the power loss is rather high for a practical
usage of the DO241 package, diodes with a fully-isolated TO220 package are chosen. One possibility is
to use of the Fairchild ultrafast diode FFPF05U120S with 5-A rated current, 1200 V rated voltage, and
100ns reverse recovery time, which is good enough for 50 kHz switching frequency.
Single Phase On-Line UPS Using MC9S12E128
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59
Hardware Design
4.4.2.4 Filter Chokes
A basic design consideration when implementing a filter choke is to look at the rectified current ripple. For
an output current level in the range of 0.5 to 2 A, the relative ripple ri can be considered in the range of
50 to 20%. Let ri equal 30% for nominal conditions. Then the filter choke inductance value is given by
EQ 4-30:
δ M AX ⋅ T
∆T
L = V L ⋅ ------- = [ ( V IN – V LOSS ) ⋅ p – V OU T ] ⋅ --------------------r i ⋅ I OUT
∆i
(EQ 4-30)
–6
0.98 ⋅ 10 ×10
L = [ ( 24 – 1.6 ) ⋅ 18 – 390 ] ⋅ ----------------------------------- = 583 µH
0.3 ⋅ 0.74
(EQ 4-31)
where
VL
=
voltage across the choke when active cycle
∆Τ
=
the time during active cycle
∆i
=
current ripple
VIN
=
nominal input voltage
VLOSS
=
voltage drop on resistive components (RDS(ON), transformer primary, etc.)
p
=
transformer primary to secondary ratio
VOUT
=
nominal output voltage
δMAX
=
maximal switching duty cycle
ri
=
relative current ripple
IOUT
=
nominal output current
Filter choke performance is analyzed by simulation, and the results (Figure 4-18) verified a good design
procedure. Choke PCV2-564-02 from Coilcraft, with 560 µH inductance and 2 A saturation current, is
chosen.
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Freescale Semiconductor
Power Factor Correction and Output Inverter
1
800mA
2
1.0KV
400mA
0.5KV
0A
0V
-400mA
-0.5KV
-800mA
>>
-1.0KV
1.900ms
1
1.905ms
1.910ms
1.915ms
I(L16)
I(L17)
2
V(R3:2,R4:2)
1.920ms
1.925ms
1.930ms
1.935ms
1.940ms
Time
Figure 4-18. Secondary Voltage and Rectified Current Waveforms
4.5 Power Factor Correction and Output Inverter
4.5.1 PFC Booster Operational Description
This section deals with a design of the power factor correction booster (PFC). The PFC forms the input
stage of the UPS. It is a switchmode power converter, which provides an a.c. input current waveform that
is sinusoidal and in phase with the line voltage. The power factor is maintained so as to be close to one.
The continuous current - boost converter topology was chosen for the PFC circuitry design, as shown in
Figure 4-19. The PFC specifications are listed in Table 4-7. A power circuit consists of a current sensing
transformer CT1, input inductor L505, rectifying bridge D606, power switch Q606, voltage doubler diodes
D604, D608, and filtering capacitors C603, C602, C607, and C608. The PFC control algorithm
implemented uses an indirect digital control approach. To decrease MCU load the input current controller
is built externally.
Table 4-7. Digital PFC Specifications
Parameter
Value
Unit
Input Voltage Min.
80
V[r.m.s.]
Input Voltage Max.
270
V[r.m.s.]
Output d.c. Voltage
390
V
Output Power Nominal
525
W
Input Current Nominal
2.3
A[r.m.s]
Switching frequency
30 to 60
kHz
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61
I_IN1
I_IN2
9
7
Hardware Design
CT1
1:100
D604
DCB_POS
2
1
L505
L1
2.5mH
RHRP8120
D606
KBPC606
-
+
C603
C602
+
MKP10/22nF/630VDC
Q606
IRG4IBC20W
330uF/450V
GATE_PFC
GND_PFC
N
N
GND
C607
MKP10/22nF/630VDC
+
C608
330uF/450V
D608
DCB_NEG
RHRP8120
Figure 4-19. PFC Power Stage
The output voltage level is controlled using a digital controller algorithm executed by the MCU. The MCU
generates a sinusoidal reference waveform for the discrete current controller. The current controller circuit
can be seen in Figure 4-20. The controller performs hysteretic current control. Comparators U606A and
U606C compare the actual input current value I_IN with the upper and the low limits set by the DA1 and
DA0 signals, respectively. Comparator U606B turns on and off power switch Q606 according to the
U606A and U606C outputs. The UPS input current corresponds to the shape of the reference signals DA0
and DA1 generated by the MCU. The PFC operation is disabled if the PFC_EN signal is tied low by MCU
control.
Alternatively (if signal DA0 is not available), the low hysteresis limit can be adjusted by the configurable
voltage divider. The resulting hysteresis is then defined by the combination of resistors R664, R673,
R674, and R675. The voltage divider can be configured according to the DIV1 and DIV2 signals.
NOTE
Selecting whether the low hysteresis limit is taken from DA0 signal or from
the configurable voltage divider has to be done by resoldering the zero
resistors R666 and R667. If R666 is populated, the DA0 signal is selected.
If R667 is populated, the configurable divider is selected. By default R666
is populated and R667 is not.
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Freescale Semiconductor
+5V_A
+5V_A
R657
33
100n
GNDA
3
4
-
5
+
R658
10k
U606A
V+
V-
R660
R659
10k
10k
R664
1.6k
GNDA
GNDA
7
+
C630
100n
R667
0
I_IN
8
-
9
+
C631
100n
V+
V-
GND
G
1
Q609 S
MMBF0201NLT1
LM339M
U606C
V+
V-
R669
10k
14
R670
10k
TP611
GND
PFC_CTRL
LM339M
PWM_PFC
+5V_D
12
100
D
U606B
3
0
R668
-
R666
DA0
100
6
12
R665
12
C629
100n
C628
100n
R661
470
R662
470
2
LM339M
100
+5V_D
3
R663
DA1
+5V_D
C627
GNDA
GNDA
GNDA
R671
4.7k
D
G
UNI-3 PFC_EN
Q610 S
MMBF0201NLT1
60%
All On 55%
R673
3.3k
75%
D
DIV1
G
GNDA
85%
R675
9.1k
GND
D
DIV2
Q611 S
MMBF0201NLT1
R674
10k
G
Q612 S
MMBF0201NLT1
GNDA
U601
GNDA
PWM_PFC
GND
+15V_PFC
1
8
2
7
3
6
4
5
HCPL3150
D609
C609
100nF
BAT42
R606
GATE_PFC
10
R607
100
D628
15V
GND_PFC
GND_PFC
Figure 4-20. PFC Current Controller
Hardware Design
4.5.2 PFC Booster Design Considerations
In this section we will discuss the design considerations of the PFC booster critical components.
4.5.2.1 PFC Boost Inductor L1
The input inductor must be selected with respect to two parameters, the input current ripple and the
switching frequency. It is designed for maximum input power, minimum input voltage, when the sine wave
current peak is at a maximum.
The maximum input current value is then calculated from the maximum output power Pout max and
minimum input voltage Vin min. We also have to include efficiency of the boost converter. For a continuous
current boost converter, the efficiency is estimated at 95%. The maximum current value is calculated as
follows:
I in max =
Pout max
- =
2 ⋅ ---------------------V in min ⋅ η
525
2 ⋅ ------------------------ = 4.2A
184 ⋅ 0.95
(EQ 4-32)
If we know the input current maximum value we can calculate a current ripple. We chose the current ripple
to be 15% of the input peak current. For the given peak current value it is:
∆I = I in max ⋅ 0.15 = 0.645A
(EQ 4-33)
When the PFC switch is turned on, the following equation has to be met:
∆I
L 1 ⋅ -------- = V in
T on
(EQ 4-34)
where
L1
=
inductance of the input boost inductor
∆I
=
p-p input current ripple
Ton
=
turn-on time of the PFC switch
Vin
=
instantaneous input voltage value
Turn on time T on can be expressed from EQ 4-34 as follows:
∆I ⋅ L
T on = ---------------1V in
(EQ 4-35)
When the PFC switch is turned off, the following equation has to be met:
– ∆I
L 1 ⋅ --------- = V in – V out
T off
(EQ 4-36)
where
Toff
=
turn-off time of the PFC switch
Vout
=
output voltage
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Freescale Semiconductor
Power Factor Correction and Output Inverter
Again, turn off time Toff can be expressed:
– ∆I ⋅ L 1
T off = ----------------------V i n – V out
(EQ 4-37)
Switching period T equals the sum of Ton and Toff times:
∆I ⋅ L
∆I ⋅ L 1
∆I ⋅ L 1 ⋅ V out
- = -----------------------------------T = T on + T off = ---------------1- – ----------------------2
Vi n
V in – V out
V out ⋅ V in – V in
(EQ 4-38)
Frequency is an inverse value of the period. The switching frequency of the PFC is then given by the
formula:
2
V out ⋅ V i n – V in
1
f sw = --- = -----------------------------------T
∆I ⋅ L 1 ⋅ V out
(EQ 4-39)
Switching losses of the IGBT transistor are proportional to the switching frequency. To maintain switching
losses within acceptable limits we have to design the input inductor L1 with respect to a maximum
switching frequency. From EQ 4-39, we can calculate the level of input voltage (Vin) when the switching
frequency reaches its maximum value. We get the maximum switching frequency at
V out
V in = --------2
(EQ 4-40)
If we substitute EQ 4-40 for EQ 4-39 we can solve the equation and find the value of the required input
inductance value for the given ripple current (∆I), output voltage (Vout) and maximum switching frequency
(fmax):
V out
L 1 = -------------------------4 ⋅ ∆I ⋅ f max
(EQ 4-41)
If we enumerate the equation for desired values we get:
–3
390
L 1 = -------------------------------------------- = 2.5 ⋅ 10 H = 2.5mH
3
4 ⋅ 0.645 ⋅ 60 ⋅ 10
(EQ 4-42)
To limit the maximum frequency at 60 kHz at ripple current 0.645 A, we choose the input PFC inductance
L1 = 2.5 mH.
4.5.2.2 L1 Inductor Core Selection
As soon as we know the required inductance, we can proceed to select the core material and size. For
the PFC application, we will consider an iron powder material.
Size of the core can be established based by an iterative process using manufacturer’s catalog data. We
have chosen Micrometals as a material supplier. They offer a design software, which makes this process
easier. We used this software to find the best fitting core.
In the window “PFC Boost Design Requirements” we entered the in following parameters (see Table 4-8).
Single Phase On-Line UPS Using MC9S12E128
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65
Hardware Design
:
Table 4-8. PFC Inductor Parameters
Parameter
Value
Unit
2500
µH
5
A
PEAK REGULATOR INPUT VOLTAGE
113
V
REGULATOR dc OUTPUT VOLTAGE
390
V
FREQUENCY
60
kHz
TEMPERATURE
55
°C
TOROID
-
FULL WINDOW
-
INDUCTANCE AT MAX CURRENT
MAXIMUM CURRENT
CORE SHAPE
WINDING TYPE
We ran the calculation and got a list of suitable cores, that met our selection criteria. From the list we
selected core: T175-8/90. The software calculates all important data (number of turns, wire diameter,
losses, Rdc, Al, dimensions, etc.). For the selected core, the parameters are as follows:
Table 4-9. Design Parameters for Core P/N: T175-8/90
Parameter
Value
Unit
Al
48
nH
TURNS
287
-
WIRE
1.00
mm
FILL
38.9
%
Rdc
0.4971
Ω
Core Loss
0.28
W
Cu Loss
6.21
W
Temp. Rise
41.8
°C
The core T175-8/90 meets all of our criteria, is an acceptable size, with moderate losses and good
linearity.
4.5.2.3 dc-Bus Capacitor Design
When designing a dc-bus capacitor, we must consider its rated voltage, capacitance, size, and cost.
Because there is no upper limit to the capacitance (the higher capacitance the better), we should focus
on finding the possible smallest capacitance, which still meets our requirements on dc-bus voltage ripple
and output voltage quality. The correct design of capacitor is very important and can significantly influence
final manufacturing cost of the product. The cost of capacitor rises exponentially with its rated voltage and
capacitance.
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Freescale Semiconductor
Power Factor Correction and Output Inverter
The dc-bus capacitor is a storage of energy for output power factor circuit and feeds an output inverter.
The dc-bus voltage should be set above the peak at maximum r.m.s. input voltage. For input RMS voltage
Vin = 270 V, the peak voltage is Vin peak max = 381 V. To achieve good regulation of the dc-bus voltage,
the dc-bus voltage should be at least 10% above the peak at nominal r.m.s. input voltage, i.e. for
Vin nom = 230 V RMS: Vdc-bus min = 1.1x1.41x230 = 356 V. Having Vin peak max and Vdc-bus min, we can
determine the dc-bus nominal voltage. We chose Vdc-bus nom = 390 V.
The dc-bus capacitor voltage should at least be rated at 450 V dc.
If ac input is lost, it is desired that the dc-bus capacitor is large enough to hold up the dc-bus voltage at
value Vdc-bus hup, allowing the output inverter voltage to remain within specifications for a time T hup.
The maximum nominal output voltage is Vout nom = 230 V RMS. The dc-bus voltage has to be higher than
the output voltage peak value Vout peak = 325 V. The hold-up time we define as a half-period of the output
ac voltage frequency Thup = 10ms. The minimum dc-bus capacitor value can calculated:
I av ⋅ T hup
C 0 = ----------------------------------------------------V dc – busnom – V outpeak
(EQ 4-43)
where
Iav is the average capacitor current during the drop from Vdc-bus nom to Vout peak.
The Iav current can be calculated according to the formula:
2P out
I a v = -------------------------------------------------------------η ( V dc – busnom + V outpeak )
(EQ 4-44)
where
Pout is the inverter output power
η is the inverter efficiency
We can enumerate equation EQ 4-44 and obtain:
2 ⋅ 525
I a v = ---------------------------------------- = 1.728A
0.85 ( 390 + 325 )
(EQ 4-45)
The minimum output capacitor value can be calculated if we enumerate formula EQ 4-43:
–3
–6
1.728 ⋅ 10 ⋅ 10
C 0 = --------------------------------------- = 266 ⋅ 10 F
390 – 325
(EQ 4-46)
The minimum output capacitance of the dc-bus capacitor is 266µF.
The next parameter we need to know for selecting the output capacitor is the ripple current rating. The
dc-bus capacitor current consists of a dc-component plus an ac-component (100/120 Hz). The
dc-component flows to the load, ac-component flows into the capacitor C0. The ripple current amplitude
is equal to the peak load current. The ripple current can be then calculated:
I load
I ri ppl e = --------2
(EQ 4-47)
Pout
525
I l oad = ------------------------------------------ = ------------------------------- = 0.792A
2 ⋅ V dc – busnom ⋅ η
2 ⋅ 390 ⋅ 0.85
(EQ 4-48)
The peak load current Iload is:
Single Phase On-Line UPS Using MC9S12E128
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Hardware Design
Ripple current is then: Iripple = 0.792/1.41 = 0.562 A.
The waveform applied to the dc-bus capacitor is a near-rectangular waveform at the switching frequency.
Therefore the dc-bus capacitor should have a low impedance at the switching frequency. A low-ESR
electrolytic capacitor should be considered for this application.
Considering all the above requirements, we selected following dc-bus capacitor:
Table 4-10. dc-bus Capacitor Parameters
Parameter
Manufacturer
Value
Unit
BC Components (Vishay)
Catalogue Number
2222 157 47331
Rated Capacitance
330
µF
Rated Voltage
450
V d.c.
ESR @ 100 Hz
300
mΩ
Ripple Current@ 120 Hz
2.19
A
4.5.3 Output Inverter Operational Description
This section deals with the design of the output inverter of the single-phase UPS. The purpose of the
output inverter is to convert dc-voltage of the dc-bus to an output single-phase sinusoidal voltage of the
required amplitude and frequency.
The topology of the inverter circuitry is shown in Figure 4-21. The power circuit consists of IGBT power
switches Q605 and Q608, which are connected across dc-bus capacitors C602, C608. An emitter
terminal of Q605 and a collector terminal of Q608 are connected to a sinusoidal filter (inductor L506 and
a capacitor C605). Output of the sinusoidal filter is then connected to the by-pass relay RE2 and EMC
filter (L205, C604, C602). Output relays RE1, RE3, connect the inverter output to output terminals of the
UPS. The nominal specifications of the output inverter are listed in theTable 4-11.
Table 4-11. Output Inverter Specifications
Parameter
Value
Unit
Input Voltage Min.
2x340
V[d.c.]
Input Voltage Max.
2x430
V[d.c.]
Output a.c. Voltage
80 - 270
V [r.m.s.]
Output Apparent Power Nominal(1)
750
VA
Output Current Nominal
3.3
A[r.m.s]
Switching frequency
20
kHz
1. Nominal output apparent power for nominal output voltage 230 V r.m.s.
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RE1
MZPA001
5 o
OUT1
o 4
3 o
+15V
1
2
RE2
MZPA001
D602
5 o
o 4
L2
3 o
+15V
RLY_OUT1
1
Q602 S
MMBF0201NLT1
GND
RE3
MZPA001
D603
D
R603
G
100
2
BAT42
RLY_BYPASS
D
BAT42
R602
5 o
OUT2
o 4
G
100
3 o
Q603 S
MMBF0201NLT1
GND
+15V
1
2
DCB_POS
D605
D
BAT42
R604
RLY_OUT2
C602
+
330uF/450V
GATE_TOP
Q604 S
MMBF0201NLT1
GND
Q605
HGTG10N120BND
V_OUT
L506
GND_TOP
5mH
2
6.8uF/400V
4
L507
TL34P
C604
1
3
3
4
C605
1
2
N
CT2
GND
I_OUT2
5
8
CS2106
I_OUT1
Q608
+
GATE_BOT
C608
330uF/450V
G
100
HGTG10N120BND
GND_BOT
DCB_NEG
Figure 4-21. Output Inverter Power Circuit
PE
4.7nF/Y1
C606
4.7nF/Y1
N_OUT
Hardware Design
The power IGBTs Q605 and Q608 switch in a complementary manner (if Q605 is on, Q608 is off, and vice
versa). Using the power IGBTs, the dc-bus voltage is pulse-width modulated at 20kHz switching
frequency to obtain an output voltage with a low frequency a.c. component (50/60 Hz). The junction of
C602 and C608 is a zero-volts reference for the generated output waveform. The junction of the
capacitors is galvanically connected to the mains N-terminal and is labelled as system ground.
Switching pulses to gates Q605 and Q608 are generated by the dual IGBT gate opto-drive HCPL-315J
(U615). The opto-drive provides the circuitry with galvanic isolation between the MCU and each of the
IGBTs. Its topology is shown in the Figure 4-22. The IGBT gates are floating during the inverter operation
in a voltage range +/- 430 V dc. Each channel of the dual opto-drive IC is supplied from a galvanically
isolated voltage supply of +15V dc.
GATE_TOP
+15V_TOP
D611
D610
BAT42
PWM_TOP
C610
100nF
R608
BAT42
330
33
D625
5V
R610
100
D613
1
2
3
BAT42
PWM_BOT
D624
15V
R609
R611
6
7
8
330
U615
N/C
VCC1
ANODE1
VO1
CATHODE1 VEE1
16
15
14
ANODE2
VCC2
CATHODE2 VO2
N/C
VEE2
11
10
9
C632
100nF
GND_TOP
-5V_TOP
GATE_BOT
+15V_BOT
HCPL-315J
GND
GND_TOP
D612
C611
100nF
BAT42
D626
15V
R612
33
D627
5V
R613
100
C633
100nF
GND_BOT
GND_BOT
-5V_BOT
Figure 4-22. Inverter IGBT Gate Drive Circuitry
The by-pass relay RE2 connects the UPS output to either the inverter or the mains voltage.
The relays RE1 and RE3 connect the UPS output socket banks to the output voltage.
A current transformer CT2 is put into the output current path. Together with current-to-voltage converter
circuitry, it makes up the sensing circuitry of the output load current.
NOTE
Please note that during operation, the voltage on the power IGBTs is a sum
of the voltages on the dc-bus capacitors, i.e., it can reach up to
2 x 430 V = 960 V! The IGBTs must be rated for a collector-emitter voltage
of 1200 V.
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Power Factor Correction and Output Inverter
4.5.4 Output Inverter Design Considerations
In this section we will discuss the design considerations of the critical components of the output inverter.
The sinusoidal output filter is a low-pass LC-filter consisting of an inductor L506 and a capacitor C605.
The resonant frequency of the circuit has to be selected with respect to the output voltage control loop.
Based on the Simulink simulation results we have selected a resonant frequency in the range:
600 to 900 Hz.
Having the resonant frequency we are able to select values of the inductor and capacitor. To achieve the
required resonant frequency of the filter we have plenty of variants of L and C distribution. The values of
the components have to be selected with consideration of their size, cost and availability. Considering the
components available in the market, we have chosen following combination:
• L506 = 5 mH
• C605 = 6.8 µF
The resonant frequency of such a circuit is 863 Hz and falls in our range.
4.5.4.1 C605 Capacitor Selection
The capacitor parameters have to fulfil safety requirements for rated ac voltage. Low ESR and ESL
parameters are required to achieve a low output voltage ripple. For the output sinusoidal filter we selected
MKP 338 4 X2 capacitor from Vishay BC components. See Table 4-12.
Table 4-12. MKP 338 4 X2 Capacitor Reference Data
Parameter
Capacitance
Value
6.8 µF
Capacitance tolerance
20%
Rated (ac) voltage, 50 to 60 Hz
300V
Rated (dc) voltage
630V
Rated temperature
105°C
Safety class
X2; across the line
4.5.4.2 L506 Inductor Core Selection
As soon as we know the required inductance, we can proceed to select the core material and size.
Because the inductor current contains a high frequency ripple, we will consider an iron-powder core.
Size of the core can be established by an iterative process using the manufacturer’s catalog data. We
have chosen Micrometals as the material supplier. Again as with the PFC inductor design, we used the
Micrometals software to find the best fitting core.
For the design of the output filter inductor, we can use either “dc biased” design or “PFC boost”. The
calculations of both are similar, however, the “PFC Boost” calculations account for a periodic change to
the switching duty-cycle. We can thus more accurately represent the losses in the inductor core.
Therefore we selected “PFC Boost” design. In the parameter window of the design, we entered the
parameters shown in Table 4-13.
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Hardware Design
Table 4-13. Output Filter Inductor Parameters
Parameter
Value
Unit
5000
µH
Maximum current
4.6
A
Peak regulator input voltage
340
V
Regulator dc output voltage
400
V
Frequency
20
kHz
Temperature
55
°C
Core shape
Toroid
-
Full window
-
Inductance at max current
Winding type
NOTE
Note that we swapped the input and output peak voltage values in the
design parameters. In a real inverter, the dc voltage is the input parameter
and the ac voltage is the output parameter. To make an analogy with PFC,
we have to swap these parameters in the input table.
We ran the calculation and got a list of suitable cores that met our selection criteria. From the list we
selected core: T200-30B. The software calculates all important data (number of turns, wire diameter,
losses, Rdc, Al, dimensions, etc.). For the selected core, the parameters are as follows:
Table 4-14. Design Parameters for Core P/N: T175-8/90
Parameter
Value
Unit
Al
51
nH
Turns
388
-
Wire
1.00
MM.
Fill
38.5
%
Rdc
0.8868
Ohms
Core loss
1.46
W
Cu loss
9.38
W
Temperature rise
46.4
°C
The core T200-30B meets all of our criteria, is an acceptable size, with moderate losses and low price.
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Chapter 5
Software Design
5.1 Introduction
This section describes the design of the software blocks for the UPS. The software is described in terms
of:
• Data flow
• Main software flowchart
• State diagram
For more information on the control technique used, see Chapter 3 UPS Control.
5.2 Data Flow
The control algorithm obtains values from the user interface and sensors, processes them, and generates
PWM signals for the dc/dc step-up converter, output inverter, and sine wave reference for PFC, as can
be seen on the data flow analysis shown in Figure 5-1.
5.2.1 Software Variables and Defined Constants
Important system variables, named in the data flow, are listed in Table 5-1. The table includes the name,
range used, and representation in real quantities.
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counter_actual
Button
Processing
v_out_rms
PLL
Algorithm
phase_out
phase_pfc
phase_pfc_inc
amplitude_correction
phase_out_inc
Mains Line
Detection
RMS
Correction
v_dcb_req
buttonStatus
v_out_freq_detect
amplitude_ref
v_dcb[]
Application State
Machine
DC Bus
Scaling
Sine Wave
Reference
appState
Ramp
v_sin_ref
v_dcb[]
v_dcb_req_rmp
v_out
v_dcdc_req
Inverter
Control
PFC Control
LED
Processing
PWM_to_DCB_scale
V_bat
I_bat
Ramp
PWMB_duty_cycle
i_n_ref
Sine Wave
Reference
v_dcdc_req_rmp
v_dcdc_sum
DC/DC Step Up
Control
pfc_ref_h
PWMC_duty_cycle
Figure 5-1. Main Data Flow
Battery Charge
Control
BatState
Data Flow
Table 5-1. Software Variables
Name
Type
<Range>; [Scale]
Description
amp_ControllerPar
Structure
-
PI controller parameters for RMS correction
amplitude_correction
U16
<0, 39936>; [0V, 400V]
output of RMS correction
amplitude_ref
U16
<0, 39936>; [0V, 400V]
required amplitude of output sine wave
appState
enum
-
state of application state machine
BatState
enum
-
state of battery charger
counter_actual
U16
<0,5580>; [0 s, 7.14 ms (70
Hz)]
period of input voltage zero crossing
dcdc_duty
U16
<0, 121>; [0%, 96.8%]
duty cycle of dc/dc step-up converter
i_bat
S16
<0, 1023>; [0 A, 2.34 A]
battery charging current
i_out
S16
<-32768, 32767>;
[-13 A, 13 A]
actual output current
i_out_rms
S16
<-32768, 32767>;
[-13 A, 13 A]
RMS value of output current
pfc_ref_h
U8
<0, 152>; [0 A, 5 A]
required actual input (PFC) current
phase_diff
S16
<-32768, 32767>;
[-180º, 180º]
phase difference between expected and actual
phase of PLL
phase_measured
S16
<-32768, 32767>;
[-180º, 180º]
calculated phase
phase_out
S16
<-32768, 32767>;
[-180º, 180º]
actual phase of generated output voltage
phase_out_inc
U16
<33554, 58720>;
[40 Hz, 70 Hz]
increment to sine wave table (output voltage)
phase_pfc
S16
<-32768, 32767>;
[-180º, 180º]
actual phase of input voltage calculated by PLL
PWMB_duty_cycle
U16
<0, 625>; [-100%, 100%]
duty cycle of output inverter
PWMC_duty_cycle
U16
<0, 121>; [0%, 96.8%]
duty cycle of dc/dc step-up converter
temperature
U16
<0, 205>; [0 ºC, 100 ºC]
temperature of power stage heatsink
v_bat
U16
<0, 1023>; [0 V, 39 V]
battery voltage
v_dcb[]
U16
<0, 1023>; [0 V, 450 V]
dc bus voltage
v_dcdcControllerPar
Structure
-
PI controller parameters for dc/dc controller
v_in
U16
<0, 1023>; [0 V, 324 V]
RMS value of input voltage
v_out
S16
<-19968, 19968>;
[-400 V, 400 V]
actual output voltage
v_out_freq_detect
U16
<33554, 58720>;
[40 Hz, 70 Hz]
detected input frequency
v_out_rms
U16
<-19968, 19968>;
[-400 V, 400 V]
RMS value of output voltage
v_pfcControlerPar
Structure
-
PI controller parameters for PFC controller
v_sine_ref
S16
<-19968, 19968>;
[-400 V, 400 V]
required value of output voltage (sine wave
reference including amplitude correction)
Type: S8 = signed 8-bit, U8 = unsigned 8-bit, S16 = signed 16-bit, U16 = unsigned 16-bit.
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Software Design
5.2.2 Process PLL Algorithm
The PLL algorithm synchronizes the pointer to the PFC sine wave reference with the input line voltage.
The algorithm uses the variable counter_actual as an input and calculates the phase_pfc,
phase_pfc_inc, phase_out and phase_out_inc. The variables relating to the output inverter are
generated if the output is synchronized with the output.
5.2.3 Process RMS Correction
Because the output inverter PID controller is not able to keep a constant RMS value of output voltage due
to slight or missing integral part of the controller, the RMS correction must be calculated. The RMS
controller compares the actual RMS value v_out_rms with the required RMS value calculated from
amplitude_ref. The output of PI controller is correction to the amplitude, stored in
amplitude_correction.
5.2.4 Process Mains Line Detection
This process sets the mains line system to 230 V, 50 Hz or 115 V, 60 Hz according to state of
START/STOP switch on the MC9S12E128 controller board. The detected values amplitude_ref and
v_out_freq_detected are used for the output inverter to generate the correct output and for the PFC
PLL to determine that the PLL algorithm is synchronized.
5.2.5 Process Ramp
The ramp process changes an input value in a time period with a predefined slope. A different ramp can
be defined for a rising and falling slope.
5.2.6 Process Sine Wave Reference
The sine wave reference process generates the sine wave reference waveform v_sin ref based on the
actual phase phase_out, phase increment corresponding to the generated frequency phase_out_inc,
and amplitude amplitude_ref + amplitude_correction.
5.2.7 Process Button Processing
The button processing reads the status of the ON/OFF and BYPASS buttons. It recognizes a short and
long push. The results are saved in variable buttonStatus.
5.2.8 Process LED Processing
The process handles the LEDs on the user interface. Each LED can be switched on, off, or to flash. The
LED status bar works in two modes. In output power mode, the status bar displays the actual output
power. In battery mode it shows remaining battery capacity.
5.2.9 Process Application State Machine
This process provides the state machine of UPS. The state machine defines the following states:
• Init
• Standby on battery
• Standby on line
• Run on battery
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Data Flow
•
•
•
•
Run on line
Run on bypass
Error
UPS off
After RESET, the state machine enters into the Standby on battery state if the mains line is available.
Then if the user pushes the ON/OFF button, the state machine continues on to the Run on line state.
During mains line failure, the state machine goes to the Run on battery state. The state machine stays
there until the batteries are discharged, the user switches the UPS off, or the main line is restored. If the
batteries are discharged the state machine goes to the Standby on battery state. If the state machine
stays in this state one minute, the UPS is switched off (UPS state) to avoid total discharge of the batteries.
In the case of some fault, the state machine goes into the Error state.
If the state machine goes from one to another state, a respective transition function is called.
CPU RESET
INIT
STANDBY
BATTERY
STANDBY
ONLINE
RUN ON LINE
RUN
ON BATTERY
ERROR
RUN BYPASS
UPS OFF
Figure 5-2. Application State Machine
5.2.10 Process PFC Control
The PFC control process consists of the PI controller, which controls the dc bus voltage
v_dcb[] to the required value v_dcb_req (v_dcb_req_rmp). The result defines the
amplitude of the input current (i_n_ref).
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Software Design
5.2.11 Process Sine Wave Reference (PFC)
This process generates a rectified sine wave waveform based on the required amplitude i_n_ref, actual
phase phase_pfc, and the required frequency phase_pfc_inc. The result pfc_ref_h is sent to the
D/A converter and is used as the reference for the external current controller.
5.2.12 Process dc Bus Scaling
The scaling process calculates the correction constant PWM_to_DCB_scale for inverter duty cycle. The
duty cycle, which outputs from the PID controller, is related to constant dc bus voltage. If the actual dc
bus is different, the duty cycle has to be recalculated to the actual dc bus. For example, if the output duty
cycle is 50% (195 V) for 390 V of dc bus voltage and the actual dc bus voltage is equal to 380 V, the
resultant duty cycle has to be recalculated to 51.3% to maintain 195 V.
5.2.13 Process dc/dc Step-Up Control
The process is similar to the PFC control process. The input value is v_dcdc_req (v_dcdc_req_rmp)
and the result is PWMC_duty_cycle.
5.2.14 Process Inverter Control
The inverter control process performs PID controller including feed forward technique. The inputs are
v_sin_ref, v_out, and PWM_to_DCB_scale, and the output is the duty cycle PWMB_duty_cycle.
5.2.15 Process Battery Charge Control
The battery charger control process charges the batteries. The charging current i_bat and battery
voltage v_bat are read, and according to the actual battery current, the state of the charging algorithm
BatState is set to BULK CHARGE MODE, ABSORPTION MODE, or FLOAT MODE.
5.3 Main Software Flowchart
The software is written in C language using Metrowerks CodeWarrior software. Some time-critical parts
such as sine wave generation and arithmetical functions are written in assembler.
The software consists of the following parts:
• Initialization of peripherals and variables
• Background group
• 5 periodic interrupts (2 x 50 µs, 1 x 1 ms, 1 x 10 (8.3) ms, 1 x 50 ms)
• 3 event interrupts (PMF faults, LVI, SCI)
5.3.1 Initialization of Peripherals and Variables
After RESET, the program goes into the initialization routine. The routine initializes the following
peripherals:
• PLL
• I/O pins
• Analog to digital converter
• Digital to analog converter
• Pulse-width modulator with fault protection
• Timer 0
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Main Software Flowchart
•
•
Pulse-width modulator
Voltage regulator
Subsequently, the communication with the PC is initialized, and the program variables are set to default
values.
Then the program enters the never-ending loop providing the application state machine (see main
function listing below).
void main ()
{
InitPeripherals();
PCMaster_Config();
EnableInterrupts; /* enable interrupts to make this routine
interruptible
(defined int PCMaster-S12.h) */
PCMasterInit();
// init PCMaster functions
InitVariables();
while(1)
{
appStateFcn[appState]();
FanControl();
}
}
The structure of the background loop can also be seen in Figure 5-3.
RESET
Peripheral and variable
inicialization
Background loop
Application state machine
execution
END
of Background loop
Figure 5-3. Background Loop
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Software Design
5.3.2 Periodic Interrupts
The software uses five periodic interrupts. They are:
• PMF reload interrupt (called every 50 µs)
• ATD conversion complete interrupt (called every 50 µs)
• TIM0 CH4 input capture interrupt (called every 8.3 or 10 ms)
• TIM0 CH5 output compare interrupt (called every 1 ms)
• TIM0 CH6 output compare interrupt (called every 50 ms)
5.3.2.1 PMF Reload Interrupt
The PMF Reload Interrupt is part of the UPS main control loop. The source of the interrupt is a reload
event of counter B (output inverter). The structure of the interrupt can be seen on Figure 5-4.
PMF B Reload Interrupt
(50 ms)
Read samples
of slow ATD Conversion
Start fast ATD Conversion
Lost detection
of Line Zero Crossing
Output power and
RMS Value Calculation
Input voltage polarity detection
PFC reference sine wave
generation
Inverter reference sine wave
generation
END
of Interrupt Service Routine
Figure 5-4. Structure of PMF Interrupt
The interrupt starts by reading a slow ATD conversion. A slow ATD conversion means that the quantities
are not converted every 50 µs. There is a table which defines the order of quantities to be converted. The
results of a slow ATD conversion are ready from previous interrupt.
After saving the conversion results, a fast ATD conversion is set and started. A fast ATD conversion
means that the quantities are converted every interrupt (50 µs). The output voltage and current are
sensed in the fast ATD conversion.
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Main Software Flowchart
While the fast ATD conversion is running the following tasks are performed:
• Detection of missing zero crossing on the input line
• Detection of input voltage polarity
• RMS value calculation and output power calculation (multiplication and addition)
• Generation of rectified sine waveform for the PFC
• Generation of sine wave reference for the output inverter
The execution time for these tasks is shorter than the conversion time in a fast ATD conversion.
5.3.2.2 ATD Conversion Complete Interrupt
As soon as the fast conversion is completed and the PMF reload interrupt executed, the ATD conversion
complete interrupt is called. This interrupt performs the inverter control and starts the next slow ATD
conversion (see Figure 5-5). Because this interrupt is bounded by the PMF reload interrupt, the execution
period is also 50 µs.
Both interrupts, together with the TIM0 CH5 output compare interrupt, comprise the main part of the UPS
control algorithm. The PMF reload and ATD conversion complete interrupts have the highest priority and
are uninterruptible.
ATD Conv. Complete Interrupt
(50 ms)
Start fast ATD conversion
Output inverter controller
END
of Interrupt Service Routine
Figure 5-5. Structure of ATD Conversion Complete Interrupt
5.3.2.3 TIM0 CH4 Input Capture Interrupt
The source of this interrupt is a zero crossing on the input voltage. So the interrupt is executed every
8.3 ms or 10 ms. The interrupt performs a phase locked loop algorithm, which synchronizes the
generation of PFC and output inverter sine wave references with the input voltage.
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Software Design
TIM 0 ch 4 IC Interrupt
(Line Zero Crossing)
PFC PLL algorithm
END
of Interrupt Service Routine
Figure 5-6. TIM0 CH4 Input Capture Interrupt
5.3.2.4 TIM0 CH5 Output Compare Interrupt
The source of this interrupt is the output compare event, set to generate event every 1 ms. This interrupt
comprises the second part of the control algorithm. The structure of the interrupt is shown in Figure 5-7.
TIM 0 ch 5 OC Interrupt
(1 ms)
PFC control loop
DC/DC step up converter
control loop
Filtering and scaling
of analog values
Output power and
RMS values calculation
RMS correction
END
of Interrupt Service Routine
Figure 5-7. Structure of TIM0 CH5 Output Compare Interrupt
The interrupt performs following tasks:
• Voltage control loop of the PFC
• dc/dc step-up converter control loop
• Filtering and scaling of analog values measured in the slow ATD conversion
• finishing the RMS and output power calculations (multiplication by constant and square root)
• RMS correction algorithm
This routine has a lower priority and can be interrupted by the PMF reload and ATD complete interrupts.
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Main Software Flowchart
5.3.2.5 TIM0 CH6 Output Compare Interrupt
The last periodic interrupt is called every 50 ms. The time base is derived from TIM0 CH6 output compare
event, which is set to generate this period. The interrupt performs background tasks which require
periodic execution but with a very low priority. The tasks are:
• Software timers
• User interface handling (buttons, LED diodes)
• Battery charger algorithm
TIM 0 ch 6 OC Interrupt
(50 ms)
Software timers
User interface handling
Battery charging
END
of Interrupt Service Routine
Figure 5-8. Structure of TIM0 CH6 Output Compare Interrupt
5.3.3 Event Interrupts
The event interrupts are called on an event. The UPS application uses following event interrupts:
• SCI interrupt (performing the communication with PC)
• PMF fault interrupt
• Voltage regulator — low voltage inhibit interrupt
5.3.4 Interrupt Time Execution and MCU Load Estimation
The time execution of periodic interrupts was measured by oscilloscope. The result can be seen in
Figure 5-9.
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Software Design
Trace
PMF Reload Interrupt
Trace
ATD Complete Interrupt
Trace
1 ms Interrupt
Trace
50 ms
Figure 5-9. CPU Load of UPS Application
Trace 1 (blue) represents a PMF reload interrupt; Trace 2 (cyan) is an ATD complete interrupt; Trace 3
shows 1 ms interrupt; Trace 4 (green) is 50 ms. The total MCU load is 65.16%. The execution time of each
interrupt can be seen in Table 5-2, and the size code in Table 5-3.
Table 5-2. Execution Time of Periodic Interrupts
Execution
Period
Execution
Time
PMF reload interrupt
50 µs
15.8 µs
ATD conversion complete interrupt
50 µs
14.2 µs
8.3 ms or 10 ms
7.8 µs
TIM0 CH5 output compare interrupt
1 ms
50 µs
TIM0 CH6 output compare interrupt
1 ms
35.8 µs
Name
TIM0 CH4 input capture interrupt
Table 5-3. Size of UPS Application Code
Memory Type
Size in Bytes
FLASH
10087
RAM
2502
Stack
512
Single Phase On-Line UPS Using MC9S12E128
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Software Constant Calculations
5.4 Software Constant Calculations
This section describes the calculation of some software constants from real values to software
implementation.
5.4.1 PI and PID Controller Constants
Because the MCU works with integer arithmetic only each constant KREAL in the real system is expressed
in the software as:
GAIN
K REAL = ----------------------------( 16 – SCA LE )
2
(EQ 5-1)
To keep the maximal precision of calculation, the SCALE should be set in order to push the GAIN into the
upper half of the variable range.
Example:
Let’s convert a constant 25 in U16 representation. The upper half of the U16 range is from 32768 to
65536. The get this constant to optimal range we set the SCALE to 5. Then the GAIN = 25 .
2(16-5) = 51200.
NOTE
Note that the SCALE is shared for all constants in the PI/PID controller. So
in case of a highly different order in the constants, a compromise has to be
made.
The controller implementation is explained in 3.1.5 PI and PID Controller. From EQ 3-7 results, the
proportional constant is equal to the gain of the system.
The integral constant of the controller can be expressed as:
Kh
------TI
(EQ 5-2)
where
TI
=
Integral time constant
h
=
Sampling time
K
=
Controller gain
See EQ 3-8. The derivative constants are defined as:
TD
kd1 = -------------------T D + Nh
KT D N
kd2 = -------------------T D + Nh
(EQ 5-3)
(EQ 5-4)
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
85
Software Design
where
h
=
Sampling time
TD
=
Derivative time constant
N
=
Filter constant
NOTE
The proportional constant of the output inverter controller is called q1 in the
software.
Example:
Let’s have constants for the PFC controller. The PFC uses the PI controller, where the controller gain
K(P) = 100 and Integral time constant TI = 0.0016 s. The controller is calculated every 1 ms.
–3
100 ⋅ 1 ⋅ 10
From EQ 5-2 we can calculate integral constant as: ------------------------------ = 6.25 .
0.0016
Since the scale is common for both constants, we choose SCALE = 8. Then we get a proportional gain
100 . 2(16-8) = 25600 and an integral gain 6.25 . 2(16-8) = 1600. In the source code we can see:
#define PFC_P_GAIN_BASE
#define PFC_I_GAIN_BASE
#define PFC_SCALE
25600
1600
8
Single Phase On-Line UPS Using MC9S12E128
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Freescale Semiconductor
Chapter 6
Tests and Measurements
6.1 Test Equipment
All tests were done using the following equipment:
• 2x multimeter 34401A, Hewlett Packard
• Scope TDS3014B, Tektronix
• 3-phase precision power meter LMG 310, Zimmer Electronic Systems
6.2 Load Parameters
The parameters were measured for both linear and non-linear loads. The loads were calculated according
to standard IEC 62040-1. The reference load was calculated for a nominal output power of 750 VA. The
parameters of the loads are:
• Linear load: R = 100 Ω
• Non-linear load: R = 160 W, RS = 2.8 W, C = 780 mF (see Figure 6-1)
D1
D3
Rs
2.8
+
D2
C1
937 uF
P1
160
D4
Figure 6-1. Non-Linear Load
Single Phase On-Line UPS Using MC9S12E128
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87
Tests and Measurements
6.3 Test Results
6.3.1 Overall Efficiency at Linear Load
The total efficiency at a linear load is 91%. See Figure 6-2. The picture shows the display of 3-phase
precision power meter indicating the input power (P1), output power (P2), losses (LOSS) and calculated
efficiency (EFF).
Figure 6-2. Overall Efficiency at Linear Load
Figure 6-3. Output Voltage and Current at Linear Load
Single Phase On-Line UPS Using MC9S12E128
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Freescale Semiconductor
6.3.2 Overall Efficiency at Non-linear Load
The total efficiency at a non-linear load is 90%. See Figure 6-4.
Figure 6-4. Overall Efficiency at Non-linear Load
Figure 6-5. Output Voltage and Current at Non-linear Load
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
89
Tests and Measurements
6.3.3 Output Frequency Measurement
The next two pictures show the generation of output frequency. The left multimeter shows input
frequency, and the right one shows output frequency. Figure 6-6 shows the synchronized output with
input. Figure 6-7 shows a free running mode. In this case the precision of the output frequency is given
by the precision of the MCU crystal.
Figure 6-6. Output Frequency in Synchronized Mode
Figure 6-7. Output Frequency in Free-running Mode
Single Phase On-Line UPS Using MC9S12E128
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Freescale Semiconductor
Test Results
6.3.4 Output Voltage THD
Output voltage THD was measured for three cases:
• Without load: THD = 0.4%
• With full linear load: THD = 1%
• With full non-linear load: THD = 5%
The next two pictures show details of output voltage and current at a non-linear load.
Figure 6-8. Output Voltage and Current at Non-linear Load — Detail
Figure 6-9. Output Voltage and Current at Non-linear Load
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
91
Tests and Measurements
6.3.5 Power Factor Measurement
The power factor measured can be seen in Figure 6-10. The figure shows input voltage U3, input current
I3, and power factor λ3.
Figure 6-10. Power Factor Measurement
6.3.6 Response on Step Load
The following four pictures show the response of the output controller a on step load from 20% to 100%,
and vice versa, for a linear load.
Single Phase On-Line UPS Using MC9S12E128
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Freescale Semiconductor
Test Results
Figure 6-11. Load Step from 20% to 100%
Figure 6-12. Load Step from 20% to 100% — Detail
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
93
Tests and Measurements
Figure 6-13. Load Step from 100% to 20%
Figure 6-14. Load Step from 100% to 20% — Detail
Single Phase On-Line UPS Using MC9S12E128
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Freescale Semiconductor
Test Results
6.3.7 Summary
All measured parameters are summarized in Table 6-1
Table 6-1. Summary of Measured Parameters
Load
Parameter
Efficiency
Linear
Non-linear
91%
90%
Output voltage THD without load
Output voltage THD
Power factor
Precision of generated frequency
0.4%
1%
5%
0.99
< 0.01%
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
95
Tests and Measurements
Single Phase On-Line UPS Using MC9S12E128
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Freescale Semiconductor
Chapter 7
System Set-Up and Operation
WARNING
This application operates in an environment that includes dangerous
voltages. The application includes batteries and dangerous voltage
may appear even if the application is not connected to the mains line.
An isolating transformer should be used during debugging. If an
isolating transformer is not used, power stage grounds and
oscilloscope grounds will be at different potentials, unless the
oscilloscope is floating. Note that probe grounds, such as in the case
of a floating oscilloscope, are subject to dangerous voltages. Take
note of the following points and recommendations
•
•
•
•
•
•
•
Switch off the high-voltage supply before moving scope probes or
making connections.
Avoid inadvertently touching live parts, and use plastic covers
where possible.
When the high voltage is applied, using only one hand to operate
the test setup will reduce the possibility of electrical shock.
Avoid using the application in laboratory environments that have
grounded tables or chairs.
Wear safety glasses, avoid ties and jewelry, use shields, and make
use of personnel trained in high-voltage laboratory techniques.
The power module heatsink can reach temperatures hot enough to
cause burns.
When powering down, due to storage in the bus capacitors,
dangerous voltages are present until the power-on LED is off.
7.1 Hardware Setup
The UPS demo is mounted into a metal case which provides safe operation. The case cover is made from
transparent plastic, which allows the UPS construction to be seen (see Figure 7-1).
Single Phase On-Line UPS Using MC9S12E128
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System Set-Up and Operation
Figure 7-1. UPS Demo
WARNING
Do not touch any part of the board inside the metal case regardless of
whether the UPS is running from mains line or batteries. There is a
high risk of electric shock caused by high voltage, which may cause
serious injury or death.
To prepare the UPS for operation, follow these steps:
1. Connect the power supply cable to the INPUT LINE socket.
2. Connect the load supply cable to any OUTPUT SECTION socket. Be sure that the load power is
within the limit of the UPS demo.
3. In the case of remote operation from a PC, connect a serial cable between the PC and the J2
connector of the UPS (on the right-hand side in Figure 7-3 and Figure 7-5).
4. Switch MAINS INPUT LINE switch ON.
5.
If the mains line is available, the UPS will go into standby on-line mode. In this mode, the MCU
works and the batteries are charged, but the output is still switched off.
In the case of remote operation, run the FreeMaster software on the PC and load the project file,
UPS.pmp.
The UPS is ready for operation.
Single Phase On-Line UPS Using MC9S12E128
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Freescale Semiconductor
MAINS LINE
SWITCH
OUTPUT
SECTION 2
OUTPUT
SECTION 1
MAIN LINE
INPUT
Figure 7-2. UPS Input and Outputs
7.1.1 Setting of Mains Line System
Because the UPS can not detect the mains line system if it starts to run from batteries, the system can be
predefined by the START/STOP switch on the MC9S12E128 controller board. If the switch is in the RUN
position, the UPS generates outputs 230 V, 50 Hz. In STOP position, the UPS generates 115 V, 60 Hz.
External Battery
Connector
Serial Ports
Figure 7-3. UPS Serial Ports and External Battery Connector
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
99
System Set-Up and Operation
7.2 Software Setup
7.2.1 Application Software Files
The application software files are:
• ...\software\UPS\OnlineUPS\on_line_ups.mcp, application project file
• ...\software\UPS\OnlineUPS\sources\main.c, main program
• ...\software\UPS\OnlineUPS\sources\main.h,
header file for main code
• ...\software\UPS\OnlineUPS\sources\PCMaster.c, library of FreeMaster functions
• ...\software\UPS\OnlineUPS\sources\PCMaster.h,
library of FreeMaster functions definitions file
• ...\software\UPS\OnlineUPS\sources\PCMasterConfig.h,
configuration file for FreeMaster
• ...\software\UPS\OnlineUPS\sources\projectglobals.h, global definitions file of HCS12
stationary
• ...\software\UPS\OnlineUPS\sources\projectvectors.c, source file of interrupt routines
• ...\software\UPS\OnlineUPS\sources\projectvectors.h, header file for interrupt routines
• ...\software\UPS\OnlineUPS\sources\START12.C, start up code for HCS12 stationary
• ...\software\algorithms\sin.asm,
library with sine wave generation functions
• ...\software\algorithms\sin.h,
header file for sine wave generation functions
• ...\software\algorithms\sinlut.asm,
sinus look up table for sine wave generation functions
• ...\software\algorithms\upsmath.asm,
library of mathematical functions written in assembler
• ...\software\algorithms\upsmath.c,
library of mathematical functions written in C language
• ...\software\algorithms\upsmath.h,
header file for library of mathematical functions
7.2.2 Application PC Master Software Control Files
The application PC master software control files are:
• ...\software\UPS\OnlineUPS\PCMaster\UPS.pmp,
PC master software project file
• ...\software\UPS\OnlineUPS\PCMaster\source,
directory with PC master software control page files
Single Phase On-Line UPS Using MC9S12E128
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Freescale Semiconductor
Software Setup
7.2.3 Application Build
To build the online UPS application, open the on_line_ups.mcp project file and execute the Make
command, as shown in Figure 7-4. This will build and link the application with all the required Metrowerks
libraries.
Figure 7-4. Execute Make Command
Single Phase On-Line UPS Using MC9S12E128
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101
System Set-Up and Operation
7.2.4 Programming the MCU
Because the UPS power supply is controlled by the MCU, the following sequence must be used to
program the MCU:
1. Switch the UPS OFF by the ON/OFF switch
2. Switch the MAINS LINE switch to OFF
3. Wait one minute until the UPS has totally switched off
4. Disconnect the power supply cable from the socket
5. Remove the transparent plastic cover
6. Disconnect the cable from J4 on the user interface
7. Connect a BDM cable to the MC9S12E128 controller board
8. Connect the cable to any test point named GND on the UPS power stage (e.g., TP206)
9. Load the code to the MCU
10. Remove the cable from GND test point and wait until the UPS has totally switched off
11. Connect the cable back to J4 on the user interface
12. Re-install the transparent plastic cover
WARNING
The BDM connector is not galvanically isolated. Therefore, be sure
that the UPS is disconnected from the mains line during
programming.
7.3 Application Control
The UPS can be controlled by the MAINS LINE switch (Figure 7-2) and by the two ON/OFF or BYPASS
buttons. The status of the UPS is indicated by four LEDs and an LED bar graph.
7.3.1 On-line Operation
If the mains line is available and the UPS is set up as is described in 7.1 Hardware Setup, the UPS is in
standby on-line mode. To switch the UPS on, quickly push the ON/OFF button. As soon as the button is
released the UPS goes into run on-line mode. All UPS outputs are active and the UPS supplies the load.
The run on-line mode is indicated by the green status LED. The actual load is indicated by LED bar graph.
Optionally, a bypass can be activated by quickly pushing the BYPASS button. In bypass mode the load
is connected directly to the mains line. The bypass mode is indicated by the yellow LED.
Single Phase On-Line UPS Using MC9S12E128
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Freescale Semiconductor
Application Control
ON/OFF
Button
Status
LEDs
LED Bargraph
Bypass
Button
Figure 7-5. UPS User Interface
In the case of a mains line failure, the UPS automatically goes into run on battery mode. If the UPS is in
bypass mode at the moment of the failure, the UPS is switched off. Run on battery mode is indicated by
the orange LED and the UPS regularly beeps. If the batteries are discharged the UPS switches the
outputs off and goes into standby on battery mode. In this mode the UPS stays for one minute, then
switches itself off.
Then user can switch the UPS by pushing the ON/OFF button for more than four seconds, during this time
the UPS constantly beeps.
7.3.2 Battery Operation
If the mains line is not available, the UPS goes directly into run-on-battery mode after the ON/OFF button
is pressed for less than four seconds and released. The bypass is not available during battery operation.
The UPS can be switched off by the user in the same way as in on-line operation. If the mains line is
restored during battery operation, the UPS goes automatically into the run on-line mode.
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
103
System Set-Up and Operation
7.3.3 Remote Operation
If the UPS is connected to the PC it can be controlled by the FreeMaster software. The FreeMaster’s
control page offers the same interface, so that the UPS can be controlled from in the same way. The
remote control works in parallel with the user interface.
Figure 7-6. UPS Project in FreeMaster
In addition to remote control, the FreeMaster displays the values of some variables. There is also a
recorder and scope showing the output voltage and temperature of the power stage.
Single Phase On-Line UPS Using MC9S12E128
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Freescale Semiconductor
Application Control
Appendix A. Schematics
A.1 Schematics of Power Stage
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
105
5
4
3
1
J101
PSH02_02P
J100
J104
J103
1
2
J102
2
Auxiliary Power Supplies
+VBAT
D
-5V_TOP
GND_TOP
+15V_TOP
-5V_BOT
GND_BOT
+15V_BOT
+VBAT
GND_PFC
+15V_PFC
FUSE AUTO 40A
+5V_A
+5V_D
+15V
/POWER_EN
POWER_EN
3
4
GNDA
GND
F101
1
2
+5V_REF
D
Battery Charger
L
J105
L
N
F102
+5V_A
+5V_A
GNDA
GND
6.3A/fast
GNDA
/POWER_ON
GND
F100
+VBAT
-VBAT
+15V
+5V_D
+5V_A
+15V_TOP
-5V_TOP
-5V_BOT
GND_BOT
+15V_PFC
GNDA
VBAT
IBAT
J106
GND_TOP
+15V_BOT
GND
HV_BAT_LEVEL
IBAT_CONTROL
2A/fast
N
+VBAT
-VBAT
GND_PFC
+5V_REF
-5V_TOP
GND_TOP
+15V_TOP
-5V_BOT
GND_BOT
+15V_BOT
GND_PFC
+15V_PFC
PE MH100
+5V_A
+5V_D
+15V
L1
L2
N
PE
C
GNDA
GND
+5V_REF
PFC+Inverter
C
PE CONNECTION
PWM_TOP
PWM_BOT
J108
FAN_PWM
OUT1
OUT2
N_OUT
DCB_POS
DCB_NEG
AD2
AD3
FAULT0
FAULT1
RLY_IN
RLY_BYPASS
RLY_OUT1
RLY_OUT2
V_DCB_TOP
V_DCB_BOT
V_IN
I_IN
V_OUT_TOP
V_OUT_BOT
I_OUT
TEMP
+5V_D
+5V_A
+15V
PWM10
PWM12
TIM14
TIM15
TIM16
TIM17
DIV1
DIV2
UNI-3 PFC_EN
PFC_ZC
GNDA
GND
+5V_D
+5V_A
+15V
DA0
DA1
GND
J107
Control Board Interface
GNDA
J109
FAN+
FAN-
J110
1
2
AD1
AD4
UNI-3_PWM2
AD5
UNI-3_PWM3
AD6
UNI-3_PWM4
UNI-3 PHAIS UNI-3_PWM5
UNI-3 PHCIS
UNI-3 DCBI UNI-3 PFC_EN
UNI-3 DCBV UNI-3 SERIAL
PSH02_02P
J111
1
2
PSH02_02P
UNI-3 BEMFZCA
UNI-3 BEMFZCC
UNI-3 BEMFZCB
UNI-3 PFC_ZC
DA0
DA1
B
DC-DC Step Up
Fault1
Fault0
B
GNDA
GND
GND
GNDA
+VBAT
-VBAT
+VBAT
-VBAT
DCB_POS
DCB_NEG
PWM4
PWM5
A
A
Motorola MCSL Roznov
1. maje 1009
756 61 Roznov p. R., Czech Republic, Europe
Title
750 VA UPS Power Stage
Pavel Grasblum
Author:
Size
Schematic Name: 00165_01
A3 Design File Name:
Rev
01
Wednesday, October 01, 2003
of
2
10
Modify Date:
Sheet
Copyright Motorola
2003
POPI Status: Motorola General Business
5
4
3
Figure 7-7. Block Schematic
2
1
C201
T1
R201
TP201
+15V_TOP
220
D201
100pF
12
+15V_TOP
LL4448
8z.
1
+15V
11
C204
L201
47nF
330u
R202
R203
510R
1
2
3
4
1
R206
16K
2
+ C206
330uF/35V
COMP
VFB
ISENSE
RT/CT
MMBD914LT1
8
7
6
5
VREF
VCC
OUT
GND
R207
GND
GND
GND
GND
GND
R205
100pF
D205
TP202
+15V_BOT
220
+15V_BOT
LL4448
TR01/MC145
C208
C213
-5V_BOT
R211
TP203
+15V_PFC
220
D208
LL4448
+
GND_PFC
U202
LM2575-5
TP204
+5V_D
4
1
+5V_D
L202
2
470uH
5
R213
100
+5V_D
+15V
+15V
GND
GND
GND
GND
+15V_TOP
GND_TOP
GND_TOP
-5V_TOP
+5V_REF
+5V_D
+15V_TOP
GND
+15V_BOT
GND
-5V_TOP
+15V_BOT
GND_BOT
GND_BOT
U200
LM2575-ADJ
TP200
+15V
4
1
GND
GNDA
680uH
R216
1.8K
C217
220uF/35V
D214
KA3528LSGT
2
GND
L205
3
220uH
+
C219
22u/20V
GNDA
C221
100nF
U203
MC78L05ACP
VIN
VO
2
+15V
GND
GND
GND
GNDA
1
GND
TP207
+5V_A
+5V_A
GND
C200
100nF
GND
TP208
Vref
L200
+5V_REF
220uH
+15V_PFC
+15V_PFC
GND_PFC
+
12
C218
22uF/50V
1u
R214
2.4k
R215
20K
D213
MBRA140
+
-5V_BOT
L204
5
3
GNDA
-5V_BOT
L203
2
GND
+15V
1
POWER_EN
GND
2
+5V_REF
+5V_A
D211
KA3528LSGT
1
+5V_A
C215
220uF/35V
C216
22uF/50V
TP206
GND
R200
510
+
D210
MBRA140
+
2
3
/POWER_EN
Q200
BC846
GND_PFC
1
R212
33k
+15V_PFC
TP213
D209
GND_PFC
BZV55/15V
C214
100uF/16V
+
C220
22u/20V
GNDA
Figure 7-8. Auxiliary Power Supplies
GND
GNDA
GROUND CONNECTION
TP211
GND_BOT
TP212
GND_BOT
D207
-5V_BOT
BZV55/5V1
+ C210
100uF/16V
100pF
+VBAT
D206
BZV55/15V
+ C207
100uF/16V
R210
1.8
GND
TP210
-5V_TOP
-5V_TOP
C205
6
6z.
100pF
C212
100pF
GND
C203
100uF/16V
5
1k
100nF
C211
100pF
S
Q201
NTF3055
GND_TOP
D203
BZV55/5V1
+
7
R204
220
D1
R209
C209
5z.
2
D
G
33
UC3843
R208
N/P
GND
D204
15k
U201
8
8z.
TP209
GND_TOP
D202
BZV55/15V
+ C202
100uF/16V
GND_PFC
5
4
3
2
1
D
D
C302
220uF/450V
+
D302
B250R
D303
P6KE200
C301
+
L
4.7nF
T300
1
L300
13
R302
1M
9
D305
BYV26C
R306
1M
5
+VBAT
R303
24k
D304
-
6
1N4148
TR02/MC145
C303
220uF/50V
100nF
220uF/50V
100u/50
+
+
C304
R305
1k8
+
R309
2k4
GND_TR
2
L
F
C
1
4
ISO300
SFH615A-2
4
X
GND_CH
1
R329
1K
R313
27R
5 3
3
IBAT1
+
VBAT
R310
5K6
C315
100n
C
Q301
MMBF0201NLT1
GND
IBAT2
GNDA
2
C307
47uF/10V
5.05V @ 39V
-VBAT
R314
HV_BAT_LEVEL
100
C316
100n
R315
7.5k
R307
620
S
47uH
CONTROL
TOP249Y
R300
0.1
L301
sense
7
sense
U300
R312
200
G
D300
1N4148
C
R304
39k
C306
C305
D
R311
33k
29.4V @ Q4 ON
27.4V @ Q4 OFF
47uH
LINE_OK
R301
68k
7
N
TP300
Vbat
D301
BYW29E-200
R308
3K6
R331
100
5
R321
1k6
7
C300
3
+
2
-
GND_CH
R318
1
100k
U301A
MC33502
100K
220n
Q300
B
8
BC847
U302
TL431ACD
GND
C314
N/P
R323
1k
GND_CH
R325
33K
470nF
GND
R324
1k
IBAT_CONTROL
C311
C310
4.875V @ 2.34A
GND
1
8
R320
R322
220
D309
5V1
100nF
C308
4
6
IBAT2
MC33502
U301B
+
IBAT1
+5V_A
C309
470nF
R319
1k6
-
B
R317
33K
6
R316
220
470nF
GND
IBAT
GND
+5V_A
+5V_A
LINE_OK
GND
A
R327
560
GND
C312
D307
10nF/100V
BAV103
100nF/100V
GNDA
GND_TR
/POWER_ON
68K
C313
D308
BAV103
GNDA
R328
D
R330
10k
A
G
Q302 S
MMBF0201NLT1
Motorola MCSL Roznov
1. maje 1009
756 61 Roznov p. R., Czech Republic, Europe
Title
GND
750 VA UPS Power Stage
Author:
Pavel Grasblum
Size
Schematic Name: Battery Charger
A3 Design File Name:
Modify Date:
Thursday, August 19, 2004
Copyright Motorola
2003
5
4
3
Figure 7-9. Battery Charger
2
Rev
01
Sheet
4
10
of
POPI Status: Motorola General Business
1
5
4
3
2
GND
J401
GND
D
1
1
3
5
7
9
11
13
15
17
19
21
23
25
27
29
31
33
35
37
39
GNDA
UNI-3_PWM2
UNI-3_PWM3
UNI-3_PWM4
UNI-3_PWM5
GND
+5V_D
GNDA
+15V
UNI-3 DCBV
UNI-3 PHAIS
UNI-3 PHCIS
GNDA
+5V_A
+5V_A
+5V_D
+5V_D
+15V
+15V
UNI-3 PFC_ZC
UNI-3 BEMFZCB
GNDA
C
J402
GND
2
4
6
8
10
1
3
5
7
9
2
4
6
8
10
12
14
16
18
20
22
24
26
28
30
32
34
36
38
40
D
GND
+5V_D
GNDA
UNI-3 DCBI
GNDA
UNI-3 SERIAL
UNI-3 PFC_EN
UNI-3 BEMFZCA
UNI-3 BEMFZCC
C
UNI-3
Fault0
Fault1
J400
+5V
FAULTS HEADER
AD1
AD3
AD5
DA1
GNDA
2
4
6
8
10
12
14
1
3
5
7
9
11
13
AD2
AD4
AD6
DA0
+5V_A
B
B
ADC and DAC HEADER
J403
A
GND
2
4
6
8
10
12
14
16
18
20
22
24
26
1
3
5
7
9
11
13
15
17
19
21
23
25
PWM10
PWM12
TIM14
TIM15
TIM16
TIM17
+5V
PWM and Timer HEADER
Title
Motorola MCSL Roznov
1. maje 1009
756 61 Roznov p. R., Czech Republic, Europe
750 VA UPS Power Stage
Author:
Pavel Grasblum
Size
Schematic Name: Control Board Interface
A
Design File Name:
Rev
01
of
5
10
Modify Date:
Sheet
Wednesday, October 01, 2003
Copyright Motorola
POPI Status: Motorola General Business
2003
5
4
3
Figure 7-10. Control Board Interface
2
1
A
L501
+Bat
MUR180
1
1
2
FFPF05U120STU
D500
680u/50V
1
D504
D505
10
L503
330u
OutA
GND_BAT
8
7
1
R505
2
10
5
1
L500
330u
1
2
R506
47uF
C510
C508
1n
1
1
GND_BAT
GND_BAT
Q501 Q500
NTP45N06 NTP45N06
D
D
G
G
S
Q502 Q503
NTP45N06 NTP45N06
D
D
G
S
G1
S
2
R500
U501
8 NC
MC33152D
VCC
NC
1
2
7 OutA
InA
2
2
5 OutB
InB
4
TP502
PWM_5
10
S
1
R507
GND_BAT
GND_BAT
GND_BAT
GND_BAT
TP503
GND_BAT
TP500 TP504
GND GNDA
GND_BAT
GND
GND
GND
GNDA
GNDA
Figure 7-11. dc/dc Step-Up Converter
2
GND
GND_BAT
PWM5
R509
10k
10
GND
GNDA
2
100n
C500
GND_BAT
10
2
R508
10k
OutB
4 InB
3
1
PWM4
1
R503
100R/1W
C507
1n
6
2 InA
T500
TR03/MC145
9
1
1
GND_BAT
MC33152D
VCC
NC
DCB_POS
+15V
2
GND_BAT
100n
C511
+OUT
650u/1A
2
+
2
C506
22n/400V
18
4
6
100R/1W
R504
2
2
D503 L502
FFPF05U120STU
1
47uF
C509
1
GND
13
15
FFPF05U120STU
+15V
TP501
PWM_4
2
MUR180
GND_BAT
U500
1 NC
1
FFPF05U120STU
D502
2
R502
1k/5W
+
2
2
2
680u/50V
680u/50V
2
R501
1k/5W
DCB_NEG
C501
22n/400V
3
-VBAT
2
2
C502 + C503 + C504 + C505 + C512 + C513 +
-OUT
6
1
680u/50V
1
1
1
+VBAT
1
680u/50V 680u/50V
650u/1A
D501
1
5
4
3
+5V_REF
TP610
2
I_OUT1
R614
I_IN
130R
I_IN
R679
180
C612
10n
D619
MBR0540
6
-
1
U604B
MC33502D
R617
100k
D617
BZV55/5V1
2
2
3
R600
10
I_OUT
MC33502D
U604A
100n
GNDA
+ C614
22uF
GNDA
V_INP
D
C613
2
GNDA
TP600
I_OUT
1
1
D618
MBR0540
R678
180
7
GNDA
DCB_POS
+5V_A
GNDA
+5V_REF
D600
1N4007
+5V_REF
C616
100n
R619
300k
R620
11k
R618
330k
TP601
-DCB_DIV
GNDA
V_DCB_BOT_DIV
R625
300k
R622
470k
C
R631
130k
V_DCB_TOP_DIV
V_IN
R636
33K
TP603
+DCB_DIV
1
R632
2
2
TP602
R621
V_OUT_NEG
11k
R630
300k
V_DCB_TOP
V_OUT_BOT
R672
11K
GNDA
GNDA
C
GNDA
R634
300k
C620
33n
2
0R
D620
BZV55/3V6
R627
330k
C617
33n
R624
1
V_DCB_BOT
R629
300k
1K
R633
11k
+ C619
10uF/10V
R623
1K
R626
330k
R628
330k
TP604
V_IN
1
1
R616
180
I_IN2
+
2
D
D616
BZV55/5V1
5
GNDA
8
I_IN1
+
D615
MBR0540
4
R615
100k
-
D614
MBR0540
1
I_OUT2
R635
300k
V_OUT
R637
GNDA
GNDA
680k
DCB_NEG
GNDA
R638
300k
+5V_D
GNDA
+5V_D
R641
V_DCB_TOP_DIV
R642
10k
10k
3
C600
V_INP
R647
R648
330k
330k
330k
D622
BAT42
D623
BAT42
C621
15n
10
-
11
+
U606D
V+
V-
13
TP606
+
6
-
PFC_ZC
2
V_OUT_TOP
1K
D621
BAT42
B
3
C622
33n
GNDA
1
R651
680k
2
GND
1K
1
C625
33n
R680
33
C634
R653
100n
10K
+15V
+5V_D
C623
100n
TP609
REF_NEG
2
R655
1
10k
GNDA
3
+
2
-
4
GNDA
+5V_D
+15V
+5V_REF
+5V_REF
TEMP
8
+Vout
R652
+5V_A
+5V_D
3
2 1
+5V_A
+5V_A
TP608
TEMP
Q600
LM35CA
GNDA
GNDA
2
GNDA
+5V_REF
GNDA
R645
1
R649
11k
TP607
REF_POS
10K
+Vs
TP605
V_OUT_POS
GNDA
R650
C624
100n
R643
330k
+5V_REF
GNDA
3
FAULT1
PFC_ZC
LM339M
+5V_A
7
U605B
LM393D
100n
12
B
R646
R644
10k
R639
300k
R640
10k
5
A
GNDA
1
GND
R654
10k
GND
GNDA
FAULT0
U605A
LM393D
GNDA
A
GNDA
V_DCB_BOT_DIV
R656
10k
C626
100n
GNDA
Title
4
3
Figure 7-12. Analog Sensing Circuits
750 VA UPS Power Stage
Pavel Grasblum
Author:
Size
Schematic Name:
A3 Design File Name:
GNDA
5
Motorola MCSL Roznov
1. maje 1009
756 61 Roznov p. R., Czech Republic, Europe
2
Rev
01
Analog_Sensing
Modify Date:
Monday, March 08, 2004
2003
Copyright Motorola
Sheet
7
10
of
Motorola General Business
POPI Status:
1
5
4
3
D
U601
PWM_PFC
GND
2
1
D
+15V_PFC
1
8
2
7
3
6
4
5
+15V_TOP
D609
C609
100nF
R606
MBR0540
R607
GATE_PFC
10
D628
15V
100
GND_TOP
GND_TOP
-5V_TOP
GND_PFC
HCPL3150
+15V_TOP
-5V_TOP
+15V_BOT
+15V_BOT
GND_PFC
GND_BOT
GATE_TOP
+15V_TOP
D611
C
D610
BAT42
PWM_TOP
C610
100nF
R608
330
R609
MBR0540
R610
33
1
2
3
BAT42
R611
6
7
8
330
U615
N/C
VCC1
ANODE1
VO1
CATHODE1 VEE1
16
15
14
ANODE2
VCC2
CATHODE2 VO2
N/C
VEE2
11
10
9
-5V_BOT
-5V_BOT
+15V_PFC
D625
5V
100
D613
PWM_BOT
D624
15V
GND_BOT
GND_PFC
GND_PFC
GND_TOP
C632
100nF
C
+15V_PFC
GND_TOP
GND
GND
-5V_TOP
GATE_BOT
+15V_BOT
HCPL-315J
D612
B
C611
100nF
GND
D626
15V
R612
MBR0540
R613
B
33
D627
5V
100
C633
100nF
GND_BOT
GND_BOT
-5V_BOT
Motorola MCSL Roznov
1. maje 1009
756 61 Roznov p. R., Czech Republic, Europe
A
Title
750 VA UPS Power Stage
Author:
Pavel Grasblum
Size Schematic Name:
IGBT_Drives
Design File Name:
Modify Date: Monday, March 08, 2004
Sheet
of
8
10
Copyright Motorola
POPI Status: Motorola General Business
2003
A4
5
4
3
Figure 7-13. PFC and Inverter IGBT Drivers
2
1
Rev
01
A
5
4
3
2
1
RE1
MZPA001
5 o
MBRS130
+15V
D601
L504
D
D
R601
FAN_PWM
D1
+ C601
10u/15V
3 o
FAN-
+15V
1
2
RE2
MZPA001
330u
D
D602
5 o
G
68
S
OUT1
o 4
FAN+
o 4
Q601
NTF3055
L2
GND
BAT42
3 o
+15V
R602
RLY_OUT1
1
Q602
BC846
4K7
2
GND
I_IN1
RE3
MZPA001
D603
I_IN2
7
9
BAT42
RLY_BYPASS
CT1
1:100
1
L505
+15V
3 o
GND
D604
2.5mH
+15V
1
-
BAT42
+
5
7
o
o
o
4
6
8
2
o
C602
+
C603
Q606
IRG4IBC20W
MKP10/22nF/630VDC
330uF/450V
GND
HGTG10N120BND
V_OUT
L506
GND_TOP
6mH
GATE_PFC
R605
Q607
BC846
4K7
GND_PFC
C605
2
3.3uF/400V
4
1
2
GND
N
RLY_IN
4K7
Q605
GATE_TOP
Q604
BC846
GND
L507
TL34P
C604
1
3
PE
4.7nF/Y1
C606
4.7nF/Y1
N_OUT
3
4
3
o
1
o
RE4
MZPA002
C
R604
RLY_OUT2
D607
BAT42
2
D605
RHRP8120
D606
KBPC606
C
DCB_POS
OUT2
o 4
Q603
BC846
4K7
2
V_INP
L1
DCB_POS
5 o
R603
CT2
GND
B
B
5
I_OUT2
I_OUT1
Q608
C607
+
MKP10/22nF/630VDC
8
CS2106
GATE_BOT
C608
330uF/450V
HGTG10N120BND
GND_BOT
D608
+15V
+15V
RHRP8120
GND
DCB_NEG
DCB_NEG
GND
A
A
Title
Motorola MCSL Roznov
1. maje 1009
756 61 Roznov p. R., Czech Republic, Europe
750 VA UPS Power Stage
Pavel Grasblum
Author:
Size
Schematic Name:
A3 Design File Name:
5
4
3
Figure 7-14. PFC and Inverter
2
Rev
01
Inverter
Modify Date:
Monday, March 08, 2004
2003
Copyright Motorola
9
10
Sheet
of
Motorola General Business
POPI Status:
1
5
4
3
2
1
+5V_A
+5V_A
R657
33
100n
GNDA
3
R663
100
DA1
4
-
5
+
R658
10k
U606A
V+
V-
R660
R659
10k
10k
R665
N/P
12
R664
1.6k
GNDA
GNDA
C
+
V+
V-
GND
G
1
Q609 S
MMBF0201NLT1
12
R667
0
I_IN
7
D
U606B
3
N/P
C630
N/P
R668
100
-
LM339M
R666
DA0
6
D
C628
100n
R661
470
R662
470
2
LM339M
C629
10n
+5V_D
3
D
+5V_D
C627
8
-
9
+
C631
10n
U606C
V+
V-
R669
10k
14
R670
10k
TP611
PFC_CTRL
LM339M
GND
PWM_PFC
C
12
+5V_D
GNDA
GNDA
MMBF0201NLT1
60%
3.3K
MMBF0201NLT1
75%
10k
85%
9.1k
GNDA
R671
4.7k
D
G
UNI-3 PFC_EN
Q610 S
MMBF0201NLT1
R673
N/P
R674
N/P
R675
N/P
GND
B
B
D
All On 55%
G
DIV1
Q611
N/P
D
G
DIV2
Q612
N/P
S
GNDA
S
GNDA
GNDA
Motorola MCSL Roznov
1. maje 1009
756 61 Roznov p. R., Czech Republic, Europe
A
Title
750 VA UPS Power Stage
Author:
Ivan Feno
Size Schematic Name:
PFC_Control
Design File Name:
Modify Date: Monday, March 08, 2004
Sheet
of
10
10
Copyright Motorola
POPI Status: Motorola General Business
2003
A4
5
4
3
Figure 7-15. PFC Current Control Circuit
2
1
Rev
01
A
Application Control
A.2 Schematics of User Interface
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
115
5
4
3
2
1
+5V_D
LED_FAULT
SW1
R1
1300
R2
10k
D1
L53LID
BT_BYPASS
D
D
J1
LED_LEV5
LED_LEV3
LED_LEV1
BT_BYPASS
LED_BAT
LED_FAULT
GND
2
4
6
8
10
12
14
16
18
20
22
24
26
1
3
5
7
9
11
13
15
17
19
21
23
25
GND
BEEP
LED_LEV6
LED_LEV4
LED_LEV2
Switch/P-0SYB
+5V_D
BT_ON/OFF
LED_BYPASS
LED_ON
J3
1
3
5
7
9
R4
10k
SW2
+5V_D
5
9
4
8
3
7
2
6
1
2
4
6
8
10
BT_ON/OFF
HEADER 5X2
HEADER 13x2
LED_ON
J2
R3
1300
D2
L53LGD
GND
LED_BAT
CON/CANNON9
R5
270
D3
L53ND
C
GND
2
1
Switch/P-0SEB
R6
LED_LEV1
R9
LED_LEV3
R10
LED_LEV4
R11
LED_LEV5
B
LED_LEV6
R12
GND
LED_BYPASS
J4
PSH02_02W
1300
R8
LED_LEV2
J6
1300
R7
1300
1300
1
3
5
7
9
1300
5
9
4
8
3
7
2
6
1
2
4
6
8
10
1300
HEADER 5X2
D4
L53LYD
J5
GND
BEEP
BZ1
CON/CANNON9
1300
D5
L53LID
D6
L53LGD
C
D7
L53LGD
D8
L53LGD
D9
L53LGD
B
SA003
D10
L53LID
GND
+5V_D
+5V_D
GND
GND
GND
GND
GND
GND
GND
GND
Motorola MCSL Roznov
1. maje 1009
756 61 Roznov p. R., Czech Republic, Europe
A
Title
UPS 750 VA User Interface
Author:
Pavel Grasblum
Size Schematic Name: 00165B01
A4 Design File Name:
Rev
01
Modify Date: Wednesday, September 10, 2003
Sheet
of
1
1
Copyright Motorola
POPI Status: Motorola General Business
2003
5
4
3
Figure 7-16. UPS User Interface
2
1
A
Application Control
A.3 Schematics of Input Filter
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
117
5
4
3
2
1
D
C
D
L
R103
330k
N
SIOV-S20K275
4.7nF/Y1
J100
J101
C100
C100B
100nF/X1 1uF/X1
4
2
TL34P
L100
3
1
C101
R100
C102
R101
L_OUT
J104
N_OUT
MH1
PE
C
R102
SIOV-S20K275
100nF/X1
J103
SG-190
C103
4.7nF/Y1
PE
J102
GROUND CONNECTION
B
MH2
B
GROUND CONNECTION
A
Title
Motorola MCSL Roznov
1. maje 1009
756 61 Roznov p. R., Czech Republic, Europe
750 VA UPS Input Filter
Author:
Pavel Grasblum
Size
Schematic Name: 00165C01
A
Design File Name:
5
4
3
Rev
01
2
2
of
Modify Date:
Sheet
Monday, September 15, 2003
Copyright Motorola
POPI Status: Motorola General Business
2003
2
1
A
Application Control
A.4 Parts List of UPS Power Stage
Table A-1. Parts List of UPS Power Stage (Sheet 1 of 5)
Reference
Qty
Description
Manufacturer
Part number
CT1
1
current transformer — custom
design
CT2
1
current transformer
COILCRAFT
C200, C209, C221, C303, C308, C610,
C611, C632, C633
9
100-nF ceramic SMD 0805
any available
C201, C205, C208, C211, C212, C213
6
100-pF ceramic SMD 0805
any available
C202, C203, C207, C210, C214
5
100-µF/16-V radial electrolytic
5 x 11 mm
any available
C204
1
47-nF ceramic SMD 0805
any available
C206
1
330-µF/35-V radial electrolytic
10 x 20 mm
any available
C215, C217
2
220-µF/35-V radial electrolytic
10 x 20 mm
any available
C216, C218
2
22-µF/50-V 5 x 11 mm
any available
C219, C220
2
22-µ/20-V tantalum size D
any available
C300
1
220n ceramic SMD 0805
any available
C301
1
4.7-nF polyester
Vishay
MKT1820
C302
1
220-µF/450-V electrolytic
EPCOS
B43504
C304, C305
2
220-µF/50-V electrolytic
Rubycon
ZL series
C306
1
100-µ/50-V electrolytic
Jamicon
C307
1
47-µF/10-V electrolytic
Jamicon
C309, C310, C311
3
470-nF ceramic SMD 0805
any available
C312
1
10-nF/100-V ceramic
any available
C313
1
100-nF/100-V ceramic
any available
R208, C314, C630, R665, R666, R673,
R674, R675
8
no populated
-
C315, C316, C600, C613, C616, C623,
C624, C626, C627, C628, C634
11
100n ceramic SMD 0805
any available
C500, C511
2
100n ceramic SMD 1206
any available
C501, C506
2
22n/400-V metallized
WIMA
MKP10
C502, C503, C504, C505, C512, C513
6
680µ/50-V
Rubycon
ZL series
C507, C508
2
1n/100-V
WIMA
MKS 2
C509, C510
2
47-µF/25-V radial electrolytic
5 x 11 mm
any available
C601
1
10-µ/15-V tantalum size D
any available
TRONIC
3044202
CS2106
C602, C608
2
330-µF/450-V electrolytic
EPCOS
B43504
C603, C607
2
22-nF/630-Vdc
WIMA
MKP10
C604, C606
2
4.7-nF/Y1
any available
C605
1
3.3-µF/400-V
WIMA
C609
1
100-nF ceramic SMD 1206
any available
C612, C629, C631
3
10n ceramic SMD 0805
any available
C614
1
22-µF/16-V radial electrolytic
5 x 11 mm
any available
MKP10
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
119
System Set-Up and Operation
Table A-1. Parts List of UPS Power Stage (Sheet 2 of 5)
Reference
Qty
Description
Manufacturer
Part number
C617, C620, C622, C625
4
33n ceramic SMD 0805
any available
C619
1
10-µF/25-V radial electrolytic
5 x 11 mm
any available
C621
1
15n ceramic SMD 0805
any available
D201,D205,D208, D304
4
LL4448 signal diode
Fairchild
LL4448
D202,D206,D209
3
zener diode 15-V
Philips
BZV55/15V
D203,D207,D616,D617
4
zener diode 5.1-V
Philips
BZV55/5V1
D204
1
high-speed switching diode
ON Semiconductor
MMBD914LT1
D210,D213
2
schottky diode
ON Semiconductor
MBRA140
D211,D214
2
LED diode SMD green
Kingbright
KA3528SGT
D300
1
high-speed diode
Philips
1N4148
D301
1
ultra fast diode
Vishay
BYW29E-200
bridge rectifier
Diotec
Semiconductor
B250R
D302
1
D303
1
transient voltage suppressor
Vishay
P6KE200
D305
1
ultra fast diode
Vishay
BYV26C
D307,D308
2
general purpose diode
Philips
BAV103
D309
1
zener diode 5V1
Philips
BZV55/5V1
D500,D502,D504,D505
4
fast recovery diode
Fairchild
FFPF05U120STU
D501,D503
2
ultra fast diode
ON Semiconductor
MUR180
D600
1
diode
Philips
1N4007
D601
1
schottky diode
ON Semiconductor
MBRS130
D602,D603,D605,D607,D611,D613,D62
9
1,D622,D623
schottky diode
Philips
BAT42
D604,D608
hyperfast diode
Fairchild
RHRP8120
1
bridge rectifier
Diotec
Semiconductor
KBPC606
D609,D610,D612,D614,D615,D618,D61
7
9
schottky diode
ON Semiconductor
MBR0540
D620
1
zener diode 3V6
Philips
BZV55/3V6
D624,D626,D628
3
zener diode 15 V
Philips
BZV55/15V
BZV55/5V1
D606
2
D625,D627
2
zener diode 5.1 V
Philips
F100
1
fast fuse 2 A
any available
F101
1
car fuse 40 A
any available
F102
1
fast fuse 6.3 A
any available
ISO300
1
optocupler
Vishay
SFH615A-2
PSH02_02P
J100,J102,J103,J104,J105,J106,J107,J
9
108,J109
FASTON
J101,J110,J111
3
connector
EZK (distributor)
J400
1
header 7 x 2
any available
J401
1
connector
EZK (distributor)
J402
1
header 5 x 2
any available
J403
1
header 13 x 2
any available
L200,L205
2
220-µH axial inductor 130 mA
FASTRON
PFL_20X2
Single Phase On-Line UPS Using MC9S12E128
120
Freescale Semiconductor
Application Control
Table A-1. Parts List of UPS Power Stage (Sheet 3 of 5)
Reference
Qty
Description
Manufacturer
Part number
L201,L500,L503,L504
4
330µ radial inductor 500 mA
FASTRON
L202
1
470 µH
FASTRON
09P/F-471k
L203
1
680 µH
FASTRON
09P/F-681k
L204
1
1-µ axial inductor 1.2 A
FASTRON
L300,L301
2
radial inductor 47 µH
Coilcraft
PCV-1-473-03
L501, L502
2
560µ / 1 A
Coilcraft
PCV-2-564-02
L505
1
2.5 mH
custom design
see 4.5.2.1
L506
1
5 mH
custom design
see 4.5.4.2
L507
1
toroid choke
Tesla Blatna
TL34P
Q200, Q602, Q603, Q604, Q607
5
general-purpose bipolar transistor
ON Semiconductor
BC846
Q201, Q601
2
Power MOSFET transistor
ON Semiconductor
NTF3055
Q300
1
general-purpose bipolar transistor
ON Semiconductor
BC847
Q301, Q302, Q609, Q610
4
Power MOSFET transistor
ON Semiconductor
MMBF0201NLT1
Q500, Q501, Q502, Q503
4
Power MOSFET transistor
ON Semiconductor
NTP45N06
LM35CA
Q600
1
temperature sensor
National
Semiconductor
Q605, Q608
2
IGBT
Fairchild
HGTG10N120BND
Q606
1
IGBT
International
Rectifier
IRG4IBC20W
Q611, Q612
2
no populated
RE1, RE2, RE3
3
relay
CARLO GAVAZZI
MZPA001
RE4
1
relay
CARLO GAVAZZI
MZPA002
R200, R203
2
510 SMD 0805
any available
R201, R204, R205, R211, R316, R322
6
220 SMD 0805
any available
R202
1
15k SMD 0805
any available
R206
1
16k SMD 0805
any available
R207, R657, R680
3
33 SMD 0805
any available
R209, R323, R324, R329, R623, R632,
R645, R652
8
1k SMD 0805
any available
R210
1
1.8 SMD 0805
any available
R212, R317, R325
3
33k SMD 0805
any available
R213, R314, R331, R663, R668
5
100 SMD 0805
any available
R214
1
2.4k SMD 0805
any available
R215
1
20k SMD 0805
any available
R216
1
1.8k SMD 0805
any available
R300
1
precision shunt resistor
Isabellenhütte
Heusler GmbH KG
R301
1
68k, 2W
any available
R302, R306
2
1M size 0207
any available
R303
1
24k SMD 0805
any available
R304
1
39k SMD 0805
any available
R305
1
1k8 SMD 0805
any available
R307
1
620 SMD 0805
any available
R308
1
3K6 SMD 0805
any available
PMA-C - R100 - 1
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
121
System Set-Up and Operation
Table A-1. Parts List of UPS Power Stage (Sheet 4 of 5)
Reference
Qty
Description
Manufacturer
R309
1
2k4 SMD 0805
R310
1
5K6 SMD 0805
any available
R311, R636
2
33k, size 0207
any available
Part number
any available
R312
1
200 SMD 0805
any available
R313
1
27R SMD 0805
any available
R315
1
7.5k SMD 0805
any available
R318, R320, R615, R617
4
100k SMD 0805
any available
R319, R321
2
1k6 SMD 0805
any available
R326
1
3k9 SMD 0805
any available
R327
1
560 SMD 0805
any available
R328
1
68k SMD 0805
any available
R330, R508, R509, R640, R641, R642,
R644, R654, R655, R656, R658, R659,
R660, R669, R670
15
10k SMD 0805
any available
R500, R505, R506, R507, R606
5
10 SMD 1206
any available
R501, R502
2
1-k/5-W
any available
R503, R504
2
100R/1W
any available
R600
1
10 SMD 0805
any available
R601
1
68 SMD 0805
any available
R602, R603, R604, R605
4
4K7 SMD 0805
any available
R607, R610, R613
3
100 SMD 1206
any available
R608, R611
2
330 SMD 0805
any available
R609, R612
2
33 SMD 1206
any available
R614
1
130RSMD 0805
any available
R616, R678, R679
3
180 SMD 1206
any available
R618, R626, R627, R628, R643, R646,
R647, R648
8
330k size 0207
any available
R619, R625, R629, R630, R634, R635,
R638, R639
8
300k size 0207
any available
R620, R621, R633, R649, R672
5
11k SMD 0805
any available
R622
1
470k size 0207
any available
R624, R667
2
0R SMD 0805
any available
R631
1
130k size 0207
any available
R637, R651
2
680k SMD 0805
any available
R650, R653
2
10k SMD 4315
any available
R661, R662
2
470 SMD 0805
any available
R664
1
1.6k SMD 0805
any available
R671
1
4.7k SMD 0805
any available
T1
1
transformer
customer design
see 4.3.1
T300
1
transformer
customer design
see 4.2.4
T500
1
transformer
customer design
see 4.4.2.1
U200
1
switching regulator
ON Semiconductor
LM2575-ADJ
U201
1
switching regulator
ON Semiconductor
UC3843
U202
1
switching regulator
ON Semiconductor
LM2575-5
Single Phase On-Line UPS Using MC9S12E128
122
Freescale Semiconductor
Application Control
Table A-1. Parts List of UPS Power Stage (Sheet 5 of 5)
Reference
Qty
Description
Manufacturer
Part number
U203
1
linear regulator
ON Semiconductor
MC78L05ACP
U300
1
switching regulator
Power Integrations
TOP249Y
U301, U604
1
operational amplifier
ON Semiconductor
MC33502
U302
1
voltage reference
Fairchild
TL431ACD
U500,U501
2
MOSFET driver
ON Semiconductor
MC33152D
U601
1
opto driver
Agilent
HCPL3150
U605
1
dual comparators
ON Semiconductor
LM393D
U606
1
quad comparators
ON Semiconductor
LM339M
U615
1
opto driver
Agilent
HCPL-315J
A.5 Parts List of User Interface
Table A-2. Parts List of User Interface
Reference
Qty
Description
buzzer
Manufacturer
EZK (distributor)
Part number
BZ1
1
SA003
D1, D10
3
LED diode red
Kingbright
L53LID
D2,D5,D6,D7,D8,D9
6
LED diode green
Kingbright
L53LGD
D3
1
LED diode orange
Kingbright
L53ND
D4
1
LED diode yellow
Kingbright
L53LYD
J1
1
header 13 x 2
any available
J2,J5
2
connector CANNON 9 pin
any available
J3,J6
2
header 5 x 2
any available
J4
1
connector
any available
R1, R3, R6, R7, R8, R9, R10, R11, R12 9
1300 SMD 0805
any available
R2, R4
2
10k SMD 0805
any available
R5
1
270 SMD 0805
any available
SW1
1
Switch
MEC
switch 15501
extender 16250
cap 1D06
SW2
1
Switch
MEC
switch 15501
extender 16250
cap 1D02
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
123
System Set-Up and Operation
A.6 Parts List of Input Filter
Table A-3. Parts List of Input Filter
Reference
C100B
Qty
1
Description
1−µF / X1
Manufacturer
EPCOS
Part number
B81133
C100, C101
2
100-nF / X1
EPCOS
B81133
C102, C103
2
4.7-nF / Y1
MURATA
DE2E3KH472MA3B
J100,J101,J102,J103,J104
5
faston 6.3 mm
any available
L100
1
toroid choke
Tesla Blatna
TL34P
R100
1
inrush current limiter
Rhopoint
Components
SG-190
R101, R102
2
EPCOS
SIOV-S20K275
R103
1
330k, 0.6 W
any available
Single Phase On-Line UPS Using MC9S12E128
124
Freescale Semiconductor
Application Control
Appendix B. References
1.
2.
3.
4.
5.
6.
7.
8.
9.
10.
11.
12.
13.
14.
15.
16.
17.
18.
19.
20.
21.
22.
23.
24.
25.
26.
27.
28.
29.
30.
31.
32.
33.
Feno, I.: Analysis and Synthesis of the IGBT switching techniques and verification in Partial Series
Resonant Converter. Ph.D. Dissertation, University of Zilina, Faculty of Electrical Engineering,
August 2003.
A More Realistic Characterization Of Power MOSFET Output Capacitance Coss. Application Note
AN-1001, International Rectifier.
Billings, K.: Switchmode Power Supply Handbook, second edition. McGraw-Hill, 1999.
Pressman, A. I.: Switching Power Supply Design, second edition, McGraw-Hill, 1998.
International Standard IEC62040-1-1, Uninterruptable power systems (UPS) - Part 1-2: General
and safety requirements for UPS used in operator access areas.
International Standard IEC62040-1-2, Uninterruptable power systems (UPS) - Part 1-2: General
and safety requirements for UPS used in restricted access locations.
International Standard IEC62040-2, Uninterruptable power systems (UPS) - Part 2:
Electromagnetic compatibility (EMC) requirements.
International Standard IEC62040-3, Uninterruptable power systems (UPS) - Part 3: Method of
specifying the performance and test requirements.
YUASA NP valve regulated lead acid battery manual. Yuasa Battery GMBH, 1999.
TOP242-250 Up to 290 W Extended power, design flexible, EcoSmart, integrated off-line switcher
family, data sheet. Power Integrations, August 2003
AN-18, TOPSwitch Flyback Transformer Construction Guide. Power Integrations, 1996.
AN-16, TOPSwitch Flyback Design Methodology. Power Integrations, 1996.
MC9S12E-Family Device User Guide, data sheet. Motorola, 2003.
HCS12 CPU V2.0 Reference Manual, Reference Manual. Motorola, 2003.
HCS12 10-Bit, 16-Channel Analog to Digital Converter (ATD) Block Guide. Reference Manual.
Motorola, 2003.
HCS12 Background Debug Module Block Guide. Reference Manual. Motorola, 2003.
HCS12 Clocks and Reset Generator (CRG) Block Guide. Reference Manual. Motorola, 2003.
Digital-to-Analog Converter: 8-Bit, 1-Channel. Reference Manual. Motorola, 2003.
Debug Module. Reference Manual. Motorola, 2003.
Port Integration Module: 9S12E128. Reference Manual. Motorola, 2003.
HCS12 128K FLASH Block Guide. Reference Manual. Motorola, 2003.
HCS12 Inter-Integrated Circuit (IIC) Block Guide. Reference Manual. Motorola, 2003.
Interrupt (INT) Module V1 Block User Guide. Reference Manual. Motorola, 2003.
Multiplexed External Bus Interface (MEBI) Module V3 Block User Guide. Reference Manual.
Motorola, 2003.
Module Mapping Control (MMC) V4 Block User Guide. Reference Manual. Motorola, 2003.
HCS12 Oscillator Block Guide. Reference Manual. Motorola, 2003.
Pulse Modulator with Fault Protection: 15-Bit, 6-Channel. Reference Manual. Motorola, 2003.
HCS12 8-Bit, 6-Channel Pulse Width Modulator (PWM) Block Guide. Reference Manual. Motorola,
2003.
HCS12 Serial Communications Interface (SCI) Block Guide. Reference Manual. Motorola, 2003.
HCS12 Serial Peripheral Interface (SPI) Block Guide. Reference Manual. Motorola, 2003.
Timer: 16-Bit, 4-Channel. Reference Manual. Motorola, 2003.
Voltage Regulator 3V3 Block User Guide V2. Reference Manual. Motorola, 2003.
MC9S12E128 Controller Board, Design Reference Manual, Motorola 2004
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
125
System Set-Up and Operation
Single Phase On-Line UPS Using MC9S12E128
126
Freescale Semiconductor
Application Control
Appendix C. Glossary
ac
alternating current
ac/dc converter
a converter that converts alternating voltage (ac) to direct voltage (dc)
ATD
analog-to-digital converter
A/D
analog-to-digital
AVR
automatic voltage regulation
CW
CodeWarrior; compilers produced by Metrowerks
DAC
digital-to-analog converter
dc
direct current
dc/ac converter
a converter that converts direct voltage (dc) to alternating voltage (ac)
dc/dc converter
converter that converts one level of direct voltage to another level of direct voltage
DT
dead time; a short time that must be inserted between turning off one transistor in the
inverter half-bridge and turning on the complementary transistor, to allow for the
limited switching speed of the transistors.
duty cycle
the ratio of the time the signal is on to the time it is off. Duty cycle is usually quoted
as a percentage.
EMC
electro magnetic compatibility
EMI
electro magnetic interference
IC
integrated circuit
IDE
integrated development environment
IGBT
Insulated gate bipolar transistor
input/output (I/O)
input/output interfaces between a computer system and the external world. A CPU
reads an input to sense the level of an external signal and writes to an output to
change the level on an external signal.
interrupt
a temporary break in the sequential execution of a program to respond to signals
from peripheral devices by executing a subroutine.
logic 1
a voltage level approximately equal to the input power voltage (VDD)
logic 0
a voltage level approximately equal to the ground voltage (VSS)
HCS12
a Freescale Semiconductor family of 16-bit MCUs
MCU
microcontroller unit; a complete computer system, including a CPU, memory, a clock
oscillator, and input/output (I/O) on a single integrated circuit
Single Phase On-Line UPS Using MC9S12E128
Freescale Semiconductor
127
System Set-Up and Operation
MW
Metrowerks Corporation
PC
personal computer
PCB
printed circuit board
PCM
PC master software for communication between PC and system
PFC
power factor correction
PI Controller
proportional-integral controller
PID Controller
proportional-integral-derivative controller
PLL
phase-locked loop; a clock generator circuit in which a voltage controlled oscillator
produces an oscillation that is synchronized to a reference signal
PMP
FreeMaster software project file
PVAL
PWM value register of motor control PWM module of the MC9S12E128
microcontroller; it defines the duty cycle of the generated PWM signal.
PWM
pulse width modulation
RESET
to force a device to a known condition
RMS
root mean square
SCI
serial communications interface module; a module that supports asynchronous
communication
SMPS
switched mode power supply
software
instructions and data that control the operation of a microcontroller
SPI
serial peripheral interface module; a module that supports synchronous
communication
SWI
software interrupt; an instruction that causes an interrupt and its associated vector
fetch
THD
total harmonic distortion
timer
A module used to relate events in a system to a point in time
UPS
uninterruptable power supply
Single Phase On-Line UPS Using MC9S12E128
128
Freescale Semiconductor
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DRM064
Rev. 0, 09/2004