14-Bit, 500 kSPS PulSAR ADC in MSOP AD7946 APPLICATION DIAGRAM 0.5V TO 5V 14-bit resolution with no missing codes Throughput: 500 kSPS INL: ±0.4 LSB typical, ±1 LSB maximum (±0.0061% of FSR) SINAD: 85 dB @ 20 kHz THD: −100 dB @ 20 kHz Pseudo differential analog input range 0 V to REF with REF up to VDD No pipeline delay Single-supply 5 V operation with 1.8 V/2.5 V/3 V/5 V logic interface Serial interface, SPI/QSPI/MICROWIRE™/DSP compatible Daisy-chain multiple ADCs and BUSY indicator Power dissipation 3.3 mW @ 5 V/100 kSPS 3.3 μW @ 5 V/100 SPS Standby current: 1 nA 10-lead MSOP (MSOP-8 size) and 3 mm × 3 mm QFN (LFCSP) (SOT-23 size) Pin-for-pin compatible with the 16-bit AD7686 0V TO REF IN+ IN– 5V REF VDD VIO SDI AD7946 1.8V TO VDD SCK SDO GND 3- OR 4-WIRE INTERFACE (SPI, DAISY CHAIN, CS) CNV 04656-001 FEATURES Figure 1. GENERAL DESCRIPTION The AD7946 is a 14-bit, charge redistribution, successive approximation, analog-to-digital converter (ADC) that operates from a single 5 V power supply, VDD. It contains a low power, high speed, 14-bit sampling ADC with no missing codes, an internal conversion clock, and a versatile serial interface port. The part also contains a low noise, wide bandwidth, short aperture delay track-and-hold circuit. On the CNV rising edge, it samples an analog input IN+ between 0 V to REF with respect to a ground sense IN−. The reference voltage, REF, is applied externally and can be set up to the supply voltage. APPLICATIONS Battery-powered equipment Data acquisition Instrumentation Medical instruments Process control Its power scales linearly with throughput. The SPI-compatible serial interface also features the ability, using the SDI input, to daisy-chain several ADCs on a single, 3-wire bus, or it provides an optional BUSY indicator. It is compatible with 1.8 V, 2.5 V, 3 V, or 5 V logic, using the separate supply VIO. The AD7946 is housed in a 10-lead MSOP or a 10-lead QFN (LFCSP) with operation specified from −40°C to +85°C. Table 1. MSOP, QFN (LFCSP) 14-/16-/18-Bit PulSAR® ADC Type 14-Bit 16-Bit 100 kSPS AD7940 AD7680 AD7683 AD7684 18-Bit 1 250 kSPS AD7942 1 AD76851 AD76871 AD7694 AD76911 400 kSPS to 500 kSPS AD79461 AD76861 AD76881 AD76931 AD76901 ≥1000 kSPS ADC Driver AD79801 AD79831 ADA4941 ADA4841 AD79821 AD79841 ADA4941 ADA4841 Pin-for-pin compatible. Rev. A Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 www.analog.com Fax: 781.461.3113 ©2005–2007 Analog Devices, Inc. All rights reserved. AD7946 TABLE OF CONTENTS Features .............................................................................................. 1 Voltage Reference Input ............................................................ 14 Applications....................................................................................... 1 Power Supply............................................................................... 15 Application Diagram........................................................................ 1 Supplying the ADC from the Reference.................................. 15 General Description ......................................................................... 1 Single-Supply Application......................................................... 15 Revision History ............................................................................... 2 Digital Interface.......................................................................... 16 Specifications..................................................................................... 3 CS MODE 3-Wire, No BUSY Indicator .................................. 17 Timing Specifications .................................................................. 5 CS Mode 3-Wire with BUSY Indicator ................................... 18 Absolute Maximum Ratings............................................................ 6 CS Mode 4-Wire, No BUSY Indicator..................................... 19 ESD Caution.................................................................................. 6 CS Mode 4-Wire with BUSY Indicator ................................... 20 Pin Configurations and Function Descriptions ........................... 7 Chain Mode, No BUSY Indicator ............................................ 21 Typical Performance Characteristics ............................................. 8 Chain Mode with BUSY Indicator........................................... 22 Terminology .................................................................................... 11 Application Guidelines .................................................................. 23 Theory of Operation ...................................................................... 12 Layout .......................................................................................... 23 Circuit Information.................................................................... 12 Evaluating the AD7946’s Performance.................................... 23 Converter Operation.................................................................. 12 Outline Dimensions ....................................................................... 24 Typical Connection Diagram ................................................... 13 Ordering Guide .......................................................................... 24 Analog Input ............................................................................... 13 Driver Amplifier Choice............................................................ 14 REVISION HISTORY 12/07—Rev. 0 to Rev. A QFN Package Available......................................................Universal Changes to Table 1............................................................................ 1 Changes to Table 5............................................................................ 6 Changes to Ordering Guide .......................................................... 24 7/05—Revision 0: Initial Version Rev. A | Page 2 of 24 AD7946 SPECIFICATIONS VDD = 4.5 V to 5.5 V, VIO = 2.3 V to VDD, REF = VDD, TA = −40°C to +85°C, unless otherwise noted. Table 2. Parameter RESOLUTION ANALOG INPUT Voltage Range Absolute Input Voltage Analog Input CMRR Leakage Current at 25°C Input Impedance ACCURACY No Missing Codes Differential Linearity Error Integral Linearity Error Transition Noise Gain Error 2 , TMIN to TMAX Gain Error Temperature Drift Offset Error2, TMIN to TMAX Offset Temperature Drift Power Supply Sensitivity THROUGHPUT Conversion Rate Transient Response AC ACCURACY Signal-to-Noise Spurious-Free Dynamic Range Total Harmonic Distortion Signal-to-(Noise + Distortion) Conditions Min 14 IN+ − IN− IN+ IN− fIN = 200 kHz Acquisition phase 0 −0.1 −0.1 Typ Max Unit Bits REF VDD + 0.1 0.1 V V V dB nA 65 1 See the Analog Input section 14 −0.7 −1 REF = VDD = 5 V VDD = 5 V ± 5% ±0.3 ±0.4 0.33 ±0.3 ±1 ±0.3 ±1 ±0.1 0 Intermodulation Distortion 4 1 84.5 84.5 ±6 ±6 500 400 Full-scale step fIN = 20 kHz, REF = 5 V fIN = 20 kHz, REF = 2.5 V fIN = 20 kHz fIN = 20 kHz fIN = 20 kHz, REF = 5 V fIN = 20 kHz, REF = 5 V, −60 dB input +0.7 +1 85 84 −100 −100 85 25 100 Bits LSB 1 LSB LSB LSB ppm/°C LSB ppm/°C LSB kSPS ns dB 3 dB dB dB dB dB dB LSB means least significant bit. With the 5 V input range, one LSB is 305.2 μV. See the Terminology section. These specifications do include full temperature range variation but do not include the error contribution from the external reference. 3 All specifications in dB are referred to a full-scale input, FS. Tested with an input signal at 0.5 dB below full scale, unless otherwise specified. 4 fIN1 = 21.4 kHz, fIN2 = 18.9 kHz, each tone at −7 dB below full scale. 2 Rev. A | Page 3 of 24 AD7946 VDD = 4.5 V to 5.5 V, VIO = 2.3 V to VDD, REF = VDD, TA = −40°C to +85°C, unless otherwise noted. Table 3. Parameter REFERENCE Voltage Range Load Current SAMPLING DYNAMICS −3 dB Input Bandwidth Aperture Delay DIGITAL INPUTS Logic Levels VIL VIH IIL IIH DIGITAL OUTPUTS Data Format Pipeline Delay Conditions VOL VOH POWER SUPPLIES VDD VIO VIO Range Standby Current 1, 2 Power Dissipation ISINK = +500 μA ISOURCE = −500 μA TEMPERATURE RANGE 3 Specified Performance Min Typ 0.5 Max Unit VDD + 0.3 500 kSPS, REF = 5 V 100 V μA VDD = 5 V 9 2.5 MHz ns −0.3 0.7 × VIO −1 −1 Serial 14-bits straight binary Conversion results available immediately after completed conversion 0.4 VIO − 0.3 Specified performance Specified performance 4.5 2.3 1.8 VDD and VIO = 5 V, 25°C VDD = 5 V, 100 SPS throughput VDD = 5 V, 100 kSPS throughput VDD = 5 V, 500 kSPS throughput TMIN to TMAX 0.3 × VIO VIO + 0.3 +1 +1 1 3.3 3.3 −40 1 With all digital inputs forced to VIO or GND as required. During acquisition phase. 3 Contact sales for extended the temperature range. 2 Rev. A | Page 4 of 24 5.5 VDD + 0.3 VDD + 0.3 50 V V μA μA V V 3.8 19 V V V nA μW mW mW +85 °C AD7946 TIMING SPECIFICATIONS TA = −40°C to +85°C, VDD = 4.5 V to 5.5 V, VIO = 2.3 V to 5.5 V or VDD + 0.3 V, whichever is the lowest, unless otherwise stated. See Figure 2 and Figure 3 for load conditions. Table 4. Parameter Conversion Time: CNV Rising Edge to Data Available Acquisition Time Time Between Conversions CNV Pulse Width (CS Mode) SCK Period (CS Mode) SCK Period (Chain Mode) VIO Above 4.5 V VIO Above 3 V VIO Above 2.7 V VIO Above 2.3 V SCK Low Time SCK High Time SCK Falling Edge to Data Remains Valid SCK Falling Edge to Data Valid Delay VIO Above 4.5 V VIO Above 3 V VIO Above 2.7 V VIO Above 2.3 V CNV or SDI Low to SDO D15 MSB Valid (CS Mode) VIO Above 4.5 V VIO Above 2.7 V VIO Above 2.3 V CNV or SDI High or Last SCK Falling Edge to SDO High Impedance (CS Mode) SDI Valid Setup Time from CNV Rising Edge (CS Mode) SDI Valid Hold Time from CNV Rising Edge (CS Mode) SCK Valid Setup Time from CNV Rising Edge (Chain Mode) SCK Valid Hold Time from CNV Rising Edge (Chain Mode) SDI Valid Setup Time from SCK Falling Edge (Chain Mode) SDI Valid Hold Time from SCK Falling Edge (Chain Mode) SDI High to SDO High (Chain Mode with Busy Indicator) VIO Above 4.5 V VIO Above 2.3 V Rev. A | Page 5 of 24 Symbol tCONV tACQ tCYC tCNVH tSCK tSCK tSCKL tSCKH tHSDO tDSDO Min 0.5 400 2 10 15 Typ Max 1.6 17 18 19 20 7 7 5 Unit μs ns μs ns ns ns ns ns ns ns ns ns 14 15 16 17 ns ns ns ns 15 18 22 25 ns ns ns ns ns ns ns ns ns ns 15 26 ns ns tEN tDIS tSSDICNV tHSDICNV tSSCKCNV tHSCKCNV tSSDISCK tHSDISCK tDSDOSDI 15 0 5 5 3 4 AD7946 ABSOLUTE MAXIMUM RATINGS Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. Table 5. Parameter Analog Inputs IN+ 1 , IN−1 REF Supply Voltages VDD, VIO to GND VDD to VIO Digital Inputs to GND Digital Outputs to GND Storage Temperature Range Junction Temperature θJA Thermal Impedance 10-Lead MSOP 10-Lead QFN θJC Thermal Impedance 10-Lead MSOP 10-Lead QFN Lead Temperature Vapor Phase (60 sec) Infrared (15 sec) GND − 0.3 V to VDD + 0.3 V or ±130 mA GND − 0.3 V to VDD + 0.3 V −0.3 V to +7 V ±7 V −0.3 V to VIO + 0.3 V −0.3 V to VIO + 0.3 V −65°C to +150°C 150°C ESD CAUTION 200°C/W 48.7°C/W 44°C/W 2.96°C/W 215°C 220°C See the Analog Input section. 500µA TO SDO IOL 1.4V CL 50pF 500µA 04656-002 IOH Figure 2. Load Circuit for Digital Interface Timing 70% OVDD 30% VIO tDELAY tDELAY 2V or OVDD – 0.5V1 0.8V or 0.5V2 2V or VIO – 0.5V1 0.8V or 0.5V2 NOTES 12V IF VIO ABOVE 2.5V, VIO – 0.5V IF VIO BELOW 2.5V. 20.8V IF VIO ABOVE 2.5V, 0.5V IF VIO BELOW 2.5V. Figure 3. Voltage Levels for Timing Rev. A | Page 6 of 24 04656-003 1 Rating AD7946 PIN CONFIGURATIONS AND FUNCTION DESCRIPTIONS VIO AD7946 9 SDI TOP VIEW (Not to Scale) 8 SCK 7 SDO 6 CNV IN+ 3 IN– 4 GND 5 REF 1 VDD 2 IN+ 3 IN– 4 GND 5 10 VIO AD7946 TOP VIEW (Not to Scale) 9 SDI 8 SCK 7 SDO 6 CNV 04656-005 10 04656-004 REF 1 VDD 2 Figure 5. 10-Lead QFN (LFCSP) Pin Configuration Figure 4. 10-Lead MSOP Pin Configuration Table 6. Pin Function Descriptions Pin No. 1 Mnemonic REF Type 1 AI 2 3 VDD IN+ P AI 4 5 6 IN− GND CNV AI P DI 7 8 9 SDO SCK SDI DO DI DI 10 VIO P 1 Description Reference Input Voltage. The REF range is from 0.5 V to VDD, and is referred to the GND pin. This pin should be decoupled closely to the pin with a 10 μF capacitor. Power Supply. Analog Input. It is referred to IN−. The voltage range, that is, the difference between IN+ and IN−, is 0 V to REF. Analog Input Ground Sense. Connect to the analog ground plane or to a remote sense ground. Power Supply Ground. Convert Input. This input has multiple functions. On its leading edge, it initiates the conversions and selects the interface mode, chain, or CS. In CS mode, it enables the SDO pin when low. In chain mode, the data should be read when CNV is high. Serial Data Output. The conversion result is output on this pin. It is synchronized to SCK. Serial Data Clock Input. When the part is selected, the conversion result is shifted out by this clock. Serial Data Input. This input provides multiple features. It selects the interface mode of the ADC as follows: Chain mode is selected if SDI is low during the CNV rising edge. In this mode, SDI is used as a data input to daisy-chain the conversion results of two or more ADCs onto a single SDO line. The digital data level on SDI is output on SDO with a delay of 14 SCK cycles. CS mode is selected if SDI is high during the CNV rising edge. In this mode, either SDI or CNV can enable the serial output signals when low, and if SDI or CNV is low when the conversion is complete, the BUSY indicator feature is enabled. Input/Output Interface Digital Power. Nominally at the same supply as the host interface (1.8 V, 2.5 V, 3 V, or 5 V). AI = analog input, DI = digital input, DO = digital output, and P = power. Rev. A | Page 7 of 24 AD7946 TYPICAL PERFORMANCE CHARACTERISTICS 1.0 1.0 POSITIVE INL = +0.17LSB NEGATIVE INL = –0.26LSB 0.6 0.4 0.4 0.2 0.2 DNL (LSB) 0.6 0 –0.2 –0.4 –0.4 –0.6 –0.6 –0.8 0 4096 8192 12288 04656-009 0 –0.2 –0.8 –1.0 16384 0 4096 8192 CODE Figure 6. Integral Nonlinearity vs. Code 150000 261120 VDD = REF = 5V 131592 125000 200000 100000 COUNTS 250000 150000 50000 50000 25000 0 0 200A 200B 200C 0 0 0 200D 200E 200F CODE IN HEX 0 –60 –80 –100 –120 –140 –180 0 04656-008 –160 20 40 60 80 2059 205A 205B 205C 0 0 205D 205E 90 SNR REFERENCE TO FULL SCALE (dB) –40 0 Figure 10. Histogram of a DC Input at the Code Transition 8192 POINT FFT VDD = REF = 5V fS = 500kSPS fIN = 20.14kHz SNR = 85.3dB THD = –105.2dB SECOND HARMONIC = –106dB THIRD HARMONIC = –110dB –20 0 CODE IN HEX Figure 7. Histogram of a DC Input at the Code Center 0 VDD = REF = 5V 88 86 84 82 80 –10 100 120 140 160 180 200 220 240 FREQUENCY (kHz) 04656-011 0 2009 04656-046 0 129528 75000 100000 AMPLITUDE (dB of Full Scale) 16384 Figure 9. Differential Nonlinearity vs. Code 300000 COUNTS 12288 CODE 04656-047 –1.0 POSITIVE DNL = +0.20LSB NEGATIVE DNL = –0.13LSB 0.8 04656-006 INL (LSB) 0.8 –8 –6 –4 INPUT LEVEL (dB) Figure 8. FFT Plot Figure 11. SNR vs. Input Level Rev. A | Page 8 of 24 –2 AD7946 90.0 15.0 87.5 14.5 –90 14.0 SINAD THD, SFDR (dB) 85.0 ENOB (Bits) SNR ENOB 82.5 –100 THD –105 SFDR –110 13.5 2.7 3.1 3.5 3.9 4.3 4.7 5.1 13.0 5.5 –120 2.3 04656-015 80.0 2.3 04656-012 –115 2.7 3.1 REFERENCE VOLTAGE (V) 3.5 3.9 4.3 4.7 –90 REF = 5V REF = 5V 87.5 –100 THD (dB) 85.0 82.5 –110 80.0 –55 04656-013 –120 –35 –15 5 25 45 65 85 105 –130 –55 125 04656-016 SNR (dB) 5.5 Figure 15. THD, SFDR vs. Reference Voltage 90.0 –35 –15 TEMPERATURE (°C) 95 –70 90 –80 THD (dB) –60 REF = 5V, –10dB 80 25 45 65 85 105 125 Figure 16. THD vs. Temperature 100 85 5 TEMPERATURE (°C) Figure 13. SNR vs. Temperature REF = 5V, –1dB –90 REF = 5V, –1dB –100 REF = 5V, –10dB 75 0 50 100 150 –120 200 FREQUENCY (kHz) 04656-017 –110 04656-014 70 5.1 REFERENCE VOLTAGE (V) Figure 12. SNR, SINAD, and ENOB vs. Reference Voltage SINAD (dB) SNR, SINAD (dB) –95 0 50 100 FREQUENCY (kHz) Figure 14. SINAD vs. Frequency Figure 17. THD vs. Frequency Rev. A | Page 9 of 24 150 200 AD7946 3 1000 VDD 500 250 VIO 0 4.50 4.75 5.00 5.25 2 1 OFFSET ERROR 0 –1 GAIN ERROR –2 –3 –55 5.50 04656-021 OFFSET AND GAIN ERROR (LSB) 750 04656-048 OPERATING CURRENT (µA) fS = 100kSPS –35 –15 Figure 18. Operating Current vs. Supply 25 45 65 85 105 125 Figure 21. Offset and Gain Error vs. Temperature 1000 25 20 750 TDSDO DELAY (ns) POWER-DOWN CURRENT (nA) 5 TEMPERATURE (°C) SUPPLY (V) 500 15 VDD = 5V, 85°C 10 VDD = 5V, 25°C 250 0 –55 –35 –15 5 25 45 65 04656-050 VDD+VIO 85 105 125 TEMPERATURE (°C) Figure 19. Power-Down Current vs. Temperature VDD = 5V 500 250 04656-049 OPERATING CURRENT (µA) fS = 100kSPS VIO 0 –55 –35 –15 5 25 45 65 85 105 0 20 40 60 80 SDO CAPACITIVE LOAD (pF) 100 Figure 22. tDSDO Delay vs. Capacitance Load and Supply 1000 750 0 04656-022 5 125 TEMPERATURE (°C) Figure 20. Operating Current vs. Temperature Rev. A | Page 10 of 24 120 AD7946 TERMINOLOGY Integral Nonlinearity Error (INL) INL refers to the deviation of each individual code from a line drawn from negative full scale through positive full scale. The point used as negative full scale occurs ½ LSB before the first code transition. Positive full scale is defined as a level 1½ LSB beyond the last code transition. The deviation is measured from the middle of each code to the true straight line (Figure 24). Differential Nonlinearity Error (DNL) In an ideal ADC, code transitions are 1 LSB apart. DNL is the maximum deviation from this ideal value. It is often specified in terms of resolution for which no missing codes are guaranteed. Offset Error The first transition should occur at a level ½ LSB above analog ground (152.6 μV for the 0 V to 5 V range). The offset error is the deviation of the actual transition from that point. Gain Error The last transition (from 111 … 10 to 111 … 11) should occur for an analog voltage 1½ LSB below the nominal full scale (4.999542 V for the 0 V to 5 V range). The gain error is the deviation of the actual level of the last transition from the ideal level after the offset has been adjusted out. Spurious-Free Dynamic Range (SFDR) SFDR is the difference, in decibels (dB), between the rms amplitude of the input signal and the peak spurious signal. Effective Number of Bits (ENOB) ENOB is a measurement of the resolution with a sine wave input. It is related to SINAD by the following formula: ENOB = (SINADdB − 1.76)/6.02 and is expressed in bits. Total Harmonic Distortion (THD) THD is the ratio of the rms sum of the first five harmonic components to the rms value of a full-scale input signal and is expressed in dB. Signal-to-Noise Ratio (SNR) SNR is the ratio of the rms value of the actual input signal to the rms sum of all other spectral components below the Nyquist frequency, excluding harmonics and dc. The value for SNR is expressed in dB. Signal-to-(Noise + Distortion) Ratio (SINAD) SINAD is the ratio of the rms value of the actual input signal to the rms sum of all other spectral components below the Nyquist frequency, including harmonics but excluding dc. The value for SINAD is expressed in dB. Aperture Delay Aperture delay is the measurement of the acquisition performance and is the time between the rising edge of the CNV input and when the input signal is held for a conversion. Transient Response Transient response is the time required for the ADC to accurately acquire its input after a full-scale step function is applied. Rev. A | Page 11 of 24 AD7946 THEORY OF OPERATION IN+ SWITCHES CONTROL MSB REF 8192C 4096C LSB 4C 2C C SW+ C BUSY COMP GND 8192C 4096C 4C 2C C CONTROL LOGIC OUTPUT CODE C MSB LSB SW– 04656-023 CNV IN– Figure 23. ADC Simplified Schematic The AD7946 is a fast, low power, single-supply, precise 14-bit ADC using a successive approximation architecture. The AD7946 can convert 500,000 samples per second (500 kSPS) and powers down between conversions. When operating at 100 SPS, for example, it consumes 3.3 μW typically, ideal for battery-powered applications. The AD7946 provides the user with an on-chip track-and-hold and does not exhibit any pipeline delay or latency, making it ideal for multiple multiplexed channel applications. The AD7946 is specified from 4.5 V to 5.5 V and can be interfaced to any of the 1.8 V to 5 V digital logic family. It is housed in a 10-lead MSOP or a tiny 10-lead QFN (LFCSP) that combines space savings and allows flexible configurations. It is pin-for-pin compatible with the 16-bit ADC AD7686. CONVERTER OPERATION The AD7946 is a successive approximation ADC based on a charge redistribution DAC. Figure 23 shows the simplified schematic of the ADC. The capacitive DAC consists of two identical arrays of 14 binary weighted capacitors, which are connected to the two comparator inputs. The control logic toggles these switches, starting with the MSB, in order to bring the comparator back into a balanced condition. After completing this process, the part returns to the acquisition phase, and the control logic generates the ADC output code and a BUSY signal indicator. Because the AD7946 has an on-board conversion clock, the serial clock, SCK, is not required for the conversion process. Transfer Functions The ideal transfer characteristic for the AD7946 is shown in Figure 24 and Table 7. ADC CODE (Straight Binary) CIRCUIT INFORMATION 111...111 111...110 111...101 000...010 000...000 –FSR During the acquisition phase, the terminals of the array that are tied to the comparator’s input are connected to GND via SW+ and SW−. All independent switches are connected to the analog inputs. Thus, the capacitor arrays are used as sampling capacitors and acquire the analog signal on the IN+ and IN− inputs. When the acquisition phase is complete and the CNV input goes high, a conversion phase is initiated. When the conversion phase begins, SW+ and SW− are opened first. The two capacitor arrays are then disconnected from the inputs and connected to the GND input. Therefore, the differential voltage between the inputs IN+ and IN− captured at the end of the acquisition phase is applied to the comparator inputs, causing the comparator to become unbalanced. By switching each element of the capacitor array between GND and REF, the comparator input varies by binary weighted voltage steps (REF/2, REF/4 … REF/16,384). –FSR + 1 LSB +FSR – 1 LSB +FSR – 1.5 LSB –FSR + 0.5 LSB ANALOG INPUT 04656-024 000...001 Figure 24. ADC Ideal Transfer Function Table 7. Output Codes and Ideal Input Voltages Description FSR − 1 LSB Midscale + 1 LSB Midscale Midscale − 1 LSB −FSR + 1 LSB −FSR Analog Input REF = 5 V 4.999695 V 2.500305 V 2.5 V 2.499695 V 305.2 μV 0V Digital Output Code Hexa 3FFF1 2001 2000 1FFF 0001 00002 1 This is also the code for an overranged analog input (VIN+ − VIN− above REF − VGND). 2 This is also the code for an underranged analog input (VIN+ − VIN− below VGND). Rev. A | Page 12 of 24 AD7946 TYPICAL CONNECTION DIAGRAM Figure 25 shows an example of the recommended connection diagram for the AD7946 when multiple supplies are available. (NOTE 1) V+ 5V REF 10µF (NOTE 2) 100nF 1.8V TO VDD V+ 100nF REF 33Ω VDD VIO SDI IN+ 0V TO REF (ADA4841 OR NOTE 3) (NOTE 4) SCK AD7946 2.7nF V– 3- OR 4-WIRE INTERFACE (NOTE 5) SDO IN– CNV GND 04656-025 NOTES 1. SEE REFERENCE SECTION FOR REFERENCE SELECTION. 2. CREF IS USUALLY A 10µF CERAMIC CAPACITOR (X5R). 3. SEE DRIVER AMPLIFIER CHOICE SECTION. 4. OPTIONAL FILTER. SEE ANALOG INPUT SECTION. 5. SEE DIGITAL INTERFACE FOR MOST CONVENIENT INTERFACE MODE. Figure 25. Typical Application Diagram with Multiple Supplies 70 ANALOG INPUT Figure 26 shows an equivalent circuit of the input structure of the AD7946. 60 CMRR (dB) 50 40 1 D1 100 1k 10k Figure 27. Analog Input CMRR vs. Frequency RIN CIN D2 04656-026 CPIN 10 FREQUENCY (kHz) VDD IN+ OR IN– VDD = 5V 04656-027 The two diodes, D1 and D2, provide ESD protection for the analog inputs IN+ and IN−. Care must be taken to ensure that the analog input signal never exceeds the supply rails by more than 0.3 V because this causes these diodes to begin to forwardbias and start conducting current. These diodes can handle a maximum forward-biased current of 130 mA. For instance, these conditions could eventually occur when the input buffer’s (U1) supplies are different from VDD. In such a case, an input buffer with a short-circuit current limitation can be used to protect the part. GND Figure 26. Equivalent Analog Input Circuit The analog input structure allows the sampling of the differential signal between IN+ and IN−. By using this differential input, small signals common to both inputs are rejected, as shown in Figure 27, which represents the typical CMRR over frequency. For instance, by using IN− to sense a remote signal ground, ground potential differences between the sensor and the local ADC ground are eliminated. During the acquisition phase, the impedance of the analog inputs (IN+ or IN−) can be modeled as a parallel combination of capacitor, CPIN, and the network formed by the series connection of RIN and CIN. CPIN is primarily the pin capacitance. RIN is typically 600 Ω and is a lumped component made up of some serial resistors and the on resistance of the switches. CIN is typically 30 pF and is mainly the ADC sampling capacitor. During the conversion phase, when the switches are opened, the input impedance is limited to CPIN. RIN and CIN make a 1-pole, low-pass filter, which reduces undesirable aliasing effects and limits the noise. When the source impedance of the driving circuit is low, the AD7946 can be driven directly. Large source impedances significantly affect the ac performance, especially total harmonic distortion (THD). The dc performances are less sensitive to the input impedance. The maximum source impedance depends on the amount of THD that can be Rev. A | Page 13 of 24 AD7946 tolerated. The THD degrades as a function of the source impedance and the maximum input frequency, as shown in Figure 28. Table 8. Recommended Driver Amplifiers Amplifier ADA4841 AD8021 AD8655 AD8022 OP184 AD8605, AD8615 AD8519 AD8031 –80 –85 THD (dB) –90 RS = 250Ω –95 RS =100Ω –100 RS = 33Ω The AD7946 voltage reference input REF has a dynamic input impedance and should therefore be driven by a low impedance source with efficient decoupling between the REF and GND pins, as explained in the Layout section. 04656-028 –110 VOLTAGE REFERENCE INPUT RS = 50Ω –105 0 25 50 75 100 FREQUENCY (kHz) When REF is driven by a very low impedance source, for example, a reference buffer using the AD8031 or the AD8603, a 10 μF (X5R, 0805 size) ceramic chip capacitor is appropriate for optimum performance. Figure 28. THD vs. Analog Input Frequency and Source Resistance DRIVER AMPLIFIER CHOICE Although the AD7946 is easy to drive, the driver amplifier needs to meet the following requirements: • Typical Application Very low noise, small and low power Very low noise and high frequency 5 V single-supply, low noise, and low power Low noise and high frequency Low power, low noise, and low frequency 5 V single-supply, low power Small, low power, and low frequency High frequency and low power The noise generated by the driver amplifier needs to be kept as low as possible to preserve the SNR and transition noise performance of the AD7946. Note that the AD7946 has a noise much lower than most of the other 14-bit ADCs and, therefore, can be driven by a noisier amplifier to meet a given system noise specification. The noise coming from the amplifier is filtered by the AD7946 analog input circuit 1-pole, low-pass filter made by RIN and CIN or by the external filter, if one is used. • For ac applications, the driver should have a THD performance commensurate with the AD7946. Figure 17 shows the THD vs. frequency that the driver should exceed. • For multichannel multiplexed applications, the driver amplifier and the AD7946 analog input circuit must settle a full-scale step onto the capacitor array at a 14-bit level (0.006%). In the amplifier’s data sheet, settling at 0.1% to 0.01% is more commonly specified. This could differ significantly from the settling time at a 14-bit level and should be verified prior to driver selection. If an unbuffered reference voltage is used, the decoupling value depends on the reference used. For instance, a 22 μF (X5R, 1206 size) ceramic chip capacitor is appropriate for optimum performance using a low temperature drift ADR43x reference. If desired, smaller reference decoupling capacitor values down to 2.2 μF can be used with a minimal impact on performance, especially DNL. Regardless, there is no need for an additional lower value ceramic decoupling capacitor (for example, 100 nF) between the REF and GND pins. Rev. A | Page 14 of 24 AD7946 POWER SUPPLY SUPPLYING THE ADC FROM THE REFERENCE The AD7946 is specified at 4.5 V to 5.5 V. It uses two power supply pins: a core supply VDD and a digital input/output interface supply VIO. VIO allows direct interface with any logic between 1.8 V and VDD. To reduce the supplies needed, the VIO and VDD can be tied together. The AD7946 is independent of power supply sequencing between VIO and VDD. Additionally, it is very insensitive to power supply variations over a wide frequency range, as shown in Figure 29, which represents PSRR over frequency. For simplified applications, the AD7946, with its low operating current, can be supplied directly using the reference circuit shown in Figure 31. The reference line can be driven by one of the following: • The system power supply directly. • A reference voltage with enough current output capability, such as the ADR43x. • A reference buffer, such as the AD8031 or AD8603, which can also filter the system power supply, as shown in Figure 31. 90 80 5V VDD = 5V 10kΩ 5V 60 1kΩ 1µF 47kΩ AD8603 10µF 1µF (NOTE 1) 50 REF VIO AD7946 04656-029 40 30 1 10 100 1k 10k NOTES 1. OPTIONAL REFERENCE BUFFER AND FILTER Figure 31. Example of Application Circuit FREQUENCY (kHz) SINGLE-SUPPLY APPLICATION Figure 29. PSRR vs. Frequency The AD7946 powers down automatically at the end of each conversion phase and, therefore, the power scales linearly with the sampling rate, as shown in Figure 30. This makes the part ideal for low sampling rate (even a few Hz) and low batterypowered applications. 1000 VDD = 5V 100 VIO 10 1 0.1 0.01 0.001 10 04656-051 OPERATING CURRENT (µA) VDD 100 1k 10k 04656-031 PSRR (dB) 70 100k SAMPLING RATE (SPS) Figure 30. Operating Currents vs. Sampling Rate 1M Figure 32 shows a typical 14-bit single-supply application. There are different challenges to doing a single-supply, high resolution design, and the ADA4841 addresses these nicely. The combination of low noise, low power, wide input range, rail-to-rail output, and high speed make the ADA4841 a perfect driver solution for low power, single-supply 14-bit ADCs, such as the AD7946. In a single-supply system, one of the main challenges is to use the amplifier in buffer mode to have the lowest output noise and still preserve linearity compatible with the ADC. Rail-to-rail input amplifiers usually have higher noise than the ADA4841 and cannot be used on their entire input range in buffer mode because of the nonlinear region around the crossover point of their input stage. The ADA4841, which has no crossover region but has a wide linear input range from ground to 1 V below positive rail, solves this issue, as shown in Figure 32, where it can accept the 0 V to 4.096 V input range with a supply as low as 5.2 V. This supply allows using a small, low dropout, low temperature drift ADR364 reference voltage. Note that, like any rail-to-rail output amplifier at the low end of its output range close to ground, the ADA4841 can exhibit some nonlinearity on a small region of approximately 25 mV from ground. The ADA4841 drives a 1-pole, low-pass filter. This filter limits the already very low noise contribution from the amplifier to the AD7946. Rev. A | Page 15 of 24 AD7946 >5.2V independent of the readback timing (SDI). This is useful in low jitter sampling or simultaneous sampling applications. 100nF ADR364 100nF ADA4841 The AD7946, when in chain mode, provides a daisy chain feature using the SDI input for cascading multiple ADCs on a single data line similar to a shift register. 10µF 100nF 0V TO 4.096V 33Ω REF VDD IN+ VIO SDI AD7946 2.7nF SCK SDO IN– CNV 04656-052 GND Figure 32. Example of a Single-Supply Application Circuit DIGITAL INTERFACE Although the AD7946 has a reduced number of pins, it offers flexibility in its serial interface modes. The AD7946, when in CS mode, is compatible with SPI, QSPI™, digital hosts, and DSPs, for example, Blackfin® ADSP-BF53x or ADSP-219x. This interface can use either 3-wire or 4-wire. A 3-wire interface using the CNV, SCK, and SDO signals minimizes wiring connections useful, for instance, in isolated applications. A 4-wire interface using the SDI, CNV, SCK, and SDO signals allows CNV, which initiates the conversions, to be The operating mode depends on the SDI level when the CNV rising edge occurs. CS mode is selected if SDI is high, and chain mode is selected if SDI is low. The SDI hold time is such that when SDI and CNV are connected, the chain mode is always selected. In either mode, the AD7946 offers the flexibility to optionally force a start bit in front of the data bits. This start bit can be used as a BUSY signal indicator to interrupt the digital host and trigger the data reading. Otherwise, without a BUSY indicator, the user must time out the maximum conversion time prior to readback. BUSY indicator feature is enabled • In CS mode, if CNV or SDI is low when the ADC conversion ends (see Figure 36 and Figure 40). • In chain mode, if SCK is high during the CNV rising edge (see Figure 44). Rev. A | Page 16 of 24 AD7946 are then clocked by subsequent SCK falling edges. The data is valid on both SCK edges. Although the rising edge can be used to capture the data, a digital host using the SCK falling edge allows a faster reading rate, provided it has an acceptable hold time. After the 14th SCK falling edge or when CNV goes high, whichever is earlier, SDO returns to high impedance. CS MODE 3-WIRE, NO BUSY INDICATOR This mode is usually used when a single AD7946 is connected to an SPI-compatible digital host. The connection diagram is shown in Figure 33 and the corresponding timing is given in Figure 34. With SDI tied to VIO, a rising edge on CNV initiates a conversion, selects the CS mode, and forces SDO to high impedance. Once a conversion is initiated, it continues to completion irrespective of the state of CNV. For instance, it could be useful to bring CNV low to select other SPI devices, such as analog multiplexers, but CNV must be returned high before the minimum conversion time and held high until the maximum conversion time to avoid the generation of the BUSY signal indicator. When the conversion is complete, the AD7946 enters the acquisition phase and powers down. When CNV goes low, the MSB is output onto SDO. The remaining data bits CONVERT DIGITAL HOST CNV VIO SDI AD7946 DATA IN SDO 04656-032 SCK CLK Figure 33. CS Mode 3-Wire, No BUSY Indicator Connection Diagram (SDI High) SDI = 1 tCYC tCNVH CNV ACQUISITION tCONV tACQ CONVERSION ACQUISITION tSCK tSCKL 1 2 3 12 tHSDO 14 tSCKH tDSDO tEN SDO 13 D13 D12 D11 tDIS D1 D0 Figure 34. CS Mode 3-Wire, No BUSY Indicator Serial Interface Timing (SDI High) Rev. A | Page 17 of 24 04656-033 SCK AD7946 edges. Although the rising edge can be used to capture the data, a digital host using the SCK falling edge allows a faster reading rate, provided it has an acceptable hold time. After the optional 15th SCK falling edge, or when CNV goes high, whichever is earlier, SDO returns to high impedance. CS MODE 3-WIRE WITH BUSY INDICATOR This mode is usually used when a single AD7946 is connected to an SPI-compatible digital host having an interrupt input. The connection diagram is shown in Figure 35, and the corresponding timing is given in Figure 36. If multiple AD7946s are selected at the same time, the SDO output pin handles this contention without damage or induced latch-up. Meanwhile, it is recommended to keep this contention as short as possible to limit extra power dissipation. With SDI tied to VIO, a rising edge on CNV initiates a conversion, selects the CS mode, and forces SDO to high impedance. SDO is maintained in high impedance until the completion of the conversion irrespective of the state of CNV. Prior to the minimum conversion time, CNV could be used to select other SPI devices, such as analog multiplexers, but CNV must be returned low before the minimum conversion time and held low until the maximum conversion time to guarantee the generation of the BUSY signal indicator. When the conversion is complete, SDO goes from high impedance to low. With a pull-up on the SDO line, this transition can be used as an interrupt signal to initiate the data reading controlled by the digital host. The AD7946 then enters the acquisition phase and powers down. The data bits are then clocked out, MSB first, by subsequent SCK falling edges. The data is valid on both SCK CONVERT VIO CNV VIO AD7946 DATA IN SDO SCK IRQ 04656-034 SDI DIGITAL HOST 47kΩ CLK Figure 35. CS Mode 3-Wire with BUSY Indicator Connection Diagram (SDI High) SDI = 1 tCYC tCNVH CNV ACQUISITION tCONV tACQ CONVERSION ACQUISITION tSCK tSCKL 1 2 3 13 14 15 tSCKH tHSDO tDSDO SDO tDIS D13 D12 D1 D0 Figure 36. CS Mode 3-Wire with BUSY Indicator Serial Interface Timing (SDI High) Rev. A | Page 18 of 24 04656-035 SCK AD7946 time and held high until the maximum conversion time to avoid the generation of the BUSY signal indicator. When the conversion is complete, the AD7946 enters the acquisition phase and powers down. Each ADC result can be read by bringing its SDI input low, which consequently outputs the MSB onto SDO. The remaining data bits are then clocked by subsequent SCK falling edges. The data is valid on both SCK edges. Although the rising edge can be used to capture the data, a digital host using the SCK falling edge allows a faster reading rate, provided it has an acceptable hold time. After the 14th SCK falling edge, or when SDI goes high, whichever is earlier, SDO returns to high impedance and another AD7946 can be read. CS MODE 4-WIRE, NO BUSY INDICATOR This mode is usually used when multiple AD7946s are connected to an SPI-compatible digital host. A connection diagram example using two AD7946s is shown in Figure 37, and the corresponding timing is given in Figure 38. With SDI high, a rising edge on CNV initiates a conversion, selects the CS mode, and forces SDO to high impedance. In this mode, CNV must be held high during the conversion phase and the subsequent data readback (if SDI and CNV are low, SDO is driven low). Prior to the minimum conversion time, SDI could be used to select other SPI devices, such as analog multiplexers, but SDI must be returned high before the minimum conversion CS2 CS1 CONVERT CNV SDI AD7946 DIGITAL HOST CNV SDO SDI AD7946 SCK SDO SCK 04656-036 DATA IN CLK Figure 37. CS Mode 4-Wire, No BUSY Indicator Connection Diagram tCYC CNV ACQUISITION tCONV tACQ CONVERSION ACQUISITION tSSDICNV SDI(CS1) tHSDICNV SDI(CS2) tSCK tSCKL SCK 1 2 3 12 tHSDO 14 15 16 26 27 28 tDSDO tEN D13 D12 D11 tDIS D1 D0 D13 D12 D1 D0 04656-037 SDO 13 tSCKH Figure 38. CS Mode 4-Wire, No BUSY Indicator Serial Interface Timing Rev. A | Page 19 of 24 AD7946 low. With a pull-up on the SDO line, this transition can be used as an interrupt signal to initiate the data readback controlled by the digital host. The AD7946 then enters the acquisition phase and powers down. The data bits are then clocked out, MSB first, by subsequent SCK falling edges. The data is valid on both SCK edges. Although the rising edge can be used to capture the data, a digital host using the SCK falling edge allows a faster reading rate, provided it has an acceptable hold time. After the optional 15th SCK falling edge or SDI going high, whichever is earlier, the SDO returns to high impedance. CS MODE 4-WIRE WITH BUSY INDICATOR This mode is usually used when a single AD7946 is connected to an SPI-compatible digital host, which has an interrupt input, and it is desired to keep CNV, which is used to sample the analog input, independent of the signal used to select the data reading. This requirement is particularly important in applications where low jitter on CNV is desired. The connection diagram is shown in Figure 39, and the corresponding timing is given in Figure 40. With SDI high, a rising edge on CNV initiates a conversion, selects the CS mode, and forces SDO to high impedance. In this mode, CNV must be held high during the conversion phase and the subsequent data readback (if SDI and CNV are low, SDO is driven low). Prior to the minimum conversion time, SDI could be used to select other SPI devices, such as analog multiplexers, but SDI must be returned low before the minimum conversion time and held low until the maximum conversion time to guarantee the generation of the BUSY signal indicator. When the conversion is complete, SDO goes from high impedance to CS1 CONVERT VIO DIGITAL HOST CNV AD7946 DATA IN SDO SCK IRQ 04656-038 SDI 47kΩ CLK Figure 39. CS Mode 4-Wire with BUSY Indicator Connection Diagram tCYC CNV ACQUISITION tCONV tACQ CONVERSION ACQUISITION tSSDICNV SDI tSCK tHSDICNV tSCKL 1 2 3 tHSDO 13 14 15 tSCKH tDSDO tDIS tEN SDO D13 D12 D1 Figure 40. CS Mode 4-Wire with BUSY Indicator Serial Interface Timing Rev. A | Page 20 of 24 D0 04656-039 SCK AD7946 onto SDO, and the AD7946 enters the acquisition phase and powers down. The remaining data bits stored in the internal shift register are then clocked by subsequent SCK falling edges. For each ADC, SDI feeds the input of the internal shift register and is clocked by the SCK falling edge. Each ADC in the chain outputs its data MSB first, and 14 × N clocks are required to readback the N ADCs. The data is valid on both SCK edges. Although the rising edge can be used to capture the data, a digital host using the SCK falling edge allows a faster reading rate and consequently more AD7946s in the chain, provided the digital host has an acceptable hold time. The maximum conversion rate may be reduced due to the total readback time. For instance, with a 3 ns digital host setup time and 3 V interface, up to four AD7946s running at a conversion rate of 360 kSPS can be daisy-chained on a 3-wire port. CHAIN MODE, NO BUSY INDICATOR This mode can be used to daisy-chain multiple AD7946s on a 3-wire serial interface. This feature is useful for reducing component count and wiring connections, for example, in isolated multiconverter applications or for systems with a limited interfacing capacity. Data readback is analogous to clocking a shift register. A connection diagram example using two AD7946s is shown in Figure 41, and the corresponding timing is given in Figure 42. When SDI and CNV are low, SDO is driven low. With SCK low, a rising edge on CNV initiates a conversion, selects the chain mode, and disables the BUSY indicator. In this mode, CNV is held high during the conversion phase and the subsequent data readback. When the conversion is complete, the MSB is output CONVERT CNV AD7946 SDO DIGITAL HOST AD7946 SDI A SDO DATA IN B SCK SCK 04656-040 SDI CNV CLK Figure 41. Chain Mode, No BUSY Indicator Connection Diagram SDIA = 0 tCYC CNV tACQ CONVERSION ACQUISITION tSCK tSCKL tSSCKCNV SCK 1 tHSCKCNV 2 3 12 13 tSSDISCK 14 15 16 DA13 DA12 26 27 28 DA1 DA0 tSCKH tHSDISCK tEN SDOA = SDIB DA13 DA12 DA11 DA1 DA0 DB13 DB12 DB11 DB1 DB0 tHSDO tDSDO SDOB Figure 42. Chain Mode, No BUSY Indicator Serial Interface Timing Rev. A | Page 21 of 24 04656-041 ACQUISITION tCONV AD7946 Figure 43) SDO is driven high. This transition on SDO can be used as a BUSY indicator to trigger the data readback controlled by the digital host. The AD7946 then enters the acquisition phase and powers down. The data bits stored in the internal shift register are then clocked out, MSB first, by subsequent SCK falling edges. For each ADC, SDI feeds the input of the internal shift register and is clocked by the SCK falling edge. Each ADC in the chain outputs its data MSB first, and 14 × N + 1 clocks are required to readback the N ADCs. Although the rising edge can be used to capture the data, a digital host using the SCK falling edge allows a faster reading rate and consequently more AD7946s in the chain, provided the digital host has an acceptable hold time. For instance, with a 3 ns digital host setup time and 3 V interface, up to four AD7946s running at a conversion rate of 360 kSPS can be daisy-chained to a single 3-wire port. CHAIN MODE WITH BUSY INDICATOR This mode can be used to daisy-chain multiple AD7946s on a 3-wire serial interface while providing a BUSY indicator. This feature is useful for reducing component count and wiring connections, for example, in isolated multiconverter applications or for systems with a limited interfacing capacity. Data readback is analogous to clocking a shift register. A connection diagram example using three AD7946s is shown in Figure 43, and the corresponding timing is given in Figure 44. When SDI and CNV are low, SDO is driven low. With SCK high, a rising edge on CNV initiates a conversion, selects the chain mode, and enables the BUSY indicator feature. In this mode, CNV is held high during the conversion phase and the subsequent data readback. When all ADCs in the chain have completed their conversions, the near-end ADC (ADC C in CONVERT SDI AD7946 CNV SDO SDI A AD7946 SDO SDI B SCK DIGITAL HOST CNV AD7946 DATA IN SDO C SCK SCK IRQ 04656-042 CNV CLK Figure 43. Chain Mode with BUSY Indicator Connection Diagram tCYC ACQUISITION tCONV tACQ ACQUISITION CONVERSION tSSCKCNV SCK tHSCKCNV tSCKH 1 tEN tSSDISCK SDOA = SDIB SDOB = SDIC 2 3 4 13 14 15 16 17 27 28 29 30 31 tSCKL tHSDISCK DA13 DA12 DA11 tDSDOSDI tSCK DA1 42 43 tDSDOSDI DA0 tHSDO tDSDO tDSDOSDI DB13 DB12 DB11 DB1 DB0 DA13 DA12 DA1 DA0 DC13 DC12 DC11 DC1 DC0 DB13 DB12 DB1 DB0 DA13 DA12 tDSDOSDI SDOC 41 tDSDOSDI Figure 44. Chain Mode with BUSY Indicator Serial Interface Timing Rev. A | Page 22 of 24 DA1 DA0 04656-043 CNV = SDIA AD7946 APPLICATION GUIDELINES LAYOUT The printed circuit board that houses the AD7946 should be designed so that the analog and digital sections are separated and confined to certain areas of the board. The pinout of the AD7946, with all its analog signals on the left side and all its digital signals on the right side, eases this task. At least one ground plane should be used. It could be common or split between the digital and analog sections. In the latter case, the planes should be joined underneath the AD7946s. 04656-044 Avoid running digital lines under the device because these couple noise onto the die, unless a ground plane under the AD7946 is used as a shield. Fast switching signals, such as CNV or clocks, should never run near analog signal paths. Crossover of digital and analog signals should be avoided. Figure 45. Example of Layout of the AD7946 (Top Layer) The AD7946 voltage reference input REF has a dynamic input impedance and should be decoupled with minimal parasitic inductances. This is done by placing the reference decoupling ceramic capacitor close to, and ideally right up against, the REF and GND pins and connecting it with wide, low impedance traces. Finally, the power supplies VDD and VIO of the AD7946 should be decoupled with ceramic capacitors (typically 100 nF) placed close to the AD7946 and connected using short and wide traces to provide low impedance paths and reduce the effect of glitches on the power supply lines. 04656-045 An example of layout following these rules is shown in Figure 45 and Figure 46. EVALUATING THE AD7946’S PERFORMANCE Other recommended layouts for the AD7946 are outlined in the documentation of the evaluation board for the AD7946 (EVAL-AD7946CB). The evaluation board package includes a fully assembled and tested evaluation board, documentation, and software for controlling the board from a PC via the EVAL-CONTROL BRD3. Rev. A | Page 23 of 24 Figure 46. Example of Layout of the AD7946 (Bottom Layer) AD7946 OUTLINE DIMENSIONS 3.10 3.00 2.90 6 10 3.10 3.00 2.90 1 5 5.15 4.90 4.65 PIN 1 0.50 BSC 0.95 0.85 0.75 1.10 MAX 0.15 0.05 0.33 0.17 SEATING PLANE 0.80 0.60 0.40 8° 0° 0.23 0.08 COPLANARITY 0.10 COMPLIANT TO JEDEC STANDARDS MO-187-BA Figure 47.10-Lead Mini Small Outline Package [MSOP] (RM-10) Dimensions shown in millimeters 0.30 0.23 0.18 0.50 BSC 10 6 PIN 1 INDEX AREA *EXPOSED PAD (BOTTOM VIEW) 0.50 0.40 0.30 5 TOP VIEW 0.80 MAX 0.55 NOM 0.80 0.75 0.70 SEATING PLANE 1 2.48 2.38 2.23 0.05 MAX 0.02 NOM 0.20 REF 1.74 1.64 1.49 PIN 1 INDICATOR (R 0.19) *PADDLE CONNECTED TO GND. THIS CONNECTION IS NOT REQUIRED TO MEET THE ELECTRICAL PERFORMANCES 101207-B 3.00 BSC SQ Figure 48. 10-Lead Lead Frame Chip Scale Package [QFN (LFCSP_WD)] 3 mm × 3 mm Body, Very Very Thin, Dual Lead (CP-10-9) Dimensions shown in millimeters ORDERING GUIDE Model AD7946BRM AD7946BRM-RL7 AD7946BRMZ 1 AD7946BRMZRL71 AD7946BCPZRL71 AD7946BCPZRL1 EVAL-AD7946CBZ1, 2 EVAL-CONTROL BRD3Z1, 3 Temperature Range −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C Package Description 10-Lead MSOP 10-Lead MSOP 10-Lead MSOP 10-Lead MSOP 10-Lead QFN (LFCSP_WD) 10-Lead QFN (LFCSP_WD) Evaluation Board Evaluation Board Package Option RM-10 RM-10 RM-10 RM-10 CP-10-9 CP-10-9 Ordering Quantity Tube, 50 Reel, 1,000 Tube, 50 Reel, 1,000 Reel, 1,000 Reel, 5,000 Branding C1E C1E C4X C4X C4X C4X 1 Z = RoHS Compliant Part. This board can be used as a standalone evaluation board or in conjunction with the EVAL-CONTROL BRD3Z for evaluation/demonstration purposes. 3 This board allows a PC to control and communicate with all Analog Devices, Inc. evaluation boards ending in the CB designator. 2 ©2005–2007 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D04656-0-12/07(A) T T Rev. A | Page 24 of 24