PWR-82520 3-PHASE DC MOTOR TORQUE CONTROLLER FEATURES DESCRIPTION The PWR-82520 is a high-performance current-regulating torque loop controller. It is designed to accurately regulate the current in the windings of 3-phase brushless DC and brush DC motors. PWR-82520 can be tuned by using an external Proportional-Integral (PI) regulator network in conjunction with the internal error amplifier. The PWR-82520 is a completely selfcontained motor controller that converts the analog input command signal into motor current and uses the signals from Hall-effect sensors in the motor to commutate the current in the motor windings. The motor current is internally sensed and processed into an analog signal. This signal is summed together with the command signal to produce an error signal that controls the pulse width modulation (PWM) duty cycle of the output, thus controlling the motor current. The Packaged in a small DIP-style hybrid, the PWR-82520 are ideal for applications with limited printed circuit board area. APPLICATIONS The PWR-82520 is ideal for application requiring current regulation and/or holding torque at zero input command. System applications include flight surface control on aircraft for horizontal stabilizers and flaps, missile fin control, fuel and hydraulic pumps, radar and countermeasures systems. • 100V Rating for 28V Motors • 10 Amp Continuous Output Current • Complementary Four-Quadrant • • • • • • • Operation 3% Linearity Accuracy 5% Current Regulating Accuracy User-Programmable Compensation 10 kHz - 50 kHz PWM Frequency Operates as Current or Voltage Controller Self-Contained 3-Phase Motor Controller Built-in Current Limit 5.0V 10K 10K 10K HALL A HALL B HALL C +15V HALL SUPPLY OUTPUT HALL SUPPLY GND COMMAND OUT COMMAND IN + COMMAND IN - 39 HA 38 HB 37 40 +15V 41 33 VBUS+ 4,5,6 10K 31 10K 30 10K - 100 ENABLE +15V SUPPLY GROUND -15V SUPPLY PWM IN PWM OUT SYNC IN PWM GND ERROR AMP OUT ERROR AMP IN 17 CASE PWM LOGIC CIRCUITRY 10K 36 28 DRIVE B PHASE B DRIVE C PHASE C PHASE B 7,8,9 + 26 VEE 19 PHASE C 1,2,3 20 22 100 21 32 34 - 35 90.9 IS+ 10 100 ERROR AMPLIFIER CURRENT AMP + FIGURE 1. PWR-82520 BLOCK DIAGRAM © PHASE A 14,15,16 VDD + 27 + CURRENT MONITOR OUT PHASE A COMMAND BUFFER 29 5.0V CASE GND DRIVE A + 10K COMMAND GND COMMUTATION LOGIC HC 1994, 1999 Data Device Corporation Rsense VBUS– 11,12,13 TABLE 1. ABSOLUTE MAXIMUM RATINGS (TC = +25°C UNLESS OTHERWISE SPECIFIED) PARAMETER SYMBOL VALUE UNITS Bus Voltage VBUS+ 100 VDC +15V Supply VDD +17.5 VDC -15V Supply VEE -17.5 VDC Continuous Output Current IOC 10 A IPEAK 15 A Command input + Command input+ ±15 VDC Command input - Command input- ±15 VDC ENABLE HA, HB, HC 7.0 VDC SYNC ±15.0 VDC Peak Output Current Logic inputs Sync Input TABLE 2. PWR-82520 SPECIFICATIONS (Unless otherwise specified, VBUS = 28 VDC, VDD = +15V, VEE = -15V, TC = 25°C) PARAMETERS SYMBOL VALUE TEST CONDITIONS MIN OUTPUT Output Current Continuous Output Current Pulsed Current Limit Current Offset Output On-Resistance Output On-Resistance Output Conductor Resistance Load Inductance COMMAND IN+/Differential Input IOC (note 1) IOP ICL IOFFSET RON(note 2, 3) RON(note 2, 3) RC LMIN VDF = 0V +25°C +85°C +85°C 12.0 -0.3 UNITS TYP MAX 14.0 - 10 14 15.4 +0.3 0.040 0.055 A A A A Ω Ω Ω µH note 3 100 VDIF -10 +10 VDC COMMAND OUT Internal Voltage Clamp VCLMP -11.5 +11.5 VDC CURRENT COMMAND Transconductance ratio Non-Linearity G See FIGURE 9 0.95 -3.0 1.0 1.05 +3.0 A/V % 0.97 -0.1 -10 1.0 0 1.03 0.1 10 100 V/A VDC mA Ω +18 +28 +70 VDC 0.250 VDC CURRENT MONITOR AMP Current Monitor Gain Current Monitor Offset Output Current Output Resistance ROUT VBUS+ SUPPLY Nominal Operating Voltage VNOM VBUS- To PWM GND Voltage differential VDF = 0V VGNDDIF +15 VDC Voltage Current VS + I+ +14.25 +15.0 100 +15.75 150 VDC mA -15 VDC Voltage Current VS I- -15.75 -15.0 80 -14.25 150 VDC mA +20 V ns % SYNC (Note 2) Voltage Pulse Width Sync range as % of free-run frequency See FIGURE 7 ±7.5 130 0 Note: 1) IOC is average current as measured in motor winding 2) Guaranteed by design, not tested. 3) The maximum output conductor resistance and on-resistance of FETs at +85°C are: ΦAU = 0.20Ω, ΦAL = 0.16Ω, ΦBU = 0.08Ω, ΦBL = 0.08Ω, ΦCU = 0.08Ω, ΦCL = 0.20Ω 2 TABLE 2. PWR-82520 SPECIFICATIONS (CONTINUED) (Unless otherwise specified, VBUS = 28 VDC, VDD = +15V, VEE = -15V, TC = 25°C) VALUE PARAMETERS PWM IN +Peak -Peak Frequency Non -linearity Duty Cycle SYMBOL TEST CONDITIONS VP+ VPf LIN D CYCLE PWM OUT Free Run Frequency HALL POWER SUPPLY Max Current Draw HALL SIGNALS Logic 1 Logic 0 ENABLE INPUT Enabled Disabled ISOLATION CASE to PIN SWITCHING CHARACTERISTICS Upper drive Turn-on Rise Time Turn-off Fall Time Lower drive Turn-on Rise Time Turn-off Fall Time Diode Forward Voltage Drop TYP MAX 9.8 -10.2 10 -2 49 10.0 -10.0 50 10.2 -9.8 60 +2 51 V V KHz % % 45 50 55 KHz 50 mA IMDRW HA, HB, HC 3.5 — — 0.7 VDC VDC ENABLE — 3.5 0.7 — VDC 500 VDC HIPOT tr tf Td (on) Td (off) MΩ 10 125 200 ns ns 200 200 1.25 ns ns V 40 µs 20 µs 6 10 +175 +125 +150 °C/W °C/W °C °C °C 1.7(48) oz(gr) Ip = 4 A tr tf VF ID = 1A PROPAGATION DELAY THERMAL Thermal Resistance Junction - Case Case - Air Junction Temperature Case Operating Temperature Case Storage Temperature UNITS MIN From to From to Ip = 4A 0.7V on ENABLE 10% of VOUT 3.5V on ENABLE 90% of VOUT θJ-C θC-A TJ TC TCS -55 -65 WEIGHT over the operating temperature range and the total error due to all the factors such as offset, initial component accuracies etc. is maintained well below 5% of the rated output current. INTRODUCTION The PWR-82520 is high performance current control (torque loop) hybrid which use complementary four quadrant switching topology (See BASIC OPERATION) to provide linearity through zero current. The high Pulse Width Modulation (PWM) switching frequency makes it suitable for even low inductance motors. The PWR-82520 hybrid can accept single-ended or differential mode command signals. The current gain can be easily programmed to match the end user system requirements. With the compensation network externally wired, the hybrid can provide optimum control of a wide range of loads. The Hall sensor interface for current commutation has built-in decoder logic that separates illegal codes and ensures that there is no cross conduction. The hybrid also has a +15V supply output for powering the Hall sensors. The Hall sensor inputs are internally pulled up to +5V and they can be driven from open-collector outputs. The PWM frequency can be programmed externally by adding a capacitor from PWM OUT to PWM GND. In addition, multiple PWR-82520’s can be synchronized by using one device as a master and connecting its PWM OUT pin to the PWM IN of all the other slave devices in a system or by applying a SYNC pulse to pin 22. The PWR-82520 uses unique current sense technology and a non-inductive hybrid sense resistor which yields a highly linear current output over the wide military temperature range (see FIGURE 9). The output current non-linearity is better than 3% 3 The ENABLE input signal provides quick start and shutdown of the output power switches. In addition, built-in power sequence fault protection turns off the output in case of low power supply voltages. VBUS The hybrid features dual current limiting functions. The input command amplifier output is limited to 10.8V thus limiting the current under normal operation. In addition, there is a built in over current limit which trips at 14 Amps, protecting the hybrid as well as the load. ON PHASE A UPPER PHASE B OFF UPPER I PHASE B PHASE A - + BASIC OPERATION The PW-82520 utilizes a complimentary four-quadrant drive technique to control current in the load. The complimentary drive has the following advantages over the standard drive: OFF PHASE C PHASE A LOWER 1. Maximum holding torque and position accuracy 2. Linear current control through zero 3. No deadband at zero PHASE B LOWER ON Rsense The complementary drive design uses a 50% PWM duty cycle for a zero command signal. For a zero input command, a pair of MOSFETs are turned on in the drive, Phase A upper & Phase B lower as shown in FIGURE 2A, to supply current into the load for the first half of the PWM cycle. This is the same mode of operation for the standard four-quadrant drive as shown in FIGURE 3A/B. During the second half of the PWM cycle, a second pair of transistors are turned on, Phase A lower & Phase B upper as shown in FIGURE 2B, for the flyback current and to provide load current in the opposite direction. FIGURE 2A. COMPLEMENTARY FOUR-QUANDRANT DRIVE FIRST HALF OF PWM CYCLE This is normally the dead time for standard four-quadrant drive as shown in FIGURE 3B. The result is current flowing in both directions in the motor for each PWM cycle. The advantage this has over standard four-quadrant drive is that at 50% duty cycle, which corresponds to zero average current in the motor, holding torque is provided. The motor current at 50% duty cycle is simply the magnetizing current of the motor winding. VBUS Using the complimentary four-quadrant technique allows the motor direction to be defined by the duty cycle. Relative to a given switch pair i.e., Phase A upper and Phase B lower, a duty cycle greater than 50% will result in a clockwise rotation whereas a duty cycle less than 50% will result in a counter clockwise rotation. Therefore, with the use of average current mode control, direction can be controlled without the use of a direction bit and the current can be controlled through zero in a very precise and linear fashion. OFF PHASE A UPPER PHASE A The PW-82520 contains all the circuitry required to close an average current mode control loop around a complimentary fourquadrant drive. The PWR-82520 use of average current mode control simplifies the control loop by eliminating the need for slope compensation and eliminating the pole created by the motor inductance. These two effects are normally associated with 50% duty cycle limitations when implementing standard peak current mode control. PHASE A LOWER ON PHASE B + _ ON PHASE B UPPER I PHASE C PHASE B LOWER OFF Rsense FIGURE 2B. COMPLEMENTARY FOUR-QUADRANT DRIVE SECOND HALF OF PWM CYCLE 4 FUNCTIONAL AND PIN DESCRIPTIONS: VBUS ON PHASE A UPPER PHASE B OFF UPPER I PHASE B PHASE A - + OFF COMMAND IN+, COMMAND IN- (Pins 30 & 31) The command amplifier has a differential input that operates from a ±10 V analog current command. The differential input voltage may vary between ±10 VDC, maximum, corresponding to ±maximum voltage or current for the output. Either input (COMMAND IN + or COMMAND IN-) may be referenced to the command ground (Pin 29) and the other input varied from ±10 VDC to obtain full output. The COMMAND OUT signal is internally limited to approximately ±11.5 VDC; that is, inputs above or below ±11.5 VDC will be clamped to ±11.5 VDC. The input impedance of the Command Amplifier is 10K Ohms. PHASE C PHASE A LOWER PHASE B LOWER The PWR-82520 can be used either as a current or voltage mode controller. When the PWR-82520 is used as a torque amplifier (current mode) as shown in FIGURE 13, the transfer function of the command amplifier is 1.0 A/V. The input command signal is processed through the command buffer. The output of the buffer (COMMAND OUT) is summed with the current monitor output into the error amplifier. When external compensation is used on the error amp, as shown in FIGURE 6A, the response time can be adjusted to meet the application. ON Rsense When used in the voltage mode the Voltage Command uses the same differential input terminals to control the voltage applied to the motor (see FIGURE 12). The error amp directly varies the PWM duty cycle of the voltage applied to the motor phase. The transfer function in the voltage mode is 4.7% /V ±5% variation of the PWM duty cycle vs. input command. The duty cycle range of the output voltage is limited to approximately 5-95% in both current and voltage modes. FIGURE 3A. STANDARD FOUR QUANDRANT DRIVE FIRST HALF OF PWM CYCLE TRANSCONDUCTANCE RATIO AND OFFSET When the PWR-82520 is used in the Current Mode, the command inputs (COMMAND IN+ and COMMAND IN-) are designed such that ±10 VDC on either input, with the other input connected to Ground, will result in ±10 DC Average Amperes of current into the load. The DC current transfer ratio accuracy is ±5% of the rated output current. The initial output DC current offset with both COMMAND IN+ and COMMAND IN- tied to the Ground will be less than 100 mA when measured using a load of 0.5 mH and 1.0 Ohms at room ambient with standard current loop compensation (see FIGURE 6A). The winding phase current error shall be within the cumulative limits of the transconductance ratio error and the offset error. VBUS OFF PHASE A UPPER PHASE B OFF UPPER PHASE A PHASE B + _ I Flyback OFF PHASE A LOWER PHASE C PHASE B LOWER HALL A,B,C SIGNALS (Pins 37, 38 and 39) OFF These are logic signals from the motor Rotor Position Sensors (HA, HB, HC). They use a phasing convention referred to as 120 degree spacing; that is, the output of HA is in phase with motor back EMF voltage VAB, HB is in phase VBC, and HC is in phase with VCA. Logic “1” (or HIGH) is defined by an input greater than 3.5 VDC or an open circuit to the controller; Logic “0” (or LOW) is defined as any Hall voltage input less than 0.7 VDC. Internal to the PWR-82520 are 5K pull-up resistors tied to +5 VDC on each Hall input. Rsense The PWR-82520 will operate with Hall phasing of 60° or 120° electrical spacing. If 60° commutation is used, then the output of FIGURE 3B. STANDARD 4 QUANDRANT DRIVE SECOND HALF OF PWM CYCLE 5 HC must be inverted as shown in FIGURES 4 and 5. In FIGURE 4, the Hall sensor outputs are shown with the corresponding voltage they are in phase with. HALL-EFFECT SENSOR PHASING vs. MOTOR BACK EMF FOR CW ROTATION (120° Commutations) 300° 0° VAB 60° 120° VBC 180° 240° VCA 300° 360°/0° 60° BACK EMF OF MOTOR ROTATING CW Hall Input Signal Conditioning: When the motor is located more than two feet away from the PWR-82520 controller the Hall inputs require filtering from noise. It is recommended to use a 1 kΩ resistor in series with the Hall signal and a 2000 pF capacitor from the Hall input pin to the Hall supply ground pin as shown in FIGURE 12 and 13. CW COMPENSATION In Phase with VAB The PI regulator in the PWR-82520 can be tuned to a specific load for optimum performance. FIGURE 6A shows the standard current loop configuration and tuning components, and FIGURE 6B shows the frequency response for the PI regulator. By adjusting R1, R2 and C1, the amplifier can be tuned. The value of R1, C1 will vary, depending on the loop bandwidth requirement. HA In Phase with VBC HB HC In Phase with VCA In Phase with VAC (60˚) HC EXTERNAL PI REGULATOR FIGURE 4. HALL PHASING 10.0 K R1 4700 pF C1 1 MEG HA R7 120° 120° S N 34 R2B 10.0 K HC ERROR AMP INPUT 32 470 pf ERROR AMP OUT - R2A 10.0 K O + HB COMMAND OUT CURRENT 35 MONITOR OUT 33 REMOTE POSITION SENSOR (HALL) SPACING FOR 120 DEGREE COMMUTATION FIGURE 6A. STANDARD PI CURRENT LOOP 60° HA 120° 200 100 S N HC A, dB 0 60° -100 HC HB 180 θ, degree REMOTE POSITION SENSOR (HALL) SPACING FOR 60 DEGREE COMMUTATION 90 0 FIGURE 5. HALL SENSOR SPACING 10Hz 100Hz 1.0KHz 10KHz 100KHz 1.0MHz 10MHz 100MHz FREQUENCY FIGURE 6B. PI REGULATOR FREQUENCY RESPONSE 6 ENABLE (Pin 36) SYNC PERIOD This is a logic input to the controller that enables or disables the controller. In the disabled state, no voltage shall be applied to the motor phases. The disabled state occurs when the Enable input is greater than 3.5 VDC or is left open; to enable the controller, this input must be pulled to less than 0.7 VDC. The Enable input has a 10K pull-up resistor tied to +5 VDC. +7.5V VBUS+ (Pins 4, 5 and 6) 130ns -7.5V The VBUS+ supply is the power source for the motor phases and is nominally +28 VDC. The normal operating voltage may actually vary from +18 to +48 VDC with respect to Vbus-. The power stage MOSFETS in the hybrid have an absolute maximum VBUS+ Supply voltage rating of 100V. The recommended operating voltage must not exceed +70 VDC, and is subject to the safe operating curve within FIGURE 10. The user must supply sufficient external capacitance or circuitry to prevent the bus supply from exceeding +70 VDC at the hybrid power terminals under any conditions. FIGURE 7. SYNC INPUT SIGNAL PWM FREQUENCY The PWM frequency from the PWM OUT pin will free-run at a frequency of 50 kHz ±10 kHz. The user can adjust this frequency down to 10 kHz through the addition of an external capacitor. The PWM triangle wave generated internally is brought out to the PWM OUT pin. This output, or an external triangle waveform generated by the user, may be connected to PWM IN on the hybrid. The VBUS should be applied at least 50 ms after ±15 VDC to allow the internal analog circuitry to stabilize. If this is not possible, the hybrid must be powered up in the “disabled” mode. VBUS- (Pins 11, 12, and 13) WARNING: Never apply power to the hybrid without connecting either PWM OUT or an external triangular wave to PWM IN! Failure to do so may result in one or more outputs latching on. This is the high current ground return for VBUS+. This point must be externally connected to Ground for proper operation of the current loop. The voltage difference between Vbus- and the Ground connections must be less than 0.250 VDC including transients. PWM OUT (Pin 20) This is the output of the internally generated PWM triangle wave form. It is normally connected to PWM In. The frequency of this output may be lowered by connecting an NPO capacitor (Cext) between PWM OUT and PWM GND. The typical PWM frequency is determined by the following formula: GROUNDS SUPPLY GND (Pin 27): This is the return line for the ±15 VDC supplies. The phase current sensing technique of the PWR-82520 requires that VBUS- and Supply Ground be connected together externally (see VBUS- supply). PWM GND (Pin 21): This is used for the return side of the external PWM capacitor (Cext) when switching frequencies below 50 KHz are required. COMMAND GND (Pin 29): This is used when the command buffer is used single-ended and the COMMAND IN- or COMMAND IN+ are tied to COMMAND GND. HALL GND (Pin 41): This is used for the return of the +15V HALL supply and should be tied to SUPPLY GROUND. 16.5E-6 330 pF + CEXT pF CASE (Pin 17) This pin is internally connected to the hybrid case. In some applications the user may want to tie Pin 17 to Ground for EMI considerations. ±15 VDC (+15V Supply, Pin 28 / -15V Supply, Pin 26) PHASES A, B, C (Pin A 14-16, B 7-9, C 1-3) These inputs are used to power the small signal analog and digital circuitry of the hybrid. An internal +5 VDC supply is derived from the +15 VDC source. These inputs should not vary more than ±5%, maximum. The absolute maximum voltage ratings of these inputs are ±17.5 VDC. Reversal of the power supplies will result in destruction of the hybrid. These are the power drive outputs to the motor and switch between VBUS+ Input and VBUS- Input or become high impedance - see TABLE 3. +15 VDC HALL SUPPLY OUTPUT (Pin 40) SYNC IN (Pin 22) This output provides power to the Hall Sensors in the motor. Maximum current drawn from this supply by the user must not exceed 50 mA. The Sync pulse, as shown in FIGURE 7, can be used to synchronize the switching frequency up to 20% faster than the free running frequency of all th slave devices. 7 TABLE 3. COMMUTATION TRUTH TABLE INPUTS OUTPUTS VBUS+ ENABLE DIR ** HA HB HC PHASE A PHASE B PHASE C L CW 1 0 0 H L Z L CW 1 1 0 H Z L L CW 0 1 0 Z H L L CW 0 1 1 L H Z L CW 0 0 1 L Z H L CW 1 0 1 Z L H L CCW 1 0 1 Z H L HALL A L HALL B PHASE A PHASE B PHASE C VBUS- L CCW 0 1 0 H Z L CCW 0 1 1 H L Z L CCW 0 1 0 Z L H L CCW 1 1 0 L Z H L CCW 1 0 0 L H Z H — — — — Z Z Z HALL C HALL SUPPLY GND +15V HALL SUPPLY OUT 6 5 4 16 15 14 9 8 7 3 2 1 13 12 11 39 38 +28V PHASE A PHASE C GND +5V +5V 37 41 40 FIGURE 8. BRUSH MOTOR HOOK UP 1=Logic Voltage >3.5 VDC, 0=Logic voltage < 0.7 VDC ** DIR is based on the convention shown in Figure 4. Actual motor set up might be different. OUTPUT CURRENT Output current derating as a function of the hybrid case temperature is provided in FIGURE 10. The hybrid contains internal pulse by pulse current limit circuitry to limit the output current during fault conditions.(See TABLE 2) Current Limit accuracy is +10/-15%. CURRENT MONITOR OUT (Pin 35) This is a bipolar analog output voltage representative of motor current. The Current Monitor Output will have the same scaling as the Current Command input, 1.0 V/A. The output resistance will be less than 100 Ω. WARNING: The PWR-82520 does not have short circuit protection. The PWR-82520 must see a minimum of 100uH inductive load or enough line-to-line resistance to limit the output current to <10A at all times. Operation into a short or a condition that requires excessive output current will damage the hybrid. BRUSH MOTOR OPERATION The PWR-82520 can also be used as a brush motor controller for current or voltage control in an H-Bridge configuration. The PWR-82520 would be connected as shown in FIGURE 8. All other connections are as shown in either FIGURE 12 or 13 depending on current or voltage mode operation. The Hall inputs are wired per TABLE 4. A positive input command will result in positive current to the motor out of Phase A. THERMAL OPERATION It is recommended the PWR-82520 be mounted to a heat sink. This heat sink shall have the capacity to dissipate heat generated by the hybrid at all levels of current output, up to the peak limit, while maintaining the case temperature limit as per FIGURE 10. 10 TABLE 4. HALL INPUTS FOR H-BRIDGE CONTROLLER INPUT ENABLE COMMAND IN OUTPUT 5 Accuracy = ± 5% (of rated output) Current HA HB HC PH A PH B PH C L Positive 1 1 0 H Z L L Negative 1 1 0 L Z H H — 1 1 0 Z Z Z 0 (Amps) -5 -10 -10 -8 -6 -4 -2 0 2 4 Input Command (Volt), Inductive Load FIGURE 9. LINEARITY CURVE 8 6 8 10 11 Continuous Current (Amps) 10 9 8 28V, Cont. Cur. 7 6 42V, Cont. Cur. 5 4 70V, Cont. Cur. 3 2 1 0 -60 -20 -40 0 20 60 40 80 100 120 140 Case Temperature (°C) FIGURE 10. MOTOR CURRENT DRIVE 2. Switching Losses (Ps) PWR-82520 POWER DISSIPATION (SEE FIGURE 11) Ps = [ Vcc ( IOA (ts1) + IOB (ts2) ) fo] / 2 There are two major contributors to power dissipation in the motor driver: conduction losses and switching losses. Ps = [ 28 V ( 3 A (125 ns) + 7 A (200 ns) ) 50 kHz] / 2 VBUS = +28 V (Bus Voltage) Ps = 1.24 Watts IoA = 3 A, IOB = 7 A (see FIGURE 11) TRANSISTOR POWER DISSIPATION ( PQ ) ton = 36 µs, T = 40 µs (period) (see FIGURE 11) PQ = PT + Ps Ron = 0.055 Ω (on-resistance, see TABLE 2) PQ = 1.30 + 1.24 = 2.54 Watts Rc = 0.133 Ω (conductor resistance, see TABLE 2,) OUTPUT CONDUCTOR DISSIPATION PC = (Imotor rms)2 x (Rc) ts1 = 125 ns, ts2 = 200 ns (see FIGURE 11) fo = 50 kHz (switching frequency) PC = (4.87)2 x (0.133) PC = 3.15 Watts 1. Transistor Conduction Losses (PC) PT = (Imotor rms)2 x (Ron) Imotor rms = TRANSISTOR POWER DISSIPATION FOR CONTINUOUS COMMUTATION 2 PQC = PQ (0.33) (IOBIOA + (IOB - IOA) )( ton ) 3 T PQC = (2.54) X (0.33) PQC = 0.84 Watts Imotor rms = (7 * 3 + (7 - 3)2)( 36 40 3 ) TOTAL HYBRID POWER DISSIPATION PTOTAL = (PQ + PC) x 2 PT = (4.87)2 x (0.055) PTOTAL = (2.54 +3.15) x 2 PT = 1.30 Watts PTOTAL = 11.38 Watts ton VBUS IOB IOA IO ts1 t s2 FIGURE 11. OUTPUT CHARACTERISTICS 9 OPTIONAL 17 19 20 Cext -15V 21 26 + 27 GND 28 + 29 +15V 30 COMMAND SIGNAL 31 32 R1 R5 CURRENT MONITOR OUT 10K 10K 33 34 35 36 ENABLE VBUS+ CASE GND PWM IN PWR-82520 PHASE A PWM OUT PWM GND PHASE B -15V SUPPLY SUPPLY GND PHASE C +15V SUPPLY COMMAND GND COMMAND IN COMMAND IN + VBUS- - - + + ERROR AMP OUT HALL A HALL B 470 pF COMMAND OUT 6 5 4 16 15 14 9 8 7 3 2 1 13 12 11 HALL C - 39 38 +28V PHASE A PHASE B PHASE C GND R4 HALL A R3 1K HALL B R2 1K 37 HALL C 1K + ERROR AMP INPUT MOTOR BLDC CURRENT MONITOR OUT HALL SUPPLY GND 41 C4 2000pF C3 2000pF C5 2000pF HALL SUPPLY GND ENABLE +15V HALL SUPPLY OUT 40 +15V HALL SUPPLY OUTPUT FIGURE 12. VOLTAGE CONTROL HOOK-UP OPTIONAL 17 19 20 Cext -15V 21 26 + 27 GND 28 + 29 +15V 30 31 COMMAND SIGNAL 32 R2A C1 R1 4700pF 10K 10K R7 1MEG ENABLE R2B 10K 33 34 35 36 VBUS+ CASE GND PWM IN PWR-82520 PHASE A PWM OUT PWM GND PHASE B -15V SUPPLY SUPPLY GND PHASE C +15V SUPPLY COMMAND GND COMMAND IN COMMAND IN + VBUS- - - + + ERROR AMP OUT COMMAND OUT ERROR AMP INPUT 6 5 4 16 15 14 9 8 7 3 2 1 13 12 11 HALL A HALL B 470 pF HALL C - 39 38 +28V PHASE A PHASE B PHASE C GND R4 1K HALL A R3 1K 37 MOTOR BLDC HALL B R2 HALL C 1K + CURRENT MONITOR OUT HALL SUPPLY GND 41 C4 2000pF ENABLE +15V HALL SUPPLY OUT 40 FIGURE 13. TORQUE CONTROL HOOK-UP 10 C3 2000pF C5 2000pF HALL SUPPLY GND +15V HALL SUPPLY OUTPUT TABLE 5. PIN ASSIGNMENTS PIN FUNCTION PIN FUNCTION 1 PHASE C 41 HALL SUPPLY GND 2 PHASE C 40 +15V HALL SUPPLY OUTPUT 3 PHASE C 39 HA 4 VBUS + 38 HB 5 VBUS + 37 HC 6 VBUS + 36 ENABLE 7 PHASE B 35 CURRENT MONITOR OUTPUT 8 PHASE B 34 ERROR AMP INPUT 9 PHASE B 33 COMMAND OUT 10 IS+ 32 ERROR AMP OUT 11 VBUS - 31 COMMAND IN + 12 VBUS - 30 COMMAND IN - 13 VBUS - 29 COMMAND GND 14 PHASE A 28 +15V SUPPLY 15 PHASE A 27 SUPPLY GND 16 PHASE A 26 -15V SUPPLY — 25 N/C — 24 N/C — 23 N/C — 22 SYNC — 21 PWM GND — 20 PWM OUT — 19 PWM IN — 18 N/C — 17 CASE GND 29.21 FIGURE 14. MECHANICAL OUTLINE Note: 1. N/C pins have internal connections for factory test purposes. 11 ORDERING INFORMATION PWR-82520-XX0X Supplemental Process Requirements: S = Pre-Cap Source Inspection L = Pull Test Q = Pull Test and Pre-Cap Inspection K = One Lot Date Code W = One Lot Date Code and PreCap Source Y = One Lot Date Code and 100% Pull Test Z = One Lot Date Code, PreCap Source and 100% Pull Test Blank = None of the Above Process Requirements: 0 = Standard DDC Processing, no Burn-In (See table below.) 1 = MIL-PRF-38534 Compliant 2 = B* 3 = MIL-PRF-38534 Compliant with PIND Testing 4 = MIL-PRF-38534 Compliant with Solder Dip 5 = MIL-PRF-38534 Compliant with PIND Testing and Solder Dip 6 = B* with PIND Testing 7 = B* with Solder Dip 8 = B* with PIND Testing and Solder Dip 9 = Standard DDC Processing with Solder Dip, no Burn-In (See table below.) Temperature Grade/Data Requirements: 1 = -55°C to +125°C 2 = -40°C to +85°C 3 = 0°C to +70°C 4 = -55°C to +125°C with Variables Test Data 5 = -40°C to +85°C with Variables Test Data 8 = 0°C to +70°C with Variables Test Data *Standard DDC Processing with burn-in and full temperature test — see table below. STANDARD DDC PROCESSING MIL-STD-883 TEST METHOD(S) CONDITION(S) INSPECTION 2009, 2010, 2017, and 2032 — SEAL 1014 A and C TEMPERATURE CYCLE 1010 C CONSTANT ACCELERATION 2001 A BURN-IN 1015, Table 1 — The information in this data sheet is believed to be accurate; however, no responsibility is assumed by Data Device Corporation for its use, and no license or rights are granted by implication or otherwise in connection therewith. Specifications are subject to change without notice. 105 Wilbur Place, Bohemia, New York 11716-2482 For Technical Support - 1-800-DDC-5757 ext. 7420 Headquarters - Tel: (631) 567-5600 ext. 7420, Fax: (631) 567-7358 Southeast - Tel: (703) 450-7900, Fax: (703) 450-6610 West Coast - Tel: (714) 895-9777, Fax: (714) 895-4988 Europe - Tel: +44-(0)1635-811140, Fax: +44-(0)1635-32264 Asia/Pacific - Tel: +81-(0)3-3814-7688, Fax: +81-(0)3-3814-7689 World Wide Web - http://www.ddc-web.com PRINTED IN THE U.S.A. C-12/99-1M 12