Order this document by LM311/D The ability to operate from a single power supply of 5.0 V to 30 V or ±15 V split supplies, as commonly used with operational amplifiers, makes the LM211/LM311 a truly versatile comparator. Moreover, the inputs of the device can be isolated from system ground while the output can drive loads referenced either to ground, the VCC or the VEE supply. This flexibility makes it possible to drive DTL, RTL, TTL, or MOS logic. The output can also switch voltages to 50 V at currents to 50 mA. Thus the LM211/LM311 can be used to drive relays, lamps or solenoids. HIGH PERFORMANCE VOLTAGE COMPARATORS SEMICONDUCTOR TECHNICAL DATA 8 Typical Comparator Design Configurations Split Power Supply with Offset Balance VCC 2 Inputs Inputs 6 + 3 8 7 Output 3 – 8 + RL 5.0 k 5 2 N SUFFIX PLASTIC PACKAGE CASE 626 Single Supply VCC 3.0 k 1 – VEE RL 7 Output 1 8 4 1 1 D SUFFIX PLASTIC PACKAGE CASE 751 (SO–8) 4 VEE Ground–Referred Load Load Referred to Negative Supply VCC VCC 2 2 8 + 7 Inputs Inputs 3 – 8 – 1 3 Output 1 4 + 7 Output 4 RL PIN CONNECTIONS RL Gnd VEE Input polarity is reversed when Gnd pin is used as an output. VEE Input polarity is reversed when Gnd pin is used as an output. 2 Inputs + 3 – 2 8 7 Inputs RL – 3 4 Strobe Capability VCC VCC 2 + Inputs VEE Load Referred to Positive Supply 1 Output 1 4 VEE 3 8 + 7 VCC 7 Output 6 Balance/Strobe 5 Balance (Top View) RL Output 1 – 4 VEE ORDERING INFORMATION 6 TTL Strobe 1.0 k Operating Temperature Range Package LM211D TA = 25° to +85°C SO–8 LM311D LM311N TA = 0° to +70°C SO–8 Plastic DIP Device Motorola, Inc. 1996 MOTOROLA ANALOG IC DEVICE DATA 8 Rev 5 1 LM311 LM211 MAXIMUM RATINGS (TA = +25°C, unless otherwise noted.) Rating Total Supply Voltage Output to Negative Supply Voltage Ground to Negative Supply Voltage Input Differential Voltage Input Voltage (Note 2) Voltage at Strobe Pin Power Dissipation and Thermal Characteristics Plastic DIP Derate Above TA = +25°C Operating Ambient Temperature Range Operating Junction Temperature Storage Temperature Range Symbol LM211 LM311 Unit VCC +VEE VO –VEE 36 36 Vdc 50 40 Vdc VEE VID Vin – 30 30 Vdc ±30 ±30 Vdc ±15 ±15 Vdc VCC to VCC–5 VCC to VCC–5 Vdc PD 1/θJA TA 625 5.0 –25 to +85 TJ(max) Tstg mW mW/°C 0 to +70 °C +150 +150 °C –65 to +150 –65 to +150 °C ELECTRICAL CHARACTERISTICS (VCC = +15 V, VEE = –15 V, TA = 25°C, unless otherwise noted [Note 1].) LM211 Ch Characteristic i i S b l Symbol LM311 Min Typ Max Min Typ Max – – 0.7 – 3.0 4.0 – – 2.0 – 7.5 10 U i Unit Input Offset Voltage (Note 3) RS ≤ 50 kΩ, TA = +25°C RS ≤ 50 kΩ, Tlow ≤ TA ≤ Thigh* VIO Input Offset Current (Note 3) TA = +25°C Tlow ≤ TA ≤ Thigh* IIO – – 1.7 – 10 20 – – 1.7 – 50 70 nA Input Bias Current TA = +25°C Tlow ≤ TA ≤ Thigh* IIB – – 45 – 100 150 – – 45 – 250 300 nA Voltage Gain AV 40 200 – 40 200 – V/mV – 200 – – 200 – ns – – 0.75 – 1.5 – – – – 0.75 – 1.5 – – 0.23 – 0.4 – – – – 0.23 – 0.4 – 3.0 – – 3.0 – mA – – – 0.2 – 0.1 10 – 0.5 – – – – 0.2 – – 50 – nA nA µA VICR –14.5 –14.7 to 13.8 +13.0 –14.5 –14.7 to 13.8 +13.0 V Positive Supply Current ICC – +2.4 +6.0 – +2.4 +7.5 mA Negative Supply Current IEE – –1.3 –5.0 – –1.3 –5.0 mA Response Time (Note 4) Saturation Voltage VID ≤ –5.0 mV, IO = 50 mA, TA = 25°C VID ≤–10 mV, IO = 50 mA, TA = 25°C VCC ≥ 4.5 V, VEE = 0, Tlow ≤ TA ≤ Thigh* VID 6≤6.0 mV, Isink ≤ 8.0 mA VID 6≤10 mV, Isink ≤ 8.0 mA Strobe ”On” Current (Note 5) VOL IS Output Leakage Current VID ≥ 5.0 mV, VO= 35 V, TA = 25°C, Istrobe= 3.0 mA VID ≥ 10 mV, VO= 35 V, TA = 25°C, Istrobe= 3.0 mA VID ≥ 5.0 mV, VO= 35 V, Tlow ≤ TA ≤ Thigh* Input Voltage Range (Tlow ≤ TA ≤ Thigh*) mV V * Tlow = –25°C for LM211 Thigh = +85°C for LM211 = 0°C for LM311 = +70°C for LM311 NOTES: 1. Offset voltage, offset current and bias current specifications apply for a supply voltage range from a single 5.0 V supply up to ±15 V supplies. 2. This rating applies for ±15 V supplies. The positive input voltage limit is 30 V above the negative supply. The negative input voltage limit is equal to the negative supply voltage or 30 V below the positive supply, whichever is less. 3. The offset voltages and offset currents given are the maximum values required to drive the output within a volt of either supply with a 1.0 mA load. Thus, these parameters define an error band and take into account the ”worst case” effects of voltage gain and input impedance. 4. The response time specified is for a 100 mV input step with 5.0 mV overdrive. 5. Do not short the strobe pin to ground; it should be current driven at 3.0 mA to 5.0 mA. 2 MOTOROLA ANALOG IC DEVICE DATA LM311 LM211 Figure 1. Circuit Schematic 8 VCC Balance Balance/Strobe 5 1.3 k 300 6 300 1.3 k 800 800 3.0 k 100 5.0 k 3.7 k 3.7 k 7 200 300 Output 900 250 600 800 1.3 k 2 1 Inputs 730 3 1.3 k 340 Gnd 5.4 k 4 VEE Figure 2. Input Bias Current versus Temperature Figure 3. Input Offset Current versus Temperature 5.0 VCC = +15 V VEE = –15 V 120 I IO , INPUT OFFSET CURRENT (nA) I IB , INPUT BIAS CURRENT (nA) 140 Pins 5 & 6 Tied to VCC 100 Normal 80 40 0 –55 –25 0 25 50 75 100 4.0 Pins 5 & 6 Tied to VCC 3.0 2.0 1.0 0 –55 125 VCC = +15 V VEE = –15 V Normal –25 0 25 50 75 TA, TEMPERATURE (°C) TA, TEMPERATURE (°C) Figure 4. Input Bias Current versus Differential Input Voltage Figure 5. Common Mode Limits versus Temperature 100 125 100 125 VCC = +15 V VEE = –15 V TA = +25°C 120 COMMON MODE LIMITS (V) I IB , INPUT BIAS CURRENT (nA) 140 100 80 60 40 20 0 –16 –12 –8.0 –4.0 0 4.0 8.0 DIFFERENTIAL INPUT VOLTAGE (V) MOTOROLA ANALOG IC DEVICE DATA 12 16 VCC –0.5 Referred to Supply Voltages –1.0 –1.5 0.4 0.2 VEE –55 –25 0 25 50 75 TA, TEMPERATURE (°C) 3 LM311 LM211 VO , OUTPUT VOLTAGE (V) 5.0 4.0 3.0 2.0 1.0 0 Vin ,INPUT VOLTAGE (mV) +5.0 V 20 mV * ) Vin 2.0 mV 500 Ω VO VCC = +15 V VEE = –15 V TA = +25°C 100 50 0 0 0.1 0.2 0.3 0.4 tTLH, RESPONSE TIME (µs) 0.5 0.6 15 10 5.0 0 –5.0 –10 –15 20 mV 5.0 mV Vin VO , OUTPUT VOLTAGE (V) Figure 8. Response Time for Various Input Overdrives VCC * ) VO 2.0 k Vin ,INPUT VOLTAGE (mV) VO , OUTPUT VOLTAGE (V) Vin ,INPUT VOLTAGE (mV) 5.0 mV Vin ,INPUT VOLTAGE (mV) VO , OUTPUT VOLTAGE (V) Figure 6. Response Time for Various Input Overdrives VEE 2.0 mV 0 –50 VCC = +15 V VEE = –15 V TA = +25°C –100 0 1.0 2.0 tTLH, RESPONSE TIME (µs) Figure 7. Response Time for Various Input Overdrives 5.0 mV 5.0 4.0 3.0 2.0 1.0 0 2.0 mV VCC = +15 V VEE = –15 V TA = +25°C 0 –50 –100 0 0.60 75 0.45 Short Circuit Current 50 0.30 25 0.15 0 0 5.0 10 VO, OUTPUT VOLTAGE (V) 4 0 15 V , SATURATION VOLTAGE (V) OL 0.75 Power Dissipation 0.1 0.2 0.3 0.4 tTHL, RESPONSE TIME (µs) 0.5 0.6 Figure 9. Response Time for Various Input Overdrives VCC 15 10 5.0 0 –5.0 –10 –15 5.0 mV 2.0 mV Vin * ) VO 2.0 k VEE 20 mV VCC = +15 V VEE = –15 V TA = +25°C 100 50 0 0 1.0 tTHL, RESPONSE TIME (µs) 2.0 0.90 PD , POWER DISSIPATION (W) OUTPUT SHORT CIRCUIT CURRENT (mA) 0.90 100 VO Figure 11. Output Saturation Voltage versus Output Current TA = +25°C 125 500 Ω 20 mV Figure 10. Output Short Circuit Current Characteristics and Power Dissipation 150 +5.0 V * ) Vin 0.75 0.60 TA = –55°C 0.45 0.30 TA = +25°C TA = +125°C 0.15 0 0 8.0 16 24 32 40 48 56 IO, OUTPUT CURRENT (mA) MOTOROLA ANALOG IC DEVICE DATA LM311 LM211 Figure 13. Power Supply Current versus Supply Voltage 3.6 100 VCC = +15 V VEE = –15 V POWER SUPPLY CURRENT (mA) OUTPUT LEAKAGE CURRENT (mA) Figure 12. Output Leakage Current versus Temperature 10 1.0 Output VO = +50 V (LM11/211 only) 0.1 0.01 25 TA = +25°C 3.0 Positive Supply – Output Low 2.4 1.8 Positive and Negative Power Supply – Output H igh 1.2 0.6 0 45 65 85 105 125 0 5.0 TA, TEMPERATURE (°C) 10 15 20 25 30 VCC–VEE, POWER SUPPLY VOLTAGE (V) Figure 14. Power Supply Current versus Temperature SUPPLY CURRENT (mA) 3.0 2.6 VCC = +15 V VEE = –15 V Postive Supply – Output Low 2.2 1.8 Positive and Negative Supply – Output High 1.4 1.0 –55 –25 0 25 50 75 TA, TEMPERATURE (°C) 100 125 APPLICATIONS INFORMATION Figure 15. Improved Method of Adding Hysteresis Without Applying Positive Feedback to the Inputs Figure 16. Conventional Technique for Adding Hysteresis +15 V +15 V 3.0 k 3.0 k 82 4.7 k 33 k 5.0 k C1 0.1 µF 8 2 Input + R1 C2 4.7 k 0.002 6 µF 8 Input 5 LM311 1 – R2 3 5.0 k 0.1 µF 7 Output 100 0.1 µF –15 V MOTOROLA ANALOG IC DEVICE DATA 6 C1 + R1 C2 100 R2 4 3 5 LM311 1 – 2 7 Output 4 1.0 M 0.1 µF –15 V 510 k 5 LM311 LM211 TECHNIQUES FOR AVOIDING OSCILLATIONS IN COMPARATOR APPLICATIONS When a high speed comparator such as the LM211 is used with high speed input signals and low source impedances, the output response will normally be fast and stable, providing the power supplies have been bypassed (with 0.1 µF disc capacitors), and that the output signal is routed well away from the inputs (Pins 2 and 3) and also away from Pins 5 and 6. However, when the input signal is a voltage ramp or a slow sine wave, or if the signal source impedance is high (1.0 kΩ to 100 kΩ), the comparator may burst into oscillation near the crossing–point. This is due to the high gain and wide bandwidth of comparators like the LM211 series. To avoid oscillation or instability in such a usage, several precautions are recommended, as shown in Figure 15. The trim pins (Pins 5 and 6) act as unwanted auxiliary inputs. If these pins are not connected to a trim–pot, they should be shorted together. If they are connected to a trim–pot, a 0.01 µF capacitor (C1) between Pins 5 and 6 will minimize the susceptibility to AC coupling. A smaller capacitor is used if Pin 5 is used for positive feedback as in Figure 15. For the fastest response time, tie both balance pins to VCC. Certain sources will produce a cleaner comparator output waveform if a 100 pF to 1000 pF capacitor (C2) is connected directly across the input pins. When the signal source is applied through a resistive network, R1, it is usually advantageous to choose R2 of the same value, both for DC and for dynamic (AC) considerations. Carbon, tin–oxide, and metal–film resistors have all been used with good results in comparator input circuitry, but inductive wirewound resistors should be avoided. When comparator circuits use input resistors (e.g., summing resistors), their value and placement are particularly important. In all cases the body of the resistor should be close to the device or socket. In other words, there should be a very short lead length or printed–circuit foil run between comparator and resistor to radiate or pick up signals. The same applies to capacitors, pots, etc. For example, if R1 = 10 kΩ, as little as 5 inches of lead between the resistors and the input pins can result in oscillations that are very hard to dampen. Twisting these input leads tightly is the best alternative to placing resistors close to the comparator. Figure 17. Zero–Crossing Detector Driving CMOS Logic Since feedback to almost any pin of a comparator can result in oscillation, the printed–circuit layout should be engineered thoughtfully. Preferably there should be a groundplane under the LM211 circuitry (e.g., one side of a double layer printed circuit board). Ground, positive supply or negative supply foil should extend between the output and the inputs to act as a guard. The foil connections for the inputs should be as small and compact as possible, and should be essentially surrounded by ground foil on all sides to guard against capacitive coupling from any fast high–level signals (such as the output). If Pins 5 and 6 are not used, they should be shorted together. If they are connected to a trim–pot, the trim–pot should be located no more than a few inches away from the LM211, and a 0.01 µF capacitor should be installed across Pins 5 and 6. If this capacitor cannot be used, a shielding printed–circuit foil may be advisable between Pins 6 and 7. The power supply bypass capacitors should be located within a couple inches of the LM211. A standard procedure is to add hysteresis to a comparator to prevent oscillation, and to avoid excessive noise on the output. In the circuit of Figure 16, the feedback resistor of 510 kΩ from the output to the positive input will cause about 3.0 mV of hysteresis. However, if R2 is larger than 100 Ω, such as 50 kΩ, it would not be practical to simply increase the value of the positive feedback resistor proportionally above 510 kΩ to maintain the same amount of hysteresis. When both inputs of the LM211 are connected to active signals, or if a high–impedance signal is driving the positive input of the LM211 so that positive feedback would be disruptive, the circuit of Figure 15 is ideal. The positive feedback is applied to Pin 5 (one of the offset adjustment pins). This will be sufficient to cause 1.0 mV to 2.0 mV hysteresis and sharp transitions with input triangle waves from a few Hz to hundreds of kHz. The positive–feedback signal across the 82 Ω resistor swings 240 mV below the positive supply. This signal is centered around the nominal voltage at Pin 5, so this feedback does not add to the offset voltage of the comparator. As much as 8.0 mV of offset voltage can be trimmed out, using the 5.0 kΩ pot and 3.0 kΩ resistor as shown. Figure 18. Relay Driver with Strobe Capability VEE VCC = +15 V Balance Adjust Balance Input Inputs VEE 3.0 k 10 k 5.0 k + LM311 VCC Gnd VEE = –15 V Inputs Output to CMOS Logic VCC2 VCC Output + VEE 6 VCC1 LM311 Gnd Balance/Strobe 2N2222 Q1 or Equiv 1.0 k TTL Strobe *D1 *Zener Diode D1 protects the comparator from inductive kickback and voltage transients on the VCC2 supply line. MOTOROLA ANALOG IC DEVICE DATA LM311 LM211 OUTLINE DIMENSIONS N SUFFIX PLASTIC PACKAGE CASE 626–05 ISSUE K 8 NOTES: 1. DIMENSION L TO CENTER OF LEAD WHEN FORMED PARALLEL. 2. PACKAGE CONTOUR OPTIONAL (ROUND OR SQUARE CORNERS). 3. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 5 –B– 1 MILLIMETERS MIN MAX 9.40 10.16 6.10 6.60 3.94 4.45 0.38 0.51 1.02 1.78 2.54 BSC 0.76 1.27 0.20 0.30 2.92 3.43 7.62 BSC ––– 10_ 0.76 1.01 4 DIM A B C D F G H J K L M N F –A– NOTE 2 L C J –T– INCHES MIN MAX 0.370 0.400 0.240 0.260 0.155 0.175 0.015 0.020 0.040 0.070 0.100 BSC 0.030 0.050 0.008 0.012 0.115 0.135 0.300 BSC ––– 10_ 0.030 0.040 N SEATING PLANE D M K G H 0.13 (0.005) M T A M B M D SUFFIX PLASTIC PACKAGE CASE 751–05 (SO–8) ISSUE R D A NOTES: 1. DIMENSIONING AND TOLERANCING PER ASME Y14.5M, 1994. 2. DIMENSIONS ARE IN MILLIMETERS. 3. DIMENSION D AND E DO NOT INCLUDE MOLD PROTRUSION. 4. MAXIMUM MOLD PROTRUSION 0.15 PER SIDE. 5. DIMENSION B DOES NOT INCLUDE MOLD PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.127 TOTAL IN EXCESS OF THE B DIMENSION AT MAXIMUM MATERIAL CONDITION. C 8 5 0.25 H E M B M 1 4 h B e X 45 _ q A C SEATING PLANE L 0.10 A1 B 0.25 M C B S A S MOTOROLA ANALOG IC DEVICE DATA DIM A A1 B C D E e H h L q MILLIMETERS MIN MAX 1.35 1.75 0.10 0.25 0.35 0.49 0.18 0.25 4.80 5.00 3.80 4.00 1.27 BSC 5.80 6.20 0.25 0.50 0.40 1.25 0_ 7_ 7 LM311 LM211 Motorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation consequential or incidental damages. “Typical” parameters which may be provided in Motorola data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. 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Box 20912; Phoenix, Arizona 85036. 1–800–441–2447 or 602–303–5454 JAPAN: Nippon Motorola Ltd.; Tatsumi–SPD–JLDC, 6F Seibu–Butsuryu–Center, 3–14–2 Tatsumi Koto–Ku, Tokyo 135, Japan. 03–81–3521–8315 MFAX: [email protected] – TOUCHTONE 602–244–6609 INTERNET: http://Design–NET.com ASIA/PACIFIC: Motorola Semiconductors H.K. Ltd.; 8B Tai Ping Industrial Park, 51 Ting Kok Road, Tai Po, N.T., Hong Kong. 852–26629298 8 ◊ *LM311/D* MOTOROLA ANALOG IC DEVICE DATA LM311/D