LM211, LM311 Highly Flexible Voltage Comparators The ability to operate from a single power supply of 5.0 V to 30 V or ±15 V split supplies, as commonly used with operational amplifiers, makes the LM211/LM311 a truly versatile comparator. Moreover, the inputs of the device can be isolated from system ground while the output can drive loads referenced either to ground, the VCC or the VEE supply. This flexibility makes it possible to drive DTL, RTL, TTL, or MOS logic. The output can also switch voltages to 50 V at currents to 50 mA. Thus the LM211/LM311 can be used to drive relays, lamps or solenoids. VCC 3.0k http://onsemi.com MARKING DIAGRAMS 8 PDIP–8 N SUFFIX CASE 626 8 1 VCC RL 5.0k 5 2 6 + Inputs 3 8 7 – 2 Inputs Output 3 1 8 + - VEE 4 VEE Split Power Supply with Offset Balance Inputs 3 – 2 7 Inputs Output 1 4 8 1 3 + 8 – 1 4 RL VEE x = 2 or 3 A = Assembly Location WL, L = Wafer Lot YY, Y = Year WW, W = Work Week 7 PIN CONNECTIONS Output RL Gnd VEE Input polarity is reversed when Gnd pin is used as an output. Input polarity is reversed when Gnd pin is used as an output. Ground–Referred Load LMx11 ALYW 1 VCC 8 + Output SO–8 D SUFFIX CASE 751 Single Supply VCC 2 8 1 4 1 RL 7 LM311N AWL YYWW Inputs 1 2 3 VEE Load Referred to Negative Supply + – 4 8 VCC 7 Output 6 Balance/Strobe 5 Balance (Top View) VCC 2 VCC 2 Inputs + 3 – Inputs 8 7 RL Output 1 4 VEE Load Referred to Positive Supply 3 8 + – 4 VEE 6 7 ORDERING INFORMATION RL Output 1 TTL Strobe 1.0k Strobe Capability Device Package Shipping LM211D SO–8 98 Units/Rail LM211DR2 SO–8 2500 Tape & Reel LM311D SO–8 98 Units/Rail LM311DR2 SO–8 2500 Tape & Reel PDIP–8 50 Units/Rail LM311N Figure 1. Typical Comparator Design Configurations Semiconductor Components Industries, LLC, 2001 February, 2001 – Rev. 0 1 Publication Order Number: LM211/D LM211, LM311 MAXIMUM RATINGS (TA = +25°C, unless otherwise noted.) Symbol LM211 LM311 Unit VCC +VEE 36 36 Vdc Output to Negative Supply Voltage VO –VEE 50 40 Vdc Ground to Negative Supply Voltage VEE 30 30 Vdc Input Differential Voltage VID ±30 ±30 Vdc Input Voltage (Note 2.) Vin ±15 ±15 Vdc – VCC to VCC–5 VCC to VCC–5 Vdc Rating Total Supply Voltage Voltage at Strobe Pin Power Dissipation and Thermal Characteristics Plastic DIP Derate Above TA = +25°C PD 1/θJA Operating Ambient Temperature Range 625 5.0 TA Operating Junction Temperature Storage Temperature Range –25 to +85 mW mW/°C 0 to +70 °C TJ(max) +150 +150 °C Tstg –65 to +150 –65 to +150 °C ELECTRICAL CHARACTERISTICS (VCC = +15 V, VEE = –15 V, TA = 25°C, unless otherwise noted [Note 1.]) LM211 Characteristic Symbol LM311 Min Typ Max Min Typ Max – – 0.7 – 3.0 4.0 – – 2.0 – 7.5 10 Unit Input Offset Voltage (Note 3.) RS ≤ 50 kΩ, TA = +25°C RS ≤ 50 kΩ, Tlow ≤ TA ≤ Thigh* VIO mV Input Offset Current (Note 3.) TA = +25°C Tlow ≤ TA ≤ Thigh* IIO – – 1.7 – 10 20 – – 1.7 – 50 70 nA Input Bias Current TA = +25°C Tlow ≤ TA ≤ Thigh* IIB – – 45 – 100 150 – – 45 – 250 300 nA Voltage Gain AV 40 200 – 40 200 – V/mV – 200 – – 200 – ns – – 0.75 – 1.5 – – – – 0.75 – 1.5 – – 0.23 – 0.4 – – – – 0.23 – 0.4 – 3.0 – – 3.0 – mA – – – 0.2 – 0.1 10 – 0.5 – – – – 0.2 – – 50 – nA nA µA VICR –14.5 –14.7 to 13.8 +13.0 –14.5 –14.7 to 13.8 +13.0 V Positive Supply Current ICC – +2.4 +6.0 – +2.4 +7.5 mA Negative Supply Current IEE – –1.3 –5.0 – –1.3 –5.0 mA Response Time (Note 4.) Saturation Voltage VID ≤ –5.0 mV, IO = 50 mA, TA = 25°C VID ≤–10 mV, IO = 50 mA, TA = 25°C VCC ≥ 4.5 V, VEE = 0, Tlow ≤ TA ≤ Thigh* VID ≤6.0 mV, Isink ≤ 8.0 mA VID ≤10 mV, Isink ≤ 8.0 mA Strobe ”On” Current (Note 5.) VOL V IS Output Leakage Current VID ≥ 5.0 mV, VO= 35 V, TA = 25°C, Istrobe= 3.0 mA VID ≥ 10 mV, VO= 35 V, TA = 25°C, Istrobe= 3.0 mA VID ≥ 5.0 mV, VO= 35 V, Tlow ≤ TA ≤ Thigh* Input Voltage Range (Tlow ≤ TA ≤ Thigh*) * LM211: Tlow = –25°C, Thigh = +85°C LM311: Tlow = 0°C, Thigh = +70°C 1. Offset voltage, offset current and bias current specifications apply for a supply voltage range from a single 5.0 V supply up to ±15 V supplies. 2. This rating applies for ±15 V supplies. The positive input voltage limit is 30 V above the negative supply. The negative input voltage limit is equal to the negative supply voltage or 30 V below the positive supply, whichever is less. 3. The offset voltages and offset currents given are the maximum values required to drive the output within a volt of either supply with a 1.0 mA load. Thus, these parameters define an error band and take into account the “worst case” effects of voltage gain and input impedance. 4. The response time specified is for a 100 mV input step with 5.0 mV overdrive. 5. Do not short the strobe pin to ground; it should be current driven at 3.0 mA to 5.0 mA. http://onsemi.com 2 LM211, LM311 8 Balance Balance/Strobe 5 1.3k 300 6 300 1.3k 800 800 3.0k 100 5.0k 3.7k 3.7k VCC 7 200 300 Output 900 250 600 1.3k 2 800 1 Inputs 340 730 3 1.3k 5.4k 4 Gnd VEE Figure 2. Circuit Schematic I IO , INPUT OFFSET CURRENT (nA) 120 Pins 5 & 6 Tied to VCC 100 Normal 80 40 0 -55 -25 0 25 50 75 100 3.0 2.0 1.0 Normal -25 0 25 50 75 Figure 3. Input Bias Current versus Temperature Figure 4. Input Offset Current versus Temperature VCC = +15 V VEE = -15 V TA = +25°C 100 VCC 80 60 40 20 -12 Pins 5 & 6 Tied to VCC TA, TEMPERATURE (°C) 120 0 -16 4.0 0 -55 125 VCC = +15 V VEE = -15 V TA, TEMPERATURE (°C) 140 I IB , INPUT BIAS CURRENT (nA) 5.0 VCC = +15 V VEE = -15 V COMMON MODE LIMITS (V) I IB , INPUT BIAS CURRENT (nA) 140 -8.0 -4.0 0 4.0 8.0 12 100 125 Referred to Supply Voltages -1.0 -1.5 0.4 0.2 VEE -25 0 25 50 75 DIFFERENTIAL INPUT VOLTAGE (V) TA, TEMPERATURE (°C) Figure 5. Input Bias Current versus Differential Input Voltage Figure 6. Common Mode Limits versus Temperature http://onsemi.com 3 125 -0.5 -55 16 100 VO , OUTPUT VOLTAGE (V) +5.0V 20 mV Vin 500Ω VO 2.0 mV 0 0.1 0.2 0.3 0.4 tTLH, RESPONSE TIME (µs) 0.5 Vin ,INPUT VOLTAGE (mV) VCC = +15 V VEE = -15 V TA = +25°C 100 50 0 0.6 Figure 7. Response Time for Various Input Overdrives 15 10 5.0 0 -5.0 -10 -15 20 mV 5.0 mV Vin VCC VO 2.0k VO , OUTPUT VOLTAGE (V) Vin ,INPUT VOLTAGE (mV) 5.0 4.0 3.0 2.0 1.0 0 Vin ,INPUT VOLTAGE (mV) VO , OUTPUT VOLTAGE (V) 5.0 mV VEE 2.0 mV 0 -50 Vin ,INPUT VOLTAGE (mV) VO , OUTPUT VOLTAGE (V) LM211, LM311 VCC = +15 V VEE = -15 V TA = +25°C -100 0 1.0 2.0 tTLH, RESPONSE TIME (µs) +5.0V 5.0 mV 5.0 4.0 3.0 2.0 1.0 0 20 mV VCC = +15 V VEE = -15 V TA = +25°C 0 -50 -100 0 0.1 0.75 0.60 75 0.45 Short Circuit Current 50 0.30 25 0.15 0 0 5.0 0.2 0.3 0.4 tTHL, RESPONSE TIME (µs) 0.5 0.6 Figure 8. Response Time for Various Input Overdrives VCC 15 10 5.0 0 -5.0 -10 -15 5.0 mV Vin 2.0 mV VO 2.0k VEE 20 mV VCC = +15 V VEE = -15 V TA = +25°C 100 50 0 0 1.0 tTHL, RESPONSE TIME (µs) 2.0 0.90 PD , POWER DISSIPATION (W) V , SATURATION VOLTAGE (V) OL OUTPUT SHORT CIRCUIT CURRENT (mA) 0.90 Power Dissipation 100 VO Figure 10. Response Time for Various Input Overdrives TA = +25°C 125 500Ω 2.0 mV Figure 9. Response Time for Various Input Overdrives 150 Vin 0.75 0.60 0.30 TA = +25°C TA = +125°C 0.15 0 0 15 10 TA = -55°C 0.45 0 VO, OUTPUT VOLTAGE (V) 8.0 16 24 32 40 48 56 IO, OUTPUT CURRENT (mA) Figure 11. Output Short Circuit Current Characteristics and Power Dissipation Figure 12. Output Saturation Voltage versus Output Current http://onsemi.com 4 3.6 100 1.0 POWER SUPPLY CURRENT (mA) 10 VCC = +15 V VEE = -15 V Output VO = +50 V (LM211 only) 0.1 0.01 25 45 65 85 105 Positive Supply - Output Low 2.4 1.8 Positive and Negative Power Supply - Output H igh 1.2 0.6 0 125 TA = +25°C 3.0 0 5.0 10 15 20 25 TA, TEMPERATURE (°C) VCC-VEE, POWER SUPPLY VOLTAGE (V) Figure 13. Output Leakage Current versus Temperature Figure 14. Power Supply Current versus Supply Voltage 3.0 SUPPLY CURRENT (mA) OUTPUT LEAKAGE CURRENT (mA) LM211, LM311 2.6 VCC = +15 V VEE = -15 V Postive Supply - Output Low 2.2 1.8 1.4 Positive and Negative Supply - Output High 1.0 -55 -25 0 25 50 75 TA, TEMPERATURE (°C) 100 125 Figure 15. Power Supply Current versus Temperature APPLICATIONS INFORMATION +15 V +15 V 3.0 k 4.7 k 3.0 k 82 33 k 5.0 k C1 0.1 µF Input 2 R1 C2 R2 8 + 3 - 4.7 k 0.002 6 µF LM311 5.0 k 0.1 µF Input 5 1 7 Output 100 R1 C2 100 R2 4 3 8 + 6 C1 LM311 2 - 1 7 Output 4 1.0 M 0.1 µF 5 0.1 µF -15 V 510 k -15 V Figure 17. Conventional Technique for Adding Hysteresis Figure 16. Improved Method of Adding Hysteresis Without Applying Positive Feedback to the Inputs http://onsemi.com 5 30 LM211, LM311 TECHNIQUES FOR AVOIDING OSCILLATIONS IN COMPARATOR APPLICATIONS Since feedback to almost any pin of a comparator can result in oscillation, the printed–circuit layout should be engineered thoughtfully. Preferably there should be a groundplane under the LM211 circuitry (e.g., one side of a double layer printed circuit board). Ground, positive supply or negative supply foil should extend between the output and the inputs to act as a guard. The foil connections for the inputs should be as small and compact as possible, and should be essentially surrounded by ground foil on all sides to guard against capacitive coupling from any fast high–level signals (such as the output). If Pins 5 and 6 are not used, they should be shorted together. If they are connected to a trim–pot, the trim–pot should be located no more than a few inches away from the LM211, and a 0.01 µF capacitor should be installed across Pins 5 and 6. If this capacitor cannot be used, a shielding printed–circuit foil may be advisable between Pins 6 and 7. The power supply bypass capacitors should be located within a couple inches of the LM211. A standard procedure is to add hysteresis to a comparator to prevent oscillation, and to avoid excessive noise on the output. In the circuit of Figure 17, the feedback resistor of 510 kΩ from the output to the positive input will cause about 3.0 mV of hysteresis. However, if R2 is larger than 100 Ω, such as 50 kΩ, it would not be practical to simply increase the value of the positive feedback resistor proportionally above 510 kΩ to maintain the same amount of hysteresis. When both inputs of the LM211 are connected to active signals, or if a high–impedance signal is driving the positive input of the LM211 so that positive feedback would be disruptive, the circuit of Figure 16 is ideal. The positive feedback is applied to Pin 5 (one of the offset adjustment pins). This will be sufficient to cause 1.0 mV to 2.0 mV hysteresis and sharp transitions with input triangle waves from a few Hz to hundreds of kHz. The positive–feedback signal across the 82 Ω resistor swings 240 mV below the positive supply. This signal is centered around the nominal voltage at Pin 5, so this feedback does not add to the offset voltage of the comparator. As much as 8.0 mV of offset voltage can be trimmed out, using the 5.0 kΩ pot and 3.0 kΩ resistor as shown. When a high speed comparator such as the LM211 is used with high speed input signals and low source impedances, the output response will normally be fast and stable, providing the power supplies have been bypassed (with 0.1 µF disc capacitors), and that the output signal is routed well away from the inputs (Pins 2 and 3) and also away from Pins 5 and 6. However, when the input signal is a voltage ramp or a slow sine wave, or if the signal source impedance is high (1.0 kΩ to 100 kΩ), the comparator may burst into oscillation near the crossing–point. This is due to the high gain and wide bandwidth of comparators like the LM211 series. To avoid oscillation or instability in such a usage, several precautions are recommended, as shown in Figure 16. The trim pins (Pins 5 and 6) act as unwanted auxiliary inputs. If these pins are not connected to a trim–pot, they should be shorted together. If they are connected to a trim–pot, a 0.01 µF capacitor (C1) between Pins 5 and 6 will minimize the susceptibility to AC coupling. A smaller capacitor is used if Pin 5 is used for positive feedback as in Figure 16. For the fastest response time, tie both balance pins to VCC. Certain sources will produce a cleaner comparator output waveform if a 100 pF to 1000 pF capacitor (C2) is connected directly across the input pins. When the signal source is applied through a resistive network, R1, it is usually advantageous to choose R2 of the same value, both for DC and for dynamic (AC) considerations. Carbon, tin–oxide, and metal–film resistors have all been used with good results in comparator input circuitry, but inductive wirewound resistors should be avoided. When comparator circuits use input resistors (e.g., summing resistors), their value and placement are particularly important. In all cases the body of the resistor should be close to the device or socket. In other words, there should be a very short lead length or printed–circuit foil run between comparator and resistor to radiate or pick up signals. The same applies to capacitors, pots, etc. For example, if R1 = 10 kΩ, as little as 5 inches of lead between the resistors and the input pins can result in oscillations that are very hard to dampen. Twisting these input leads tightly is the best alternative to placing resistors close to the comparator. http://onsemi.com 6 LM211, LM311 VEE VEE VCC = +15 V Balance Adjust Balance Input Inputs 3.0 k + Inputs LM311 10 k 5.0 k Gnd + LM311 VCC1 VCC Gnd Output to CMOS Logic VCC Output Balance/Strobe 2N2222 or Q1 Equivalent 1.0k VEE TTL Strobe VEE = -15 V Figure 18. Zero–Crossing Detector Driving CMOS Logic VCC2 *D1 *Zener Diode D1 protects the comparator from inductive kickback and voltage transients on the VCC2 supply line. Figure 19. Relay Driver with Strobe Capability http://onsemi.com 7 LM211, LM311 PACKAGE DIMENSIONS PDIP–8 N SUFFIX CASE 626–05 ISSUE K 8 NOTES: 1. DIMENSION L TO CENTER OF LEAD WHEN FORMED PARALLEL. 2. PACKAGE CONTOUR OPTIONAL (ROUND OR SQUARE CORNERS). 3. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 5 –B– 1 4 DIM A B C D F G H J K L M N F –A– NOTE 2 L C J –T– MILLIMETERS MIN MAX 9.40 10.16 6.10 6.60 3.94 4.45 0.38 0.51 1.02 1.78 2.54 BSC 0.76 1.27 0.20 0.30 2.92 3.43 7.62 BSC --10 0.76 1.01 INCHES MIN MAX 0.370 0.400 0.240 0.260 0.155 0.175 0.015 0.020 0.040 0.070 0.100 BSC 0.030 0.050 0.008 0.012 0.115 0.135 0.300 BSC --10 0.030 0.040 N SEATING PLANE D M K G H 0.13 (0.005) M T A B M M SO–8 D SUFFIX CASE 751–07 ISSUE W –X– NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DIMENSION A AND B DO NOT INCLUDE MOLD PROTRUSION. 4. MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER SIDE. 5. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.127 (0.005) TOTAL IN EXCESS OF THE D DIMENSION AT MAXIMUM MATERIAL CONDITION. A 8 5 0.25 (0.010) S B 1 M Y M 4 K –Y– G C N X 45 SEATING PLANE –Z– 0.10 (0.004) H D 0.25 (0.010) M Z Y S X M S http://onsemi.com 8 J DIM A B C D G H J K M N S MILLIMETERS MIN MAX 4.80 5.00 3.80 4.00 1.35 1.75 0.33 0.51 1.27 BSC 0.10 0.25 0.19 0.25 0.40 1.27 0 8 0.25 0.50 5.80 6.20 INCHES MIN MAX 0.189 0.197 0.150 0.157 0.053 0.069 0.013 0.020 0.050 BSC 0.004 0.010 0.007 0.010 0.016 0.050 0 8 0.010 0.020 0.228 0.244 LM211, LM311 Notes http://onsemi.com 9 LM211, LM311 Notes http://onsemi.com 10 LM211, LM311 Notes http://onsemi.com 11 LM211, LM311 ON Semiconductor and are trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice to any products herein. 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