19-1533; Rev 0; 9/99 KIT ATION EVALU E L B A AVAIL 420ksps, +5V, 6-/2-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface Power consumption is only 10mW at the maximum sampling rate of 420ksps. Two software-selectable powerdown modes enable the MAX1294/MAX1296 to be shut down between conversions; accessing the parallel interface returns them to normal operation. Powering down between conversions can reduce supply below 10µA at lower sampling rates. Both devices offer software-configurable analog inputs for unipolar/bipolar and single-ended/pseudo-differential operation. In single-ended mode, the MAX1294 has six input channels and the MAX1296 has two (three input channels and one input channel, respectively, when in pseudo-differential mode). Excellent dynamic performance and low power combined with ease of use and small package size make these converters ideal for battery-powered and data-acquisition applications or for other circuits with demanding powerconsumption and space requirements. The MAX1294 is offered in a 28-pin QSOP package, while the MAX1296 is available in a 24-pin QSOP. For pin-compatible +3V, 12-bit versions, see the MAX1295/MAX1297. Features ♦ 12-Bit Resolution, ±0.5LSB Linearity ♦ Single +5V Operation ♦ Internal +2.5V Reference ♦ Software-Configurable Analog Input Multiplexer 6-Channel Single-Ended/ 3-Channel Pseudo-Differential (MAX1294) 2-Channel Single-Ended/ 1-Channel Pseudo-Differential (MAX1296) ♦ Software-Configurable Unipolar/Bipolar Analog Inputs ♦ Low Current 2.0mA (420ksps) 1.0mA (100ksps) 400µA (10ksps) 2µA (shutdown) ♦ Internal 6MHz Full-Power Bandwidth Track/Hold ♦ Parallel 12-Bit Interface ♦ Small Footprint 28-Pin QSOP (MAX1294) 24-Pin QSOP (MAX1296) Pin Configurations TOP VIEW Applications D9 1 24 D10 Data Logging D8 2 23 D11 Energy Management Patient Monitoring D7 3 22 VDD Data-Acquisition Systems Touchscreens D6 4 21 REF Industrial Control Systems D5 5 Ordering Information PART TEMP. RANGE MAX1294ACEI 0°C to +70°C 28 QSOP INL (LSB) ±0.5 MAX1294BCEI 0°C to +70°C 28 QSOP ±1 MAX1294AEEI -40°C to +85°C 28 QSOP ±0.5 MAX1294BEEI -40°C to +85°C 28 QSOP ±1 MAX1296ACEG 0°C to +70°C 24 QSOP ±0.5 MAX1296BCEG 0°C to +70°C 24 QSOP ±1 MAX1296AEEG -40°C to +85°C 24 QSOP ±0.5 MAX1296BEEG -40°C to +85°C 24 QSOP ±1 PIN-PACKAGE D4 6 20 REFADJ MAX1296 19 GND D3 7 18 COM D2 8 17 CH0 D1 9 16 CH1 D0 10 15 CS INT 11 14 CLK RD 12 13 WR QSOP Pin Configurations continued at end of data sheet. Typical Operating Circuits appear at end of data sheet. ________________________________________________________________ Maxim Integrated Products 1 For free samples & the latest literature: http://www.maxim-ic.com, or phone 1-800-998-8800. For small orders, phone 1-800-835-8769. MAX1294/MAX1296 General Description The MAX1294/MAX1296 low-power, 12-bit analog-todigital converters (ADCs) feature a successive-approximation ADC, automatic power-down, fast wake-up (2µs), on-chip clock, +2.5V internal reference, and high-speed 12-bit parallel interface. They operate with a single +5V analog supply. MAX1294/MAX1296 420ksps, +5V, 6-/2-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface ABSOLUTE MAXIMUM RATINGS VDD to GND ..............................................................-0.3V to +6V CH0–CH5, COM to GND ............................-0.3V to (VDD + 0.3V) REF, REFADJ to GND.................................-0.3V to (VDD + 0.3V) Digital Inputs to GND ...............................................-0.3V to +6V Digital Outputs (D0–D11, INT) to GND.......-0.3V to (VDD + 0.3V) Continuous Power Dissipation (TA = +70°C) 24-Pin QSOP (derate 9.5mW/°C above +70°C)..........762mW 28-Pin QSOP (derate 8.00mW/°C above +70°C)........667mW Operating Temperature Ranges MAX1294_C_ _/MAX1296_C_ _ .........................0°C to +70°C MAX1294_E_ _/MAX1296_E_ _ ......................-40°C to +85°C Storage Temperature Range .............................-65°C to +150°C Lead Temperature (soldering, 10sec) .............................+300°C Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. ELECTRICAL CHARACTERISTICS (VDD = +5V ±10%, COM = GND, REFADJ = VDD, VREF = +2.5V, 4.7µF capacitor at REF pin, fCLK = 7.6MHz (50% duty cycle), TA = TMIN to TMAX, unless otherwise noted. Typical values are at TA = +25°C.) PARAMETER SYMBOL CONDITIONS MIN TYP MAX UNITS DC ACCURACY (Note 1) Resolution RES Relative Accuracy (Note 2) INL Differential Nonlinearity DNL 12 Bits MAX129_A ±0.5 MAX129_B ±1 No missing codes over temperature ±1 LSB ±4 LSB Offset Error ±4 Gain Error (Note 3) LSB LSB Gain Temperature Coefficient ±2.0 ppm/°C Channel-to-Channel Offset Matching ±0.2 LSB DYNAMIC SPECIFICATIONS (fIN(sine wave) = 50kHz, VIN = 2.5Vp-p, 420ksps, external fCLK = 7.6MHz, bipolar input mode) Signal-to-Noise Plus Distortion SINAD Total Harmonic Distortion (including 5th-order harmonic) THD Spurious-Free Dynamic Range SFDR 67 70 dB -80 -80 dB dB fIN1 = 49kHz, fIN2 = 52kHz 76 Channel-to-Channel Crosstalk fIN = 175kHz (Note 4) -78 dB Full-Linear Bandwidth SINAD > 68dB 350 kHz Full-Power Bandwidth -3dB rolloff 6 MHz Intermodulation Distortion IMD dB CONVERSION RATE Conversion Time (Note 5) T/H Acquisition Time tCONV 2 External acquisition/internal clock mode 2.5 3.0 3.5 Internal acquisition/internal clock mode 3.2 3.6 4 400 External acquisition or external clock mode Aperture Jitter Duty Cycle 2.1 tACQ Aperture Delay External Clock Frequency External clock mode fCLK 25 External acquisition or external clock mode <50 Internal acquisition/internal clock mode <200 µs ns ns ps 0.1 7.6 MHz 30 70 % _______________________________________________________________________________________ 420ksps, +5V, 6-/2-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface (VDD = +5V ±10%, COM = GND, REFADJ = VDD, VREF = +2.5V, 4.7µF capacitor at REF pin, fCLK = 7.6MHz (50% duty cycle), TA = TMIN to TMAX, unless otherwise noted. Typical values are at TA = +25°C.) PARAMETER SYMBOL CONDITIONS MIN TYP MAX UNITS ANALOG INPUTS Unipolar, VCOM = 0 Analog Input Voltage Range Single-Ended and Differential (Note 6) VIN Multiplexer Leakage Current Bipolar, VCOM = VREF/2 0 VREF -VREF/2 +VREF/2 ±0.01 On/off-leakage current, VIN = 0 or VDD Input Capacitance ±1 12 CIN V µA pF INTERNAL REFERENCE 2.49 REF Output Voltage REF Short-Circuit Current REF Temperature Coefficient TCREF REFADJ Input Range For small adjustments REFADJ High Threshold To power down the internal reference Load Regulation (Note 7) 0 to 0.5mA output load 2.51 V 15 mA ±20 ppm/°C ±100 mV VDD - 1 V 0.2 0.5 mV/mA 0.01 1 µF 4.7 10 µF 1.0 VDD + 50mV V 300 µA 2 µA Capacitive Bypass at REFADJ Capacitive Bypass at REF 2.5 EXTERNAL REFERENCE AT REF REF Input Voltage Range VREF REF Input Current IREF 200 VREF = 2.5V, fSAMPLE = 420ksps Shutdown mode DIGITAL INPUTS AND OUTPUTS Input Voltage High VIH Input Voltage Low VIL Input Hysteresis 4.0 200 VHYS Input Leakage Current IIN Input Capacitance CIN Output Voltage Low VOL ISINK = 1.6mA Output Voltage High VOH ISOURCE = 1mA Three-State Leakage Current Three-State Output Capacitance V 0.8 ±0.1 VIN = 0 or VDD V mV ±1 15 µA pF 0.4 VDD - 0.5 V V ILEAKAGE CS = VDD ±0.1 COUT CS = VDD 15 ±1 µA pF POWER REQUIREMENTS Analog Supply Voltage Positive Supply Current 4.5 VDD IDD IDD Operating mode, fSAMPLE = 420ksps Standby mode 2.6 2.9 External reference 2.2 2.5 Internal reference 1.0 1.2 External reference 0.5 0.8 Shutdown mode Power-Supply Rejection PSR 5.5 Internal reference VDD = 5V ±10%, full-scale input V mA 2 10 µA ±0.3 ±0.7 mV _______________________________________________________________________________________ 3 MAX1294/MAX1296 ELECTRICAL CHARACTERISTICS (continued) MAX1294/MAX1296 420ksps, +5V, 6-/2-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface TIMING CHARACTERISTICS (VDD = +5V ±10%, COM = GND, REFADJ = VDD, VREF = +2.5V, 4.7µF capacitor at REF pin, fCLK = 7.6MHz (50% duty cycle), TA = TMIN to TMAX, unless otherwise noted. Typical values are at TA = +25°C.) PARAMETER SYMBOL CONDITIONS MIN TYP MAX UNITS CLK Period tCP 132 ns CLK Pulse Width High tCH 40 ns CLK Pulse Width Low tCL 40 ns Data Valid to WR Rise Time tDS 40 ns WR Rise to Data Valid Hold Time tDH 0 ns WR to CLK Fall Setup Time tCWS 60 ns CLK Fall to WR Hold Time tCWH 40 ns CS to CLK or WR Setup Time tCSWS 40 ns CLK or WR to CS Hold Time tCSWH 0 ns CS Pulse Width tCS 100 ns WR Pulse Width (Note 8) tWR CS Rise to Output Disable tTC CLOAD = 20pF, Figure 1 10 60 ns RD Rise to Output Disable tTR CLOAD = 20pF, Figure 1 10 40 ns RD Fall to Output Data Valid tDO CLOAD = 20pF, Figure 1 10 50 ns RD Fall to INT High Delay tINT1 CLOAD = 20pF, Figure 1 50 ns CS Fall to Output Data Valid tDO2 CLOAD = 20pF, Figure 1 100 ns 60 ns Note 1: Tested at VDD = +5V, COM = GND, unipolar single-ended input mode. Note 2: Relative accuracy is the deviation of the analog value at any code from its theoretical value after offset and gain errors have been removed. Note 3: Offset nulled. Note 4: On channel is grounded; sine wave applied to off channels. Note 5: Conversion time is defined as the number of clock cycles times the clock period; clock has a 50% duty cycle. Note 6: Input voltage range referenced to negative input. The absolute range for the analog inputs is from GND to VDD. Note 7: External load should not change during conversion for specified accuracy. Note 8: When bit 5 is set low for internal acquisition, WR must not return low until after the first falling clock edge of the conversion. VDD 3k DOUT CLOAD 20pF 3k DOUT CLOAD 20pF GND a) High-Z to VOH and VOL to VOH GND b) High-Z to VOL and VOH to VOL Figure 1. Load Circuits for Enable/Disable Times 4 _______________________________________________________________________________________ 420ksps, +5V, 6-/2-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface DIFFERENTIAL NONLINEARITY vs. DIGITAL OUTPUT CODE 0.4 0.3 0.2 0.1 0.1 0 -0.1 0 -0.2 -0.3 -0.3 -0.4 -0.4 -0.5 -0.5 3000 4000 5000 WITH EXTERNAL REFERENCE 0 0 1000 DIGITAL OUTPUT CODE SUPPLY CURRENT vs. SUPPLY VOLTAGE 3000 4000 5000 1 10 RL = ∞ CODE = 101010100000 2.2 IDD (mA) 1k 10k 100k 1M STANDBY CURRENT vs. SUPPLY VOLTAGE 2.1 2.0 100 fSAMPLE (Hz) 990 980 STANDBY IDD (µA) RL = ∞ CODE = 101010100000 2.1 IDD (mA) 0.1 SUPPLY CURRENT vs. TEMPERATURE 2.3 MAX1294/6 toc03 2.2 2000 DIGITAL OUTPUT CODE 2.0 1.9 MAX1294/6 toc05 2000 100 10 MAX1294/6 toc04 1000 WITH INTERNAL REFERENCE 1000 -0.1 -0.2 0 10,000 IDD (µA) 0.2 DNL (LSB) INL (LSB) 0.3 MAX1294/6-02 0.4 SUPPLY CURRENT vs. SAMPLE FREQUENCY 0.5 MAX1294/6-01 0.5 MAX1294/6-02A INTEGRAL NONLINEARITY vs. DIGITAL OUTPUT CODE 970 960 950 1.9 940 1.8 1.8 4.75 5.00 5.25 5.50 -40 -15 10 35 60 4.50 85 4.75 5.00 5.25 VDD (V) TEMPERATURE (°C) VDD (V) STANDBY CURRENT vs. TEMPERATURE POWER-DOWN CURRENT vs. SUPPLY VOLTAGE POWER-DOWN CURRENT vs. TEMPERATURE 970 960 950 2.0 1.5 5.50 MAX1294/6 toc08 2.5 POWER-DOWN IDD (µA) POWER-DOWN IDD (µA) 980 2.2 MAX1290/2 toc07 3.0 MAX1294/6 toc06 990 STANDBY IDD (µA) 930 1.7 4.50 2.1 2.0 1.9 940 1.0 930 -40 -15 10 35 TEMPERATURE (°C) 60 85 4.50 4.75 5.00 VDD (V) 5.25 5.50 1.8 -40 -15 10 35 60 85 TEMPERATURE (°C) _______________________________________________________________________________________ 5 MAX1294/MAX1296 Typical Operating Characteristics (VDD = +5V, VREF = +2.500V, fCLK = 7.6MHz, CL = 20pF, TA = +25°C, unless otherwise noted.) Typical Operating Characteristics (continued) (VDD = +5V, VREF = +2.500V, fCLK = 7.6MHz, CL = 20pF, TA = +25°C, unless otherwise noted.) REFERENCE VOLTAGE vs. TEMPERATURE MAX1294/6-10 2.51 2.50 2.50 2.49 2.49 1.0 OFFSET ERROR (LSB) 2.51 2.52 VREF (V) 4.50 4.75 5.00 5.25 -1.0 -40 5.50 -15 10 35 60 85 5.00 35 60 1.0 0 4.50 85 4.75 5.00 5.25 5.50 VDD (V) TEMPERATURE (°C) -40 -15 10 VDD = 5V fIN = 50kHz fSAMPLE = 400ksps AMPLITUDE (dB) -20 MAX1294/6-15 FFT PLOT 0 -40 -60 -80 -100 -120 -140 0 200 400 35 TEMPERATURE (°C) 20 600 800 1000 FREQUENCY (kHz) 6 5.50 0.5 -2 -2 1.5 GAIN ERROR (LSB) 0 -1 -1 2.0 MAX1294/6 toc13 1 GAIN ERROR (LSB) 0 5.25 GAIN ERROR vs. TEMPERATURE 2 MAX1294/6 toc12 1 10 4.75 VDD (V) GAIN ERROR vs. SUPPLY VOLTAGE OFFSET ERROR vs. TEMPERATURE 2 -15 4.50 TEMPERATURE (°C) VDD (V) -40 0 -0.5 2.48 2.48 0.5 MAX1294/6 toc14 VREF (V) 2.52 OFFSET ERROR vs. SUPPLY VOLTAGE 2.53 MAX1294/6-09 2.53 MAX1294/6 toc11 INTERNAL REFERENCE VOLTAGE vs. SUPPLY VOLTAGE OFFSET ERROR (LSB) MAX1294/MAX1296 420ksps, +5V, 6-/2-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface _______________________________________________________________________________________ 60 85 420ksps, +5V, 6-/2-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface PIN NAME FUNCTION MAX1294 MAX1296 1 1 D9 Three-State Digital Output (D9) 2 2 D8 Three-State Digital Output (D8) 3 3 D7 Three-State Digital I/O Line (D7) 4 4 D6 Three-State Digital I/O Line (D6) 5 5 D5 Three-State Digital I/O Line (D5) 6 6 D4 Three-State Digital I/O Line (D4) 7 7 D3 Three-State Digital I/O Line (D3) 8 8 D2 Three-State Digital I/O Line (D2) 9 9 D1 Three-State Digital I/O Line (D1) 10 10 D0 Three-State Digital I/O Line (D0) 11 11 INT INT goes low when the conversion is complete and output data is ready. 12 12 RD Active-Low Read Select. If CS is low, a falling edge on RD will enable the read operation on the data bus. 13 13 WR Active-Low Write Select. When CS is low in the internal acquisition mode, a rising edge on WR latches in configuration data and starts an acquisition plus a conversion cycle. When CS is low in external acquisition mode, the first rising edge on WR ends acquisition and starts a conversion. 14 14 CLK Clock Input. In external clock mode, drive CLK with a TTL/CMOS-compatible clock. In internal clock mode, connect this pin to either VDD or GND. 15 15 CS 16 — CH5 Analog Input Channel 5 17 — CH4 Analog Input Channel 4 18 — CH3 Analog Input Channel 3 19 — CH2 Analog Input Channel 2 20 16 CH1 Analog Input Channel 1 21 17 CH0 Analog Input Channel 0 22 18 COM Ground Reference for Analog Inputs. Sets zero-code voltage in single-ended mode and must be stable to ±0.5LSB during conversion. 23 19 GND Analog and Digital Ground 24 20 REFADJ Active-Low Chip Select. When CS is high, digital outputs (INT, D11–D0) are high impedance. Bandgap Reference Output/Bandgap Reference Buffer Input. Bypass to GND with a 0.01µF capacitor. When using an external reference, connect REFADJ to VDD to disable the internal bandgap reference. _______________________________________________________________________________________ 7 MAX1294/MAX1296 Pin Description 420ksps, +5V, 6-/2-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface MAX1294/MAX1296 Pin Description (continued) PIN NAME FUNCTION 21 REF Bandgap Reference Buffer Output/External Reference Input. Add a 4.7µF capacitor to GND when using the internal reference. 26 22 VDD Analog +5V Power Supply. Bypass with a 0.1µF capacitor to GND. 27 23 D11 Three-State Digital Output (D11) 28 24 D10 Three-State Digital Output (D10) MAX1294 MAX1296 25 REF REFADJ 17k AV = 2.05 (CH5) (CH4) (CH3) (CH2) CH1 ANALOG INPUT MULTIPLEXER T/H CHARGE REDISTRIBUTION 12-BIT DAC CH0 12 COM SUCCESSIVEAPPROXIMATION REGISTER CLK 1.22V REFERENCE COMP CLOCK CS WR RD INT CONTROL LOGIC & LATCHES MAX1294 MAX1296 VDD 12 THREE-STATE, BIDIRECTIONAL I/O INTERFACE GND D0–D11 12-BIT DATA BUS ( ) ARE FOR MAX1294 ONLY. Figure 2. Simplified Functional Diagram _______________Detailed Description Converter Operation The MAX1294/MAX1296 ADCs use a successive-approximation (SAR) conversion technique and an input 8 track/hold (T/H) stage to convert an analog input signal to a 12-bit digital output. This output format provides easy interface to standard microprocessors (µPs). Figure 2 shows the simplified internal architecture of the MAX1294/ MAX1296. _______________________________________________________________________________________ 420ksps, +5V, 6-/2-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface tial mode, IN+ and IN- are selected from analog input pairs (Table 3) and are internally switched to either of the analog inputs. This configuration is pseudo-differential to the effect that only the signal at IN+ is sampled. The return side (IN-) must remain stable within ±0.5LSB (±0.1LSB for best performance) with respect to GND during a conversion. To accomplish this, connect a 0.1µF capacitor from IN- (the selected input) to GND. The sampling architecture of the ADCs’ analog comparator is illustrated in the equivalent input circuits of Figure 3. In single-ended mode, IN+ is internally switched to channels CH0–CH5 for the MAX1294 (Figure 3a) and to CH0–CH1 for the MAX1296 (Figure 3b), while IN- is switched to COM (Table 2). In differen- 12-BIT CAPACITIVE DAC 12-BIT CAPACITIVE DAC VREF CH0 VREF COMPARATOR INPUT CHOLD MUX – + ZERO CH0 12pF CSWITCH T/H SWITCH COM RIN 800Ω CH1 CSWITCH HOLD TRACK CH4 CH5 ZERO 12pF RIN 800Ω CH1 CH2 CH3 COMPARATOR INPUT CHOLD MUX – + TRACK AT THE SAMPLING INSTANT, THE MUX INPUT SWITCHES FROM THE SELECTED IN+ CHANNEL TO THE SELECTED IN- CHANNEL. T/H SWITCH COM SINGLE-ENDED MODE: IN+ = CH0–CH5, IN- = COM. DIFFERENTIAL MODE: IN+ AND IN- SELECTED FROM PAIRS OF CH0/CH1 AND CH2/CH3, AND CH4/CH5 HOLD AT THE SAMPLING INSTANT, THE MUX INPUT SWITCHES FROM THE SELECTED IN+ CHANNEL TO THE SELECTED IN- CHANNEL. SINGLE-ENDED MODE: IN+ = CH0–CH1, IN- = COM. DIFFERENTIAL MODE: IN+ AND IN- SELECTED FROM PAIR CH0/CH1. Figure 3a. MAX1294 Simplified Input Structure Figure 3b. MAX1296 Simplified Input Structure Table 1. Control-Byte Functional Description BIT NAME FUNCTIONAL DESCRIPTION PD1 and PD0 select the various clock and power-down modes. D7, D6 D5 D4 D3 D2, D1, D0 PD1, PD0 0 0 Full Power-Down Mode. Clock mode is unaffected. 0 1 Standby Power-Down Mode. Clock mode is unaffected. 1 0 Normal Operation Mode. Internal clock mode selected. 1 1 Normal Operation Mode. External clock mode selected. ACQMOD ACQMOD = 0: Internal Acquisition Mode ACQMOD = 1: External Acquisition Mode SGL/DIF SGL/DIF = 0: Pseudo-Differential Analog Input Mode SGL/DIF = 1: Single-Ended Analog Input Mode In single-ended mode, input signals are referred to COM. In pseudo-differential mode, the voltage difference between two channels is measured (see Tables 2, 4). UNI/BIP UNI/BIP = 0: Bipolar Mode UNI/BIP = 1: Unipolar Mode In unipolar mode, an analog input signal from 0V to VREF can be converted; in bipolar mode, the signal can range from -VREF/2 to +VREF/2. A2, A1, A0 Address bits A2, A1, A0 select which of the 6/2 (MAX1294/MAX1296) channels is to be converted (see Tables 2, 3). _______________________________________________________________________________________ 9 MAX1294/MAX1296 Single-Ended and Pseudo-Differential Operation MAX1294/MAX1296 420ksps, +5V, 6-/2-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface Table 2. Channel Selection for Single-Ended Operation (SGL/DIF = 1) A2 A1 A0 CH0 0 0 0 + 0 0 1 0 1 0 0 1 1 1 0 0 1 0 1 CH1 CH2* CH3* CH4* CH5* COM - + + + + + - *Channels CH2–CH5 apply to MAX1294 only. Table 3. Channel Selection for Pseudo-Differential Operation (SGL/DIF = 0) A2 A1 A0 CH0 CH1 CH2* CH3* CH4* CH5* 0 0 0 + 0 0 1 0 1 0 0 1 1 1 0 0 + - 1 0 1 - + + + + *Channels CH2–CH5 apply to MAX1294 only. During the acquisition interval, the channel selected as the positive input (IN+) charges capacitor CHOLD. At the end of the acquisition interval, the T/H switch opens, retaining charge on CHOLD as a sample of the signal at IN+. The conversion interval begins with the input multiplexer switching CHOLD from the positive input (IN+) to the negative input (IN-). This unbalances node ZERO at the comparator’s positive input. The capacitive digital-toanalog converter (DAC) adjusts during the remainder of the conversion cycle to restore node ZERO to 0V within the limits of 12-bit resolution. This action is equivalent to transferring a 12pF [(VIN+ - VIN-)] charge from CHOLD to the binary-weighted capacitive DAC, which in turn forms a digital representation of the analog input signal. Analog Input Protection Internal protection diodes, which clamp the analog input to VDD and GND, allow each input channel to swing within (GND - 300mV) to (VDD + 300mV) without damage. However, for accurate conversions near full scale, both inputs must not exceed (VDD + 50mV) or be less than (GND - 50mV). 10 If an analog input voltage exceeds the supplies by more than 50mV, limit the forward-bias input current to 4mA. Track/Hold The MAX1294/MAX1296 T/H stage enters its tracking mode on the rising edge of WR. In external acquisition mode, the part enters its hold mode on the next on rising edge of WR. In internal acquisition mode, the part enters its hold mode on the fourth falling edge of clock after writing the control byte. Note that in internal clock mode this is approximately 1µs after writing the control byte. In single-ended operation, IN- is connected to COM and the converter samples the positive “+” input. In pseudo-differential operation, IN- connects to the negative input “-”, and the difference of |(IN+) - (IN-)| is sampled. At the beginning of the next conversion, the positive input connects back to IN+ and C HOLD charges to the input signal. The time required for the T/H stage to acquire an input signal depends on how quickly its input capacitance is charged. If the input signal’s source impedance is high, ______________________________________________________________________________________ 420ksps, +5V, 6-/2-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface tACQ = 9 (RS + RIN) CIN where RS is the source impedance of the input signal, RIN (800Ω) is the input resistance, and CIN (12pF) is the ADC’s input capacitance. Source impedances below 3kΩ have no significant impact on the MAX1294/ MAX1296’s AC performance. Higher source impedances can be used if a 0.01µF capacitor is connected to the individual analog inputs. Together with the input impedance, this capacitor forms an RC filter, limiting the ADC’s signal bandwidth. Input Bandwidth The MAX1294/MAX1296 T/H stage offers a 350kHz fulllinear and a 6MHz full-power bandwidth. This makes it possible to digitize high-speed transients and measure periodic signals with bandwidths exceeding the ADCs sampling rate by using undersampling techniques. To avoid high-frequency signals being aliased into the frequency band of interest, anti-alias filtering is recommended. Starting a Conversion Initiate a conversion by writing a control byte, which selects the multiplexer channel and configures the MAX1294/MAX1296 for either unipolar or bipolar operation. A write pulse (WR + CS) can either start an acquisition interval or initiate a combined acquisition plus conversion. The sampling interval occurs at the end of the acquisition interval. The ACQMOD (acquisition mode) bit in the input control byte (Table 1) offers two options for acquiring the signal: an internal and an external acquisition. The conversion period lasts for 13 clock cycles in either the internal or external clock or acquisition mode. Writing a new control byte during a conversion cycle will abort the conversion and start a new acquisition interval. Internal Acquisition Select internal acquisition by writing the control byte with the ACQMOD bit cleared (ACQMOD = 0). This causes the write pulse to initiate an acquisition interval whose duration is internally timed. Conversion starts when this acquisition interval (three external clock cycles or approximately 1µs in internal clock mode) ends (Figure 4). Note that when the internal acquisition is combined with the internal clock, the aperture jitter can be as high as 200ps. Internal clock users wishing to achieve the 50ps jitter specification should always use external acquisition mode. External Acquisition Use external acquisition mode for precise control of the sampling aperture and/or dependent control of acquisition and conversion times. The user controls acquisition and start-of-conversion with two separate write pulses. The first pulse, written with ACQMOD = 1, starts an acquisition interval of indeterminate length. The second write pulse, written with ACQMOD = 0 (all other bits in control byte unchanged), terminates acquisition and starts conversion on WR rising edge (Figure 5). The address bits for the input multiplexer must have the same values on the first and second write pulse. Power-down mode bits (PD0, PD1) can assume new values on the second write pulse (see Power-Down Modes section). Changing other bits in the control byte will corrupt the conversion. Reading a Conversion A standard interrupt signal INT is provided to allow the MAX1294/MAX1296 to flag the µP when the conversion has ended and a valid result is available. INT goes low when the conversion is complete and the output data is ready (Figures 4, 5). It returns high on the first read cycle or if a new control byte is written. Selecting Clock Mode The MAX1294/MAX1296 operate with either an internal or an external clock. Control bits D6 and D7 select either internal or external clock mode. The part retains the last requested clock mode if a power-down mode is selected in the current input word. For both internal and external clock mode, internal or external acquisition can be used. At power-up, the MAX1294/MAX1296 enter the default external clock mode. Internal Clock Mode Select internal clock mode to release the µP from the burden of running the SAR conversion clock. Bits D6 and D7 of the control byte must be set to 1; the internal clock frequency is then selected, resulting in a conversion time of 3.6µs. When using the internal clock mode, tie the CLK pin either high or low to prevent the pin from floating. ______________________________________________________________________________________ 11 MAX1294/MAX1296 the acquisition time lengthens and more time must be allowed between conversions. The acquisition time, tACQ, is the maximum time the device takes to acquire the signal, and is also the minimum time required for the signal to be acquired. Calculate this with the following equation: MAX1294/MAX1296 420ksps, +5V, 6-/2-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface tCS CS tACQ tCSWS tCSWH tWR tCONV WR tDH tDS CONTROL BYTE D11–D0 ACQMOD ="0" tINT1 INT RD tTR tD0 HIGH-Z VALID DATA DOUT HIGH-Z Figure 4. Conversion Timing Using Internal Acquisition Mode tCS CS tCSWS tWR tACQ tCSLOH tCONV WR tDH tDS CONTROL BYTE ACQMOD = "1" D11–D0 CONTROL BYTE ACQMOD = "0" tNT1 INT RD tD0 HIGH-Z tTR VALID DATA DOUT Figure 5. Conversion Timing Using External Acquisition Mode 12 ______________________________________________________________________________________ HIGH-Z 420ksps, +5V, 6-/2-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface ACQUISITION STARTS tCP Digital Interface The input and output data are multiplexed on a threestate parallel interface (I/O) that can easily be interfaced with standard µPs. The signals CS, WR, and RD control the write and read operations. CS represents the chip-select signal, which enables a µP to address the MAX1294/MAX1296 as an I/O port. When high, CS disables the CLK, WR, and RD inputs and forces the interface into a high-impedance (high-Z) state. CONVERSION STARTS ACQUISITION ENDS CLK tCWS tCH WR tCL WR GOES HIGH WHEN CLK IS HIGH ACQMOD = "0" tCWH ACQUISITION STARTS ACQUISITION ENDS CONVERSION STARTS CLK WR ACQMOD = "0" WR GOES HIGH WHEN CLK IS LOW Figure 6a. External Clock and WR Timing (Internal Acquisition Mode) ACQUISITION ENDS ACQUISITION STARTS CONVERSION STARTS CLK tCWS tDH WR ACQMOD = "0" ACQMOD = "1" WR GOES HIGH WHEN CLK IS HIGH ACQUISITION STARTS ACQUISITION ENDS CONVERSION STARTS CLK tCWH tDH WR ACQMOD = "1" WR GOES HIGH WHEN CLK IS LOW ACQMOD = "0" Figure 6b. External Clock and WR Timing (External Acquisition Mode) ______________________________________________________________________________________ 13 MAX1294/MAX1296 External Clock Mode To select external clock mode, bits D6 and D7 of the control byte must be set to zero. Figure 6 shows the clock and WR timing relationship for internal (Figure 6a) and external (Figure 6b) acquisition modes with an external clock. For proper operation, a 100kHz to 7.6MHz clock frequency with 30% to 70% duty cycle is recommended. Operating the MAX1294/MAX1296 with clock frequencies lower than 100kHz is not recommended because the resulting voltage droop across the hold capacitor in the T/H stage will degrade performance. MAX1294/MAX1296 420ksps, +5V, 6-/2-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface Table 4. Control-Byte Format D7 (MSB) D6 D5 D4 D3 D2 D1 D0 (LSB) PD1 PD0 ACQMOD SGL/DIF UNI/BIP A2 A1 A0 Input Format The control bit sequence is latched into the device on pins D7–D0 during a write command. Table 4 shows the control-byte format. Output Data Format The 12-bit-wide output format for both the MAX1294/ MAX1296 is binary in unipolar mode and two’s complement in bipolar mode. CS, RD, WR, INT, and the 12 bits of output data can interface directly to a 16-bit data bus. When reading the output data, CS and RD must be low. VDD = +5V 50k MAX1294 MAX1296 330k 50k REFADJ 4.7µF REF 0.01µF __________Applications Information Power-On Reset When power is first applied, internal power-on reset circuitry activates the MAX1294/MAX1296 in external clock mode and sets INT high. After the power supplies stabilize, the internal reset time is 10µs; no conversions should be attempted during this phase. When using the internal reference, 500µs is required for VREF to stabilize. Internal and External Reference The MAX1294/MAX1296 can be used with an internal or external reference voltage. An external reference can be connected directly to REF or REFADJ. An internal buffer is designed to provide +2.5V at REF for both devices. The internally trimmed +1.22V reference is buffered with a +2.05V/V gain. Internal Reference The full-scale range with the internal reference is +2.5V with unipolar inputs and ±1.25V with bipolar inputs. The internal reference buffer allows for small adjustments (±100mV) in the reference voltage (Figure 7). Note: The reference buffer must be compensated with an external capacitor (4.7µF min) connected between REF and GND to reduce reference noise and switching spikes from the ADC. To further minimize reference noise, connect a 0.01µF capacitor between REFADJ and GND. External Reference With the MAX1294/MAX1296, an external reference can be placed at either the input (REFADJ) or the output (REF) of the internal-reference buffer amplifier. 14 Figure 7. Reference Adjustment with External Potentiometer Using the REFADJ input makes buffering the external reference unnecessary. The REFADJ input impedance is typically 17kΩ. When applying an external reference to REF, disable the internal reference buffer by connecting REFADJ to VDD. The DC input resistance at REF is 25kΩ. Therefore, an external reference at REF must deliver up to 200µA DC load current during a conversion and have an output impedance less than 10Ω. If the reference has higher output impedance or is noisy, bypass it close to the REF pin with a 4.7µF capacitor. Power-Down Modes To save power, place the converter in a low-current shutdown state between conversions. Select standby mode or shutdown mode through bits D6 and D7 of the control byte (Tables 1, 4). In both software power-down modes, the parallel interface remains active, but the ADC does not convert. Standby Mode While in standby mode, the supply current is typically 1mA. The part will power up on the next rising edge of WR and be ready to perform conversions. This quick turn-on time allows the user to realize significantly reduced power consumption for conversion rates below 420ksps. ______________________________________________________________________________________ 420ksps, +5V, 6-/2-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface UNIPOLAR MODE BIPOLAR MODE Full Scale VREF + COM Zero Scale COM Zero Scale COM — — Negative Full Scale -VREF/2 + COM Positive Full Scale 111 . . . 111 FS = REF + COM 111 . . . 110 ZS = COM FULL-SCALE TRANSITION 011 . . . 111 FS = REF + COM 2 011 . . . 110 ZS = COM 000 . . . 010 100 . . . 010 1LSB = 100 . . . 000 000 . . . 001 REF 4096 000 . . . 000 -REF + COM 2 REF 1LSB = 4096 -FS = 111 . . . 111 011 . . . 111 111 . . . 110 011 . . . 110 111 . . . 101 011 . . . 101 100 . . . 001 000 . . . 001 100 . . . 000 000 . . . 000 0 1 (COM) VREF/2 + COM OUTPUT CODE OUTPUT CODE 100 . . . 001 MAX1294/MAX1296 Table 5. Full Scale and Zero Scale for Unipolar and Bipolar Operation 2 2048 INPUT VOLTAGE (LSB) - FS FS FS - 3/2LSB COM* +FS - 1LSB INPUT VOLTAGE (LSB) *COM ≤ VREF/2 Figure 8. Unipolar Transfer Functions Figure 9. Bipolar Transfer Functions Shutdown Mode Shutdown mode turns off all chip functions that draw quiescent current, reducing the typical supply current to 2µA immediately after the current conversion is completed. A rising edge on WR causes the MAX1294/ MAX1296 to exit shutdown mode and return to normal operation. To achieve full 12-bit accuracy with a 4.7µF reference bypass capacitor, 500µs is required after power-up. Waiting 500µs in standby mode instead of in full-power mode can reduce power consumption by a factor of three or more. When using an external reference, only 50µs is required after power-up. Enter standby mode by performing a dummy conversion with the control byte specifying standby mode. Note: Bypass capacitors larger than 4.7µF between REF and GND will result in longer power-up delays. unipolar input/output (I/O) transfer function, and Figure 9 shows the bipolar I/O transfer function. Code transitions occur halfway between successive-integer LSB values. Output coding is binary, with 1LSB = (VREF/4096). Transfer Function Table 5 shows the full-scale voltage ranges for unipolar and bipolar modes. Figures 8 depicts the nominal Maximum Sampling Rate/ Achieving 475ksps When running at the maximum clock frequency of 7.6MHz, the specified throughput of 420ksps is achieved by completing a conversion every 18 clock cycles: one write cycle, three acquisition cycles, 13 conversion cycles, and one read cycle. This assumes that the results of the last conversion are read before the next control byte is written. It is possible to achieve higher throughputs, up to 475ksps, by first writing a control byte to begin the acquisition cycle of the next conversion, and then reading the results of the previous conversion from the bus. This technique (Figure 10) allows a conversion to be completed every 16 clock cycles. Note that the switching of the data bus during ______________________________________________________________________________________ 15 MAX1294/MAX1296 420ksps, +5V, 6-/2-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface 1 CLK WR RD D7–D0 STATE CONTROL WORD 2 3 4 5 6 7 8 9 D11– D0 10 11 12 13 14 15 16 D11–D0 CONTROL WORD ACQUISITION CONVERSION ACQUISITION SAMPLING INSTANT Figure 10. Timing Diagram for Fastest Conversion acquisition or conversion can cause additional supplynoise, which may make it difficult to achieve true 12-bit performance. SUPPLIES Layout, Grounding, and Bypassing For best performance, use printed circuit boards. Wirewrap configurations are not recommended, since the layout should ensure proper separation of analog and digital traces. Do not run analog and digital lines parallel to each other, and don’t lay out digital signal paths underneath the ADC package. Use separate analog and digital PC board ground sections with only one “star point” (Figure 11) connecting the two ground systems (analog and digital). For lowest noise operation, ensure the ground return to the star ground’s power supply is low impedance and as short as possible. Route digital signals far away from sensitive analog and reference inputs. High-frequency noise in the power supply, VDD, could impair operation of the ADC’s fast comparator. Bypass VDD to the star ground with a network of two parallel capacitors, 0.1µF and 4.7µF, located as close to the MAX1294/MAX1296’s power-supply pin as possible. Minimize capacitor lead length for best supply-noise rejection and add an attenuation resistor (5Ω) if the power supply is extremely noisy. 16 +5V R* = 5Ω +5V GND +5V DGND 4.7µF 0.1µF VDD GND COM MAX1294 MAX1296 DIGITAL CIRCUITRY *OPTIONAL Figure 11. Power-Supply and Grounding Connections ______________________________________________________________________________________ 420ksps, +5V, 6-/2-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface Integral Nonlinearity Integral nonlinearity (INL) is the deviation of the values on an actual transfer function from a straight line. This straight line can be either a best-straight-line fit or a line drawn between the end points of the transfer function, once offset and gain errors have been nullified. INL for the MAX1294/MAX1296 is measured using the endpoint method. Differential Nonlinearity Differential nonlinearity (DNL) is the difference between an actual step width and the ideal value of 1LSB. A DNL error specification of less than 1LSB guarantees no missing codes and a monotonic transfer function. Aperture Jitter Aperture jitter (tAJ) is the sample-to-sample variation in the time between the samples. Aperture Delay Aperture delay (t AD ) is the time between the rising edge of the sampling clock and the instant when an actual sample is taken. Signal-to-Noise Ratio For a waveform perfectly reconstructed from digital samples, signal-to-noise ratio (SNR) is the ratio of full-scale analog input (RMS value) to the RMS quantization error (residual error). The ideal, theoretical minimum analogto-digital noise is caused by quantization error only and results directly from the ADC’s resolution (N bits): SNR = (6.02 · N + 1.76)dB In reality, there are other noise sources besides quantization noise, including thermal noise, reference noise, clock jitter, etc. Therefore, SNR is calculated by taking the ratio of the RMS signal to the RMS noise, which includes all spectral components minus the fundamental, the first five harmonics, and the DC offset. Signal-to-Noise Plus Distortion Signal-to-noise plus distortion (SINAD) is the ratio of the fundamental input frequency’s RMS amplitude to the RMS equivalent of all other ADC output signals: SINAD (dB) = 20 · log (SignalRMS/NoiseRMS) Effective Number of Bits Effective number of bits (ENOB) indicates the global accuracy of an ADC at a specific input frequency and sampling rate. An ideal ADC’s error consists of quantization noise only. With an input range equal to the fullscale range of the ADC, calculate the effective number of bits as follows: ENOB = (SINAD - 1.76) / 6.02 Total Harmonic Distortion Total harmonic distortion (THD) is the ratio of the RMS sum of the first five harmonics of the input signal to the fundamental itself. This is expressed as: THD = 20 ⋅log V22 + V32 + V4 2 + V52 / V1 where V1 is the fundamental amplitude, and V2 through V5 are the amplitudes of the 2nd- through 5th-order harmonics. Spurious-Free Dynamic Range Spurious-free dynamic range (SFDR) is the ratio of RMS amplitude of the fundamental (maximum signal component) to the RMS value of the next largest distortion component. Chip Information TRANSISTOR COUNT: 5781 SUBSTRATE CONNECTED TO GND ______________________________________________________________________________________ 17 MAX1294/MAX1296 _________________________Definitions 420ksps, +5V, 6-/2-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface MAX1294/MAX1296 Typical Operating Circuits CLK CLK +5V MAX1294 VDD µP CONTROL INPUTS CS REF WR REFADJ 0.1µF 4.7µF RD INT D11 µP CONTROL INPUTS OUTPUT STATUS CS REF WR REFADJ D11 D10 D9 D9 D8 D8 D7 D7 CH5 CH3 D4 CH2 D3 D2 D1 D0 GND µP DATA BUS CH1 CH0 COM GND µP DATA BUS Pin Configurations (continued) TOP VIEW D9 1 28 D10 D8 2 27 D11 D7 3 26 VDD D6 4 25 REF D5 5 D4 6 24 REFADJ MAX1294 23 GND D3 7 22 COM D2 8 21 CH0 D1 9 20 CH1 D0 10 19 CH2 INT 11 18 CH3 RD 12 17 CH4 WR 13 16 CH5 CLK 14 15 CS QSOP 18 OUTPUT STATUS D3 COM D0 INT D5 CH0 D1 4.7µF D4 ANALOG INPUTS CH1 D2 0.1µF D6 CH4 D5 +2.5V RD D10 D6 +5V MAX1296 VDD +2.5V ______________________________________________________________________________________ ANALOG INPUTS 420ksps, +5V, 6-/2-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface QSOP.EPS ______________________________________________________________________________________ 19 MAX1294/MAX1296 Package Information MAX1294/MAX1296 420ksps, +5V, 6-/2-Channel, 12-Bit ADCs with +2.5V Reference and Parallel Interface NOTES Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are implied. Maxim reserves the right to change the circuitry and specifications without notice at any time. 20 ____________________Maxim Integrated Products, 120 San Gabriel Drive, Sunnyvale, CA 94086 408-737-7600 © 1999 Maxim Integrated Products Printed USA is a registered trademark of Maxim Integrated Products.