TC7106/A/TC7107/A 3-1/2 Digit Analog-to-Digital Converters Features: General Description: • Internal Reference with Low Temperature Drift: - TC7106/TC7107: 80 ppm/°C (Typical) - TC7106A/TC7107A: 20 ppm/°C (Typical) • Drives LCD (TC7106) or LED (TC7107) Display Directly • Zero Reading with Zero Input • Low Noise for Stable Display • Auto-Zero Cycle Eliminates Need for Zero Adjustment • True Polarity Indication for Precision Null Applications • Convenient 9V Battery Operation (TC7106A) • High-Impedance CMOS Differential Inputs: 1012Ω • Differential Reference Inputs Simplify Ratiometric Measurements • Low-Power Operation: 10 mW The TC7106A and TC7107A 3-1/2 digit direct display drive Analog-to-Digital Converters allow existing TC7106/TC7107 based systems to be upgraded. Each device has a precision reference with a 20 ppm/°C maximum temperature coefficient. This represents a 4 to 7 times improvement over similar 3-1/2 digit converters. Existing TC7106 and TC7107 based systems may be upgraded without changing external passive component values. The TC7107A drives common anode light emitting diode (LED) displays directly with 8 mA per segment. A low cost, high resolution indicating meter requires only a display, four resistors, and four capacitors. The TC7106A low-power drain and 9V battery operation make it suitable for portable applications. Applications: • Thermometry • Bridge Readouts: Strain Gauges, Load Cells, Null Detectors • Digital Meters: Voltage/Current/Ohms/Power, pH • Digital Scales, Process Monitors • Portable Instrumentation © 2008 Microchip Technology Inc. The TC7106A/TC7107A reduces linearity error to less than 1 count. Rollover error – the difference in readings for equal magnitude, but opposite polarity input signals, is below ±1 count. High-impedance differential inputs offer 1 pA leakage current and a 1012Ω input impedance. The differential reference input allows ratiometric measurements for ohms or bridge transducer measurements. The 15 µVP–P noise performance ensures a “rock solid” reading. The autozero cycle ensures a zero display reading with a zero volts input. DS21455D-page 1 TC7106/A/TC7107/A Package Type NC OSC1 REF HI V+ TEST D1 OSC3 C1 OSC2 B1 44 43 42 41 40 F1 7 39 REF LO VREF- G1 8 38 CREF CREF- E1 9 37 CREF D2 10 36 COMMON CREFANALOG COMMON VIN+ TC7106ACLW TC7107ACLW 12 B2 13 100s' 34 NC 33 IN LO A2 14 32 A/Z F2 15 31 BUFF E2 16 30 INT D2 17 29 V- G2 C3 A3 G3 18 19 20 21 22 23 24 25 26 27 28 21 BP/GND (7106A/7107A) BP/GND 24 C3 23 A3 22 G3 35 IN HI C2 11 30 VIN29 CAZ 28 VBUFF 27 VINT 26 V25 G2 NC E3 18 AB4 19 POL 20 (Minus Sign) 1000s' 1 POL 100s' D3 15 B3 16 F3 17 2 V- 10s' C2 B2 11 A2 12 F2 13 E2 14 3 AB4 D2 4 INT E1 5 E3 G1 35 34 7 33 8 9 TC7106ACPL 32 TC7107AIPL 31 10 6 BUFF B1 4 A1 5 F1 6 40 OSC1 39 OSC2 38 OSC3 37 TEST 36 VREF+ F3 1s' Normal Pin Configuration B3 V+ 1 D1 2 C1 3 44-Pin PLCC A1 40-Pin PDIP A/Z IN LO IN HI COM CREF CREF REF LO REF HI 44-Pin MQFP 44 43 42 41 40 39 38 37 36 35 34 NC 1 33 NC NC 2 32 G2 TEST 3 31 C3 OSC3 4 30 A3 29 G3 NC 5 TC7106ACKW TC7107ACKW OSC2 6 OSC1 7 28 BP/GND 27 POL V+ 8 26 AB4 D1 9 25 E3 C1 10 24 F3 B1 11 23 B3 DS21455D-page 2 D3 E2 F2 A2 B2 C1 D1 E1 G1 F1 A1 12 13 14 15 16 17 18 19 20 21 22 © 2008 Microchip Technology Inc. TC7106/A/TC7107/A Typical Application 0.1 µF 1 MΩ + Analog Input 0.01 µF – 31 CREF+ C REF LCD Display (TC7106/A) or Common Node with LED Display (TC7107/A) 2 - 19 22 - 25 30 VIN - POL 32 ANALOG COMMON BP V+ 27 20 21 Minus Sign Backplane Drive 1 24 kΩ + VBUFF VREF VREF + 36 CAZ 1 kΩ 9V VREF - 35 100 mV VINT OSC2 OSC3 39 38 C VOSC1 OSC R OSC 100 kΩ © 2008 Microchip Technology Inc. Segment Drive TC7106/A TC7107/A 0.47 µF 29 0.22 µF 33 VIN + 28 47 kΩ 34 100 pF 40 26 To Analog Common (Pin 32) 3 Conversions/Sec 200 mV Full Scale DS21455D-page 3 TC7106/A/TC7107/A 1.0 ELECTRICAL CHARACTERISTICS TC7107A Supply Voltage (V+) .......................................................... +6V Supply Voltage (V-) ............................................................-9V Analog Input Voltage (either Input) (Note 1) .............. V+ to V- Absolute Maximum Ratings† TC7106A Supply Voltage (V+ to V-) ..................................................15V Analog Input Voltage (either Input) (Note 1) .............. V+ to VReference Input Voltage (either Input) ....................... V+ to VClock Input .............................................................. Test to V+ Package Power Dissipation (TA ≤ 70°C) (Note 2): 40-Pin PDIP ......................................................1.23W 44-Pin PLCC.....................................................1.23W 44-Pin MQFP ....................................................1.00W Operating Temperature Range: C (Commercial) Devices........................0°C to +70°C I (Industrial) Devices ..........................-25°C to +85°C Storage Temperature Range .........................-65°C to +150°C Reference Input Voltage (either Input)....................... V+ to VClock Input............................................................. GND to V+ Package Power Dissipation (TA ≤ 70°C) (Note 2): 40-Pin PDIP...................................................... 1.23W 44-Pin PLCC .................................................... 1.23W 44-Pin MQFP.................................................... 1.00W Operating Temperature Range: C (Commercial) Devices ....................... 0°C to +70°C I (Industrial) Devices.......................... -25°C to +85°C Storage Temperature Range......................... -65°C to +150°C † Notice: Stresses above those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only and functional operation of the device at these or any other conditions above those indicated in the operation sections of the specifications is not implied. Exposure to Absolute Maximum Rating conditions for extended periods may affect device reliability. TC7106/A AND TC7107/A ELECTRICAL SPECIFICATIONS Electrical Characteristics: Unless otherwise noted, specifications apply to both the TC7106/TC7106A and TC7107/TC7107A at TA = +25°C, fCLOCK = 48 kHz. Parts are tested in the circuit of the Typical Operating Circuit. Parameter Min Typ Max -000.0 ±000.0 +000.0 999 999/1000 1000 -1 ±0.2 +1 Counts VIN- = + VIN+ ≅ 200 mV Linearity (Maximum Deviation from Best Straight Line Fit) -1 ±0.2 +1 Counts Full Scale = 200 mV or Full Scale = 2.000V Common Mode Rejection Ratio (Note 3) CMRR — 50 — µV/V VCM = ±1V, VIN = 0V, Full Scale = 200.0 mV Noise (Peak to Peak Value not Exceeded 95% of Time) eN — 15 — µV VIN = 0V Full Scale - 200.0 mV Leakage Current at Input IL Zero Input Reading Symbol ZIR Ratiometric Reading Rollover Error (Difference in Reading for Equal Positive and Negative Reading Near Full Scale) R/O Zero Reading Drift Scale Factor Temperature Coefficient TCSF Unit Digital VIN = 0.0V Reading Full Scale = 200.0 mV Digital VIN = VREF Reading VREF = 100 mV — 1 10 pA — 0.2 1 µV/°C VIN = 0V “C” Device = 0°C to +70°C — 1.0 2 µV/°C VIN = 0V “I” Device = -25°C to +85°C — 1 5 ppm/°C VIN = 199.0 mV, “C” Device = 0°C to +70°C (Ext. Ref = 0 ppm°C) — — 20 ppm/°C VIN = 199.0 mV “I” Device = -25°C to +85°C Supply Current (Does not include LED Current For TC7107/A) IDD — 0.8 1.8 mA Analog Common Voltage (with Respect to Positive Supply) VC 2.7 3.05 3.35 V Note 1: 2: 3: 4: Test Conditions VIN = 0V VIN = 0.8 25 kΩ Between Common and Positive Supply Input voltages may exceed the supply voltages, provided the input current is limited to ±100 µA. Dissipation rating assumes device is mounted with all leads soldered to printed circuit board. Refer to “Differential Input” discussion. Backplane drive is in phase with segment drive for “OFF” segment, 180° out of phase for “ON” segment. Frequency is 20 times the conversion rate. Average DC component is less than 50 mV. DS21455D-page 4 © 2008 Microchip Technology Inc. TC7106/A/TC7107/A TC7106/A AND TC7107/A ELECTRICAL SPECIFICATIONS (CONTINUED) Electrical Characteristics: Unless otherwise noted, specifications apply to both the TC7106/TC7106A and TC7107/TC7107A at TA = +25°C, fCLOCK = 48 kHz. Parts are tested in the circuit of the Typical Operating Circuit. Parameter Symbol Min Typ Max Unit — — — — 25 kΩ Between Common and Positive Supply 7106/7/A 7106/7 20 80 50 — ppm/°C ppm/°C 0°C ≤ TA ≤ +70°C (“C” Commercial Temperature Range Devices) VCTC — — 75 ppm/°C 0°C ≤ TA ≤ +70°C (“I” Industrial Temperature Range Devices) TC7106A ONLY Peak to Peak Segment Drive Voltage VSD 4 5 6 V V+ to V- = 9V (Note 4) TC7106A ONLY Peak to Peak Backplane Drive Voltage VBD 4 5 6 V V+ to V- = 9V (Note 4) TC7107A ONLY Segment Sinking Current (Except Pin 19) 5 8.0 — mA V+ = 5.0V Segment Voltage = 3V TC7107A ONLY Segment Sinking Current (Pin 19) 10 16 — mA V+ = 5.0V Segment Voltage = 3V Temperature Coefficient of Analog Common (with Respect to Positive Supply) VCTC Temperature Coefficient of Analog Common (with Respect to Positive Supply) Note 1: 2: 3: 4: Test Conditions Input voltages may exceed the supply voltages, provided the input current is limited to ±100 µA. Dissipation rating assumes device is mounted with all leads soldered to printed circuit board. Refer to “Differential Input” discussion. Backplane drive is in phase with segment drive for “OFF” segment, 180° out of phase for “ON” segment. Frequency is 20 times the conversion rate. Average DC component is less than 50 mV. © 2008 Microchip Technology Inc. DS21455D-page 5 TC7106/A/TC7107/A 2.0 PIN DESCRIPTIONS The descriptions of the pins are listed in Table 2-1. TABLE 2-1: PIN FUNCTION TABLE Pin Number (40-Pin PDIP) Normal Pin No. (40-Pin PDIP) (Reversed Symbol 1 (40) V+ Positive supply voltage. Description 2 (39) D1 Activates the D section of the units display. 3 (38) C1 Activates the C section of the units display. 4 (37) B1 Activates the B section of the units display. 5 (36) A1 Activates the A section of the units display. 6 (35) F1 Activates the F section of the units display. 7 (34) G1 Activates the G section of the units display. 8 (33) E1 Activates the E section of the units display. 9 (32) D2 Activates the D section of the tens display. 10 (31) C2 Activates the C section of the tens display. 11 (30) B2 Activates the B section of the tens display. 12 (29) A2 Activates the A section of the tens display. 13 (28) F2 Activates the F section of the tens display. 14 (27) E2 Activates the E section of the tens display. 15 (26) D3 Activates the D section of the hundreds display. 16 (25) B3 Activates the B section of the hundreds display. 17 (24) F3 Activates the F section of the hundreds display. 18 (23) E3 Activates the E section of the hundreds display. 19 (22) AB4 20 (21) POL 21 (20) BP/GND 22 (19) G3 Activates the G section of the hundreds display. 23 (18) A3 Activates the A section of the hundreds display. 24 (17) C3 Activates the C section of the hundreds display. 25 (16) G2 Activates the G section of the tens display. Activates both halves of the 1 in the thousands display. Activates the negative polarity display. LCD Backplane drive output (TC7106A). Digital Ground (TC7107A). 26 (15) V- 27 (14) VINT Integrator output. Connection point for integration capacitor. See INTEGRATING CAPACITOR section for more details. Negative power supply voltage. 28 (13) VBUFF Integration resistor connection. Use a 47 kΩ resistor for a 200 mV full scale range and a 47 kΩ resistor for 2V full scale range. 29 (12) CAZ The size of the auto-zero capacitor influences system noise. Use a 0.47 µF capacitor for 200 mV full scale, and a 0.047 µF capacitor for 2V full scale. See Section 7.1 “Auto-Zero Capacitor (CAZ)” on Auto-Zero Capacitor for more details. 30 (11) VIN- The analog LOW input is connected to this pin. 31 (10) VIN+ The analog HIGH input signal is connected to this pin. 32 (9) ANALOG This pin is primarily used to set the Analog Common mode voltage for battery COMMON operation or in systems where the input signal is referenced to the power supply. It also acts as a reference voltage source. See Section 8.3 “Analog Common (Pin 32)” on ANALOG COMMON for more details. 33 (8) CREF- See Pin 34. 34 (7) CREF+ A 0.1 µF capacitor is used in most applications. If a large Common mode voltage exists (for example, the VIN- pin is not at analog common), and a 200 mV scale is used, a 1 µF capacitor is recommended and will hold the rollover error to 0.5 count. 35 (6) VREF- See Pin 36. DS21455D-page 6 © 2008 Microchip Technology Inc. TC7106/A/TC7107/A TABLE 2-1: PIN FUNCTION TABLE (CONTINUED) Pin Number (40-Pin PDIP) Normal Pin No. (40-Pin PDIP) (Reversed Symbol Description 36 (5) VREF+ The analog input required to generate a full scale output (1999 counts). Place 100 mV between Pins 35 and 36 for 199.9 mV full scale. Place 1V between Pins 35 and 36 for 2V full scale. See paragraph on Reference Voltage. 37 (4) TEST Lamp test. When pulled HIGH (to V+) all segments will be turned on and the display should read -1888. It may also be used as a negative supply for externally generated decimal points. See paragraph under TEST for additional information. 38 (3) OSC3 See Pin 40. 39 (2) OSC2 See Pin 40. 40 (1) OSC1 Pins 40, 39, 38 make up the oscillator section. For a 48 kHz clock (3 readings per section), connect Pin 40 to the junction of a 100 kΩ resistor and a 100 pF capacitor. The 100 kΩ resistor is tied to Pin 39 and the 100 pF capacitor is tied to Pin 38. © 2008 Microchip Technology Inc. DS21455D-page 7 TC7106/A/TC7107/A 3.0 DETAILED DESCRIPTION (All Pin designations refer to 40-Pin PDIP.) 3.1 For a constant VIN: EQUATION 3-2: Dual Slope Conversion Principles The TC7106A and TC7107A are dual slope, integrating Analog-to-Digital Converters. An understanding of the dual slope conversion technique will aid in following the detailed operation theory. The conventional dual slope converter measurement cycle has two distinct phases: • Input Signal Integration • Reference Voltage Integration (De-integration) The input signal being converted is integrated for a fixed time period (TSI). Time is measured by counting clock pulses. An opposite polarity constant reference voltage is then integrated until the integrator output voltage returns to zero. The reference integration time is directly proportional to the input signal (TRI). See Figure 3-1. VIN = VR TRI TSI The dual slope converter accuracy is unrelated to the integrating resistor and capacitor values as long as they are stable during a measurement cycle. An inherent benefit is noise immunity. Noise spikes are integrated or averaged to zero during the integration periods. Integrating ADCs are immune to the large conversion errors that plague successive approximation converters in high noise environments. Interfering signals with frequency components at multiples of the averaging period will be attenuated. Integrating ADCs commonly operate with the signal integration period set to a multiple of the 50/60Hz power line period (see Figure 3-2). C Analog Input Signal Integrator – + +/– Comparator – + Switch Driver Phase Control Polarity Control REF Voltage Control Logic Normal Mode Rejection (dB) 30 20 10 T = Measured Period 0 Output Integrator DISPLAY Counter VIN µ VREF VIN µ1/2 VREF Fixed Signal Integrate Time Variable Reference Integrate Time FIGURE 3-1: 0.1/T EQUATION 3-1: 10/T FIGURE 3-2: Normal Mode Rejection of Dual Slope Converter. Basic Dual Slope Converter. In a simple dual slope converter, a complete conversion requires the integrator output to “ramp-up” and “ramp-down.” A simple mathematical equation relates the input signal, reference voltage and integration time. 1/T Input Frequency C INT Where: V FS 1 ( 4000 ) ⎛ -------------⎞ ⎛ -----------⎞ ⎝ F OSC⎠ ⎝ R INT⎠ = -----------------------------------------------------V INT FOSC = Clock Frequency at Pin 38 VFS = Full Scale Input Voltage RINT = Integrating Resistor VINT = Desired Full Scale Integrator Output Swing V R T RI 1 - T SI ------V IN ( t )dt = -------------∫ RC 0 RC Where: VR = Reference voltage TSI = Signal integration time (fixed) TRI = Reference voltage integration time (variable). DS21455D-page 8 © 2008 Microchip Technology Inc. TC7106/A/TC7107/A 4.0 ANALOG SECTION In addition to the basic signal integrate and deintegrate cycles discussed, the circuit incorporates an auto-zero cycle. This cycle removes buffer amplifier, integrator, and comparator offset voltage error terms from the conversion. A true digital zero reading results without adjusting external potentiometers. A complete conversion consists of three cycles: an auto-zero, signal integrate, and reference integrate cycle. 4.1 Auto-Zero Cycle During the auto-zero cycle, the differential input signal is disconnected from the circuit by opening internal analog gates. The internal nodes are shorted to analog common (ground) to establish a zero input condition. Additional analog gates close a feedback loop around the integrator and comparator. This loop permits comparator offset voltage error compensation. The voltage level established on CAZ compensates for device offset voltages. The offset error referred to the input is less than 10 µV. 4.3 Reference Integrate Phase The third phase is reference integrate or de-integrate. VIN- is internally connected to analog common and VIN+ is connected across the previously charged reference capacitor. Circuitry within the chip ensures that the capacitor will be connected with the correct polarity to cause the integrator output to return to zero. The time required for the output to return to zero is proportional to the input signal and is between 0 and 2000 counts. The digital reading displayed is: EQUATION 4-2: V IN 1000 = -----------V REF The auto-zero cycle length is 1000 to 3000 counts. 4.2 Signal Integrate Cycle The auto-zero loop is entered and the internal differential inputs connect to VIN+ and VIN-. The differential input signal is integrated for a fixed time period. The TC7106/TC7106A signal integration period is 1000 clock periods or counts. The externally set clock frequency is divided by four before clocking the internal counters. The integration time period is: EQUATION 4-1: 4 T SI = ------------- × 1000 F OSC Where: FOSC = Externally set clock frequency The differential input voltage must be within the device Common mode range when the converter and measured system share the same power supply common (ground). If the converter and measured system do not share the same power supply common, VIN- should be tied to analog common. Polarity is determined at the end of signal integrate phase. The sign bit is a true polarity indication, in that signals less than 1 LSB are correctly determined. This allows precision null detection limited only by device noise and auto-zero residual offsets. © 2008 Microchip Technology Inc. DS21455D-page 9 TC7106/A/TC7107/A 5.0 DIGITAL SECTION (TC7106A) The TC7106A (Figure 5-2) contains all the segment drivers necessary to directly drive a 3-1/2 digit liquid crystal display (LCD). An LCD backplane driver is included. The backplane frequency is the external clock frequency divided by 800. For three conversions per second, the backplane frequency is 60Hz with a 5V nominal amplitude. When a segment driver is in phase with the backplane signal, the segment is “OFF.” An out of phase segment drive signal causes the segment to be “ON” or visible. This AC drive configuration results in negligible DC voltage across each LCD segment. This insures long LCD display life. The polarity segment driver is “ON” for negative analog inputs. If VIN+ and VIN- are reversed, this indicator will reverse. When the TEST pin on the TC7106A is pulled to V+, all segments are turned “ON.” The display reads -1888. During this mode, the LCD segments have a constant DC voltage impressed. DO NOT LEAVE THE DISPLAY IN THIS MODE FOR MORE THAN SEVERAL MINUTES! LCD displays may be destroyed if operated with DC levels for extended periods. The display font and the segment drive assignment are shown in Figure 5-1. Display Font 1000s' FIGURE 5-1: Assignment 100s' 10s' 1s' Display Font and Segment In the TC7106A, an internal digital ground is generated from a 6-volt zener diode and a large P channel source follower. This supply is designed to absorb the large capacitive currents when the backplane voltage is switched. DS21455D-page 10 © 2008 Microchip Technology Inc. FIGURE 5-2: © 2008 Microchip Technology Inc. VIN - ANALOG COMMON VIN + INT 30 32 A/Z INT 31 10 mA 34 DE (–) DE (+) V- A/Z 35 VREF - AZ & DE (±) DE (+) DE (–) A/Z 36 +CREFVREF + CREF + – + – 26 V+ – 3.0V 33 CREF - VBUFF TC7106A 1 Low Tempco VREF 28 V+ RINT – + 27 Thousands To Digital Section ROSC 39 OSC2 Clock COSC 38 OSC3 µ4 Hundreds 7 Segment Decode VTH = 1V Control Logic Tens Data Latch 7 Segment Decode LCD Segment Drivers LCD Display Internal Digital Ground FOSC To Switch Drivers From Comparator Output VINT CINT Comparator 40 OSC1 A/Z + – 29 Integrator CAZ V+ Segment Output Internal Digital Ground 2 mA 0.5 mA Typical Segment Output Units 7 Segment Decode 500 Ω 6.2V 26 37 1 V- V+ Backplane µ 200 21 TEST TC7106/A/TC7107/A TC7106A Block Diagram. DS21455D-page 11 TC7106/A/TC7107/A 6.0 DIGITAL SECTION (TC7107A) Figure 6-2 shows a TC7106A block diagram. It is designed to drive common anode LEDs. It is identical to the TC7106A, except that the regulated supply and backplane drive have been eliminated and the segment drive is typically 8 mA. The 1000’s output (Pin 19) sinks current from two LED segments, and has a 16 mA drive capability. 6.2 Clock Circuit Three clocking methods may be used (see Figure 6-1): 1. 2. 3. An external oscillator connected to Pin 40. A crystal between Pins 39 and 40. An RC oscillator using all three pins. TC7106A TC7107A In both devices, the polarity indication is “ON” for negative analog inputs. If VIN- and VIN+ are reversed, this indication can be reversed also, if desired. µ4 To Counter The display font is the same as the TC7106A. 40 6.1 System Timing The oscillator frequency is divided by 4 prior to clocking the internal decade counters. The four-phase measurement cycle takes a total of 4000 counts, or 16,000 clock pulses. The 4000-count cycle is independent of input signal magnitude. 39 38 Crystal EXT OSC RC Network To TEST Pin on TSC7106A To GND Pin on TSC7107A FIGURE 6-1: Clock Circuits. Each phase of the measurement cycle has the following length: 1. Auto-zero phase: 1000 to 3000 counts (4000 to 12000 clock pulses). For signals less than full scale, the auto-zero phase is assigned the unused reference integrate time period: 2. Signal integrate: 1000 counts (4000 clock pulses). This time period is fixed. The integration period is: EQUATION 6-1: 4 T SI = ------------- × 1000 F OSC Where: FOSC 3. = Externally set clock frequency Reference Integrate: 0 to 2000 counts (0 to 8000 clock pulses). The TC7106A/TC7107A are drop-in replacements for the TC7106/TC7107 parts. External component value changes are not required to benefit from the low drift internal reference. DS21455D-page 12 © 2008 Microchip Technology Inc. FIGURE 6-2: © 2008 Microchip Technology Inc. VIN - ANALOG COMMON VIN + 30 32 31 INT A/Z DE (–) DE (+) 35 VREF - AZ & DE (±) DE (+) DE (–) A/Z 36 VREF + 34 INT 10 mA CREF + CREF 26 V- – + + – V+ – 3.0V 33 CREF- VBUFF TC7107A 1 Low Tempco VREF 28 V+ RINT – + 27 ROSC 39 OSC2 Clock Thousands To Digital Section COSC 38 OSC3 FOSC To Switch Drivers from Comparator Output CINT VINT Comparator 40 OSC1 A/Z + – 29 Integrator CAZ V+ Segment Output Internal Digital Ground 8 mA 0.5 mA Typical Segment Output 7 Segment Decode Logic Control Tens Data Latch Digital Ground µ4 Hundreds 7 Segment Decode LCD Segment Drivers Led Display 500Ω Units 37 TEST 7 Segment Decode 21 1 Digital Ground V+ TC7106/A/TC7107/A TC7107A Block Diagram. DS21455D-page 13 TC7106/A/TC7107/A 7.0 COMPONENT VALUE SELECTION 7.1 Auto-Zero Capacitor (CAZ) The CAZ capacitor size has some influence on system noise. A 0.47 µF capacitor is recommended for 200 mV full scale applications where 1LSB is 100 µV. A 0.047 µF capacitor is adequate for 2.0V full scale applications. A mylar type dielectric capacitor is adequate. 7.2 7.4 Integrating Resistor (RINT) The input buffer amplifier and integrator are designed with class A output stages. The output stage idling current is 100 µA. The integrator and buffer can supply 20 µA drive currents with negligible linearity errors. RINT is chosen to remain in the output stage linear drive region, but not so large that printed circuit board leakage currents induce errors. For a 200 mV full scale, RINT is 47 kΩ. 2.0V full scale requires 470 kΩ. TABLE 7-1: COMPONENT VALUES AND NOMINAL FULL SCALE VOLTAGE Component Value Nominal Full Scale Voltage 200.0 mV 2.000V CAZ 0.47 µF 0.047 µF RINT 47 kΩ 470 kΩ 0.22 µF 0.22 µF Reference Voltage Capacitor (CREF) The reference voltage used to ramp the integrator output voltage back to zero during the reference integrate cycle is stored on CREF. A 0.1 µF capacitor is acceptable when VIN- is tied to analog common. If a large Common mode voltage exists (VREF- – analog common) and the application requires 200 mV full scale, increase CREF to 1.0 µF. Rollover error will be held to less than 1/2 count. A mylar dielectric capacitor is adequate. 7.3 Integrating Capacitor (CINT) CINT should be selected to maximize the integrator output voltage swing without causing output saturation. Due to the TC7106A/TC7107A superior temperature coefficient specification, analog common will normally supply the differential voltage reference. For this case, a ±2V full scale integrator output swing is satisfactory. For 3 readings/second (FOSC = 48 kHz), a 0.22 µF value is suggested. If a different oscillator frequency is used, CINT must be changed in inverse proportion to maintain the nominal ±2V integrator swing. An exact expression for CINT is: EQUATION 7-1: C INT Where: V FS 1 ( 4000 ) ⎛⎝ -------------⎞⎠ ⎛⎝ -----------⎞⎠ F OSC R INT = ----------------------------------------------------V INT FOSC = Clock Frequency at Pin 38 VFS = Full Scale Input Voltage RINT = Integrating Resistor VINT = Desired Full Scale Integrator Output Swing CINT must have low dielectric absorption to minimize rollover error. A polypropylene capacitor is recommended. CINT Note: 7.5 FOSC = 48 kHz (3 readings per sec). Oscillator Components ROSC (Pin 40 to Pin 39) should be 100 kΩ. COSC is selected using the equation: EQUATION 7-2: F OSC = 0.45 ---------RC Where: FOSC = 48 kHz COSC = 100 pF Note that FOSC is divided by four to generate the TC7106A internal control clock. The backplane drive signal is derived by dividing FOSC by 800. To achieve maximum rejection of 60 Hz noise pickup, the signal integrate period should be a multiple of 60 Hz. Oscillator frequencies of 240 kHz, 120 kHz, 80 kHz, 60 kHz, 48 kHz, 40 kHz, etc. should be selected. For 50 Hz rejection, oscillator frequencies of 200 kHz, 100 kHz, 66-2/3 kHz, 50 kHz, 40 kHz, etc. would be suitable. Note that 40 kHz (2.5 readings/ second) will reject both 50 Hz and 60 Hz. 7.6 Reference Voltage Selection A full scale reading (2000 counts) requires the input signal be twice the reference voltage. Required Full Scale Voltage* VREF 200.0 mV 100.0 mV 2.000V 1.000V * VFS = 2VREF DS21455D-page 14 © 2008 Microchip Technology Inc. TC7106/A/TC7107/A In some applications, a scale factor other than unity may exist between a transducer output voltage and the required digital reading. Assume, for example, a pressure transducer output is 400 mV for 2000 lb/in2. Rather than dividing the input voltage by two, the reference voltage should be set to 200 mV. This permits the transducer input to be used directly. The differential reference can also be used when a digital zero reading is required when VIN is not equal to zero. This is common in temperature measuring instrumentation. A compensating offset voltage can be applied between analog common and VIN-. The transducer output is connected between VIN+ and analog common. The internal voltage reference potential available at analog common will normally be used to supply the converter’s reference. This potential is stable whenever the supply potential is greater than approximately 7V. In applications where an externally generated reference voltage is desired, refer to Figure 7-1. © 2008 Microchip Technology Inc. V+ V+ V+ VREF + 6.8V Zener V 6.8 kΩ TC7106A 20 kΩ TC7107A REF - TC7106A TC7107A V+ IZ VREF + VREF - 1.2V Ref Common (a) (b) FIGURE 7-1: External Reference. DS21455D-page 15 TC7106/A/TC7107/A 8.0 DEVICE PIN FUNCTIONAL DESCRIPTION 8.1 Differential Signal Inputs VIN+ (Pin 31), VIN- (Pin 30) 8.2 The reference voltage can be generated anywhere within the V+ to V- power supply range. The TC7106A/TC7107A is designed with true differential inputs and accepts input signals within the input stage common mode voltage range (VCM). The typical range is V+ – 1.0 to V+ + 1V. Common mode voltages are removed from the system when the TC7106A/TC7107A operates from a battery or floating power source (isolated from measured system) and VIN- is connected to analog common (VCOM) (see Figure 8-2). In systems where Common mode voltages exist, the 86 dB Common mode rejection ratio minimizes error. Common mode voltages do, however, affect the integrator output level. Integrator output saturation must be prevented. A worst-case condition exists if a large positive VCM exists in conjunction with a full scale negative differential signal. The negative signal drives the integrator output positive along with VCM (see Figure 8-1). For such applications the integrator output swing can be reduced below the recommended 2.0V full scale swing. The integrator output will swing within 0.3V of V+ or V- without increasing linearity errors. CI Input Buffer + RI + – VIN – VI + Integrator – Where: TI RI CI [ VCM – V IN TI = Integration Time = [ VI = VCM Differential Reference VREF+ (Pin 36), VREF- (Pin 35) 4000 FOSC To prevent rollover type errors being induced by large Common mode voltages, CREF should be large compared to stray node capacitance. The TC7106A/TC7107A circuits have a significantly lower analog common temperature coefficient. This gives a very stable voltage suitable for use as a reference. The temperature coefficient of analog common is 20 ppm/°C typically. 8.3 Analog Common (Pin 32) The analog common pin is set at a voltage potential approximately 3.0V below V+. The potential is between 2.7V and 3.35V below V+. Analog common is tied internally to the N channel FET capable of sinking 20 mA. This FET will hold the common line at 3.0V should an external load attempt to pull the common line toward V+. Analog common source current is limited to 10 µA. Analog common is, therefore, easily pulled to a more negative voltage (i.e., below V+ – 3.0V). The TC7106A connects the internal VIN+ and VINinputs to analog common during the auto-zero cycle. During the reference integrate phase, VIN- is connected to analog common. If VIN- is not externally connected to analog common, a Common mode voltage exists. This is rejected by the converter’s 86 dB Common mode rejection ratio. In battery operation, analog common and VIN- are usually connected, removing Common mode voltage concerns. In systems where V- is connected to the power supply ground, or to a given voltage, analog common should be connected to VIN-. CI = Integration Capacitor RI = Integration Resistor FIGURE 8-1: Common Mode Voltage Reduces Available Integrator Swing (VCOM ≠ VIN). DS21455D-page 16 © 2008 Microchip Technology Inc. TC7106/A/TC7107/A Segment Drive Measured System V BUF V IN + V+ V- V+ V- V IN GND Analog Common C AZ V INT POL BP OSC1 TC7106A OSC3 V REF - V REF+ GND + 9V Common Mode Voltage Removed in Battery Operation with VIN- = Analog Common. With sufficiently high total supply voltage (V+ – V- > 7.0V), analog common is a very stable potential with excellent temperature stability, typically 20 ppm/°C. This potential can be used to generate the reference voltage. An external voltage reference will be unnecessary in most cases because of the 50 ppm/°C maximum temperature coefficient. See Section 8.5 “Internal Voltage Reference”. TEST (Pin 37) The TEST pin potential is 5V less than V+. TEST may be used as the negative power supply connection for external CMOS logic. The TEST pin is tied to the internally generated negative logic supply (Internal Logic Ground) through a 500Ω resistor in the TC7106A. The TEST pin load should be no more than 1 mA. external voltage references. External R and C values do not need to be changed. Figure 8-4 shows analog common supplying the necessary voltage reference for the TC7106A/TC7107A. 200 180 Temperature Coefficient (ppm/°C) The analog common pin serves to set the analog section reference or common point. The TC7106A is specifically designed to operate from a battery, or in any measurement system where input signals are not referenced (float), with respect to the TC7106A power source. The analog common potential of V+ – 3.0V gives a 6V end of battery life voltage. The common potential has a 0.001% voltage coefficient and a 15Ω output impedance. 8.4 OSC2 V- V+ Power Source FIGURE 8-2: LCD Display No Maximum Specified 160 140 Typical 120 100 80 Maximum Limit 40 20 0 TC 7106A ICL7106 ICL7136 FIGURE 8-3: Analog Common Temperature Coefficient. 1 V+ V- 24kΩ TC7106A TC7107A VREF + 36 1kΩ VREF VREF - 35 Analog 32 Common Internal Voltage Reference © 2008 Microchip Technology Inc. Typical Typical The TEST pin will sink about 10 mA when pulled to V+. The analog common voltage temperature stability has been significantly improved (Figure 8-3). The “A” version of the industry standard circuits allow users to upgrade old systems and design new systems without No Maximum Specified 60 If TEST is pulled to V+ all segments plus the minus sign will be activated. Do not operate in this mode for more than several minutes with the TC7106A. With TEST = V+, the LCD segments are impressed with a DC voltage which will destroy the LCD. 8.5 No Maximum Specified Set VREF = 1/2 V FULL SCALE FIGURE 8-4: Connection. Internal Voltage Reference DS21455D-page 17 TC7106/A/TC7107/A 9.0 POWER SUPPLIES 9.1 The TC7107A is designed to work from ±5V supplies. However, if a negative supply is not available, it can be generated from the clock output with two diodes, two capacitors, and an inexpensive IC (Figure 9-1). V+ CD4009 V+ OSC1 OSC2 0.047 µF OSC3 TC7107A 1N914 + – 10 µF 1N914 TC7107 Power Dissipation Reduction The TC7107A sinks the LED display current and this causes heat to build up in the IC package. If the internal voltage reference is used, the changing chip temperature can cause the display to change reading. By reducing the LED common anode voltage, the TC7107A package power dissipation is reduced. Figure 9-3 is a curve tracer display showing the relationship between output current and output voltage for a typical TC7107CPL. Since a typical LED has 1.8 volts across it at 7 mA, and its common anode is connected to +5V, the TC7107A output is at 3.2V (point A on Figure 9-3). Maximum power dissipation is 8.1 mA x 3.2V x 24 segments = 622 mW. GND V- 10.000 FIGURE 9-1: From +5V. Generating Negative Supply In selected applications a negative supply is not required. The conditions to use a single +5V supply are: • The input signal can be referenced to the center of the Common mode range of the converter. • The signal is less than ±1.5V. • An external reference is used. The TSC7660 DC-to-DC converter may be used to generate -5V from +5V (Figure 9-2). 1 36 V+ V REF + VREF COM 35 32 TC7107A VIN + 31 VIN VIN - 30 V- GND 26 8 + 10 µF 2 4 TC7660 5 21 (-5V) 9.000 A 8.000 B C 7.000 6.000 2.00 2.50 3.00 3.50 4.00 Output Voltage (V) FIGURE 9-3: Output Voltage. TC7107 Output Current vs. Notice, however, that once the TC7107A output voltage is above two volts, the LED current is essentially constant as output voltage increases. Reducing the output voltage by 0.7V (point B in Figure 9-3) results in 7.7 mA of LED current, only a 5 percent reduction. Maximum power dissipation is only 7.7 mA x 2.5V x 24 = 462 mW, a reduction of 26%. An output voltage reduction of 1 volt (point C) reduces LED current by 10% (7.3 mA) but power dissipation by 38% (7.3 mA x 2.2V x 24 = 385 mW). +5V LED DRIVE Output Current (mA) V- = -3.3V Reduced power dissipation is very easy to obtain. Figure 9-4 shows two ways: either a 5.1Ω, 1/4W resistor, or a 1A diode placed in series with the display (but not in series with the TC7107A). The resistor will reduce the TC7107A output voltage, when all 24 segments are “ON,” to point “C” of Figure 9-4. When segments turn off, the output voltage will increase. The diode, on the other hand, will result in a relatively steady output voltage, around point “B”. 3 + 10 µF FIGURE 9-2: Negative Power Supply Generation with TC7660. DS21455D-page 18 © 2008 Microchip Technology Inc. TC7106/A/TC7107/A In addition to limiting maximum power dissipation, the resistor reduces the change in power dissipation as the display changes. This effect is caused by the fact that, as fewer segments are “ON,” each “ON” output drops more voltage and current. For the best case of six segments (a “111” display) to worst-case (a “1888” display), the resistor will change about 230 mW, while a circuit without the resistor will change about 470 mW. Therefore, the resistor will reduce the effect of display dissipation on reference voltage drift by about 50%. The change in LED brightness caused by the resistor is almost unnoticeable as more segments turn off. If display brightness remaining steady is very important to the designer, a diode may be used instead of the resistor. 24 kΩ -5V IN +5V + – 1 MΩ 150Ω TP3 1 kΩ 100 pF TP5 100 kΩ TP2 TP1 0.47 µF 0.01 µF 0.22 µF Display 0.1 µF 47 kΩ 40 30 TP 4 21 TC7107A 1 10 5.1Ω 1/4W 20 Display 1N4001 FIGURE 9-4: Diode or Resistor Limits Package Power Dissipation. © 2008 Microchip Technology Inc. DS21455D-page 19 TC7106/A/TC7107/A 10.0 TYPICAL APPLICATIONS 10.1 Decimal Point and Annunciator Drive The TEST pin is connected to the internally generated digital logic supply ground through a 500Ω resistor. The TEST pin may be used as the negative supply for external CMOS gate segment drivers. LCD display annunciators for decimal points, low battery indication, or function indication may be added without adding an additional supply. No more than 1 mA should be supplied by the TEST pin; its potential is approximately 5V below V+ (see Figure 10-1). input and the voltage across the known resistor is applied to the reference input. If the unknown equals the standard, the display will read 1000. The displayed reading can be determined from the following expression: EQUATION 10-1: R UNKNOWN Displayed (Reading) = ----------------------------- × 1000 R STANDARD The display will over range for: RUNKNOWN ≥ 2 x RSTANDARD VREF + V+ VREF - RSTANDARD V+ V+ LCD Display VIN + 4049 TC7106A To LCD Decimal Point BP 21 TEST TC7106A RUNKNOWN VIN Analog Common GND 37 To LCD Backplane FIGURE 10-2: Low Parts Count Ratiometric Resistance Measurement. V+ V+ + BP 160 kΩ TC7106A 300kΩ V+ VIN- 1N4148 Sensor TEST 300 kΩ To LCD Decimal Point Decimal Point Select 4030 GND 9V R2 50 kΩ R1 50 kΩ VIN+ V- TC7106A VREF+ VFS = 2V VREFCommon FIGURE 10-1: Decimal Point Drive Using Test as Logic Ground. 10.2 Ratiometric Resistance Measurements FIGURE 10-3: Temperature Sensor. The true differential input and differential reference make ratiometric reading possible. Typically in a ratiometric operation, an unknown resistance is measured, with respect to a known standard resistance. No accurately defined reference voltage is needed. The unknown resistance is put in series with a known standard and a current passed through the pair. The voltage developed across the unknown is applied to the DS21455D-page 20 © 2008 Microchip Technology Inc. TC7106/A/TC7107/A 5.6 kΩ 160 kΩ V+ 1N914 To Pin 1 9V + R1 V- VIN- 20 kΩ VIN+ 0.7%/×C PTC R3 TC7106A R2 20 kΩ TC7107A VREF+ VREFCommon FIGURE 10-4: Positive Temperature Coefficient Resistor Temperature Sensor. Set V TC7106A 100 kΩ REF = 100 mV 100 pF 0.1 µF Set VREF = 100 mV 100 pF 0.1 µF 1 kΩ 22 kΩ 1MΩ 0.47 µF 0.22 µF IN – 47 kΩ 0.22µF -5V To Display 1 40 CC IN 0.01 µF 47 kΩ + To Logic V + + +5V 22 kΩ 1 MΩ 0.01 µF V+ 1 kΩ 0.47 µF 100 kΩ FIGURE 10-6: TC7107 Internal Reference: 200 mV Full Scale, 3RPS, VIN- Tied to GND for Single Ended Inputs. To Pin 1 40 39 38 37 36 35 34 33 32 31 30 29 28 27 26 25 24 23 22 21 40 39 38 37 36 35 34 33 32 31 30 29 28 27 26 25 24 23 22 21 TC7106A – To Logic VCC 9V – To Display To Backplane V- O/R U/R 20 FIGURE 10-5: TC7106A, Using the Internal Reference: 200 mV Full Scale, 3 Readings-PerSecond (RPS). CD4023 OR 74C10 CD4077 21 O/R = Over Range U/R = Under Range FIGURE 10-7: Circuit for Developing Under Range and Over Range Signals from TC7106A Outputs. © 2008 Microchip Technology Inc. DS21455D-page 21 TC7106/A/TC7107/A To Pin 1 Set V TC7106A TC7107A 40 39 38 37 36 35 34 33 32 31 30 29 28 27 26 25 24 23 22 21 100 kΩ REF 100 pF To PIn 1 = 1V 24 kΩ V+ 25 kΩ 0.1 µF 1 MΩ 0.047 µF + TC7107A IN 0.01 µF – 470 kΩ 0.22 µF V- To Display FIGURE 10-8: TC7106/TC7107: Recommended Component Values for 2.00V Full Scale. 40 39 38 37 36 35 34 33 32 31 30 29 28 27 26 25 24 23 22 21 100k Ω IN4148 200 mV 9 MΩ 900 kΩ 90 kΩ 1 mF 10 kΩ 2V 0.02 mF 1 MΩ 47 kΩ 1W 200V 10% 10 kΩ COM + 1.2V 1MΩ 0.01µF 0.47µF IN – 47k Ω 0.22 µF To Display FIGURE 10-9: TC7107 Operated from Single +5V Supply. 9V 26 – 1 14 2 13 4 – 6.8µF + V+ + 1 AD636 TC7106A 1 kΩ 11 28 35 V REF- 6 9 7 8 32 Analog Common 31 V + 20 kΩ 10% C1 = 3 - 10 pF Variable C2 = 132 pF Variable 1 MΩ 10% 29 36 V + REF 10 5 27 V- V+ 24 kΩ 12 3 1 MΩ 20V 10kΩ 10kΩ 1kΩ 0.1 µF + VIN Set VREF = 100mV 100pF 40 IN 2.2µF 0.01 µF 30 V IN 26 V- 38 39 SEG DRIVE BP LCD Display FIGURE 10-10: DS21455D-page 22 3-1/2 Digit True RMS AC DMM. © 2008 Microchip Technology Inc. TC7106/A/TC7107/A 9V 2 V+ 1 V+ Constant 5V VREF+ REF02 VOUT ADJ TEMP 6 51 kΩ R 5 4 NC 3 5.1 kΩ R2 R 1 1.3k 4 TC7106A VREFVFS= 2.00V 8 VINVOUT= 1.86V @ 25×C 50 kΩ R1 GND 4 FIGURE 10-11: 50 kΩ 5 2 – 3 + Temperature Dependent Output TC911 VIN+ Common V26 Integrated Circuit Temperature Sensor. © 2008 Microchip Technology Inc. DS21455D-page 23 TC7106/A/TC7107/A 11.0 PACKAGING INFORMATION 11.1 Package Marking Information Example: 40-Pin PDIP XXXXXXXXXXXXXXXXXX XXXXXXXXXXXXXXXXXX XXXXXXXXXXXXXXXXXX YYWWNNN e3 TC7106CPL^^ 0743256 *h *h 44-Pin MQFP Example: M M XXXXXXXXXX XXXXXXXXXX XXXXXXXXXX YYWWNNN TC106CKW ^^0743256 e3 44-Pin PLCC Example: 1 M M XXXXXXXXXXX XXXXXXXXXXX XXXXXXXXXXX YYWWNNN TC7106CLW e3 ^^0743256 Legend: XX...X Y YY WW NNN e3 * Note: DS21455D-page 24 Customer-specific information Year code (last digit of calendar year) Year code (last 2 digits of calendar year) Week code (week of January 1 is week ‘01’) Alphanumeric traceability code Pb-free JEDEC designator for Matte Tin (Sn) This package is Pb-free. The Pb-free JEDEC designator ( e3 ) can be found on the outer packaging for this package. In the event the full Microchip part number cannot be marked on one line, it will be carried over to the next line, thus limiting the number of available characters for customer-specific information. © 2008 Microchip Technology Inc. TC7106/A/TC7107/A /HDG3ODVWLF'XDO,Q/LQH3/±PLO%RG\>3',3@ 1RWH )RUWKHPRVWFXUUHQWSDFNDJHGUDZLQJVSOHDVHVHHWKH0LFURFKLS3DFNDJLQJ6SHFLILFDWLRQORFDWHGDW KWWSZZZPLFURFKLSFRPSDFNDJLQJ N NOTE 1 E1 1 2 3 D E A2 A L c b1 A1 b e eB 8QLWV 'LPHQVLRQ/LPLWV 1XPEHURI3LQV ,1&+(6 0,1 1 120 0$; 3LWFK H 7RSWR6HDWLQJ3ODQH $ ± ± 0ROGHG3DFNDJH7KLFNQHVV $ ± %DVHWR6HDWLQJ3ODQH $ ± ± 6KRXOGHUWR6KRXOGHU:LGWK ( ± 0ROGHG3DFNDJH:LGWK ( ± 2YHUDOO/HQJWK ' ± 7LSWR6HDWLQJ3ODQH / ± /HDG7KLFNQHVV F ± E ± E ± H% ± ± 8SSHU/HDG:LGWK /RZHU/HDG:LGWK 2YHUDOO5RZ6SDFLQJ %6& 1RWHV 3LQYLVXDOLQGH[IHDWXUHPD\YDU\EXWPXVWEHORFDWHGZLWKLQWKHKDWFKHGDUHD 6LJQLILFDQW&KDUDFWHULVWLF 'LPHQVLRQV'DQG(GRQRWLQFOXGHPROGIODVKRUSURWUXVLRQV0ROGIODVKRUSURWUXVLRQVVKDOOQRWH[FHHGSHUVLGH 'LPHQVLRQLQJDQGWROHUDQFLQJSHU$60(<0 %6& %DVLF'LPHQVLRQ7KHRUHWLFDOO\H[DFWYDOXHVKRZQZLWKRXWWROHUDQFHV 0LFURFKLS 7HFKQRORJ\ 'UDZLQJ &% © 2008 Microchip Technology Inc. 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TC7106/A/TC7107/A APPENDIX A: REVISION HISTORY Revision D (February 2008) The following is the list of modifications. 1. 2. 3. 4. Updated Section 11.0 “Packaging Information”. Added Appendix A. Updated the Product Identification System page. Revision C (April 2006) The following is the list of modifications: • Undocumented Changes. Revision B (May 2002) The following is the list of modifications: • Undocumented Changes. Revision A (April 2002) • Original Release of this Document. © 2008 Microchip Technology Inc. DS21455D-page 29 TC7106/A/TC7107/A NOTES: DS21455D-page 30 © 2008 Microchip Technology Inc. TC7106/A/TC7107/A PRODUCT IDENTIFICATION SYSTEM To order or obtain information, e.g., on pricing or delivery, refer to the factory or the listed sales office. PART NO. X XX Device Temperature Range Package Device: XXX Tape & Reel TC7106: 3-3/4 Digit A/D, with Frequency Counter and Probe TC7106A: 3-3/4 Digit A/D, with Frequency Counter and Probe TC7106: 3-3/4 Digit A/D, with Frequency Counter and Probe TC7107A: 3-3/4 Digit A/D, with Frequency Counter and Probe Examples: a) TC7106CLW: b) TC7106CPL: c) TC7106CKW713: a) TC7106ACLW: b) TC7106ACPL: Temperature Range: C I = 0°C to +70°C = -25°C to +85°C c) TC7106ACKW713: Package: = Plastic Leaded Chip Carrier (PLCC), 44-lead = Plastic DIP, (600 mil Body), 40-lead = Plastic Metric Quad Flatpack, (MQFP), 44-lead a) TC7107CLW: b) TC7107CLP: c) TC7107CKW713: a) TC7107ACLW: b) TC7107ACLP: c) TC7107ACKW: Tape & Reel: LW PL KW 713 = Tape and Reel © 2008 Microchip Technology Inc. 3-3/4 A/D Converter, 44LD PLCC package. 3-3/4 A/D Converter, 40LD PDIP package. 3-3/4 A/D Converter, 44LD MQFP package, Tape and Reel. 3-3/4 A/D Converter, 44LD PLCC package. 3-3/4 A/D Converter, 40LD PDIP package. 3-3/4 A/D Converter, 44LD MQFP package, Tape and Reel 3-3/4 A/D Converter, 44LD PLCC package. 3-3/4 A/D Converter, 40LD PDIP package. 3-3/4 A/D Converter, 44LD MQFP package Tape and Reel. 3-3/4 A/D Converter, 44LD PLCC package. 3-3/4 A/D Converter, 40LD PDIP package. 3-3/4 A/D Converter, 44LD MQFP package. DS21455D-page 31 TC7106/A/TC7107/A NOTES: DS21455D-page 32 © 2008 Microchip Technology Inc. Note the following details of the code protection feature on Microchip devices: • Microchip products meet the specification contained in their particular Microchip Data Sheet. • Microchip believes that its family of products is one of the most secure families of its kind on the market today, when used in the intended manner and under normal conditions. • There are dishonest and possibly illegal methods used to breach the code protection feature. All of these methods, to our knowledge, require using the Microchip products in a manner outside the operating specifications contained in Microchip’s Data Sheets. Most likely, the person doing so is engaged in theft of intellectual property. • Microchip is willing to work with the customer who is concerned about the integrity of their code. • Neither Microchip nor any other semiconductor manufacturer can guarantee the security of their code. Code protection does not mean that we are guaranteeing the product as “unbreakable.” Code protection is constantly evolving. We at Microchip are committed to continuously improving the code protection features of our products. Attempts to break Microchip’s code protection feature may be a violation of the Digital Millennium Copyright Act. If such acts allow unauthorized access to your software or other copyrighted work, you may have a right to sue for relief under that Act. Information contained in this publication regarding device applications and the like is provided only for your convenience and may be superseded by updates. It is your responsibility to ensure that your application meets with your specifications. MICROCHIP MAKES NO REPRESENTATIONS OR WARRANTIES OF ANY KIND WHETHER EXPRESS OR IMPLIED, WRITTEN OR ORAL, STATUTORY OR OTHERWISE, RELATED TO THE INFORMATION, INCLUDING BUT NOT LIMITED TO ITS CONDITION, QUALITY, PERFORMANCE, MERCHANTABILITY OR FITNESS FOR PURPOSE. Microchip disclaims all liability arising from this information and its use. Use of Microchip devices in life support and/or safety applications is entirely at the buyer’s risk, and the buyer agrees to defend, indemnify and hold harmless Microchip from any and all damages, claims, suits, or expenses resulting from such use. No licenses are conveyed, implicitly or otherwise, under any Microchip intellectual property rights. Trademarks The Microchip name and logo, the Microchip logo, Accuron, dsPIC, KEELOQ, KEELOQ logo, MPLAB, PIC, PICmicro, PICSTART, PRO MATE, rfPIC and SmartShunt are registered trademarks of Microchip Technology Incorporated in the U.S.A. and other countries. FilterLab, Linear Active Thermistor, MXDEV, MXLAB, SEEVAL, SmartSensor and The Embedded Control Solutions Company are registered trademarks of Microchip Technology Incorporated in the U.S.A. Analog-for-the-Digital Age, Application Maestro, CodeGuard, dsPICDEM, dsPICDEM.net, dsPICworks, dsSPEAK, ECAN, ECONOMONITOR, FanSense, In-Circuit Serial Programming, ICSP, ICEPIC, Mindi, MiWi, MPASM, MPLAB Certified logo, MPLIB, MPLINK, mTouch, PICkit, PICDEM, PICDEM.net, PICtail, PIC32 logo, PowerCal, PowerInfo, PowerMate, PowerTool, REAL ICE, rfLAB, Select Mode, Total Endurance, UNI/O, WiperLock and ZENA are trademarks of Microchip Technology Incorporated in the U.S.A. and other countries. SQTP is a service mark of Microchip Technology Incorporated in the U.S.A. All other trademarks mentioned herein are property of their respective companies. © 2008, Microchip Technology Incorporated, Printed in the U.S.A., All Rights Reserved. Printed on recycled paper. Microchip received ISO/TS-16949:2002 certification for its worldwide headquarters, design and wafer fabrication facilities in Chandler and Tempe, Arizona; Gresham, Oregon and design centers in California and India. The Company’s quality system processes and procedures are for its PIC® MCUs and dsPIC® DSCs, KEELOQ® code hopping devices, Serial EEPROMs, microperipherals, nonvolatile memory and analog products. In addition, Microchip’s quality system for the design and manufacture of development systems is ISO 9001:2000 certified. © 2008 Microchip Technology Inc. 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