MICROCHIP TC7106AIJL

TC7106/A/TC7107/A
3-1/2 Digit Analog-to-Digital Converters
Features
General Description
• Internal Reference with Low Temperature Drift
- TC7106/7: 80ppm/°C Typical
- TC7106A/7A: 20ppm/°C Typical
• Drives LCD (TC7106) or LED (TC7107)
Display Directly
• Zero Reading with Zero Input
• Low Noise for Stable Display
• Auto-Zero Cycle Eliminates Need for Zero
Adjustment
• True Polarity Indication for Precision Null
Applications
• Convenient 9V Battery Operation (TC7106A)
• High Impedance CMOS Differential Inputs: 1012Ω
• Differential Reference Inputs Simplify Ratiometric
Measurements
• Low Power Operation: 10mW
The TC7106A and TC7107A 3-1/2 digit direct display
drive analog-to-digital converters allow existing 7106/
7107 based systems to be upgraded. Each device has
a precision reference with a 20ppm/°C max temperature coefficient. This represents a 4 to 7 times improvement over similar 3-1/2 digit converters. Existing 7106
and 7107 based systems may be upgraded without
changing external passive component values. The
TC7107A drives common anode light emitting diode
(LED) displays directly with 8mA per segment. A low
cost, high resolution indicating meter requires only a
display, four resistors, and four capacitors.The
TC7106A low power drain and 9V battery operation
make it suitable for portable applications.
Applications
• Thermometry
• Bridge Readouts: Strain Gauges, Load Cells, Null
Detectors
• Digital Meters: Voltage/Current/Ohms/Power, pH
• Digital Scales, Process Monitors
• Portable Instrumentation
The TC7106A/TC7107A reduces linearity error to less
than 1 count. Rollover error – the difference in readings
for equal magnitude, but opposite polarity input signals,
is below ±1 count. High impedance differential inputs
offer 1pA leakage current and a 1012Ω input impedance. The differential reference input allows ratiometric
measurements for ohms or bridge transducer measurements. The 15µVP–P noise performance ensures a
“rock solid” reading. The auto-zero cycle ensures a
zero display reading with a zero volts input.
Device Selection Table
Package
Code
Package
Pin Layout
Temperature
Range
CPI
40-Pin PDIP
Normal
0°C to +70°C
IPL
40-Pin PDIP
Normal
-25°C to +85°C
IJL
40-Pin CERDIP
Normal
-25°C to +85°C
CKW
44-Pin PQFP
Formed Leads
0°C to +70°C
CLW
44-Pin PLCC
—
0°C to +70°C
 2002 Microchip Technology Inc.
DS21455B-page 1
TC7106/A/TC7107/A
Package Type
40-Pin PDIP
1's
10's
100's
1000's
40-Pin CERDIP
40 OSC1
OSC1
1
39
OSC2
OSC2
2
3
38 OSC3
OSC3
3
38 C1
4
37 TEST
TEST
4
37 B1
A1
5
36 VREF+
VREF+
5
36 A1
F1
6
35 VREF-
VREF-
6
35
G1
7
34 CREF+
CREF+ 7
E1
8
33 CREF-
CREF-
D2
9
V+
1
D1
2
C1
B1
Normal Pin
Configuration
TC7106ACPL
TC7107AIPL
8
ANALOG 9
COMMON
VIN+ 10
Reverse
Configuration
40 V+
39 D1
34 G1
TC7106AIJL
TC7107AIJL
33 E1
C2 10
32 ANALOG
COMMON
31 VIN+
B2 11
30 VIN-
VIN- 11
30 B2
A2
29 CAZ
CAZ 12
29 A2
12
F2 13
28 VBUFF
E2
27 VINT
14
VBUFF 13
32 D2
31 C2
28
27 E2
26 V-
V-
15
26 D3
B3
16
25 G2
G2
16
25 B3
F3 17
24 C3
C3
17
24
E3
18
23 A3
A3
18
23 E3
AB4
19
22 G3
G3 19
21 BP/GND
(7106A/7107A)
POL 20
(Minus Sign)
100's
10's
F2
VINT 14
D3 15
100's
1's
F1
100's
F3
22 AB4
1000's
21 POL
(Minus Sign)
BP/GND 20
(7106A/7107A)
B1
C1
D1
V+
NC
OSC1
OSC2
OSC3
TEST
REF HI
REF HI
REF LO
CREF
CREF
COM
IN HI
IN LO
A/Z
BUFF
INT
V-
44-Pin PQFP
A1
44-Pin PLCC
6
5
4
3
2
1
44
43
42
41
40
44
43
42
41
40
39
38
37
36
35
34
F1
7
39 REF LO
NC
1
33
NC
G1
8
38 CREF
NC
2
32
G2
E1
9
37 CREF
TEST
3
31
C3
D2
10
36 COMMON
OSC3
4
30
A3
C2
11
35 IN HI
NC
5
29
G3
NC
12
34 NC
OSC2
6
28
BP/GND
B2
13
33 IN LO
OSC1
7
27
POL
A2
14
32 A/Z
V+
8
26
AB4
F2
15
31 BUFF
D1
9
25
E3
E2
16
30 INT
C1
10
24
F3
D3
17
29 V-
B1
11
23
B3
18
19
20
21
22
23
24
25
26
27
28
12
13
14
15
16
17
18
19
20
21
22
F3
E3
AB4
POL
NC
BP/GND
G3
A3
C3
G2
A1
F1
G1
E1
D2
C2
B2
A2
F2
E2
D3
TC7106ACKW
TC7107ACKW
B3
TC7106ACLW
TC7107ACLW
DS21455B-page 2
 2002 Microchip Technology Inc.
TC7106/A/TC7107/A
Typical Application
0.1µF
1MΩ
+
Analog
Input
–
31
34
33
CREF+
CREF-
VIN+
2 - 19
22 - 25
30
VIN-
POL
32
ANALOG
COMMON
0.01µF
28
47kΩ
27
BP
V+
Segment
Drive
20
21
Minus Sign
Backplane
Drive
1
TC7106/A
TC7107/A
24kΩ
+
VBUFF
VREF
VREF+ 36
0.47µF
29
0.22µF
LCD Display (TC7106/A) or
Common Node w/ LED
Display (TC7107/A)
CAZ
1kΩ
9V
VREF- 35 100mV
VINT
VOSC2 OSC3 OSC1
39
38 COSC 40
ROSC 100pF
26
To Analog
Common (Pin 32)
3 Conversions/Sec
200mV Full Scale
100kΩ
 2002 Microchip Technology Inc.
DS21455B-page 3
TC7106/A/TC7107/A
1.0
ELECTRICAL
CHARACTERISTICS
*Stresses above those listed under "Absolute Maximum
Ratings" may cause permanent damage to the device. These
are stress ratings only and functional operation of the device
at these or any other conditions above those indicated in the
operation sections of the specifications is not implied.
Exposure to Absolute Maximum Rating conditions for
extended periods may affect device reliability.
Absolute Maximum Ratings*
TC7106A
Supply Voltage (V+ to V-) ....................................... 15V
Analog Input Voltage (either Input) (Note 1) ... V+ to VReference Input Voltage (either Input) ............ V+ to VClock Input ................................................... Test to V+
Package Power Dissipation (TA ≤ 70°C) (Note 2):
40-Pin CERDIP .......................................2.29W
40-Pin PDIP ............................................1.23W
44-Pin PLCC ...........................................1.23W
44-Pin PQFP ...........................................1.00W
Operating Temperature Range:
C (Commercial) Devices .............. 0°C to +70°C
I (Industrial) Devices ................ -25°C to +85°C
Storage Temperature Range .............. -65°C to +150°C
TC7107A
Supply Voltage (V+) ...............................................+6V
Supply Voltage (V-)..................................................-9V
Analog Input Voltage (either Input) (Note 1) ... V+ to VReference Input Voltage (either Input) ............ V+ to VClock Input ..................................................GND to V+
Package Power Dissipation (TA ≤ 70°C) (Note 2):
40-Pin CERDip ........................................2.29W
40-Pin PDIP ............................................1.23W
44-Pin PLCC ...........................................1.23W
44-Pin PQFP ...........................................1.00W
Operating Temperature Range:
C (Commercial) Devices .............. 0°C to +70°C
I (Industrial) Devices ................ -25°C to +85°C
Storage Temperature Range .............. -65°C to +150°C
TC7106/A AND TC7107/A ELECTRICAL SPECIFICATIONS
Electrical Characteristics: Unless otherwise noted, specifications apply to both the TC7106/A and TC7107/A at TA = 25°C,
fCLOCK = 48kHz. Parts are tested in the circuit of the Typical Operating Circuit.
Symbol
ZIR
R/O
Note 1:
2:
3:
4:
Parameter
Min
Typ
Max
Unit
Test Conditions
Zero Input Reading
-000.0
±000.0
+000.0
Ratiometric Reading
999
999/1000
1000
Rollover Error (Difference in Reading for
Equal Positive and Negative
Reading Near Full Scale)
-1
±0.2
+1
Counts
VIN- = + VIN+ ≅ 200mV
Linearity (Max. Deviation from Best
Straight Line Fit)
-1
±0.2
+1
Counts
Full Scale = 200mV or
Full Scale = 2.000V
Digital VIN = 0.0V
Reading Full Scale = 200.0mV
Digital VIN = VREF
Reading VREF = 100mV
Input voltages may exceed the supply voltages, provided the input current is limited to ±100µA.
Dissipation rating assumes device is mounted with all leads soldered to printed circuit board.
Refer to “Differential Input” discussion.
Backplane drive is in phase with segment drive for “OFF” segment, 180° out of phase for “ON” segment.
Frequency is 20 times conversion rate. Average DC component is less than 50mV.
DS21455B-page 4
 2002 Microchip Technology Inc.
TC7106/A/TC7107/A
TC7106/A AND TC7107/A ELECTRICAL SPECIFICATIONS (CONTINUED)
Electrical Characteristics: Unless otherwise noted, specifications apply to both the TC7106/A and TC7107/A at TA = 25°C,
fCLOCK = 48kHz. Parts are tested in the circuit of the Typical Operating Circuit.
Symbol
Parameter
Min
Typ
Max
Unit
Test Conditions
CMRR
Common Mode Rejection Ratio (Note 3)
—
50
—
µV/V
VCM = ±1V, VIN = 0V,
Full Scale = 200.0mV
eN
Noise (Peak to Peak Value not Exceeded
95% of Time)
—
15
—
µV
VIN = 0V
Full Scale - 200.0mV
IL
Leakage Current at Input
—
1
10
pA
VIN = 0V
Zero Reading Drift
—
0.2
1
µV/°C
VIN = 0V
“C” Device = 0°C to +70°C
—
1.0
2
µV/°C
VIN = 0V
“I” Device = -25°C to +85°C
—
1
5
ppm/°C
VIN = 199.0mV,
“C” Device = 0°C to +70°C
(Ext. Ref = 0ppm°C)
—
—
20
ppm/°C
VIN = 199.0mV
“I” Device = -25°C to +85°C
TCSF
Scale Factor Temperature Coefficient
IDD
Supply Current (Does not include LED
Current For TC7107/A)
—
0.8
1.8
mA
VIN = 0.8
VC
Analog Common Voltage
(with Respect to Positive Supply)
2.7
3.05
3.35
V
25kΩ Between Common and
Positive Supply
VCTC
Temperature Coefficient of Analog
Common (with Respect to Positive Supply)
—
—
—
—
25kΩ Between Common and
Positive Supply
7106/7/A
7106/7
20
80
50
—
ppm/°C
ppm/°C
0°C ≤ TA ≤ +70°C
(“C” Commercial Temperature
Range Devices)
0°C ≤ TA ≤ +70°C
(“I” Industrial Temperature
Range Devices)
VCTC
Temperature Coefficient of Analog
Common (with Respect to Positive Supply)
—
—
75
ppm/°C
VSD
TC7106A ONLY Peak to Peak
Segment Drive Voltage
4
5
6
V
V+ to V- = 9V
(Note 4)
VBD
TC7106A ONLY Peak to Peak
Backplane Drive Voltage
4
5
6
V
V+ to V- = 9V
(Note 4)
TC7107A ONLY
Segment Sinking Current (Except Pin 19)
5
8.0
—
mA
V+ = 5.0V
Segment Voltage = 3V
TC7107A ONLY
Segment Sinking Current (Pin 19)
10
16
—
mA
V+ = 5.0V
Segment Voltage = 3V
Note 1:
2:
3:
4:
Input voltages may exceed the supply voltages, provided the input current is limited to ±100µA.
Dissipation rating assumes device is mounted with all leads soldered to printed circuit board.
Refer to “Differential Input” discussion.
Backplane drive is in phase with segment drive for “OFF” segment, 180° out of phase for “ON” segment.
Frequency is 20 times conversion rate. Average DC component is less than 50mV.
 2002 Microchip Technology Inc.
DS21455B-page 5
TC7106/A/TC7107/A
2.0
PIN DESCRIPTIONS
The descriptions of the pins are listed in Table 2-1.
TABLE 2-1:
PIN FUNCTION TABLE
Pin Number
(40-Pin PDIP)
Normal
Pin No.
(40-Pin PDIP)
(Reversed
Symbol
1
(40)
V+
Positive supply voltage.
2
(39)
D1
Activates the D section of the units display.
3
(38)
C1
Activates the C section of the units display.
4
(37)
B1
Activates the B section of the units display.
5
(36)
A1
Activates the A section of the units display.
6
(35)
F1
Activates the F section of the units display.
7
(34)
G1
Activates the G section of the units display.
8
(33)
E1
Activates the E section of the units display.
9
(32)
D2
Activates the D section of the tens display.
10
(31)
C2
Activates the C section of the tens display.
Description
11
(30)
B2
Activates the B section of the tens display.
12
(29)
A2
Activates the A section of the tens display.
13
(28)
F2
Activates the F section of the tens display.
14
(27)
E2
Activates the E section of the tens display.
15
(26)
D3
Activates the D section of the hundreds display.
16
(25)
B3
Activates the B section of the hundreds display.
17
(24)
F3
Activates the F section of the hundreds display.
18
(23)
E3
Activates the E section of the hundreds display.
19
(22)
AB4
Activates both halves of the 1 in the thousands display.
20
(21)
POL
Activates the negative polarity display.
21
(20)
BP/GND
22
(19)
G3
Activates the G section of the hundreds display.
23
(18)
A3
Activates the A section of the hundreds display.
24
(17)
C3
Activates the C section of the hundreds display.
25
(16)
G2
Activates the G section of the tens display.
26
(15)
V-
Negative power supply voltage.
27
(14)
VINT
28
(13)
VBUFF
Integration resistor connection. Use a 47kΩ resistor for a 200mV full scale range and
a 47kΩ resistor for 2V full scale range.
29
(12)
CAZ
The size of the auto-zero capacitor influences system noise. Use a 0.47µF capacitor
for 200mV full scale, and a 0.047µF capacitor for 2V full scale. See Section 7.1 on
Auto-Zero Capacitor for more details.
30
(11)
VIN -
The analog LOW input is connected to this pin.
31
(10)
VIN+
The analog HIGH input signal is connected to this pin.
32
(9)
LCD Backplane drive output (TC7106A). Digital Ground (TC7107A).
Integrator output. Connection point for integration capacitor. See INTEGRATING
CAPACITOR section for more details.
ANALOG This pin is primarily used to set the Analog Common mode voltage for battery operaCOMMON tion or in systems where the input signal is referenced to the power supply. It also
acts as a reference voltage source. See Section 8.3 on ANALOG COMMON for more
details.
33
(8)
CREF-
See Pin 34.
34
(7)
CREF +
A 0.1µF capacitor is used in most applications. If a large Common mode voltage
exists (for example, the VIN- pin is not at analog common), and a 200mV scale is
used, a 1µF capacitor is recommended and will hold the rollover error to 0.5 count.
35
(6)
VREF-
See Pin 36.
DS21455B-page 6
 2002 Microchip Technology Inc.
TC7106/A/TC7107/A
TABLE 2-1:
PIN FUNCTION TABLE (CONTINUED)
Pin Number
(40-Pin PDIP)
Normal
Pin No.
(40-Pin PDIP)
(Reversed
Symbol
Description
36
(5)
VREF+
The analog input required to generate a full scale output (1999 counts). Place 100mV
between Pins 35 and 36 for 199.9mV full scale. Place 1V between Pins 35 and 36 for
2V full scale. See paragraph on Reference Voltage.
37
(4)
TEST
Lamp test. When pulled HIGH (to V+) all segments will be turned on and the display
should read -1888. It may also be used as a negative supply for externally generated
decimal points. See paragraph under TEST for additional information.
38
(3)
OSC3
See Pin 40.
39
(2)
OSC2
See Pin 40.
40
(1)
OSC1
Pins 40, 39, 38 make up the oscillator section. For a 48kHz clock (3 readings per
section), connect Pin 40 to the junction of a 100kΩ resistor and a 100pF capacitor.
The 100kΩ resistor is tied to Pin 39 and the 100pF capacitor is tied to Pin 38.
 2002 Microchip Technology Inc.
DS21455B-page 7
TC7106/A/TC7107/A
3.0
DETAILED DESCRIPTION
For a constant VIN:
(All Pin designations refer to 40-Pin PDIP.)
Dual Slope Conversion Principles
The TC7106A and TC7107A are dual slope, integrating
analog-to-digital converters. An understanding of the
dual slope conversion technique will aid in following the
detailed operation theory.
The conventional dual slope converter measurement
cycle has two distinct phases:
• Input Signal Integration
• Reference Voltage Integration (De-integration)
The input signal being converted is integrated for a
fixed time period (TSI). Time is measured by counting
clock pulses. An opposite polarity constant reference
voltage is then integrated until the integrator output
voltage returns to zero. The reference integration time
is directly proportional to the input signal (TRI). See
Figure 3-1.
FIGURE 3-1:
FIGURE 3-2:
+
+/–
Comparator
–
+
Switch
Driver
Phase
Control
REF
Voltage
Clock
Control
Logic
Polarity Control
DISPLAY
Integrator
Output
NORMAL MODE
REJECTION OF DUAL
SLOPE CONVERTER
30
C
Integrator
–
TRI
TSI
The dual slope converter accuracy is unrelated to the
integrating resistor and capacitor values as long as
they are stable during a measurement cycle. An inherent benefit is noise immunity. Noise spikes are integrated or averaged to zero during the integration
periods. Integrating ADCs are immune to the large conversion errors that plague successive approximation
converters in high noise environments. Interfering signals with frequency components at multiples of the
averaging period will be attenuated. Integrating ADCs
commonly operate with the signal integration period set
to a multiple of the 50/60Hz power line period (see
Figure 3-2).
BASIC DUAL SLOPE
CONVERTER
Analog
Input
Signal
Fixed
Signal
Integrate
Time
VIN = VR
Counter
VIN ≈ VREF
VIN ≈ 1/2 VREF
Normal Mode Rejection (dB)
3.1
EQUATION 3-2:
20
10
T = Measured Period
0
0.1/T
1/T
Input Frequency
10/T
Variable
Reference
Integrate
Time
In a simple dual slope converter, a complete conversion requires the integrator output to “ramp-up” and
“ramp-down.” A simple mathematical equation relates
the input signal, reference voltage and integration time.
EQUATION 3-1:
1 TSI
VRTRI
RC ∫ 0 VIN(t)dt = RC
Where:
VR = Reference voltage
TSI = Signal integration time (fixed)
TRI = Reference voltage integration time (variable).
DS21455B-page 8
 2002 Microchip Technology Inc.
TC7106/A/TC7107/A
4.0
ANALOG SECTION
In addition to the basic signal integrate and deintegrate cycles discussed, the circuit incorporates an
auto-zero cycle. This cycle removes buffer amplifier,
integrator, and comparator offset voltage error terms
from the conversion. A true digital zero reading results
without adjusting external potentiometers. A complete
conversion consists of three cycles: an auto-zero,
signal integrate and reference integrate cycle.
4.1
Auto-Zero Cycle
During the auto-zero cycle, the differential input signal
is disconnected from the circuit by opening internal
analog gates. The internal nodes are shorted to analog
common (ground) to establish a zero input condition.
Additional analog gates close a feedback loop around
the integrator and comparator. This loop permits comparator offset voltage error compensation. The voltage
level established on CAZ compensates for device offset
voltages. The offset error referred to the input is less
than 10µV.
The auto-zero cycle length is 1000 to 3000 counts.
4.2
Signal Integrate Cycle
The auto-zero loop is entered and the internal differential inputs connect to VIN+ and VIN-. The differential
input signal is integrated for a fixed time period. The
TC7136/A signal integration period is 1000 clock periods or counts. The externally set clock frequency is
divided by four before clocking the internal counters.
The integration time period is:
EQUATION 4-1:
TSI =
4
x 1000
FOSC
The time required for the output to return to zero is proportional to the input signal and is between 0 and 2000
counts.
The digital reading displayed is:
EQUATION 4-2:
1000 =
5.0
DIGITAL SECTION (TC7106A)
The TC7106A (Figure 5-2) contains all the segment
drivers necessary to directly drive a 3-1/2 digit liquid
crystal display (LCD). An LCD backplane driver is
included. The backplane frequency is the external
clock frequency divided by 800. For three conversions/
second, the backplane frequency is 60Hz with a 5V
nominal amplitude. When a segment driver is in phase
with the backplane signal, the segment is “OFF.” An
out of phase segment drive signal causes the segment
to be “ON” or visible. This AC drive configuration
results in negligible DC voltage across each LCD segment. This insures long LCD display life. The polarity
segment driver is “ON” for negative analog inputs. If
VIN+ and V IN- are reversed, this indicator will reverse.
When the TEST pin on the TC7106A is pulled to V+, all
segments are turned “ON.” The display reads -1888.
During this mode, the LCD segments have a constant
DC voltage impressed. DO NOT LEAVE THE DISPLAY IN THIS MODE FOR MORE THAN SEVERAL
MINUTES! LCD displays may be destroyed if operated
with DC levels for extended periods.
The display font and the segment drive assignment are
shown in Figure 5-1.
FIGURE 5-1:
Where: FOSC = external clock frequency.
The differential input voltage must be within the device
Common mode range when the converter and measured system share the same power supply common
(ground). If the converter and measured system do not
share the same power supply common, VIN- should be
tied to analog common.
Polarity is determined at the end of signal integrate
phase. The sign bit is a true polarity indication, in that
signals less than 1LSB are correctly determined. This
allows precision null detection limited only by device
noise and auto-zero residual offsets.
4.3
Reference Integrate Phase
The third phase is reference integrate or de-integrate.
VIN- is internally connected to analog common and
VIN+ is connected across the previously charged reference capacitor. Circuitry within the chip ensures that
the capacitor will be connected with the correct polarity
to cause the integrator output to return to zero.
 2002 Microchip Technology Inc.
VIN
VREF
DISPLAY FONT AND
SEGMENT ASSIGNMENT
Display Font
1000's
100's
10's
1's
In the TC7106A, an internal digital ground is generated
from a 6-volt zener diode and a large P channel source
follower. This supply is made stiff to absorb the large
capacitive currents when the backplane voltage is
switched.
DS21455B-page 9
DS21455B-page 10
VIN-
ANALOG
COMMON
VIN+
30
32
31
INT
A/Z
DE (–)
DE
(+)
–
+
+
–
V+ – 3.0V
33
CREF- VBUFF
26
V-
A/Z
35
VREF-
AZ & DE (±)
DE (+)
DE
(–)
A/Z
36
VREF+
34
INT
10
µA
CREF+
CREF
TC7106A
1
Low
Tempco
VREF
28
V+
RINT
–
+
Thousands
To
Digital
Section
ROSC
39
OSC2
Clock
COSC
38
OSC3
÷4
Hundreds
7 Segment
Decode
VTH = 1V
Control Logic
Tens
Data Latch
7 Segment
Decode
LCD Segment Drivers
LCD Display
Internal Digital Ground
FOSC
To Switch Drivers
From Comparator Output
27
VINT
CINT
Comparator
40
OSC1
A/Z
+
–
29
Integrator
CAZ
Internal Digital Ground
Segment
Output
V+
Units
7 Segment
Decode
500Ω
6.2V
26
37
1
V-
TEST
V+
Backplane
÷ 200
21
FIGURE 5-2:
2mA
0.5mA
Typical Segment Output
TC7106/A/TC7107/A
TC7106A BLOCK DIAGRAM
 2002 Microchip Technology Inc.
TC7106/A/TC7107/A
6.0
DIGITAL SECTION (TC7107A)
Figure 6-2 shows a TC7107A block diagram. It is
designed to drive common anode LEDs. It is identical
to the TC7106A, except that the regulated supply and
backplane drive have been eliminated and the segment
drive is typically 8mA. The 1000's output (Pin 19) sinks
current from two LED segments, and has a 16mA drive
capability.
6.2
Clock Circuit
Three clocking methods may be used (see Figure 6-1):
1.
2.
3.
An external oscillator connected to Pin 40.
A crystal between Pins 39 and 40.
An RC oscillator using all three pins.
FIGURE 6-1:
In both devices, the polarity indication is “ON” for negative analog inputs. If VIN- and VIN+ are reversed, this
indication can be reversed also, if desired.
CLOCK CIRCUITS
TC7106A
TC7107A
÷4
The display font is the same as the TC7106A.
6.1
System Timing
39
40
The oscillator frequency is divided by 4 prior to clocking
the internal decade counters. The four-phase measurement cycle takes a total of 4000 counts, or 16,000
clock pulses. The 4000-count cycle is independent of
input signal magnitude.
To
Counter
38
Crystal
EXT
OSC
RC Network
To TEST Pin on TSC7106A
To GND Pin on TSC7107A
Each phase of the measurement cycle has the following length:
1.
Auto-zero phase: 1000 to 3000 counts (4000 to
12000 clock pulses).
For signals less than full scale, the auto-zero phase is
assigned the unused reference integrate time period:
2.
Signal integrate: 1000 counts (4000 clock
pulses).
This time period is fixed. The integration period is:
EQUATION 6-1:
TSI = 4000
 1 
F
 OSC 
Where: FOSC is the externally set clock frequency.
3.
Reference Integrate: 0 to 2000 counts (0 to 8000
clock pulses).
The TC7106A/7107A are drop-in replacements for the
7106/7107 parts. External component value changes
are not required to benefit from the low drift internal
reference.
 2002 Microchip Technology Inc.
DS21455B-page 11
DS21455B-page 12
VIN-
ANALOG
COMMON
VIN+
30
32
31
INT
A/Z
DE (–)
DE
(+)
+
–
26
V+ – 3.0V
+
–
CREF- VBUFF
33
V-
A/Z
35
VREF-
AZ & DE (±)
DE (+)
DE
(–)
A/Z
36
VREF+
34
INT
10
µA
CREF+
CREF
TC7107A
1
Low
Tempco
VREF
28
V+
RINT
–
+
27
ROSC
39
OSC2
Clock
Thousands
To
Digital
Section
COSC
38
OSC3
FOSC
To Switch Drivers
from Comparator Output
VINT
CINT
Comparator
40
OSC1
A/Z
+
–
29
Integrator
CAZ
Internal Digital Ground
Segment
Output
V+
Digital Ground
÷4
Hundreds
7 Segment
Decode
Logic Control
Tens
Data Latch
7 Segment
Decode
LCD Segment Drivers
Led Display
500Ω
Units
37
TEST
7 Segment
Decode
21
1
Digital
Ground
V+
FIGURE 6-2:
8mA
0.5mA
Typical Segment Output
TC7106/A/TC7107/A
TC7107A BLOCK DIAGRAM
 2002 Microchip Technology Inc.
TC7106/A/TC7107/A
7.0
7.1
COMPONENT VALUE
SELECTION
7.4
Auto-Zero Capacitor (C AZ)
The CAZ capacitor size has some influence on system
noise. A 0.47µF capacitor is recommended for 200mV
full scale applications where 1LSB is 100µV. A 0.047µF
capacitor is adequate for 2.0V full scale applications. A
mylar type dielectric capacitor is adequate.
Integrating Resistor (RINT)
The input buffer amplifier and integrator are designed
with class A output stages. The output stage idling current is 100µA. The integrator and buffer can supply
20µA drive currents with negligible linearity errors.
RINT is chosen to remain in the output stage linear drive
region, but not so large that printed circuit board leakage currents induce errors. For a 200mV full scale,
RINT is 47kΩ. 2.0V full scale requires 470kΩ.
Nominal Full Scale Voltage
Reference Voltage Capacitor
(CREF)
Component
Value
200.0mV
2.000V
The reference voltage used to ramp the integrator output voltage back to zero during the reference integrate
cycle is stored on CREF. A 0.1µF capacitor is acceptable
when VIN- is tied to analog common. If a large Common
mode voltage exists (VREF- – analog common) and the
application requires 200mV full scale, increase CREF to
1.0µF. Rollover error will be held to less than 1/2 count.
A mylar dielectric capacitor is adequate.
CAZ
0.47µF
0.047µF
7.2
7.3
Integrating Capacitor (C INT)
CINT should be selected to maximize the integrator output voltage swing without causing output saturation.
Due to the TC7106A/7107A superior temperature coefficient specification, analog common will normally supply the differential voltage reference. For this case, a
±2V full scale integrator output swing is satisfactory.
For 3 readings/second (FOSC = 48kHz), a 0.22µF value
is suggested. If a different oscillator frequency is used,
CINT must be changed in inverse proportion to maintain
the nominal ±2V integrator swing.
An exact expression for CINT is:
EQUATION 7-1:
V
(4000)  1   FS 
FOSC RINT
CINT =
Where:
FOSC =
VFS =
RINT =
VINT =



VINT
CINT must have low dielectric absorption to minimize
rollover error. A polypropylene capacitor is recommended.
47kΩ
470kΩ
0.22µF
0.22µF
Note:
7.5
FOSC = 48kHz (3 readings per sec).
Oscillator Components
ROSC (Pin 40 to Pin 39) should be 100kΩ. C OSC is
selected using the equation:
EQUATION 7-2:
FOSC =
0.45
RC
For FOSC of 48kHz, COSC is 100pF nominally.
Note that FOSC is divided by four to generate the
TC7106A internal control clock. The backplane drive
signal is derived by dividing FOSC by 800.
To achieve maximum rejection of 60Hz noise pickup,
the signal integrate period should be a multiple of
60Hz. Oscillator frequencies of 240kHz, 120kHz,
80kHz, 60kHz, 48kHz, 40kHz, etc. should be selected.
For 50Hz rejection, oscillator frequencies of 200kHz,
100kHz, 66-2/3kHz, 50kHz, 40kHz, etc. would be suitable. Note that 40kHz (2.5 readings/second) will reject
both 50Hz and 60Hz.
7.6
Clock Frequency at Pin 38
Full Scale Input Voltage
Integrating Resistor
Desired Full Scale Integrator Output Swing
RINT
CINT
Reference Voltage Selection
A full scale reading (2000 counts) requires the input
signal be twice the reference voltage.
Required Full Scale Voltage*
VREF
200.0mV
100.0mV
2.000V
1.000V
* VFS = 2V REF.
In some applications, a scale factor other than unity
may exist between a transducer output voltage and the
required digital reading. Assume, for example, a pressure transducer output is 400mV for 2000 lb/in2.
Rather than dividing the input voltage by two, the reference voltage should be set to 200mV. This permits the
transducer input to be used directly.
 2002 Microchip Technology Inc.
DS21455B-page 13
TC7106/A/TC7107/A
The differential reference can also be used when a digital zero reading is required when VIN is not equal to
zero. This is common in temperature measuring instrumentation. A compensating offset voltage can be
applied between analog common and VIN-. The transducer output is connected between V IN+ and analog
common.
The internal voltage reference potential available at
analog common will normally be used to supply the
converter's reference. This potential is stable whenever the supply potential is greater than approximately
7V. In applications where an externally generated reference voltage is desired, refer to Figure 7-1.
FIGURE 7-1:
FIGURE 8-1:
CI
+
Input Buffer
RI
+
–
VIN
–
VI
+
Integrator
–
VCM
EXTERNAL REFERENCE
V+
COMMON MODE
VOLTAGE REDUCES
AVAILABLE INTEGRATOR
SWING (VCOM ≠ VIN)
VI =
Where:
TI
RI CI
[ VCM – VIN [
4000
TI = Integration Time = F
OSC
CI = Integration Capacitor
RI = Integration Resistor
V+
V+
VREF+
6.8V
Zener
VREF-
TC7106A
TC7107A
V+
6.8kΩ
TC7106A 20kΩ
TC7107A
IZ
1.2V
Ref
Common
(a)
(b)
8.0
DEVICE PIN FUNCTIONAL
DESCRIPTION
8.1
Differential Signal Inputs
VIN+ (Pin 31), VIN- (Pin 30)
The TC7106A/7017A is designed with true differential
inputs and accepts input signals within the input stage
common mode voltage range (VCM). The typical range
is V+ – 1.0 to V+ + 1V. Common mode voltages are
removed from the system when the TC7106A/
TC7107A operates from a battery or floating power
source (isolated from measured system) and VIN- is
connected to analog common (VCOM) (see Figure 8-2).
In systems where Common mode voltages exist, the
86dB Common mode rejection ratio minimizes error.
Common mode voltages do, however, affect the integrator output level. Integrator output saturation must be
prevented. A worst case condition exists if a large positive VCM exists in conjunction with a full scale negative
differential signal. The negative signal drives the integrator output positive along with VCM (see Figure 8-1).
For such applications the integrator output swing can
be reduced below the recommended 2.0V full scale
swing. The integrator output will swing within 0.3V of
V+ or V- without increasing linearity errors.
DS21455B-page 14
Differential Reference
VREF+ (Pin 36), VREF- (Pin 35)
The reference voltage can be generated anywhere
within the V+ to V- power supply range.
VREF+
VREF-
8.2
To prevent rollover type errors being induced by large
Common mode voltages, CREF should be large compared to stray node capacitance.
The TC7106A/TC7107A circuits have a significantly
lower analog common temperature coefficient. This
gives a very stable voltage suitable for use as a reference. The temperature coefficient of analog common is
20ppm/°C typically.
8.3
Analog Common (Pin 32)
The analog common pin is set at a voltage potential
approximately 3.0V below V+. The potential is between
2.7V and 3.35V below V+. Analog common is tied internally to the N channel FET capable of sinking 20mA.
This FET will hold the common line at 3.0V should an
external load attempt to pull the common line toward
V+. Analog common source current is limited to 10µA.
Analog common is, therefore, easily pulled to a more
negative voltage (i.e., below V+ – 3.0V).
The TC7106A connects the internal VIN+ and VINinputs to analog common during the auto-zero cycle.
During the reference integrate phase, VIN- is connected to analog common. If VIN- is not externally connected to analog common, a Common mode voltage
exists. This is rejected by the converter's 86dB Common mode rejection ratio. In battery operation, analog
common and VIN- are usually connected, removing
Common mode voltage concerns. In systems where Vis connected to the power supply ground, or to a given
voltage, analog common should be connected to VIN-.
 2002 Microchip Technology Inc.
TC7106/A/TC7107/A
FIGURE 8-2:
COMMON MODE VOLTAGE REMOVED IN BATTERY OPERATION WITH
VIN- = ANALOG COMMON
Segment
Drive
Measured
System
V+
V-
VBUF
VINT
POL BP
OSC1
TC7106A
OSC3
VIN+
VIN-
GND
CAZ
LCD Display
OSC2
V-
Analog
Common VREF- VREF+ V+
V+ V-
GND
Power
Source
With sufficiently high total supply voltage (V+ – V- >
7.0V), analog common is a very stable potential with
excellent temperature stability, typically 20ppm/°C.
This potential can be used to generate the reference
voltage. An external voltage reference will be unnecessary in most cases because of the 50ppm/°C maximum
temperature coefficient. See Internal Voltage Reference discussion.
9V
FIGURE 8-3:
180
No Maximum Specified
160
No
Maximum
Specified
140
Typical
120
100
80
TEST (Pin 37)
The TEST pin potential is 5V less than V+. TEST may
be used as the negative power supply connection for
external CMOS logic. The TEST pin is tied to the internally generated negative logic supply (Internal Logic
Ground) through a 500Ω resistor in the TC7106A. The
TEST pin load should be no more than 1mA.
If TEST is pulled to V+ all segments plus the minus sign
will be activated. Do not operate in this mode for more
than several minutes with the TC7106A. With
TEST = V+, the LCD segments are impressed with a
DC voltage which will destroy the LCD.
The TEST pin will sink about 10mA when pulled to V+.
8.5
Internal Voltage Reference
The analog common voltage temperature stability has
been significantly improved (Figure 8-3). The “A” version of the industry standard circuits allow users to
upgrade old systems and design new systems without
external voltage references. External R and C values
do not need to be changed. Figure 8-4 shows analog
common supplying the necessary voltage reference for
the TC7106A/TC7107A.
 2002 Microchip Technology Inc.
Maximum
Limit
No
Maximum
Specified
Typical
60
40
20
8.4
ANALOG COMMON
TEMPERATURE
COEFFICIENT
200
Temperature Coefficient (ppm/°C)
The analog common pin serves to set the analog section
reference or common point. The TC7106A is specifically
designed to operate from a battery, or in any measurement system where input signals are not referenced
(float), with respect to the TC7106A power source. The
analog common potential of V+ – 3.0V gives a 6V end of
battery life voltage. The common potential has a 0.001%
voltage coefficient and a 15Ω output impedance.
+
0
Typical
TC
7106A
FIGURE 8-4:
ICL7106
ICL7136
INTERNAL VOLTAGE
REFERENCE
CONNECTION
1
V-
24kΩ
V+
TC7106A
TC7107A
VREF+
36
1kΩ
VREF
VREF-
35
Analog 32
Common
Set VREF = 1/2 VFULL SCALE
DS21455B-page 15
TC7106/A/TC7107/A
9.0
POWER SUPPLIES
9.1
The TC7107A is designed to work from ±5V supplies.
However, if a negative supply is not available, it can be
generated from the clock output with two diodes, two
capacitors, and an inexpensive IC (Figure 9-1).
FIGURE 9-1:
GENERATING NEGATIVE
SUPPLY FROM +5V
V+
CD4009
V+
OSC1
OSC2
0.047
µF
OSC3
TC7107A
1N914
+
–
10
µF
1N914
TC7107 Power Dissipation
Reduction
The TC7107A sinks the LED display current and this
causes heat to build up in the IC package. If the internal voltage reference is used, the changing chip temperature can cause the display to change reading. By
reducing the LED common anode voltage, the
TC7107A package power dissipation is reduced.
Figure 9-3 is a curve tracer display showing the relationship between output current and output voltage for
a typical TC7107CPL. Since a typical LED has 1.8 volts
across it at 7mA, and its common anode is connected
to +5V, the TC7107A output is at 3.2V (point A on
Figure 9-3). Maximum power dissipation is 8.1mA x
3.2V x 24 segments = 622mW.
FIGURE 9-3:
TC7107 OUTPUT
CURRENT VS. OUTPUT
VOLTAGE
GND
V-
V- = -3.3V
In selected applications a negative supply is not
required. The conditions to use a single +5V supply
are:
• The input signal can be referenced to the center
of the Common mode range of the converter.
• The signal is less than ±1.5V.
• An external reference is used.
The TSC7660 DC to DC converter may be used to generate -5V from +5V (Figure 9-2).
Output Current (mA)
10.000
9.000
A
8.000
B
C
7.000
6.000
2.00
2.50
3.00
3.50
4.00
Output Voltage (V)
FIGURE 9-2:
NEGATIVE POWER
SUPPLY GENERATION
WITH TC7660
+5V
1
36
V+ V
REF+
VREF-
LED
DRIVE
COM
35
32
TC7107A
VIN+
31
VIN
VIN- 30
V- GND
26
8
10µF
+
2
4 TC7660
5
3
+ 10µF
DS21455B-page 16
(-5V)
21
Notice, however, that once the TC7107A output voltage
is above two volts, the LED current is essentially constant as output voltage increases. Reducing the output
voltage by 0.7V (point B in Figure 9-3) results in 7.7mA
of LED current, only a 5 percent reduction. Maximum
power dissipation is only 7.7mA x 2.5V x 24 = 462mW,
a reduction of 26%. An output voltage reduction of 1
volt (point C) reduces LED current by 10% (7.3mA) but
power dissipation by 38% (7.3mA x 2.2V x 24 =
385mW).
Reduced power dissipation is very easy to obtain.
Figure 9-4 shows two ways: either a 5.1 ohm, 1/4 watt
resistor or a 1 Amp diode placed in series with the display (but not in series with the TC7107A). The resistor
will reduce the TC7107A output voltage, when all 24
segments are “ON,” to point “C” of Figure 9-4. When
segments turn off, the output voltage will increase. The
diode, on the other hand, will result in a relatively
steady output voltage, around point “B.”
In addition to limiting maximum power dissipation, the
resistor reduces the change in power dissipation as the
display changes. This effect is caused by the fact that,
as fewer segments are “ON,” each “ON” output drops
more voltage and current. For the best case of six seg-
 2002 Microchip Technology Inc.
TC7106/A/TC7107/A
ments (a “111” display) to worst case (a “1888” display),
the resistor will change about 230mW, while a circuit
without the resistor will change about 470mW. Therefore, the resistor will reduce the effect of display dissipation on reference voltage drift by about 50%.
The change in LED brightness caused by the resistor is
almost unnoticeable as more segments turn off. If display brightness remaining steady is very important to
the designer, a diode may be used instead of the
resistor.
FIGURE 9-4:
DIODE OR RESISTOR
LIMITS PACKAGE POWER
DISSIPATION
+5V
+
-5V
IN
–
1MΩ
24kΩ
150Ω
TP3
1kΩ
100
pF
TP5
TP2
100
kΩ
0.47
µF
0.01
µF
0.1
µF
TP1
Display
47
kΩ
40
30
TC7107A
1
0.22
µF
TP
4
21
10
20
10.2
Light Emitting Diode Display
Sources
Several LED manufacturers supply seven segment
digits with and without decimal point annunciators for
the TC7107A.
Manufacturer
Address/Phone
Display
Hewlett-Packard
Components
640 Page Mill Rd.
Palo Alto, CA 94304
LED
AND
720 Palomar Ave.
Sunnyvale, CA 94086
408-523-8200
LED
10.3
Decimal Point and Annunciator
Drive
The TEST pin is connected to the internally generated
digital logic supply ground through a 500Ω resistor. The
TEST pin may be used as the negative supply for external CMOS gate segment drivers. LCD display annunciators for decimal points, low battery indication, or
function indication may be added without adding an
additional supply. No more than 1mA should be supplied by the TEST pin; its potential is approximately 5V
below V+ (see Figure 10-1).
FIGURE 10-1:
Display
5.1Ω 1/4W
DECIMAL POINT DRIVE
USING TEST AS LOGIC
GROUND
1N4001
V+
V+
10.0
TYPICAL APPLICATIONS
10.1
Liquid Crystal Display Sources
4049
TC7106A
Several manufacturers supply standard LCDs to interface with the TC7106A 3-1/2 digit analog-to-digital
converter.
Manufacturer
Address/Phone
To LCD
Decimal
Point
BP 21
TEST
GND
37
To LCD
Backplane
Representative
Part Numbers*
Crystaloid
Electronics
5282 Hudson Dr.
Hudson, OH 44236
216-655-2429
C5335, H5535,
T5135, SX440
AND
720 Palomar Ave.
Sunnyvale, CA 94086
408-523-8200
FE 0201, 0701
FE 0203, 0701
FE 0501
Epson
3415 Kashikawa st.
Torrance, CA 90505
213-534-0360
LD-B709BZ
LD-H7992AZ
Hamlin, Inc.
612 E. Lake St.
Lake Mills, WI 53551
414-648-236100
3902, 3933, 3903
V+
V+
BP
TC7106A
TEST
To LCD
Decimal
Point
Decimal
Point
Select
4030
GND
Note: Contact LCD manufacturer for full product listing and
specifications.
 2002 Microchip Technology Inc.
DS21455B-page 17
TC7106/A/TC7107/A
10.4
FIGURE 10-4:
Ratiometric Resistance
Measurements
The true differential input and differential reference
make ratiometric reading possible. Typically in a ratiometric operation, an unknown resistance is measured,
with respect to a known standard resistance. No accurately defined reference voltage is needed.
The unknown resistance is put in series with a known
standard and a current passed through the pair. The
voltage developed across the unknown is applied to the
input and the voltage across the known resistor is
applied to the reference input. If the unknown equals
the standard, the display will read 1000.
POSITIVE TEMPERATURE
COEFFICIENT RESISTOR
TEMPERATURE SENSOR
9V
+
5.6kΩ
160kΩ
V+
1N914
R1
20kΩ
V-
VINVIN+
0.7%/°C
PTC
R3
TC7106A
R2
20kΩ
VREF+
VREF-
The displayed reading can be determined from the
following expression:
Common
RUnknown
Displayed ( Reading ) = -------------------------------x1000
RS tan dard
FIGURE 10-5:
The display will over range for:
RUNKNOWN ≥ 2 x R STANDARD
FIGURE 10-2:
LOW PARTS COUNT
RATIOMETRIC
RESISTANCE
MEASUREMENT
To Pin 1
VREF+ V+
VREF-
RSTANDARD
LCD Display
VIN+
TC7106A
RUNKNOWN
TC7106A
VINAnalog
Common
FIGURE 10-3:
TEMPERATURE SENSOR
+
160kΩ
300kΩ
9V
TC7106A, USING THE
INTERNAL REFERENCE:
200mV FULL SCALE, 3
READINGS-PER-SECOND
(RPS)
40
39
38
37
36
35
34
33
32
31
30
29
28
27
26
25
24
23
22
21
Set VREF = 100mV
100kΩ
100pF
0.1µF
1kΩ
22kΩ
1MΩ
+
IN
0.01µF
+
0.47µF
47kΩ
0.22µF
–
9V
–
To Display
To Backplane
300kΩ
V+
V-
VIN1N4148
Sensor
R2
50kΩ
R1
50kΩ
VIN+
TC7106A
VFS = 2V
VREF+
VREFCommon
DS21455B-page 18
 2002 Microchip Technology Inc.
TC7106/A/TC7107/A
FIGURE 10-6:
TC7107 INTERNAL
REFERENCE: 200mV
FULL SCALE, 3RPS,
VIN- TIED TO GND FOR
SINGLE ENDED INPUTS
FIGURE 10-8:
To Pin 1
To Pin 1
TC7107A
40
39
38
37
36
35
34
33
32
31
30
29
28
27
26
25
24
23
22
21
FIGURE 10-7:
Set VREF = 100mV
100kΩ
100pF
+5V
0.1µF
1kΩ
22kΩ
1MΩ
+
IN
0.01µF
0.47µF
TC7106A
TC7107A
–
47kΩ
0.22µF
-5V
To Display
CIRCUIT FOR
DEVELOPING UNDER
RANGE AND OVER
RANGE SIGNALS FROM
TC7106A OUTPUTS
V+
1
To Logic
VCC
V-
O/R
U/R
20
CD4077
 2002 Microchip Technology Inc.
21
100kΩ
100pF
24kΩ
V+
25kΩ
0.1µF
1MΩ
+
IN
0.01µF
0.047µF
–
470kΩ
0.22µF
V-
To Display
TC7107 OPERATED FROM
SINGLE +5V SUPPLY
To PIn 1
TC7107A
TC7106A
Set VREF = 1V
40
39
38
37
36
35
34
33
32
31
30
29
28
27
26
25
24
23
22
21
FIGURE 10-9:
40
To Logic
VCC
CD4023
OR 74C10
TC7106/TC7107:
RECOMMENDED
COMPONENT VALUES
FOR 2.00V FULL SCALE
40
39
38
37
36
35
34
33
32
31
30
29
28
27
26
25
24
23
22
21
100kΩ
Set VREF = 100mV
100pF
10kΩ
10kΩ
V+
0.1µF
1kΩ
1.2V
0.01µF
0.47µF
IN
1MΩ
–
47kΩ
0.22µF
To Display
Note: An external reference must be used in this application.
O/R = Over Range
U/R = Under Range
DS21455B-page 19
TC7106/A/TC7107/A
FIGURE 10-10:
3-1/2 DIGIT TRUE RMS AC DMM
+
IN4148
200mV
VIN
1µF
10kΩ
9MΩ
900kΩ
90kΩ
2V
0.02
µF
1MΩ
26
–
1
14
2
13
AD636
4
47kΩ
1W
10%
1
+
10
6
9
32
8
7
20kΩ
10%
COM
29
28
35 V
REF1MΩ 10%
10kΩ
TC7106A
36 V
REF+
1kΩ
11
5
27
24kΩ
–
6.8µF
V-
V+
12
3
1MΩ
20V
200V
9V
+
0.01
µF
2.2µF
C1 = 3 - 10pF Variable
C2 = 132pF Variable
Analog Common
31 V +
IN
40
30
38
26
VIN-
39
V-
SEG
DRIVE
BP
LCD Display
FIGURE 10-11:
INTEGRATED CIRCUIT TEMPERATURE SENSOR
9V
2
1
Constant 5V
V+
V+
VREF+
REF02
VOUT
ADJ
TEMP
6
51kΩ
R4
5
NC
3
DS21455B-page 20
TC911
R2
R5
2 –
50kΩ
1
4
1.3k
TC7106A
VREFVFS = 2.00V
8
3 +
Temperature
Dependent
Output
GND
4
5.1kΩ
VINVOUT =
1.86V @
25°C
50kΩ
R1
VIN+
Common
V26
 2002 Microchip Technology Inc.
TC7106/A/TC7107/A
11.0
PACKAGING INFORMATION
11.1
Package Marking Information
Package marking data not available at this time.
11.2
Taping Form
Component Taping Orientation for 44-Pin PLCC Devices
User Direction of Feed
PIN 1
W
P
Standard Reel Component Orientation
for TR Suffix Device
Carrier Tape, Number of Components Per Reel and Reel Size
Package
44-Pin PLCC
Carrier Width (W)
Pitch (P)
Part Per Full Reel
Reel Size
32 mm
24 mm
500
13 in
Note: Drawing does not represent total number of pins.
Component Taping Orientation for 44-Pin PQFP Devices
User Direction of Feed
PIN 1
W
P
Standard Reel Component Orientation
for TR Suffix Device
Carrier Tape, Number of Components Per Reel and Reel Size
Package
44-Pin PQFP
Carrier Width (W)
Pitch (P)
Part Per Full Reel
Reel Size
24 mm
16 mm
500
13 in
Note: Drawing does not represent total number of pins.
 2002 Microchip Technology Inc.
DS21455B-page 21
TC7106/A/TC7107/A
11.3
Package Dimensions
40-Pin PDIP (Wide)
PIN 1
.555 (14.10)
.530 (13.46)
2.065 (52.45)
2.027 (51.49)
.610 (15.49)
.590 (14.99)
.200 (5.08)
.140 (3.56)
.040 (1.02)
.020 (0.51)
.150 (3.81)
.115 (2.92)
.110 (2.79)
.090 (2.29)
.070 (1.78)
.045 (1.14)
.015 (0.38)
.008 (0.20)
3° MIN.
.700 (17.78)
.610 (15.50)
.022 (0.56)
.015 (0.38)
Dimensions: inches (mm)
40-Pin CERDIP (Wide)
PIN 1
.540 (13.72)
.510 (12.95)
.030 (0.76) MIN.
.098 (2.49) MAX.
2.070 (52.58)
2.030 (51.56)
.620 (15.75)
.590 (15.00)
.060 (1.52)
.020 (0.51)
.210 (5.33)
.170 (4.32)
.150 (3.81)
MIN.
.200 (5.08)
.125 (3.18)
.110 (2.79)
.090 (2.29)
.065 (1.65)
.045 (1.14)
.020 (0.51)
.016 (0.41)
.015 (0.38)
.008 (0.20)
3° MIN.
.700 (17.78)
.620 (15.75)
Dimensions: inches (mm)
DS21455B-page 22
 2002 Microchip Technology Inc.
TC7106/A/TC7107/A
11.3
Package Dimensions (Continued)
44-Pin PLCC
PIN 1
.021 (0.53)
.013 (0.33)
.050 (1.27) TYP.
.695 (17.65)
.685 (17.40)
.630 (16.00)
.591 (15.00)
.656 (16.66)
.650 (16.51)
.032 (0.81)
.026 (0.66)
.020 (0.51) MIN.
.656 (16.66)
.650 (16.51)
.120 (3.05)
.090 (2.29)
.695 (17.65)
.685 (17.40)
.180 (4.57)
.165 (4.19)
Dimensions: inches (mm)
44-Pin PQFP
7° MAX.
.009 (0.23)
.005 (0.13)
PIN 1
.018 (0.45)
.012 (0.30)
.041 (1.03)
.026 (0.65)
.398 (10.10)
.390 (9.90)
.557 (14.15)
.537 (13.65)
.031 (0.80) TYP.
.398 (10.10)
.390 (9.90)
.557 (14.15)
.537 (13.65)
.010 (0.25) TYP.
.083 (2.10)
.075 (1.90)
.096 (2.45) MAX.
Dimensions: inches (mm)
 2002 Microchip Technology Inc.
DS21455B-page 23
TC7106/A/TC7107/A
PRODUCT IDENTIFICATION SYSTEM
To order or obtain information, e.g., on pricing or delivery, refer to the factory or the listed sales office.
PART CODE
6 = LCD
7 = LED
TC711X X X
XXX
}
A or blank*
R (reversed pins) or blank (CPL pkg only)
* "A" parts have an improved reference TC
Package Code (see below):
SALES AND SUPPORT
Data Sheets
Products supported by a preliminary Data Sheet may have an errata sheet describing minor operational differences and recommended workarounds. To determine if an errata sheet exists for a particular device, please contact one of the following:
1.
2.
3.
Your local Microchip sales office
The Microchip Corporate Literature Center U.S. FAX: (480) 792-7277
The Microchip Worldwide Site (www.microchip.com)
Please specify which device, revision of silicon and Data Sheet (include Literature #) you are using.
New Customer Notification System
Register on our web site (www.microchip.com/cn) to receive the most current information on our products.
DS21455B-page 24
 2002 Microchip Technology Inc.
TC7106/A/TC7107/A
Information contained in this publication regarding device
applications and the like is intended through suggestion only
and may be superseded by updates. It is your responsibility to
ensure that your application meets with your specifications.
No representation or warranty is given and no liability is
assumed by Microchip Technology Incorporated with respect
to the accuracy or use of such information, or infringement of
patents or other intellectual property rights arising from such
use or otherwise. Use of Microchip’s products as critical components in life support systems is not authorized except with
express written approval by Microchip. No licenses are conveyed, implicitly or otherwise, under any intellectual property
rights.
Trademarks
The Microchip name and logo, the Microchip logo, FilterLab,
KEELOQ, microID, MPLAB, PIC, PICmicro, PICMASTER,
PICSTART, PRO MATE, SEEVAL and The Embedded Control
Solutions Company are registered trademarks of Microchip Technology Incorporated in the U.S.A. and other countries.
dsPIC, ECONOMONITOR, FanSense, FlexROM, fuzzyLAB,
In-Circuit Serial Programming, ICSP, ICEPIC, microPort,
Migratable Memory, MPASM, MPLIB, MPLINK, MPSIM,
MXDEV, PICC, PICDEM, PICDEM.net, rfPIC, Select Mode
and Total Endurance are trademarks of Microchip Technology
Incorporated in the U.S.A.
Serialized Quick Turn Programming (SQTP) is a service mark
of Microchip Technology Incorporated in the U.S.A.
All other trademarks mentioned herein are property of their
respective companies.
© 2002, Microchip Technology Incorporated, Printed in the
U.S.A., All Rights Reserved.
Printed on recycled paper.
Microchip received QS-9000 quality system
certification for its worldwide headquarters,
design and wafer fabrication facilities in
Chandler and Tempe, Arizona in July 1999
and Mountain View, California in March 2002.
The Company’s quality system processes and
procedures are QS-9000 compliant for its
PICmicro ® 8-bit MCUs, KEELOQ® code hopping
devices, Serial EEPROMs, microperipherals,
non-volatile memory and analog products. In
addition, Microchip’s quality system for the
design and manufacture of development
systems is ISO 9001 certified.
 2002 Microchip Technology Inc.
DS21455B-page 25
WORLDWIDE SALES AND SERVICE
AMERICAS
ASIA/PACIFIC
Japan
Corporate Office
Australia
2355 West Chandler Blvd.
Chandler, AZ 85224-6199
Tel: 480-792-7200 Fax: 480-792-7277
Technical Support: 480-792-7627
Web Address: http://www.microchip.com
Microchip Technology Australia Pty Ltd
Suite 22, 41 Rawson Street
Epping 2121, NSW
Australia
Tel: 61-2-9868-6733 Fax: 61-2-9868-6755
Microchip Technology Japan K.K.
Benex S-1 6F
3-18-20, Shinyokohama
Kohoku-Ku, Yokohama-shi
Kanagawa, 222-0033, Japan
Tel: 81-45-471- 6166 Fax: 81-45-471-6122
Rocky Mountain
China - Beijing
2355 West Chandler Blvd.
Chandler, AZ 85224-6199
Tel: 480-792-7966 Fax: 480-792-7456
Microchip Technology Consulting (Shanghai)
Co., Ltd., Beijing Liaison Office
Unit 915
Bei Hai Wan Tai Bldg.
No. 6 Chaoyangmen Beidajie
Beijing, 100027, No. China
Tel: 86-10-85282100 Fax: 86-10-85282104
Atlanta
500 Sugar Mill Road, Suite 200B
Atlanta, GA 30350
Tel: 770-640-0034 Fax: 770-640-0307
Boston
2 Lan Drive, Suite 120
Westford, MA 01886
Tel: 978-692-3848 Fax: 978-692-3821
Chicago
333 Pierce Road, Suite 180
Itasca, IL 60143
Tel: 630-285-0071 Fax: 630-285-0075
Dallas
4570 Westgrove Drive, Suite 160
Addison, TX 75001
Tel: 972-818-7423 Fax: 972-818-2924
Detroit
Tri-Atria Office Building
32255 Northwestern Highway, Suite 190
Farmington Hills, MI 48334
Tel: 248-538-2250 Fax: 248-538-2260
Kokomo
2767 S. Albright Road
Kokomo, Indiana 46902
Tel: 765-864-8360 Fax: 765-864-8387
Los Angeles
18201 Von Karman, Suite 1090
Irvine, CA 92612
Tel: 949-263-1888 Fax: 949-263-1338
China - Chengdu
Microchip Technology Consulting (Shanghai)
Co., Ltd., Chengdu Liaison Office
Rm. 2401, 24th Floor,
Ming Xing Financial Tower
No. 88 TIDU Street
Chengdu 610016, China
Tel: 86-28-6766200 Fax: 86-28-6766599
China - Fuzhou
Microchip Technology Consulting (Shanghai)
Co., Ltd., Fuzhou Liaison Office
Unit 28F, World Trade Plaza
No. 71 Wusi Road
Fuzhou 350001, China
Tel: 86-591-7503506 Fax: 86-591-7503521
China - Shanghai
Microchip Technology Consulting (Shanghai)
Co., Ltd.
Room 701, Bldg. B
Far East International Plaza
No. 317 Xian Xia Road
Shanghai, 200051
Tel: 86-21-6275-5700 Fax: 86-21-6275-5060
China - Shenzhen
150 Motor Parkway, Suite 202
Hauppauge, NY 11788
Tel: 631-273-5305 Fax: 631-273-5335
Microchip Technology Consulting (Shanghai)
Co., Ltd., Shenzhen Liaison Office
Rm. 1315, 13/F, Shenzhen Kerry Centre,
Renminnan Lu
Shenzhen 518001, China
Tel: 86-755-2350361 Fax: 86-755-2366086
San Jose
Hong Kong
Microchip Technology Inc.
2107 North First Street, Suite 590
San Jose, CA 95131
Tel: 408-436-7950 Fax: 408-436-7955
Microchip Technology Hongkong Ltd.
Unit 901-6, Tower 2, Metroplaza
223 Hing Fong Road
Kwai Fong, N.T., Hong Kong
Tel: 852-2401-1200 Fax: 852-2401-3431
New York
Toronto
6285 Northam Drive, Suite 108
Mississauga, Ontario L4V 1X5, Canada
Tel: 905-673-0699 Fax: 905-673-6509
India
Microchip Technology Inc.
India Liaison Office
Divyasree Chambers
1 Floor, Wing A (A3/A4)
No. 11, O’Shaugnessey Road
Bangalore, 560 025, India
Tel: 91-80-2290061 Fax: 91-80-2290062
Korea
Microchip Technology Korea
168-1, Youngbo Bldg. 3 Floor
Samsung-Dong, Kangnam-Ku
Seoul, Korea 135-882
Tel: 82-2-554-7200 Fax: 82-2-558-5934
Singapore
Microchip Technology Singapore Pte Ltd.
200 Middle Road
#07-02 Prime Centre
Singapore, 188980
Tel: 65-6334-8870 Fax: 65-6334-8850
Taiwan
Microchip Technology Taiwan
11F-3, No. 207
Tung Hua North Road
Taipei, 105, Taiwan
Tel: 886-2-2717-7175 Fax: 886-2-2545-0139
EUROPE
Denmark
Microchip Technology Nordic ApS
Regus Business Centre
Lautrup hoj 1-3
Ballerup DK-2750 Denmark
Tel: 45 4420 9895 Fax: 45 4420 9910
France
Microchip Technology SARL
Parc d’Activite du Moulin de Massy
43 Rue du Saule Trapu
Batiment A - ler Etage
91300 Massy, France
Tel: 33-1-69-53-63-20 Fax: 33-1-69-30-90-79
Germany
Microchip Technology GmbH
Gustav-Heinemann Ring 125
D-81739 Munich, Germany
Tel: 49-89-627-144 0 Fax: 49-89-627-144-44
Italy
Microchip Technology SRL
Centro Direzionale Colleoni
Palazzo Taurus 1 V. Le Colleoni 1
20041 Agrate Brianza
Milan, Italy
Tel: 39-039-65791-1 Fax: 39-039-6899883
United Kingdom
Arizona Microchip Technology Ltd.
505 Eskdale Road
Winnersh Triangle
Wokingham
Berkshire, England RG41 5TU
Tel: 44 118 921 5869 Fax: 44-118 921-5820
03/01/02
*DS21455B*
DS21455B-page 26
 2002 Microchip Technology Inc.