HA5024 September 1998 File Number 3550.4 Quad 125MHz Video Current Feedback Amplifier with Disable Features The HA5024 is a quad version of the popular Intersil HA5020. It features wide bandwidth and high slew rate, and is optimized for video applications and gains between 1 and 10. It is a current feedback amplifier and thus yields less bandwidth degradation at high closed loop gains than voltage feedback amplifiers. • Individual Output Enable/Disable • Quad Version of HA-5020 • Input Offset Voltage . . . . . . . . . . . . . . . . . . . . . . . . 800µV • Wide Unity Gain Bandwidth . . . . . . . . . . . . . . . . . 125MHz • Slew Rate . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 475V/µs • Differential Gain . . . . . . . . . . . . . . . . . . . . . . . . . . . 0.03% The low differential gain and phase, 0.1dB gain flatness, and ability to drive two back terminated 75Ω cables, make this amplifier ideal for demanding video applications. The HA5024 also features a disable function that significantly reduces supply current while forcing the output to a true high impedance state. This functionality allows 2:1 and 4:1 video multiplexers to be implemented with a single IC. The current feedback design allows the user to take advantage of the amplifier’s bandwidth dependency on the feedback resistor. By reducing RF, the bandwidth can be increased to compensate for decreases at higher closed loop gains or heavy output loads. • Differential Phase . . . . . . . . . . . . . . . . . . . . 0.03 Degrees • Supply Current (per Amplifier) . . . . . . . . . . . . . . . . 7.5mA • ESD Protection. . . . . . . . . . . . . . . . . . . . . . . . . . . . 4000V • Guaranteed Specifications at ±5V Supplies Applications • Video Multiplexers; Video Switching and Routing • Video Gain Block • Video Distribution Amplifier/RGB Amplifier • Flash A/D Driver Pinout • Current to Voltage Converter HA5024 (PDIP, SOIC) TOP VIEW OUT1 1 -IN1 2 +IN1 3 • Medical Imaging • Radar and Imaging Systems 20 OUT4 - - + + 19 -IN4 Ordering Information 18 +IN4 PART NUMBER TEMP. RANGE (oC) PACKAGE PKG. NO. DIS1 4 17 DIS4 NC 5 16 NC HA5024IP -40 to 85 20 Ld PDIP E20.3 V+ 6 15 V- HA5024IB -40 to 85 20 Ld SOIC M20.3 DIS2 7 14 DIS3 +IN2 8 -IN2 9 + + - - OUT2 10 13 +IN3 HA5024EVAL High Speed Op Amp DIP Evaluation Board 12 -IN3 11 OUT3 1 CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. http://www.intersil.com or 407-727-9207 | Copyright © Intersil Corporation 1999 HA5024 Absolute Maximum Ratings Thermal Information Voltage Between V+ and V- Terminals. . . . . . . . . . . . . . . . . . . . 36V DC Input Voltage (Note 3) . . . . . . . . . . . . . . . . . . . . . . . . ±VSUPPLY Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10V Output Current (Note 4) . . . . . . . . . . . . . . . . Short Circuit Protected ESD Rating (Note 3) Human Body Model (Per MIL-STD-883 Method 3015.7) . . .2000V Thermal Resistance (Typical, Note 2) θJA (oC/W) PDIP Package . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 75 SOIC Package . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 90 Maximum Junction Temperature (Note 1) . . . . . . . . . . . . . . . . .175oC Maximum Junction Temperature (Plastic Package, Note 1) . . . . 150oC Maximum Storage Temperature Range . . . . . . . . . . -65oC to 150oC Maximum Lead Temperature (Soldering 10s) . . . . . . . . . . . . 300oC (SOIC - Lead Tips Only) Operating Conditions Temperature Range . . . . . . . . . . . . . . . . . . . . . . . . . . -40oC to 85oC Supply Voltage Range (Typical) . . . . . . . . . . . . . . . . . ±4.5V to ±15V CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. NOTES: 1. Maximum power dissipation, including output load, must be designed to maintain junction temperature below 175oC for die, and below 150oC for plastic packages. See Application Information section for safe operating area information. 2. θJA is measured with the component mounted on an evaluation PC board in free air. 3. The non-inverting input of unused amplifiers must be connected to GND. 4. Output is protected for short circuits to ground. Brief short circuits to ground will not degrade reliability, however, continuous (100% duty cycle) output current should not exceed 15mA for maximum reliability. VSUPPLY = ±5V, RF = 1kΩ, AV = +1, RL = 400Ω, CL ≤ 10pF,Unless Otherwise Specified Electrical Specifications PARAMETER TEST CONDITIONS (NOTE 11) TEST TEMP. LEVEL (oC) MIN TYP MAX UNITS INPUT CHARACTERISTICS Input Offset Voltage (VIO) A 25 - 0.8 3 mV A Full - - 5 mV Delta VIO Between Channels A Full - 1.2 3.5 mV Average Input Offset Voltage Drift B Full - 5 - µV/oC A 25 53 - - dB A Full 50 - - dB A 25 60 - - dB A Full 55 - - dB A Full ±2.5 - - V A 25 - 3 8 µA A Full - - 20 µA A 25 - - 0.15 µA/V A Full - - 0.5 µA/V A 25 - - 0.1 µA/V A Full - - 0.3 µA/V A 25,85 - 4 12 µA A -40 - 10 30 µA A 25,85 - 6 15 µA A -40 - 10 30 µA A 25 - - 0.4 µA/V A Full - - 1.0 µA/V VIO Common Mode Rejection Ratio VIO Power Supply Rejection Ratio Input Common Mode Range Note 5 ±3.5V ≤ VS ≤ ±6.5V Note 5 Non-Inverting Input (+IN) Current +IN Common Mode Rejection 1 ) (+IBCMR =--------R IN Note 5 +IN Power Supply Rejection ±3.5V ≤ VS ≤ ±6.5V Inverting Input (-IN) Current Delta -IN BIAS Current Between Channels -IN Common Mode Rejection Note 5 2 HA5024 VSUPPLY = ±5V, RF = 1kΩ, AV = +1, RL = 400Ω, CL ≤ 10pF,Unless Otherwise Specified (Continued) Electrical Specifications PARAMETER TEST CONDITIONS ±3.5V ≤ VS ≤ ±6.5V -IN Power Supply Rejection (NOTE 11) TEST TEMP. LEVEL (oC) MIN TYP MAX UNITS A 25 - - 0.2 µA/V A Full - - 0.5 µA/V Input Noise Voltage f = 1kHz B 25 - 4.5 - nV/√Hz +Input Noise Current f = 1kHz B 25 - 2.5 - pA/√Hz -Input Noise Current f = 1kHz B 25 - 25.0 - pA/√Hz Note 16 A 25 1.0 - - MΩ A Full 0.85 - - MΩ 25A 25 70 - - dB A Full 65 - - dB A 25 50 - - dB A Full 45 - - dB A 25 ±2.5 ±3.0 - V A Full ±2.5 ±3.0 - V TRANSFER CHARACTERISTICS Transimpedence RL = 400Ω, VOUT = ±2.5V Open Loop DC Voltage Gain RL = 100Ω, VOUT = ±2.5V Open Loop DC Voltage Gain OUTPUT CHARACTERISTICS Output Voltage Swing RL = 150Ω Output Current RL = 150Ω B Full ±16.6 ±20.0 - mA Output Current, Short Circuit VIN = ±2.5V, VOUT = 0V A Full ±40 ±60 - mA Output Current, Disabled (Note 5) DISABLE = 0V, VOUT = ±2.5V, VIN = 0V A Full - - 2 µA Output Disable Time Note 12 B 25 - 40 - µs Output Enable Time Note 13 B 25 - 40 - ns Output Capacitance Disabled Note 14 B 25 - 15 - pF Supply Voltage Range A 25 5 - 15 V Quiescent Supply Current A Full - 7.5 10 mA/Op Amp POWER SUPPLY CHARACTERISTICS Supply Current, Disabled DISABLE = 0V A Full - 5 7.5 mA/Op Amp Disable Pin Input Current DISABLE = 0V A Full - 1.0 1.5 mA Minimum Pin 8 Current to Disable Note 6 A Full 350 - - µA Maximum Pin 8 Current to Enable Note 7 A Full - - 20 µA Slew Rate Note 8 B 25 275 350 - V/µs Full Power Bandwidth Note 9 B 25 22 28 - MHz Rise Time Note 10 B 25 - 6 - ns Fall Time Note 10 B 25 - 6 - ns Propagation Delay Note 10 B 25 - 6 - ns B 25 - 4.5 - % AC CHARACTERISTICS (AV = +1) Overshoot -3dB Bandwidth VOUT = 100mV B 25 - 125 - MHz Settling Time to 1% 2V Output Step B 25 - 50 - ns Settling Time to 0.25% 2V Output Step B 25 - 75 - ns 3 HA5024 VSUPPLY = ±5V, RF = 1kΩ, AV = +1, RL = 400Ω, CL ≤ 10pF,Unless Otherwise Specified (Continued) Electrical Specifications PARAMETER TEST CONDITIONS (NOTE 11) TEST TEMP. LEVEL (oC) MIN TYP MAX UNITS AC CHARACTERISTICS (AV = +2, RF = 681Ω) Slew Rate Note 8 B 25 - 475 - V/µs Full Power Bandwidth Note 9 B 25 - 26 - MHz Rise Time Note 10 B 25 - 6 - ns Fall Time Note 10 B 25 - 6 - ns Propagation Delay Note 10 B 25 - 6 - ns B 25 - 12 - % Overshoot -3dB Bandwidth VOUT = 100mV B 25 - 95 - MHz Settling Time to 1% 2V Output Step B 25 - 50 - ns Settling Time to 0.25% 2V Output Step B 25 - 100 - ns Gain Flatness 5MHz B 25 - 0.02 - dB 20MHz B 25 - 0.07 - dB AC CHARACTERISTICS (AV = +10, RF = 383Ω) Slew Rate Note 8 B 25 350 475 - V/µs Full Power Bandwidth Note 9 B 25 28 38 - MHz Rise Time Note 10 B 25 - 8 - ns Fall Time Note 10 B 25 - 9 - ns Propagation Delay Note 10 B 25 - 9 - ns B 25 - 1.8 - % Overshoot -3dB Bandwidth VOUT = 100mV B 25 - 65 - MHz Settling Time to 1% 2V Output Step B 25 - 75 - ns Settling Time to 0.1% 2V Output Step B 25 - 130 - ns Differential Gain (Note 15) RL = 150Ω B 25 - 0.03 - % Differential Phase (Note 15) RL = 150Ω B 25 - 0.03 - Degrees VIDEO CHARACTERISTICS NOTES: 5. VCM = ±2.5V. At -40oC Product is tested at VCM = ±2.25V because short test duration does not allow self heating. 6. RL = 100Ω, VIN = 2.5V. This is the minimum current which must be pulled out of the Disable pin in order to disable the output. The output is considered disabled when -10mV ≤ VOUT ≤ +10mV. 7. VIN = 0V. This is the maximum current that can be pulled out of the Disable pin with the HA5024 remaining enabled. The HA5024 is considered disabled when the supply current has decreased by at least 0.5mA. 8. VOUT switches from -2V to +2V, or from +2V to -2V. Specification is from the 25% to 75% points. Slew Rate 9. FPBW = ----------------------------; V = 2V . 2πV PEAK PEAK 10. RL = 100Ω, VOUT = 1V. Measured from 10% to 90% points for rise/fall times; from 50% points of input and output for propagation delay. 11. A. Production Tested; B. Typical or Guaranteed Limit based on characterization; C. Design Typical for information only. 12. VIN = +2V, DISABLE = +5V to 0V. Measured from the 50% point of DISABLE to VOUT = 0V. 13. VIN = +2V, DISABLE = 0V to +5V. Measured from the 50% point of DISABLE to VOUT = 2V. 14. VIN = 0V, Force VOUT from 0V to ±2.5V, tR = tF = 50ns, DISABLE = 0V. 15. Measured with a VM700A video tester using an NTC-7 composite VITS. 16. VOUT = ±2.5V. At -40oC Product is tested at VOUT = ±2.25V because short test duration does not allow self heating. 4 HA5024 Test Circuits and Waveforms + DUT 50Ω HP4195 NETWORK ANALYZER 50Ω FIGURE 1. TEST CIRCUIT FOR TRANSIMPEDANCE MEASUREMENTS (NOTE 17) 100Ω (NOTE 17) 100Ω VIN + VIN DUT VOUT - 50Ω RL 100Ω + DUT VOUT - 50Ω RI 681Ω RF, 681Ω RL 400Ω RF, 1kΩ FIGURE 2. SMALL SIGNAL PULSE RESPONSE CIRCUIT FIGURE 3. LARGE SIGNAL PULSE RESPONSE CIRCUIT NOTE: 17. A series input resistor of ≥100Ω is recommended to limit input currents in case input signals are present before the HA5024 is powered up. Vertical Scale: VIN = 100mV/Div., VOUT = 100mV/Div. Horizontal Scale: 20ns/Div. FIGURE 4. SMALL SIGNAL RESPONSE 5 Vertical Scale: VIN = 1V/Div., VOUT = 1V/Div. Horizontal Scale: 50ns/Div. FIGURE 5. LARGE SIGNAL RESPONSE Schematic (One Amplifier of Four) V+ R2 800 R5 2.5K R6 15K R10 820 D2 QP8 R15 400 QP9 R19 400 QP11 QP1 QP5 QP14 R11 1K R17 280 QN5 R24 140 6 QP2 QP12 QP6 QN6 R7 15K R12 280 QP4 R28 20 -IN QP17 QN13 +IN QN17 QP13 R25 20 C2 1.4pF HA5024 DIS R3 6K QN15 QN2 R21 140 QN10 D1 QP16 C1 1.4pF QN8 QP3 R31 5 R20 140 QP15 QN12 R8 1.25K R1 60K QP19 QP20 QP10 QN1 QP18 R18 280 R29 9.5 R33 2K R27 200 QN3 R14 280 QP7 QN4 R25 140 QN16 QN14 R13 1K QN7 R22 280 R16 400 QN21 QN18 R23 400 R26 200 R32 5 QN19 QN20 R26 200 R30 7 OUT R4 800 V- R33 800 R9 820 QN9 QN11 HA5024 Application Information Driving Capacitive Loads Optimum Feedback Resistor Capacitive loads will degrade the amplifier’s phase margin resulting in frequency response peaking and possible oscillations. In most cases the oscillation can be avoided by placing an isolation resistor (R) in series with the output as shown in Figure 6. The table below lists recommended RF values for various gains, and the expected bandwidth. GAIN (ACL) RF (Ω) BANDWIDTH (MHz) -1 750 100 +1 1000 125 +2 681 95 +5 1000 52 +10 383 65 -10 750 22 PC Board Layout The frequency response of this amplifier depends greatly on the amount of care taken in designing the PC board. The use of low inductance components such as chip resistors and chip capacitors is strongly recommended. If leaded components are used the leads must be kept short especially for the power supply decoupling components and those components connected to the inverting input. Attention must be given to decoupling the power supplies. A large value (10µF) tantalum or electrolytic capacitor in parallel with a small value (0.1µF) chip capacitor works well in most cases. A ground plane is strongly recommended to control noise. Care must also be taken to minimize the capacitance to ground seen by the amplifier’s inverting input (-IN). The larger this capacitance, the worse the gain peaking, resulting in pulse overshoot and possible instability. It is recommended that the ground plane be removed under traces connected to -IN, and that connections to -IN be kept as short as possible to minimize the capacitance from this node to ground. 7 100Ω VIN R + VOUT - RT CL RF RI FIGURE 6. PLACEMENT OF THE OUTPUT ISOLATION RESISTOR, R The selection criteria for the isolation resister is highly dependent on the load, but 27Ω has been determined to be a good starting value. Power Dissipation Considerations Due to the high supply current inherent in quad amplifiers, care must be taken to insure that the maximum junction temperature (TJ, see Absolute Maximum Ratings) is not exceeded. Figure 7 shows the maximum ambient temperature versus supply voltage for the available package styles (Plastic DIP, SOIC). At ±5VDC quiescent operation both package styles may be operated over the full industrial range of -40oC to 85oC. It is recommended that thermal calculations, which take into account output power, be performed by the designer. 130 MAX. AMBIENT TEMPERATURE The plots of inverting and non-inverting frequency response, see Figure 11 and Figure 12 in the Typical Performance Curves section, illustrate the performance of the HA5024 in various closed loop gain configurations. Although the bandwidth dependency on closed loop gain isn’t as severe as that of a voltage feedback amplifier, there can be an appreciable decrease in bandwidth at higher gains. This decrease may be minimized by taking advantage of the current feedback amplifier’s unique relationship between bandwidth and RF. All current feedback amplifiers require a feedback resistor, even for unity gain applications, and RF, in conjunction with the internal compensation capacitor, sets the dominant pole of the frequency response. Thus, the amplifier’s bandwidth is inversely proportional to RF. The HA5024 design is optimized for a 1000Ω RF at a gain of +1. Decreasing RF in a unity gain application decreases stability, resulting in excessive peaking and overshoot. At higher gains the amplifier is more stable, so RF can be decreased in a trade-off of stability for bandwidth. 120 110 PDIP 100 90 80 70 SOIC 60 50 5 7 9 11 SUPPLY VOLTAGE (±V) 13 15 FIGURE 7. MAXIMUM OPERATING AMBIENT TEMPERATURE vs SUPPLY VOLTAGE Enable/Disable Function When enabled the amplifier functions as a normal current feedback amplifier with all of the data in the electrical specifications table being valid and applicable. When disabled the amplifier output assumes a true high impedance state and the supply current is reduced significantly. HA5024 The circuit shown in Figure 8 is a simplified schematic of the enable/disable function. The large value resistors in series with the DISABLE pin makes it appear as a current source to the driver. When the driver pulls this pin low current flows out of the pin and into the driver. This current, which may be as large as 350µA when external circuit and process variables are at their extremes, is required to insure that point “A” achieves the proper potential to disable the output.The driver must have the compliance and capability of sinking all of this current. When VCC is +5V the DISABLE pin may be driven with a dedicated TTL gate. The maximum low level output voltage of the TTL gate, 0.4V, has enough compliance to insure that the amplifier will always be disabled even though D1 will not turn on, and the TTL gate will sink enough current to keep point “A” at its proper voltage. When VCC is greater than +5V the DISABLE pin should be driven with an open collector device that has a breakdown rating greater than VCC . Referring to Figure 8, it can be seen that R6 will act as a pull-up resistor to +VCC if the DISABLE pin is left open. In those cases where the enable/disable function is not required on all circuits some circuits can be permanently enabled by letting the DISABLE pin float. If a driver is used to set the enable/disable level, be sure that the driver does not sink more than 20µA when the DISABLE pin is at a high level. TTL gates, especially CMOS versions, do not violate this criteria so it is permissible to control the enable/disable function with TTL. When the plus supply rail is 5V the disable pin can be driven by a dedicated TTL gate as discussed earlier. If a multiplexer IC or its equivalent is used to select channels its logic must be break before make. When these conditions are satisfied the HA5024IP is often used as a remote video multiplexer, and the multiplexer may be extended by adding more amplifier ICs. Low Impedance Multiplexer Two common problems surface when you try to multiplex multiple high speed signals into a low impedance source such as an A/D converter. The first problem is the low source impedance which tends to make amplifiers oscillate and causes gain errors. The second problem is the multiplexer which supplies no gain, introduces all kinds of distortion and limits the frequency response. Using op amps which have an enable/disable function, such as the HA5024, eliminates the multiplexer problems because the external mux chip is not needed, and the HA5024 can drive low impedance (large capacitance) loads if a series isolation resistor is used. VIDEO INPUT #1 R1 75 (NOTE 17) 100Ω 3 + 2 - (NOTE 17) 100Ω R6 15K R10 R8 R7 15K A QP3 ENABLE/DISABLE INPUT FIGURE 8. SIMPLIFIED SCHEMATIC OF ENABLE/DISABLE FUNCTION 10 +5V 2 3 4 7 S1 ALL OFF R10 2000 -5V (NOTE 17) 100Ω 13 15 11 12 + VIDEO INPUT #3 1 R21 100 R9 75 R7 681 R8 681 QP18 D1 8 + 9 - U1B R6 75 R33 R5 2000 R2 681 R3 681 VIDEO OUTPUT TO 75Ω LOAD 4 U1A +VCC R4 75 1 R14 75 - R11 75 U1C 14 R15 2000 R12 681 R13 681 Typical Applications +5V Four Channel Video Multiplexer Referring to the amplifier U1A in Figure 9, R1 terminates the cable in its characteristic impedance of 75Ω, and R4 back terminates the cable in its characteristic impedance. The amplifier is set up in a gain configuration of +2 to yield an overall network gain of +1 when driving a double terminated cable. The value of R3 can be changed if a different network gain is desired. R5 holds the disable pin at ground thus inhibiting the amplifier until the switch, S1, is thrown to position 1. At position 1 the switch pulls the disable pin up to the plus supply rail thereby enabling the amplifier. Since all of the actual signal switching takes place within the amplifier, its differential gain and phase parameters, which are 0.03% and 0.03 degrees respectively, determine the circuit’s performance. The other three circuits, U1B through U1D, operate in a similar manner. 8 (NOTE 17) 100Ω 18 VIDEO INPUT #4 19 U1D R16 75 R18 681 6 + - R19 75 20 17 R17 681 R20 2000 +5V -5V IN +5V IN 0.1µF 10µF 0.1µF -5V 10µF NOTES: 18. U1 is HA5024IP. 19. All resistors in Ω. 20. S1 is break before make. 21. Use ground plane. FIGURE 9. FOUR CHANNEL VIDEO MULTIPLEXER HA5024 to be break before make. R4 is enclosed in the feedback loop of the amplifier so that the large open loop amplifier gain of U2 will present the load with a small closed loop output impedance while keeping the amplifier stable for all values of load capacitance. Referring to Figure 10, both inputs are terminated in their characteristic impedance; 75Ω is typical for video applications. Since the drivers usually are terminated in their characteristic impedance the input gain is 0.5, thus the amplifiers, U2, are configured in a gain of +2 to set the circuit gain equal to one. Resistors R2 and R3 determine the amplifier gain, and if a different gain is desired R2 should be changed according to the equation G = (1 + R3/R2). R3 sets the frequency response of the amplifier so you should refer to the manufacturers data sheet before changing its value. R5, C1 and D1 are an asymmetrical charge/discharge time circuit which configures U1 as a break before make switch to prevent both amplifiers from being active simultaneously. If this design is extended to more channels the drive logic must be designed The circuit shown in Figure 10 was tested for the full range of capacitor values with no oscillations being observed; thus, problem one has been solved.The frequency and gain characteristics of the circuit are now those of the amplifier independent of any multiplexing action; thus, problem two has been solved. The multiplexer transition time is approximately 15µs with the component values shown. R3A 681 INPUT B R1A 681 R1A 75 R4A U2A 27 16 1 + 4 -5V 2 100Ω 3 (NOTE 17) 0.01µF INPUT A D1A 1N4148 R1B 75 R5A U1C 2000 R3B 681 C1A 0.047µF R2B 681 CHANNEL SWITCH R5B 2000 U1A INHIBIT R6 100K U1B 100Ω (NOTE 17) 7 U2B - 10 6 + 13 5 OUTPUT +5V 0.01µF U1D D1B 1N4148 C1B 0.047µF FIGURE 10. LOW IMPEDANCE MULTIPLEXER 9 R4B 27 NOTES: 22. U2: HA5022/24. 23. U1: CD4011. HA5024 Typical Performance Curves VSUPPLY = ±5V, AV = +1, RF = 1kΩ, RL = 400Ω, TA = 25oC, Unless Otherwise Specified 5 5 VOUT = 0.2VP-P CL = 10pF AV = +1, RF = 1kΩ 3 AV = 2, RF = 681Ω 2 AV = 5, RF = 1kΩ 3 1 0 -1 -2 -3 AV = -1 2 1 AV = -2 0 -1 -2 AV = -10 -3 AV = 10, RF = 383Ω AV = -5 -4 -4 -5 -5 100 200 2 -90 90 AV = -1, RF = 750Ω -135 45 AV = +10, RF = 383Ω -100 0 -225 -45 -270 -90 AV = -10, RF = 750Ω -315 -135 VOUT = 0.2VP-P CL = 10pF -360 2 -180 10 100 -3dB BANDWIDTH (MHz) 135 -45 INVERTING PHASE (DEGREES) AV = +1, RF = 1kΩ 180 VOUT = 0.2VP-P CL = 10pF AV = +1 130 120 -3dB BANDWIDTH 5 200 500 700 -3dB BANDWIDTH 10 5 GAIN PEAKING 800 950 0 1100 FEEDBACK RESISTOR (Ω) FIGURE 15. BANDWIDTH AND GAIN PEAKING vs FEEDBACK RESISTANCE 10 -3dB BANDWIDTH (MHz) 95 GAIN PEAKING (dB) -3dB BANDWIDTH (MHz) VOUT = 0.2VP-P CL = 10pF AV = +2 650 900 1100 1300 FEEDBACK RESISTOR (Ω) 0 1500 FIGURE 14. BANDWIDTH AND GAIN PEAKING vs FEEDBACK RESISTANCE 100 500 10 GAIN PEAKING FIGURE 13. PHASE RESPONSE AS A FUNCTION OF FREQUENCY 350 200 140 FREQUENCY (MHz) 90 100 FIGURE 12. INVERTING FREQUENCY RESPONSE FIGURE 11. NON-INVERTING FREQUENCY RESPONSE 0 10 FREQUENCY (MHz) GAIN PEAKING (dB) 10 FREQUENCY (MHz) 130 120 -3dB BANDWIDTH 110 6 100 GAIN PEAKING VOUT = 0.2VP-P 90 4 2 CL = 10pF AV = +1 80 0 200 400 600 800 LOAD RESISTOR (Ω) FIGURE 16. BANDWIDTH AND GAIN PEAKING vs LOAD RESISTANCE 0 1000 GAIN PEAKING (dB) 2 NONINVERTING PHASE (DEGREES) VOUT = 0.2VP-P CL = 10pF RF = 750Ω 4 NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) 4 HA5024 Typical Performance Curves VSUPPLY = ±5V, AV = +1, RF = 1kΩ, RL = 400Ω, TA = 25oC, Unless Otherwise Specified (Continued) 16 80 VOUT = 0.1VP-P CL = 10pF VSUPPLY = ±5V, AV = +2 60 OVERSHOOT (%) -3dB BANDWIDTH (MHz) VOUT = 0.2VP-P CL = 10pF AV = +10 40 12 VSUPPLY = ±15V, AV = +2 6 20 VSUPPLY = ±5V, AV = +1 VSUPPLY = ±15V, AV = +1 0 200 350 500 650 FEEDBACK RESISTOR (Ω) 800 0 950 FIGURE 17. BANDWIDTH vs FEEDBACK RESISTANCE 0 200 800 1000 FIGURE 18. SMALL SIGNAL OVERSHOOT vs LOAD RESISTANCE 0.08 0.10 FREQUENCY = 3.58MHz 0.08 DIFFERENTIAL PHASE (DEGREES) FREQUENCY = 3.58MHz DIFFERENTIAL GAIN (%) 400 600 LOAD RESISTANCE (Ω) RL = 75Ω 0.06 RL = 150Ω 0.04 0.02 RL = 1kΩ 0.06 0.04 RL = 150Ω RL = 75Ω 0.02 RL = 1kΩ 0.00 0.00 3 5 7 9 11 SUPPLY VOLTAGE (±V) 13 3 15 5 7 9 11 SUPPLY VOLTAGE (±V) 13 15 FIGURE 20. DIFFERENTIAL PHASE vs SUPPLY VOLTAGE FIGURE 19. DIFFERENTIAL GAIN vs SUPPLY VOLTAGE -40 VOUT = 2.0VP-P CL = 30pF 0 -10 -50 REJECTION RATIO (dB) DISTORTION (dBc) HD2 -60 3RD ORDER IMD -70 HD2 HD3 -80 -20 -30 -40 CMRR -50 -60 NEGATIVE PSRR -70 -80 HD3 -90 0.3 AV = +1 1 FREQUENCY (MHz) FIGURE 21. DISTORTION vs FREQUENCY 11 10 POSITIVE PSRR 0.001 0.01 0.1 FREQUENCY (MHz) 1 10 FIGURE 22. REJECTION RATIOS vs FREQUENCY 30 HA5024 Typical Performance Curves VSUPPLY = ±5V, AV = +1, RF = 1kΩ, RL = 400Ω, TA = 25oC, Unless Otherwise Specified (Continued) 12 8.0 RLOAD = 100Ω VOUT = 1.0VP-P PROPAGATION DELAY (ns) PROPAGATION DELAY (ns) RL = 100Ω VOUT = 1.0VP-P AV = +1 7.5 7.0 6.5 10 AV = +10, RF = 383Ω 8 AV = +2, RF = 681Ω 6 AV = +1, RF = 1kΩ 4 6.0 -50 -25 0 25 50 75 TEMPERATURE (oC) 100 125 3 FIGURE 23. PROPAGATION DELAY vs TEMPERATURE 5 7 9 11 SUPPLY VOLTAGE (±V) 13 15 FIGURE 24. PROPAGATION DELAY vs SUPPLY VOLTAGE 500 0.8 VOUT = 2VP-P VOUT = 0.2VP-P CL = 10pF 0.6 450 0.4 SLEW RATE (V/µs) NORMALIZED GAIN (dB) + SLEW RATE 400 350 - SLEW RATE 300 250 200 0.2 0 AV= +2, RF = 681Ω -0.2 -0.4 AV= +5, RF = 1kΩ -0.6 AV = +1, RF = 1kΩ -0.8 150 -1.0 100 AV = +10, RF = 383Ω -1.2 -50 -25 0 25 50 75 TEMPERATURE (oC) 100 125 5 10 15 20 FREQUENCY (MHz) 25 30 FIGURE 26. NON-INVERTING GAIN FLATNESS vs FREQUENCY FIGURE 25. SLEW RATE vs TEMPERATURE 0.8 VOUT = 0.2VP-P CL = 10pF RF = 750Ω 0.2 AV = -1 0 -0.2 -0.4 -0.6 AV = -5 -0.8 -1.0 -1.2 10 -INPUT NOISE CURRENT 80 800 600 60 +INPUT NOISE CURRENT 400 40 INPUT NOISE VOLTAGE 200 20 AV = -2 AV = -10 5 1000 AV = +10, RF = 383Ω 15 20 25 30 FREQUENCY (MHz) FIGURE 27. INVERTING GAIN FLATNESS vs FREQUENCY 12 0 0.01 0.1 1 10 0 100 FREQUENCY (kHz) FIGURE 28. INPUT NOISE CHARACTERISTICS CURRENT NOISE (pA/√Hz) NORMALIZED GAIN (dB) 0.4 100 VOLTAGE NOISE (nV/√Hz) 0.6 HA5024 Typical Performance Curves VSUPPLY = ±5V, AV = +1, RF = 1kΩ, RL = 400Ω, TA = 25oC, Unless Otherwise Specified (Continued) 1.5 BIAS CURRENT (µA) 2 VIO (mV) 1.0 0.5 0.0 -60 0 -2 -4 -40 -20 0 20 40 60 80 100 120 -60 140 -40 -20 0 60 80 100 120 140 4000 TRANSIMPEDANCE (kΩ) 22 BIAS CURRENT (µA) 40 FIGURE 30. +INPUT BIAS CURRENT vs TEMPERATURE FIGURE 29. INPUT OFFSET VOLTAGE vs TEMPERATURE 20 18 16 -60 -40 -20 0 20 40 60 80 100 120 3000 2000 1000 -60 140 -40 -20 0 20 40 60 80 100 120 140 TEMPERATURE (oC) TEMPERATURE (oC) FIGURE 31. -INPUT BIAS CURRENT vs TEMPERATURE FIGURE 32. TRANSIMPEDANCE vs TEMPERATURE 74 25 72 REJECTION RATIO (dB) 55oC 20 125oC ICC (mA) 20 TEMPERATURE (oC) TEMPERATURE (oC) 15 10 5 3 4 5 6 7 70 68 -PSRR 66 64 62 60 25oC 8 9 10 11 12 13 14 SUPPLY VOLTAGE (±V) FIGURE 33. SUPPLY CURRENT vs SUPPLY VOLTAGE 13 15 +PSRR 58 -100 CMRR -50 0 50 100 150 200 TEMPERATURE (oC) FIGURE 34. REJECTION RATIO vs TEMPERATURE 250 HA5024 Typical Performance Curves VSUPPLY = ±5V, AV = +1, RF = 1kΩ, RL = 400Ω, TA = 25oC, Unless Otherwise Specified (Continued) 4.0 30 +10V +5V +15V OUTPUT SWING (V) SUPPLY CURRENT (mA) 40 20 10 3.8 3.6 0 0 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 -60 -40 -20 0 20 40 60 80 100 120 140 TEMPERATURE (oC) DISABLE INPUT VOLTAGE (V) FIGURE 35. SUPPLY CURRENT vs DISABLE INPUT VOLTAGE FIGURE 36. OUTPUT SWING vs TEMPERATURE 30 1.2 VS = ±15V 1.1 VIO (mV) VOUT (VP-P) 20 VS = ±10V 1.0 10 0.9 VS = ±4.5V 0.8 0 0.01 0.10 1.00 -60 10.00 -40 -20 0 40 60 80 100 120 140 FIGURE 38. INPUT OFFSET VOLTAGE CHANGE BETWEEN CHANNELS vs TEMPERATURE FIGURE 37. OUTPUT SWING vs LOAD RESISTANCE 1.5 30 -55oC 25 1.0 ICC (mA) ∆BIAS CURRENT (µA) 20 TEMPERATURE (oC) LOAD RESISTANCE (kΩ) 25oC 20 15 0.5 125oC 10 0.0 -60 5 -40 -20 0 20 40 60 80 TEMPERATURE (oC) 100 120 FIGURE 39. INPUT BIAS CURRENT CHANGE BETWEEN CHANNELS vs TEMPERATURE 14 140 3 4 5 6 7 8 9 10 11 SUPPLY VOLTAGE (±V) 12 13 14 15 FIGURE 40. DISABLE SUPPLY CURRENT vs SUPPLY VOLTAGE HA5024 Typical Performance Curves VSUPPLY = ±5V, AV = +1, RF = 1kΩ, RL = 400Ω, TA = 25oC, Unless Otherwise Specified (Continued) 18 30 ENABLE 28 ENABLE TIME (ns) -40 -50 -60 16 14 26 ENABLE 24 10 20 8 18 6 DISABLE 4 16 -70 14 -80 0.1 1 FREQUENCY (MHz) 10 -10 -0.5 0 0.5 1.0 1.5 0 2.5 2.0 OUTPUT VOLTAGE (V) FIGURE 42. ENABLE/DISABLE TIME vs OUTPUT VOLTAGE TRANSIMPEDANCE (MΩ) 0 2 DISABLE 12 -2.5 -2.0 -1.5 -1.0 30 FIGURE 41. CHANNEL SEPARATION vs FREQUENCY DISABLE = 0V VIN = 5VP-P RF = 750Ω -20 -30 -40 -50 10 RL = 100Ω 1 0.1 0.01 180 0.001 135 90 45 -60 0 -70 -45 -80 -90 1 FREQUENCY (MHz) 10 FIGURE 43. DISABLE FEEDTHROUGH vs FREQUENCY 20 0.001 0.01 0.1 1 FREQUENCY (MHz) 10 RL = 400Ω 1 0.1 0.01 180 0.001 135 90 45 0 -45 -90 -135 0.001 0.01 0.1 1 10 FREQUENCY (MHz) 100 FIGURE 45. TRANSIMPEDENCE vs FREQUENCY 15 10 -135 100 FIGURE 44. TRANSIMPEDANCE vs FREQUENCY PHASE ANGLE (DEGREES) 0.1 TRANSIMPEDANCE (MΩ) FEEDTHROUGH (dB) 12 22 PHASE ANGLE (DEGREES) SEPARATION (dB) 20 32 AV = +1 VOUT = 2VP-P DISABLE TIME (µs) -30 HA5024 Die Characteristics DIE DIMENSIONS: PASSIVATION: 2680µm x 2600µm x 483µm Type: Nitride Thickness: 4kÅ ±0.4kÅ METALLIZATION: TRANSISTOR COUNT: Type: Metal 1: AlCu (1%) Thickness: Metal 1: 8kÅ ±0.4kÅ 248 Type: Metal 2: AlCu (1%) Thickness: Metal 2: 16kÅ ±0.8kÅ PROCESS: High Frequency Bipolar Dielectric Isolation SUBSTRATE POTENTIAL (Powered Up): V- Metallization Mask Layout HA5024 -IN1 OUT1 OUT4 -IN4 2 1 20 19 +IN1 3 18 +IN4 DIS1 4 17 DIS4 V+ 6 15 V- DIS2 7 14 DIS3 +IN2 8 13 +IN3 9 10 11 12 -IN2 OUT2 OUT3 -IN3 All Intersil semiconductor products are manufactured, assembled and tested under ISO9000 quality systems certification. Intersil semiconductor products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries. For information regarding Intersil Corporation and its products, see web site http://www.intersil.com 16