MCP37211-200 MCP37D11-200 200 Msps, 12-Bit Low-Power ADC with 8-Channel MUX Features • Sample Rates: - 200 Msps for single-channel mode - 200 Msps/number of channels used • SNR with fIN = 15 MHz and -1 dBFS: - 71.3 dBFS (typical) at 200 Msps • SFDR with fIN = 15 MHz and -1 dBFS: - 90 dBc (typical) at 200 Msps • Power Dissipation with LVDS Digital I/O: - 468 mW at 200 Msps • Power Dissipation with CMOS Digital I/O: - 436 mW at 200 Msps, Output Clock = 100 MHz • Power Dissipation Excluding Digital I/O: - 387 mW at 200 Msps • Power-Saving Modes: - 80 mW during Standby - 33 mW during Shutdown • Supply Voltage: - Digital Section: 1.2V, 1.8V - Analog Section: 1.2V, 1.8V • Selectable Full-Scale Input Range: up to 2.975 VP-P • Input Channel Bandwidth: 500 MHz • Channel-to-Channel Crosstalk in Multi-Channel Mode (Input = 15 MHz, -1 dBFS): >95 dB • Output Data Format: - Parallel CMOS, DDR LVDS • Optional Output Data Randomizer • Serial Peripheral Interface (SPI) • Digital Signal Post-Processing (DSPP) Options: - Decimation filters for improved SNR - Fractional Delay Recovery (FDR) for timedelay corrections in multi-channel operations (dual-/octal-channel modes) - Noise-Shaping Requantizer (NSR) - Phase, Offset and Gain adjust of individual channels - Digital Down-Conversion (DDC) with I/Q or fS/8 output (MCP37D11-200) - Continuous wave beamforming for octalchannel mode (MCP37D11-200) • Built-In ADC Linearity Calibration Algorithms: - Harmonic Distortion Correction (HDC) - DAC Noise Cancellation (DNC) - Dynamic Element Matching (DEM) - Flash Error Calibration • Package Options: - VTLA-124 (9 mm x 9 mm x 0.9 mm) - TFBGA-121 (8 mm x 8 mm x 1.08 mm) • No external reference decoupling capacitor required for TFBGA Package • Industrial Temperature Range: -40°C to +85°C Typical Applications • • • • • • Communication Instruments Microwave Digital Radio Cellular Base Stations Radar Ultrasound and Sonar Imaging Scanners and Low-Power Portable Instruments MCP372XX/MCP37DXX Family Comparison (1, 2): Digital Digital CW Decimation(3) Down-Conversion(4) Beamforming(5) Noise-Shaping Requantizer(3) Part Number Sample Rate Resolution MCP37231-200 200 Msps 16 Yes No No No MCP37221-200 200 Msps 14 Yes No No No MCP37211-200 200 Msps 12 Yes No No Yes MCP37D31-200 200 Msps 16 Yes Yes Yes No MCP37D21-200 200 Msps 14 Yes Yes Yes No MCP37D11-200 200 Msps 12 Yes Yes Yes Yes Note 1: 2: 3: 4: 5: For TFBGA package, contact Microchip Technology Inc. for availability. Devices in the same package type are pin-to-pin compatible. Available in single- and dual-channel mode. Available in single- and dual-channel mode, and octal-channel mode when CW beamforming is enabled. Available in octal-channel mode. 2014-2015 Microchip Technology Inc. DS20005355B-page 1 MCP37211-200 AND MCP37D11-200 Functional Block Diagram AVDD12 CLK+ AVDD18 DVDD12 Duty Cycle Correction Clock Selection CLK- GND DVDD18 DLL PLL AIN0+ AIN0- AIN7+ AIN7- Input Multiplexer Output Clock Control DCLK+ DCLK- Digital Signal Post-Processing: Pipelined ADC - FDR, Decimation - Phase/Offset/Gain Adj. - DDC, CW Beamforming (MCP37D11-200) VREF+ WCK VREF- OVR Output Control: VCM - CMOS, DDR LVDS - Serialized LVDS Reference Generator SENSE Q[11:0] Internal Registers VBG REF1+ DS20005355B-page 2 REF1- REF0+ REF0- SDIO SCLK CS 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 Description The MCP37211-200 is Microchip's baseline 12-bit 200 Msps pipelined ADC, featuring built-in high-order digital decimation filters, noise-shaping requantizer, gain and offset adjustment per channel and fractional delay recovery. The MCP37D11-200 device features digital downconversion and CW beamforming capability, in addition to the features offered by the MCP37211-200. All devices feature harmonic distortion correction and DAC noise cancellation that enable high-performance specifications with SNR of 71.3 dBFS (typical) and SFDR of 90 dBc (typical). These A/D converters exhibit industry-leading lowpower performance with only 468 mW operation while using the LVDS interface at 200 Msps. This superior low-power operation coupled with high dynamic performance makes these devices ideal for various high-performance, high-speed data acquisition systems, including communications equipment, radar and portable instrumentation. representation, with or without the data randomizer option. The output data is available as full-rate CMOS or Double-Data-Rate (DDR) LVDS. These devices also include various features designed to maximize flexibility in the user’s applications and minimize system cost, such as a programmable PLL clock, output data rate control and phase alignment and programmable digital pattern generation. The device’s operational modes and feature sets are configured by setting up the user-programmable registers. The device is available in Pb-free VTLA-124 and TFBGA-121 packages. The device operates over the commercial temperature range of -40°C to +85°C. Package Types Bottom View In single or dual-channel mode, the Noise-Shaping Requantizer (NSR) feature can allow the ADC to improve SNR beyond a conventional 11- or 12-bit ADC. The NSR reshapes the quantization noise, such that most of the noise power is pushed outside the frequency of interest. As a result, SNR is improved significantly within a selected frequency band of interest while SFDR is not affected. The digital down-conversion option in the MCP37D10200 can be utilized with the decimation and quadrature output (I and Q data) option, and offers great flexibility in various digital communication system designs, including cellular base-stations and narrow-band communication systems. The output decimation filter option improves SNR performance up to 73.7 dBFS. The digital downconversion option, in conjunction with the decimation and quadrature output options, offers great flexibility in digital communication system design, including cellular base-stations and narrow-band communications. Dimension: 9 mm x 9 mm x 0.9 mm (a) VTLA-124 Package. Bottom View These devices can have up to eight differential input channels through an input MUX. The sampling rate is up to 200 Msps when a single channel is used, or 25 Msps per channel when all eight input channels are used. In dual or octal-channel mode, the Fractional Delay Recovery (FDR) feature digitally corrects the difference in sampling instance between different channels, so that all inputs appear to have been sampled at the same time. The differential full-scale analog input range is programmable up to 2.975 VP-P. The ADC output data can be coded in two's complement or offset binary 2014-2015 Microchip Technology Inc. Dimension: 8 mm x 8 mm x 1.08 mm Ball Pitch: 0.65 mm Ball Diameter: 0.4 mm (b) TFBGA-121 Package. (Contact Microchip Technology Inc. for availability) DS20005355B-page 3 MCP37211-200 AND MCP37D11-200 NOTES: DS20005355B-page 4 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 1.0 PACKAGE PIN CONFIGURATIONS AND FUNCTION DESCRIPTIONS Top View (Not to Scale) AVDD18 GND AVDD12 REF0- REF0+ AVDD12 VBG NC A68 A66 A67 A1 B56 A65 B55 A64 B54 A63 B52 B53 B1 A60 A61 B50 B51 A58 A59 B48 B49 AVDD18 REF0- REF0+ Note 2 A2 A62 REF1- REF1+ AVDD12 V CM A57 A56 B46 B47 A54 A55 B45 NC SCLK SDIO B43 CS DVDD18 A49 A48 B2 AIN6- B40 B3 AIN2- DVDD12 B39 AIN2+ A4 VTLA-124 (9 mm x 9 mm x 0.9 mm) AIN4+ A5 B4 AIN4- WCK/OVR+ (OVR) B38 AIN0+ A6 B5 AIN0- Q11/Q5+ B37 VCMIN A7 B6 AIN1- DVDD18 B36 AIN1+ EP (GND) A8 B7 AIN7+ AIN7- A9 AIN3- A10 A46 A45 WCK/OVR(WCK) A44 Q10/Q5- B35 Q6/Q3- B34 A42 Q7/Q3+ Note 4 B8 AIN3+ A47 A43 Q9/Q4+ Q8/Q4- B9 AIN5+ Q5/Q2+ B33 B10 Q3/Q1+ AIN5- A11 A41 DVDD18 A40 Q4/Q2- B32 A12 A39 Q2/Q1B11 A13 DVDD18 B31 AVDD12 A38 Q1/Q0+ B12 Q0/Q0- B30 A37 A14 B29 B13 A15 AVDD12 NC B14 A16 A17 Note 2 B41 AVDD18 AIN6+ A3 A51 A50 B42 B44 SENSE REF1- REF1+ A52 A53 A18 Note 2 B15 A19 CLK- B16 A20 B17 A21 Note 1 ADR0 SYNC GND B18 A22 B19 A23 CLK+ AVDD18 SLAVE B20 A24 B21 A25 B22 A26 TP DVDD18 RESET DCLK+ B23 A27 DVDD12 CAL DCLK- B25 B24 A28 A29 Note 3 A36 DVDD18 B26 A30 A31 DVDD12 NC B28 B27 A32 A33 A35 A34 Note 2 Note 1: Tie to GND or DVDD18. ADR1 is internally bonded to GND. 2: NC – Not connected pins. These pins can float or be tied to ground. 3: TP – Test pins. Leave these pins floating and do not tie to ground or supply. 4: Exposed pad (EP – back pad of the package) is the common ground (GND) for analog and digital supplies. Connect this pad to a clean ground reference on the PCB. FIGURE 1-1: VTLA-124 Package. See Table 1-1 for the pin descriptions. Decoupling capacitors for reference pins and VBG are embedded in the package. Leave TP pins floating always. 2014-2015 Microchip Technology Inc. DS20005355B-page 5 MCP37211-200 AND MCP37D11-200 TABLE 1-1: PIN FUNCTION TABLE FOR VTLA-124 Pin No. Name I/O Type Description A2, A22, A65, B1, B52 AVDD18 Supply A12, A56, A60, A63, B10, B11, B12, B13, B15, B16, B45, B49, B53 AVDD12 Supply voltage input (1.2V) for analog section A25, A30, B39 DVDD12 Supply voltage input (1.2V) for digital section A41, B24, B27, B31, B36, B43 DVDD18 Supply voltage input (1.8V) for digital section and all digital I/O EP GND Power Supply Pins Supply voltage input (1.8V) for analog section Exposed pad: Common ground pin for digital and analog sections ADC Analog Input Pins A3 AIN6+ B2 AIN6- Analog Input Channel 6 differential analog input (+) A4 AIN2+ Channel 2 differential analog input (+) B3 AIN2- Channel 2 differential analog input (-) A5 AIN4+ Channel 4 differential analog input (+) B4 AIN4- Channel 4 differential analog input (-) A6 AIN0+ Channel 0 differential analog input (+) B5 AIN0- Channel 0 differential analog input (-) B6 AIN1+ Channel 1 differential analog input (+) A8 AIN1- Channel 1 differential analog input (-) B7 AIN7+ Channel 7 differential analog input (+) A9 AIN7- Channel 7 differential analog input (-) Channel 6 differential analog input (-) B8 AIN3+ Channel 3 differential analog input (+) A10 AIN3- Channel 3 differential analog input (-) B9 AIN5+ Channel 5 differential analog input (+) A11 AIN5- Channel 5 differential analog input (-) A21 CLK+ Differential clock input (+) B17 CLK- Differential clock input (-) Reference Pins(1) A57, B46 REF1+ Analog Output Differential reference 1 (+) voltage A58, B47 REF1- A61, B50 REF0+ Differential reference 0 (+) voltage Differential reference 1 (-) voltage A62, B51 REF0- Differential reference 0 (-) voltage SENSE, Bandgap and Common-Mode Voltage Pins B48 SENSE Analog Input Analog input full-scale range selection. See Table 4-2 for SENSE voltage settings. A59 VBG Analog Output Internal bandgap output voltage Connect a decoupling capacitor (2.2 µF) A7 VCMIN Analog Input Common-mode voltage input for auto-calibration Connect VCM voltage(2) A55 VCM DS20005355B-page 6 Common-mode output voltage (900 mV) for analog input signal Connect a decoupling capacitor (0.1 µF)(3) 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 TABLE 1-1: PIN FUNCTION TABLE FOR VTLA-124 (CONTINUED) Pin No. Name I/O Type Description Digital I/O Pins Digital Input SPI address selection pin (A0 bit). Tie to GND or DVDD18.(4) B18 ADR0 A23 SLAVE B19 SYNC Digital Input/ Not used. Leave this pin floating(11) Output B21 RESET Digital Input Reset control input: High: Normal operating mode Low: Reset mode(5) A26 CAL B22 DCLK+ LVDS: Differential digital clock output (+) CMOS: Digital clock output(7) A27 DCLK- LVDS: Differential digital clock output (-) CMOS: Unused (leave floating) Not used. Tie to GND(11) Digital Output Calibration status flag digital output: High: Calibration is complete Low: Calibration is not complete(5) ADC Output Pins(8) B30 Q0/Q0- A38 Q1/Q0+ Digital Output Digital data output: CMOS = Q0, DDR LVDS = Q0Digital data output: CMOS = Q1, DDR LVDS = Q0+ A39 Q2/Q1- Digital data output: CMOS = Q2, DDR LVDS = Q1- B32 Q3/Q1+ Digital data output: CMOS = Q3, DDR LVDS = Q1+ A40 Q4/Q2- Digital data output: CMOS = Q4, DDR LVDS = Q2- B33 Q5/Q2+ Digital data output: CMOS = Q5, DDR LVDS = Q2+ B34 Q6/Q3- Digital data output: CMOS = Q6, DDR LVDS = Q3- A42 Q7/Q3+ Digital data output: CMOS = Q7, DDR LVDS = Q3+ B35 Q8/Q4- Digital data output: CMOS = Q8, DDR LVDS = Q4- A43 Q9/Q4+ Digital data output: CMOS = Q9, DDR LVDS = Q4+ A44 Q10/Q5- Digital data output: CMOS = Q10, DDR LVDS = Q5- B37 Q11/Q5+ Digital data output: CMOS = Q11, DDR LVDS = Q5+ B38 WCK/OVR+ (OVR) A45 WCK/OVR(WCK) WCK: Word clock sync digital output OVR: Input over-range indication digital output(10) SPI Interface Pins A53 SDIO A54 SCLK B44 CS Digital Input/ SPI data input/output Output Digital Input SPI serial clock input SPI Chip Select input Not Connected Pins A1, A13 - A20, A32 - A37, A46 - A52, A66 - A68, B14, B28, B29, B40, B41, B42, B55, B56 NC These pins can be tied to ground or left floating. Pins that need to be grounded A24, A64, B20, B54 GND These pins are not supply pins, but need to be tied to ground. Output Test Pins A28, A29, A31, B23, B25, B26 TP 2014-2015 Microchip Technology Inc. Digital Output Output test pins. Do not use. Always Leave these pins floating.(9) DS20005355B-page 7 MCP37211-200 AND MCP37D11-200 Notes: 1. These pins are for the internal reference voltage outputs. They should not be driven. External decoupling circuits are required. See Section 4.5.3, "Decoupling Circuits for Internal Voltage Reference and Bandgap Output" for details. 2. VCMIN is used for Auto-Calibration only. VCMIN+ and VCMIN- should be tied together always. There should be no voltage difference between the two pins. Typically both VCMIN+ and VCMIN- are tied to the VCM output pin together, but they can be tied to another common-mode voltage if external VCM is used. This pin has High Z input in Shutdown, Standby and Reset modes. 3. When the VCM output is used for the common-mode voltage of analog inputs (i.e. by connecting to the centertap of a balun), the VCM pin should be decoupled with a 0.1 µF capacitor, and should be directly tied to the VCMIN+ and VCMIN- pins. 4. ADR1 (for A1 bit) is internally bonded to GND (‘0’). If ADR0 is dynamically controlled, ADR0 must be held constant while CS is "Low” 5. The device is in Reset mode while this pin stays "Low". On the rising edge of RESET, the device exits Reset mode, initializes all internal user registers to default values, and begins power-up calibration. 6. CAL pin stays "Low" at power-up until the first power-up calibration is completed. When the first calibration has completed, this pin has "High" output. It stays "High" until the internal calibration is restarted by hardware or a soft reset command. In Reset mode, this pin is "Low". In Standby and Shutdown modes, this pin will maintain the prior condition. 7. The phase of DCLK relative to the data output bits may be adjusted depending on the operating mode. This is controlled differently depending on the configuration of the digital signal post-processing, PLL and/or DLL. See also Addresses 0x52, 0x64 and 0x6D (Registers 5-7, 5-22 and 5-28) for more details. 8. DDR LVDS: Two data bits are multiplexed onto each differential output pair. The output pins shown here are for the “Even bit first”, which is the default setting of OUTPUT_MODE<1:0> in Address 0x62 (Register 5-20). The even data bits (Q0, Q2, Q4, Q6, Q8, Q10) appear when DCLK+ is "High". The odd data bits (Q1, Q3, Q5, Q7, Q9, Q11) appear when DCLK+ is "Low”. See Addresses 0x65 (Register 5-23) and 0x68 (Register 5-26) for output polarity control. See Figure 2-2 for LVDS output timing diagram. 9. Do not tie to ground or supply. 10. CMOS output mode: WCK/OVR- is WCK and WCK/OVR+ is OVR. DDR LVDS output mode: The rising edge of DCLK+ is WCK and the falling edge is OVR. OVR: OVR will be held “High”’ when analog input overrange is detected. Digital signal post-processing will cause OVR to assert early relative to the output data. See Figure 2-2 for LVDS timing of these bits. WCK: WCK is normally “Low”. WCK is “High” while data from the first channel is sent out. In single-channel mode, WCK stays “High” except when in I/Q output mode. See Section 4.12.4 “Word Clock (WCK)” for further WCK description. 11. This pin function is not released yet. DS20005355B-page 8 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 Top View (Not to Scale) 1 2 A SDIO VCM B SCLK CS C WCK/ WCK/ OVR- OVR+ (WCK) (OVR) 3 4 REF1+ REF1- 5 VBG 6 7 REF0+ REF0- 8 9 10 11 GND GND AIN4- AIN2+ GND GND SENSE AVDD12 AVDD12 AVDD18 AVDD18 AIN4+ AIN2- GND GND AVDD12 AVDD12 AVDD12 GND GND AIN6- AIN0+ D Q10/Q5- Q11/Q5+ GND GND AVDD12 AVDD12 AVDD12 GND GND AIN6+ AIN0- E Q8/Q4- Q9/Q4+ GND GND AVDD12 AVDD12 AVDD12 GND GND AIN5+ AIN1+ F Q6/Q3- Q7/Q3+ DVDD18 DVDD18 AVDD12 AVDD12 AVDD12 GND GND AIN5- AIN1- G Q4/Q2- Q5/Q2+ DVDD18 DVDD18 GND GND GND AIN7- AIN3+ H Q2/Q1- Q3/Q1+ DVDD12 DVDD12 GND GND GND GND GND AIN7+ AIN3- J Q0/Q0- Q1/Q0+ DVDD12 DVDD12 GND GND GND GND GND CAL GND SLAVE ADR0 ADR1 GND GND CLK- GND AVDD18 K TP TP TP DCLK- L TP TP TP DCLK+ RESET SYNC All others: AVDD12 AVDD12 CLK+ VCMIN+ VCMINGND Analog Digital Supply Voltage Notes: • • • • Die dimension: 8 mm x 8 mm x 1.08 mm. Ball dimension: (a) Ball Pitch = 0.65 mm, (b) Ball Diameter = 0.4 mm. Flip-chip solder ball composition: Sn with Ag 1.8%. Solder sphere composition: SAC-405 (Sn/Au 4%/Cu 0.5%). FIGURE 1-2: TFBGA-121 Package. See Table 1-2 for the pin descriptions. Decoupling capacitors for reference pins and VBG are embedded in the package. Leave TP pins floating always. 2014-2015 Microchip Technology Inc. DS20005355B-page 9 MCP37211-200 AND MCP37D11-200 TABLE 1-2: PIN FUNCTION TABLE FOR TFBGA-121 Ball No. Name A1 SDIO A2 VCM A3 A4 A5 REF1+ REF1VBG A6 A7 A8 A9 REF0+ REF0GND A10 AIN4- Analog Input Channel 4 differential analog input (-) A11 B1 AIN2+ SCLK Channel 2 differential analog input (+) Digital Input SPI serial clock input B2 B3 B4 B5 CS GND B6 B7 B8 B9 SENSE AVDD12 AIN4+ B11 C1 AIN2WCK/OVR(WCK) WCK/OVR+ (OVR) GND C3 C4 C5 C6 C7 C8 C9 Supply Analog Input Supply Analog Input C11 D1 AIN0+ Q10/Q5- D2 Q11/Q5+ D3 D4 GND DS20005355B-page 10 Analog input range selection. See Table 4-2 for SENSE voltage settings. Supply voltage input (1.2V) for analog section Channel 4 differential analog input (+) Digital Output Channel 2 differential analog input (-) WCK: Word clock sync digital output OVR: Input overrange indication digital output(2) Supply Common ground for analog and digital sections Supply voltage input (1.2V) for analog section GND AIN6- SPI Chip Select input Common ground for analog and digital sections Supply voltage input (1.8V) for analog section AVDD12 C10 Description Digital Input/ SPI data input/output Output Analog Common-mode output voltage (900 mV) for analog input signal Output Connect a decoupling capacitor (0.1 µF)(1) Differential reference voltage 1 (+/-). Decoupling capacitors are embedded in the TFBGA package. Leave these pins floating. Internal bandgap output voltage A decoupling capacitor (2.2 μF) is embedded in the TFBGA package. Leave this pin floating. Differential reference 0 (+/-) voltage. Decoupling capacitors are embedded in the TFBGA package. Leave these pins floating. Supply Common ground for analog and digital sections AVDD18 B10 C2 I/O Type Common ground pin for analog and digital sections Analog Input Digital Output Supply Channel 6 differential analog input (-) Channel 0 differential analog input (+) Digital data output(3) CMOS = Q10 DDR LVDS = Q5Digital data output(3) CMOS = Q11 DDR LVDS = Q5+ Common ground for analog and digital sections 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 TABLE 1-2: PIN FUNCTION TABLE FOR TFBGA-121 (CONTINUED) Ball No. Name I/O Type D5 D6 D7 D8 D9 AVDD12 Supply D10 AIN6+ D11 E1 AIN0Q8/Q4- E2 Q9/Q4+ E3 E4 E5 E6 E7 E8 E9 GND GND Analog Input Digital Output Supply E11 F1 AIN1+ Q6/Q3- F2 Q7/Q3+ F3 F4 F5 F6 F7 F8 F9 DVDD18 F10 AIN5- F11 G1 AIN1Q4/Q2- G2 Q5/Q2+ G3 G4 G5 G6 G7 G8 G9 DVDD18 Channel 0 differential analog input (-) Digital data output(3) CMOS = Q8 DDR LVDS = Q4Digital data output(3) CMOS = Q9 DDR LVDS = Q4+ Common ground for analog and digital sections Common ground for analog and digital sections Analog Input Digital Output Supply AVDD12 GND Channel 5 differential analog input (+) Channel 1 differential analog input (+) Digital data output(3) CMOS = Q6 DDR LVDS = Q3Digital data output(3) CMOS = Q7 DDR LVDS = Q3+ Supply voltage input (1.8V) for digital section. All digital input pins are driven by the same DVDD18 potential. Supply voltage input (1.2V) for analog section Common ground for analog and digital sections Analog Input Digital Output Supply GND AVDD12 Channel 6 differential analog input (+) Supply voltage input (1.2V) for analog section GND AIN5+ Supply voltage input (1.2V) for analog section Common ground for analog and digital sections AVDD12 E10 Description Supply GND 2014-2015 Microchip Technology Inc. Channel 5 differential analog input (-) Channel 1 differential analog input (-) Digital data output(3) CMOS = Q4 DDR LVDS = Q2Digital data output(3) CMOS = Q5 DDR LVDS = Q2+ Supply voltage input (1.8V) for digital section All digital input pins are driven by the same DVDD18 potential Common ground for analog and digital sections Supply voltage input (1.2V) for analog section Common ground for analog and digital sections DS20005355B-page 11 MCP37211-200 AND MCP37D11-200 TABLE 1-2: Ball No. PIN FUNCTION TABLE FOR TFBGA-121 (CONTINUED) Name G10 AIN7- G11 H1 AIN3+ Q2/Q1- H2 Q3/Q1+ H3 H4 H5 H6 H7 H8 H9 DVDD12 H10 AIN7+ H11 J1 AIN3Q0/Q0- J2 Q1/Q0+ J3 J4 J5 J6 J7 J8 J9 DVDD12 J10 VCMIN+ J11 VCMIN- K1 K2 K3 K4 TP DCLK- K5 CAL K6 K7 GND SLAVE K8 K9 K10 K11 L1 L2 L3 L4 ADR0 ADR1 GND I/O Type Analog Input Digital Output Supply GND DCLK- DS20005355B-page 12 Channel 3 differential analog input (+) Digital data output(3) CMOS = Q2 DDR LVDS = Q1Digital data output(3) CMOS = Q3 DDR LVDS = Q1+ Supply voltage input (1.2V) for digital section Common ground for analog and digital sections Analog Input Digital Output Supply GND TP Description Channel 7 differential analog input (-) Channel 7 differential analog input (+) Channel 3 differential analog input (-) Digital data output(3) CMOS = Q0 DDR LVDS = Q0Digital data output(3) CMOS = Q1 DDR LVDS = Q0+ DC supply voltage input pin for digital section (1.2V) Common ground for analog and digital sections Analog Input Common-mode voltage input for auto-calibration(4) These two pins should be tied together and connected to VCM voltage. Digital Output Output test pints. Leave these pins floating always(8) LVDS: Differential digital clock output (-) CMOS: Not used (leave floating) Digital Calibration status flag digital output(5) Output High: Calibration is complete Low: Calibration is not complete Supply Common ground pin for analog and digital sections Digital Input Not used. Tie this pin to GND(10) SPI address selection pin (A0 bit). Tie to GND or DVDD18(6) SPI address selection pin (A1 bit). Tie to GND or DVDD18(6) Supply Common ground for analog and digital sections Digital Output Output test pints. Leave these pins floating always(8) LVDS: Differential digital clock output (+) CMOS: Digital clock output(7) 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 TABLE 1-2: PIN FUNCTION TABLE FOR TFBGA-121 (CONTINUED) Ball No. Name L5 RESET L6 SYNC L7 L8 L9 L10 GND CLK+ CLKGND L11 AVDD18 I/O Type Description Digital Input Reset control input: High: Normal operating mode Low: Reset mode(9) Digital Input/ Not used. Leave this pin floating(10) Output Supply Common ground for analog and digital sections Analog Input Differential clock input (+) Differential clock input (-) Supply Common ground for analog and digital sections Analog Input Supply voltage input (1.8V) for analog section Notes: 1. When the VCM output is used for the common-mode voltage of analog inputs (i.e. by connecting to the center-tap of a balun), the VCM pin should be decoupled with a 0.1 µF capacitor, and should be directly tied to the VCMIN+ and VCMIN- pins. 2. CMOS output mode: WCK/OVR- is WCK and WCK/OVR+ is OVR. DDR LVDS output mode: The rising edge of DCLK+ is WCK and the falling edge is OVR. OVR: OVR will be held “High”’ when analog input overrange is detected. Digital signal post-processing will cause OVR to assert early relative to the output data. See Figure 2-2 for LVDS timing of these bits. WCK: WCK is normally “Low”. WCK is “High” while data from the first channel is sent out. In single-channel mode, WCK stays “High” except when in I/Q output mode. See Section 4.12.4 “Word Clock (WCK)” for further WCK description. 3. DDR LVDS: Two data bits are multiplexed onto each differential output pair. The output pins shown here are for the “Even bit first”, which is the default setting of OUTPUT_MODE<1:0> in Address 0x62 (Register 5-20). The even data bits (Q0, Q2, Q4, Q6, Q8, Q10) appear when DCLK+ is “High”. The odd data bits (Q1, Q3, Q5, Q7, Q9, Q11) appear when DCLK+ is "Low". See Addresses 0x65 (Register 5-23) and 0x68 (Register 5-26) for output polarity control. See Figure 2-2 for LVDS output timing diagram. 4. VCMIN is used for Auto-Calibration only. VCMIN+ and VCMIN- should be tied together always. There should be no voltage difference between the two pins. Typically both VCMIN+ and VCMIN- are tied to the VCM output pin together, but they can be tied to another common-mode voltage if external VCM is used. This pin has High Z input in Shutdown, Standby and Reset modes. 5. CAL pin stays "Low" at power-up until the first power-up calibration is completed. When the first calibration has completed, this pin has "High" output. It stays "High" until the internal calibration is restarted by hardware or a soft reset command. In Reset mode, this pin is "Low". In Standby and Shutdown modes, this pin will maintain the prior condition. 6. If the SPI address is dynamically controlled, the Address pin must be held constant while CS is "Low”. 7. The phase of DCLK relative to the data output bits may be adjusted depending on the operating mode. This is controlled differently depending on the configuration of the digital signal post-processing, PLL and/or DLL. See also Addresses 0x52, 0x64 and 0x6D (Registers 5-7, 5-22 and 5-28) for more details. 8. Do not tie to ground or supply. 9. The device is in Reset mode while this pin stays "Low". On the rising edge of RESET, the device exits Reset mode, initializes all internal user registers to default values, and begins power-up calibration. 10. This pin function is not released yet. 2014-2015 Microchip Technology Inc. DS20005355B-page 13 MCP37211-200 AND MCP37D11-200 NOTES: DS20005355B-page 14 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 2.0 ELECTRICAL SPECIFICATIONS 2.1 Absolute Maximum Ratings† Analog and digital supply voltage (AVDD12, DVDD12) .............. ......................................................................................... -0.3V to 1.32V Analog and digital supply voltage (AVDD18, DVDD18) .............. ......................................................................................... -0.3V to 1.98V All inputs and outputs with respect to GND ............................ ........................................................................... –0.3V to AVDD18 + 0.3V Differential input voltage.......................................................... ........................................................................................|AVDD18 - GND| Current at input pins................................................................ ...................................................................................................... ±2 mA Current at output and supply pins .......................................... .................................................................................................. ±250 mA Storage temperature ............................................................... ...................................................................................... -65°C to +150°C Ambient temperature with power applied (TA) ........................ ...................................................................................... -55°C to +125°C Maximum junction temperature (TJ)........................................ .................................................................................................... +150°C ESD protection on all pins....................................................... ................................................................................................ 2 kV HBM Solder reflow profile ................................................................ ................................ See Microchip Application Note AN233 (DS00233) Notice†: Stresses above those listed under “Maximum Ratings” may cause permanent damage to the device. This is a stress rating only and functional operation of the device at those or any other conditions above those indicated in the operational listings of this specification is not implied. Exposure to maximum rating conditions for extended periods may affect device reliability. 2.2 Electrical Specifications TABLE 2-1: ELECTRICAL CHARACTERISTICS Electrical Specifications: Unless otherwise specified, all parameters apply for TA = -40°C to +85°C, AVDD18 = DVDD18 = 1.8V, AVDD12 = DVDD12 = 1.2V, GND = 0V, SENSE = AVDD12, Single-channel mode, Differential Analog Input (AIN) = Sine wave with amplitude of -1 dBFS, fIN = 70 MHz, Clock Input = 200 MHz, fS = 200 Msps (ADC Core), PLL and decimation filters are disabled, Output load: CMOS data pin = 10 pF, LVDS = 100termination, LVDS driver current setting = 3.5 mA, +25°C is applied for typical value. Parameters Sym. Min. Typ. Max. Units Analog Supply Voltage AVDD18 1.71 1.8 1.89 V AVDD12 1.14 1.2 1.26 V Digital Supply Voltage DVDD18 1.71 1.8 1.89 V DVDD12 1.14 1.2 1.26 V Conditions Power Supply Requirements Note 1 Analog Supply Current Analog Supply Current During Conversion IDD_A18 — 27 46 mA at AVDD18 pin IDD_A12 — 185 252 mA at AVDD12 pin Digital Supply Current During Conversion IDD_D12 — 97 226 mA at DVDD12 pin Digital I/O Current in CMOS Output Mode IDD_D18 — 27 — mA at DVDD18 pin DCLK = 100 MHz Digital I/O Current in LVDS Mode IDD_D18 3.5 mA mode Digital Supply Current Measured at DVDD18 Pin — 45 66 mA 33 — mA 57 1.8 mA mode 5.4 mA mode Supply Current during Power-Saving Modes During Standby Mode During Shutdown Mode ISTANDBY_AN — 21 — ISTANDBY_DIG — 41 — IDD_SHDN — 25 — 2014-2015 Microchip Technology Inc. mA Address 0x00<4:3> = 1,1(2) mA Address 0x00<7,0> = 1,1(3) DS20005355B-page 15 MCP37211-200 AND MCP37D11-200 TABLE 2-1: ELECTRICAL CHARACTERISTICS (CONTINUED) Electrical Specifications: Unless otherwise specified, all parameters apply for TA = -40°C to +85°C, AVDD18 = DVDD18 = 1.8V, AVDD12 = DVDD12 = 1.2V, GND = 0V, SENSE = AVDD12, Single-channel mode, Differential Analog Input (AIN) = Sine wave with amplitude of -1 dBFS, fIN = 70 MHz, Clock Input = 200 MHz, fS = 200 Msps (ADC Core), PLL and decimation filters are disabled, Output load: CMOS data pin = 10 pF, LVDS = 100termination, LVDS driver current setting = 3.5 mA, +25°C is applied for typical value. Parameters Sym. Min. Typ. Max. Units Conditions IDD_PLL — 21 — mA PDISS_ADC — 387 — mW Total Power Dissipation During Conversion with CMOS Output Mode PDISS_CMOS — 436 — mW fS = 200 Msps, DCLK = 100 MHz Total Power Dissipation During Conversion with LVDS Output Mode PDISS_LVDS mW 3.5 mA mode PLL Circuit PLL Circuit Current PLL enabled. Included in analog supply current specification. Total Power Dissipation(4) Power Dissipation During Conversion, Excluding Digital I/O 468 — — 446 — 1.8 mA mode 490 5.4 mA mode During Standby Mode PDISS_STANDBY — 80.4 — mW Address 0x00<4:3> = 1,1(2) During Shutdown Mode PDISS_SHDN — 33 — mW Address 0x00<7,0> = 1,1(3) Power-on Reset (POR) Voltage Threshold Voltage Hysteresis SENSE VPOR — 800 — mV Applicable to AVDD12 only VPOR_HYST — 40 — mV (POR tracks AVDD12) VSENSE GND — AVDD12 V VSENSE selects reference RIN_SENSE — 500 — To virtual ground at 0.55V. 400 mV < VSENSE < 800 mV ISENSE — 500 — µA SENSE = 0.8V — 0.74 — V VSENSE = GND — 1.49 — Input(5,7) SENSE Input Voltage SENSE Pin Input Resistance Current Sink into SENSE Pin Reference and Common-Mode Voltages Internal Reference Voltage (Selected by VSENSE) VREF — 1.86 x VSENSE — Common-Mode Voltage Output VCM — 0.9 — V Available at VCM pin VREF1 — 0.4 — V VSENSE = GND — 0.8 — — 0.4 - 0.8 — — 0.7 — Reference Voltage Output(7,8) VREF0 Bandgap Voltage Output DS20005355B-page 16 VBG VSENSE = AVDD12 400 mV < VSENSE < 800 mV VSENSE = AVDD12 400 mV < VSENSE < 800 mV V VSENSE = GND — 1.4 — VSENSE = AVDD12 — 0.7 - 1.4 — 400 mV < VSENSE < 800 mV — 0.55 — V Available at VBG pin 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 TABLE 2-1: ELECTRICAL CHARACTERISTICS (CONTINUED) Electrical Specifications: Unless otherwise specified, all parameters apply for TA = -40°C to +85°C, AVDD18 = DVDD18 = 1.8V, AVDD12 = DVDD12 = 1.2V, GND = 0V, SENSE = AVDD12, Single-channel mode, Differential Analog Input (AIN) = Sine wave with amplitude of -1 dBFS, fIN = 70 MHz, Clock Input = 200 MHz, fS = 200 Msps (ADC Core), PLL and decimation filters are disabled, Output load: CMOS data pin = 10 pF, LVDS = 100termination, LVDS driver current setting = 3.5 mA, +25°C is applied for typical value. Parameters Sym. Min. Typ. Max. Units AFS — 1.4875 — VP-P Conditions Analog Inputs Full-Scale Differential Analog Input Range(5,7) VSENSE = GND — 2.975 — VSENSE = AVDD12 — 3.71875 x VSENSE — 400 mV < VSENSE < 800 mV fIN_3dB — 500 — MHz AIN = -3 dBFS CIN 5 6 7 pF Note 5, Note 9 Analog Input Channel Cross-Talk XTALK — 100 — dBc Note 10 Analog Input Leakage Current (AIN+, AIN- pins) ILI_AH — — +1 µA VIH = AVDD12 ILI_AL -1 — — µA VIL = GND fS 40 — 200 Msps Tested at 200 Msps fCLK — — 250 MHz Note 5 VCLK_IN 300 — 800 CLKJITTER — 175 — fSRMS 49 50 51 % Duty cycle correction disabled 30 50 70 % Duty cycle correction enabled ILI_CLKH — — +110 µA VIH = AVDD12 ILI_CLKL -20 — — µA VIL = GND — — 12 bits Analog Input Bandwidth Differential Input Capacitance ADC Conversion Rate(11) Conversion Rate Clock Inputs (CLK+, CLK-)(12) Clock Input Frequency Differential Input Voltage Clock Jitter Clock Input Duty Cycle(5) Input Leakage Current at CLK input pin Converter mVP-P Note 5 Note 5 Accuracy(6) ADC Resolution (with no missing code) Offset Error — ±0.31 ±3.8 LSb Gain Error Integral Nonlinearity GER INL — ±0.5 — % of FS — ±0.125 — LSb Differential Nonlinearity DNL — ±0.03 — LSb CMRRDC — 70 — dB Analog Input Common-Mode Rejection Ratio 2014-2015 Microchip Technology Inc. DC measurement DS20005355B-page 17 MCP37211-200 AND MCP37D11-200 TABLE 2-1: ELECTRICAL CHARACTERISTICS (CONTINUED) Electrical Specifications: Unless otherwise specified, all parameters apply for TA = -40°C to +85°C, AVDD18 = DVDD18 = 1.8V, AVDD12 = DVDD12 = 1.2V, GND = 0V, SENSE = AVDD12, Single-channel mode, Differential Analog Input (AIN) = Sine wave with amplitude of -1 dBFS, fIN = 70 MHz, Clock Input = 200 MHz, fS = 200 Msps (ADC Core), PLL and decimation filters are disabled, Output load: CMOS data pin = 10 pF, LVDS = 100termination, LVDS driver current setting = 3.5 mA, +25°C is applied for typical value. Parameters Sym. Min. Typ. Max. Units Spurious Free Dynamic Range SFDR 78 90 — dBc fIN = 15 MHz dBc fIN = 70 MHz Signal-to-Noise Ratio SNR Dynamic Accuracy Conditions (6,15) 77 85 — 70.63 71.33 — dBFS fIN = 15 MHz dBFS fIN = 70 MHz bits fIN = 15 MHz SNR — 71.09 — ENOB 11.44 11.56 — ENOB — 11.52 — bits fIN = 70 MHz Total Harmonic Distortion (for all resolutions, first 13 harmonics) THD 78 89 — dBc fIN = 15 MHz 77 82 — dBc fIN = 70 MHz Worst Second or Third Harmonic Distortion HD2 or HD3 — 90 — dBc fIN = 15 MHz — 83 — dBc fIN = 70 MHz Two-Tone Intermodulation Distortion fIN1 = 17.6 MHz, fIN2 = 20.6 MHz IMD — 90.5 — dBc Effective Number of Bits (ENOB)(13) AIN = -7 dBFS, with two input frequencies Digital Logic Input and Output (Except LVDS Output) Schmitt Trigger High-Level Input Voltage VIH 0.7 DVDD18 — DVDD18 V Schmitt Trigger Low-Level Input Voltage VIL GND — 0.3 DVDD18 V VHYST — 0.05 DVDD18 — V Hysteresis of Schmitt Trigger Inputs (All digital inputs) Low-Level Output Voltage VOL — — 0.3 V IOL = -3 mA, all digital I/O pins High-Level Output Voltage VOH DVDD18 – 0.5 1.8 — V IOL = +3 mA, all digital I/O pins Digital Data Output (CMOS Mode) Maximum External Load Capacitance CLOAD — 10 — pF From output pin to GND Internal I/O Capacitance CINT — 4 — pF Note 5 DS20005355B-page 18 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 TABLE 2-1: ELECTRICAL CHARACTERISTICS (CONTINUED) Electrical Specifications: Unless otherwise specified, all parameters apply for TA = -40°C to +85°C, AVDD18 = DVDD18 = 1.8V, AVDD12 = DVDD12 = 1.2V, GND = 0V, SENSE = AVDD12, Single-channel mode, Differential Analog Input (AIN) = Sine wave with amplitude of -1 dBFS, fIN = 70 MHz, Clock Input = 200 MHz, fS = 200 Msps (ADC Core), PLL and decimation filters are disabled, Output load: CMOS data pin = 10 pF, LVDS = 100termination, LVDS driver current setting = 3.5 mA, +25°C is applied for typical value. Parameters Sym. Digital Data Output (LVDS Mode) Min. Typ. Max. Units Conditions (5) LVDS High-Level Differential Output Voltage VH_LVDS 200 300 400 mV 100 differential termination, LVDS bias = 3.5 mA LVDS Low-Level Differential Output Voltage VL_LVDS -400 -300 -200 mV 100 differential termination, LVDS bias = 3.5 mA LVDS Common-Mode Voltage VCM_LVDS 1 1.15 1.4 V Output Capacitance CINT_LVDS — 4 — pF Internal capacitance from output pin to GND Differential Load Resistance (LVDS) RLVDS — 100 — Across LVDS output pairs ILI_DH — — +1 µA VIH = DVDD18 ILI_DL -1 — — µA VIL = GND ILI_DH — — +6 µA VIH = DVDD18 ILI_DL -35 — — µA VIL = GND(14) Input Leakage Current on Digital I/O Pins Data Output Pins I/O Pins except Data Output Pins Notes: 1. 2. 3. 4. 5. 6. 7. 8. 9. 10. 11. 12. 13. 14. 15. This 1.8V digital supply voltage is used for the digital I/O circuit, including SPI, CMOS and LVDS data output drivers. Standby Mode: Most of the internal circuits are turned off, except the internal reference, clock, bias circuits and SPI interface. Shutdown Mode: All circuits including reference and clock are turned off except the SPI interface. The total power dissipation (typical) is calculated by using the following equation: PDISS = 1.8V x (IDD_A18 + IDD_D18) + 1.2V x (IDD_A12 + IDD_D12), where IDD_D18 is the digital I/O current for LVDS or CMOS output. This parameter is ensured by design, but not 100% tested in production. This parameter is ensured by characterization, but not 100% tested in production. See Table 4-2 for details. Differential reference voltage output at REF1+/- and REF0+/- pins. VREF1 = VREF1+ – VREF1-. VREF0 = VREF0+ – VREF0-. These references should not be driven. Input capacitance refers to the effective capacitance between one differential input pin pair. Channel cross-talk is measured when AIN = -1 dBFS at 12 MHz is applied on one channel while other channel(s) are terminated with 50. See Figure 3-45 for details. The ADC core conversion rate. In multi-channel mode, the conversion rate of an individual channel is fS/N, where N is the number of input channels used. See Figure 4-8 for the details of the clock input circuit. ENOB = (SINAD - 1.76)/6.02. This leakage current is due to the internal pull-up resistor. Dynamic performance is characterized with CH(n)_DIG_GAIN<7:0> = 0011-1000. 2014-2015 Microchip Technology Inc. DS20005355B-page 19 MCP37211-200 AND MCP37D11-200 TABLE 2-2: TIMING REQUIREMENTS - LVDS AND CMOS OUTPUTS Electrical Specifications: Unless otherwise specified, all parameters apply for TA = -40°C to +85°C, AVDD18 = DVDD18 = 1.8V, AVDD12 = DVDD12 = 1.2V, GND = 0V, SENSE = AVDD12, Single-channel mode, Differential Analog Input (AIN) = Sine wave with amplitude of -1 dBFS, fIN = 70 MHz, Clock Input = 200 MHz, fS = 200 Msps (ADC Core), PLL and decimation filters are disabled, Output load: CMOS data pin = 10 pF, LVDS = 100termination, LVDS driver current setting = 3.5 mA, +25°C is applied for typical value. Parameters Aperture Delay Out-of-Range Recovery Time Symbol Min. Typ. Max. Units tA — 1 — ns tOVR Conditions Note 1 — 1 — — 50 — TLATENCY — 28 — Clocks Note 2, Note 4 Power-Up Calibration Time TPCAL — 227 — Clocks First 227 sample clocks after power-up Background Calibration Update Rate TBCAL — 230 — Clocks Per 230 sample clocks after TPCAL TRESET 5 — — ns Input Clock to Output Clock Propagation Delay tCPD — — 3.2 ns Output Clock to Data Propagation Delay tDC -0.25 — +0.25 ns Input Clock to Output Data Propagation Delay tPD — — 3.25 ns Rise Time (20% to 80% of output amplitude)(2,3) tRISE_DATA — 0.25 0.5 ns tRISE_CLK — 0.25 0.5 ns Fall Time (80% to 20% of output amplitude)(2,3) tFALL_DATA — 0.25 0.5 ns tFALL_CLK — 0.25 0.5 ns Output Clock Duty Cycle Pipeline Latency System Calibration Clocks Note 1 % Note 1 (1 ) RESET Low Time See Figure 2-6 for details(1) LVDS Data Output Mode Note 1 CMOS Data Output Mode Input Clock to Output Clock Propagation Delay tCPD 6 ns DCLK=100 MHz, fs = 200 Msps Output Clock to Data Propagation Delay tDC 0.25 ns DCLK=100 MHz, fs = 200 Msps Input Clock to Output Data Propagation Delay tPD 6.25 ns DCLK=100 MHz, fs = 200 Msps tRISE_DATA TBD ns DCLK=100 MHz, fs = 200 Msps tRISE_CLK TBD ns DCLK=100 MHz, fs = 200 Msps tFALL_DATA TBD ns DCLK=100 MHz, fs = 200 Msps tFALL_CLK TBD ns DCLK=100 MHz, fs = 200 Msps Rise Time (20% to 80% of output amplitude) Fall Time (80% to 20% of output amplitude) Note 1: 2: 3: 4: This parameter is ensured by design, but not 100% tested in production. This parameter is ensured by characterization, but not 100% tested in production. tRISE = approximately less than 10% of duty cycle. Output latency is measured without using fractional delay recovery (FDR), decimation filter or digital down-converter options. DS20005355B-page 20 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 S-1 Input Signal: S+1 S *S = Sample Point S+L-1 S+L tA Latency = L Cycles Input Clock: CLKCLK+ tCPD Digital Clock Output: DCLK tDC tPD Output Data: Q<N:0> S-L-1 S-L S-L+1 S-1 S S-L-1 S-L S-L+1 S-1 S Over-Range Output: OVR FIGURE 2-1: Timing Diagram - CMOS Output. S-1 Input Signal: S+1 S+L-1 S *S = Sample Point S+L tA Latency = L Cycles Input Clock: CLKCLK+ tCPD Digital Clock Output: DCLKDCLK+ tDC tPD Output Data: Q-[N:0] Q+[N:0] EVEN S-L-1 ODD S-L-1 EVEN S-L ODD S-L EVEN S-L+1 EVEN S-1 ODD S-1 EVEN S WCK S-L-1 OVR S-L-1 WCK S-L OVR S-L WCK S-L+1 WCK S-1 OVR S-1 WCK S Word-CLK/ Over-Range Output: WCK/OVRWCK/OVR+ FIGURE 2-2: Timing Diagram - LVDS Output with Even Bit First. 2014-2015 Microchip Technology Inc. DS20005355B-page 21 MCP37211-200 AND MCP37D11-200 TABLE 2-3: SPI SERIAL INTERFACE TIMING SPECIFICATIONS Electrical Specifications: Unless otherwise specified, all parameters apply for TA = -40°C to +85°C, AVDD18 = DVDD18 = 1.8V, AVDD12 = DVDD12 = 1.2V, GND = 0V, SENSE = AVDD12, Single-channel mode, Differential Analog Input (AIN) = Sine wave with amplitude of -1 dBFS, fIN = 70 MHz, Clock Input = 200 MHz, fS = 200 Msps (ADC Core), PLL and decimation filters are disabled, Output load: CMOS data pin = 10 pF, LVDS = 100termination, LVDS driver current setting = 3.5 mA, +25°C is applied for typical value. All timings are measured at 50%. Parameters Symbol Min. Typ. Max. Units Conditions Serial Clock frequency, fSCK = 50 MHz CS Setup Time tCSS 10 — — ns CS Hold Time tCSH 20 — — ns CS Disable Time tCSD 20 — — ns Data Setup Time tSU 2 — — ns Data Hold Time tHD 4 — — ns Serial Clock High Time tHI 8 — — ns Serial Clock Low Time tLO 8 — — ns Serial Clock Delay Time tCLD 20 — — ns Serial Clock Enable Time tCLE 20 — — ns Output Valid from SCK Low tDO — — 20 ns Output Disable Time tDIS — — 10 ns Note 1: Note 1 Note 1 This parameter is ensured by design, but not 100% tested. tCSD CS tSCK tHI tLO tCSS tCLE tCSH tCLD SCLK tSU SDIO (SDI) FIGURE 2-3: tHD MSb in LSb in SPI Serial Input Timing Diagram. CS tSCK tHI tLO tCSH SCLK tDO SDIO (SDO) FIGURE 2-4: DS20005355B-page 22 MSb out tDIS LSb out SPI Serial Output Timing Diagram. 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 Power-on Reset (POR) AVDD12 227 cycles (TPCAL) Power-Up calibration complete. • Registers are initialized • Device is ready for correct conversion FIGURE 2-5: POR Related Events: Register Initialization and Power-Up Calibration. RESET Pin tRESET Power-Up Calibration Time (TPCAL) Stop ADC conversion Start register initialization and ADC recalibration Recalibration complete: • CAL Pin: High • ADC_CAL_STAT = 1 RESET Pin Timing Diagram. FIGURE 2-6: TABLE 2-4: TEMPERATURE CHARACTERISTICS Electrical Specifications: Unless otherwise specified, all parameters apply for TA = -40°C to +85°C, AVDD18 = DVDD18 = 1.8V, AVDD12 = DVDD12 = 1.2V, GND = 0V, SENSE = AVDD12, Single-channel mode, Differential Analog Input (AIN) = Sine wave with amplitude of -1 dBFS, fIN = 70 MHz, Clock Input = 200 MHz, fS = 200 Msps (ADC Core), PLL and decimation filters are disabled, Output load: CMOS data pin = 10 pF, LVDS = 100termination, LVDS driver current setting = 3.5 mA, +25°C is applied for typical value. Parameters Temperature Operating Temperature Range Thermal Package Min. Typ. Max. Units TA -40 — +85 °C JA — 40.2 — °C/W Conditions Resistances(2) 121L Ball-TFBGA Junction-to-Ambient Thermal Resistance (8 mm x 8 mm) Junction-to-Case Thermal Resistance 124L – VTLA (9 mm x 9 mm) Note 1: 2: Sym. Ranges(1) JC — 8.4 — °C/W Junction-to-Ambient Thermal Resistance JA — 21 — °C/W Junction-to-Case (top) Thermal Resistance JC — 8.7 — °C/W Maximum allowed power-dissipation (PDMAX) = (TJMAX - TA)/JA. This parameter value is achieved by package simulations. 2014-2015 Microchip Technology Inc. DS20005355B-page 23 MCP37211-200 AND MCP37D11-200 NOTES: DS20005355B-page 24 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 3.0 TYPICAL PERFORMANCE CURVES Note: The graphs and tables provided following this note are a statistical summary based on a limited number of samples and are provided for informational purposes only. The performance characteristics listed herein are not tested or guaranteed. In some graphs or tables, the data presented may be outside the specified operating range (e.g., outside specified power supply range) and therefore outside the warranted range. Note: Unless otherwise specified, all parameters apply for TA = -40°C to +85°C, AVDD18 = DVDD18 = 1.8V, AVDD12 = DVDD12 = 1.2V, GND = 0V, SENSE = AVDD12, Single-channel mode, Differential Analog Input (AIN) = Sine wave with amplitude of -1 dBFS, fIN = 70 MHz, Clock Input = 200 MHz, fS = 200 Msps (ADC Core), PLL and decimation filters are disabled. When NSR option is used, 12-bit mode is applied and the noise is calculated within the NSR bandwidth (25% of sampling frequency). 0RGH 6LQJOH I&/. 0+] I6 0VSV&K I,1 0+]#G%)6 615 G%G%)6 6)'5 G%F 7+' G%F +' G%F +' G%F $PSOLWXGHG%)6 )UHTXHQF\0+] FIGURE 3-1: FFT for 14.7 MHz Input Signal: fS = 200 Msps/Ch., AIN = -1 dBFS. $PSOLWXGHG%)6 )UHTXHQF\0+] $PSOLWXGHG%)6 )UHTXHQF\0+] FIGURE 3-5: FFT for 69.6 MHz Input Signal: fS = 200 Msps/Ch., AIN = -4 dBFS. I&/. 0+] I6 0VSV&K +' G%F I,1 0+]#G%)6 615 G%G%)6 6)'5 G%F 7+' G%F +' G%F +' G%F )UHTXHQF\0+] FIGURE 3-3: FFT for 151 MHz Input Signal: fS = 200 Msps/Ch., AIN = -1 dBFS. 2014-2015 Microchip Technology Inc. 0RGH 6LQJOH I,1 0+]#G%)6 615 G%G%)6 6)'5 G%F 7+' G%F +' G%F 0RGH 6LQJOH I&/. 0+] I6 0VSV&K )UHTXHQF\0+] 0RGH 6LQJOH I&/. 0+] I6 0VSV&K I,1 0+]#G%)6 615 G%G%)6 6)'5 G%F 7+' G%F +' G%F +' G%F FIGURE 3-2: FFT for 69.6 MHz Input Signal: fS = 200 Msps/Ch., AIN = -1 dBFS. FIGURE 3-4: FFT for 14.7 MHz Input Signal: fS = 200 Msps/Ch., AIN = -4 dBFS. $PSOLWXGHG%)6 $PSOLWXGHG%)6 0RGH 6LQJOH I&/. 0+] I6 0VSV&K I,1 0+]#G%)6 615 G%G%)6 6)'5 G%F 7+' G%F +' G%F +' G%F 0RGH 6LQJOH I&/. 0+] I6 0VSV&K I,1 0+]#G%)6 615 G%G%)6 6)'5 G%F 7+' G%F +' G%F +' G%F $PSOLWXGHG%)6 )UHTXHQF\0+] FIGURE 3-6: FFT for 151 MHz Input Signal: fS = 200 Msps/Ch., AIN = -4 dBFS. DS20005355B-page 25 MCP37211-200 AND MCP37D11-200 0RGH 'XDO I&/. 0+] I6 0VSV&K I,1 0+]#G%)6 615 G%G%)6 6)'5 G%F 7+' G%F +' G%F +' G%F $PSOLWXGHG%)6 $PSOLWXGHG%)6 $PSOLWXGHG%)6 $PSOLWXGHG%)6 $PSOLWXGHG%)6 )UHTXHQF\0+] FIGURE 3-9: FFT for 14.7 MHz Input Signal: fS = 25 Msps/Ch., Octal, AIN = -1 dBFS. DS20005355B-page 26 )UHTXHQF\0+] )UHTXHQF\0+] 0RGH 2FWDO I&/. 0+] I6 0VSV&K I,1 0+]#G%)6 615 G%G%)6 6)'5 G%F 7+' G%F +' G%F +' G%F FIGURE 3-11: FFT for 14.7 MHz Input Signal: fS = 50 Msps/Ch., Quad, AIN = -4 dBFS. FIGURE 3-8: FFT for 14.7 MHz Input Signal: fS = 50 Msps/Ch., Quad, AIN = -1 dBFS. 0RGH 4XDG I&/. 0+] I6 0VSV&K I,1 0+]#G%)6 615 G%G%)6 6)'5 G%F 7+' G%F +' G%F +' G%F )UHTXHQF\0+] 0RGH 4XDG I&/. 0+] I6 0VSV&K I,1 0+]#G%)6 615 G%G%)6 6)'5 G%F 7+' G%F +' G%F +' G%F FIGURE 3-10: FFT for 14.7 MHz Input Signal: fS = 100 Msps/Ch., Dual, AIN = -4 dBFS. FIGURE 3-7: FFT for 14.7 MHz Input Signal: fS = 100 Msps/Ch., Dual, AIN = -1 dBFS. )UHTXHQF\0+] 0RGH 'XDO I&/. 0+] I6 0VSV&K I,1 0+]#G%)6 615 G%G%)6 6)'5 G%F 7+' G%F +' G%F +' G%F $PSOLWXGHG%)6 0RGH 2FWDO I&/. 0+] I6 0VSV&K I,1 0+]#G%)6 615 G%G%)6 6)'5 G%F 7+' G%F +' G%F +' G%F )UHTXHQF\0+] FIGURE 3-12: FFT for 14.7 MHz Input Signal: fS = 25 Msps/Ch., Octal, AIN = -4 dBFS. 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 0 0 Amplitude (dBFS) ‐20 ‐40 ‐60 ‐80 3 5 ‐120 0 2 7 6 4 6 8 Frequency (MHz) 10 ‐40 ‐60 ‐80 3 2 4 ‐100 12 FIGURE 3-13: FFT for 69.6 MHz Input Signal: fS = 25 Msps/Ch., Octal, AIN = -1 dBFS. ‐100 5 ‐120 0 2 4 6 8 Frequency (MHz) )UHTXHQF\0+] 0RGH 6LQJOH I&/. 0+] I6 0VSV&K I,1 0+]#G%)6 615 G%G%)6 6)'5 G%F 7+' G%F +' G%F +' G%F )UHTXHQF\0+] FIGURE 3-17: FFT for 69.6 MHz Input Signal with NSR enabled: NSR = 20, fS = 200 Msps/Ch., AIN = -4 dBFS. $PSOLWXGHG%)6 $PSOLWXGHG%)6 0RGH 6LQJOH I&/. 0+] I6 0VSV&K I,1 0+]#G%)6 615 G%G%)6 6)'5 G%F 7+' G%F +' G%F +' G%F 12 FIGURE 3-14: FFT for 69.6 MHz Input Signal with NSR enabled: NSR = 20, fS = 200 Msps/Ch., AIN = -1 dBFS. 10 0RGH 6LQJOH I&/. 0+] I6 0VSV&K I,1 0+]#G%)6 615 G%G%)6 6)'5 G%F 7+' G%F +' G%F 7 6 0RGH 6LQJOH I&/. 0+] I6 0VSV&K I,1 0+]#G%)6 615 G%G%)6 6)'5 G%F 7+' G%F +' G%F $PSOLWXGHG%)6 $PSOLWXGHG%)6 2 4 FIGURE 3-16: FFT for 69.6 MHz Input Signal: fS = 25 Msps/Ch., Octal, AIN = -4 dBFS. Mode = Octal fCLK= 200 MHz fS = 25 Msps/Ch. fIN = 69.6 MHz @ ‐4.0 dBFS SNR = 67.2 dB (71.2 dBFS) SFDR = 90.0 dBc THD = ‐88.2 dBc HD2 = ‐97.7 dBc HD3 = ‐90.0 dBc ‐20 Amplitude (dBFS) Mode = Octal fCLK= 200 MHz fS = 25 Msps/Ch. fIN = 69.6 MHz @ ‐1.0 dBFS SNR = 70.1 dB (71.1 dBFS) SFDR = 78.6 dBc THD = ‐78.1 dBc HD2 = ‐98.3 dBc HD3 = ‐78.6 dBc )UHTXHQF\0+] FIGURE 3-15: FFT for 20.3 MHz Input Signal with NSR enabled: NSR = 27, fS = 200 Msps/Ch., AIN = -1 dBFS. 2014-2015 Microchip Technology Inc. )UHTXHQF\0+] FIGURE 3-18: FFT for 20.3 MHz Input Signal with NSR enabled: NSR = 27, fS = 200 Msps/Ch., AIN = -4 dBFS. DS20005355B-page 27 MCP37211-200 AND MCP37D11-200 0RGH 6LQJOH I&/. 0+] I6 0VSV&K I,1 0+]#G%)6 615 G%G%)6 6)'5 G%F 7+' G%F +' G%F $PSOLWXGHG%)6 $PSOLWXGHG%)6 )UHTXHQF\0+] )UHTXHQF\0+] FIGURE 3-20: FFT for 15.8 MHz Input Signal with NSR enabled: NSR = 63, fS = 200 Msps/Ch., AIN = -1 dBFS. I 0RGH 6LQJOH I&/. 0+] I6 0VSV&K I,1 0+]#G%)6 615 G%G%)6 6)'5 G%F 7+' G%F +' G%F +' G%F )UHTXHQF\0+] FIGURE 3-22: FFT for 69.6 MHz Input Signal with NSR enabled: NSR = 52, fS = 200 Msps/Ch., AIN = -4 dBFS. $PSOLWXGHG%)6 0RGH 6LQJOH I&/. 0+] I6 0VSV&K I,1 0+]#G%)6 615 G%G%)6 6)'5 G%F 7+' G%F +' G%F +' G%F FIGURE 3-19: FFT for 69.6 MHz Input Signal with NSR enabled: NSR = 52, fS = 200 Msps/Ch., AIN = -1 dBFS. $PSOLWXGHG%)6 )UHTXHQF\0+] FIGURE 3-23: FFT for 15.8 MHz Input Signal with NSR enabled: NSR = 63, fS = 200 Msps/Ch., AIN = -4 dBFS. 0RGH 6LQJOH I&/. 0+] I 0+]#G%)6 I 0+] #G%)6 I±I G%F I±I G%F 6)'5 G%F I I I I I I I I±I I±I I ±I $PSOLWXGHG%)6 0RGH 6LQJOH I&/. 0+] I6 0VSV&K I,1 0+]#G%)6 615 G%G%)6 6)'5 G%F 7+' G%F +' G%F )UHTXHQF\0+] FIGURE 3-21: Two-Tone FFT: fIN1 = 17.6 MHz and fIN2 = 20.6 MHz, AIN = -7 dBFS per Tone, fS = 200 Msps. DS20005355B-page 28 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 615G% ,QSXW$PSOLWXGHG%)6 6)'5G%F 615G% ,QSXW$PSOLWXGHG%)6 615G%)6 6)'5G%F 615G% 615G% 6)'5G%F ,QSXW$PSOLWXGHG%)6 FIGURE 3-28: SNR/SFDR vs. Analog Input Amplitude: fS = 200 Msps, fIN = 70 MHz, Low-Reference Mode (SENSE = GND). 615G%6)'5G%FG%)6 615G%)6 6)'5G%)6 615G%)6 6)'5G%)6 FIGURE 3-25: SNR/SFDR vs. Analog Input Amplitude: fS = 200 Msps, fIN = 15 MHz, Low-Reference Mode (SENSE = GND). ,QSXW$PSOLWXGHG%)6 FIGURE 3-27: SNR/SFDR vs. Analog Input Amplitude: fS = 200 Msps, fIN = 70 MHz, High-Reference Mode (SENSE = AVDD12). 615G%)6 615G%6)'5G%FG%)6 615G%)6 615G%)6 6)'5G%)6 6)'5G%)6 6)'5G%F 615G% FIGURE 3-24: SNR/SFDR vs. Analog Input Amplitude: fS = 200 Msps, fIN = 15 MHz, High-Reference Mode (SENSE = AVDD12). 615G%)6 615G%)6 6)'5G%F 615G% 615G%6)'5G%FG%)6 615G%6)'5G%FG%)6 6)'5G%F 615G%6)'5G%FG%)6 615G%)6 615G%)6 615G%)6 6)'5G%)6 615G%)6 615G%6)'5G%FG%)6 6)'5G%)6 ,QSXW$PSOLWXGHG%)6 FIGURE 3-26: SNR/SFDR vs. Analog Input Amplitude: fS = 200 Msps, fIN = 15 MHz, High-Reference Mode (SENSE = AVDD12) with NSR enabled. AIN 0.8 dBFS for NSR. 2014-2015 Microchip Technology Inc. ,QSXW$PSOLWXGHG%)6 FIGURE 3-29: SNR/SFDR vs. Analog Input Amplitude: fS = 200 Msps, fIN = 70 MHz, High-Reference Mode (SENSE = AVDD12) with NSR enabled. AIN 0.8 dBFS for NSR. DS20005355B-page 29 MCP37211-200 AND MCP37D11-200 I,1 0+] $,1 G%)6 I,1 0+] $,1 G%)6 6)'5G%)6 615G%)6 6)'5G%)6 615G%)6 615G%)6 615G%)6 %*+,*+ 6(16(3LQ9ROWDJH FIGURE 3-31: SNR/SFDR vs. SENSE Pin Voltage: fS = 200 Msps, fIN = 70 MHz. 6)'5G%)6 %*/2: I6 0VSV I,1 0+] $,1 G%)6 6)'5G%)6 6DPSOH5DWH0636 FIGURE 3-33: SNR/SFDR vs. Sample Rate (Msps): fIN = 15 MHz. I6 0VSV I,1 0+] $,1 G%)6 %*/2: 6)'5G%)6 6DPSOH5DWH0636 FIGURE 3-30: SNR/SFDR vs. Sample Rate (Msps): fIN = 70 MHz. 615G%)6 6)'5G%)6 615G%)6 6)'5G%)6 615G%)6 615G%)6 6)'5G%)6 6(16(3LQ9ROWDJH %*+,*+ FIGURE 3-34: SNR/SFDR vs. SENSE Pin Voltage: fS = 200 Msps, fIN = 15 MHz. 615#$,1 G%)6 615G%)6 615#$,1 G%)6 6)'5#$,1 G%)6 6)'5#$,1 G%)6 ,QSXW)UHTXHQF\0+] FIGURE 3-32: Frequency. DS20005355B-page 30 6)'5G%)6 SNR/SFDR vs. Input 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 6XSSO\9ROWDJH9 6XSSO\9ROWDJH9 615G%)6 FIGURE 3-38: HD2/HD3 vs. Supply Voltage: fS = 200 Msps, fIN = 15 MHz. $9'' 9 95()9 6)'5G%)6 615G%)6 +'G%)6 96(16( $9'' I6 0VSV I,1 0+] $,1 G%)6 +'G%)6 FIGURE 3-35: SNR/SFDR vs. Supply Voltage: fS = 200 Msps, fIN = 15 MHz. I6 0VSV I,1 0+] $,1 G%)6 +'1G%)6 6)'5G%)6 6)'5G%)6 I6 0VSV I,1 0+] $,1 G%)6 615G%)6 615G%)6 $9'' 9 $9'' 9 6)'5G%)6 7HPSHUDWXUH& FIGURE 3-36: SNR/SFDR vs. Temperature: fS = 200 Msps, fIN = 15 MHz. 615G%)6 VREF0 vs. Temperature. ([WHUQDO9&09 FIGURE 3-37: SNR/SFDR vs. VCM Voltage (Externally Applied): fS = 200 Msps, fIN = 15 MHz. 2014-2015 Microchip Technology Inc. 2IIVHW(UURU 6)'5G%)6 6)'5G%)6 615G%)6 7HPSHUDWXUH& FIGURE 3-39: *DLQ(UURU 2IIVHW(UURU/6% *DLQ(UURUG% 7HPSHUDWXUH& FIGURE 3-40: Gain and Offset Error Drifts vs. Temperature Using Internal Reference, with Respect to 25°C: fS = 200 Msps. DS20005355B-page 31 MCP37211-200 AND MCP37D11-200 I&/. 0+] ,1/ /6% $PSOLWXGHG% ,1/(UURU/6% I,1 0+] $,1 )6 2XWSXW&RGH FIGURE 3-41: INL Error vs. Output Code: fS = 200 Msps, fIN = 4 MHz. I&/. 0+] '1/ /6% FIGURE 3-44: )UHTXHQF\0+] Input Bandwidth. I,1 0+] $,1 )6 &URVVWDONG% '1/(UURU/6% I6 0VSV $,1 G%)6 &+WR&+ &+WR&+ 2XWSXW&RGH FIGURE 3-42: DNL Error vs. Output Code: fS = 200 Msps, fIN = 4 MHz. ,QSXW)UHTXHQF\0+] FIGURE 3-45: Input Channel Crosstalk. 1.5M $,1 G%)6 fS = 200 Msps 500k 7 UH &R & ' 2 U$ 6, IR HU /9' Z W 3R HS DO H[F RW ,''B' 3RZHUP: 1.0M &XUUHQWP$ Occurrences ,''B$ ,''B' ,''B$ 0 -20 -15 -10 FIGURE 3-43: DS20005355B-page 32 -5 0 5 Output Code 10 15 20 Shorted Input Histogram. 6DPSOLQJ)UHTXHQF\0+] FIGURE 3-46: Power Consumption vs. Sampling Frequency (LVDS Mode). 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 4.0 THEORY OF OPERATION 4.1 ADC Core Architecture Figure 4-1 shows the simplified block diagram of the ADC core. The first stage consists of a 17-level flash ADC, multi-level Digital-to-Analog Converter (DAC) and a residue amplifier with a gain of 8. Stages 2 to 6 consist of a 9-level (3-bit) flash ADC, multi-level DAC and a residue amplifier with a gain of 4. The last stage is a 9-level 3-bit flash ADC. Dither is added in each of the first three stages.The digital outputs from all seven stages are combined in a digital error correction logic block and digitally processed for the final output. The MCP37211-200 and MCP37D11-200 device family is a low-power, 12-bit, 200 Msps Analog-to-Digital Converter (ADC) with built-in features including Harmonic Distortion Correction (HDC), DAC Noise Cancellation (DNC), Dynamic Element Matching (DEM) and flash error calibration. The devices offer various built-in digital signal postprocessing features. Both the MCP37211-200 and MCP37D11-200 offer high-order FIR digital decimation filters, noise-shaping requantizer (NSR), gain and offset adjustment per channel and fractional delay recovery (FDR). The MCP37D11-200 includes additional features such as digital down-conversion (DDC) and CW beamforming capability. These built-in advanced digital signal post-processing sub-blocks, which are individually controlled using configuration register bit settings, can be used for various special applications such as I/Q demodulation, digital downconversion and ultrasound imaging. The first three stages include patented digital calibration features: • Harmonic Distortion Correction (HDC) algorithm that digitally measures and cancels ADC errors arising from distortions introduced by the residue amplifiers • DAC Noise Cancellation (DNC) algorithm that corrects DAC’s nonlinearity errors • Dynamic Element Matching (DEM) which randomizes DAC errors, thereby converting harmonic distortion to white noise When the device is first powered-up, it performs internal calibrations by itself and runs with default settings. From this point, the user can configure the device registers using the SPI command. These digital correction algorithms are first applied during the Power-on Reset sequence and then operate in the background during normal operation of the pipelined ADC. These algorithms automatically track and correct any environmental changes in the ADC. More details of the system correction algorithms are shown in Section 4.13 “System Calibration”. In multi-channel mode, the input channel selection and MUX scan order are user-configurable, and the inputs are sequentially multiplexed by the input MUX defined by the scan order. The device samples the analog input on the rising edge of the clock. The digital output code is available after 28 clock cycles of data latency. Latency will increase if any of the various digital signal post-processing (DSPP) options are enabled. The output data can be coded in two’s complement or offset binary format, and randomized using the user option. Data can be output using either the CMOS or LVDS (Low-Voltage Differential Signaling) interface. Reference Generator REF0 REF0 REF1 REF1 Clock Generation REF1 REF1 REF1 REF1 REF1 AIN0+ AIN0Input MUX AIN7+ AIN7 - Pipeline Stage 1 (3-bit) Pipeline Stage 2 (2-bit) Pipeline Stage 3 (2-bit) HDC1, DNC1 HDC2, DNC2 HDC3, DNC3 Pipeline Stage 4 (2-bit) Pipeline Stage 5 (2-bit) Pipeline Stage 6 (2-bit) 3-bit Flash Stage 7 (3-bit) Digital Error Correction User-Programmable Options Programmable Digital Signal Post-Processing (DSPP) 12-Bit Digital Output FIGURE 4-1: ADC Core Block Diagram. 2014-2015 Microchip Technology Inc. DS20005355B-page 33 MCP37211-200 AND MCP37D11-200 4.2 Supply Voltage (DVDD, AVDD, GND) The device operates from two sets of supplies and a common ground: EQUATION 4-1: SAMPLE RATE PER CHANNEL Full ADC Sample Rate fs Sample Rate/Channel = --------------------------------------------------------------------Number of Channel Used • Digital Supplies (DVDD) for the digital section: 1.8V and 1.2V • Analog Supplies (AVDD) for the analog section: 1.8V and 1.2V • Ground (GND): Common ground for both digital and analog sections. 4.4 The supply pins require an appropriate bypass capacitor (ceramic) to attenuate the high-frequency noise present in most application environments. The ground pins provide the current return path. These ground pins must connect to the ground plane of the PCB through a low-impedance connection. A ferrite bead can be used to separate analog and digital supply lines if a common power supply is used for both analog and digital sections. • SEL_NCH<2:0> in Address 0x01 (Register 5-2): Select the total number of input channels to be used. • Addresses 0x7D – 0x7F (Registers 5-38 – 5-40): Select auto-scan channel order. The voltage regulators for each supply need to have sufficient output current capabilities to support a stable ADC operation. 4.3 Input Sample Rate In single-channel mode, the device samples the input at full speed. In multi-channel mode, the core ADC is multiplexed between the selected channels. The resulting effective sample rate per channel is shown in Equation 4-1. For example, with 200 Msps operation, the input is sampled at the full 200 Msps rate if a single channel is used, or at 25 Msps per channel if all eight channels are used. TABLE 4-1: No. of Channels (1) Analog Input Channel Selection The analog input is auto-multiplexed sequentially as defined by the channel-order selection bit setting. The user can configure the input MUX using the following registers: The user can select up to eight input channels. If all eight input channels are to be used, SEL_NCH<2:0> is set to 000 and the input channel sampling order is set using Addresses 0x7D – 0x7F (Registers 5-38 – 5-40). Regardless of how many channels are selected, all eight channels must be programmed in Addresses 0x7D – 0x7F (Registers 5-38 – 5-40) without duplication. Program the addresses of the selected channels in sequential order, followed by the unused channels. The order of the unused channels has no effect. The device samples the first N-Channels listed in Addresses 0x7D – 0x7F (Registers 5-38 – 5-40) sequentially, where N is the total number of channels to be used, defined by the SEL_NCH<2:0>. Table 4-1 shows examples of input channel selection using Addresses 0x7D – 0x7F (Registers 5-38 – 5-40). EXAMPLE: CHANNEL ORDER SELECTION USING ADDRESSES 0X7D – 0X7F Selected Channels Channel Order(2) Address 0x7F b 7 Address 0x7E b 0 b 7 Address 0x7D b 0 b 7 b 0 Channel Order Bit Settings 5th Ch. 8 4th Ch. 6th Ch. 3rd Ch. 7th Ch. 2nd Ch. 8th Ch. 1st Ch. [0 1 2 3 4 5 6 7] [0 1 2 3 4 5 6 7] (Default) 1 0 0 0 1 1 1 0 1 0 1 0 1 1 0 0 0 1 1 1 1 0 0 0 [7 6 5 4 3 2 1 0] [7 6 5 4 3 2 1 0] 0 1 1 1 0 0 0 1 0 1 0 1 0 0 1 1 1 0 0 0 0 1 1 1 [0 2 4 6 1 3 5 7] [0 2 4 6 1 3 5 7] 0 0 1 1 1 0 0 1 1 1 0 0 1 0 1 0 1 0 1 1 1 0 0 0 [1 3 5 7 0 2 4 6] [1 3 5 7 0 2 4 6] 0 0 0 1 1 1 0 1 0 1 0 1 1 0 0 0 1 1 1 1 0 0 0 1 Channel Order Bit Settings 7 Note 1: 2: Unused 4th Ch. 5th Ch. 3rd Ch. 6th Ch. 2nd Ch. 7th Ch. 1st Ch. [0 1 2 3 4 5 6] [0 1 2 3 4 5 6 7] 1 1 1 0 1 1 1 0 0 0 1 0 1 0 1 0 0 1 1 1 0 0 0 0 [0 2 4 6 1 3 5] [0 2 4 6 1 3 5 7] 1 1 1 1 1 0 0 0 1 1 0 0 0 1 1 0 1 0 1 0 1 0 0 0 Defined by SEL_NCH<2:0> in Address 0x01 (Register 5-2). Individual channel order should not be repeated. Unused channels are still assigned after the selected channel address. The order of the unused channel addresses has no meaning since they are not used. DS20005355B-page 34 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 TABLE 4-1: No. of Channels (1) EXAMPLE: CHANNEL ORDER SELECTION USING ADDRESSES 0X7D – 0X7F Selected Channels Channel Order(2) Address 0x7F b 7 Address 0x7E b 0 b 7 Address 0x7D b 0 b 7 b 0 Channel Order Bit Settings 6 Unused Unused 4th Ch. 3rd Ch. 5th Ch. 2nd Ch. 6th Ch. 1st Ch. [0 1 2 3 4 5] [0 1 2 3 4 5 6 7] 1 1 1 1 1 0 0 1 1 0 1 0 1 0 0 0 0 1 1 0 1 0 0 0 [0 2 4 6 1 3] [0 2 4 6 1 3 5 7] 1 1 1 1 0 1 1 1 0 1 0 0 0 0 1 0 1 0 0 1 1 0 0 0 Channel Order Bit Settings 5 Unused Unused Unused 3rd Ch. 4th Ch. 2nd Ch. 5th Ch. 1st Ch. [0 1 2 3 4] [0 1 2 3 4 5 6 7] 1 1 0 1 0 1 1 1 1 0 1 0 0 1 1 0 0 1 1 0 0 0 0 0 [0 2 4 6 1] [0 2 4 6 1 3 5 7] 1 0 1 0 1 1 1 1 1 1 0 0 1 1 0 0 1 0 0 0 1 0 0 0 Channel Order Bit Settings Unused Unused Unused Unused 3rd Ch. 2nd Ch. 4 4th Ch. 1st Ch. [0 1 2 3 ] [0 1 2 3 4 5 6 7] 1 1 0 1 0 1 1 1 1 1 0 0 0 1 0 0 0 1 0 1 1 0 0 0 [4 5 6 7] [4 5 6 7 0 1 2 3] 0 1 0 0 0 1 0 1 1 0 0 0 1 1 0 1 0 1 1 1 1 1 0 0 [0 2 4 6] [0 2 4 6 1 3 5 7] 1 0 1 0 1 1 1 1 1 0 0 1 1 0 0 0 1 0 1 1 0 0 0 0 [1 3 5 7] [1 3 5 7 0 2 4 6] 1 0 0 0 1 0 1 1 0 0 0 0 1 0 1 0 1 1 1 1 1 0 0 1 Channel Order Bit Settings 3 Unused Unused Unused Unused Unused 2nd Ch. 3rd Ch. 1st Ch. [0 1 2] [0 1 2 3 4 5 6 7] 1 0 1 1 0 0 1 1 0 0 1 1 1 1 1 0 0 1 0 1 0 0 0 0 [0 2 4] [0 2 4 6 1 3 5 7] 0 1 1 0 0 1 1 0 1 1 1 0 1 1 1 0 1 0 1 0 0 0 0 0 Channel Order Bit Settings Unused Unused Unused Unused Unused Unused 2nd Ch. 2 1st Ch. [0 1] [0 1 2 3 4 5 6 7] 1 0 1 1 0 0 1 1 0 0 1 1 1 1 1 0 1 0 0 0 1 0 0 0 [2 3] [2 3 0 1 4 5 6 7] 1 0 1 1 0 0 1 1 0 0 0 1 1 1 1 0 0 0 0 1 1 0 1 0 [4 5] [4 5 0 1 2 3 6 7] 0 1 1 0 1 0 1 1 0 0 0 1 1 0 1 0 0 0 1 0 1 1 0 0 [6 7] [6 7 0 1 2 3 4 5] 0 1 1 0 1 0 1 0 0 0 0 1 1 0 1 0 0 0 1 1 1 1 1 0 Channel Order Bit Settings Unused Unused Unused Unused Unused Unused Unused 1st Ch. 1 Note 1: 2: [0] [0 1 2 3 4 5 6 7] 1 0 0 0 1 1 1 0 1 0 1 0 1 1 0 0 0 1 1 1 1 0 0 0 [1] [1 0 2 3 4 5 6 7] 1 0 0 0 1 1 1 0 1 0 1 0 1 1 0 0 0 0 1 1 1 0 0 1 [2] [2 0 1 3 4 5 6 7] 1 0 0 0 1 1 1 0 1 0 0 1 1 1 0 0 0 0 1 1 1 0 1 0 [3] [3 0 1 2 4 5 6 7] 1 0 0 0 1 0 1 0 1 0 0 1 1 1 0 0 0 0 1 1 1 0 1 1 [4] [4 0 1 2 3 5 6 7] 0 1 1 0 1 0 1 0 1 0 0 1 1 1 0 0 0 0 1 1 1 1 0 0 [5] [5 0 1 2 3 4 6 7] 0 1 1 0 1 0 1 0 0 0 0 1 1 1 0 0 0 0 1 1 1 1 0 1 [6] [6 0 1 2 3 4 5 7] 0 1 1 0 1 0 1 0 0 0 0 1 1 0 1 0 0 0 1 1 1 1 1 0 [7] [7 0 1 2 3 4 5 6] 0 1 1 0 1 0 1 0 0 0 0 1 1 0 1 0 0 0 1 1 0 1 1 1 Defined by SEL_NCH<2:0> in Address 0x01 (Register 5-2). Individual channel order should not be repeated. Unused channels are still assigned after the selected channel address. The order of the unused channel addresses has no meaning since they are not used. 2014-2015 Microchip Technology Inc. DS20005355B-page 35 MCP37211-200 AND MCP37D11-200 Analog Input Circuit The analog input (AIN) of all MCP37XXX devices is a differential, CMOS switched capacitor sample-and-hold circuit. Figure 4-2 shows the equivalent input structure of the device. The input impedance of the device is mostly governed by the input sampling capacitor (CS = 6 pF) and input sampling frequency (fS). The performance of the device can be affected by the input signal conditioning network (see Figure 4-3). The analog input signal source must have sufficiently low output impedance to charge the sampling capacitors (CS = 6 pF) within one clock cycle. A small external resistor (e.g., 5Ω) in series with each input is recommended, as it helps reduce transient currents and dampens ringing behavior. A small differential shunt capacitor at the chip side of the resistors may be used to provide dynamic charging currents and may improve performance. The resistors form a low-pass filter with the capacitor and their values must be determined by application requirements and input frequency. The VCM pin provides a common-mode voltage reference (0.9V), which can be used for a center-tap voltage of an RF transformer or balun. If the VCM pin voltage is not used, the user may create a commonmode voltage at mid-supply level (AVDD18/2). 4.5.1 4.5.1.1 ANALOG INPUT DRIVING CIRCUIT Differential Input Configuration The device achieves optimum performance when the input is driven differentially, where common-mode noise immunity and even-order harmonic rejection are significantly improved. If the input is single-ended, it must be converted to a differential signal in order to properly drive the ADC input. The differential conversion and common-mode application can be accomplished by using an RF transformer or balun with a center-tap. Additionally, one or more anti-aliasing filters may be added for optimal noise performance and should be tuned such that the corner frequency is appropriate for the system. Figure 4-3 shows an example of the differential input circuit with transformer. Note that the input-driving circuits are terminated by 50 near the ADC side through a pair of 25 resistors from each input to the common-mode (VCM) from the device. The RF transformer must be carefully selected to avoid artificially high harmonic distortion. The transformer can be damaged if a strong RF input is applied or an RF input is applied while the MCP37XXX is powered-off. The transformer has to be selected to handle sufficient RF input power. Figure 4-4 shows an input configuration example when a differential output amplifier is used. 1 MCP37XXX Hold Sample AIN+ 50 CS = 6 pF 3 pF MABAES0060 6 1 1 4 6 MABAES0060 3 3 VCM AVDD18 5 Analog Input 4 25 0.1 µF 25 5 Hold Sample 50 3 pF CS = 6 pF FIGURE 4-3: Configuration. AIN+ 50 3.3 pF 50 AIN- Transformer Coupled Input 50 VCM 0.1 µF FIGURE 4-2: Equivalent Input Circuit. High-Speed Differential Amplifier Analog Input MCP37XXX 0.1 µF AVDD18 AIN- VCM 100 + CM - AIN+ 6.8 pF 100 MCP37XXX 4.5 AIN- FIGURE 4-4: DC-Coupled Input Configuration with Preamplifier: the external signal conditioning circuit and associated component values are for reference only. Typically, the amplifier manufacturer provides reference circuits and component values. DS20005355B-page 36 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 Single-Ended Input Configuration 4.5.2 Figure 4-5 shows an example of a single-ended input configuration. This single-ended input configuration is not recommended for the best performance. SNR and SFDR performance degrades significantly when the device is operated in a single-ended configuration. The unused negative side of the input should be AC-coupled to ground using a capacitor. The device has a bandgap-based differential internal reference voltage. The SENSE pin voltage is used to select the reference voltage source and configure the input full-scale range. A comparator detects the SENSE pin voltage and configures the full-scale input range into one of the three possible modes which are summarized in Table 4-2. Figure 4-6 shows an example of how the SENSE pin should be driven. VCM 50 0.1 µF 1 k R AIN+ VCM C 1 k 10 µF FIGURE 4-5: Configuration. 0.1 µF The SENSE pin can sink or source currents as high as 500 µA across all operational conditions. Therefore, it may require a driver circuit, unless the SENSE reference source provides sufficient output current. 0.1 µF R MCP37XXX Analog Input 10 µF SENSE VOLTAGE AND INPUT FULL-SCALE RANGE MCP1700 0.1 µF AIN- R1 SENSE R2 Singled-Ended Input (Note 1) Note 1: This voltage buffer can be removed if the SENSE reference is coming from a stable source (such as MCP1700) which can provide a sufficient output current to the SENSE pin. FIGURE 4-6: TABLE 4-2: 0.1 µF MCP37XXX 4.5.1.2 SENSE Pin Voltage Setup. SENSE PIN VOLTAGE AND INPUT FULL-SCALE RANGE SENSE Pin Voltage (VSENSE) Selected Reference Voltage (VREF) Full-Scale Input Voltage Range (AFS) LSb Size (Calculated with AFS) Tied to GND 0.7V 1.4875 VP-P(1) 363.16 µV Low-Reference Mode(4) 0.4V – 0.8V 0.7V – 1.4V 1.4875 VP-P to 2.975 VP-P(2) Adjustable Sense Mode(5) 726.32 µV High-Reference Mode(4) Tied to AVDD12 Note 1: 2: 3: 4: 5: 1.4875V 2.975 VP-P(3) Condition AFS = (17/16) x 1.4 VP-P = 1.487 VP-P. AFS = (17/16) x 2.8 VP-P x (VSENSE)/0.8 = 1.4875 VP-P to 2.975 VP-P. AFS = (17/16) x 2.8 VP-P = 2.975 VP-P. Based on internal bandgap voltage. Based on VSENSE. 2014-2015 Microchip Technology Inc. DS20005355B-page 37 MCP37211-200 AND MCP37D11-200 4.5.2.1 SENSE Selection Vs. SNR/SFDR Performance The SENSE pin is used to configure the full-scale input range of the ADC. Depending on the application conditions, the SNR, SFDR and dynamic range performance are affected by the SENSE pin configuration. Table 4-3 summarizes these settings. • High-Reference Mode This mode is enabled by setting the SENSE pin to AVDD12 (1.2V). This mode provides the highest input full-scale range (2.975 VP-P) and the highest SNR performance. In this mode, the internal thermal noise is less than 1 LSb of the 12-bit ADC (726 µV). This has the consequence of making it difficult to resolve small input signals unless some dither is added to the ADC input. In typical applications, thermal noise generated by the system driving the ADC will provide the necessary dithering effect. Figure 3-24 and Figure 3-27 show SNR/SFDR versus input amplitude in High-Reference mode. Note: Adding dither to the ADC has a negative side effect of reducing the maximum achievable SNR. • Low-Reference Mode This mode is enabled by setting the SENSE pin to ground. This mode is suitable for applications which have a smaller input full-scale range. This mode provides improved SFDR characteristics, but SNR is reduced by -3 dB compared to the High-Reference Mode. • SENSE Mode This mode is enabled by driving the SENSE pin with an external voltage source between 0.4V and 0.8V. This mode allows the user to adjust the input full-scale range such that SNR and dynamic range are optimized in a given application system environment. • NSR Mode The use of the Noise-Shaping Requantizer (NSR), further described in Section 4.8.2 “Noise-Shaping Requantizer (NSR)”, is best suited for applications which require a high SNR and a wide dynamic range as well as a relatively narrow bandwidth. When the NSR is enabled, the noise level in a selected portion of the frequency band is reduced to a level below that of a conventional 12-bit ADC, while the noise level outside of this band remains significantly higher. The SNR achievable in this mode is about 78 dBFS when integrated across 50% of the Nyquist bandwidth. This is an optimum selection for applications where the full Nyquist bandwidth of the ADC is not needed, and where the digital signal post-processing of the ADC data is capable of removing the out-of-band noise added by the NSR. Figures 3-26 and 3-29 show the SNR/SFDR versus input amplitude with NSR enabled. TABLE 4-3: SENSE VS. SNR/SFDR PERFORMANCE SENSE Descriptions High-Reference Mode (SENSE pin = AVDD12) High-input full-scale range (2.975 VP-P) and optimized SNR Low-Reference Mode (SENSE pin = ground) Low-input full-scale range (1.4875 VP-P) and reduced SNR, but optimized SFDR Sense Mode (SENSE pin = 0.4V to 0.8V) Adjustable-input full-scale range (1.4875 VP-P - 2.975 VP-P). Dynamic trade-off between High-Reference and Low-Reference modes can be used. Noise-Shaping Requantizer (NSR) Optimized SNR, but reduced usable bandwidth. NSR can be employed in any SENSE pin configuration. DS20005355B-page 38 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 DECOUPLING CIRCUITS FOR INTERNAL VOLTAGE REFERENCE AND BANDGAP OUTPUT 4.5.3.1 Decoupling Circuits for REF1 and REF0 Pins 4.6 External Clock Input For optimum performance, the MCP37XXX requires a low-jitter differential clock input at the CLK+ and CLK− pins. Figure 4-8 shows the equivalent clock input circuit. The device has two internal voltage references, and these references are available at pins REF0 and REF1. REF0 is the internal voltage reference for the ADC input stage, while REF1 is for all remaining stages. VTLA-124 Package Device: Figure 4-7 shows the recommended circuit for the REF1 and REF0 pins for the VTLA-124 package. Placing a 2.2 µF ceramic capacitor with two additional optional capacitors (22 nF and 220 nF) between the positive and negative reference pins is recommended. The negative reference pin is then grounded through a 220 nF capacitor. The capacitors should be placed as close to the ADC as possible with short and thick traces. Vias on the PCB are not recommended for this reference pin circuit. MCP37XXX ~300 fF CLK+ 300 AVDD12 Decoupling Circuit for VBG Pin The bandgap circuit is a part of the reference circuit and the output is available at the VBG pin. VTLA-124 Package Device: VBG pin needs an external decoupling capacitor (2.2 µF) as shown in Figure 4-7. TFBGA-121 Package Device: The decoupling capacitor is embedded in the package. Therefore, no external circuit is required on the PCB. REF1+ REF1- REF0+ REF0- VBG 2.2 µF 2.2 µF 22 nF 22 nF 220 nF (optional) 2 pF Clock Buffer 300 ~300 fF FIGURE 4-8: Circuit. Equivalent Clock Input The clock input amplitude range is between 300 mVP-P and 800 mVP-P. When a single-ended clock source is used, an RF transformer or balun can be used to convert the clock into a differential signal for the best ADC performance. Figure 4-9 shows an example clock input circuit. The common-mode voltage is internally generated and a center-tap is not required. The back-to-back Schottky diodes across the transformer’s secondary current limit the clock amplitude to approximately 0.8 VP-P differential. This limiter helps prevent large voltage swings of the input clock while preserving the high slew rate that is critical for low jitter. 2.2 µF 220nF CLK+ 220 nF Coilcraft WBC1-1TL 6 1 4 3 50 FIGURE 4-7: External Circuit for Voltage Reference and VBG pins for the VTLA-124 Package. Note that this external circuit is not required for the TFBGA-121 package. 2014-2015 Microchip Technology Inc. 100 fF 100 fF Clock Source 220 nF 12 k CLK- TFBGA-121 Package Device: The decoupling capacitor is embedded in the package. Therefore, no external circuit is required on the PCB. 4.5.3.2 AVDD12 AVDD12 0.1 µF Schottky Diodes (HSMS-2812) MCP37XXX 4.5.3 CLK- FIGURE 4-9: Transformer-Coupled Differential Clock Input Configuration. DS20005355B-page 39 MCP37211-200 AND MCP37D11-200 4.6.1 CLOCK JITTER AND SNR PERFORMANCE In a high-speed pipelined ADC, the SNR performance is directly limited by thermal noise and clock jitter. Thermal noise is independent of input clock and dominant term at low-input frequency. On the other hand, the clock jitter becomes a dominant term as input frequency increases. Equation 4-2 shows the SNR jitter component, which is expressed in terms of the input frequency (fIN) and the total amount of clock jitter (TJitter), where TJitter is a sum of the following two components: • Input clock jitter (phase noise) • Internal aperture jitter (due to noise of the clock input buffer). EQUATION 4-2: SNR VS.CLOCK JITTER SNR Jitter dBc = – 20 log 10 2 f IN T Jitter where the total jitter term (Tjitter) is given by: T Jitter = 2 2 t Jitter , Clock Input + t Aperture , ADC The clock jitter can be minimized by using a high-quality clock source and jitter cleaners, as well as a bandpass filter at the external clock input while a faster clock slew rate improves the ADC aperture jitter. With a fixed amount of clock jitter, the SNR degrades as the input frequency increases. This is illustrated in Figure 4-10. If the input frequency increases from 10 MHz to 20 MHz, the maximum achievable SNR degrades about 6 dB. For every decade (e.g. 10 MHz to 100 MHz), the maximum achievable SNR due to clock jitter is reduced by 20 dB. 160 Jitter = 0.0625 ps 140 Jitter = 0.125 ps SNR (dBc) 120 Jitter = 0.25 ps Jitter = 0.5 ps Jitter = 1 ps 100 80 60 40 20 0 1 10 100 Input Frequency (fIN, MHz) FIGURE 4-10: DS20005355B-page 40 1000 SNR vs. Clock Jitter. 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 4.7 ADC Clock Selection This section describes the ADC clock selection and how to use the built-in Delay-Locked Loop (DLL) and Phase-Locked Loop (PLL) blocks. When the device is first powered-up, the external clock input (CLK+/-) is directly used for the ADC timing as default. After this point, the user can enable the DLL or PLL circuit by setting the register bits. Figure 4-11 shows the clock control blocks. Table 4-4 shows an example of how to select the ADC clock depending on the operating conditions. TABLE 4-4: ADC CLOCK SELECTION (EXAMPLE) Features Control Bit Settings(1) Operating Conditions Input Clock Duty Cycle Correction DCLK Output Phase Delay Control EN_DLL = 0 EN_DLL_DCLK = 0 EN_PHDLY = 0 Not Available Not Available EN_DLL = 1 EN_DLL_DCLK = 0 EN_PHDLY = 0 Available • DLL output is used • Decimation is not used EN_DLL = 1 EN_DLL_DCLK = 1 EN_PHDLY = 1 Available • DLL output is not used • Decimation is used(4) EN_DLL = 0 EN_DLL_DCLK = X EN_PHDLY = 1 Not Available EN_DLL = 1 EN_DLL_DCLK = 0 EN_PHDLY = 1 Available CLK_SOURE = 0 (Default)(2) • DLL output is not used • Decimation is not used (Default)(3) Available CLK_SOURCE = 1(5) • Decimation is not used EN_DLL = X EN_DLL_DCLK = X EN_PHDLY = 0 • Decimation is used(4) EN_DLL = X EN_DLL_DCLK = X EN_PHDLY = 1 Note 1: 2: 3: 4: 5: Not Available Available See Addresses 0x52, 0x53, and 0x64 for bit settings. The sampling frequency (fS) of the ADC core comes directly from the input clock buffer Output data is synchronized with the output data clock (DCLK), which comes directly from the input clock buffer. While using decimation, output clock rate and phase delay are controlled by the digital clock output control block The sampling frequency (fS) is generated by the PLL circuit. The external clock input is used as the reference input clock for the PLL block. 2014-2015 Microchip Technology Inc. DS20005355B-page 41 MCP37211-200 AND MCP37D11-200 fS EN_DLL Clock Input (fCLK): < 250 MHz RESET_DLL EN_DLL_DCLK = 0 EN_DLL = 0 EN_CLK Input Clock Buffer DLL Circuit EN_PHDLY DCLK if CLK_SOURCE = 0 DCLK Phase Delay Duty Cycle Correction (DCC) DCLK_PHDLY_DLL<2:0> EN_DLL_DCLK EN_DUTY DLL Block See Address 0x52 and 0x64<7> for details if digital decimation is used See Address 0x7A, 0x7B, 0x7C, and 0x81 if CLK_SOURCE = 1 EN_PHDLY DCLK_PHDLY_DEC<2:0> Digital Output Clock Phase Delay Control (when decimation filter is used) DCLK Digital Output Clock Rate Control OUT_CLKRATE<3:0> Digital Clock Output Control Block See Address 0x64 and 0x02 for control parameters fREF (5 MHz to 250 MHz) EN_PLL EN_PLL_BIAS Loop Filter Control Parameters: C1: PLL_CAP1<4:0> C3 C2 C1 C3: PLL_CAP3<4:0> R1 PLL_REFDIV<9:0> R1: PLL_RES<4:0> ÷R EN_PLL_REFDIV C2: PLL_CAP2<4:0> if digital decimation is used See Address 0x7A, 0x7B, 0x7C, and 0x81 fS (80 MHz - 250 MHz) EN_PLL_OUT fQ Phase/Freq. Detector Current Charge Pump Loop Filter (3rd Order) fVCO Output/Div DCLK DCLK Delay VCO Loop Filter Control PLL_CHAGPUMP<3:0> ÷N PLL_PRE<11:0> EN_PLL_CLK DCLK_DLY_PLL<2:0> PLL_OUTDIV<3:0> PLL Output Control Block See Address 0x55 and 0x6D for control parameters PLL Block See Address 0x54 - 0x5D for Control Parameters Note: VCO output range is 1.075 GHz – 1.325 GHz by setting PLL_REFDIV<10:0> and PLL_PRE<11:0>, with fREF = 5 MHz - 250 MHz range. N = ---- f = 1.075 – 1.325 GHz VCO R REF f FIGURE 4-11: DS20005355B-page 42 Timing Clock Control Blocks. 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 4.7.1 USING DLL MODE Using the DLL block is the best option when output clock phase control is needed while the clock multiplication and digital decimation are not required. When the DLL block is enabled, the user can control the input clock Duty Cycle Correction (DCC) and the output clock phase delay. See the DLL block in Figure 4-11 for details. Table 4-5 summarizes the DLL control register bits. In addition, see Table 4-24 for the output clock phase control. TABLE 4-5: DLL CONTROL REGISTER BITS Control Parameter Register Descriptions CLK_SOURCE 0x53 CLK_SOURCE = 0: external clock input becomes input of the DLL block EN_DUTY 0x52 Input clock duty cycle correction control bit(1) EN_DLL 0x52 EN_DLL =1: enable DLL block EN_DLL_DCLK 0x52 DLL output clock enable bit EN_PHDLY<2:0> 0x52 Phase delay control bits of digital output clock (DCLK) when DLL or decimation filter is used(2) RESET_DLL 0x52 Reset control bit for the DLL block Note 1: 2: 4.7.1.1 Duty cycle correction is not recommended when a high-quality external clock is used. If decimation is used, the output clock phase delay is controlled using DCLK_PHDLY_DEC<2:0> in Address 0x64. Input Clock Duty Cycle Correction 4.7.1.2 DLL Block Reset Event The ADC performance is sensitive to the clock duty cycle. The ADC achieves optimum performance with 50% duty cycle, and all performance characteristics are ensured when the duty cycle is 50% with ±1% tolerance. The DLL must be reset if the clock frequency is changed. The DLL reset is controlled by using the RESET_DLL bit in Address 0x52 (Register 5-7). The DLL has an automatic reset with the following events: When CLK_SOURCE = 0, the external clock is used as the sampling frequency (fS) of the ADC core. When the external input clock is not high-quality (for example, duty cycle is not 50%), the user can enable the internal clock duty cycle correction circuit by setting the EN_DUTY bit in Address 0x52 (Register 5-7). When duty cycle correction is enabled (EN_DUTY=1), only the falling edge of the clock signal is modified (rising edge is unaffected). • During power-up: Stay in reset until the RESET_DLL bit is cleared. • When a SOFT_RESET command is issued while the DLL is enabled: the RESET_DLL bit is automatically cleared after reset. Because the duty cycle correction process adds additional jitter noise to the clock signal, this option is recommended only when an asymmetrical input clock source causes significant performance degradation or when the input clock source is not stable. Note: The clock duty cycle correction is only applicable when the DLL block is enabled (EN_DLL = 1). It is not applicable for the PLL output. 2014-2015 Microchip Technology Inc. DS20005355B-page 43 MCP37211-200 AND MCP37D11-200 4.7.2 USING PLL MODE The PLL block is mainly used when clock multiplication is needed. When CLK_SOURCE = 1, the sampling frequency (fS) of the ADC core is coming from the internal PLL block. The recommended PLL output clock range is from 80 MHz to 250 MHz. The external clock input is used as the PLL reference frequency. The range of the clock input frequency is from 5 MHz to 250 MHz. Note: 4.7.2.1 The PLL mode is only supported for sampling frequencies between 80 MHz and 250 MHz. PLL Output Frequency and Output Control Parameters The internal PLL can provide a stable timing output ranging from 80 MHz to 250 MHz. Figure 4-11 shows the PLL block using a charge-pump-based integer N PLL and the PLL output control block. The PLL block includes various user control parameters for the desired output frequency. Table 4-6 summarizes the PLL control register bits and Table 4-7 shows an example of register bit settings for the PLL charge pump and loop filter. The PLL block consists of: • • • • • • Reference Frequency Divider (R) Prescaler - which is a feedback divider (N) Phase/Frequency Detector (PFD) Current Charge Pump Loop Filter - a 3rd order RC low-pass filter Voltage-Controlled Oscillator (VCO) The external clock at the CLK+ and CLK- pins is the input frequency to the PLL. The range of input frequency (fREF) is from 5 MHz to 250 MHz. This input frequency is divided by the reference frequency divider (R) which is controlled by the 10-bit-wide PLL_REFDIV<9:0> setting. In the feedback loop, the VCO frequency is divided by the prescaler (N) using PLL_PRE<11:0>. The ADC core sampling frequency (fS), ranging from 80 MHz to 250 MHz, is obtained after the output frequency divider (PLL_OUTDIV<3:0>). For stable operation, the user needs to configure the PLL with the following limits: • Input clock frequency (fREF) = 5 MHz to 250 MHz • Charge pump input frequency = 4 MHz to 50 MHz (after PLL reference divider) • VCO output frequency = 1.075 to1.325 GHz • PLL output frequency after output divider = 80 MHz to 250 MHz The charge pump is controlled by the PFD, and forces sink (DOWN) or source (UP) current pulses onto the loop filter. The charge pump bias current is controlled by the PLL_CHAGPUMP<3:0> bits, approximately 25 µA per step. The loop filter consists of a 3rd order passive RC filter. Table 4-7 shows the recommended settings of the DS20005355B-page 44 charge pump and loop filter parameters, depending on the charge pump input frequency range (output of the reference frequency divider). When the PLL is locked, it tracks the input frequency (fREF) with the ratio of dividers (N/R). The PLL operating status is monitored by the PLL status indication bits: <PLL_VCOL_STAT> and <PLL_VCOH_STAT> in Address 0xD1 (Register 5-81). Equation 4-3 shows the VCO output frequency (fVCO) as a function of the two dividers and reference frequency: EQUATION 4-3: VCO OUTPUT FREQUENCY N f VCO = ---- f REF = 1.075 GHz to 1.325 GHz R Where: N = 1 to 4095 controlled by PLL_PRE<11:0> R = 1 to 1023 controlled by PLL_REFDIV<9:0> See Addresses 0x54 to 0x57 (Registers 5-9 – 5-12) for these bits settings. The tuning range of the VCO is 1.075 GHz to 1.325 GHz. N and R values must be chosen so the VCO is within this range. In general, lower values of the VCO frequency (fVCO) and higher values of the charge pump frequency (fQ) should be chosen to optimize the clock jitter. Once the VCO output frequency is determined to be within this range, set the final ADC sampling frequency (fS) with the PLL output divider using PLL_OUTDIV<3:0>. Equation 44 shows how to obtain the ADC core sampling frequency: EQUATION 4-4: SAMPLING FREQUENCY f VCO f S = -------------------------------------- = 80 MHz to 250 MHz PLL_OUTDIV Table 4-8 shows an example of generating fS = 200 MHz output using the PLL control parameters. 4.7.2.2 PLL Calibration The PLL should be recalibrated following a change in clock input frequency or in the PLL configuration register bit settings (Addresses 0x54 - 0x57; Registers 5-9 – 5-12). The PLL can be calibrated by toggling the PLL_CAL_TRIG bit in Address 0x6B (Register 5-27) or by sending a SOFT_RESET command (See Address 0x00, Register 5-1). The PLL calibration status is observed by the PLL_CAL_STAT bit in Address 0xD1 (Register 5-81). 4.7.2.3 Monitoring of PLL Drifts The PLL drifts can be monitored using the status monitoring bits in Address 0xD1 (Register 5-81). Under normal operation, the PLL maintains a lock across all temperature ranges. It is not necessary to actively monitor the PLL unless extreme variations in the supply voltage are expected or if the input reference clock frequency has been changed. 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 TABLE 4-6: PLL CONTROL REGISTER BITS Control Parameter Register Descriptions PLL Global Control Bits EN_PLL 0x59 Master enable bit for the PLL circuit EN_PLL_OUT 0x5F Master enable bit for the PLL output EN_PLL_BIAS 0x5F Master enable bit for the PLL bias EN_PLL_REFDIV 0x59 Master enable bit for the PLL reference divider PLL Block Setting Bits PLL_REFDIV<9:0> 0x54-0x55 PLL reference divider (R) (See Table 4-8) PLL_PRE<11:0> 0x56-0x57 PLL prescaler (N) (See Table 4-8) PLL_CHAGPUMP<3:0> 0x58 PLL charge pump bias current control: from 25 µA to 375 µA, 25 µA per step PLL_RES<4:0> 0x5A PLL loop filter resistor value selection (See Table 4-7) PLL_CAP3<4:0> 0x5B PLL loop filter capacitor 3 value selection (See Table 4-7) PLL_CAP2<4:0> 0x5D PLL loop filter capacitor 2 value selection (See Table 4-7) PLL_CAP1<4:0> 0x5C PLL loop filter capacitor 1 value selection (See Table 4-7) PLL Output Control Bits PLL_OUTDIV<3:0> 0x55 PLL output divider (See Table 4-8) DCLK_DLY_PLL<2:0> 0x6D Delay DCLK output up to 15 cycles of VCO clocks EN_PLL_CLK 0x6D EN_PLL_CLK = 1 enable PLL output clock to the ADC circuits PLL Drift Monitoring Bits PLL_VCOL_STAT 0xD1 PLL drift status monitoring bit PLL_VCOH_STAT 0xD1 PLL drift status monitoring bit 0x6B Forcing recalibration of the PLL PLL Block Calibration Bits PLL_CAL_TRIG SOFT_RESET 0x00 PLL is calibrated when exiting soft reset mode PLL_CAL_STAT 0xD1 PLL auto-calibration status indication 2014-2015 Microchip Technology Inc. DS20005355B-page 45 MCP37211-200 AND MCP37D11-200 TABLE 4-7: RECOMMENDED PLL CHARGE PUMP AND LOOP FILTER BIT SETTINGS PLL Charge Pump and Loop Filter Parameter fQ = fREF/PLL_REFDIV fQ<5 MHz 5 MHz ≤ fQ < 25 MHz fQ ≥ 25 MHz PLL_CHAGPUMP<3:0> 0x04 0x04 0x04 PLL_RES<4:0> 0x1F 0x1F 0x07 PLL_CAP3<4:0> 0x07 0x02 0x07 PLL_CAP2<4:0> 0x07 0x01 0x08 PLL_CAP1<4:0> 0x07 0x01 0x08 TABLE 4-8: EXAMPLE OF PLL CONTROL BIT SETTINGS FOR fS = 200 MHz WITH fREF = 100 MHz PLL Control Parameter fREF Target Value 100 MHZ fS(1) Descriptions fREF is coming from the external clock input 200 MHZ ADC sampling frequency Target fVCO(2) 1.2 GHZ Range of fVCO = 1.0375 GHz – 1.325 GHz Target fQ(3) 10 MHZ fQ = fREF/PLL_REFDIV (See Table 4-7) PLL Reference Divider (R) 10 PLL_REFDIV<9:0> = 0x0A PLL Prescaler (N) 120 PLL_PRE<11:0> = 0x78 PLL Output Divider 6 Note 1: 2: 3: PLL_OUTDIV<3:0> = 0x06 fS = fVCO/PLL_OUTDIV = 1.2 GHz/6 = 200 MHz fVCO = (N/R) x fREF = (12) x 100 MHz = 1.2 GHz fQ should be maximized for the best noise performance. DS20005355B-page 46 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 4.8 Digital Signal Post-Processing (DSPP) Options While the device converts the analog input signals to digital output codes, the user can enable various digital signal post-processing (DSPP) options for special applications. These options are individually enabled or disabled by setting the configuration bits. Table 4-9 summarizes the digital signal post-processing (DSPP) options that are available for each device family. TABLE 4-9: DIGITAL SIGNAL POST PROCESSING (DSPP) OPTIONS Digital Signal Post Processing Option Available Operating Mode Fractional Delay Recovery (FDR) Dual and octal-channel modes FIR Decimation Filters Single and dual-channel modes CW octal-channel mode Offering Device MCP37211-200 MCP37D11-200 DDC for I and Q data Noise-Shaping Requantizer (NSR) Single and dual-channel modes Digital Gain and Offset correction per channel Available for all channels Digital-Down Conversion (DDC) Single and dual-channel modes CW octal-channel mode Continuous Wave (CW) Beamforming 4.8.1 CW octal-channel mode FRACTIONAL DELAY RECOVERY FOR DUAL- AND OCTAL-CHANNEL MODES The FDR feature is available in dual and octal-channel modes only. When FDR is enabled, the built-in highorder, band-limited interpolation filter compensates for the time delay between input samples of different channels. Due to the finite bandwidth of the interpolation filter, the fractional delay recovery is not guaranteed for input frequencies near the Nyquist frequency (fS/2). For example, in dual-channel mode, FDR can operate correctly for input frequencies in the range from 0 to 0.45*fS (or from 0.55*fs to fS if the input is in the 2nd Nyquist band). In octal-channel mode, FDR can operate correctly for input frequencies in the range from 0 to 0.38*fS. See Table 4-11 for the summary of the input bandwidth requirement for FDR. The FDR process takes place in the digital domain and requires 59 clock cycles of processing time. Therefore, the output data latency is also increased by 59 clock periods. Figure 4-12 shows the simplified block diagram for the ADC output data path with FDR. The related configuration register bits are listed in Table 4-10. Table 4-11 shows the input bandwidth limits of the FDR feature for distortion less than 0.1 mdB (0.1 × 10-3 dB), where fS is the sampling frequency per channel. Figures 4-13 and 4-14 show the responses of the dual-channel and octal-channel FDRs, respectively. 2014-2015 Microchip Technology Inc. MCP37D11-200 FIR Decimation Filters ADC Output for dual or octal-channel Fractional Delay Recovery (FDR) Noise-Shaping Requantizer (NSR) Digital Down-Conversion (DDC) (MCP37D11-200) FDR Control CW Beamforming (MCP37D11-200) ADC data after sampling time delay between channels is removed FIGURE 4-12: Simplified Block Diagram for ADC Output Data Path with Fractional Delay Recovery Option. Note that Fractional Delay Recovery occurs prior to other DSPP features. DS20005355B-page 47 MCP37211-200 AND MCP37D11-200 TABLE 4-10: CONTROL PARAMETERS FOR FRACTIONAL DELAY RECOVERY (FDR) Channel Operation Control Parameter Register Descriptions Global control for both dual and octal-channel modes EN_FDR = 1 0x7A Enable FDR features FDR_BAND 0x81 Select 1st or 2nd Nyquist band Dual-channel SEL_FDR = 0 0x81 Select FDR for dual-channel mode EN_DSPP_8 = 0 0x81 Select digital signal post-processing feature for dual-channel mode EN_DSPP_2 = 1 0x79 Enable all digital post-processing functions for dual-channel operation SEL_FDR = 1 0x81 Select FDR for octal-channel mode EN_DSPP_8 = 1 0x81 Select digital signal post-processing feature for octal-channel operation Octal-channel TABLE 4-11: INPUT BANDWIDTH REQUIREMENT FOR FDR 0 Bandwidth in percentage of fS(1) Nyquist Band (2) -0.0005 0 2nd 45 – 55% Nyquist Band (FDR_BAND = 1) Avoid Octal-Channel Mode 0 – 38% Note 1: 2: 1st Amplitude (dBc) 55 – 100% 1st Nyquist Band (FDR_BAND = 0) fS/2 Interpolation Filter Frequency Response fS 0 Dual-Channel Mode 0 – 45% In-Band Ripple 0.0005 -30 -60 -90 Nyquist Band (FDR_BAND = 0) fs is sampling frequency per channel. Distortion is less than 0.1 mdB. See Address 0x81 for FDR_BAND bit setting -120 0 fS/2 Frequency fS FIGURE 4-13: Response of the DualChannel Fractional Delay Recovery (1st Nyquist Band). fS is the Sampling Frequency. In-Band Ripple 0.0005 0 -0.0005 0 fS/2 fS 2×fS Frequency 3×fS 4×fS fS/2 fS 2×fS Frequency 3×fS 4×fS Amplitude (dBc) 0 -30 -60 -90 -120 0 FIGURE 4-14: Response of the OctalChannel Fractional Delay Recovery (1st Nyquist Band). fS is the Sampling Frequency. DS20005355B-page 48 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 NOISE-SHAPING REQUANTIZER (NSR) The device includes 11-bit and 12-bit digital Noise-Shaping Requantizer (NSR) options. When this function is enabled (see Register 5-33), output data is requantized to 11-bit or 12-bit, respectively. The NSR reshapes the requantization noise function and pushes most of the noise outside the frequency band of interest. As a result, the noise floor within the selected bandwidth is substantially lower than that of a typical 12-bit ADC. To ensure the stability of the NSR, the input signal to the NSR should be limited to less than -0.8 dBFS (~90% of full scale). This can be achieved either by limiting the analog input level or by adjusting the digital gain control. See Section 4.9 “Digital Offset and Digital Gain Settings” and Registers 5-63 to 5-70 for details on the digital gain control. Input levels higher than -0.8 dBFS may corrupt the NSR output and should be avoided. The NSR feature is available only for the single- and dual-channel modes and can be independently controlled per channel via the register settings. Two NSRs are used: • NSRA for channel A • NSRB for channel B In single-channel mode, only NSRA is used. In dual-channel mode, both NSRA and NSRB are used: NSRA is used for the first selected channel, and NSRB is used for the second selected channel. Both have 11-bit and 12-bit options. Each NSR block consists of a series of filters which are selectable using the NSRA<6:0> and NSRB<6:0> register bit settings. Each filter is defined by a specific percentage bandwidth and center frequency. The available percentage bandwidths are: • 11-bit mode: 22% and 25% of the sampling frequency • 12-bit mode: 25% and 29% of the sampling frequency The center frequency of the band is tunable such that the frequency band of interest can be placed anywhere within the Nyquist band. Table 4-12 lists all the NSR-related registers. Equations 4-5 and 4-6 describe the NSR bandwidth of the 11-bit and 12-bit options, respectively. EQUATION 4-5: NSR BANDWIDTH FOR 11-BIT OPTION (a) 22% BW: f Center ---------------- = 0.12 + 0.26 ---------- NSR fS 20 where 0 NSR 20 (b) 25% BW: f Center ---------- NSR – 21 --------------- = 0.125 + 0.25 20 fS where 21 NSR 41 NSR represents the NSR filter number. See Tables 4-13 and 4-14 for details. EQUATION 4-6: NSR BANDWIDTH FOR 12-BIT OPTION (a) 25% BW: f Center ---------------- = 0.125 + 0.25 ---------- NSR – 42 fS 20 where 42 NSR 62 (b) 29% BW: f Center ---------------- = 0.15 + 0.2 ------- NSR – 63 fS 12 where 63 NSR 76 NSR represents the NSR filter number. See Tables 4-13 and 4-14 for details. The center frequency of the band is tuned such that the frequency spectrum of interest can be placed anywhere within the Nyquist band. Figure 4-15 shows a graphical demonstration of the NSR bandwidth, which is a percentage of the ADC sampling frequency. I,1 $PSOLWXGHG%)6 4.8.2 I/ I&HQWHU I+ ELWQRLVHIORRU WKHUPDOQRLVHIORRU I% I6 )UHTXHQF\ I6 FIGURE 4-15: Graphical demonstration of the NSR filter’s transfer function. Note that fB is controlled as a percentage of the sampling frequency (fS). 2014-2015 Microchip Technology Inc. DS20005355B-page 49 MCP37211-200 AND MCP37D11-200 Tables 4-13 and 4-14 show the NSR filter selections. The selectable filters (tuning word) for each mode are: • 11-bit mode: 0 to 41 • 12-bit mode: 42 to 76 NSR does not affect harmonic distortion. Various FFT spectrum plots when NSR is applied are shown in Figures 3-14 to 3-15, Figures 3-17 to 3-20 and Figures 3-22 to 3-23. SNR and SFDR performance versus input amplitude when NSR is enabled is shown in Figures 3-26 and 3-29. In this case, SNR and SFDR are measured within the 12-bit mode NSR bandwidth (25% of the sampling frequency). When the NSR block is disabled, the ADC data is provided directly to the output. TABLE 4-12: REGISTER CONTROL PARAMETERS FOR NSR Control Parameter Register Descriptions NSR Enable bits <EN_NSRA_11> 0x7A Enable 11-bit NSR for channel A <EN_NSRA_12> 0x7A Enable 12-bit NSR for channel A <EN_NSRB_11> 0x7A Enable 11-bit NSR for channel B <EN_NSRB_12> 0x7A Enable 12-bit NSR for channel B NSR Settings NSRA<6:0> 0x78 NSR A settings for single-channel or channel A for dual-channel mode NSRB<6:0> 0x79 NSR B settings for channel B in dual-channel mode 0x78 Resets NSR in the event of overload NSR Block Reset Control <EN_NSR_RESET> Digital Post Processing (DPP) Function Block Settings EN_DPPDUAL TABLE 4-13: NSR Filter No. (Tuning Word) 0x79 Enable DPP block for dual-channel mode 11-BIT NSR FILTER SELECTION(1) fCenter/fS TABLE 4-14: NSRA<6:0> fB (% of fS) NSRB<6:0> 12-BIT NSR FILTER SELECTION(1) NSR Filter No. fB f /f (Tuning Word) Center S (% of fS) NSRA<6:0> NSRB<6:0> 0 0.12 22 000-0000 42 0.125 25 010-1010 1 0.133 22 000-0001 43 0.1375 25 010-1011 2 0.146 22 000-0010 44 0.15 25 010-1100 — — — 19 0.367 22 61 0.3625 25 011-1101 001-0011 62 0.375 25 011-1110 20 0.38 22 001-0100 63 0.15 29 011-1111 21 0.125 25 001-0101 64 0.1667 29 100-0000 22 0.1375 25 001-0110 65 0.1833 29 100-0001 23 0.15 25 001-0111 0.35 29 100-1011 0.3667 29 100-1100 — — — — 75 40 0.3625 25 010-1000 76 41 0.375 25 010-1001 Note 1: Note 1: Filters 0 - 41 are used for 11-bit mode only. If these are used for 12-bit mode, the output becomes unknown state. DS20005355B-page 50 Filters 42 - 76 are used for 12-bit mode only. If these are used for 11-bit mode, the output becomes unknown state. 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 4.8.3 DECIMATION FILTERS The decimation feature is available in single and dualchannel modes and CW octal-channel mode. Figure 4-16 shows a simplified decimation filter block, and Table 4-16 shows the register settings. The decimation rate is controlled by FIR_A<8:0> and FIR_B<7:0> register settings (Addresses 0x7A – 0x7C: Registers 5-35 - 5-37). These registers are thermometer encoded. In single-channel mode, FIR B is disabled and only FIR A is used. In this mode, the maximum programmable decimation rate is 512x using nine cascaded decimation stages. In dual-channel mode or when using the Digital DownConversion (DDC) in I/Q mode, both FIR A and FIR B are used (see Figure 4-16). In this case, both channels are set to the same decimation rate. Note that stage 1A in FIR A is unused: the user must clear FIR_A<0> in Address 0x7A (Register 5-35). In dual-channel mode, the maximum programmable decimation rate is up to 256x, which is half the single-channel decimation rate (512x). The overall SNR performance can be improved with higher decimation rate, but limited to about 73.7 dBFS after 16x. This limitation is mainly due to the relative quantization noise level with respect to the 12-bit LSB size. Decimation rates beyond 16x do not further improve SNR but do serve to filter the output data and reduce the overall output data rate. Table 4-15 summarizes decimation rate versus SNR. TABLE 4-15: DECIMATION RATE VS. SNR PERFORMANCE Decimation Rate SNR (dBFS) 2x 71.4 4x 72.2 8x 72.9 16x 73.3 32x 4.8.3.1 Output Data Rate and Clock Phase Control When Decimation is Used When decimation is used, it also reduces the output clock rate and output bandwidth by a factor equal to the decimation rate applied: the output clock rate is therefore no longer equal to the ADC sampling clock. The user needs to adjust the output clock and data rates in Address 0x02 (Register 5-3) based on the decimation applied. This allows the output data to be synchronized to the output data clock. Phase shifts in the output clock can be achieved using DCLK_PHDLY_DEC<2:0> in Address 0x64 (Register 5-22). Only four output sampling phases are available when a decimation rate of 2x is used, while all eight clock phases are available for other decimation rates. See Section 4.12.8 “Output Data and Clock Rates” for more details. 4.8.3.2 Using Decimation with CW Beamforming and Digital DownConversion Decimation can be used in conjunction with CW octalchannel mode or DDC. In CW octal-channel mode operation, the eight input channels are summed into a single channel prior to entering the decimation filters. When DDC is enabled, the I and Q outputs can be decimated using the same signal path for the dualchannel mode: I and Q data are fed into Channel A and B, respectively. In DDC mode, the half-band filter already includes a 2x decimation rate. Therefore, the maximum decimation rate setting for I/Q filtering is 128x for the FIR_A<8:1> and FIR_B<7:0>. See Section 4.8.4 “Digital Down-Conversion (MCP37D11-200 only)” for details. Note: Fractional Delay Recovery, Digital Gain/Offset adjustment and DDC for I/Q data options occur prior to the decimation filters if they are enabled. 64x 128x 73.7 256x 512x Note: The above data is validated with fS = 200 Msps, fIN = 5 MHz, AIN = -1 dBFS. 2014-2015 Microchip Technology Inc. DS20005355B-page 51 MCP37211-200 AND MCP37D11-200 TABLE 4-16: REGISTER CONTROL PARAMETERS FOR USING DECIMATION FILTERS Control Parameter Register Descriptions Decimation Filter Settings FIR_A<8:0> 0x7A, 0x7B Channel A FIR configuration for single- or dual-channel mode FIR_B<7:0> 0x7C Channel B FIR configuration for single- or dual-channel mode Output Data Rate and Clock Rate Settings(1) OUT_DATARATE<3:0> 0x02 Output data rate: Equal to decimation rate OUT_CLKRATE<3:0> 0x02 Output clock rate: Equal to decimation rate Output Clock Phase Control Settings(2) EN_PHDLY 0x64 Enable digital output phase delay when decimation filter is used DCLK_PHDLY_DEC<2:0> 0x64 Digital output clock phase delay control Digital Signal Post-Processing (DSPP) Function Block Settings EN_DSPP_2 = 1 Note 1: 2: 0x79 Enable dual-channel decimation The output data and clock rates must be updated when decimation rates are changed. Output clock (DCLK) phase control is used when the output clock is divided by OUT_CLKRATE<3:0> bit settings. I Single-channel operation Single Ch. Input Stage 1A FIR D2 Single Stage 2A FIR 2 D4 Single 2 Stage 3A FIR 2 Stage 3B FIR D8 Single 2 Stage 9A FIR 2 Stage 9B FIR (Note 1) (Note 3) Ch. A Dual Input Ch. DeMUX Ch. B Input Dual-channel operation Input for DDC Input DeMUX D512 Single 2 Stage 2B FIR (Note 2) Ch. A Output MUX D2 Dual Output MUX D4 Dual 2 Output MUX D256 Dual Output MUX D128 I/Q Ch. B DDC I/Q filtering Note 1: Stage 1A FIR is the first stage of the FIR A filter. 2: (a) Single-channel mode: Only Channel A is used and controlled by FIR_A<8:0>. (b) Dual-channel mode or I/Q filtering in DDC mode: Both Channel A and Channel B are used: Channel A is used for the first channel or I data, and Channel B is used for the second channel or Q data. 3: Maximum decimation rate: (a) When I/Q filtering in DDC mode is not used: 512x for single-channel and 256x for dual-channel mode. (b) I/Q filtering in DDC mode: 128x each for FIR_A<8:1> and FIR_B<7:0>. FIGURE 4-16: DS20005355B-page 52 Simplified Block Diagram of Decimation Filters. 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 4.8.4 DIGITAL DOWN-CONVERSION (MCP37D11-200 ONLY) Example: If the ADC is sampling an input at 200 Msps, but the user is only interested in a 5 MHz span which is centered at 67 MHz, the digital down-conversion may be used to mix the sampled ADC data with 67 MHz to convert it to DC. The resulting signal can then be decimated by 16x such that the bandwidth of the ADC output is 6.25 MHz (200 Msps/16x decimation gives 12.5 Msps with 6.25 MHz Nyquist bandwidth). If fS/8 mode is selected, then a single 25 Msps channel is output, where 6.25 MHz in the output data corresponds to 67 MHz at the ADC input. If I/Q mode is selected, then two 12.5 Msps channels are output, where DC corresponds to 67 MHz and the channels represent in-phase (I) and quadrature (Q) components of the down-conversion. The Digital Down-Conversion (DDC) feature is available in single-, dual- and CW octal-channel modes in the MCP37D11-200. This feature can be optionally combined with the decimation filter and used to: • translate the input frequency spectrum to a lower frequency band • remove the unwanted out-of-band portion • output the resulting signal as either I/Q data or as a real signal centered at 25% of the output data rate. Figure 4-17 and Figure 4-18 show the DDC configuration for single- and dual-channel DDC mode, respectively. The DDC includes a 32-bit, complex numerically controlled oscillator (NCO), a selectable (high/low) half-band filter, optional decimation, and two output modes (I/Q or fS/8). 4.8.4.1 Single-Channel DDC Figure 4-17 shows the single-channel DDC configuration. Each of these processing sub-blocks are individually controlled. Examples of setting registers for selected output type are shown in Tables 4-17 and 4-18. Frequency translation is accomplished with the NCO. The NCO frequency is programmable from 0 Hz to fS. Phase and amplitude dither can be enabled to improve spurious performance of the NCO. This DDC feature can be used in a variety of highspeed signal-processing applications, including digital radio, wireless base stations, radar, cable modems, digital video, MRI imaging, etc. I or IDEC (Note 5) Q or QDEC FIR_A<8:1> (Note 3) I CH. A ADC DATA Q COS Half-Band Filter A LP/HP SIN NCO (32-bit) (Note 2) HBFILTER_A FIR A Decimation Filter FIR B Decimation Filter NCO ( fS/8 DER ) EN_DDC_FS/8 FIR_B<7:0> (Note 4) Real or RealDEC EN_DDC2 EN_NCO EN_DDC1 Down-Converting and Decimation (Note 1) Decimation and Output Frequency Translation (Note 1) Note 1: See Address 0x80 - 0x81 (Registers 5-41 – 5-42) for the control parameters. 2: See Figure 4-19 for details of NCO control block. 3: Half-band Filter A includes a single- stage decimation filter. 4: See Figure 4-16 for details. 5: Switches are closed if decimation filter is not used, and open if decimation filter is used. FIGURE 4-17: Simplified DDC Block Diagram for Single-Channel Mode. See Tables 4-17 and 4-18 for Using This DDC Block. 2014-2015 Microchip Technology Inc. DS20005355B-page 53 MCP37211-200 AND MCP37D11-200 4.8.4.2 Dual-Channel DDC output after the half-band filter is up-converted by fS/8 for each channel. Otherwise, I/Q of each channel will be output separately, similar to a four-channel input device with the WCK output pin toggling synchronously with the I-data of Channel A. Note that the NCO phase can be adjusted uniquely for each of the two input channels (see Figure 4-19). Examples of setting registers for selected output type are shown in Tables 4-19 and 4-20. Figure 4-18 shows the dual-channel DDC configuration. Each channel includes the same processing elements as shown in the single-channel DDC, however the I/Q outputs cannot be separately decimated since the device only supports two channels of decimation (four would be required for I/Q of Channel A and I/Q of Channel B). The decimation option can be used if the DDC IA ADC Data: IA CH. A QA EN_NCO (Note 2) SIN CH. B RealA HBFILTER_A NCO (32-bit) COS Half-Band Filter A LP/HP SIN COS QA (Note 3) EN_DDC_FS/8 NCO (fS/8) EN_DDC2 (Note 3) QB IB EN_DDC1 RealB Half-Band Filter B LP/HP IB HBFILTER_B QB Down-Converting and Decimation (Note 1) Output Frequency Translation and Decimation (Note 1) Note 1: See Address 0x80 – 0x81 for the Control Parameters. 2: See Figure 4-19 for details of NCO control block. 3: Half-band Filter A and B include a single-stage decimation filter. FIGURE 4-18: Simplified DDC Block Diagram for Dual-Channel Mode. See Tables 4-19 and 4-20 for Using this DDC Block. DS20005355B-page 54 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 4.8.4.3 Numerically Controlled Oscillator (NCO) The on-board Numerically Controlled Oscillator (NCO) provides the frequency reference for the in-phase and quadrature mixers in the digital down-converter (DDC). The NCO serves as a quadrature local oscillator, capable of producing an NCO frequency of between 0 Hz and fS with a resolution of fS/232, where fS is the ADC core sampling frequency. Phase Offset Control CH(n) NCO_PHASE<15:0> Phase Dither Note: The NCO is only used for DDC or CW octalchannel mode. It should be disabled when not in use. EN_PHSDITH Amplitude Dither EN_LFSR Sine/Cosine Signal Generator NCO Tuning EN_NCO Figure 4-19 shows the control signals associated with the NCO. In octal- or dual-channel mode, the NCO allows the output phase to be adjusted on a per-channel basis. EN_AMPDITH EN_LFSR NCO Output NCO_TUNE<31:0> FIGURE 4-19: NCO block diagram 4.8.4.4 • NCO Frequency Control: The NCO frequency is programmed from 0 Hz to fS, using the 32-bit-wide unsigned register variable NCO_TUNE<31:0> in Addresses 0x82 – 0x85 (Registers 5-43 – 5-46). The following equation is NCO_TUNE<31:0> register: EQUATION 4-7: used to set the NCO FREQUENCY NCO_TUNE<31:0> = round 2 Where: 32 Mod f NCO f S ---------------------------------- fS fS = sampling frequency (Hz) fNCO = desired NCO frequency (Hz) Mod (fNCO, fS) = gives the remainder of fNCO/fS Mod() is a remainder function. For Mod(5,2) = 1 and Mod(1.999, 2) = 1.999. example, Example 1: If fNCO is 100 MHz and fS is 200 MHz: Mod f NCO f S = Mod 100 200 = 100 32 Mod 100 200 NCO_TUNE<31:0> = round 2 -------------------------------------- 200 = 0x8000 0000 Example 2: If fNCO is 199.99999994 MHz and fS is 200 MHz: Mod f NCO f S = Mod 199.99999994 200 = 199.99999994 32 Mod 199.99999994 200 NCO_TUNE<31:0> = round 2 --------------------------------------------------------------- 200 = 0xFFFF FFFF 2014-2015 Microchip Technology Inc. NCO Amplitude and Phase Dither The EN_AMPDITH and EN_PHSDITH parameters in Address 0x80 (Register 5-41) can be used for amplitude and phase dithering, respectively. In principle, these will dither the quantization error created by the use of digital circuits in the mixer and local oscillator, thus reducing spurs at the expense of noise. In practice, the DDC circuitry has been designed with sufficient noise and spurious performance for most applications. In the worst-case scenario, the NCO has an SFDR of greater than 116 dB when the amplitude dither is enabled, and 112 dB when disabled. Although the SNR (≈ 93 dB) of the DDC is not significantly affected by the dithering option, using the NCO with dithering options enabled is always recommended for the best performance. 4.8.4.5 NCO for fS/8 and fS/(8xDER) The output of the first down-conversion block (DDC1) is a complex signal (comprising I and Q data) which can then be optionally decimated further up to 128x to provide both a lower output data rate and input channel filtering. If fS/8 mode is enabled, a second mixer stage (DDC2) will convert the I/Q signals to a real signal centered at half of the current Nyquist frequency; i.e., if the output data rate in I/Q mode is 25 Msps per channel (12.5 MHz Nyquist), then in fS/8 mode the output data rate would be 50 Msps (25 Msps each for I and Q), and the signal would be re-centered around 12.5 MHz. In single-channel mode, this is done at the output of the decimation filters (if used). In dual-channel mode, this must be done prior to the decimation. When decimation is enabled, the I/Q outputs are upconverted by fS/(8xDER), where DER is the additional decimation rate added by the FIR decimation filters. This provides a decimated output signal centered at fS/8 or fS/(8xDER) in the frequency domain. DS20005355B-page 55 MCP37211-200 AND MCP37D11-200 4.8.4.6 NCO Phase Offset Control 4.8.4.8 The user can add phase offset to the NCO frequency using the NCO phase offset control registers (Addresses 0x86 to 0x95, Registers 5-47 – 5-62). CH(n)_NCO_PHASE<15:0> is the 16-bit-wide NCO phase offset control parameter for Channel n. A 0x0000 value in the register corresponds to no offset, and a 0xFFFF corresponds to an offset of 359.995°. The phase offset can be controlled with 0.005° per step. The following equation is used to program the NCO phase offset register: EQUATION 4-8: NCO PHASE OFFSET CH(n)_NCO_PHASE<15:0> = 2 16 Offset Value ( --------------------------------------- Where: 360 n = channel number Offset Value () = desired phase offset value in degrees A decimal number is used for the binary contents of CH(n)_NCO_PHASE<15:0>. 4.8.4.7 Half-Band Filter The frequency translation is followed by a half-band digital filter, which is used to reduce the sample rate by a factor of two while rejecting aliases that fall into the band of interest. The user can select high- or low-pass half-band filter using the HBFILTER_A and HBFILTER_B bits in Address 0x80 (Register 5-41). These filters provide greater than 90 dB of attenuation in the attenuation band and less than 1 mdB (10-3 dB) of ripple in the passband region of 20% of the input sampling rate. For example, for an ADC sample rate of 200 MSPS, these filters provide less than 1 mdB of ripple over a bandwidth of 40 MHz. The filter responses shown in Figures 4-16 and 4-17 indicate a ripple of 0.5 mdB and an alias rejection of 90 dB. The output of the half-band filter is a DC-centered complex signal (I and Q). This I and Q signal is then carried to the next down-conversion stage (DDC2) for frequency translation (up-conversion), if the DDC is enabled. Note: The half-band filter delays the data output by 80 clock cycles: 2 (due to decimation) x 40 cycles (due to group delay) In-Phase and Quadrature Signals When the first down-conversion is enabled, it produces In-phase (I) and Quadrature (Q) components as shown in Equation 4-9: 0 -0.0005 0 I AND Q SIGNALS I = ADC COS 2 f NCO t + Q = ADC SIN 2 f NCO t + (a) (b) where: CH(n)_NCO_PHASE<15:0> = 360 ---------------------------------------------------------------------16 0.1 0.2 0.3 0.4 Half-Band Filter Frequency Response 0.5 0.1 0.5 0 (c) Amplitude (dBc) EQUATION 4-9: In-Band Ripple 0.0005 2 = 0.005493164 CH(n)_NCO_PHASE<15:0> where: ADC = output of the ADC block -60 -90 -120 0 0.2 0.3 0.4 Fraction of Input Sample Rate FIGURE 4-20: High-Pass (HP) Response of Half-Band Filter. = NCO phase offset of selected channel, which is defined by CH(n)_NCO_PHASE<15:0> in Addresses 0x86 - 0x95 t = k/fS, with k =1, 2, 3,..., n -30 In-Band Ripple 0.0005 0 -0.0005 0 fNCO = NCO frequency 0.1 0.2 0.3 0.4 Half-Band Filter Frequency Response 0.5 0.1 0.5 I and Q outputs are interleaved where I data is output on the rising edge of the WCK. If I and Q outputs are selected in dual-channel mode with DDC enabled, I data of Channel 0 is output at the rising edge of WCK, followed by Q data of Channel 0, then I and Q data of Channel 1 in the same way. Amplitude (dBc) 0 -30 -60 -90 -120 0 FIGURE 4-21: Half-Band Filter. DS20005355B-page 56 0.2 0.3 0.4 Fraction of Input Sample Rate Low-Pass (LP) Response of 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 4.8.5 EXAMPLES OF REGISTER SETTINGS FOR USING DDC AND DECIMATION The following tables show examples of setting registers for using decimation and digital down-conversion (DDC) depending on the output type selection. This feature is available in the MCP37D11-200 device only. DDC Mode Addr. 0x02(2) 0x7A<6> (FIR_A<0>) 0x7B (FIR_A<8:1>) 0x7C (FIR_B<7:0>) 0x80<5,1,0>(3) 0x81<6,3,2>(4) 0x79<7> (EN_DSPP_2) REGISTER SETTINGS FOR DECIMATION AND DDC OPTIONS FOR SINGLE-CHANNEL MODE – EXAMPLE Decimation Rate (by FIR A and FIR B)(1) TABLE 4-17: 0 Disabled 0x00 0 0x00 0x00 0,0,0 0,0,0 0 ADC 8 Disabled 0x33 1 0x03 0x00 0,0,0 0,0,0 0 ADC with decimation (÷8) 512 Disabled 0x99 1 0xFF 0x00 0,0,0 0,0,0 0 ADC with decimation (÷512) 0 I/Q 0x00(5) 0 0x00 0x00 1,0,1 0,0,0 0 I/Q Data 8 I/Q 0x33 0 0x07 0x07 1,0,1 0,0,0 0 Decimated I/Q (÷8) 0 fS/8 0x11(6) 0 0x00 0x00 1,1,1 0,0,0 0 Real without additional decimation 8 fS/8 0x44 0 0x07 0x07 1,0,1 1,0,0 0 Real with decimation (÷16) Note 1: 2: 3: 4: 5: 6: FIR A Filter FIR B Filter DDC1 DDC2 Dual-Channel DSPP Control Output When DDC is used, the actual total decimation is 2x larger since 2x is included from the DDC Half-Band Filter. Example: Decimation = 8x with DDC-I/Q option actually has 16x decimation with 8x provided by the decimation filter and 2x from the DDC Half-Band Filter. Output data and clock rate control register. 0x80<5,1,0> = <EN_NCO, EN_DDC_FS/8, EN_DDC1>. 0x81<6,3,2> = <EN_DDC2, EN_DSPP_8, 8CH_CW>. Each of I/Q has 1/2 of fS bandwidth. The combined bandwidth is the same as the fS bandwidth. Therefore the data rate adjustment is not needed. The Half-Band Filter A includes decimation of 2. 2014-2015 Microchip Technology Inc. DS20005355B-page 57 MCP37211-200 AND MCP37D11-200 TABLE 4-18: OUTPUT TYPE VS. CONTROL PARAMETERS FOR SINGLE-CHANNEL DDC (EXAMPLE) Output Type Complex: I and Q Decimated I and Q:IDEC, QDEC Real: RealA after DDC(fS/8/DER) without using Decimation Filter Control Parameter Register Descriptions EN_DDC1 = 1 0X80 Enable DDC1 block EN_NCO = 1 0X80 Enable 32-bit NCO HBFILTER_A = 1 0X80 Enable Half-Band Filter A, includes 2x decimation EN_DDC_FS/8 = 0 0X80 NCO(fS/8/DER) is disabled EN_DDC2 = 0 0X81 DDC2 is disabled FIR_A<8:1> = 0x00 0X7B FIR A decimation filter is disabled FIR_B<7:0> = 0x00 0X7C FIR B decimation filter is disabled OUT_CLKRATE<3:0> 0X02 Output clock rate is not affected (no need to change) EN_DDC1 = 1 0X80 Enable DDC1 block EN_NCO = 1 0X80 Enable 32-bit NCO HBFILTER_A = 1 0X80 Enable Half-Band Filter A, includes 2x decimation EN_DDC_FS/8 = 0 0X80 NCO(fS/8/DER) is disabled EN_DDC2 = 0 0X81 DDC2 is disabled FIR_A<8:1> 0X7B Program FIR A filter for extra decimation(1) FIR_B<7:0> 0X7C Program FIR B filter for extra decimation(1) OUT_CLKRATE<3:0> 0X02 Adjust the output clock rate to the decimation rate EN_DDC1 = 1 0X80 Enable DDC1 block EN_NCO = 1 0X80 Enable 32-bit NCO HBFILTER_A = 1 0X80 Enable Half-Band Filter A, includes 2x decimation EN_DDC_FS/8 = 1 0X80 NCO(fS/8/DER) is enabled. This translates the input signal from dc to fS/8(2) EN_DDC2 = 1 0X81 DDC2 is enabled FIR_A<8:1> = 0x00 0X7B Decimation filter FIR A is disabled FIR_B<7:0> = 0x00 0X7C Decimation filter FIR B is disabled OUT_CLKRATE<3:0> = 0001 0X02 Adjust the output clock rate to divided by 2(3) Decimated Real: EN_DDC1 = 1 0X80 Enable DDC1 block RealA_DEC EN_NCO = 1 0X80 Enable 32-bit NCO HBFILTER_A = 1 0X80 Enable Half-Band Filter A, includes 2x decimation EN_DDC_FS/8 = 1 0X80 NCO(fS/8/DER) is enabled. This translates the input signal from dc to fS/8/DER(2) after Decimation Filter and DDC(fS/8/DER) Note 1: 2: 3: 4: EN_DDC2 = 1 0X81 DDC2 is enabled FIR_A<8:1> 0X7B Program FIR B filter for extra decimation(4) FIR_B<7:0> 0X7C Program FIR B filter for extra decimation(4) OUT_CLKRATE<3:0> 0X02 Adjust the output clock rate to the total decimation rate including the 2x decimation by the Half-Band Filter A For I/Q decimation, the maximum decimation rate for the FIR A and FIR B filters is 128x each since the input is already decimated by 2x in the Half-Band Filter. See Figure 4-16 for details. DER is the decimation rate setting of the FIR A and FIR B filters. Divided by 2 is due to the 2x decimation included in the Half-Band Filter A. When this filter is used, the up-conversion frequency is reduced by the extra decimation rates (DER). DS20005355B-page 58 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER SETTINGS FOR DECIMATION AND DDC OPTIONS FOR DUAL-CHANNEL MODE EXAMPLE 0x80<5,1,0>(3) 0x81<6,3,2>(4) 0x79<7> (EN_DSPP_2) Dual-Channel DSPP Control 0x7C (FIR_B<7:0>) DDC2 0x7B (FIR_A<8:1>) DDC1 0x7A<6> (FIR_A<0>) FIR B Filter Address 0x02(2) FIR A Filter DDC-Mode Decimation Rate (by FIR A and FIR B)(1) TABLE 4-19: 0 Disabled 0x00 0 0x00 0x00 0,0,0 0,0,0 0 ADC 8 Disabled 0x33 0 0x07 0x07 0,0,0 0,0,0 0 ADC with decimation (÷8) 256 Disabled 0x88 0 0xFF 0xFF 0,0,0 0,0,0 0 ADC with decimation (÷256) 0 I/Q 0x00(5) 0 0x00 0x00 1,0,1 0,0,0 1 I/Q data 0 fS/8 0x11(6) 0 0x00 0x00 1,1,1 0,0,0 1 Real without additional decimation 8 fS/8 0x44 0 0x0E 0x0E(7) 1,1,1 0,0,0 1 Real with decimation filter (÷16) Note 1: 2: 3: 4: 5: 6: 7: Output When DDC is used, the actual total decimation is 2x larger since 2x is included from the DDC Half-Band Filter. Example: Decimation = 8x with DDC-fS/2 option actually has 16x decimation with 8x provided by the decimation filter and 2x from the DDC Half-Band Filter. Output data and clock rate control register. 0x80<5,1,0> = <EN_NCO, EN_DDC_FS/8, EN_DDC1>. 0x81<6,3,2> = <EN_DDC2, EN_DSPP_8, 8CH_CW>. Each of I/Q has 1/2 of fS bandwidth. The combined bandwidth is the same as the fS bandwidth. Therefore the data rate adjustment is not needed. The Half-Band Filter A/B includes decimation of 2. 0x0E takes into account the stages 1 and 2 are bypassed. See Figure 4-16 for “dual-channel Input” for DDC. 2014-2015 Microchip Technology Inc. DS20005355B-page 59 MCP37211-200 AND MCP37D11-200 TABLE 4-20: OUTPUT TYPE VS. CONTROL PARAMETERS FOR DUAL-CHANNEL DDC EXAMPLE Output Type Complex: I and Q Real: RealA for Channel A and RealB for Channel B after NCO(fS/8/DER) Without Using Decimation Filter Decimated Real: RealA_DEC for Channel A and RealB_DEC for Channel B after NCO(fS/8/DER) and Decimation Filter Note 1: 2: 3: Control Parameter Register Descriptions EN_DSPP_2 = 1 0X79 Enable all digital post-processing functions for dual-channel operations EN_DDC1 = 1 0X80 Enable DDC1 block EN_NCO = 1 0X80 Enable 32-bit NCO HBFILTER_A = 1 0X80 Enable Half-Band Filter A, includes 2x decimation HBFILTER_B = 1 0X80 Enable Half-Band Filter B, includes 2x decimation EN_DDC_FS/8 = 0 0X80 NCO(fS/8/DER) is disabled EN_DDC2 = 0 0X81 DDC2 is disabled FIR_A<8:1> = 0x00 0X7B FIR A decimation filter is disabled FIR_B<7:0> = 0x00 0X7C FIR B decimation filter is disabled OUT_CLKRATE<3:0> 0X02 Output clock rate is not affected (no need to change) EN_DSPP_2 = 1 0X79 Enable all digital post-processing functions for dual-channel operations EN_DDC1 = 1 0X80 Enable DDC1 block EN_NCO = 1 0X80 Enable 32-bit NCO HBFILTER_A = 1 0X80 Enable Half-Band Filter A, includes 2x decimation HBFILTER_B = 1 0X80 Enable Half-Band Filter B, includes 2x decimation EN_DDC_FS/8 = 1 0X80 NCO(fS/8/DER) is enabled. This translates the input signal from DC to fS/8(1) EN_DDC2 = 1 0X81 DDC2 is enabled FIR_A<8:1> = 0x00 0X7B Decimation filter FIR A is disabled FIR_B<7:0> = 0x00 0X7C Decimation filter FIR B is disabled OUT_CLKRATE<3:0> = 0001 0X02 Adjust the output clock rate to divided by 2(2) EN_DSPP_2 = 1 0X79 Enable all digital signal post-processing functions for dualchannel operation EN_DDC1 = 1 0X80 Enable DDC1 block EN_NCO = 1 0X80 Enable 32-bit NCO HBFILTER_A = 1 0X80 Enable Half-Band Filter A, includes 2x decimation HBFILTER_B = 1 0X80 Enable Half-Band Filter B, includes 2x decimation EN_DDC_FS/8 = 1 0X80 NCO(fS/8/DER) is enabled. This translates the input signal from DC to fS/8/DER(1) EN_DDC2 = 1 0X81 DDC2 is enabled FIR_A<8:1> 0X7B Program FIR A filter for extra decimation(3) FIR_B<7:0> 0X7C Program FIR B filter for extra decimation(3) OUT_CLKRATE<3:0> 0X02 Adjust the output clock rate to the total decimation rate including the 2x decimation by the Half-Band Filter A DER is the decimation rate setting of the FIR A and FIR B filters. Divided by 2 is due to the 2x decimation included in the Half-Band Filter A. When this filter is used, the up-conversion frequency is reduced by the extra decimation rates (DER). DS20005355B-page 60 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 4.9 Digital Offset and Digital Gain Settings 4.9.2 CH(N)_DIG_GAIN<7:0> in Addresses 0x96 – 0x9D (Registers 5-63 – 5-70) is used to adjust the digital gain per channel. Figure 4-22 shows a simplified block diagram of the digital offset and gain settings. Offset is applied prior to the gain. Offset and gain adjustments occur prior to DDC, Decimation or FDR when these features are used. 4.9.1 DIGITAL GAIN SETTINGS Note 1: Digital Offset Setting: Register mapping (0x9E – 0xA7) to the corresponding channel is not sequential to the channel order defined by CH_ORDER<23:0>, except for the octal-channel mode. See Table 4-21 for details. DIGITAL OFFSET SETTINGS The offset can be corrected using a 16-bit-wide global offset correction register (0x66) for all channels, offset correction registers for individual channels (0x9E0xA7) or by combining both global and individual offset correction registers. The offset control for individual channels can be used with DIG_OFFSET_WEIGHT <1:0> in 0xA7. The corresponding registers for each correction are shown in Figure 4-22. 2: Gain and NCO Phase Offset: Register mapping to the corresponding channel is sequential to the channel order defined by CH_ORDER<23:0>. Note that, except for the octal-channel mode, the offset setting registers for individual channels, 0x9E-0xA7 (Registers 5-71 – 5-79), do not sequentially correspond to the channel order defined by CH_ORDER<23:0>. Table 4-21 shows the details of the offset registers that correspond to the actual channels, depending on the number of channels used. Corrected ADC Output ADC Output Global Digital Offset Control for all channels Digital Offset Control for individual channel DIG_OFFSET_GLOBAL<15:0> Digital Gain Control for individual channel CH(n)_DIG_GAIN<7:0> CH(n)_DIG_OFFSET<7:0> (See Address 0x66) (See Addresses 0x96 – 0x9D) (See Addresses 0x9E – 0xA5) DIG_OFFSET_WEIGHT<1:0> (See Address 0xA7) FIGURE 4-22: Number of Channel Used TABLE 4-21: Simplified Block Diagram for Digital Offset and Gain Settings. REGISTER ASSIGNMENT FOR OFFSET SETTING Register Address for Offset Setting 1st Channel 2nd Channel 3rd Channel 4th Channel 5th Channel 6th Channel 7th Channel 8th Channel 1 0x9F ─ ─ ─ ─ ─ ─ ─ 2 0xA0 0x9F ─ ─ ─ ─ ─ ─ 3 0xA1 0x9F 0xA0 ─ ─ ─ ─ ─ 4 0xA2 0x9F 0xA0 0xA1 ─ ─ ─ ─ 5 0xA3 0x9F 0xA0 0xA1 0xA2 ─ ─ ─ 6 0xA4 0x9F 0xA0 0xA1 0xA2 0xA3 ─ ─ 7 0xA5 0x9F 0xA0 0xA1 0xA2 0xA3 0xA4 ─ 8 0x9E 0x9F 0xA0 0xA1 0xA2 0xA3 0xA4 0xA5 2014-2015 Microchip Technology Inc. DS20005355B-page 61 MCP37211-200 AND MCP37D11-200 4.10 Continuous Wave (CW) Beamforming and Ultrasound Doppler Signal Processing Using CW Octal-Channel Mode (MCP37D11-200 only) In modern ultrasound medical applications, large numbers of transducers are often used. The signals from these sensors are then coherently combined for higher transducer gain and directivity. The signals from each sensor arrive at the detection device with a different time delay. Also, in multi-channel scanning operations using the MUX, there is a time delay between acquiring input signals (see Section 4.8.1 “Fractional Delay Recovery for Dual- and Octal-Channel Modes”). These time delays may need to be corrected before all input signals are combined for the signal processing. Digital beamforming is a digital signal processing technique that requires summing all input signals from different channels after correcting for time delay. The time-delay correction involves the phase alignment of the detected signals with respect to a reference. HV Amp DAC Along with beamforming, many modern medical ultrasound devices support Doppler imaging, which processes phase information in addition to the classical magnitude detection (for brightness imaging). Ultrasound Doppler signal processing is used to determine movement in the body as represented by blood flow, which can help diagnose the functioning of a heart valve or blood vessel, etc. In a traditional ultrasound system, all of these functions are typically accomplished with discrete components. Figure 4-24 shows an example of an ultrasound system implementation using various specialized components. The MCP37D11-200 device has a built-in feature that can perform some of the functions that are done traditionally using extra components. Continuous wave (CW) digital beamforming and Doppler signal processing features are available, but these are offered in octal-channel operation only. Figure 4-23 shows a simplified block diagram for the ultrasound CW beamforming with DDC I/Q decimation. Note that the sub-blocks shown after the MUX are commonly used for all input channels. Beamformer Central Control Processor Isolation LNA-VGA-ADC Array (up to 256 Channels) AAF HV MUX and T/R Switches T/R Switcher ADC VGA LNA Digital RX Beamformer Clocks Transducer Array Amp ADC Amp ADC I/Q Processing CW Doppler Processing Image and Motion Processing (B Mode) Color Doppler Processing (F Mode) Video DAC/ Video Encoder Amp/ Filter Audio DAC FIGURE 4-23: DS20005355B-page 62 Video Compression Amp Example of Ultrasound System Building Block. 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 4.10.1 BEAMFORMING Beamforming is achieved by scanning all inputs while correcting the phase of each channel with respect to a reference. This can be done using: • Fractional Delay Recovery (FDR) • Phase offset settings of each individual channel • Gain setting per channel While the CW input channel is multiplexed sequentially, the phase offset can be added to the NCO output (each channel individually). CH(n)_NCO_PHASE<15:0>, in Addresses 0x86 to 0x95 (Registers 5-47 – 5-62), corrects the time delay of the incoming signals with respect to the reference. The phase-compensated input signal is then downconverted by a wide dynamic range I/Q demodulator. The digital beamforming of the inputs is then obtained by summing I and Q data from individual channels. The combined I and Q data toals are fed to the half-band filter. Equation 4-10 shows the I and Q data of an individual channel with phase correction (phase offset), and the resulting digital beamforming signal. The processing blocks after the digital beamforming are the same as the sub-blocks used in single-channel operation described in Section 4.8.4.1 “SingleChannel DDC”, except only limited decimation rates of the FIR A and FIR B filters are used due to the processing time requirement for summing the input signals from all channels. EQUATION 4-10: BEAMFORMING SIGNALS I CH n = ADC COS 2 f NCO t + n Q CH n = ADC SIN 2 f NCO t + n N I = ICH n 4.10.2 ULTRASOUND DOPPLER SIGNAL PROCESSING Doppler shift measurement requires summing the input signals from multiple transducer channels and mixing them with a phase-controlled local oscillator frequency. The resulting low-frequency output is then centered near DC and can measure a Doppler shift produced by moving objects, such as blood flow and changes in blood pressure in arteries, etc. In traditional Doppler measurement, many discrete analog components are typically used along with a high-resolution ADC (~18-bit range). This device has unique built-in features that are suitable for ultrasound Doppler shift measurements. By utilizing these features, system engineers can reduce many discrete components which are otherwise necessary for an ultrasound Doppler measurement system. The following built-in digital signal post-processing (DSPP) features in the MCP37D11-200 can be effectively used for the ultrasound Doppler signal processing applications: • Fractional Delay Recovery (FDR): Correct the time delay of signal sampled between channels. See details in Section 4.8.1 “Fractional Delay Recovery for Dual- and Octal-Channel Modes”. • Digital Gain and Offset adjustment for each channel: See details in Section 4.9 “Digital Offset and Digital Gain Settings”. • Down-Conversion for each channel with a unique phase of the same NCO frequency prior to summing the eight channels as shown in Figure 4-24. • After down-conversion by the DDC, the resulting signal can then be decimated to achieve very high SNR in a narrow bandwidth. n=0 N Q = QCH n n=0 CH(n)_NCO_PHASE<15:0> n = 360 ---------------------------------------------------------------------16 2 = 0.005493164 CH(n)_NCO_PHASE<15:0> Where: (n) = NCO phase offset of channel n ADC = the output of the ADC block The NCO phase offset can be controlled by 0.005493164° per step. See Section 4.8.4.6 “NCO Phase Offset Control” for details. 2014-2015 Microchip Technology Inc. DS20005355B-page 63 MCP37211-200 AND MCP37D11-200 I I or IDEC Q or QDEC (Note 1) MUX HBFILTER_A ICH(n) ADC Data: Half-Band Filter A CH. 0 COS QCH(n) SIN NCO Amplitude Dither CH. 2 NCO ( fS/8 DER ) EN_DDC_FS/8 FIR_B<7:0> Real or RealDEC EN_DDC2 EN_AMPDITH EN_LFSR Decimation and Output Frequency Translation Sine/Cosine Signal Generator NCO Phase Dither CH. 7 FIR A Decimation Filter FIR B Decimation Filter LP/HP CH. 1 FIR_A<8:1> EN_PHSDITH EN_LFSR NCO Phase Offset Control NCO (32-bit) CH(n) NCO_PHASE<15:0> EN_NCO NCO_TUNE<31:0> EN_DDC1 Channel Multiplexing/Down-Converting/Digital Beamforming/Decimation (2x) Note 1: 2: (2) Switches are closed if a decimation filter is not used, and open if a decimation filter is used. Digital Gain and Offset adjustments are applied prior to the Digital Down-Converter and are not shown here. FIGURE 4-24: Simplified Block Diagram of CW Beamforming and I/Q Signal Processing - Available in MCP37D11-200 Only. DS20005355B-page 64 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 4.11 Output Data format Table 4-22 shows the relationship between the analog input voltage, the digital data output bits and the overrange bit. By default, the output data format is two’s complement. The device can output the ADC data in offset binary or two’s complement. The data format is selected by the DATA_FORMAT bit in Address 0x62 (Register 5-20). TABLE 4-22: ADC OUTPUT CODE VS. INPUT VOLTAGE (12-BIT MODE) Input Range Offset Binary(1) Two’s Complement(1) Overrange (OVR) AIN > AFS 1111-1111-1111 0111-1111-1111 1 AIN = AFS 1111-1111-1111 0111-1111-1111 0 AIN = AFS – 1 LSb 1111-1111-1110 0111-1111-1110 0 AIN = AFS – 2 LSb 1111-1111-1100 0111-1111-1100 0 • • AIN = AFS/2 1100-0000-0000 0100-0000-0000 0 AIN = 0 1000-0000-0000 0000-0000-0000 0 AIN = -AFS/2 0011-1111-1111 1011-1111-1111 0 1000-0000-0010 0 • • AIN = -AFS + 2 LSb 0000-0000-0010 AIN = -AFS + 1 LSb 0000-0000-0001 1000-0000-0001 0 AIN = -AFS 0000-0000-0000 1000-0000-0000 0 AIN < -AFS 0000-0000-0000 1000-0000-0000 1 Note 1: 4.12 MSb is sign bit Digital Output The device can operate in one of the following two digital output modes: • Full-Rate CMOS • Double-Data-Rate (DDR) LVDS The outputs are powered by DVDD18 and GND. LVDS mode is recommended for data rates above 80 Msps. The digital output mode is selected by the OUTPUT_MODE<1:0> bits in Address 0x62 (Register 5-20). Figures 2-1 – 2-2 show the timing diagrams of the digital output. 4.12.1 FULL RATE CMOS MODE In full-rate CMOS mode, the data outputs (Q11 to Q0, overrange indicator (OVR), word clock (WCK) and the data output clock (DCLK+, DCLK–) have CMOS output levels. The digital output should drive minimal capacitive loads. If the load capacitance is larger than 10 pF, a digital buffer should be used. 4.12.2 In multi-channel configuration, the data is output sequentially with the WCK that is synchronized to the first sampled channel. The device outputs the following LVDS output pairs: • Output Data: Q5+/Q5- through Q0+/Q0• OVR/WCK • DCLK+/DCLKA 100Ω differential termination resistor is required for each LVDS output pin pair. The termination resistor should be located as close as possible to the LVDS receiver. By default, the outputs are standard LVDS levels: 3.5 mA output current with a 1.15V output common-mode voltage on a 100 differential load. See Address 0x63 (Register 5-21) for more details of the LVDS mode control. Note: 2014-2015 Microchip Technology Inc. DOUBLE DATA RATE LVDS MODE In double-data-rate LVDS mode, the output is a parallel data stream which changes on each edge of the output clock. See Figure 2-2 for details. Output Data Rate in LVDS Mode: In octalchannel mode, the input sample rate per channel is fS/8. Therefore, the output data rate required to shift out all 12 bits in DDR is still equivalent to fS. For example, if fS = 200 Msps, each channel’s sample rate is fS/8 = 25 Msps, and the output clock rate (DCLK) for 12-bit DDR output is 200 MHz. DS20005355B-page 65 MCP37211-200 AND MCP37D11-200 4.12.3 OVERRANGE BIT (OVR) The input overrange status bit is asserted (logic high) when the analog input has exceeded the full-scale range of the ADC in either the positive or negative direction. In LVDS DDR Output mode, the OVR bit is multiplexed with the word clock (WCK) output bit such that OVR is output on the falling edge of the data output clock and WCK on the rising edge. The OVR bit has the same pipeline latency as the ADC data bits. In multi-channel mode, the OVR is output independently for each input channel and is synchronized to the data. See Address 0x68 (Register 526) for OVR and WCK control options. If DSPP options are enabled, OVR pipeline latency will be unaffected; however, the data will incur additional delay. This has the effect of allowing the OVR indicator to precede the affected data. 4.12.4 WORD CLOCK (WCK) The word clock output bit indicates the start of a new data set. In single-channel mode, this bit is disabled except for I/Q output mode. In DDR output with multichannel mode, it is always asserted coincidentally with the data from the first sampled channel, and multiplexed with the OVR bit. See Address 0x07 (Register 5-5) and Address 0x68 (Register 5-26) for OVR and WCK control options. 4.12.5 LVDS OUTPUT POLARITY CONTROL In LVDS mode, the output polarity can be controlled independently for each LVDS pair. Table 4-23 summarizes the LVDS output polarity control register bits. TABLE 4-23: 4.12.8 OUTPUT DATA AND CLOCK RATES The user can reduce output data and output clock rates using Address 0x02 (Register 5-3). When decimation or digital down-conversion (DDC) is used, the output data rate has to be reduced to synchronize with the reduced output clock rate. 4.12.9 PHASE SHIFTING OF OUTPUT CLOCK (DCLK) In full-rate CMOS mode, the data output bit transition occurs at the rising edge of DCLK+, so the falling edge of DCLK+ can be used to latch the output data. In double-data-rate LVDS mode, the data transition occurs at both the rising and falling edges of DCLK+. For adequate setup and hold time when latching the data into the external host device, the user can shift the phase of the digital clock output (DCLK+/DCLK-) relative to the data output bits. The output phase shift (delay) is controlled by each unique register depending on which timing source is used or if decimation is used. Table 4-24 shows the output clock phase control registers for each configuration mode: (a) when DLL is used, (b) when decimation is used, and (c) when PLL is used. Figure 4-25 shows an example of the output clock phase delay control using the DCLK_PHDLY_DLL<2:0> when DLL is used. LVDS OUTPUT POLARITY CONTROL Control Parameter Register POL_LVDS<7:0> 0x65 Control polarity of LVDS data pairs POL_WCK_OVR 0x68 Control polarity of WCK and OVR bit pair 4.12.6 Address 0x63 (Register 5-21). The internal termination helps absorb any reflections caused by imperfect impedance termination at the receiver. Descriptions PROGRAMMABLE LVDS OUTPUT In LVDS mode, the default output driver current is 3.5 mA. This current can be adjusted by using the LVDS_IMODE<2:0> bit setting in Address 0x63 (Register 5-21). Available output drive currents are 1.8 mA, 3.5 mA, 5.4 mA and 7.2 mA. 4.12.7 OPTIONAL LVDS DRIVER INTERNAL TERMINATION In most cases, using an external 100Ω termination resistor will give excellent LVDS signal integrity. In addition, an optional internal 100Ω termination resistor can be enabled by setting the LVDS_LOAD bit in DS20005355B-page 66 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 TABLE 4-24: OUTPUT CLOCK (DCLK) PHASE CONTROL PARAMETERS Control Parameter Register Operating Condition(1) When DLL is used: EN_PHDLY 0x64 EN_PHDLY = 1: Enable output clock phase delay control DCLK_PHDLY_DLL<2:0> 0x52 DCLK phase delay control when DLL is used. Decimation is not used. EN_PHDLY 0x64 EN_PHDLY = 1: Enable output clock phase delay control When decimation is used: DCLK_PHDLY_DEC<2:0> DCLK phase delay control when decimation filter is used. The phase delay is controlled in digital clock output control block. When PLL is used: DCLK_DLY_PLL<2:0> Note 1: 0x6D DCLK delay control when PLL is used. See Figure 4-11 for details. LVDS Data Output: Phase Shift: 0° (Default) Output Clock (DCLK+) (1) DCLK_PHDLY_DLL<2:0> = 0 0 0 45° + Default 0 0 1 90° + Default 0 1 0 135° + Default 0 1 1 180° + Default 1 0 0 225° + Default 1 0 1 270° + Default 1 1 0 315° + Default 1 1 1 Note 1: Default value may not be 0° in all operations. FIGURE 4-25: Example of Phase Shifting of Digital Output Clock (DCLK+) when DLL is used. 2014-2015 Microchip Technology Inc. DS20005355B-page 67 MCP37211-200 AND MCP37D11-200 4.12.10 DIGITAL OUTPUT RANDOMIZER Depending on PCB layout considerations and power supply coupling, SFDR may be improved by decorrelating the ADC input from the ADC digital output data. The device includes an output data randomizer option. When this option is enabled, the digital output is randomized by applying an exclusive-OR logic operation between the LSb (D0) and all other data output bits. To decode the randomized data, the reverse operation is applied: an exclusive-OR operation is applied between the LSb (D0) and all other bits. The DCLK, OVR, WCK and LSb (D0) outputs are not affected. Figure 4-26 shows the block diagram of the data randomizer and decoder logic. The output randomizer is enabled by setting the EN_OUT_RANDOM bit in Address 0x07 (Register 5-5). MCP37XXX DCLK OVR WCK Data Acquisition Device DCLK DCLK OVR OVR WCK Q11 Q11 Q10 Q10 WCK Q0 Q11 Q0 Q10 Q2 Q2 Q0 Q1 Q1 Q0 Q2 Q1 EN_OUT_RANDOM Q0 Q0 (a) Data Randomizer FIGURE 4-26: 4.12.11 Q0 (b) Data Decoder Logic Diagram for Digital Output Randomizer and Decoder. OUTPUT DISABLE The digital output can be disabled by setting OUTPUT_MODE<1:0> = 00 in Address 0x62 (Register 5-20). All digital outputs are disabled, including OVR, WCK, DCLK, etc. 4.12.12 OUTPUT TEST PATTERNS To facilitate testing of the I/O interface, the device can produce various predefined or user-defined patterns on the digital outputs. See TEST_PATTERNS<2:0> in Address 0x62 (Register 5-20) for the predefined test patterns. For the user-defined patterns, Addresses 0x74 – 0x77 (Registers 5-29 – 5-32) can be programmed using the SPI interface. When an output test mode is enabled, the ADC’s analog section can still be operational, but does not drive the digital outputs. The outputs are driven only with the selected test pattern. DS20005355B-page 68 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 4.12.12.1 Pseudo-random Number (PN) Sequence Output When TEST_PATTERNS<2:0> = 111, the device outputs a pseudo-random number (PN) sequence which is defined by the polynomial of degree 16, as shown in Equation 4-11. Figure 4-27 shows the block diagram of a 16-bit Linear Feedback Shift Register (LFSR) for the PN sequence. EQUATION 4-11: POLYNOMIAL FOR PN 4 13 15 Px= 1 + x + x + x + x 16 The output PN[15:4] is directly applied to the output pins Qn[11:0]. In addition to the output at the Qn[11:0] pins, the two MSbs, PN[15] and PN[14], are copied to the OVR and WCK pins, respectively. PN[3] Z-4 PN[12] Z-9 PN[14] Z-2 PN[15] Z-1 XOR FIGURE 4-27: Block Diagram of 16-bit LFSR for Pseudo-Random Number (PN) Sequence for Output Test Pattern. 4.13 System Calibration The built-in system calibration algorithm includes: • Harmonic Distortion Correction (HDC) • DAC Noise Cancellation (DNC) • Dynamic Element Matching (DEM) HDC and DNC correct the nonlinearity in the residue amplifier and DAC, respectively. The system calibration is performed by: • Power-up calibration, which takes place during the Power-on Reset sequence (requires 227 clock cycles) • Background calibration, which takes place during normal operation (per 230 clock cycles). Background calibration time is invisible to the user, and primarily affects the ADC's ability to track variations in ambient temperature. The calibration status is monitored by the CAL pin or the ADC_CAL_STAT bit in Address 0xC0 (Register 580). See Address 0x07 (Register 5-5) and 0x1E (Register 5-6) for time delay control of the autocalibration. Table 4-25 shows the calibration time for various ADC core sample rates. TABLE 4-25: CALIBRATION TIME VS. ADC CORE SAMPLE RATE fS (Msps) 200 150 100 70 50 Power-Up Calibration Time (s) 0.67 0.9 1.34 1.92 2.68 Background Calibration Time (s) 5.37 7.16 10.73 15.34 21.48 4.13.1 RESET COMMAND Although the background calibration will track changes in temperature or supply voltage, changes in clock frequency or register configuration should be followed by a recalibration of the ADC. This can be accomplished via either the Hard or Soft Reset command. The recalibration time is the same as the power-up calibration time (227 clock cycles). Resetting the device is highly recommended when exiting from Shutdown or Standby mode after an extended amount of time. During the reset, the device has the following state: • No ADC output • No change in power-on condition of internal reference • Most of the internal clocks are not distributed • Contents of internal user registers: - Not affected by Soft Reset - Reset to default values by Hardware Reset • Current consumption of the digital section is negligible, but no change in the analog section. 2014-2015 Microchip Technology Inc. DS20005355B-page 69 MCP37211-200 AND MCP37D11-200 4.13.1.1 Hardware Reset A hard reset is triggered by toggling the RESET pin. On the rising edge, all internal calibration registers and user registers are initialized to their default states and recalibration of the ADC begins. The recalibration time is the same as the power-up calibration time. See Figure 2-6 for the timing details of the hardware RESET pin. 4.13.1.2 Soft Reset The user can issue a Soft Reset command for a fast recalibration of the ADC by setting the SOFT_RESET bit to ‘0’ in Address 0x00 (Register 5-1). During Soft Reset, all internal calibration registers are initialized to their initial default states. User registers are unaffected. When exiting the Soft Reset (changing from ‘0’ to ‘1’), an automatic device calibration takes place. 4.14 Power Dissipation and Power Savings The power dissipation of the ADC core is proportional to the sample rate (fS). The digital power dissipation of the CMOS outputs are determined primarily by the strength of the digital drivers and the load condition on each output pin. The maximum digital load current (ILOAD) can be calculated as: EQUATION 4-12: 4.14.1 POWER-SAVING MODES This device has two power-saving modes: • Shutdown • Standby They are set by the SHUTDOWN and STANDBY bits in Address 0x00 (Register 5-1). In Shutdown mode, most of the internal circuitry, including the reference and clock, are turned off with the exception of the SPI interface. During Shutdown, the device consumes 25 mA (typical), primarily due to digital leakage. When exiting from Shutdown, issuing a Soft Reset at the same time is highly recommended. This will perform a fast recalibration of the ADC. The contents of the internal registers are not affected by the Soft Reset. In Standby mode, most of the internal circuitry is disabled except for the reference, clock and SPI interface. If the device has been in standby for an extended period of time, the current calibration value may not be accurate. Therefore, when exiting from Standby mode, executing the device Soft Reset at the same time is highly recommended. CMOS OUTPUT LOAD CURRENT I LOAD = DV DD1.8 f DCLK N C LOAD Where: N = Number of bits CLOAD = Capacitive load of output pin The capacitive load presented at the output pins needs to be minimized to minimize digital power consumption. The output load current of the LVDS output is constant, since it is set by LVDS_IMODE<2:0> in Address 0x63 (Register 5-21). DS20005355B-page 70 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 5.0 SERIAL PERIPHERAL INTERFACE (SPI) The user can configure the ADC for specific functions or optimized performance by setting the device’s internal registers through the serial peripheral interface (SPI). The SPI communication uses three pins: CS, SCLK and SDIO. Table 5-1 summarizes the SPI pin functions. The SCLK is used as a serial timing clock and can be used up to 50 MHz. SDIO (Serial Data Input/Output) is a dual-purpose pin that allows data to be sent or read from the internal registers. The Chip Select pin (CS) enables SPI communication when active-low. The falling edge of CS followed by a rising edge of SCLK determines the start of the SPI communication. When CS is tied to high, SPI communication is disabled and the SPI pins are placed in high-impedance mode. The internal registers are accessible by their address. Figures 5-1 and 5-2 show the SPI data communication protocols for this device with MSb-first and LSb-first options, respectively. It consists of: TABLE 5-1: Pin Name Descriptions CS Chip Select pin. SPI mode is initiated at the falling edge. It needs to maintain active-low for the entire period of the SPI communication. The device exits the SPI communication at the rising edge. SCLK Serial clock input pin. • Writing to the device: Data is latched at the rising edge of SCLK • Reading from the device: Data is latched at the falling edge of SCLK SDIO Serial data input/output pin. This pin is initially an input pin (SDI) during the first 16-bit instruction header. After the instruction header, its I/O status can be changed depending on the R/W bit: • if R/W = 0: Data input pin (SDI) for writing • if R/W = 1: Data output pin (SDO) for reading • 16-bit wide instruction header + Data byte 1 + Data byte 2 + . . . + Data Byte N Table 5-2 summarizes the bit functions. The R/W bit of the instruction header indicates whether the command is a read (‘1’) or a write (‘0’): • If the R/W bit is ‘1’, the SDIO pin changes direction from an input (SDI) to an output (SDO) after the 16-bit wide instruction header. By selecting the R/W bit, the user can write the register or read back the register contents. The W1 and W2 bits in the instruction header indicate the number of data bytes to transmit or receive in the following data frame. Bits A2 – A0 are the SPI device address bits. These bits are used when multiple devices are used in the same SPI bus. A2 is internally hardcoded to ‘0’. Bits A1 and A0 correspond to the logic level of the ADR1 and ADR0 pins, respectively. Note: In the VTLA-124 package, ADR1 is internally bonded to ground (logic ‘0’). The R9 – R0 bits represent the starting address of the configuration register to write or read. The data bytes following the instruction header are the register data. All register data is eight bits wide. Data can be sent in MSb-first mode (default) or in LSb-first mode, which is determined by the <LSb_ FIRST> bit setting in Address 0x00 (Register 5-1). In Write mode, the data is clocked in at the rising edge of the SCLK. In the Read mode, the data is clocked out at the falling edge of the SCLK. 2014-2015 Microchip Technology Inc. SPI PIN FUNCTIONS TABLE 5-2: SPI DATA PROTOCOL BIT FUNCTIONS Bit Name Descriptions R/W 1 = Read Mode 0 = Write Mode W1, W0 (Data Length) 00 = Data for one register (1 byte) 01 = Data for two registers (2 bytes) 10 = Data for three registers (3 bytes) 11 = Continuous reading or writing by clocking SCLK(1) A2 - A0 Device SPI Address for multiple devices in SPI bus A2: Internally hardcoded to ‘0’ A1: Logic level of ADR1 pin A0: Logic level of ADR0 pin R9 - R0 Address of starting register D7 - D0 Note 1: Register data. MSb or LSb first, depending on the LSb_FIRST bit setting in 0x00 The register address counter is incremented by one per step. The counter does not automatically reset to 0x00 after reaching the last address (0x15D). Be aware that the user registers are not sequentially allocated. DS20005355B-page 71 MCP37211-200 AND MCP37D11-200 CS SCLK SDIO R/W W1 W0 A2 A1 A0 R9 R8 R7 R6 R5 R4 R3 Device Address R2 R1 R0 D7 D6 D5 D4 D3 D2 D1 D0 Address of Starting Register D7 D6 D5 D4 D3 D2 D1 D0 Register Data 2 Register Data of starting register defined by R9 - R0 16-Bit Instruction Header D2 D1 D0 Register Data N Register Data FIGURE 5-1: SPI Serial Data Communication Protocol with MSb-first. See Figures 2-3 and 2-4 for Timing Specifications. CS SCLK SDIO R0 R1 R2 R3 R4 R5 R6 R7 R8 R9 A0 A1 A2 W0 W1 R/W D0 D1 D2 D3 D4 D5 D6 D7 D0 Address of Starting Register D1 D2 D3 D4 D5 D6 D7 Register Data 2 Device Address 16-Bit Instruction Header D5 D6 D7 Register Data N Register Data of starting register defined by R9 - R0 Register Data FIGURE 5-2: SPI Serial Data Communication Protocol - with LSb-First. See Figures 2-3 and 2-4 for Timing Specifications. 5.1 Register Initialization The internal configuration registers are initialized to their default values under two different conditions: • After 220 clock cycles of delay from the power-on reset (POR). • Resetting the hardware reset pin (RESET). Note 1: All address and bit locations that are not included in the following register map table should not be written or modified by the user. 2: Some registers include factory-controlled bits (FCB). Do not overwrite these bits. Figures 2-3 and 2-4 show the timing details. 5.2 Configuration Registers The internal registers are mapped from Addresses 0x00 – 0x15D. These user registers are not sequentially located. Some user configuration registers include factory-controlled bits. The factory-controlled bits should not be overwritten by the user. All user configuration registers are read/write, except for the last four registers, which are read-only. Each register is made of an 8-bit-wide volatile memory, and their default values are loaded during the power-up sequence or by using the hardware RESET pin. All registers are accessible by the SPI command using the register address. Table 5-3 shows the user-register memory map, and Registers 5-1 – 5-83 show the details of the register bit functions. DS20005355B-page 72 2014-2015 Microchip Technology Inc. REGISTER MAP TABLE Bits Addr. Register Name b7 0x00 SPI Bit Ordering and ADC Mode Selection SHUTDOWN 1 = Shutdown 0x01 No. of Channel Selection and Independency Control of Output Data and Clock Divider 0x02 Output Data and Clock Rate Control 0x04 SPI SDO Timing Control SDO_TIME 0x07 Output Randomizer and WCK Polarity Control POL_WCK 0x1E Auto-Calibration Time Delay Control 0x52 DLL Control 0x53 Clock Source Selection 0x54 PLL Reference Divider 0x55 PLL Output and Reference Divider 0x56 PLL Prescaler (LSb) 0x57 PLL Prescaler (MSb) EN_DATCLK_IND b6 b5 LSb-FIRST b4 STANDBY SOFT_RESET 1 = LSb first 0 = MSb first 0 = Soft Reset FCB<3> = 0 b3 b2 STANDBY 1 = Standby 1 = Standby b1 SOFT_RESET 0=Soft Reset b0 LSb-FIRST 1 = LSb first 0 = MSb first SEL_NCH<2:0> SHUTDOWN 0x0F OUT_CLKRATE<3:0> 0x00 FCB<6:0> = 0011111 EN_AUTOCAL_ TIMEDLY 0x9F FCB<4:0> = 10001 EN_OUT_ RANDOM AUTOCAL_TIMEDLY<7:0> EN_DUTY DCLK_PHDLY_DLL<2:0> FCB<6:4>= 010 0x62 0x80 EN_DLL_DCLK EN_DLL CLK_SOURCE EN_CLK RESET_DLL FCB<3:0>= 0101 0x0A 0x45 PLL_REFDIV<7:0> PLL_OUTDIV<3:0> 0x24 1 = Shutdown FCB<2:0> = 111 OUT_DATARATE<3:0> Default Value 0x00 FCB<1:0> = 10 PLL_REFDIV<9:8> PLL_PRE (LSB)<7:0> 0x48 0x78 FCB<3:0> = 0100 PLL_PRE (MSB)<11:8> 0x40 0x58 PLL Charge Pump 0x59 PLL Enable Control 1 U FCB<4:3> = 10 0x5A PLL Loop Filter Resistor U FCB<1:0> = 01 PLL_RES<4:0> 0x2F FCB<2:0> = 000 PLL_BIAS PLL_CHAGPUMP<3:0> EN_PLL_REFDIV FCB<2:1> = 00 EN_PLL 0x12 FCB<0> = 1 0x41 DS20005355B-page 73 0x5B PLL Loop Filter Cap3 U FCB<1:0> = 01 PLL_CAP3<4:0> 0x27 0x5C PLL Loop Filter Cap1 U FCB<1:0> = 01 PLL_CAP1<4:0> 0x27 0x5D PLL Loop Filter Cap2 U FCB<1:0> = 01 PLL_CAP2<4:0> 0x5F PLL Enable Control 2 0x62 Output Data Format and Output Test Pattern 0x63 LVDS Output Load and Drive Current Control 0x64 Output Clock Phase Control when Decimation Filter is used 0x65 LVDS Output Polarity Control 0x66 Digital Offset Correction - Lower Byte Legend: 2: FCB<5:2> = 1111 U FCB<0> = 0 EN_PLL_OUT DATA_FORMAT OUTPUT_MODE<1:0> FCB<3:0> = 0000 EN_PHDLY LVDS_IMODE<2:0> 0x01 FCB<3:0> = 0011 0x03 NO EFFECT<1:0> DIG_OFFSET_GLOBAL<7:0> 1 = bit is set 0 = bit is cleared 0xF1 0x10 POL_LVDS<5:0> U = Unimplemented bit, read as ‘0’ FCB = Factory-Controlled bits. Do not program Read-only register. Preprogrammed at the factory for internal use. FCB<1:0> = 01 TEST_PATTERNS<2:0> LVDS_LOAD DCLK_PHDLY_DEC<2:0> 0x27 EN_PLL_BIAS 0x00 0x00 x = bit is unknown MCP37211-200 AND MCP37D11-200 2014-2015 Microchip Technology Inc. TABLE 5-3: REGISTER MAP TABLE (CONTINUED) Bits Addr. Register Name b7 0x67 Digital Offset Correction - Upper Byte b6 b5 b4 b3 b2 b1 b0 DIG_OFFSET_GLOBAL<15:8> FCB<5:2> = 0010 0x68 WCK and OVR 0x6B PLL Calibration 0x6D PLL Output and Output Clock Phase 0x74 User-Defined Output Pattern A - Lower Nibble 0x75 User-Defined Output Pattern A - Upper Byte 0x76 User-Defined Output Pattern B - Lower Nibble 0x77 User-Defined Output Pattern B - Upper Byte 0x78 Noise-Shaping Requantizer Channel A Filter 0x79 Dual-Channel DSPP Control EN_DSPP_2 0x7A FIRA0 Filter, FDR and NSR Control FCB<1> = 0 POL_WCK_OVR FCB<6:2> = 00001 U<1:0> EN_PLL_CLK FCB<1> = 0 0x00 EN_WCK_OVR FCB<1:0> = 00 0x24 PLL_CAL_TRIG FCB<1:0> = 00 0x08 DCLK_DLY_PLL<2:0> PATTERN A<3:0> FCB<0> = 0 Do not use (Leave these bits as ‘0000’) 0x00 Do not use (Leave these bits as ‘0000’) 0x00 PATTERN B<11:4> 0x00 NSRA<6:0> NSR_RESET 0x00 NSRB<6:0> FIR_A<0> EN_FDR FCB<0> = 0 EN_NSRB_11 0x00 0x00 PATTERN A<11:4> PATTERN B<3:0> Default Value 0x00 EN_NSRB_12 EN_NSRA_11 EN_NSRA_12 0x00 2014-2015 Microchip Technology Inc. 0x7B FIR A Filter FIR_A<8:1> 0x00 0x7C FIR B Filter FIR_B<7:0> 0x00 0x7D Auto-Scan Channel Order Lower Byte CH_ORDER<7:0> 0x78 0x7E Auto-Scan Channel Order Middle Byte CH_ORDER<15:8> 0xAC 0x7F Auto-Scan Channel Order Upper Byte CH_ORDER<23:16> 0x8E 0x80 Digital Down-Converter Control 1 HBFILTER_B HBFILTER_A EN_NCO EN_AMPDITH EN_PHSDITH EN_LFSR 0x81 Digital Down-Converter Control 2 FDR_BAND EN_DDC2 GAIN_HBF_DDC SEL_FDR EN_DSPP_8 8CH_CW 0x82 Numerically Controlled Oscillator (NCO) Tuning Lower Byte NCO_TUNE<7:0> 0x00 0x83 Numerically Controlled Oscillator (NCO) Tuning Middle Lower Byte NCO_TUNE<15:8> 0x00 0x84 Numerically Controlled Oscillator (NCO) Tuning Middle Upper Byte NCO_TUNE<23:16> 0x00 Legend: 2: U = Unimplemented bit, read as ‘0’ FCB = Factory-Controlled bits. Do not program Read-only register. Preprogrammed at the factory for internal use. 1 = bit is set 0 = bit is cleared x = bit is unknown EN_DDC_FS/8 EN_DDC1 GAIN_8CH<1:0> 0x00 0x00 MCP37211-200 AND MCP37D11-200 DS20005355B-paage 74 TABLE 5-3: REGISTER MAP TABLE (CONTINUED) Bits Addr. Register Name b7 0x85 Numerically Controlled Oscillator (NCO) Tuning Upper Byte 0x86 b6 b5 b4 b3 b2 b1 b0 Default Value DS20005355B-page 75 NCO_TUNE<31:24> 0x00 CH0 NCO Phase Offset in CW or DDC Mode - Lower Byte CH0_NCO_PHASE<7:0> 0x00 0x87 CH0 NCO Phase Offset in CW or DDC Mode - Upper Byte CH0_NCO_PHASE<15:8> 0x00 0x88 CH1 NCO Phase Offset in CW or DDC Mode - Lower Byte CH1_NCO_PHASE<7:0> 0x00 0x89 CH1 NCO Phase Offset in CW or DDC Mode - Upper Byte CH1_NCO_PHASE<15:8> 0x00 0x8A CH2 NCO Phase Offset in CW or DDC Mode - Lower Byte CH2_NCO_PHASE<7:0> 0x00 0x8B CH2 NCO Phase Offset in CW or DDC Mode - Upper Byte CH2_NCO_PHASE<15:8> 0x00 0x8C CH3 NCO Phase Offset in CW or DDC Mode - Lower Byte CH3_NCO_PHASE<7:0> 0x00 0x8D CH3 NCO Phase Offset in CW or DDC Mode - Upper Byte CH3_NCO_PHASE<15:8> 0x00 0x8E CH4 NCO Phase Offset in CW or DDC Mode - Lower Byte CH4_NCO_PHASE<7:0> 0x00 0x8F CH4 NCO Phase Offset in CW or DDC Mode - Upper Byte CH4_NCO_PHASE<15:8> 0x00 0x90 CH5 NCO Phase Offset in CW or DDC Mode - Lower Byte CH5_NCO_PHASE<7:0> 0x00 0x91 CH5 NCO Phase Offset in CW or DDC Mode - Upper Byte CH5_NCO_PHASE<15:8> 0x00 0x92 CH6 NCO Phase Offset in CW or DDC Mode - Lower Byte CH6_NCO_PHASE<7:0> 0x00 0x93 CH6 NCO Phase Offset in CW or DDC Mode - Upper Byte CH6_NCO_PHASE<15:8> 0x00 0x94 CH7 NCO Phase Offset in CW or DDC Mode - Lower Byte CH7_NCO_PHASE<7:0> 0x00 0x95 CH7 NCO Phase Offset in CW or DDC Mode - Upper Byte CH7_NCO_PHASE<15:8> 0x00 0x96 CH0 Digital Gain CH0_DIG_GAIN<7:0> 0x3C 0x97 CH1 Digital Gain CH1_DIG_GAIN<7:0> 0x3C 0x98 CH2 Digital Gain CH2_DIG_GAIN<7:0> 0x3C 0x99 CH3 Digital Gain CH3_DIG_GAIN<7:0> Legend: 2: U = Unimplemented bit, read as ‘0’ FCB = Factory-Controlled bits. Do not program Read-only register. Preprogrammed at the factory for internal use. 1 = bit is set 0 = bit is cleared 0x3C x = bit is unknown MCP37211-200 AND MCP37D11-200 2014-2015 Microchip Technology Inc. TABLE 5-3: REGISTER MAP TABLE (CONTINUED) Bits Addr. Register Name b7 b6 b5 b4 b3 b2 b1 b0 Default Value 0x9A CH4 Digital Gain CH4_DIG_GAIN<7:0> 0x3C 0x9B CH5 Digital Gain CH5_DIG_GAIN<7:0> 0x3C 0x9C CH6 Digital Gain CH6_DIG_GAIN<7:0> 0x3C 0x9D CH7 Digital Gain CH7_DIG_GAIN<7:0> 0x3C 0x9E CH0 Digital Offset CH0_DIG_OFFSET<7:0> 0x00 0x9F CH1 Digital Offset CH1_DIG_OFFSET<7:0> 0x00 0xA0 CH2 Digital Offset CH2_DIG_OFFSET<7:0> 0x00 0xA1 CH3 Digital Offset CH3_DIG_OFFSET<7:0> 0x00 0xA2 CH4 Digital Offset CH4_DIG_OFFSET<7:0> 0x00 0xA3 CH5 Digital Offset CH5_DIG_OFFSET<7:0> 0x00 0xA4 CH6 Digital Offset CH6_DIG_OFFSET<7:0> 0x00 0xA5 CH7 Digital Offset CH7_DIG_OFFSET<7:0> 0xA7 Digital Offset Weight Control 0xC0 Calibration Status Indication (Read only) 0xD1 PLL Calibration Status and PLL Drift Status Indication (Read only) 0x15C CHIP ID - Lower Byte(2) (Read only) CHIP_ID<7:0> ─ 0x15D CHIP ID - Upper Byte(2) (Read only) CHIP_ID<15:8> ─ Legend: 2: FCB<5:3> = 010 ADC_CAL_STAT FCB<4:3> = xx 0x00 DIG_OFFSET_WEIGHT<1:0> FCB<2:0> = 111 0x47 FCB<6:0> = 000-0000 PLL_CAL_STAT U = Unimplemented bit, read as ‘0’ FCB = Factory-Controlled bits. Do not program Read-only register. Preprogrammed at the factory for internal use. FCB<2:1> = xx 1 = bit is set 0 = bit is cleared ─ PLL_VCOL_STAT x = bit is unknown PLL_VCOH_STAT FCB<0> = x ─ 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 DS20005355B-paage 76 TABLE 5-3: MCP37211-200 AND MCP37D11-200 REGISTER 5-1: ADDRESS 0X00 – SPI BIT ORDERING AND ADC MODE SELECTION(1) R/W-0 R/W-0 R/W-1 R/W-0 R/W-0 R/W-1 R/W-0 R/W-0 SHUTDOWN LSb_FIRST SOFT_RESET STANDBY STANDBY SOFT_RESET LSb_FIRST SHUTDOWN bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared bit 7 SHUTDOWN: Shutdown mode setting for power-saving(2) 1 = ADC in Shutdown mode 0 = Not in Shutdown mode (Default) bit 6 LSb_FIRST: Select SPI communication bit order 1 = Start SPI communication with LSb first 0 = Start SPI communication with MSb first (Default) bit 5 SOFT_RESET: Soft Reset control bit(3) 1 = Not in Soft Reset mode (Default) 0 = ADC in Soft Reset bit 4 STANDBY: Send the device into a power-saving Standby mode(4) 1 = ADC in Standby mode 0 = Not in Standby mode (Default) bit 3 STANDBY: Send the device into a power-saving Standby mode(4) 1 = ADC in Standby mode 0 = Not in Standby mode (Default) bit 2 SOFT_RESET: Soft Reset control bit(3) 1 = Not in Soft Reset mode (Default) 0 = ADC in Soft Reset bit 1 LSb_FIRST: Select SPI communication bit order 1 = Start SPI communication with LSb first 0 = Start SPI communication with MSb first (Default) bit 0 SHUTDOWN: Shutdown mode setting for power-saving(2) 1 = ADC in Shutdown mode 0 = Not in Shutdown mode (Default) Note 1: 2: 3: 4: x = Bit is unknown Upper and lower nibble are mirrored, which makes the MSb- or LSb-first mode interchangeable. The lower nibble (bit <3:0>) has a higher priority when the mirrored bits have different values. During Shutdown mode, most of the internal circuits including the reference and clock are turned-off except for the SPI interface. When exiting from Shutdown (changing from ‘1’ to ‘0’), executing the device Soft Reset simultaneously is highly recommended for a fast recalibration of the ADC. The internal user registers are not affected. This bit forces the device into Soft Reset mode, which initializes the internal calibration registers to their initial default states. The user-registers are not affected. When exiting Soft Reset mode (changing from ‘0’ to ‘1’), the device performs an automatic device calibration including PLL calibration if PLL is enabled. DLL is reset if enabled. During Soft Reset, the device has the following states: - no ADC output - no change in power-on condition of internal reference - most of the internal clocks are not distributed - power consumption: (a) digital section - negligible, (b) analog section - no change During Standby mode, most of the internal circuits are turned off except for the reference, clock and SPI interface. When exiting from Standby mode (changing from ‘1’ to ‘0’) after an extended amount of time, executing Soft Reset simultaneously is highly recommended. The internal user registers are not affected. 2014-2015 Microchip Technology Inc. DS20005355B-page 77 MCP37211-200 AND MCP37D11-200 REGISTER 5-2: ADDRESS 0X01 – NUMBER OF CHANNELS, INDEPENDENCY CONTROL OF OUTPUT DATA AND CLOCK DIVIDER R/W-0 R/W-0 EN_DATCLK_IND FCB<3> R/W-0 R/W-0 R/W-1 R/W-1 SEL_NCH<2:0> R/W-1 R/W-1 FCB<2:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7 EN_DATCLK_IND: Enable data and clock divider independently(1) 1 = Enabled 0 = Disabled (Default) bit 6 FCB<3>: Factory-Controlled bit. This is not for the user. Do not change default setting. bit 5-3 SEL_NCH<2:0>: Select the total number of input channels to be used(2) 111 = 7 inputs 110 = 6 inputs 101 = 5 inputs 100 = 4 inputs 011 = 3 inputs 010 = 2 inputs 001 = 1 input (Default) 000 = 8 inputs bit 2-0 Note FCB<2:0>: Factory-Controlled bits. This is not for the user. Do not change default settings. 1: 2: EN_DATCLK_IND = 1 enables OUT_CLKRATE<3:0> settings in Address 0x02 (Register 5-3). See Addresses 0x7D – 0x7F (Registers 5-38 – 5-40) for selecting the input channel order. DS20005355B-page 78 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER 5-3: R/W-0 ADDRESS 0X02 – OUTPUT DATA AND CLOCK RATE CONTROL(1) R/W-0 R/W-0 R/W-0 R/W-0 OUT_DATARATE<3:0> R/W-0 R/W-0 R/W-0 OUT_CLKRATE<3:0> bit 0 bit 7 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared bit 7-4 OUT_DATARATE<3:0>: Output data rate control bits 1111 = Output data is all 0’s 1110 = Output data is all 0’s 1101 = Output data is all 0’s 1100 = Internal test only(2) 1011 = Internal test only(2) 1010 = Internal test only(2) 1001 = Full speed divided by 512 1000 = Full speed divided by 256 0111 = Full speed divided by 128 0110 = Full speed divided by 64 0101 = Full speed divided by 32 0100 = Full speed divided by 16 0011 = Full speed divided by 8 0010 = Full speed divided by 4 0001 = Full speed divided by 2 0000 = Full-speed rate (Default) bit 3-0 OUT_CLKRATE<3:0>: Output clock rate control bits(3,4) 1111 = Full-speed rate 1110 = No clock output 1101 = No clock output 1100 = No clock output 1011 = No clock output 1010 = No clock output 1001 = Full speed divided by 512 1000 = Full speed divided by 256 0111 = Full speed divided by 128 0110 = Full speed divided by 64 0101 = Full speed divided by 32 0100 = Full speed divided by 16 0011 = Full speed divided by 8 0010 = Full speed divided by 4 0001 = Full speed divided by 2 0000 = No clock output (Default) Note 1: 2: 3: 4: x = Bit is unknown This register should be used to realign the output data and clock when the decimation or digital down-conversion (DDC) option is used. 1100 - 1010: Do not reprogram. These settings are used for the internal test only. If these bits are reprogrammed with different settings, the outputs will be in an undefined state. Bits <3:0> become active if EN_DATCLK_IND = 1 in Address 0x01 (Register 5-2). When no clock output is selected (Bits 1110 - 1010): clock output is not available at the DCLK+/DCLK- pins. 2014-2015 Microchip Technology Inc. DS20005355B-page 79 MCP37211-200 AND MCP37D11-200 REGISTER 5-4: ADDRESS 0X04 – SPI SDO OUTPUT TIMING CONTROL R/W-1 R/W-0 R/W-0 R/W-1 R/W-1 R/W-1 R/W-1 R/W-1 FCB<6:0> SDO_TIME bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7 SDO_TIME: SPI SDO output timing control bit 1 = SDO output at the falling edge of clock (Default) 0 = SDO output at the rising edge of clock bit 6-0 FCB<6:0>: Factory-Controlled bits. This is not for the user. Do not change default settings. REGISTER 5-5: ADDRESS 0X07 – OUTPUT RANDOMIZER AND WCK POLARITY CONTROL R/W-0 R/W-1 POL_WCK EN_AUTOCAL_TIMEDLY R/W-1 R/W-0 R/W-0 R/W-0 R/W-1 FCB<4:0> R/W-0 EN_OUT_RANDOM bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7 POL_WCK: WCK polarity control bit(1) 1 = Inverted 0 = Not inverted (Default) bit 6 EN_AUTOCAL_TIMEDLY: Auto-calibration starter time delay counter control bit(2) 1 = Enabled (Default) 0 = Disabled bit 5-1 FCB<4:0>: Factory-Controlled bits. This is not for the user. Do not change default settings. bit 0 EN_OUT_RANDOM: Output randomizer control bit 1 = Enabled: ADC data output is randomized 0 = Disabled (Default) Note 1: 2: See Address 0x68 (Register 5-26) for WCK/OVR pair control. This bit enables the AUTOCAL_TIMEDLY<7:0> settings. See Address 0x1E (Register 5-6). DS20005355B-page 80 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 ADDRESS 0X1E – AUTOCAL TIME DELAY CONTROL(1) REGISTER 5-6: R/W-1 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 AUTOCAL_TIMEDLY<7:0> bit 0 bit 7 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared bit 7-0 Note x = Bit is unknown AUTOCAL_TIMEDLY<7:0>: Auto-calibration start time delay control bits 1111-1111 = Maximum value ••• 1000-0000 = (Default) ••• 0000-0000 = Minimum value 1: EN_AUTOCAL_TIMEDLY in Address 0x07 (Register 5-5) enables this register setting. This register controls the time delay before the auto-calibration starts. The value increases linearly with the bit settings, from minimum to maximum values. REGISTER 5-7: R/W-0 ADDRESS 0X52 – DLL CONTROL R/W-0 EN_DUTY R/W-0 R/W-0 DCLK_PHDLY_DLL<2:0> R/W-1 R/W-0 R/W-1 R/W-0 EN_DLL_DCLK EN_DLL EN_CLK RESET_DLL bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7 EN_DUTY: Enable DLL circuit for duty cycle correction (DCC) of input clock 1 = Correction is ON 0 = Correction is OFF (Default) bit 6-4 DCLK_PHDLY_DLL<2:0>: Select the phase delay of the digital clock output when using DLL(1) 111 = +315° phase-shifted from default 110 = +270° phase-shifted from default 101 = +225° phase-shifted from default 100 = +180° phase-shifted from default 011 = +135 phase-shifted from default 010 = +90° phase-shifted from default 001 = +45° phase-shifted from default 000 = (Default) bit 3 EN_DLL_DCLK: Enable DLL digital clock output 1 = Enabled (Default) 0 = Disabled: DLL digital clock is turned off. ADC output is not available when DLL is used. bit 2 EN_DLL: Enable DLL circuitry to provide a selectable phase clock to digital output clock. 1 = Enabled 0 = Disabled. DLL block is disabled (Default) bit 1 EN_CLK: Enable clock input buffer 1 = Enabled (Default). 0 = Disabled. No clock is available to the internal circuits, ADC output is not available. bit 0 RESET_DLL: DLL circuit reset control(2) 1 = DLL is active 0 = DLL circuit is held in reset (Default) Note 1: 2: These bits have an effect only if EN_PHDLY = 1 and decimation is not used. DLL reset control procedure: Set this bit to ‘0’ (reset) and then to ‘1’. 2014-2015 Microchip Technology Inc. DS20005355B-page 81 MCP37211-200 AND MCP37D11-200 REGISTER 5-8: ADDRESS 0X53 – CLOCK SOURCE SELECTION R/W-0 R/W-1 R/W-0 FCB<6:4> R/W-0 R/W-0 R/W-1 CLK_SOURCE R/W-0 R/W-1 FCB<3:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7-5 FCB<6:4>: Factory-Controlled bits. This is not for the user. Do not change default settings. bit 4 CLK_SOURCE: Select internal timing source 1 = PLL output is selected as timing source 0 = External clock input is selected as timing source (Default) bit 3-0 FCB<3:0>: Factory-Controlled bits. This is not for the user. Do not change default settings. REGISTER 5-9: R/W-0 ADDRESS 0X54 – PLL REFERENCE DIVIDER R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 PLL_REFDIV<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared PLL_REFDIV<7:0>: PLL Reference clock divider control bits(1) 1111-1111 = PLL reference divided by 255 (if PLL_REFDIV<9:8> = 00) 1111-1110 = PLL reference divided by 254 (if PLL_REFDIV<9:8> = 00) ••• 0000-0011 = PLL reference divided by 3 (if PLL_REFDIV<9:8> = 00) 0000-0010 = Do not use (No effect) 0000-0001 = PLL reference divided by 1 (if PLL_REFDIV<9:8> = 00) 0000-0000 = PLL reference not divided (if PLL_REFDIV<9:8> = 00) (Default) bit 7-0 Note x = Bit is unknown 1: PLL_REFDIV is a 10-bit wide setting. See Address 0x55 (Register 5-10) for the upper two bits and Table 5-4 for PLL_REFDIV<9:0> bit settings. This setting controls the clock division ratio of the PLL reference clock (external clock input at the CLK pin) before the PLL phase-frequency detector circuitry. Note that the divider value of 2 is not supported. EN_PLL_REFDIV in Address 0x59 (Register 5-14) must be set. DS20005355B-page 82 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER 5-10: R/W-0 ADDRESS 0X55 – PLL OUTPUT AND REFERENCE DIVIDER R/W-1 R/W-0 R/W-0 R/W-1 R/W-0 R/W-0 FCB<1:0> PLL_OUTDIV<3:0> R/W-0 PLL_REFDIV<9:8> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown PLL_OUTDIV<3:0>: PLL output divider control bits(1) 1111 = PLL output divided by 15 1110 = PLL output divided by 14 ••• 0100 = PLL output divided by 4 (Default) 0011 = PLL output divided by 3 0010 = PLL output divided by 2 0001 = PLL output divided by 1 0000 = PLL output not divided bit 7-4 bit 3-2 FCB<1:0>: Factory-Controlled bits. This is not for the user. Do not change default settings. bit 1-0 PLL_REFDIV<9:8>: Upper two MSb bits of PLL_REFDIV<9:0>(2) 00 = see Table 5-4. (Default) Note 1: 2: PLL_OUTDIV<3:0> controls the PLL output clock divider: VCO output is divided by the PLL_OUTDIV<3:0> setting. See Address 0x54 (Register 5-9) and Table 5-4 for PLL_REFDIV<9:0> settings. EN_PLL_REFDIV in Address 0x59 (Register 5-14) must be set. TABLE 5-4: EXAMPLE – PLL REFERENCE DIVIDER BIT SETTINGS VS. PLL REFERENCE INPUT FREQUENCY PLL_REFDIV<9:0> PLL Reference Frequency 11-1111-1111 Reference frequency divided by 1023 11-1111-1110 Reference frequency divided by 1022 ─ ─ 00-0000-0011 Reference frequency divided by 3 00-0000-0010 Do not use (not supported) 00-0000-0001 Reference frequency divided by 1 00-0000-0000 Reference frequency divided by 1 2014-2015 Microchip Technology Inc. DS20005355B-page 83 MCP37211-200 AND MCP37D11-200 REGISTER 5-11: R/W-0 ADDRESS 0X56 – PLL PRESCALER (LSB) R/W-1 R/W-1 R/W-1 R/W-1 R/W-0 R/W-0 R/W-0 PLL_PRE<7:0> bit 0 bit 7 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared PLL_PRE<7:0>: PLL prescaler selection(1) 1111-1111 = VCO clock divided by 255 (if PLL_PRE<11:8> = 0000) ••• 0111-1000 = VCO clock divided by 120 (if PLL_PRE<11:8> = 0000) (Default) ••• 0000-0010 = VCO clock divided by 2 (if PLL_PRE<11:8> = 0000) 0000-0001 = VCO clock divided by 1 (if PLL_PRE<11:8> = 0000) 0000-0000 = VCO clock not divided (if PLL_PRE<11:8> = 0000) bit 7-0 Note x = Bit is unknown 1: PLL_PRE is a 12-bit-wide setting. The upper four bits (PLL_PRE<11:8>) are defined in Address 0x57. See Table 5-5 for the PLL_PRE<11:0> settings. The PLL Prescaler is used to divide down the VCO output clock in the PLL phase-frequency detector loop circuit. REGISTER 5-12: R/W-0 ADDRESS 0X57 – PLL PRESCALER (MSB) R/W-1 R/W-0 R/W-0 R/W-0 R/W-0 FCB<3:0> R/W-0 R/W-0 PLL_PRE<11:8> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7-4 FCB<3:0>: Factory-Controlled bits. This is not for the user. Do not change default settings. bit 3-0 PLL_PRE<11:8>: PLL prescaler selection(1) 1111 = 212 - 1 (max), if PLL_PRE<7:0> = 0xFF ••• 0000 = Default) Note 1: PLL_PRE is a 12-bit-wide setting. See the lower eight bit settings (PLL_PRE<7:0>) in Address 0x56 (Register 5-11). See Table 5-5 for the PLL_PRE<11:0> settings for PLL feedback frequency. TABLE 5-5: Example: PLL Prescaler Bit Settings and PLL Feedback Frequency PLL_PRE<11:0> PLL Feedback Frequency 1111-1111-1111 VCO clock divided by 4095 (212 - 1) 1111-1111-1110 VCO clock divided by 4094 (212 - 2) ─ ─ 0000-0000-0011 VCO clock divided by 3 0000-0000-0010 VCO clock divided by 2 0000-0000-0001 VCO clock divided by 1 0000-0000-0000 VCO clock divided by 1 DS20005355B-page 84 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER 5-13: R/W-0 ADDRESS 0X58 – PLL CHARGE-PUMP R/W-0 R/W-0 R/W-1 FCB<2:0>: R/W-0 R/W-0 PLL_BIAS R/W-1 R/W-0 PLL_CHAGPUMP<3:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7-5 FCB<2:0>: Factory-Controlled bits. This is not for the user. Do not change default settings. bit 4 PLL_BIAS: PLL charge-pump bias source selection bit 1 = Self-biasing coming from AVDD (Default) 0 = Bandgap voltage from the reference generator (1.2V) bit 3-0 PLL_CHAGPUMP<3:0>: PLL charge pump bias current control bits(1) 1111 = Maximum current ••• 0010 = (Default) ••• 0000 = Minimum current Note 1: PLL_CHAGPUMP<3:0> should be set based on the phase detector comparison frequency. The bias current amplitude increases linearly with increasing the bit setting values. The increase is from approximately 25 µA to 375 µA, 25 µA per step. See Section 4.7.2.1, "PLL Output Frequency and Output Control Parameters" for more details of the PLL block. REGISTER 5-14: U-0 ADDRESS 0X59 – PLL ENABLE CONTROL 1 R/W-1 — R/W-0 FCB<4:3> R/W-0 EN_PLL_REFDIV R/W-0 R/W-0 FCB<2:1> R/W-0 R/W-1 EN_PLL FCB<0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7 Unimplemented: Not used. bit 6-5 FCB<4:3>: Factory-Controlled bits. This is not for the user. Do not change default settings. bit 4 EN_PLL_REFDIV: Enable PLL Reference Divider (PLL_REFDIV<9:0>). 1 = Enabled 0 = Reference divider is bypassed (Default) bit 3-2 FCB<2:1>: Factory-Controlled bits. This is not for the user. Do not change default settings. bit 1 EN_PLL: Enable PLL circuit. 1 = Enabled 0 = Disabled (Default) bit 0 FCB<0>: Factory-Controlled bit. This is not for the user. Do not change default setting. 2014-2015 Microchip Technology Inc. DS20005355B-page 85 MCP37211-200 AND MCP37D11-200 REGISTER 5-15: U-0 ADDRESS 0X5A – PLL LOOP FILTER RESISTOR R/W-0 — R/W-1 R/W-0 R/W-1 R/W-1 FCB<1:0> R/W-1 R/W-1 PLL_RES<4:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7 Unimplemented: Not used. bit 6-5 FCB<1:0>: Factory-Controlled bits. This is not for the user. Do not change default settings. bit 4-0 PLL_RES<4:0>: Resistor value selection bits for PLL loop filter(1) 11111 = Maximum value ••• 01111= (Default) ••• 00000 = Minimum value Note 1: PLL_RES<4:0> should be set based on the phase detector comparison frequency. The resistor value increases linearly with the bit settings, from minimum to maximum values. See the PLL loop filter section in Section 4.7, "ADC Clock Selection". REGISTER 5-16: U-0 ADDRESS 0X5B – PLL LOOP FILTER CAP3 R/W-0 — R/W-1 FCB<1:0> R/W-0 R/W-0 R/W-1 R/W-1 R/W-1 PLL_CAP3<4:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7 Unimplemented: Not used. bit 6-5 FCB<1:0>: Factory-Controlled bits. This is not for the user. Do not change default settings. bit 4-0 PLL_CAP3<4:0>: Capacitor 3 value selection bits for PLL loop filter(1) 11111 = Maximum value ••• 00111= (Default) ••• 00000 = Minimum value Note 1: This capacitor is in series with the shunt resistor, which is set by PLL_RES<4:0>. The capacitor value increases linearly with the bit settings, from minimum to maximum values. This setting should be set based on the phase detector comparison frequency. DS20005355B-page 86 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER 5-17: U-0 ADDRESS 0X5C – PLL LOOP FILTER CAP1 R/W-0 — R/W-1 R/W-0 R/W-0 FCB<1:0> R/W-1 R/W-1 R/W-1 PLL_CAP1<4:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7 Unimplemented: Not used. bit 6-5 FCB<1:0>: Factory-Controlled bits. This is not for the user. Do not change default settings. bit 4-0 PLL_CAP1<4:0>: Capacitor 1 value selection bits for PLL loop filter(1) 11111 = Maximum value ••• 00111= (Default) ••• 00000 = Minimum value Note 1: This capacitor is located between the charge pump output and ground, and in parallel with the shunt resistor which is defined by the PLL_RES<4:0>. The capacitor value increases linearly with the bit settings, from minimum to maximum values. This setting should be set based on the phase detector comparison frequency. REGISTER 5-18: U-0 ADDRESS 0X5D – PLL LOOP FILTER CAP2 R/W-0 — R/W-1 FCB<1:0> R/W-0 R/W-0 R/W-1 R/W-1 R/W-1 PLL_CAP2<4:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7 Unimplemented: Not used. bit 6-5 FCB<1:0>: Factory-Controlled bits. This is not for the user. Do not change default settings. bit 4-0 PLL_CAP2<4:0>: Capacitor 2 value selection bits for PLL loop filter(1) 11111 = Maximum value ••• 00111= (Default) ••• 00000 = Minimum value Note 1: This capacitor is located between the charge pump output and ground, and in parallel with CAP1 which is defined by the PLL_CAP1<4:0>. The capacitor value increases linearly with the bit settings, from minimum to maximum values. This setting should be set based on the phase detector comparison frequency. 2014-2015 Microchip Technology Inc. DS20005355B-page 87 MCP37211-200 AND MCP37D11-200 ADDRESS 0X5F – PLL ENABLE CONTROL 2(1) REGISTER 5-19: R/W-1 R/W-1 R/W-1 FCB<5:2> R/W-1 R/W-0 R/W-0 R/W-0 EN_PLL_OUT EN_PLL_BIAS R/W-1 FCB<1:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7-4 FCB<5:2>: Factory-Controlled bits. This is not for the user. Do not change the default settings. bit 3 EN_PLL_OUT: Enable PLL output. 1 = Enabled 0 = Disabled (Default) bit 2 EN_PLL_BIAS: Enable PLL bias 1 = Enabled 0 = Disabled (Default) bit 1-0 Note FCB<1:0>: Factory-Controlled bits. This is not for the user. Do not change default settings. 1: To enable PLL output, EN_PLL_OUT, EN_PLL_BIAS and EN_PLL in Address 0x59 (Register 5-14) must be set. DS20005355B-page 88 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER 5-20: ADDRESS 0X62 – OUTPUT DATA FORMAT AND OUTPUT TEST PATTERN U-0 R/W-0 R/W-0 — FCB DATA_FORMAT R/W-1 R/W-0 R/W-0 OUTPUT_MODE<1:0> R/W-0 R/W-0 TEST_PATTERNS<2:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7 Unimplemented: Not used. bit 6 FCB: Factory-controlled bit. This is not for the user. Do not change default setting. bit 5 DATA_FORMAT: Output data format selection 1 = Offset binary (unsigned) 0 = Two’s complement (Default) bit 4-3 OUTPUT_MODE<1:0>: Output mode selection(1) 11 = Do not use. Output is undefined 10 = Select DDR LVDS output mode with even bit first(2)(Default) 01 = Select CMOS output mode 00 = Output disabled bit 2-0 TEST_PATTERNS<2:0>: Test output data pattern selection(3) 111 = Output data is pseudo-random number (PN) sequence(4) 110 = Sync Pattern for LVDS output Output: '11111111 0000' 101 = Alternating Sequence for LVDS mode Output: ‘01010101 1010’ 100 = Alternating Sequence for CMOS mode Output: ‘11111111 1111’ alternating with ‘00000000 0000’ 011 = Alternating Sequence for CMOS Output: ‘01010101 0101’ alternating with ‘10101010 1010’ 010 = Ramp Pattern: Output (Q0) is incremented by1 LSB per 64 clock cycles(5) 001 = Double Custom Patterns Output: Alternating custom pattern A (see Addresses 0X74 - 0X75 – Registers 5-29 –5-30) and custom pattern B (see Address 0X76 - 0X77 – Registers 5-31 – 5-32)(6) 000 = Normal Operation. Output: ADC data (Default) Note 1: 2: 3: 4: 5: 6: See Figures 2-1 –2-2 for the timing diagrams. Rising edge: Q10, Q8, Q6, Q4, Q2, Q0. Falling edge: Q11, Q9, Q7, Q5, Q3, Q1. See Section 4.12.12 “Output Test Patterns” for more details. (a) In LVDS mode: only the active pins (per register settings) are active. Inactive output pins are High Z state. (b) In CMOS mode: all data output pins (Q11-Q0), output test pins (TP), OVR and WCK pins are active, even if they are disabled by register settings. Since the output test pins (TP) can toggle during this test, the output test pins can draw extra current if they are connected to the supply pin or ground. To avoid the extra current draws, always leave the TP pins floating (not connected). Pseudo-random number (PN) code is generated by the linear feedback shift register (LFSR). See Section 4.12.12.1 “Pseudo-random Number (PN) Sequence Output” for more details. OVR and WCK bits are incremented by 1 per 219 and 218 clock cycles, respectively. Pattern A<11:0> and B<11:0> are applied to Q<11:0>. Q11 = OVR, Q10 = WCK. 2014-2015 Microchip Technology Inc. DS20005355B-page 89 MCP37211-200 AND MCP37D11-200 REGISTER 5-21: R/W-0 ADDRESS 0X63 – LVDS OUTPUT LOAD AND DRIVER CURRENT CONTROL R/W-0 R/W-0 FCB<3:0> R/W-0 R/W-0 LVDS_LOAD R/W-0 R/W-0 R/W-1 LVDS_IMODE<2:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7-4 FCB<3:0>: Factory-controlled bits. This is not for the user. Do not change default setting. bit 3 LVDS_LOAD: Internal LVDS load termination 1 = Enable internal load termination 0 = Disable internal load termination (Default) bit 2-0 LVDS_IMODE<2:0>: LVDS driver current control bits 111 = 7.2 mA 011 = 5.4 mA 001 = 3.5 mA (Default) 000 = 1.8 mA Do not use the following settings (1): 110, 101, 100, 010 Note 1: Do not use these settings. These settings can result in unknown output currents. DS20005355B-page 90 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER 5-22: R/W-0 ADDRESS 0X64 – OUTPUT CLOCK PHASE CONTROL WHEN DECIMATION FILTER IS USED R/W-0 EN_PHDLY R/W-0 R/W-0 R/W-0 R/W-0 R/W-1 R/W-1 FCB<3:0> DCLK_PHDLY_DEC<2:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7 EN_PHDLY: Enable digital output clock phase delay control when DLL or decimation filter is used. 1 = Enabled 0 = Disabled (Default) bit 6-4 DCLK_PHDLY_DEC<2:0>: Digital output clock phase delay control when decimation filter is used(2) 111 = +315° phase-shifted from default(2) 110 = +270° phase-shifted from default 101 = +225° phase-shifted from default(2) 100 = +180° phase-shifted from default 011 = +135° phase-shifted from default(2) 010 = +90° phase-shifted from default 001 = +45° phase-shifted from default(2) 000 = Default(3) bit 3-0 Note FCB<3:0>: Factory-Controlled bits. This is not for the user. Do not change default settings. 1: 2: 3: These bits have an effect only if EN_PHDLY = 1. See Address 0x52 (Register 5-7) for the same feature when DLL is used. Only available when the decimation filter setting is greater than 2. When FIR_A/B <8:1> = 0’s (default) and FIR_A<6> = 0, only 4phase shifts are available (+45°, +135°, +225°, +315°) from default. See Addresses 0x7A, 0x7B and 0x7C (Registers 5-35 – 5-37). See Addresses 0x6D and 0x52 (Registers 5-28 and 5-7) for DCLK phase shift for other modes. The phase delay for all other settings is referenced to this default phase. REGISTER 5-23: R/W-0 ADDRESS 0X65 – LVDS OUTPUT POLARITY CONTROL R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 NO EFFECT<1:0> POL_LVDS<5:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared bit 7-2 POL_LVDS<5:0>: Control polarity of LVDS data pairs (Q5+/Q5- – Q0+/Q0-) 111111 = Invert all LVDS pairs 111110 = Invert all LVDS pairs except the LSb pair ••• 100000 = Invert MSb LVDS pair ••• 000001 = Invert LSb LVDS pair 000000 = No inversion of LVDS bit pairs (Default) bit 1-0 NO EFFECT<1:0>: No effect bits. 2014-2015 Microchip Technology Inc. x = Bit is unknown DS20005355B-page 91 MCP37211-200 AND MCP37D11-200 REGISTER 5-24: R/W-0 ADDRESS 0X66 – DIGITAL OFFSET CORRECTION (LOWER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 DIG_OFFSET_GLOBAL<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown DIG_OFFSET_GLOBAL<7:0>: Lower byte of DIG_OFFSET_GLOBAL<15:0> for all channels(-) 0000-0000 = Default bit 7-0 -Offset is added to the ADC output. Setting is two’s complement using two combined registers (16-bits wide). Setting range: (-215 to 215 - 1) x 0.125 LSb(s) REGISTER 5-25: R/W-0 ADDRESS 0X67 – DIGITAL OFFSET CORRECTION (UPPER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 DIG_OFFSET_GLOBAL<15:8> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared DIG_OFFSET_GLOBAL<15:8>: Upper byte of DIG_OFFSET_GLOBAL<15:0> for all channels(1) 0000-0000 = Default bit 7-0 Note x = Bit is unknown 1: See Note - in Address 0x66 (Register 5-24) REGISTER 5-26: R/W-0 ADDRESS 0X68 – WCK AND OVR BIT CONTROL R/W-0 R/W-1 R/W-0 FCB<5:2> R/W-0 R/W-1 R/W-0 POL_WCK_OVR EN_WCK_OVR R/W-0 FCB<1:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7-4 FCB<5:2>: Factory-controlled bits. This is not for the user. Do not change default settings. bit 3 POL_WCK_OVR: Polarity control for WCK and OVR bit pair in LVDS mode 1 = Inverted 0 = Not inverted (Default) bit 2 EN_WCK_OVR: Enable WCK and OVR output bit pair 1 = Enabled (Default) 0 = Disabled bit 1-0 FCB<1:0>: Factory-controlled bits. This is not for the user. Do not change default settings. DS20005355B-page 92 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER 5-27: R/W-0 R/W-0 ADDRESS 0X6B – PLL CALIBRATION R/W-0 R/W-0 R/W-1 R/W-0 FCB<6:2> R/W-0 R/W-0 PLL_CAL_TRIG FCB<1:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7-3 FCB<6:2>: Factory-Controlled bits. This is not for the user. Do not change default settings. bit 2 PLL_CAL_TRIG: Manually force recalibration of the PLL at the state of bit transition(1) Toggle from “1” to “0”, or “0” to “1” = Start PLL calibration bit 1-0 Note FCB<1:0>: Factory-Controlled bits. This is not for the user. Do not program. 1: See PLL_CAL_STAT in Address 0xD1 (Register 5-81) for calibration status indication. REGISTER 5-28: U-0 U-0 ─ ADDRESS 0X6D – PLL OUTPUT AND OUTPUT CLOCK PHASE(1) R/W-0 R/W-0 EN_PLL_CLK FCB<1> R/W-0 R/W-0 R/W-0 DCLK_DLY_PLL<2:0> R/W-0 FCB<0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7-6 Unimplemented: Not used bit 5 EN_PLL_CLK: Enable PLL output clock 1 = PLL output clock is enabled to the ADC core 0 = PLL clock output is disabled (Default) bit 4 FCB<1>: Factory-Controlled bit. This is not for the user. Do not change default settings. bit 3-1 DCLK_DLY_PLL<2:0>: Output clock is delayed by the number of VCO clock cycles from the nominal PLL output(2) 111 = Delay of 15 cycles 110 = Delay of 14 cycles ••• 001 = Delay of one cycle 000 = No delay (Default) bit 0 FCB<0>: Factory-Controlled bit. This is not for the user. Do not change default setting. Note 1: 2: This register has effect only when the PLL clock is selected by the CLK_SOURCE bit in Address 0x53 (Register 5-8) and PLL circuit is enabled by EN_PLL bit in Address 0x59 (Register 5-14). This bit setting enables the output clock phase delay. This phase delay control option is applicable when PLL is used as the clock source and the decimation is not used. 2014-2015 Microchip Technology Inc. DS20005355B-page 93 MCP37211-200 AND MCP37D11-200 REGISTER 5-29: R/W-0 ADDRESS 0X74 – USER-DEFINED OUTPUT PATTERN A (LOWER NIBBLE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 Do not use (Leave these bits as ‘0000’) PATTERN_A<3:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared bit 7-4 PATTERN_A<3:0>: Lower nibble of PATTERN_A<11:0>(1) bit 3-0 Do not use: Leave these bits to default settings (‘0000’)(2) Note 1: 2: x = Bit is unknown See PATTERN_A<11:4> in Address 0x75 (Register 5-30) and TEST_PATTERNS<2:0> in Address 0x62 (Register 5-20). The output from these bit settings is on “Unused Output Pattern Test Pins”, which are recommended to be not connected to the host device. Therefore, the effect of these bit settings is not monitored. Leave these bits as default settings (‘0000’) all the time. REGISTER 5-30: R/W-0 ADDRESS 0X75 – USER-DEFINED OUTPUT PATTERN A (UPPER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 PATTERN_A<11:4> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared PATTERN_A<11:4>: Upper byte of PATTERN_A<11:0>(1) bit 7-0 Note x = Bit is unknown 1: See PATTERN_A<3:0> in Address 0x74 (Register 5-29) and TEST_PATTERNS<2:0> in Address 0x62 (Register 5-20). REGISTER 5-31: R/W-0 ADDRESS 0X76 – USER-DEFINED OUTPUT PATTERN B (LOWER NIBBLE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 Do not use (Leave these bits as ‘0000’) PATTERN_B<3:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared bit 7-4 PATTERN_B<3:0>: Lower nibble of PATTERN_B<11:0>(1) bit 3-0 Do not use: Leave these bits to default settings (‘0000’)(2) Note 1: 2: x = Bit is unknown See PATTERN_B<11:4> in Address 0x77 (Register 5-32) and TEST_PATTERNS<2:0> in Address 0x62 (Register 5-20). The output from these bit settings is on “Unused Output Pattern Test Pins”, which are recommended to be not connected to the host device. Therefore, the effect of these bit settings is not monitored. Leave these bits as default settings (‘0000’) all the time. DS20005355B-page 94 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER 5-32: R/W-0 ADDRESS 0X77 – USER-DEFINED OUTPUT PATTERN B (UPPER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 PATTERN_B<11:4> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown PATTERN_B<11:4>: Upper byte of PATTERN_B<11:0>(1) bit 7-0 Note 1: See PATTERN_B<3:0> in Address 0x76 (Register 5-31) and TEST_PATTERNS<2:0> in Address 0x62 (Register 5-20). REGISTER 5-33: R/W-0 ADDRESS 0X78 – NOISE-SHAPING REQUANTIZER RESET CONTROL AND CHANNEL A FILTER (NSRA)(1) R/W-0 R/W-0 R/W-0 NSR_RESET R/W-1 R/W-0 R/W-0 R/W-0 NSRA<6:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7 NSR_RESET: Toggle of this bit causes a reset of the NSRA and NSRB state. - Toggle from ‘1’ to ‘0’ or from ‘0’ to ‘1’ = Reset of NSRA and NSRB(2) - Otherwise = No effect (Default) bit 6-0 NSRA<6:0>: NSRA filter settings. See Tables 4-13 to 4-14 for the NSR filter settings(3) 000-0000 = (Default) Note 1: This register is used for single- and dual-channel modes only. 2: The NSR filter will be also automatically reset if the filter setting is changed. 3: In dual-channel mode, NSRA<6:0> is used for channel A. REGISTER 5-34: R/W-0 ADDRESS 0X79 – DUAL-CHANNEL DIGITAL SIGNAL POST-PROCESSING CONTROL AND NOISE-SHAPING REQUANTIZER CHANNEL B FILTER (NSRB)(1) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 NSRB<6:0> EN_DSPP_2 bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7 EN_DSPP_2: Enable digital post-processing functions for dual-channel operations 1 = Enabled 0 = Disabled (Default) bit 6-0 NSRB<6:0>: NSRB filter settings. See Tables 4-13 to 4-14 for the NSR filter settings(2) 000-0000 = (Default) Note 1: 2: This register is used for single- and dual-channel modes only. In dual-channel mode, NSRB<6:0> is used for channel B. 2014-2015 Microchip Technology Inc. DS20005355B-page 95 MCP37211-200 AND MCP37D11-200 REGISTER 5-35: ADDRESS 0X7A – FIR_A0 FILTER, FDR AND NSR CONTROL(1) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 FCB<1> FIR_A<0> EN_FDR FCB<0> EN_NSRB_11 EN_NSRB_12 EN_NSRA_11 EN_NSRA_12 bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7 FCB<1>: Factory-controlled bit. This is not for the user. Do not change default setting. bit 6 FIR_A<0>: Enable the first 2x decimation (Stage 1A in FIR A) in single-channel mode(2) 1 = Enabled 0 = Disabled (Default) bit 5 EN_FDR: Enable fractional delay recovery (FDR) option 1 = Enabled (with delay of 59 clock cycles). 0 = Disabled (Default) bit 4 FCB<0>: Factory-controlled bit. This is not for the user. Do not change default setting. bit 3 EN_NSRB_11: Enable 11-bit noise-shaping requantizer for Channel B 1 = Enabled 0 = Disabled (Default) bit 2 EN_NSRB_12: Enable 12-bit noise-shaping requantizer for Channel B 1 = Enabled 0 = Disabled (Default) bit 1 EN_NSRA_11: Enable 11-bit noise-shaping requantizer for Channel A 1 = Enabled 0 = Disabled (Default) bit 0 EN_NSRA_12: Enable 12-bit noise-shaping requantizer for Channel A 1 = Enabled 0 = Disabled (Default) Note 1: 2: This register is used only for single- and dual-channel modes. This is the LSb of the FIR A filter settings. For the first 2x decimation, set FIR_A<0> = 1 for single-channel operation, and FIR_A<0> = 0 for dual-channel operation. See Address 0x7B (Register 5-36) for FIR_A<8:1> settings. DS20005355B-page 96 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER 5-36: R/W-0 R/W-0 ADDRESS 0X7B – FIR A FILTER(1,5) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 FIR_A<8:1> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared FIR_A<8:1>: Decimation Filter FIR A settings for Channel A (or I)(2) Single-Channel Mode:(3) FIR_A<8:0> = 1-1111-1111 = Stage 1 - 9 filters (decimation rate: 512) 0-1111-1111 = Stage 1 - 8 filters 0-0111-1111 = Stage 1 - 7 filters 0-0011-1111 = Stage 1 - 6 filters 0-0001-1111 = Stage 1 - 5 filters 0-0000-1111 = Stage 1 - 4 filters 0-0000-0111 = Stage 1 - 3 filters (decimation rate = 8) 0-0000-0011 = Stage 1 - 2 filters (decimation rate = 4) 0-0000-0001 = Stage 1 filter (decimation rate = 2) 0-0000-0000 = Disabled all FIR A filters. (Default) Dual-Channel Mode:(4) FIR_A<8:0> = 1-1111-1110 = Stage 2 - 9 filters (decimation rate: 256) 0-1111-1110 = Stage 2 - 8 filters 0-0111-1110 = Stage 2 - 7 filters 0-0011-1110 = Stage 2 - 6 filters 0-0001-1110 = Stage 2 - 5 filters 0-0000-1110 = Stage 2 - 4 filters 0-0000-0110 = Stage 2 - 3 filters 0-0000-0010 = Stage 2 filter (decimation rate = 2) 0-0000-0000 = Disabled all FIR A filters. (Default) bit 7-0 Note x = Bit is unknown 1: 2: 3: 4: 5: This register is used only for single and dual-channel modes. The register values are thermometer encoded. FIR_A<0> is placed in Address 0x7A (Register 5-35). In single-channel mode, the 1st stage filter is selected by FIR_A<0> = 1 in Address 0x7A (Register 5-35). In dual-channel mode, the 1st stage filter is disabled by setting FIR_A<0> = 0 in Address 0x7A. SNR is improved by approximately 2.5 dB per each filter stage, and output data rate is reduced by a factor of two per stage. The data and clock rates in Address 0X02 (Register 5-3) need to be updated accordingly. Address 0x64 (Register 5-22) setting is also affected. The maximum decimation rate for the single-channel mode is 512, and 256 for the dual-channel mode. 2014-2015 Microchip Technology Inc. DS20005355B-page 97 MCP37211-200 AND MCP37D11-200 REGISTER 5-37: R/W-0 R/W-0 ADDRESS 0X7C – FIR B FILTER(1,2) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 FIR_B<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared FIR_B<7:0>:Decimation Filter FIR B settings for Channel B (or Q)(3) 1111-1111 = Stage 2 - 9 filters (decimation rate = 256) 0111-1111 = Stage 2 - 8 filters 0011-1111 = Stage 2 - 7 filters 0001-1111 = Stage 2 - 6 filters 0000-1111 = Stage 2 - 5 filters 0000-0111 = Stage 2 - 4 filters 0000-0011 = Stage 2 - 3 filters 0000-0001 = Stage 2 filter (decimation rate = 2) 0000-0000 = Disabled all FIR B Filters. (Default) bit 7-0 Note x = Bit is unknown 1: 2: 3: This register is used for the dual-channel mode only. The register values are thermometer encoded. EN_DSPP_2 bit in Address 0x79 (Register 5-34) must be set when using decimation in dual-channel mode. SNR is improved by approximately 2.5 dB per each filter stage, and output data rate is reduced by a factor of two per stage. The data and clock rates in Address 0X02 (Register 5-3) need to be updated accordingly. Address 0x64 (Register 5-22) setting is also affected. The maximum decimation factor for the dual-channel mode is 256. REGISTER 5-38: R/W-0 R/W-1 ADDRESS 0X7D – AUTO-SCAN CHANNEL ORDER (LOWER BYTE) R/W-1 R/W-1 R/W-1 R/W-0 R/W-0 R/W-0 CH_ORDER<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH_ORDER<7:0>: Lower byte of CH_ORDER<31:0>(1) 0111-1000 = Default bit 7-0 Note x = Bit is unknown 1: See Table 5-3 for the channel order selection. See SEL_NCH<2:0> in Address 0x01 (Register 5-2) for the number of channels to be selected. REGISTER 5-39: R/W-1 R/W-0 ADDRESS 0X7E – AUTO-SCAN CHANNEL ORDER (MIDDLE BYTE) R/W-1 R/W-0 R/W-1 R/W-1 R/W-0 R/W-0 CH_ORDER<15:8> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH_ORDER<15:8>: Middle byte of CH_ORDER<31:0>(1) 1010-1100 = Default bit 7-0 Note x = Bit is unknown 1: See Table 5-3 for the channel order selection. See SEL_NCH<2:0> in Address 0x01 (Register 5-2) for the number of channels to be selected. DS20005355B-page 98 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER 5-40: R/W-1 ADDRESS 0X7F – AUTO-SCAN CHANNEL ORDER (UPPER BYTE) R/W-0 R/W-0 R/W-0 R/W-1 R/W-1 R/W-1 R/W-0 CH_ORDER<23:16> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH_ORDER<23:16>: Upper byte of CH_ORDER<31:0>(1) 1000-1110 = Default bit 7-0 Note x = Bit is unknown 1: See Table 5-3 for the channel order selection. See SEL_NCH<2:0> in Address 0x01 (Register 5-2) for the number of channels to be selected. REGISTER 5-41: ADDRESS 0X80 – DIGITAL DOWN-CONVETER CONTROL 1(1) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 HBFILTER_B HBFILTER_A EN_NCO EN_AMPDITH EN_PHSDITH EN_LFSR EN_DDC_FS/8 EN_DDC1 bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7 HBFILTER_B: Select half-bandwidth filter at DDC output of channel B in dual-channel mode(2) 1 = Select High-Pass filter at DDC output 0 = Select Low-Pass filter at DDC output (Default) bit 6 HBFILTER_A: Select half-bandwidth filter at DDC output of channel A(2) 1 = Select High-Pass filter at DDC output 0 = Select Low-Pass filter at DDC output (Default) bit 5 EN_NCO: Enable NCO of DDC1 1 = Enabled 0 = Disabled (Default) bit 4 EN_AMPDITH: Enable amplitude dithering for NCO(3, 4) 1 = Enabled 0 = Disabled (Default) bit 3 EN_PHSDITH: Enable phase dithering for NCO(3, 4) 1 = Enabled 0 = Disabled (Default) bit 2 EN_LFSR: Enable linear feedback shift register (LFSR) for amplitude and phase dithering for NCO 1 = Enabled 0 = Disabled (Default) bit 1 EN_DDC_FS/8: Enable NCO for the DDC2 to center the DDC output signal to be around fS/8/DER(5) 1 = Enabled 0 = Disabled (Default) bit 0 EN_DDC1: Enable digital down converter 1 (DDC1) 1 = Enabled(6) 0 = Disabled (Default) Note 1: 2: 3: 4: 5: 6: This register is used for single-, dual- and octal-channel modes when CW feature is enabled (8CH_CW = 1). This filter includes a decimation of 2. -Single-channel mode: HBFILTER_A is used. -Dual-channel mode: Both HBFILTER_A and HBFILTER_B are used. This requires the LFSR to be enabled: EN_LFSR=1 EN_AMPDITH = 1 and EN_PHSDITH = 1 are recommended for the best performance. DER is the decimation rate defined by FIR A or FIR B filter. If up-converter is not enabled (disabled), output is I/Q data. DDC and NCO are enabled. For DDC function, bits 0, 2 and 5 need to be enabled all together. 2014-2015 Microchip Technology Inc. DS20005355B-page 99 MCP37211-200 AND MCP37D11-200 REGISTER 5-42: ADDRESS 0X81 – DIGITAL DOWN-CONVERTER CONTROL 2 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 FDR_BAND EN_DDC2 GAIN_HBF_DDC SEL_FDR EN_DSPP_8 8CH_CW R/W-0 R/W-0 GAIN_8CH<1:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7 FDR_BAND: Select 1st or 2nd Nyquist band 1 = 2nd Nyquist band 0 = 1st Nyquist band (Default) bit 6 EN_DDC2: Enable DDC2 after the digital half-band filter (HBF) in DDC. 1 = Enabled 0 = Disabled (Default) bit 5 GAIN_HBF_DDC: Gain selection for the output of the digital half-band filter (HBF) in DDC(1) 1 = x2 0 = x1 (Default) bit 4 SEL_FDR: Select fractional delay recovery (FDR) 1 = FDR for 8-channel 0 = FDR for dual-channel (Default) bit 3 EN_DSPP_8: Enable digital signal post-processing (DSPP) features for 8-channel operation(2) 1 = Enabled 0 = Disabled (Default) bit 2 8CH_CW: Enable CW mode in octal-channel mode(2, 3) 1 = Enabled 0 = Disabled (Default) bit 1-0 GAIN_8CH<1:0>: Select gain factor for CW signal in octal-channel modes. 11 = x8, 10 = x4, 01 = x2, 00 = x1 (Default) Note 1: 2: 3: See Section 4.8.3, "Decimation Filters". By enabling this bit, the phase offset corrections in Addresses 0x086 – 0x095 (Registers 5-47 – 5-62) are also enabled. EN_DSPP_8 is a global setting bit to enable SEL_FDR and LVDS_8CH bits (Address 0x62 - Register 5-20). When CW mode is enabled, the ADC output is the result of the summation (addition) of all eight channels’ data after each channel’s digital phase offset, digital gain, and digital offset are controlled using the Addresses 0x86 - 0xA7 (Registers 5-47 to 5-79). The result is similar to the beamforming in the phased-array sensors. DS20005355B-page 100 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER 5-43: R/W-0 R/W-0 ADDRESS 0X82 – NUMERICALLY CONTROLLED OSCILLATOR TUNING (LOWER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 NCO_TUNE<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared NCO_TUNE <7:0>: Lower byte of NCO_TUNE<31:0>(1) 0000-0000 = DC (0 Hz) when NCO_TUNE<31:0> = 0x00000000 (Default) bit 7-0 Note x = Bit is unknown 1: See Note 1 and Note 2 in Address 0x85 (Register 5-46). REGISTER 5-44: R/W-0 R/W-0 ADDRESS 0X83 – NUMERICALLY CONTROLLED OSCILLATOR TUNING (MIDDLE-LOWER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 NCO_TUNE<15:8> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared NCO_TUNE<15:8>: Middle lower byte of NCO_TUNE<31:0>(1) 0000-0000 = Default bit 7-0 Note x = Bit is unknown 1: See Note 1 and Note 2 in Address 0x85 (Register 5-46). REGISTER 5-45: R/W-0 R/W-0 ADDRESS 0X84 – NUMERICALLY CONTROLLED OSCILLATOR TUNING (MIDDLE-UPPER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 NCO_TUNE<23:16> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared NCO_TUNE<23:16>: Middle upper byte of NCO_TUNE<31:0>(1) 0000-0000 = Default bit 7-0 Note x = Bit is unknown 1: See Note 1 and Note 2 in Address 0x85 (Register 5-46). 2014-2015 Microchip Technology Inc. DS20005355B-page 101 MCP37211-200 AND MCP37D11-200 REGISTER 5-46: R/W-0 R/W-0 ADDRESS 0X85 – NUMERICALLY CONTROLLED OSCILLATOR TUNING (UPPER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 NCO_TUNE<31:24> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared NCO_TUNE<31:24>: Upper byte of NCO_TUNE<31:0>(1,2) 1111-1111 = fS if NCO_TUNE<31:0> = 0xFFFF FFFF ••• 0000-0000 = Default bit 7-0 Note x = Bit is unknown 1: 2: This Register is used only when DDC is enabled: EN_DDC1 = 1 in Address 0x80 (Register 5-41). See Section 4.8.4.3, "Numerically Controlled Oscillator (NCO)" for the details of NCO. NCO frequency = (NCO_TUNE<31:0>/232) x fS, where fS is the sampling clock frequency. REGISTER 5-47: R/W-0 R/W-0 ADDRESS 0X86 – CH0 NCO PHASE OFFSET IN CW OR DDC MODE (LOWER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH0_NCO_PHASE<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH0_NCO_PHASE<7:0>: Lower byte of CH0_NCO_PHASE<15:0>(1,2,3) 1111-1111 = 1.4° when CH0_NCO_PHASE<15:0> = 0x00FF ••• 0000-0000 = 0° when CH0_NCO_PHASE<15:0> = 0x0000 (Default) bit 7-0 Note x = Bit is unknown 1: 2: 3: This register is not used in the MCP37211. In the MCP37D11, this register has an effect when the following modes are used: - CW with DDC mode in octal-channel mode - Single and dual-channel mode with DDC. CH0 is the 1st channel selected by CH_ORDER<23:0>. CH(n)_NCO_PHASE<15:0> = 216 x Phase Offset Value/360. DS20005355B-page 102 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER 5-48: R/W-0 R/W-0 ADDRESS 0X87: CH0 NCO PHASE OFFSET IN CW OR DDC MODE (UPPER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH0_NCO_PHASE<15:8> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH0_NCO_PHASE<15:8>: Upper byte of CH0_NCO_PHASE<15:0>(1) 1111-1111 = 359.995° when CH0_NCO_PHASE<15:0> = 0xFFFF ••• 0000-0000 = 0° when CH0_NCO_PHASE<15:0> = 0x0000 (Default) bit 7-0 Note x = Bit is unknown 1: See Note 1 - Note 3 in Register 5-47. REGISTER 5-49: R/W-0 R/W-0 ADDRESS 0X88 – CH1 NCO PHASE OFFSET IN CW OR DDC MODE (LOWER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH1_NCO_PHASE<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH1_NCO_PHASE<7:0>: Lower byte of CH1_NCO_PHASE<15:0>(1) 1111-1111 = 1.4° when CH1_NCO_PHASE<15:0> = 0x00FF ••• 0000-0000 = 0° when CH1_NCO_PHASE<15:0> = 0x0000 (Default) bit 7-0 Note x = Bit is unknown 1: See Note 1 - Note 3 in Register 5-47. CH1 is the 2nd channel selected by CH_ORDER<23:0> bits. REGISTER 5-50: R/W-0 R/W-0 ADDRESS 0X89 – CH1 NCO PHASE OFFSET IN CW OR DDC MODE (UPPER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH1_NCO_PHASE<15:8> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH1_NCO_PHASE <15:8>: Upper byte of CH1_NCO_PHASE<15:0>(1) 1111-1111 = 359.995° when CH1_NCO_PHASE<15:0> = 0xFFFF ••• 0000-0000 = 0° when CH1_NCO_PHASE<15:0> = 0x0000 (Default) bit 7-0 Note x = Bit is unknown 1: See Note 1 - Note 3 in Register 5-47. CH1 is the 2nd channel selected by CH_ORDER<23:0> bits. 2014-2015 Microchip Technology Inc. DS20005355B-page 103 MCP37211-200 AND MCP37D11-200 REGISTER 5-51: R/W-0 R/W-0 ADDRESS 0X8A – CH2 NCO PHASE OFFSET IN CW OR DDC MODE (LOWER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH2_NCO_PHASE<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH2_NCO_PHASE<7:0>: Lower byte of CH2_NCO_PHASE<15:0>(1) 1111-1111 = 1.4° when CH2_NCO_PHASE<15:0> = 0x00FF ••• 0000-0000 = 0° when CH2_NCO_PHASE<15:0> = 0x0000 (Default) bit 7-0 Note x = Bit is unknown 1: See Note 1 - Note 3 in Register 5-47. CH2 is the 3rd channel selected by CH_ORDER<23:0> bits. REGISTER 5-52: R/W-0 R/W-0 ADDRESS 0X8B – CH2 NCO PHASE OFFSET IN CW OR DDC MODE (UPPER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH2_NCO_PHASE<15:8> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH2_NCO_PHASE <15:8>: Upper byte of CH2_NCO_PHASE<15:0>(1) 1111-1111 = 359.995° when CH2_NCO_PHASE<15:0> = 0xFFFF ••• 0000-0000 = 0° when CH2_NCO_PHASE<15:0> = 0x0000 (Default) bit 7-0 Note x = Bit is unknown 1: See Note 1 - Note 3 in Register 5-47. CH2 is the 3rd channel selected by CH_ORDER<23:0> bits. REGISTER 5-53: R/W-0 R/W-0 ADDRESS 0X8C – CH3 NCO PHASE OFFSET IN CW OR DDC MODE (LOWER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH3_NCO_PHASE<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH3_NCO_PHASE<7:0>: Lower byte of CH3_NCO_PHASE<15:0>(1) 1111-1111 = 1.4° when CH3_NCO_PHASE<15:0> = 0x00FF ••• 0000-0000 = 0° when CH3_NCO_PHASE<15:0> = 0x0000 (Default) bit 7-0 Note x = Bit is unknown 1: See Note 1 - Note 3 in Register 5-47. CH3 is the 4th channel selected by CH_ORDER<23:0> bits. DS20005355B-page 104 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER 5-54: R/W-0 ADDRESS 0X8D – CH3 NCO PHASE OFFSET IN CW OR DDC MODE (UPPER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH3_NCO_PHASE<15:8> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH3_NCO_PHASE <15:8>: Upper byte of CH3_NCO_PHASE<15:0>(1) 1111-1111 = 359.995° when CH3_NCO_PHASE<15:0> = 0xFFFF ••• 0000-0000 = 0° when CH3_NCO_PHASE<15:0> = 0x0000 (Default) bit 7-0 Note x = Bit is unknown 1: See Note 1 - Note 3 in Register 5-47. CH3 is the 4th channel selected by CH_ORDER<23:0> bits. REGISTER 5-55: R/W-0 ADDRESS 0X8E – CH4 NCO PHASE OFFSET IN CW OR DDC MODE (LOWER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH4_NCO_PHASE<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH4_NCO_PHASE<7:0>: Lower byte of CH4_NCO_PHASE<15:0>(1) 1111-1111 = 1.4° when CH4_NCO_PHASE<15:0> = 0x00FF ••• 0000-0000 = 0° when CH4_NCO_PHASE<15:0> = 0x0000 (Default) bit 7-0 Note x = Bit is unknown 1: See Note 1 - Note 3 in Register 5-47. CH4 is the 5th channel selected by CH_ORDER<23:0> bits. REGISTER 5-56: R/W-0 ADDRESS 0X8F – CH4 NCO PHASE OFFSET IN CW OR DDC MODE (UPPER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH4_NCO_PHASE<15:8> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH4_NCO_PHASE <15:8>: Upper byte of CH4_NCO_PHASE<15:0>(1) 1111-1111 = 359.995° when CH4_NCO_PHASE<15:0> = 0xFFFF ••• 0000-0000 = 0° when CH4_NCO_PHASE<15:0> = 0x0000 (Default) bit 7-0 Note x = Bit is unknown 1: See Note 1 - Note 3 in Register 5-47. CH4 is the 5th channel selected by CH_ORDER<23:0> bits. 2014-2015 Microchip Technology Inc. DS20005355B-page 105 MCP37211-200 AND MCP37D11-200 REGISTER 5-57: R/W-0 ADDRESS 0X90 – CH5 NCO PHASE OFFSET IN CW OR DDC MODE (LOWER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH5_NCO_PHASE<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH5_NCO_PHASE<7:0>: Lower byte of CH5_NCO_PHASE<15:0>(1) 1111-1111 = 1.4° when CH5_NCO_PHASE<15:0> = 0x00FF ••• 0000-0000 = 0° when CH5_NCO_PHASE<15:0> = 0x0000 (Default) bit 7-0 Note x = Bit is unknown 1: See Note 1 - Note 3 in Register 5-47. CH5 is the 6th channel selected by CH_ORDER<23:0> bits. REGISTER 5-58: R/W-0 ADDRESS 0X91 – CH5 NCO PHASE OFFSET IN CW OR DDC MODE (UPPER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH5_NCO_PHASE<15:8> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH5_NCO_PHASE <15:8>: Upper byte of CH5_NCO_PHASE<15:0>(1) 1111-1111 = 359.995° when CH5_NCO_PHASE<15:0> = 0xFFFF ••• 0000-0000 = 0° when CH5_NCO_PHASE<15:0> = 0x0000 (Default) bit 7-0 Note x = Bit is unknown 1: See Note 1 - Note 3 in Register 5-47. CH5 is the 6th channel selected by CH_ORDER<23:0> bits. REGISTER 5-59: R/W-0 ADDRESS 0X92 – CH6 NCO PHASE OFFSET IN CW OR DDC MODE (LOWER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH6_NCO_PHASE<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH6_NCO_PHASE<7:0>: Lower byte of CH6_NCO_PHASE<15:0>(1) 1111-1111 = 1.4° when CH6_NCO_PHASE<15:0> = 0x00FF ••• 0000-0000 = 0° when CH6_NCO_PHASE<15:0> = 0x0000 (Default) bit 7-0 Note x = Bit is unknown 1: See Note 1 - Note 3 in Register 5-47. CH6 is the 7th channel selected by CH_ORDER<23:0> bits. DS20005355B-page 106 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER 5-60: R/W-0 ADDRESS 0X93 – CH6 NCO PHASE OFFSET IN CW OR DDC MODE (UPPER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH6_NCO_PHASE<15:8> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH6_NCO_PHASE <15:8>: Upper byte of CH6_NCO_PHASE<15:0>(1) 1111-1111 = 359.995° when CH6_NCO_PHASE<15:0> = 0xFFFF ••• 0000-0000 = 0° when CH6_NCO_PHASE<15:0> = 0x0000 (Default) bit 7-0 Note x = Bit is unknown 1: See Note 1 - Note 3 in Register 5-47. CH6 is the 7th channel selected by CH_ORDER<23:0> bits. REGISTER 5-61: R/W-0 ADDRESS 0X94 – CH7 NCO PHASE OFFSET IN CW OR DDC MODE (LOWER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH7_NCO_PHASE<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH7_NCO_PHASE<7:0>: Lower byte of CH7_NCO_PHASE<15:0>(1) 1111-1111 = 1.4° when CH7_NCO_PHASE<15:0> = 0x00FF ••• 0000-0000 = 0° when CH7_NCO_PHASE<15:0> = 0x0000 (Default) bit 7-0 Note x = Bit is unknown 1: See Note 1 - Note 3 in Register 5-47. CH7 is the 8th channel selected by CH_ORDER<23:0> bits. REGISTER 5-62: R/W-0 ADDRESS 0X95 – CH7 NCO PHASE OFFSET IN CW OR DDC MODE (UPPER BYTE) R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH7_NCO_PHASE<15:8> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared bit 7-0 Note 1: x = Bit is unknown CH7_NCO_PHASE <15:8>: Upper byte of CH7_NCO_PHASE<15:0>(1) 1111-1111 = 359.995° when CH7_NCO_PHASE<15:0> = 0xFFFF ••• 0000-0000 = 0° when CH7_NCO_PHASE<15:0> = 0x0000 (Default) See Note 1 - Note 3 in Register 5-47. CH7 is the 8th channel selected by CH_ORDER<23:0> bits. 2014-2015 Microchip Technology Inc. DS20005355B-page 107 MCP37211-200 AND MCP37D11-200 REGISTER 5-63: R/W-0 R/W-0 ADDRESS 0X96 – CH0 DIGITAL GAIN R/W-1 R/W-1 R/W-1 R/W-1 R/W-0 R/W-0 CH0_DIG_GAIN<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH0_DIG_GAIN<7:0>: Digital gain setting for channel 0(1,2) 1111-1111 = -0.03125 1111-1110 = -0.0625 1111-1101 = -0.09375 1111-1100 = -0.125 ••• 1000-0011 = -3.90625 1000-0010 = -3.9375 1000-0001 = -3.96875 1000-0000 = -4 0111-1111 = 3.96875 (MAX) 0111-1110 = 3.9375 0111-1101 = 3.90625 0111-1100 = 3.875 ••• 0011-1100 = 1.875 (Default) ••• 0000-0011 = 0.09375 0000-0010 = 0.0625 0000-0001 = 0.03125 0000-0000 = 0.0 bit 7-0 Note x = Bit is unknown 1: 2: CH0 is the 1st channel selected by CH_ORDER<23:0>. Max = 0x7F(3.96875), Min = 0x80 (-4), Step size = 0x01 (0.03125). Bits from 0x81-0xFF are two’s complementary of 0x000x80. Negative gain setting inverts output. See Addresses 0x7D - 0x7F (Registers 5-38 – 5-40) for channel selection. DS20005355B-page 108 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER 5-64: R/W-0 R/W-0 ADDRESS 0X97 – CH1 DIGITAL GAIN R/W-1 R/W-1 R/W-1 R/W-1 R/W-0 R/W-0 CH1_DIG_GAIN<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH1_DIG_GAIN<7:0>: Digital gain setting for channel 1(1,2) 1111-1111 = -0.03125 1111-1110 = -0.0625 1111-1101 = -0.09375 1111-1100 = -0.125 ••• 1000-0011 = -3.90625 1000-0010 = -3.9375 1000-0001 = -3.96875 1000-0000 = -4 0111-1111 = 3.96875 (MAX) 0111-1110 = 3.9375 0111-1101 = 3.90625 0111-1100 = 3.875 ••• 0011-1100 = 1.875 (Default) ••• 0000-0011 = 0.09375 0000-0010 = 0.0625 0000-0001 = 0.03125 0000-0000 = 0.0 bit 7-0 Note x = Bit is unknown 1: 2: CH1 is the 2nd channel selected by CH_ORDER<23:0>. See Note 2 in Register 5-63. 2014-2015 Microchip Technology Inc. DS20005355B-page 109 MCP37211-200 AND MCP37D11-200 REGISTER 5-65: R/W-0 R/W-0 ADDRESS 0X98 – CH2 DIGITAL GAIN R/W-1 R/W-1 R/W-1 R/W-1 R/W-0 R/W-0 CH2_DIG_GAIN<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH2_DIG_GAIN<7:0>: Digital gain setting for channel 2(1,2) 1111-1111 = -0.03125 1111-1110 = -0.0625 1111-1101 = -0.09375 1111-1100 = -0.125 ••• 1000-0011 = -3.90625 1000-0010 = -3.9375 1000-0001 = -3.96875 1000-0000 = -4 0111-1111 = 3.96875 (MAX) 0111-1110 = 3.9375 0111-1101 = 3.90625 0111-1100 = 3.875 ••• 0011-1100 = 1.875 (Default) ••• 0000-0011 = 0.09375 0000-0010 = 0.0625 0000-0001 = 0.03125 0000-0000 = 0.0 bit 7-0 Note x = Bit is unknown 1: 2: CH2 is the 3rd channel selected by CH_ORDER<23:0> bits. See Note 2 in Register 5-63. DS20005355B-page 110 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER 5-66: R/W-0 R/W-0 ADDRESS 0X99 – CH3 DIGITAL GAIN R/W-1 R/W-1 R/W-1 R/W-1 R/W-0 R/W-0 CH3_DIG_GAIN<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared bit 7-0 Note 1: 2: x = Bit is unknown CH3_DIG_GAIN<7:0>: Digital gain setting for channel 3(1,2) 1111-1111 = -0.03125 1111-1110 = -0.0625 1111-1101 = -0.09375 1111-1100 = -0.125 ••• 1000-0011 = -3.90625 1000-0010 = -3.9375 1000-0001 = -3.96875 1000-0000 = -4 0111-1111 = 3.96875 (MAX) 0111-1110 = 3.9375 0111-1101 = 3.90625 0111-1100 = 3.875 ••• 0011-1100 = 1.875 (Default) ••• 0000-0011 = 0.09375 0000-0010 = 0.0625 0000-0001 = 0.03125 0000-0000 = 0.0 CH3 is the 4th channel selected by CH_ORDER<23:0> bits. See Note 2 in Register 5-63. 2014-2015 Microchip Technology Inc. DS20005355B-page 111 MCP37211-200 AND MCP37D11-200 REGISTER 5-67: R/W-0 R/W-0 ADDRESS 0X9A – CH4 DIGITAL GAIN R/W-1 R/W-1 R/W-1 R/W-1 R/W-0 R/W-0 CH4_DIG_GAIN<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH4_DIG_GAIN<7:0>: Digital gain setting for channel 4(1,2) 1111-1111 = -0.03125 1111-1110 = -0.0625 1111-1101 = -0.09375 1111-1100 = -0.125 ••• 1000-0011 = -3.90625 1000-0010 = -3.9375 1000-0001 = -3.96875 1000-0000 = -4 0111-1111 = 3.96875 (MAX) 0111-1110 = 3.9375 0111-1101 = 3.90625 0111-1100 = 3.875 ••• 0011-1100 = 1.875 (Default) ••• 0000-0011 = 0.09375 0000-0010 = 0.0625 0000-0001 = 0.03125 0000-0000 = 0.0 bit 7-0 Note x = Bit is unknown 1: 2: CH4 is the 5th channel selected by CH_ORDER<23:0>. See Note 2 in Register 5-63. DS20005355B-page 112 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER 5-68: R/W-0 ADDRESS 0X9B – CH5 DIGITAL GAIN R/W-0 R/W-1 R/W-1 R/W-1 R/W-1 R/W-0 R/W-0 CH5_DIG_GAIN<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH5_DIG_GAIN<7:0>: Digital gain setting for channel 5(1,2) 1111-1111 = -0.03125 1111-1110 = -0.0625 1111-1101 = -0.09375 1111-1100 = -0.125 ••• 1000-0011 = -3.90625 1000-0010 = -3.9375 1000-0001 = -3.96875 1000-0000 = -4 0111-1111 = 3.96875 (MAX) 0111-1110 = 3.9375 0111-1101 = 3.90625 0111-1100 = 3.875 ••• 0011-1100 = 1.875 (Default) ••• 0000-0011 = 0.09375 0000-0010 = 0.0625 0000-0001 = 0.03125 0000-0000 = 0.0 bit 7-0 Note x = Bit is unknown 1: 2: CH5 is the 6th channel selected by CH_ORDER<23:0>. See Note 2 in Register 5-63. 2014-2015 Microchip Technology Inc. DS20005355B-page 113 MCP37211-200 AND MCP37D11-200 REGISTER 5-69: R/W-0 R/W-0 ADDRESS 0X9C – CH6 DIGITAL GAIN R/W-1 R/W-1 R/W-1 R/W-1 R/W-0 R/W-0 CH6_DIG_GAIN<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH6_DIG_GAIN<7:0>: Digital gain setting for channel 6(1,2) 1111-1111 = -0.03125 1111-1110 = -0.0625 1111-1101 = -0.09375 1111-1100 = -0.125 ••• 1000-0011 = -3.90625 1000-0010 = -3.9375 1000-0001 = -3.96875 1000-0000 = -4 0111-1111 = 3.96875 (MAX) 0111-1110 = 3.9375 0111-1101 = 3.90625 0111-1100 = 3.875 ••• 0011-1100 = 1.875 (Default) ••• 0000-0011 = 0.09375 0000-0010 = 0.0625 0000-0001 = 0.03125 0000-0000 = 0.0 bit 7-0 Note x = Bit is unknown 1: 2: CH6 is the 7th channel selected by CH_ORDER<23:0>. See Note 2 in Register 5-63. DS20005355B-page 114 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER 5-70: R/W-0 ADDRESS 0X9D – CH7 DIGITAL GAIN R/W-0 R/W-1 R/W-1 R/W-1 R/W-1 R/W-0 R/W-0 CH7_DIG_GAIN<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH7_DIG_GAIN<7:0>: Digital gain setting for channel 7(1,2) 1111-1111 = -0.03125 1111-1110 = -0.0625 1111-1101 = -0.09375 1111-1100 = -0.125 ••• 1000-0011 = -3.90625 1000-0010 = -3.9375 1000-0001 = -3.96875 1000-0000 = -4 0111-1111 = 3.96875 (MAX) 0111-1110 = 3.9375 0111-1101 = 3.90625 0111-1100 = 3.875 ••• 0011-1100 = 1.875 (Default) ••• 0000-0011 = 0.09375 0000-0010 = 0.0625 0000-0001 = 0.03125 0000-0000 = 0.0 bit 7-0 Note x = Bit is unknown 1: 2: CH7 is the 8th channel selected by CH_ORDER<23:0>. See Note 2 in Register 5-63. 2014-2015 Microchip Technology Inc. DS20005355B-page 115 MCP37211-200 AND MCP37D11-200 REGISTER 5-71: R/W-0 R/W-0 ADDRESS 0X9E – CH0 DIGITAL OFFSET R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH0_DIG_OFFSET<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH0_DIG_OFFSET <7:0>: Digital offset setting bits for channel 0(1) 1111-1111 = 0xFF x DIG_OFFSET_WEIGHT<1:0> ••• 0000-0001 = 0x01 x DIG_OFFSET_WEIGHT<1:0> 0000-0000 = 0 (Default) bit 7-0 Note x = Bit is unknown 1: See Table 4-21 for the corresponding channel. Offset value is two’s complement. This value is multiplied by DIG_OFFSET_WEIGHT<1:0> in Address 0xA7 (Register 5-79). REGISTER 5-72: R/W-0 R/W-0 ADDRESS 0X9F – CH1 DIGITAL OFFSET R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH1_DIG_OFFSET<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH1_DIG_OFFSET <7:0>: Digital offset setting bits for channel 1(1) 1111-1111 = 0xFF x DIG_OFFSET_WEIGHT<1:0> ••• 0000-0001 = 0x01 x DIG_OFFSET_WEIGHT<1:0> 0000-0000 = 0 (Default) bit 7-0 Note x = Bit is unknown 1: See Note 1 in Register 5-71. REGISTER 5-73: R/W-0 R/W-0 ADDRESS 0XA0 – CH2 DIGITAL OFFSET R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH2_DIG_OFFSET<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH2_DIG_OFFSET <7:0>: Digital offset setting bits for channel 2(1) 1111-1111 = 0xFF x DIG_OFFSET_WEIGHT<1:0> ••• 0000-0001 = 0x01 x DIG_OFFSET_WEIGHT<1:0> 0000-0000 = 0 (Default) bit 7-0 Note x = Bit is unknown 1: See Note 1 in Register 5-71. DS20005355B-page 116 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER 5-74: R/W-0 R/W-0 ADDRESS 0XA1 – CH3 DIGITAL OFFSET R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH3_DIG_OFFSET<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH3_DIG_OFFSET <7:0>: Digital offset setting bits for channel 3(1) 1111-1111 = 0xFF x DIG_OFFSET_WEIGHT<1:0> ••• 0000-0001 = 0x01 x DIG_OFFSET_WEIGHT<1:0> 0000-0000 = 0 (Default) bit 7-0 Note x = Bit is unknown 1: See Note 1 in Register 5-71. REGISTER 5-75: R/W-0 R/W-0 ADDRESS 0XA2 – CH4 DIGITAL OFFSET R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH4_DIG_OFFSET<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared bit 7-0 Note 1: x = Bit is unknown CH4_DIG_OFFSET <7:0>: Digital offset setting bits for channel 4(1) 1111-1111 = 0xFF x DIG_OFFSET_WEIGHT<1:0> ••• 0000-0001 = 0x01 x DIG_OFFSET_WEIGHT<1:0> 0000-0000 = 0 (Default) See Note 1 in Register 5-71. REGISTER 5-76: R/W-0 R/W-0 ADDRESS 0XA3 – CH5 DIGITAL OFFSET R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH5_DIG_OFFSET<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared bit 7-0 Note 1: x = Bit is unknown CH5_DIG_OFFSET <7:0>: Digital offset setting bits for channel 5(1) 1111-1111 = 0x01 x DIG_OFFSET_WEIGHT<1:0> ••• 0000-0001 = 0xFF x DIG_OFFSET_WEIGHT<1:0> 0000-0000 = 0 (Default) See Note 1 in Register 5-71. 2014-2015 Microchip Technology Inc. DS20005355B-page 117 MCP37211-200 AND MCP37D11-200 REGISTER 5-77: R/W-0 ADDRESS 0XA4 – CH6 DIGITAL OFFSET R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH6_DIG_OFFSET<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH6_DIG_OFFSET <7:0>: Digital offset setting bits for channel 6(1) 1111-1111 = 0xFF x DIG_OFFSET_WEIGHT<1:0> ••• 0000-0001 = 0x01 x DIG_OFFSET_WEIGHT<1:0> 0000-0000 = 0 (Default) bit 7-0 Note x = Bit is unknown 1: See Note 1 in Register 5-71. REGISTER 5-78: R/W-0 ADDRESS 0XA5 – CH7 DIGITAL OFFSET R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 CH7_DIG_OFFSET<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CH7_DIG_OFFSET <7:0>: Digital offset setting bits for channel 7(1) 1111-1111 = 0xFF x DIG_OFFSET_WEIGHT<1:0> ••• 0000-0001 = 0x01 x DIG_OFFSET_WEIGHT<1:0> 0000-0000 = 0 (Default) bit 7-0 Note x = Bit is unknown 1: See Note 1 in Register 5-71. REGISTER 5-79: R/W-0 ADDRESS 0XA7 – DIGITAL OFFSET WEIGHT CONTROL R/W-1 R/W-0 FCB<5:3> R/W-0 R/W-0 R/W-1 DIG_OFFSET_WEIGHT<1:0> R/W-1 R/W-1 FCB<2:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7-5 FCB<5:3>: Factory-Controlled bits. This is not for the user. Do not change default settings. bit 4-3 DIG_OFFSET_WEIGHT<1:0>: Control the weight of the digital offset settings(1) 11 = 2 LSb x Digital Gain 10 = LSb x Digital Gain 01 = LSb/2 x Digital Gain 00 = LSb/4 x Digital Gain, (Default) bit 2-0 FCB<2:0>: Factory-Controlled bits. This is not for the user. Do not change default settings. Note 1: This bit setting is used for the digital offset setting registers in Addresses 0x9E - 0xA7 (Registers 5-71 – 5-79). DS20005355B-page 118 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 REGISTER 5-80: R-0 ADDRESS 0XC0 – CALIBRATION STATUS INDICATION R-0 R-0 R-0 R-0 R-0 R-0 R-0 FCB<6:0> ADC_CAL_STAT bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7 ADC_CAL_STAT: Power-up auto-calibration status indication flag bit 1 = Device power-up calibration is completed 0 = Device power-up calibration is not completed bit 6-0 FCB<6:0>: Factory-Controlled bits. These bits are read only, and have no meaning for the user. REGISTER 5-81: R-x R-x FCB<4:3> ADDRESS 0XD1 – PLL CALIBRATION STATUS AND PLL DRIFT STATUS INDICATION R-x PLL_CAL_STAT R-x R-x FCB<2:1> R-x R-x R-x PLL_VCOL_STAT PLL_VCOH_STAT FCB<0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared x = Bit is unknown bit 7-6 FCB<4:3>: Factory-Controlled bits. These bits are read only, and have no meaning for the user. bit 5 PLL_CAL_STAT: PLL auto-calibration status indication flag bit(1) 1= Complete: PLL auto-calibration is completed 0= Incomplete: PLL auto-calibration is not completed bit 4-3 FCB<2:1>: Factory-Controlled bits. These bits are read only, and have no meaning for the user. bit 2 PLL_VCOL_STAT: PLL drift status indication bit 1 = PLL drifts out of lock with low VCO frequency 0 = PLL operates as normal bit 1 PLL_VCOH_STAT: PLL drift status indication bit 1 = PLL drifts out of lock with high VCO frequency 0 = PLL operates as normal bit 0 Note 1: FCB<0>: Factory-Controlled bit. This bit is readable, but has no meaning for the user. See PLL_CAL_TRIG bit setting in Address 0x6B (Register 5-27). 2014-2015 Microchip Technology Inc. DS20005355B-page 119 MCP37211-200 AND MCP37D11-200 REGISTER 5-82: R-x ADDRESS 0X15C – CHIP ID (LOWER BYTE) R-x R-x R-x R-x R-x R-x R-x CHIP_ID<7:0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CHIP_ID<7:0>: Device identification number. Lower byte of the CHIP ID<15:0>(1) bit 7-0 Note x = Bit is unknown 1: Read-only register. Preprogrammed at the factory for internal use. Example: MCP37211-200: ‘0000 1000 0011 0000’ MCP37D11-200: ‘0000 1010 0011 0000’ REGISTER 5-83: R-x ADDRESS 0X15D – CHIP ID (UPPER BYTE) R-x R-x R-x R-x R-x R-x R-x CHIP_ID<15:8> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared CHIP_ID<15:8>: Device identification number. Lower byte of the CHIP ID<15:0>(1) bit 7-0 Note x = Bit is unknown 1: See Note 1 in Register 5-82. DS20005355B-page 120 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 6.0 DEVELOPMENT SUPPORT Microchip offers a high-speed ADC evaluation platform which can be used to evaluate Microchip’s high-speed ADC products. The platform consists of an MCP37XXX evaluation board, an FPGA-based data capture card board, and PC-based Graphical User Interface (GUI) software for ADC configuration and evaluation. Figure 6-1 and Figure 6-2 show this evaluation tool. This evaluation platform allows users to quickly evaluate the ADC’s performance for their specific application requirements. More information is available at http://www.microchip.com. (a) MCP37XXX-200 Evaluation Board FIGURE 6-1: MCP37XXX Evaluation Kit. FIGURE 6-2: PC-Based Graphical User Interface Software. 2014-2015 Microchip Technology Inc. (b) Data Capture Board DS20005355B-page 121 MCP37211-200 AND MCP37D11-200 NOTES: DS20005355B-page 122 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 7.0 TERMINOLOGY Analog Input Bandwidth (Full-Power Bandwidth) The analog input frequency at which the spectral power of the fundamental frequency (as determined by FFT analysis) is reduced by 3 dB. Aperture Delay or Sampling Delay This is the time delay between the rising edge of the input sampling clock and the actual time at which the sampling occurs. Aperture Uncertainty The sample-to-sample variation in aperture delay. Aperture Delay Jitter The variation in the aperture delay time from conversion to conversion. This random variation will result in noise when sampling an AC input. The signal-to-noise ratio due to the jitter alone will be: EQUATION 7-1: SNR JITTER = – 20 log 2 f IN t JITTER Calibration Algorithms This device utilizes two patented analog and digital calibration algorithms, Harmonic Distortion Correction (HDC) and DAC Noise Cancellation (DNC), to improve the ADC performance. The algorithms compensate various sources of linear impairments such as capacitance mismatch, charge injection error and finite gain of operational amplifiers. These algorithms execute in both power-up sequence (foreground) and background mode: • Power-Up Calibration: The calibration is conducted within the first 227 clock cycles after power-up. The user needs to wait this Power-Up Calibration period after the device is powered-up for an accurate ADC performance. • Background Calibration: This calibration is conducted in the background while the ADC performs conversions. The update rate is about every 230 clock cycles. Pipeline Delay (LATENCY) LATENCY is the number of clock cycles between the initiation of conversion and when that data is presented to the output driver stage. Data for any given sample is available after the pipeline delay plus the output delay after that sample is taken. New data is available at every clock cycle, but the data lags the conversion by the pipeline delay plus the output delay. Latency is increased if digital signal post-processing is used. Clock Pulse Width and Duty Cycle The clock duty cycle is the ratio of the time the clock signal remains at a logic high (clock pulse width) to one clock period. Duty cycle is typically expressed as a percentage. A perfect differential sine-wave clock results in a 50% duty cycle. Differential Nonlinearity (DNL, No Missing Codes) An ideal ADC exhibits code transitions that are exactly 1 LSb apart. DNL is the deviation from this ideal value. No missing codes to 12-bit resolution indicates that all 4096 codes must be present over all the operating conditions. Integral Nonlinearity (INL) INL is the maximum deviation of each individual code from an ideal straight line drawn from negative full scale through positive full scale. Signal-to-Noise Ratio (SNR) SNR is the ratio of the power of the fundamental (PS) to the noise floor power (PN), below the Nyquist frequency and excluding the power at DC and the first nine harmonics. EQUATION 7-2: PS SNR = 10 log ------- P N SNR is either given in units of dBc (dB to carrier) when the absolute power of the fundamental is used as the reference, or dBFS (dB to full-scale) when the power of the fundamental is extrapolated to the converter full-scale range. Channel Crosstalk This is a measure of the internal coupling of a signal from an adjacent channel into the channel of interest in the multi-channel mode. It is measured by applying a full-scale input signal in the adjacent channel. Crosstalk is the ratio of the power of the coupling signal (as measured at the output of the channel of interest) to the power of the signal applied at the adjacent channel input. It is typically expressed in dBc. 2014-2015 Microchip Technology Inc. DS20005355B-page 123 MCP37211-200 AND MCP37D11-200 Signal-to-Noise and Distortion (SINAD) Maximum Conversion Rate SINAD is the ratio of the power of the fundamental (PS) to the power of all the other spectral components including noise (PN) and distortion (PD) below the Nyquist frequency, but excluding DC: The maximum clock rate at which parametric testing is performed. EQUATION 7-3: The minimum clock rate at which parametric testing is performed. PS SINAD = 10 log ---------------------- P D + P N = – 10 log 10 SNR – ----------10 – 10 Minimum Conversion Rate Spurious-Free Dynamic Range (SFDR) THD – -----------10 SINAD is either given in units of dBc (dB to carrier) when the absolute power of the fundamental is used as the reference, or dBFS (dB to full-scale) when the power of the fundamental is extrapolated to the converter full-scale range. Effective Number of Bits (ENOB) SFDR is the ratio of the power of the fundamental to the highest other spectral component (either spur or harmonic). SFDR is typically given in units of dBc (dB to carrier) or dBFS. Total Harmonic Distortion (THD) THD is the ratio of the power of the fundamental (PS) to the summed power of the first 13 harmonics (PD). EQUATION 7-5: PS THD = 10 log -------- P D The effective number of bits for a sine wave input at a given input frequency can be calculated directly from its measured SINAD using the following formula: EQUATION 7-4: SINAD – 1.76 ENOB = ---------------------------------6.02 Gain Error Gain error is the deviation of the ADC’s actual input full-scale range from its ideal value. The gain error is given as a percentage of the ideal input full-scale range. Gain error is usually expressed in LSb or as a percentage of full-scale range (%FSR). Gain-Error Drift Gain-error drift is the variation in gain-error due to a change in ambient temperature, typically expressed in ppm/°C. Offset Error The major carry transition should occur for an analog value of 50% LSb below AIN+ = AIN−. Offset error is defined as the deviation of the actual transition from that point. Temperature Drift The temperature drift for offset error and gain error specifies the maximum change from the initial (+25°C) value to the value across the TMIN to TMAX range. DS20005355B-page 124 THD is typically given in units of dBc (dB to carrier). THD is also shown by: EQUATION 7-6: 2 2 2 2 V2 + V3 + V4 + + Vn THD = – 20 log -----------------------------------------------------------------2 V1 Where: V1 = RMS amplitude of the fundamental frequency V1 through Vn = Amplitudes of the second through nth harmonics Two-Tone Intermodulation Distortion (Two-Tone IMD, IMD3) Two-tone IMD is the ratio of the power of the fundamental (at frequencies fIN1 and fIN2) to the power of the worst spectral component at either frequency 2fIN1 – fIN2 or 2fIN2 – fIN1. Two-tone IMD is a function of the input amplitudes and frequencies (fIN1 and fIN2). It is either given in units of dBc (dB to carrier) when the absolute power of the fundamental is used as the reference, or dBFS (dB to full-scale) when the power of the fundamental is extrapolated to the ADC full-scale range. 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 Common-Mode Rejection Ratio (CMRR) Common-mode rejection is the ability of a device to reject a signal that is common to both sides of a differential input pair. The common-mode signal can be an AC or DC signal or a combination of the two. CMRR is measured using the ratio of the differential signal gain to the common-mode signal gain and expressed in dB with the following equation: EQUATION 7-7: Where: A DIFF CMRR = 20 log ------------------ A CM ADIFF = Output Code/Differential Voltage ADIFF = Output Code/Common Mode Voltage 2014-2015 Microchip Technology Inc. DS20005355B-page 125 MCP37211-200 AND MCP37D11-200 NOTES: DS20005355B-page 126 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 8.0 PACKAGING INFORMATION 8.1 Package Marking Information 124-Lead VTLA (9x9x0.9 mm) Example A1 A1 XXXXXXXXXXX XXXXXXXXXXX XXXXXXXXXXX YYWWNNN Legend: XX...X Y YY WW NNN e3 * Note: MCP37211 200-I/TL ^^ e3 1417256 Customer-specific information Year code (last digit of calendar year) Year code (last 2 digits of calendar year) Week code (week of January 1 is week ‘01’) Alphanumeric traceability code Pb-free JEDEC® designator for Matte Tin (Sn) This package is Pb-free. The Pb-free JEDEC designator ( e3 ) can be found on the outer packaging for this package. In the event the full Microchip part number cannot be marked on one line, it will be carried over to the next line, thus limiting the number of available characters for customer-specific information. 2014-2015 Microchip Technology Inc. DS20005355B-page 127 MCP37211-200 AND MCP37D11-200 DS20005355B-page 128 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 2014-2015 Microchip Technology Inc. DS20005355B-page 129 MCP37211-200 AND MCP37D11-200 124-Very Thin Leadless Array Package (TL) – 9x9x0.9 mm Body [VTLA] Note: For the most current package drawings, please see the Microchip Packaging Specification located at http://www.microchip.com/packaging E E/2 G4 X1 X2 G3 E T2 C2 G1 G5 X4 G2 SILK SCREEN W3 W2 C1 RECOMMENDED LAND PATTERN Units Dimension Limits Contact Pitch E Pad Clearance G1 Pad Clearance G2 Pad Clearance G3 Pad Clearance G4 Contact to Center Pad Clearance (X4) G5 Optional Center Pad Width T2 Optional Center Pad Length W2 W3 Optional Center Pad Chamfer (X4) Contact Pad Spacing C1 Contact Pad Spacing C2 Contact Pad Width (X124) X1 Contact Pad Length (X124) X2 MIN MILLIMETERS NOM 0.50 BSC MAX 0.20 0.20 0.20 0.20 0.30 6.60 6.60 0.10 8.50 8.50 0.30 0.30 Notes: 1. Dimensioning and tolerancing per ASME Y14.5M BSC: Basic Dimension. Theoretically exact value shown without tolerances. Microchip Technology Drawing No. C04-2193A DS20005355B-page 130 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 APPENDIX A: REVISION HISTORY Revision B (July 2015) The following is the list of modifications: 1. 2. 3. 4. 5. 6. 7. 8. 9. 10. 11. 12. 13. 14. 15. 16. 17. 18. 19. 20. 21. 22. 23. 24. 25. 26. 27. 28. Updated the Features list. Updated the Functional Block Diagram. Updated the Description section. Updated and added notes in Tables 1-1 and 1-2. Updated values and notes in Tables 2-1 and 2-2. Updated value in Figure 2-1. Updated note in Section 3.0 “Typical Performance Curves”. Updated text title in Figures 3-26 and 3-29. Updated text in Section 4.0 “Theory of Operation”. Updated text in Section 4.5.1 “Analog Input Driving Circuit”. Added new column to Table 4-2. Added Section 4.5.2.1 “SENSE Selection Vs. SNR/SFDR Performance” and Section 4.5.3.1 “Decoupling Circuits for REF1 and REF0 Pins”. Replaced text in Section 4.5.3.1 “Decoupling Circuits for REF1 and REF0 Pins”. Updated values in Figure 4-7. Added note after Figure 4-7. Replaced the entire Section 4.7 “ADC Clock Selection”. Updated text in Section 4.8.1 “Fractional Delay Recovery for Dual- and Octal-Channel Modes”. Updated Figure 4-11. Changed parameters and updated/added notes in Tables 4-5, 4-6, 4-9, 4-10, 4-12, 4-13 and 4-14. Changed value in Equation 4-6. Deleted Note in Section 4.8.3 “Decimation Filters”. Added Section 4.8.3.1 “Output Data Rate and Clock Phase Control When Decimation is Used”. Changed parameter in Table 4-15 and bit names in Tables 4-17, 4-19, 4-20. Replaced and added text and reorganized structure in Section 4.8.4 “Digital DownConversion (MCP37D11-200 only)”. Replaced text in Section 4.8.4.3 “Numerically Controlled Oscillator (NCO)”. Updated values in Section 4.8.4.5 “NCO for fS/ 8 and fS/(8xDER)”. Updated parameters and notes in Tables 416, 4-17, 4-18 and 4-19. Reorganized and added text to Section 4.11 “Output Data format” and Section 4.12 2014-2015 Microchip Technology Inc. 29. 30. 31. 32. 33. 34. 35. “Digital Output”. Updated Figure 4-25. Updated Section 5.2 “Configuration Registers”. Updated Table 5-3. Updated Registers 5-1 to 5-3, 5-7, 5-8, 5-10, 5-11, 5-13, 5-22, 5-24, 5-25, 5-27, 5-28, 5-34, 5-35, 5-36, 5-37, 5-42, 5-43 to 5-46, 5-47, 5-63, 5-79 and 5-80. Deleted “Power Supply Rejection Ration” section from Section 7.0 “Terminology”. Updated Product Identification System. Minor typographical corrections. Revision A (October 2014) • Original Release of this Document. DS20005355B-page 131 MCP37211-200 AND MCP37D11-200 PRODUCT IDENTIFICATION SYSTEM To order or obtain information, e.g., on pricing or delivery, refer to the factory or the listed sales office. PART NO. [X](1) Device Tape and Reel Option Device: -XXX X Sample Temperature Rate Range /XX Package MCP37211-200: 12-Bit Low-Power ADC with 8-Channel MUX MCP37D11-200: 12-Bit Low-Power ADC with 8-Channel MUX, Digital Down-Converter and CW Beamforming Tape and Reel Option: Blank T = Standard packaging (tube or tray) = Tape and Reel(1) Sample Rate 200 = 200 Msps Temperature Range: I = -40C to +85C (Industrial) Package: TL = Examples: a) MCP37211-200I/TL: b) MCP37211T-200I/TL c) MCP37211-200I/TE* a) MCP37D11-200I/TL: b) Terminal Very Thin Leadless Array Package 9x9x0.9 mm Body (VTLA), 124-Lead TE* = Ball Plastic Thin Profile Fine Pitch Ball Grid Array 8x8x1.08 mm Body (TFBGA), 121-Lead * Contact Microchip Technology Inc. for availability. DS20005355B-page 132 c) 200 Msps, Industrial Temperature, 124LD VTLA Package 200 Msps, Tape and Reel Industrial temperature 124LD VTLA Package 200 Msps, Industrial Temperature, 121LD TFBGA Package 200 Msps, Industrial temperature, 124LD VTLA Package MCP37D11T-200I/TL 200 Msps, Tape and Reel Industrial temperature 124LD VTLA Package MCP37D11-200I/TE*: 200 Msps, Industrial Temperature, 121LD TFBGA Package Note 1: Tape and Reel identifier appears only in the catalog part number description. This identifier is used for ordering purposes and is not printed on the device package. Check with your Microchip Sales Office for package availability with the Tape and Reel option. 2014-2015 Microchip Technology Inc. MCP37211-200 AND MCP37D11-200 Note the following details of the code protection feature on Microchip devices: • Microchip products meet the specification contained in their particular Microchip Data Sheet. • Microchip believes that its family of products is one of the most secure families of its kind on the market today, when used in the intended manner and under normal conditions. • There are dishonest and possibly illegal methods used to breach the code protection feature. All of these methods, to our knowledge, require using the Microchip products in a manner outside the operating specifications contained in Microchip’s Data Sheets. Most likely, the person doing so is engaged in theft of intellectual property. • Microchip is willing to work with the customer who is concerned about the integrity of their code. • Neither Microchip nor any other semiconductor manufacturer can guarantee the security of their code. Code protection does not mean that we are guaranteeing the product as “unbreakable.” Code protection is constantly evolving. We at Microchip are committed to continuously improving the code protection features of our products. Attempts to break Microchip’s code protection feature may be a violation of the Digital Millennium Copyright Act. If such acts allow unauthorized access to your software or other copyrighted work, you may have a right to sue for relief under that Act. Information contained in this publication regarding device applications and the like is provided only for your convenience and may be superseded by updates. It is your responsibility to ensure that your application meets with your specifications. MICROCHIP MAKES NO REPRESENTATIONS OR WARRANTIES OF ANY KIND WHETHER EXPRESS OR IMPLIED, WRITTEN OR ORAL, STATUTORY OR OTHERWISE, RELATED TO THE INFORMATION, INCLUDING BUT NOT LIMITED TO ITS CONDITION, QUALITY, PERFORMANCE, MERCHANTABILITY OR FITNESS FOR PURPOSE. Microchip disclaims all liability arising from this information and its use. Use of Microchip devices in life support and/or safety applications is entirely at the buyer’s risk, and the buyer agrees to defend, indemnify and hold harmless Microchip from any and all damages, claims, suits, or expenses resulting from such use. No licenses are conveyed, implicitly or otherwise, under any Microchip intellectual property rights unless otherwise stated. Trademarks The Microchip name and logo, the Microchip logo, dsPIC, FlashFlex, flexPWR, JukeBlox, KEELOQ, KEELOQ logo, Kleer, LANCheck, MediaLB, MOST, MOST logo, MPLAB, OptoLyzer, PIC, PICSTART, PIC32 logo, RightTouch, SpyNIC, SST, SST Logo, SuperFlash and UNI/O are registered trademarks of Microchip Technology Incorporated in the U.S.A. and other countries. The Embedded Control Solutions Company and mTouch are registered trademarks of Microchip Technology Incorporated in the U.S.A. Analog-for-the-Digital Age, BodyCom, chipKIT, chipKIT logo, CodeGuard, dsPICDEM, dsPICDEM.net, ECAN, In-Circuit Serial Programming, ICSP, Inter-Chip Connectivity, KleerNet, KleerNet logo, MiWi, MPASM, MPF, MPLAB Certified logo, MPLIB, MPLINK, MultiTRAK, NetDetach, Omniscient Code Generation, PICDEM, PICDEM.net, PICkit, PICtail, RightTouch logo, REAL ICE, SQI, Serial Quad I/O, Total Endurance, TSHARC, USBCheck, VariSense, ViewSpan, WiperLock, Wireless DNA, and ZENA are trademarks of Microchip Technology Incorporated in the U.S.A. and other countries. SQTP is a service mark of Microchip Technology Incorporated in the U.S.A. Silicon Storage Technology is a registered trademark of Microchip Technology Inc. in other countries. GestIC is a registered trademarks of Microchip Technology Germany II GmbH & Co. KG, a subsidiary of Microchip Technology Inc., in other countries. All other trademarks mentioned herein are property of their respective companies. © 2014-2015, Microchip Technology Incorporated, Printed in the U.S.A., All Rights Reserved. ISBN: 978-1-63277-616-7 QUALITYMANAGEMENTSYSTEM CERTIFIEDBYDNV == ISO/TS16949== 2014-2015 Microchip Technology Inc. Microchip received ISO/TS-16949:2009 certification for its worldwide headquarters, design and wafer fabrication facilities in Chandler and Tempe, Arizona; Gresham, Oregon and design centers in California and India. The Company’s quality system processes and procedures are for its PIC® MCUs and dsPIC® DSCs, KEELOQ® code hopping devices, Serial EEPROMs, microperipherals, nonvolatile memory and analog products. In addition, Microchip’s quality system for the design and manufacture of development systems is ISO 9001:2000 certified. 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