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EL2227
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Data
September 14 ,2010
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T
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8
1-88
Dual, Very Low Noise Amplifier
Features
The EL2227 is a dual, low-noise amplifier, ideally suited to
line receiving applications in ADSL and HDSLII designs.
With low noise specification of just 1.9nV/Hz and
1.2pA/Hz, the EL2227 is perfect for the detection of very
low amplitude signals.
• Voltage noise of only 1.9nV/Hz
The EL2227 features a -3dB bandwidth of 115MHz and is
gain-of-2 stable. The EL2227 also affords minimal power
dissipation with a supply current of just 4.8mA per amplifier.
The amplifier can be powered from supplies ranging from
±2.5V to ±12V.
• Just 4.8mA per amplifier
• Current noise of only 1.2pA/Hz
• Bandwidth (-3dB) of 115MHz @AV = +2
• Gain-of-2 stable
• 8 Ld MSOP and 8 Ld SOIC package
• ±2.5V to ±12V operation
• Pb-free available (RoHS compliant)
The EL2227 is available in a space-saving 8 Ld MSOP
package as well as the industry-standard 8 Ld SOIC. It can
operate over the -40°C to +85°C temperature range.
Applications
Pinout
• HDSLII receivers
1
VINA-
2
• ADSL receivers
• Ultrasound input amplifiers
EL2227
(8 LD SOIC, 8 LD MSOP)
TOP VIEW
VOUTA
FN7058.4
• Wideband instrumentation
8
VS+
7
VOUTB
6
VINB-
5
VINB+
• Communications equipment
• AGC and PLL active filters
+
VINA+
3
+
VS-
4
• Wideband sensors
.
Ordering Information
PART
NUMBER
PART
MARKING
TEMP
RANGE
(°C)
PACKAGE
PKG.
DWG.#
EL2227CYZ* BASAA
(Note)
-40 to +85 8 Ld MSOP
M8.118A
(3.0mm) (Pb-free)
EL2227CS*
-40 to +85 8 Ld SOIC
(150 mil)
2227CS
EL2227CSZ* 2227CSZ
(Note)
M8.15E
-40 to +85 8 Ld SOIC
M8.15E
(150 mil) (Pb-free)
*Add “-T7” or “-T13” suffix for tape and reel. Please refer to TB347 for
details on reel specifications.
NOTE: These Intersil Pb-free plastic packaged products employ
special Pb-free material sets, molding compounds/die attach
materials, and 100% matte tin plate plus anneal (e3 termination
finish, which is RoHS compliant and compatible with both SnPb and
Pb-free soldering operations). Intersil Pb-free products are MSL
classified at Pb-free peak reflow temperatures that meet or exceed
the Pb-free requirements of IPC/JEDEC J STD-020.
1
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or 1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc.
Copyright Intersil Americas Inc. 2004, 2005, 2007, 2010. All Rights Reserved
All other trademarks mentioned are the property of their respective owners.
EL2227
Absolute Maximum Ratings
Thermal Information
Supply Voltage between VS+ and VS- . . . . . . . . . . . . . . . . . . . . .28V
Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . VS- - 0.3V, VS +0.3V
Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 40mA
Maximum Die Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . +150°C
ESD Voltage. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .2kV
Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C
Operating Temperature . . . . . . . . . . . . . . . . . . . . . . .-40°C to +85°C
Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves
Pb-Free Reflow Profile. . . . . . . . . . . . . . . . . . . . . . . . .see link below
http://www.intersil.com/pbfree/Pb-FreeReflow.asp
CAUTION: Do not operate at or near the maximum ratings listed for extended periods of time. Exposure to such conditions may adversely impact product reliability and
result in failures not covered by warranty.
IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests
are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA
Electrical Specifications
VS+ = +12V, VS- = -12V, RL = 500 and CL = 3pF to 0V, RF = RG = 620, and TA = +25°C, Unless Otherwise
Specified.
PARAMETER
DESCRIPTION
CONDITION
MIN
TYP
MAX
UNIT
-0.2
3
mV
INPUT CHARACTERISTICS
VOS
Input Offset Voltage
TCVOS
Average Offset Voltage Drift
IB
Input Bias Current
RIN
VCM = 0V
-0.6
µV/°C
-3.4
µA
Input Impedance
7.3
M
CIN
Input Capacitance
1.6
pF
CMIR
Common-Mode Input Range
CMRR
Common-Mode Rejection Ratio
For VIN from -11.8V to 10.4V
60
94
dB
AVOL
Open-Loop Gain
-5V VOUT 5V
70
87
dB
eN
Voltage Noise
f = 100kHz
1.9
nV/Hz
iN
Current Noise
f = 100kHz
1.2
pA/Hz
RL = 500
-10.4
-10
V
RL = 250
-9.8
-9
V
VCM = 0V
-9
-11.8
+10.4
V
OUTPUT CHARACTERISTICS
VOL
Output Swing Low
VOH
Output Swing High
RL = 500
RL = 250
9.5
10
V
ISC
Short Circuit Current
RL = 10
140
180
mA
65
95
dB
10
10.4
V
POWER SUPPLY PERFORMANCE
PSRR
Power Supply Rejection Ratio
VS is moved from ±2.25V to ±12V
IS
Supply Current (Per Amplifier)
No Load
VS
Operating Range
4.8
±2.5
6.5
mA
±12
V
DYNAMIC PERFORMANCE
SR
Slew Rate (Note 2)
±2.5V square wave, measured 25% to 75%
50
V/µs
tS
Settling to 0.1% (AV = +2)
(AV = +2), VO = ±1V
65
ns
BW
-3dB Bandwidth
RF = 358
115
MHz
HD2
2nd Harmonic Distortion
f = 1MHz, VO = 2VP-P, RL = 500, RF = 358
93
dBc
f = 1MHz, VO = 2VP-P, RL = 150, RF = 358
83
dBc
f = 1MHz, VO = 2VP-P, RL = 500, RF = 358
94
dBc
f = 1MHz, VO = 2VP-P, RL = 150, RF = 358
76
dBc
HD3
3rd Harmonic Distortion
2
40
FN7058.4
September 14 ,2010
EL2227
Electrical Specifications
VS+ = +5V, VS- = -5V, RL = 500 and CL = 3pF to 0V, RF = RG = 620, and TA = +25°C, Unless Otherwise
Specified.
PARAMETER
DESCRIPTION
CONDITION
MIN
TYP
MAX
UNIT
0.2
3
mV
INPUT CHARACTERISTICS
VOS
Input Offset Voltage
TCVOS
Average Offset Voltage Drift
IB
Input Bias Current
RIN
VCM = 0V
-0.6
µV/°C
-3.7
µA
Input Impedance
7.3
M
CIN
Input Capacitance
1.6
pF
CMIR
Common-Mode Input Range
CMRR
Common-Mode Rejection Ratio
For VIN from -4.8V to 3.4V
60
97
dB
AVOL
Open-Loop Gain
-5V VOUT 5V
70
84
dB
eN
Voltage Noise
f = 100kHz
1.9
nV/Hz
iN
Current Noise
f = 100kHz
1.2
pA/Hz
RL = 500
-3.8
-3.5
V
RL = 250
-3.7
-3.5
V
VCM = 0V
-9
-4.8
3.4
V
OUTPUT CHARACTERISTICS
VOL
VOH
ISC
Output Swing Low
Output Swing High
Short Circuit Current
RL = 500
3.5
3.7
V
RL = 250
3.5
3.6
V
RL = 10
60
100
mA
65
95
dB
POWER SUPPLY PERFORMANCE
PSRR
Power Supply Rejection Ratio
VS is moved from ±2.25V to ±12V
IS
Supply Current (Per Amplifier)
No Load
VS
Operating Range
4.5
±2.5
5.5
mA
±12
V
DYNAMIC PERFORMANCE
SR
Slew Rate
±2.5V square wave, measured 25% to 75%
tS
Settling to 0.1% (AV = +2)
BW
HD2
HD3
45
V/µs
(AV = +2), VO = ±1V
77
ns
-3dB Bandwidth
RF = 358
90
MHz
2nd Harmonic Distortion
f = 1MHz, VO = 2VP-P, RL = 500, RF = 358
98
dBc
f = 1MHz, VO = 2VP-P, RL = 150, RF = 358
90
dBc
f = 1MHz, VO = 2VP-P, RL = 500, RF = 358
94
dBc
f = 1MHz, VO = 2VP-P, RL = 150, RF = 358
79
dBc
3rd Harmonic Distortion
3
35
FN7058.4
September 14 ,2010
EL2227
4
4
3
3
2
1
RF = 1k
RF = 620
0
-1
RF = 100
-2
RF = 350
-3
-4
-5
-6
1M
VS = ±12V
AV = +2
RL = 500
10M
NORMALIZED GAIN (dB)
NORMALIZED GAIN (dB)
Typical Performance Curves
RF = 100
RF = 350
2
1
0
-1
RF = 420
-2
RF = 620
-3
-4
-5
VS = ±12V
AV = -1
RL = 500
-6
1M
100M 200M
10M
FIGURE 2. INVERTING FREQUENCY RESPONSE FOR
VARIOUS RF
4
4
3
3
2
AV = 2
0
AV = 10
AV = 5
-2
-3
-4
-5
-6
1M
VS = ±12V
RF = 350
RL = 500
10M
NORMALIZED GAIN (dB)
NORMALIZED GAIN (dB)
FIGURE 1. NON-INVERTING FREQUENCY RESPONSE FOR
VARIOUS RF
-1
2
0
-2
-3
-4
-5
AV = -10
AV = -5
VS = ±12V
RF = 420
RL = 500
10M
FIGURE 4. INVERTING FREQUENCY RESPONSE (GAIN)
135
135
90
90
0
0
AV = 2
PHASE (°)
PHASE (°)
45
AV = 5
45
-45
-90
AV = 10
-135
-270
-315
1M
100M 200M
FREQUENCY (Hz)
FIGURE 3. NON-INVERTING FREQUENCY RESPONSE
(GAIN)
-225
AV = -1
-1
-6
1M
100M 200M
AV = -2
1
FREQUENCY (Hz)
-180
100M 200M
FREQUENCY (Hz)
FREQUENCY (Hz)
1
RF = 1k
-45
-90
-135
AV = -1
AV = -2
AV = -10
AV = -5
-180
VS = ±12
RF = 350
RL = 500
-225
-270
10M
100M200M
FREQUENCY (Hz)
FIGURE 5. NON-INVERTING FREQUENCY RESPONSE
(PHASE)
4
-315
1M
VS = ±12V
RF = 420
RL = 500
10M
100M 200M
FREQUENCY (Hz)
FIGURE 6. INVERTING FREQUENCY RESPONSE (PHASE)
FN7058.4
September 14 ,2010
EL2227
Typical Performance Curves (Continued)
3
2
1
VS = ±12V
RF = 350
VIN = 20mVP-P
AV = +2
RL = 500 VIN = 100mVP-P
0
-1
VIN = 500mVP-P
-2
VIN = 1VP-P
-3
-4
VIN = 2VP-P
-5
-6
100k
1M
10M
4
NORMALIZED GAIN (dB)
NORMALIZED GAIN (dB)
4
3
2
0
-1
-2
-3
-4
-5
VIN = 2.8VP-P
VIN = 280mVP-P
VS ±12V
RF = 420
RL = 500
AV = -1
-6
1M
100M
10M
FREQUENCY (Hz)
FIGURE 8. INVERTING FREQUENCY RESPONSE FOR
VARIOUS INPUT SIGNAL LEVELS
4
CL = 30pF
4
3
NORMALIZED GAIN (dB)
NORMALIZED GAIN (dB)
5
CL = 12pF
2
1
0
CL = 2pF
-1
VS = ±12V
-2 V
= 620
RSF=±1
-3 2V
RL = 500
-4 R
= +2
AF=62
V
-5
1M
10M
CL = 30pF
3
2
CL = 12pF
1
0
-1
CL = 2pF
-2
-3
-4
-5
VS ± 12V
R F = 420
RL = 500
AV = -1
-6
1M
100M 200M
10M
FREQUENCY (Hz)
3
RL = 100
2
0
-4
-5
-6
1M
RL = 50
VS = ±12V
RF = 620
CL = 15pF
AV = +2
10M
100M 200M
FREQUENCY (Hz)
FIGURE 11. NON-INVERTING FREQUENCY RESPONSE FOR
VARIOUS RL
5
4
RL = 500
1
-1
FIGURE 10. INVERTING FREQUENCY RESPONSE FOR
VARIOUS CL
NORMALIZED GAIN (dB)
NORMALIZED GAIN (dB)
4
100M 200M
FREQUENCY (Hz)
FIGURE 9. NON-INVERTING FREQUENCY RESPONSE FOR
VARIOUS CL
-3
100M 200M
FREQUENCY (Hz)
FIGURE 7. NON-INVERTING FREQUENCY RESPONSE FOR
VARIOUS INPUT SIGNAL LEVELS
-2
VIN = 20mVP-P
VIN = 1.4VP-P
1
VO = +10V
3
VO = -10V
2
VO = +5V
1
0
-1
VO = 0V
-2
-3
-4
-5
VS = ±12V
RF = 620
RL = 500
AV = +2
-6
100k
VO = -5V
1M
10M
100M
FREQUENCY (Hz)
FIGURE 12. FREQUENCY RESPONSE FOR VARIOUS OUTPUT
DC LEVELS
FN7058.4
September 14 ,2010
EL2227
Typical Performance Curves (Continued)
AV = +2
120 RF = 620
RL = 500
100
4.0
AV = +2
80
A V= -2
60
AV = +5
40
AV = -5
AV = +10
20
0
AV = +2
3.5
AV = -1
PEAKING (dB)
3dB BANDWIDTH (MHz)
140
3.0
AV = -1
2.5
2.0
1.5 AV = +10
AV = -10
1.0
AV = +5
0.5
AV = -10
2
4
8
6
10
12
AV = +2
RF = 620
RL = 500
0
2
SUPPLY VOLTAGE (±V)
4
AV = -2
AV = -5
6
10
8
12
SUPPLY VOLTAGE (±V)
FIGURE 13. 3dB BANDWIDTH vs SUPPLY VOLTAGE
FIGURE 14. PEAKING vs SUPPLY VOLTAGE
RF = 620
AV = 2
RL = 500
0.5V/DIV
RF = 620
AV = 2
RL = 500
0.5V/DIV
100ns/DIV
100ns/DIV
FIGURE 15. LARGE SIGNAL STEP RESPONSE (VS = ±12V)
FIGURE 16. LARGE SIGNAL STEP RESPONSE (VS = ±2.5V)
RF = 620
AV = 2
RL = 500
20mV/DIV
RF = 620
AV = 2
RL = 500
20mV/DIV
100ns/DIV
FIGURE 17. SMALL SIGNAL STEP RESPONSE (VS = ±12V)
6
100ns/DIV
FIGURE 18. SMALL SIGNAL STEP RESPONSE (VS = ±2.5V)
FN7058.4
September 14 ,2010
EL2227
Typical Performance Curves (Continued)
10
0.10
8
dG (%) OR dP (°)
6
GROUP DELAY (ns)
0.08
AV = 5V
4
2
AV = 2V
0
-2
-4
-6
-8
-10
1M
VS = ±12V
RF = 620
RL = 500
PIN = -20dBm into 50
0.06
0.04
0
-0.02
-1.0
100M
10M
dG
0.5
1.0
FIGURE 20. DIFFERENTIAL GAIN/PHASE vs DC INPUT
VOLTAGE AT 3.58MHz
100
OUTPUT IMPEDANCE ()
12
1.2/DI
6
1.2/DI
0
6
10
1
0.1
0.01
10k
12
10M
FIGURE 22. CLOSED LOOP OUTPUT IMPEDANCE vs
FREQUENCY
0
90
20
PSRR (dB)
110
70
50
30
40
VS-
60
VS+
80
VS = ±12
100
1k
10k 100k
1M
FREQUENCY (Hz)
FIGURE 23. CMRR
7
100M
FREQUENCY (Hz)
FIGURE 21. SUPPLY CURRENT vs SUPPLY VOLTAGE
10
10
1M
100k
SUPPLY VOLTAGE (±V)
-CMRR (dB)
0
-0.5
DC INPUT VOLTAGE (V)
FIGURE 19. GROUP DELAY vs FREQUENCY
SUPPLY CURRENT (mA)
dP
0.02
FREQUENCY (Hz)
0
AV = 2
RF = 620
RL = 150
fO = 3.58MHz
10M 100M
100
1k
10k
100k
1M
10M
100M
FREQUENCY (Hz)
FIGURE 24. PSRR
FN7058.4
September 14 ,2010
EL2227
Typical Performance Curves (Continued)
-40
2nd
-60
-70
3rd H
-80
-70
0
8
4
12
16
3rd H
-90
-100
20
2nd
-80
-90
-100
AV = 2
RF = 358
RL = 500
-60
DISTORTION (dBc)
-50
DISTORTION (dBc)
-50
AV = 2
RF = 620
RL = 500
0
-60
-60
-70
-70
RL = 50
-90
-100
RL = 500
-110
-120
1
10
2
2.5
RL = 50
-80
-90
RL = 500
-100
-110
100
1000
-120
1
10
100
1000
FREQUENCY (kHz)
FREQUENCY (kHz)
FIGURE 27. TOTAL HARMONIC DISTORTION vs FREQUENCY
@ 2VP-P VS = ±12V
FIGURE 28. TOTAL HARMONIC DISTORTION vs FREQUENCY
@ 2VP-P VS = ±2.5V
10
0
9
8
7
IN
6
5
4
3
EN
2
1
10
A B
-20
GAIN (dB)
VOLTAGE NOISE (nV/Hz),
CURRENT NOISE (pA/Hz)
1.5
1
FIGURE 26. 1MHz 2nd AND 3rd HARMONIC DISTORTION vs
OUTPUT SWING FOR VS = ±2.5V
THD (dBc)
THD (dBc)
FIGURE 25. 1MHz 2nd AND 3rd HARMONIC DISTORTION vs
OUTPUT SWING FOR VS = ±12V
-80
0.5
OUTPUT SWING (VP-P)
OUTPUT SWING (VP-P)
100
-40
B A
-60
-80
1k
10k
100k
FREQUENCY (Hz)
FIGURE 29. VOLTAGE AND CURRENT NOISE vs FREQUENCY
8
-100
100k
1M
10M
100M
FREQUENCY (Hz)
FIGURE 30. CHANNEL-TO-CHANNEL ISOLATION vs
FREQUENCY
FN7058.4
September 14 ,2010
EL2227
Typical Performance Curves (Continued)
10.0
140
130
9.5
IS (mA)
-3dB BANDWIDTH (MHz)
150
120
110
9.0
100
90
80
-40 -20
0
20
40
60
8.5
-50
80 100 120 140
DIE TEMPERATURE (°C)
50
0
100
150
DIE TEMPERATURE (°C)
FIGURE 31. -3dB BANDWIDTH vs TEMPERATURE
FIGURE 32. SUPPLY CURRENT vs TEMPERATURE
-2
2
IBIAS (µA)
VOS (mV)
-3
0
-2
-4
-5
-4
-50
0
50
100
-6
-50
150
55
150
160
140
53
SETTLING TIME (ns)
SLEW RATE (V/µs)
100
FIGURE 34. INPUT BIAS CURRENT vs TEMPERATURE
FIGURE 33. VOS vs TEMPERATURE
51
49
47
120
0
50
100
150
DIE TEMPERATURE (°C)
FIGURE 35. SLEW RATE vs TEMPERATURE
9
VS = ±2.5V
VO = 2VP-P
VS = ±12V
VO = 5VP-P
100
80
60
40
20
45
-50
50
0
DIE TEMPERATURE (°C)
DIE TEMPERATURE (°C)
0
0.01
VS = ±12V
VO = 2VP-P
0.1
1.0
ACCURACY (%)
FIGURE 36. SETTLING TIME vs ACCURACY
FN7058.4
September 14 ,2010
EL2227
Typical Performance Curves (Continued)
POWER DISSIPATION (W)
0.9
JEDEC JESD51-3 LOW EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD
781m
0.8

0.7
JA
=
607m
0.6
0.5
J
0.4
MS
A=
0.3
0.2
+2
OP
06
SO
+1
8
60
°C
/W
8
°C
/W
0.1
0
0
25
50
75 85 100
125
150
AMBIENT TEMPERATURE (°C)
FIGURE 37. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE
Pin Descriptions
EL2227CY EL2227CS
8 Ld MSOP 8 Ld SOIC
1
1
PIN
NAME
PIN
FUNCTION
VOUTA
Output
EQUIVALENT CIRCUIT
VS+
VOUT
Circuit 1
2
2
VINA-
Input
VS+
VIN+
VIN-
VS-
Circuit 2
3
3
VINA+
Input
4
4
VS-
Supply
5
5
VINB+
Input
6
6
VINB-
Input
Reference Circuit 2
7
7
VOUTB
Output
Reference Circuit 1
8
8
VS+
Supply
10
Reference Circuit 2
FN7058.4
September 14 ,2010
EL2227
Applications Information
+12V
1k
Product Description
The EL2227 is a dual voltage feedback operational amplifier
designed especially for DMT ADSL and other applications
requiring very low voltage and current noise. It also features
low distortion while drawing moderately low supply current
and is built on Elantec's proprietary high-speed
complementary bipolar process. The EL2227 use a classical
voltage-feedback topology, which allows them to be used in
a variety of applications where current-feedback amplifiers
are not appropriate because of restrictions placed upon the
feedback element used with the amplifier. The conventional
topology of the EL2227 allows, for example, a capacitor to
be placed in the feedback path, making it an excellent choice
for applications such as active filters, sample-and-holds, or
integrators.
ADSL CPE Applications
The low noise EL2227 amplifier is specifically designed for
the dual differential receiver amplifier function with ADSL
transceiver hybrids, as well as other low-noise amplifier
applications. A typical ADSL CPE line interface circuit is
shown in Figure 38. The EL2227 is used in receiving DMT
down stream signal. With careful transceiver hybrid design
and the EL2227 1.9nV/Hz voltage noise and 1.2pA/Hz
current noise performance, -140dBm/Hz system background
noise performance can be easily achieved.
DRIVER
INPUT
+
-
ROUT
RF
RG
ZLINE
RF
ROUT
+
LINE RF
RECEIVE
OUT +
+
RECEIVE
AMPLIFIERS +
RECEIVE
OUT -
LINE +
RF
R
RIN
R
RIN
FIGURE 38. TYPICAL LINE INTERFACE CONNECTION
1µF
10k
10k
1k
+
-
1µF
4.7µF
1k
75k
FIGURE 39. IMPLEMENTATION OF ENABLE/DISABLE
FUNCTION
Power Dissipation
With the wide power supply range and large output drive
capability of the EL2227, it is possible to exceed the +150°C
maximum junction temperatures under certain load and power
supply conditions. It is therefore important to calculate the
maximum junction temperature (TJMAX) for all applications to
determine if power supply voltages, load conditions, or package
type need to be modified for the EL2227 to remain in the safe
operating area. These parameters are related in Equation 1:
(EQ. 1)
T JMAX = T MAX +   JA  PD MAXTOTAL 
where:
PDMAXTOTAL is the sum of the maximum power
dissipation of each amplifier in the package (PDMAX)
PDMAX for each amplifier can be calculated using
Equation 2:
V OUTMAX
PD MAX = 2  V S  I SMAX +  V S – V OUTMAX   ---------------------------RL
(EQ. 2)
where:
TMAX = Maximum Ambient Temperature
JA = Thermal Resistance of the Package
PDMAX = Maximum Power Dissipation of 1 Amplifier
VS = Supply Voltage
Disable Function
IMAX = Maximum Supply Current of 1 Amplifier
The EL2227 is in the standard dual amplifier package without
the enable/disable function. A simple way to implement the
enable/disable function is depicted in Figure 39. When
disabled, both the positive and negative supply voltages are
disconnected (see Figure 39).
VOUTMAX = Maximum Output Voltage Swing of the
Application
11
RL = Load Resistance
To serve as a guide for the user, we can calculate maximum
allowable supply voltages for the example of the video
cable-driver below since we know that TJMAX = +150°C,
TMAX = +75°C, ISMAX = 9.5mA, and the package JAs are
shown in Table 1. If we assume (for this example) that we are
driving a back-terminated video cable, then the maximum
average value (over duty-cycle) of VOUTMAX is 1.4V, and
RL = 150, giving the results seen in Table 1.
FN7058.4
September 14 ,2010
EL2227
Printed-Circuit Layout
TABLE 1.
JA
MAX PDISS @
TMAX
PART
PACKAGE
EL2227CS
SO8
160°C/W 0.406W @ +85°C
EL2227CY
MSOP8
206°C/W 0.315W @ +85°C
MAX VS
Single-Supply Operation
The EL2227s have been designed to have a wide input and
output voltage range. This design also makes the EL2227 an
excellent choice for single-supply operation. Using a single
positive supply, the lower input voltage range is within
200mV of ground (RL = 500), and the lower output voltage
range is within 875mV of ground. Upper input voltage range
reaches 3.6V, and output voltage range reaches 3.8V with a
5V supply and RL = 500. This results in a 2.625V output
swing on a single 5V supply. This wide output voltage range
also allows single-supply operation with a supply voltage as
high as 28V.
The EL2227s are well behaved, and easy to apply in most
applications. However, a few simple techniques will help
assure rapid, high quality results. As with any high-frequency
device, good PCB layout is necessary for optimum
performance. Ground-plane construction is highly
recommended, as is good power supply bypassing. A 0.1µF
ceramic capacitor is recommended for bypassing both
supplies. Lead lengths should be as short as possible, and
bypass capacitors should be as close to the device pins as
possible. For good AC performance, parasitic capacitances
should be kept to a minimum at both inputs and at the
output. Resistor values should be kept under 5k because
of the RC time constants associated with the parasitic
capacitance. Metal-film and carbon resistors are both
acceptable, use of wire-wound resistors is not recommended
because of their parasitic inductance. Similarly, capacitors
should be low-inductance for best performance.
Gain-Bandwidth Product and the -3dB Bandwidth
The EL2227s have a gain-bandwidth product of 137MHz
while using only 5mA of supply current per amplifier. For
gains greater than 2, their closed-loop -3dB bandwidth is
approximately equal to the gain-bandwidth product divided
by the noise gain of the circuit. For gains less than 2, higher
order poles in the amplifiers' transfer function contribute to
even higher closed loop bandwidths. For example, the
EL2227 have a -3dB bandwidth of 115MHz at a gain of +2,
dropping to 28MHz at a gain of +5. It is important to note that
the EL2227 have been designed so that this “extra”
bandwidth in low-gain applications does not come at the
expense of stability. As seen in the typical performance
curves, the EL2227 in a gain of +2 only exhibit 0.5dB of
peaking with a 1000 load.
Output Drive Capability
The EL2227s have been designed to drive low impedance
loads. They can easily drive 6VP-P into a 500 load. This
high output drive capability makes the EL2227 an ideal
choice for RF, IF and video applications.
For additional products, see www.intersil.com/en/products.html
Intersil products are manufactured, assembled and tested utilizing ISO9001 quality systems as noted
in the quality certifications found at www.intersil.com/en/support/qualandreliability.html
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time
without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be
accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third
parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
For information regarding Intersil Corporation and its products, see www.intersil.com
12
FN7058.4
September 14 ,2010
EL2227
Package Outline Drawing
M8.15E
8 LEAD NARROW BODY SMALL OUTLINE PLASTIC PACKAGE
Rev 0, 08/09
4
4.90 ± 0.10
A
DETAIL "A"
0.22 ± 0.03
B
6.0 ± 0.20
3.90 ± 0.10
4
PIN NO.1
ID MARK
5
(0.35) x 45°
4° ± 4°
0.43 ± 0.076
1.27
0.25 M C A B
SIDE VIEW “B”
TOP VIEW
1.75 MAX
1.45 ± 0.1
0.25
GAUGE PLANE
C
SEATING PLANE
0.10 C
0.175 ± 0.075
SIDE VIEW “A
0.63 ±0.23
DETAIL "A"
(0.60)
(1.27)
NOTES:
(1.50)
(5.40)
1.
Dimensions are in millimeters.
Dimensions in ( ) for Reference Only.
2.
Dimensioning and tolerancing conform to AMSE Y14.5m-1994.
3.
Unless otherwise specified, tolerance : Decimal ± 0.05
4.
Dimension does not include interlead flash or protrusions.
Interlead flash or protrusions shall not exceed 0.25mm per side.
5.
The pin #1 identifier may be either a mold or mark feature.
6.
Reference to JEDEC MS-012.
TYPICAL RECOMMENDED LAND PATTERN
13
FN7058.4
September 14 ,2010
EL2227
Package Outline Drawing
M8.118A
8 LEAD MINI SMALL OUTLINE PLASTIC PACKAGE (MSOP)
Rev 0, 9/09
3.0±0.1
8
A
0.25
CAB
3.0±0.1
4.9±0.15
DETAIL "X"
1.10 Max
PIN# 1 ID
B
SIDE VIEW 2
1
0.18 ± 0.05
2
0.65 BSC
TOP VIEW
0.95 BSC
0.86±0.09
H
GAUGE
PLANE
C
0.25
SEATING PLANE
0.33 +0.07/ -0.08
0.08 C A B
0.10 ± 0.05
3°±3°
0.10 C
0.55 ± 0.15
DETAIL "X"
SIDE VIEW 1
5.80
NOTES:
4.40
3.00
1.
Dimensions are in millimeters.
2.
Dimensioning and tolerancing conform to JEDEC MO-187-AA
and AMSE Y14.5m-1994.
3.
Plastic or metal protrusions of 0.15mm max per side are not
included.
4.
Plastic interlead protrusions of 0.25mm max per side are not
included.
5.
Dimensions “D” and “E1” are measured at Datum Plane “H”.
6.
This replaces existing drawing # MDP0043 MSOP 8L.
0.65
0.40
1.40
TYPICAL RECOMMENDED LAND PATTERN
14
FN7058.4
September 14 ,2010