LV5061V Application Note

APPLICATION NOTE
LV5061V
Low power consumption and high efficiency
Step-down switching regulator controller
Introduction
This document presents the information on IC, application, schematic, pattern layout, Bill of
Materials and Evaluation Board.
Table of contents
1. Overview
2. Features
3. Typical applications
4. Pin assignment
5. Package dimensions and mounting pad sketch
6. Block diagram
7. Specifications
Absolute maximum ratings
Recommended operating conditions
Electrical characteristics
Characterization curves
8. Pin function
9. Operation explanation
9.1 Power-saving feature
9.2 Output voltage setting
9.3 Switching frequency Setting
9.4 Soft start function
9.5 Over current protection setting
9.6 Hiccup setting
9.7 Power good function
9.8 Leading edge blanking time
10. Evaluation board manual
11. Selection of main parts
11.1 Choke coil
11.2 Output capacitor
11.3 Input capacitor
11.4 External phase compensation components
2
2
2
2
3
3
4
7
11
13
18
1 / 21
LV5061V
1. Overview
LV5061V is 1ch step-down switching regulator. The operation current is about 90uA, and low power
consumption is achieved.
2. Features
1ch SBD rectification controller IC
Maximum value of light load mode current is 90uA
Built-in OCP circuit with P-by-P method
When P-by-P is generated continuously, it shifts to the HICCUP operation.
If connect C-HICCUP to GND pin, then latch-off when over current.
The oscillatory frequency can be set by the external pin.
The oscillatory frequency is 300 kHz to 2.2 MHz
・ Built-in UVLO, TSD
・
・
・
・
・
・
Application Circuit Example
Efficiency
100
VIN=8V
90
Efficiency [%]
80
70
VIN=12V
60
50
40
30
Vout=5V
L=10uH
Fsw=400kHz
20
10
0
0.1
1
10
Iout [mA]
100
1000
10000
3. Typical applications
・ Printers
・ Set-Top Boxes, DVD Drives and HDD
・ LCD Monitors and TVs
4. Pin assignment
Top View
2 / 21
LV5061V
5. Package dimensions and mounting pad sketch
SSOP16(225mil)
(Unit:mm)
SSOP16(225mil)
5.80
0.65
0.32
1.00
Reference symbol
eE
e
b3
l1
Caution: The package dimension is a reference value,
which is not a guaranteed value.
6. Block diagram
2.EN
Wake-up
16.REF
REF
Band-gap
uvlo.comp
enable
TSD
7.PDR
Pch
Drive
4.VIN
Bias
11.C-HICCUP
HICCUP.comp
1.26V
5.RSNS
pwm.comp
14.COMP
15pluse
counter
15.FB
3.ILIM
PbyP.comp
VIN
err.amp
12.SS
+
-
1.PG
S Q
PG.comp
R Q
clk
slope
OSC
PDR
1.1V
9, 13.NC
6.HDRV
Level-shift
Init.comp
10.RT
8.GND
3 / 21
LV5061V
7. Specifications
Absolute maximum ratings at Ta=25C
Parameter
Input Voltage
Symbol
Conditions
VIN max
PDR, HDRV, RSNS
ILIM, EN, PG
VIN-PDR
Allowable Pin Voltage
REF
SS, FB, COMP
C-HICCUP, RT
Allowable Power Dissipation
Pd max
Specified substrate *1
Operating Temperature
Topr
Storage Temperature
Tstg
*1 specified substrate 114.3mm  76.1mm  1.6mm glass-epoxy
Ratings
Unit
V
22
VIN
V
6
6
V
V
REF
V
0.74
-40 to +85
-55 to +150
W
C
C
Recommended operating conditions at Ta=25C
Parameter
Input Voltage Range
Symbol
Conditions
Ratings
4.5 to 18
VIN
Unit
V
Electrical characteristics at Ta=25C, VIN=15V
Parameter
[Reference Voltage]
Internal Reference Voltage
Pch Drive Voltage
Vref
VPDR
IOUT=0 to -5mA
[Saw Wave Oscillator]
Oscillatory Frequency
FOSC
RT=470k
[ON/OFF Circuit]
IC Startup Voltage
Disable Voltage
Vcnt_on
Vcnt_off
[Soft Start Circuit]
Soft Start Source Current
Soft Start Sink Current
ISS_SC
ISS_SK
EN>1.5V
EN<1.5V, ILIM>RSNS
SS=4V at HICCUP
1.3
1.2
[UVLO Circuit]
UVLO unlocking voltage
UVLO Lock Voltage
VUVLON
VUVLOF
FB=COMP
FB=COMP
[Error Amplifier]
Input Bias Current
Error amplifier gain
Output Sink Current
IEA IN
GEA
IEA_OSK
Output Source Current
IES_OSC
[Over Current Limit Circuit]
Reference current
Over current detection comparator
offset voltage
RSNS pin input range
ILIM1
VLIM_OFS
HICCUP Timer Startup Cycle
HICCUP Comparator Threshold
Voltage
HICCUP Timer Charge Current
[PWM Comparator]
Maximum On-Duty
Symbol
VRSNS
NLCYCLES
VtHIC
IHIC
DMAX
Conditions
Min.
Typ.
Max.
1.235
VIN5.5
1.260
VIN5.0
1.285
VIN4.5
280
330
380
kHz
VIN
0.3
V
V
2.0
2.0
2.7
2.8
A
mA
3.0
2.5
3.4
2.9
3.8
3.3
V
V
FB=1.75V
-100
100
-40
-50
250
-20
100
400
-10
nA
A/V
A
FB=0.75V
10
20
40
A
48.4
-5
55
61.6
+5
A
mV
VIN
V
cycle
V
1.5
VIN0.175
1.2
15
1.26
1.32
1
2
3
95
Units
V
V
A
%
4 / 21
LV5061V
Parameter
【Logic Output】
Power Good “L” Sink Current
Ipwrgd_L
PG=5V
Power Good “H” Leakage Current
Ipwrgd_H
PG=5V
Power GoodThreshold Voltage
Power Good Hysteresis
VtPG
VPG H
[Output]
Output On-Resistance (high)
Output On-Resistance (low)
Output On-current (high)
Output On-current (low)
RONH
RONL
IONH
IONL
[The entire device]
Standby current
Light Load Mode Consumption
Current
Thermal Shutdown
*2: Design certification
Symbol
ICCS
Isleep1
TSD
Conditions
Min.
Typ.
4
Max.
5
1.0
40
1.1
50
Units
6
mA
1
A
1.2
60
V
mV


mA
mA
3
3
500
500
EN  0.3V
EN  1.5V
No Switching
*2
50
A
A
1
90
70
C
170
Characterization curves VIN=15V, RT=470k
Reference Voltage
Light Load Mode Consumption Current
75
1.27
70
Isleep1 [uA]
Vref [V]
1.265
1.26
1.255
1.25
Tj=-40℃
65
60
Tj=25℃
55
50
Tj=85℃
45
40
1.245
-50
0
50
Tj [deg]
100
0
150
Frequency
10
VIN [V]
15
20
25
Over current limit
60
400
58
380
56
ILIM1 [uA]
Fosc [kHz]
5
360
340
54
52
50
48
320
46
300
44
-50
0
50
Tj [deg]
100
150
-50
0
50
Tj [deg]
100
150
5 / 21
LV5061V
Iss_SC
2.4
2.3
Iss_SC [uA]
2.2
2.1
2
1.9
1.8
1.7
1.6
-50
0
50
Tj [deg]
100
150
Relationship between RSNS and pulse width
(Change of the pulse width when RSNS is changed at the upper limit at which COMP is operated)
Pulse width, Cycle [ns]
3500
Tj=-40℃
3000
2500
Tj=25℃
2000
Tj=85℃
1500
1000
500
0
150
160
170
180
190
RSNS[mV]
Efficiency vs load current Vout=5V
220
230
100
VIN=8V
90
90
VIN=8V
80
70
Efficiency [%]
80
Efficiency [%]
210
Efficiency vs load current Vout=3.3V
100
VIN=12V
60
50
40
30
Vout=5V
L=10uH
Fsw=400kHz
20
10
0
0.1
1
10
Iout [mA]
100
1000
70
60
VIN=12V
50
40
30
Vout=3.3V
L=10uH
Fsw=400kHz
20
10
0
10000
0.1
Efficiency vs load current Vout=5V
1
10
Iout [mA]
100
1000
10000
Efficiency vs load current Vout=3.3V
100
100
VIN=8V
VIN=8V
95
Efficiency [%]
95
Efficiency [%]
200
90
VIN=12V
85
80
Vout=5V
L=10uH
Fsw=400kHz
75
70
0
500
1000
1500
Iout [mA]
2000
2500
3000
90
85
VIN=12V
80
Vout=3.3V
L=10uH
Fsw=400kHz
75
70
0
500
1000
1500
Iout [mA]
2000
2500
3000
6 / 21
LV5061V
8. Pin function
Pin No.
Pin name
Pin Function
1
PG
Power good pin.
Connect to open drain of MOS-FET in
ICs inside.
Setting output voltage to “L”, when FB
voltage is about 1.05V or less.
2
EN
ON/OFF pin.
Equivalent circuit
1k
VIN
4.8M
3
ILIM
For current detection. Sink current is
about 55uA. The current limiter
comparator works when an external
resistor is connected between this pin
and VIN, and if the voltage of this
resistor is less than the voltage of RSNS
then PchMOS is turned off. This
operation is reset each PWM pulse.
4
VIN
Supply voltage pin.
It is observed by the UVLO function.
When its voltage becomes 3.4V or
more, ICs startup in soft start.
5
RSNS
Current detection resistor connection
pin. Resistor is connected between VIN
and this pin, and the current flows to
MOSFET is measured.
VIN
5k
1k
VIN
VIN
5k
5k
7 / 21
LV5061V
Pin No.
6
Pin name
Pin Function
HDRV
The external high-side MOSFET gate
drive pin．
Equivalent circuit
VIN
130k
7
PDR
Gate drive voltage of the external
PchMOSFET, the bypass capacitor is
connected between VIN and this pin.
1.1M
VIN
1.3M
10k
10k
10
8
GND
Ground Pin. Ground pin voltage is
reference voltage.
9
N.C.
N.C. pin
VIN
8 / 21
LV5061V
Pin No.
Pin name
Pin Function
10
RT
Oscillation frequency setting pin.
Resistor is connected between this pin
and GND.
Equivalent circuit
VIN
21k
11
C-HICCUP
It is capacitor connection pin for setting
re-startup cycle in HICCUP mode.
If connect it to GND pin, then latch-off
when over current.
VIN
1k
12
SS
Capacitor connection pin for soft start.
About 2uA current charges the soft start
capacitor.
VIN
1k
10k
1k
13
N.C.
14
COMP
N.C. pin.
Error Amplifier Output Pin.
The phase compensation network is
connected between GND pin and
COMP pin. Thanks to current-mode
control, COMP pin voltage would tell
you the output current amplitude.
COMP pin is connected internally to an
int. comparator which compares with
0.9V reference. If COMP pin voltage is
larger than 0.9V, IC operates in
“continuous mode”. If COMP pin
voltage is smaller than 0.9V, IC
operates in “discontinuous mode (low
consumption mode)”.
VIN
70k
1k
1k
9 / 21
LV5061V
Pin No.
Pin name
Pin Function
15
FB
Error amplifier reverse input pin. ICs
make its voltage keep 1.26V. Output
voltage is divided by external resistors,
and it across FB.
Equivalent circuit
VIN
10k
1k
1k
16
REF
Reference voltage.
VIN
10
10
51k
1M
450k
10 / 21
LV5061V
9. Operation explanation
9.1 Power-saving feature
This IC has power-saving feature to enhance efficiency at light load. By shutting down unnecessary circuits,
operating current of the IC is minimized and high efficiency is realized.
9.2 Output voltage setting
The output voltage is set by resistor R4 (Between VOUT and FB) and resistor R5 (Between FB and GND).
The output voltage is determined by the following expression (1).
R4
R4
VOUT = (1 + R5 )  VREF = (1 + R5 )  1.26 [V] (1)
ex) The resistor that sets the output voltage to 5V are R4=470k and R5=160k.
470×103
VOUT = (1 + 160×103 )  1.26 = 4.96 [V] (2)
9.4 Soft start setting
Soft start time (TSS) is set with the capacitor C7
(Between SS and GND). TSS is determined by the
following expression (3).
VREF
1.26
TSS = C7  I
= C7 
[s]
(3)
2.0
 10-6
SS
ex) Where C7=2200pF, TSS is 1.38ms.
1.26
TSS = 2200  10-12 
= 1.386 [ms] (4)
2.0  10-6
Graph1. R7 vs FOSC
2500
2000
FOSC [kHz]
9.3 Switching frequency setting
The switching frequency (FOSC) is set by resistor R7
(Between RT and GND).
The relation of resistor R7 with FOSC is shown in
Graph 1. And please set FOSC taking the minimum
on-time =100ns into consideration.
ex) Where R7=390kΩ, FOSC is 400kHz.
1500
1000
500
0
10
100
R7 [kΩ]
1000
9.5 Overcurrent protection setting
When the RSNS pin exceeds the overcurrent limit value for 15 cycles of the oscillatory frequency, the
overcurrent protection detects the overcurrent state, and stops the IC. Overcurrent detection voltage
(VLIM) is determined by the resistor R2 (between VIN and ILIM) and the reference current (ILIM1).
The overcurrent detection voltage (VLIM) is determined by the following expression.
VLIM = R2  ILIM1 [V]
(5)
ex) Where R2=2.7kΩ, ILIM1=55uA, VILIM is 0.1485V.
VLIM = 2.7  103  55  10-6 = 0.1485 [V]
(6)
When the current sensing resistor R1 is 30mΩ, the value of the overcurrent is 4.95A.
You can select R1 from 20m to 100m according to the above-mentioned figure which shows the
relationship between RSNS and pulse width.
9.6 Hiccup Setting
The stop time of the overcurrent protection is determined by the capacitor (C8). IC restarts when the
C-HICCUP pin exceeds 1.26V.
C8  VtHIC C8  1.26
THIC =
=
[s]
(7)
IHIC
2.0  10-6
ex) Where C8=22000pF, THIC is 13.86msec.
THIC =
22000  10-12  1.26
= 13.86[ms]
2.0  10-6
(8)
9.7 Power good function
The Output voltage is observed with the voltage of the FB pin. The PG pin turns “Low” when the voltage of
FB pin is about 1.05V or less. Because the PG pin is open-drain, the PG pin can be Wired-OR.
11 / 21
LV5061V
Fig. Timing chart: Hiccup overcurrent protection / Power good function
9.8 Leading edge blanking time
LV5061V has the leading edge blanking time whose design value is 30ns.
12 / 21
LV5061V
10. Evaluation board manual
Performance summary
Table 1. LV5061V_DemoBoard Performance Summary
Parameter
Conditions
Input Supply Voltage
Output Voltage
Current Limit Peak
Oscillatory Frequency
Rating
Min
8
4.36
Typ
12
5
4.95
400
Max
16
5.54
Unit
V
V
A
kHz
Output voltage setting
Table 2. LV5061V_DemoBoard Output Voltage Point Setting
Output Voltage [V]
R4 [kΩ]
3.3
270
5
470
R5 [kΩ]
160
160
Manipulation method
1. Connect the load between OUT and GND.
2. Connect the input power supply with VIN and GND.
3. The output becomes a set voltage.
13 / 21
LV5061V
Layout
4-layer printed circuit board
Top layer
Bottom layer
14 / 21
LV5061V
4-layer printed circuit board
2nd layer
3rd layer
15 / 21
LV5061V
Schematic
Bill of Materials
Table 5. LV5061V_DemoBoard Bill of Materials
Manufacturer Part
Designator
Value
Number
Tolerance
Quantity
U1
LV5061V
-
-
1
L1
R1
R2
R3
R5
R6
R7
R8
R9
C1
C2
C3
C5
C6
C7
C8
C9
1217AS-H-100M
ERJ8BWFR030V
RK73B1JTTD272J
RK73B1JTTD105J
RK73Z1JTTD
RK73H1JTTD4703F
RK73H1JTTD1603F
RK73B1JTTD823J
RK73B1JTTD434J
RK73B1JTTD104J
GRM31CB31E106K
C2012JB0J106M
GRM188B31E105K
GRM188B31E105K
GRM188B11H472K
GRM188B11H222K
GRM188B11E223K
-
10uH / 4.3A
30mohms
2.7kohms
1Mohms
0ohms
470kohms
160kohms
39kohms
390kohms
100kohms
10uF / 25V
10uF / 6.3V
1uF / 25V
1uF / 25V
4.7nF / 50V
2.2nF / 50V
22nF / 50V
-
10%
1%
5%
5%
1%
1%
5%
5%
5%
10%
10%
10%
10%
10%
10%
10%
-
1
1
1
1
1
1
1
1
1
1
2
3
1
1
1
1
1
-
D1
SB3003CH
-
-
1
Q1
CPH6341
-
-
1
R4
Manufacturer
SANYO
Semiconductor
TOKO INC
Panasonic
KOA
KOA
KOA
KOA
KOA
KOA
KOA
KOA
Murata
TDK
Murata
Murata
Murata
Murata
Murata
SANYO
Semiconductor
SANYO
Semiconductor
16 / 21
LV5061V
Waveforms
Ta=25deg, VIN=12V, Vo=5V
Io=0.01A output waveform
2us/div
Io=0.1A output waveform
2us/div
SW
10V/div
SW
10V/div
Vo
20mV/div
Vo
20mV/div
IL
1A/div
IL
1A/div
Io=0.2A output waveform
Io=2A output waveform
2us/div
2us/div
SW
10V/div
SW
10V/div
Vo
20mV/div
Vo
20mV/div
IL
1A/div
IL
1A/div
Load transient Io=1A  3A (Slew rate=100us)
Overcurrent protection HICCUP
10ms/div
0.5ms/div
Vo
5V/div
Vo
0.2V/div
Vss
5V/div
Vhiccup
1V/div
Io
2A/div
Io
5A/div
Soft start
Shutdown
1ms/div
1ms/div
Ven
2V/div
Ven
2V/div
Vss
2V/div
Vss
2V/div
Vo
5V/div
Vo
5V/div
Vp.good
10V/div
Vp.good
10V/div
17 / 21
LV5061V
11. Selection of main parts
11.1 Choke coil
When conditions for input voltage, output voltage and ripple current are defined, the following equation (9)
gives inductance value.
Make sure to set ripple current (∆IR) to be lower than 20% of the output current.
L =
VIN-VOUT
 Ton
∆IR
Ton =
1
{((VIN - VOUT)  (VOUT + VF)) + 1}  FOSC
FOSC
VF
VIN
VOUT
: Oscillatory Frequency
: Forward voltage of Schottky Barrier diode
: Input voltage
: Output voltage
(9)
・Inductor current: Peak value (IRP)
Current peak value (IRP) of the inductor is given by the equation (10).
VIN-VOUT
IRP = Iout +
 Ton
(10)
2L
Make sure that rating current value of the inductor is higher than a peak value of ripple current.
・Inductor current: ripple current (∆IR)
Ripple current (∆IR) is given by the equation (11).
VIN-VOUT
 Ton
(11)
ΔIR =
L
When load current (Iout) is less than 1/2 of the ripple current, inductor current flows discontinuously.
11.2 Output capacitor
Make sure to use a capacitor with high frequency impedance for switching power supply because a large
ripple current flows through output capacitor.
Effective value is given by the equation (12) because the ripple current (AC) that flows through output
capacitor is sawtooth wave.
VOUT  (VIN - VOUT)
1
IC_OUT =

[Arms]
(12)
23
L  FOSC  VIN
11.3 Input capacitor
Ripple current flows through input capacitor which is higher than that of the output capacitors.
Therefore, caution is also required for allowable ripple current value.
The effective value of the ripple current which flows through input capacitor is given by the equation (13).
IC_IN = D (1 - D)  IOUT [Arms]
(13)
TON VOUT
D= T = V
IN
In (13), D signifies the ratio between ON/OFF period. When the value is 0.5, the ripple current is at a
maximum. Make sure that the input capacitor does not exceed the allowable ripple current value given by
(13). With (13), if VIN=12V, VOUT=5V and IOUT=3.0A, then IC_IN value is about 1.48Arms.
In the board wiring from input capacitor, VIN to GND, make sure that wiring is wide enough to keep
impedance low because of the current fluctuation. Make sure to connect input capacitor near output
capacitor to lower voltage bound due to regeneration current. When change of load current is excessive
(IOUT: high  low), the power of output electric capacitor is regenerated to input capacitor. If input
capacitor is small, input voltage increases. Therefore, you need to implement a large input capacitor.
Regeneration power changes according to the change of output voltage, inductance of a coil and load
current.
18 / 21
LV5061V
11.4 Selection of external phase compensation component
This IC adopts current mode control which allows use of ceramic capacitor with low ESR and solid polymer
capacitor such as OS capacitor for output capacitor with simple phase compensation. Therefore, you can
design long-life and high quality step-down power supply circuit easily.
Frequency Characteristics
The frequency characteristic of this IC is constituted with the following transfer functions.
(1) Output resistance breeder
(2) Voltage gain of error amplifier
Current gain
(3) Impedance of phase compensation external element
(4) Current sense loop gain
(5) Output smoothing impedance
: HR
: GVEA
: GMEA
: ZC
: GCS
: ZO
Figure: Compensation networks
Closed loop gain is obtained with the following formula (14).
G  H R  G MER  Z C  G CS  Z O

VREF
 G MER
VOUT

RL
1 
  G CS 
  R C 
sC C 
1  sC O  R L

(14)
Frequency characteristics of the closed loop gain is given by pole fp1 consists of output capacitor CO and
output load resistance RL, zero point fz consists of external capacitor CC of the phase compensation and
resistance RC, and pole fp2 consists of output impedance ZER of error amplifier and external capacitor of
phase compensation CC as shown in formula (14). fp1, fz, fp2 are obtained with the following equations (15)
to (17).
1
2  C O  RL
1
fz 
2  CC  R C
1
fp2 
2  ZER  CC
fp1 
(15)
(16)
(17)
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LV5061V
Calculation of external phase compensation constant
Generally, to stabilize switching regulator, the frequency where closed loop gain is 1 (zero-cross frequency fZC)
1
1
of the switching frequency (or ). Since the switching frequency of this IC is 400 kHz, the
should be
10
5
zero-cross frequency should be 40 kHz. Based on the above condition, we obtain the following formula (18).

VREF
RL
1 
  G CS 
 GMER   R C 
1
VOUT
sC C 
1  sC O  R L

(18)
As for zero-cross frequency, since the impedance element of phase compensation is RC 
1
, the following
sCC
equation (19) is obtained.
VREF
RL
 GMER  R C  G CS 
1
VOUT
1  2  f ZC  C O  R L
(19)
Phase compensation external resistance can be obtained with the following formula (20), the variation of the
formula (19). Since 2  fZC  CO  RL  1 in the equation (20), we know that the external resistance is independent
of load resistance.
RC 
VOUT
1
1 1  2  f ZC  C O  R L



VREF GMER GCS
RL
(20)
When output is 5V and load resistance is 5Ω (1A load), the resistances of phase compensation are as follows.
GCS = 4.1A/V, GMER = 250uA/V, fZC = 40kHz
RC 

 

5
1
1 1  2  3.14  40  10 3  30  10 6 5



 29.964...  10 3
1.26 250  10  6 4.1
5
 30　[k]
If frequency of zero point fz and pole fp1 are in the same position, they cancel out each other. Therefore, only
the pole frequency remains for frequency characteristics of the closed loop gain.
In other words, gain decreases at -20dB/dec and phase only rotates by 90º and this allows characteristics
where oscillation never occurs.
fp1  fz
1
1

2  CO  RL 2  CC  RC
CC 


RL  CO 5  30  10 6

 5.172...  10 9
3
RC
30  10
 5 .2 [ nF ]
The above shows external compensation constant obtained through ideal equations. In reality, we need to
define phase constant through testing to verify constant IC operation at all temperature range, load range and
input voltage range. In the evaluation board for delivery, phase compensation constants are defined based on
the above constants. The zero-cross frequency required in the actual system board, in other word, transient
response is adjusted by external compensation resistance. Also, if the influence of noise is significant, use of
external phase compensation capacitor with higher value is recommended.
The table of compensation values for 400 kHz is provided below.
VIN
Vout
RSNS
L
RC
(kohm)
(V)
(V)
(mohm)
(uH)
8
12
5
30
10
39
15
8
12
3.3
39
10
33
15
CC
(nF)
Co
(uF)
4.7
30
4.7
30
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LV5061V
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