Integrated Adjustable 8 Amp Synchronous Switcher Features General Description • EL7558C/EL7558AC pincompatible • Improved temperature and voltage ranges • 8A continuous load current • Precision internal 1% reference • 1.0V to 3.8V output voltage • Internal power MOSFETs • >90% efficiency • Synchronous switching • Adjustable slope compensation • Over-temperature indicator • Pulse-by-pulse current limiting • Operates up to 1MHz • 1.5% typical output accuracy • Adjustable oscillator with sync • Remote enable/disable • Intel P54- and P55-compatible • VCC2DET interface • Internal soft-start The EL7558BC is an adjustable synchronous DC:DC switching regulator optimized for a 5V input and 1.0V-3.8V output. By combining integrated NMOS power FETS with a HSOP package the EL7558BC can supply up to 8A continuous output current without the use of external power devices or externally attached heat sinks, thereby minimizing design effort and overall system cost. Applications Connection Diagram • • • • • • EL7558BC EL7558BC On-chip resistorless current sensing is used to achieve stable, highly efficient, current-mode control. The EL7558BC also incorporates the VCC2DET function to directly interface with the Intel P54 and P55 microprocessors. Depending on the state of VCC2DET, the output voltage is internally preset to 3.50V or a user-adjustable voltage using two external resistors. In both internal and external feedback modes the active-high PWRGD output indicates when the regulator output is within ±10% of the programmed voltage. An on-board sensor monitors die temperature (OT) for over-temperature conditions and can be connected directly to OUTEN to provide automatic thermal shutdown. Adjustable oscillator frequency and slope compensation allow added flexibility in overall system design. The EL7558BC is available in the 28-pin HSOP package and is specified for operation over the -40°C to +85°C temperature range. PC motherboards Local high power CPU supplies 5V to 1.0V DC:DC conversion Portable electronics/instruments P54 and P55 regulators GTL+ Bus power supply R4 R3 100Ω 150Ω VIN D3 C4 1 FB1 2 CREF 3 CSLOPE FB2 28 0.1µF C7 CP 27 C2V 26 C8 C5 R1 220pF 330pF D2 1µF D4* (Optional) 20Ω 4 COSC 5 VDD VSS 25 R5 R6 5.1Ω VIN LX C11 0.22µF C6 6 D1 VHI 24 39.2Ω 23 0.1µF Ordering Information Part No EL7558BCM EL7558BCM-T13 VIN 7 VSSP LX 22 C9 C12 8 VIN LX 21 660µF 1µF 9 VSSP LX 20 C10 10 VSSP VSSP 19 1mF 11 VSSP VSSP 18 12 VSSP TEST 17 13 VCC2DET 16 PWRGD Package Tape & Reel Outline # C3 28-Pin HSOP - MDP0042 1µF 28-Pin HSOP 13” MDP0042 14 C12 = 1µF C3, C4, C5, C6, C7 C8 - ceramic C5, C11 - ceramic or tantalum C9 - Sprague 293D337X96R3 2X330µF C10 - Sprague 293D337X96R3 3X330µF L1 - Pulse Engineering, PE-53681 D1 - D4: BAT54S fast diode D4 Required for EL7558ACM only OUTEN OT 2.5µH VOUT 15 EL7558BC Manufactured under U.S. Patents No. 5,723,974 and No. 5,793,126 Note: All information contained in this data sheet has been carefully checked and is believed to be accurate as of the date of publication; however, this data sheet cannot be a “controlled document”. Current revisions, if any, to these specifications are maintained at the factory and are available upon your request. We recommend checking the revision level before finalization of your design documentation. © 2001 Elantec Semiconductor, Inc. April 27, 2001 Connect to VSSP for external feedback L1 EL7558BC EL7558BC Integrated Adjustable 8 Amp Synchronous Switcher Absolute Maximum Ratings (T Storage Temperature Range Supply (VIN) Ambient Operating Temperature A = 25°C) -65°C to +150°C 6V -40°C to +85°C Output Pins Operating Junction Temperature Peak Output Current -0.3V below GND, +0.3V above VDD 135°C 9A Important Note: All parameters having Min/Max specifications are guaranteed. Typ values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA. Electrical Characteristics VDD = VIN = 5V, COSC = 1nF, CSLOPE = 470pF, TA = 25°C unless otherwise specified. Parameter Description Conditions Min Typ Max 25 Unit General IDD VDD Supply Current OUTEN = 4V, FOSC = 120kHz 11 IDDOFF VDD Standby Current OUTEN = 0 0.1 mA IVIN VIN No Load Current OUTEN = 0 3 5 mA VOUT1 Output Initial Accuracy VCC2DET = 4V, IL = 3A (See Fig. 1) 3.450 3.500 3.550 V VOUT2 Output Initial Accuracy VCC2DET = 0V, IL = 3A R3 = 150Ω, R4 = 100Ω (See Fig. 1) 2.450 2.500 2.550 V VOUTLINE Output line Regulation VDD = 5V, ±10% -1 1 % VOUTLOAD Output Load Regulation 0A<ILOAD<6A, Relative to IL = 3A. Continuous Mode of Operation (See Fig.1) -1 1 % RSHORT Short Circuit Load Resistance IL = 6A Prior to Continuous Application of RSHORT. OUTEN Connected to OT. 100 II MAX Current Limit 9 A VOUTTC Output Tempco -40°C<TA<85°C ±1 % mA mΩ TOT Over Temperature Threshold 135 °C THYS Over Temperature Hysteresis 40 °C VPWRGD Power Good Threshold Relative to Programmed Output Voltage VDDOFF Minimum VDD for Shutdown VDDON Maximum VDD for Startup VHYS Input Hysteresis MSS DMAX VCC2SEL = 4V, VOUT = 3.50V ±6 ±10 ±14 3.15 V 4.15 VHYS = VDDON-VDDOFF % V 0.5 V Soft start slope 7 V/ns Maximum duty cycle 96 % Controller - Inputs IPUP VCC2DET, OUTEN Pull Up Current ICSLOPE Cslope Charging Current VCC2DET, OUTEN = 0 IFB1 FB1 Input Pull Up Current ROT Over Temperature Pull Up Resistance VIH VCC2DET, OUTEN Input High VIL VCC2DET, OUTEN Input Low VOH PWGD Powergood Drive High ILoad = 1mA VOL PWGD Powergood Drive Low ILoad = -1mA 10 14 18 µA 23 28.5 34 µA 2 OT = 0V 30 40 µA 50 4 kΩ V .8 3.5 V V 1.0 V Controller - Reference VREF Reference Accuracy VREFTC Reference Voltage Tempco VREFLOAD Reference Load Regulation IREF = 0 1.247 1.260 1.273 50 0<ILOAD<100µA 2 0.5 V ppm/ºC 0.5 %/ºC Electrical Characteristics VDD = VIN = 5V, COSC = 1nF, CSLOPE = 470pF, TA = 25°C unless otherwise specified. Parameter Description Conditions Min Typ Max Unit 7.5 8.1 8.7 V Controller - Doubler VC2V Voltage Doubler Output VDD = 5V, ILOAD = 10mA Controller - Oscillator FRAMP Oscillator Ramp Amplitude IOSC CHG Oscillator Charge Current 0.2V<VOSC<1.4V 0.2V<VOSC<1.4V IOSC DIS Oscillator Discharge Current FOSC Oscillator initial accuracy tsync Minimum oscillator sync width 1.2 V 150 µA 5 100 120 mA 140 50 kHz ns Power - FET ILEAK LX Output Leakage to VSS RDSON Composite FET Resistance LX = 0V RDSONTC RDSON Tempco 0.1 mΩ/ºC tbrm FET break before make delay 10 ns tLEB High side FET minimum on time (LEB) 140 ns 18 3 100 µA 30 mΩ EL7558BC EL7558BC Integrated Adjustable 8 Amp Synchronous Switcher Integrated Adjustable 8 Amp Synchronous Switcher Typical Performance Curves Efficiency vs ILOAD (VOUT=3.5V) Efficiency vs ILOAD (VDD=5.0 V) 97 100 93 VDD=5V 91 VDD=5.5V VOUT=3.5V 95 VDD=4.5V Efficiency (%) Efficiency (%) 95 89 87 90 VOUT=2.5V 85 80 VOUT=1V 75 TA=25°C 85 0.5 1.5 2.5 3.5 4.5 5.5 6.5 7.5 TA=25°C 70 0.5 8.0 1.5 2.5 3.5 4.5 IOUT (A) Line Regulation (C SLOPE=150pF) 8.0 3.53 3.52 IOUT=0.5A VIN=5.5V 3.51 3.51 VOUT (V) VOUT (V) 7.5 Load Regulation (CSLOPE=150pF) TA=25°C 3.52 IOUT=4A 3.50 3.49 IOUT=8A 3.50 VIN=5V 3.49 VIN=4.5V 3.48 3.48 3.47 3.47 3.46 0.5 4.5 5.0 VIN (V) 5.5 Line Regulation vs CSLOPE (IOUT=3A) VDD=VIN=5.0V ±10% 0.6 TA=25°C 0.7 TA=25°C 1 2 3 4 IOUT (A) 5 6 7 8 Load Regulation vs CSLOPE (VIN=5.0V) IOUT=0.5 to 6A TA=25°C 0.5 0.6 VOUT=3.5V 0.4 ∆VOUT (±) (%) VOUT=3.5V 0.5 VOUT=2.5V 0.3 0.4 VOUT=2.5V 0.3 0.2 0.2 VOUT=1V 0.1 0.1 0.0 6.5 3.54 3.53 0.8 5.5 IOUT (A) 3.54 ∆VOUT (±) (%) EL7558BC EL7558BC VOUT=1V 50 75 100 125 150 0.0 175 CSLOPE (pF) 50 75 100 125 CSLOPE (pF) 4 150 175 Typical Performance Curves 0.8 Line Regulation vs CSLOPE VIN=VDD=5.0V ±10% 0.8 TA=25°C 0.7 IOUT=0.5A ∆VOUT (±) (%) ∆VOUT (±) (%) 0.6 0.5 0.4 0.3 IOUT=6A 0.2 50 75 100 125 CSLOPE (pF) 150 0.4 VIN=5A 0.3 VIN=5.5A 0.0 50 175 VOUT vs CSLOPE (VIN=5.0V, I LOAD=.5A) 1.5 100 125 CSLOPE (pF) 150 175 VOUT Variation vs Programmed Output Voltage [VIDEAL=(1+R3/R4)] 1.0 Deviation in VOUT (%) VOUT=1V 0.0 -0.5 VOUT=2.5V -1.0 -1.5 VOUT=3.5V -2.0 0.5 CS 0.0 SC = -3.0 75 22 0p 00 pF F -0.5 TA=25°C 50 LO PE = 1 CO -1.0 -2.5 100 125 CSLOPE (pF) 150 -1.5 1.0 175 Loop Gain Induced Error 1.5 2.0 2.5 3.0 3.5 4.0 VIDEAL (V) FOSC vs COSC FOSC vs Temperature 10000 520 TA=25°C 510 1000 VDD=4.5V FOSC(kHz) 500 100 490 VDD=5.5V 480 470 10 VDD=5V 460 1 75 TA=25°C 0.5 FOSC(kHz) VIN=4.5A 0.1 1.0 ∆VOUT (±) (%) 0.5 0.2 0.1 1.5 TA=25°C 0.7 0.6 0.0 Load Regulation vs C SLOPE IOUT=0.5 to 6A 10 100 1000 450 100000 COSC (pF) 0 20 40 COSC=220pF 60 80 Temperature (°C) 5 100 120 140 EL7558BC EL7558BC Integrated Adjustable 8 Amp Synchronous Switcher Integrated Adjustable 8 Amp Synchronous Switcher Typical Performance Curves IVDD + IVIN vs FOSC IVIN vs FOSC 16 60 TA=25°C OUTEN=VDD 50 TA=25°C OUTEN=VDD 14 VDD=5.5V VDD=5.5V 40 10 30 VDD=4.5V IVIN (mA) IVDD + IVIN (mA) 12 VDD=5V 20 VDD=5V 8 6 VDD=4.5V 4 10 2 Discontinuous Mode Continuous Mode Discontinuous Mode FOSC (kHz) FOSC (kHz) IVDD vs FOSC RDSON vs Temperature 38 50 TA=25°C OUTEN=VDD 45 40 36 VDD=5.5V 34 VDD=5V 32 RDSON (m Ω) 35 IVDD (mA) Continuous Mode 0 0 30 25 VDD=4.5V 20 15 30 28 26 10 24 5 22 0 20 0 25 FOSC (kHz) 50 75 Temperature (°C) 100 125 4.5 5.0 Power On Reset IQ vs FOSC 40 2.0 TA=25°C OUTEN=VDD VDD=5.5V 30 VDD=5V Iq (mA) IQ (mA) EL7558BC EL7558BC 1.5 20 FOSC=500k VDD=4.5V 10 1.0 10 100 FOSC (kHz) 0 2.5 1000 3.0 3.5 4.0 VDD (V) 6 Typical Performance Curves Minimum Output Voltage vs FOSC 2.3 2.1 TJ=120°C VDD=5.5V 1.9 VOUT (V) 1.7 VDD=5V 1.5 1.3 VDD=4.5V 1.1 0.9 0.7 200 400 600 FOSC (kHz) 800 1000 7 EL7558BC EL7558BC Integrated Adjustable 8 Amp Synchronous Switcher EL7558BC EL7558BC Integrated Adjustable 8 Amp Synchronous Switcher Pin Descriptions I = Input, O = Output, S = Supply Pin Number Pin Name Pin Type Function 1 FB1 I Voltage feedback pin for the buck regulator. Active when VCC2DET is logic low. Normally connected to external resistor divider between VOUT and GND. A 2µA pull-up current forces VOUT to VSS in the event that FB1is floating and VCC2DET is inadvertently connected to GND. 2 CREF I Bandgap reference bypass capacitor. Typically 0.1µF to VSS. 3 CSLOPE I Slope compensation capacitor. Ramp width corresponds to LX duty cycle. CSLOPE to COSC ratio is normally 1:1.5. 4 COSC I Oscillator timing capacitor. FOSC (Hz) can be approximated by: FOSC (Hz) = 0.0001/COSC. COSC in Farads. 5 VDD S Power Supply for PWM control circuitry. Normally the same potential as VIN. 6 VIN S Power supply for the buck regulator. Connected to the drain of the high-side NMOS FET. 7 VSSP S Ground return for the buck regulator. Connected to the source of the low-side synchronous NMOS FET. 8 VIN S Same as pin 6. 9 VSSP S Same as pin 7. 10 VSSP S Same as pin 7. 11 VSSP S Same as pin 7. 12 VSSP S Same as pin 7. 13 VCC2DET I VCC2DET interface logic input. When driven to logic 1 VOUT = 3.500V. When driven to logic 0 the PWM uses FB1 to determine VOUT: VOUT = 1.0V*(1+R3/R4). 14 OUTEN I The switching regulator output is enabled when logic 1. The reference voltage output operates whenever the power supply is qualified (VDD>VPOR) regardless of the state of this pin. 15 OT O Over temperature indicator. Normally high. Pulls low when die temperature exceeds 135°C, returns to the high state when die temperature has cooled to 100°C. 16 PWRGD O Power good window comparator output. Logic 1 when regulator output is within ±10% of programmed voltage. 17 TEST I Test pin. Must be connected to VSSP in normal operation. 18 VSSP S Same as pin 7. 19 VSSP S Same as pin 7. 20 LX O Inductor drive pin. High current switching output whose average voltage equals the regulator output voltage. 21 LX O Same as pin 20. 22 LX O Same as pin 20. 23 LX O Same as pin 20. 24 VHI I Gate drive to high-side driver. Bootstrapped from LX with a 0.1µF capacitor. Ground return for the control circuitry. 25 VSS S 26 C2V I Connected to voltage doubler output. Supplies gate drive to the low-side driver. 27 CP O Drives the negative side of charge pump capacitor at one-half the oscillator frequency FOSC. 28 FB2 I Voltage feedback pin. Active when VCC2DET is logic 1. Internally preset to VOUT = 3.5V. 8 9 COSC, Pin 4 VDD OUTEN, Pin 14 CREF, Pin 27 CSLOPE, Pin 3 VCCDET, Pin 13 1.26V + + 4V R S UVLO 2-1 MUX + Σ RSS VDD + Current Sense CSS + PWM + Current Limit + + R S R FF S Q Q LEB TDELAY Over Temp Sensor Zero Cross Detect V2X + FB1, Pin1 FB2, Pin 28 VSS, Pin 25 OT, Pin 15 VSSP, Pin 9-12, 18-19 LX, Pin 20-23 VDD and VIN, Pin 5,6,8 VHI, Pin 24 C2V, Pin 26 PWRGD, Pin 16 CP, Pin 27 EL7558BC Block Diagram EL7558BC Integrated Adjustable 8 Amp Synchronous Switcher EL7558BC EL7558BC Integrated Adjustable 8 Amp Synchronous Switcher Applications Information Circuit Description the relatively large LC time constants found in power supply applications generally results in low bandwidth and poor transient response. By directly monitoring changes in inductor current via a series sense resistor the controller’s response time is not entirely limited by the output LC filter and can react more quickly to changes in line or load conditions. This feed-forward characteristic also simplifies AC loop compensation since it adds a zero to the overall loop response. Through proper selection of the current-feedback to voltage-feedback ratio, the overall loop response will approach a one pole system. The resulting system offers several advantages over traditional voltage control systems, including simpler loop compensation, pulse by pulse current limiting, rapid response to line variation and good load step response. General The EL7558BC is a fixed frequency, current mode controlled DC:DC converter with integrated N-channel power MOSFETS and a high precision reference. The device incorporates all of the active circuitry required to implement a cost effective, user-programmable 8A synchronous buck converter suitable for use in CPU power supplies. By combining HSOP packaging technology with an efficient synchronous switching architecture, high power outputs (30W) can be realized without the use of externally attached heat sinks. Theory of Operation The EL7558BC is composed of 7 major blocks: The heart of the controller is a triple-input direct summing comparator which sums voltage feedback, current feedback and slope compensating ramp signals together. Slope compensation is required to prevent system instability which occurs in current-mode topologies operating at duty-cycles greater than 50% and is also used to define the open-loop gain of the overall system. The compensation ramp amplitude is user adjustable and is set using a single external capacitor (CSLOPE). Each comparator input is weighted and determines the load and line regulation characteristics of the system. Current feedback is measured by sensing the inductor current flowing through the high-side switch whenever it is conducting. At the beginning of each oscillator period the high-side NMOS switch is turned on and CSLOPE ramps positively from its reset state (VREF potential). The comparator inputs are gated off for a minimum period of time (LEB) after the high-side switch is turned on to allow the system to settle. The Leading Edge Blanking (LEB) period prevents the detection of erroneous voltages at the comparator inputs due to switching noise. When programming low regulator output voltages the LEB delay will limit the maximum operating frequency of the circuit since the LEB will result in a minimum duty-cycle regardless of the PWM error voltage. This relationship is shown in the performance curves. If the inductor current exceeds the maximum current limit (ILMAX), a secondary over-current com- 1. PWM Controller 2. Output Voltage Mode Select 3. NMOS Power FETS and Drive Circuitry 4. Bandgap Reference 5. Oscillator 6. Temperature Sensor 7. Power Good and Power On Reset PWM Controller The EL7558BC regulates output voltage through the use of current-mode controlled pulse width modulation. The three main elements in a PWM controller are the feedback loop and reference, a pulse width modulator whose duty cycle is controlled by the feedback error signal, and a filter which averages the logic level modulator output. In a step-down (buck) converter, the feedback loop forces the time-averaged output of the modulator to equal the desired output voltage. Unlike pure voltagemode control systems current-mode control utilizes dual feedback loops to provide both output voltage and inductor current information to the controller. The voltage loop minimizes DC and transient errors in the output voltage by adjusting the PWM duty-cycle in response to changes in line or load conditions. Since the output voltage is equal to the time-average of the modulator output 10 drive for both the high-side and low-side switches is derived through a charge pump consisting of the CP pin and external components D1-D3 and C5-C6. The CP output is a low resistance inverter driven at one-half the oscillator frequency. This is used in conjunction with D2-D3 to generate a 7.5V (typical) voltage on the C2V pin which provides gate drive to the low-side NMOS switch and associated level shifter. In order to use an NMOS switch for the high-side drive it is necessary to drive the gate voltage above the source voltage (LX). This is accomplished by boot-strapping the VHI pin above the C2V voltage with capacitor C6 and diode D1. When the low-side switch is turned on the LX voltage is close to GND potential and capacitor C6 is charged through diodes D1-D3 to approximately 6.9V. At the beginning of the next cycle the high side switch turns on and the LX pin begins to rise from GND to VDD potential. As the LX pin rises the positive plate of capacitor C6 follows and eventually reaches a value of approximately 11.2V, for VDD=5V. This voltage is then level shifted and used to drive the gate of the high-side FET, via the VHI pin. parator will terminate the high-side switch. If ILMAX has not been reached, the regulator output voltage is then compared to the reference voltage VREF. The resultant error voltage is summed with the current feedback and slope compensation ramp. The high-side switch remains on until all three comparator inputs have summed to zero, at which time the high-side switch is turned off and the low-side switch is turned on. In order to eliminate cross-conduction of the high-side and low-side switches a 10ns break-before-make delay is incorporated in the switch driver circuitry. In the continuous mode of operation the low-side switch will remain on until the end of the oscillator period. In order to improve the low current efficiency of the EL7558BC, a zero-crossing comparator senses when the inductor transitions through zero. Turning off the low-side switch at zero inductor current prevents forward conduction through the internal clamping diodes (LX to VSSP) when the low-side switch turns off, reducing power dissipation. The output enable (OUTEN) input allows the regulator output to be disabled by an external logic control signal. Output Voltage Mode Select Reference The VCC2DET multiplexes the FB1 and FB2 pins to the PWM controller. A logic 1 on VCC2DET selects the FB2 input and forces the output voltage to the internally programmed value of 3.50V. A logic zero on VCC2DET selects FB1 and allows the output to be programmed from 1.0 to 3.8V. In general: A 1% temperature compensated band gap reference is integrated in the EL7558BC. The external CREF capacitor acts as the dominant pole of the amplifier and can be increased in size to maximize transient noise rejection. A value of 0.1uF is recommended. R3 V OUT = 1.0V × 1 + ------ × Volt R 4 Oscillator However, due to the relatively low open loop gain of the system, gain errors will occur as the output voltage and loop-gain are changed. This is shown in the performance curves. (The output voltage is factory trimmed to minimize error at a 2.50V output). A 2µA pull-up current from FB1 to VIN forces VOUT to GND in the event that FB1 is not used and the VCC2DET is inadvertently toggled between the internal and external feedback mode of operation. The system clock is generated by an internal relaxation oscillator with a maximum duty-cycle of approximately 96%. Operating frequency can be adjusted through the COSC pin or can be driven by an external clock source. If the oscillator is driven by an external source, care must be taken in the selection of CSLOPE. Since the COSC and CSLOPE values determine the open loop gain of the system, changes to COSC require corresponding changes to CSLOPE in order to maintain a constant gain ratio. The recommended ratio of COSC to CSLOPE is 1.5:1 NMOS Power FETS and Drive Circuitry Temperature Sensor The EL7558BC integrates low resistance (25mΩ) NMOS FETS to achieve high efficiency at 8A. Gate An internal temperature sensor continuously monitors die temperature. In the event that die temperature 11 EL7558BC EL7558BC Integrated Adjustable 8 Amp Synchronous Switcher EL7558BC EL7558BC Integrated Adjustable 8 Amp Synchronous Switcher exceeds the thermal trip-point, the OT pin will output a logic 0. The upper and lower trip points are set to 135 ºC and 100ºC respectively. To enable thermal shutdown this pin should be tied directly to OUTEN. Use of this feature is recommended during normal operation with the application of air flow. For example, the addition of 100LFM reduces the thermal resistance by approximately 15% and can extend the operating ambient to 77ºC (typical). Since the thermal performance of the IC is heavily dependent on the board layout, the system designer should exercise care during the design phase to ensure that the IC will operate under the worstcase environmental conditions. Power Good and Power On Reset During power up the output regulator will be disabled until VIN reaches 4.0V. Approximately 500mV of hysteresis is present to eliminate noise induced oscillations. Under-voltage and over-voltage conditions on the regulator output are detected through an internal window comparator. A logic 1 on the PWRGD output indicates that regulated output voltage is within ±10% of the nominally programmed output voltage. Although small, the typical values of the PWRGD threshold will vary with changes to external feedback (and resultant loop gain) of the system. This dependence is shown in the typical performance curves. Thermal Management The EL7558BC utilizes HSOP packaging technology in conjunction with the system board layout to achieve a lower thermal resistance than typically found in standard 28 lead SOIC packages. By attaching the die directly to an exposed metal slug embedded within the package body, thermal energy flows through a thermally conductive path (metal) instead of thermally resistive plastic. After conducting heat from the die to the PCB, heat transfer occurs by convection. If a significant amount of metal on the PCB is connected to the exposed heat slug, a junction-to-ambient resistance of 31ºC/W can be achieved compared to 100ºC/W found in standard packages. It can be readily seen that the thermal resistance approaches an asymptotic value of approximately 31ºC/W. Additional information can be found in Application Note #8 (Measuring the Thermal Resistance of Power Surface-Mount Packages), and Application Note #13 (EL75XX Thermal Design Considerations). If the thermal shutdown pin is connected to OUTEN the IC will enter thermal shutdown when the maximum junction temperature is reached. For a thermal shutdown of 135ºC and power dissipation of 2.2W the ambient temperature is limited to a maximum value of 67ºC (typical). The ambient temperature range can be extended 12 EL7558BC EL7558BC Integrated Adjustable 8 Amp Synchronous Switcher General Disclaimer Specifications contained in this data sheet are in effect as of the publication date shown. Elantec, Inc. reserves the right to make changes in the circuitry or specifications contained herein at any time without notice. Elantec, Inc. assumes no responsibility for the use of any circuits described herein and makes no representations that they are free from patent infringement. WARNING - Life Support Policy Elantec, Inc. products are not authorized for and should not be used within Life Support Systems without the specific written consent of Elantec, Inc. Life Support systems are equipment intended to support or sustain life and whose failure to perform when properly used in accordance with instructions provided can be reasonably expected to result in significant personal injury or death. Users contemplating application of Elantec, Inc. Products in Life Support Systems are requested to contact Elantec, Inc. factory headquarters to establish suitable terms & conditions for these applications. Elantec, Inc.’s warranty is limited to replacement of defective components and does not cover injury to persons or property or other consequential damages. April 27, 2001 Elantec Semiconductor, Inc. 675 Trade Zone Blvd. Milpitas, CA 95035 Telephone: (408) 945-1323 (888) ELANTEC Fax: (408) 945-9305 European Office: 441-18-977-6020 Japan Technical Center: 81-45-682-5820 13 Printed in U.S.A.