CC1070 CC1070 Single Chip Low Power RF Transmitter for Narrowband Systems Applications • Narrowband low power UHF wireless data transmitters • 402 / 424 / 426 / 429 / 433 / 447 / 449 / 469 / 868 and 915 MHz ISM/SRD band systems • TPMS – Tire Pressure Monitoring Systems • • • • AMR – Automatic Meter Reading Wireless alarm and security systems Home automation Low power telemetry Product Description CC1070 is a true single-chip UHF transmitter designed for very low power and very low voltage wireless applications. The circuit is mainly intended for the ISM (Industrial, Scientific and Medical) and SRD (Short Range Device) frequency bands at 402, 424, 426, 429, 433, 447, 449, 469, 868 and 915 MHz, but can easily be programmed for multi-channel operation at other frequencies in the 402 470 and 804 - 940 MHz range. CC1070 will be used together with a microcontroller and a few external passive components. CC1070 is based on Chipcon’s SmartRF® 02 technology in 0.35 µm CMOS. The CC1070 is especially suited for narrowband systems with channel spacings of 12.5 or 25 kHz complying with ARIB STD T-67 and EN 300 220. The CC1070 main operating parameters can be programmed via a serial bus, thus making CC1070 a very flexible and easy to use transmitter. In a typical application Features • True single chip UHF RF transmitter • Frequency range 402 - 470 MHz and 804 - 940 MHz • Programmable output power • Low supply voltage (2.3 to 3.6 V) • Very few external components required • Small size (QFN 20 package) • Pb-free package • Data rate up to 153.6 kBaud • OOK, FSK and GFSK data modulation • Fully on-chip VCO SWRS043 • Programmable frequency makes crystal temperature drift compensation possible without TCXO • Suitable for frequency hopping systems • Suited for systems targeting compliance with EN 300 220, FCC CFR47 part 15 and ARIB STD T-67 • Development kit available • Easy-to-use software for generating the CC1070 configuration data Page 1 of 58 CC1070 Table of Contents 1 Abbreviations................................................................................................................ 4 2 Absolute Maximum Ratings ........................................................................................ 5 3 Operating Conditions ................................................................................................... 5 4 Electrical Specifications .............................................................................................. 5 4.1 RF Transmit Section ............................................................................................ 6 4.2 Crystal Oscillator Section..................................................................................... 8 4.3 Frequency Synthesizer Section ........................................................................... 9 4.4 Digital Inputs / Outputs ...................................................................................... 10 4.5 Current Consumption......................................................................................... 11 5 Pin Assignment........................................................................................................... 12 6 Circuit Description...................................................................................................... 13 7 Application Circuit...................................................................................................... 13 8 Configuration Overview ............................................................................................. 16 8.1 9 Configuration Software ...................................................................................... 16 Microcontroller Interface ........................................................................................... 17 9.1 4-wire Serial Configuration Interface ................................................................. 18 9.2 Signal Interface .................................................................................................. 20 10 Data Rate Programming............................................................................................. 22 11 Frequency Programming ........................................................................................... 23 11.1 12 Dithering ......................................................................................................... 24 Transmitter .................................................................................................................. 24 12.1 FSK Modulation Formats ............................................................................... 24 12.2 OOK Modulation............................................................................................. 24 12.3 Output Power Programming........................................................................... 25 12.4 TX Data Latency............................................................................................. 26 12.5 Reducing Spurious Emission and Modulation Bandwidth ............................. 26 13 Output Matching and Filtering .................................................................................. 26 14 Frequency Synthesizer .............................................................................................. 29 14.1 VCO, Charge Pump and PLL Loop Filter....................................................... 29 14.2 VCO and PLL Self-Calibration ....................................................................... 30 14.3 PLL Turn-on Time versus Loop Filter Bandwidth .......................................... 31 14.4 PLL Lock Time versus Loop Filter Bandwidth ............................................... 32 15 VCO Current Control .................................................................................................. 32 16 Power Management.................................................................................................... 33 17 Crystal Oscillator ........................................................................................................ 34 18 Built-in Test Pattern Generator ................................................................................. 36 SWRS043 Page 2 of 58 CC1070 19 Interrupt upon PLL Lock ............................................................................................ 36 20 PA_EN Digital Output Pin .......................................................................................... 36 20.1 Interfacing an External PA ............................................................................. 36 20.2 General Purpose Output Control Pins ........................................................... 36 20.3 PA_EN Pin Drive ............................................................................................ 37 21 System Considerations and Guidelines................................................................... 37 22 PCB Layout Recommendations ................................................................................ 39 23 Antenna Considerations ............................................................................................ 39 24 Configuration Registers............................................................................................. 40 24.1 25 CC1070 Register Overview............................................................................ 41 Package Description (QFN 20) .................................................................................. 52 25.1 Package Marking ........................................................................................... 53 25.2 Recommended PCB footprint for package (QFN 20) .................................... 54 25.3 Package Thermal Properties ......................................................................... 54 25.4 Soldering Information ..................................................................................... 54 25.5 Tray Specification........................................................................................... 55 25.6 Carrier Tape and Reel Specification .............................................................. 55 26 Ordering Information.................................................................................................. 55 27 General Information.................................................................................................... 56 28 Address Information................................................................................................... 58 SWRS043 Page 3 of 58 CC1070 1 Abbreviations ACP AMR ASK BOM bps BT CW DNM ESR FHSS FM FS FSK GFSK IC ISM kbps MCU NA NRZ OOK PA PD PCB PN9 PLL PSEL RF SPI SRD TBD TX UHF VCO XOSC XTAL Adjacent Channel Power Automatic Meter Reading Amplitude Shift Keying Bill Of Materials bits per second Bandwidth-Time product (for GFSK) Continuous Wave Do Not Mount Equivalent Series Resistance Frequency Hopping Spread Spectrum Frequency Modulation Frequency Synthesizer Frequency Shift Keying Gaussian Frequency Shift Keying Integrated Circuit Industrial Scientific Medical kilo bits per second Micro Controller Unit Not Applicable Non Return to Zero On-Off Keying Power Amplifier Phase Detector / Power Down Printed Circuit Board Pseudo-random Bit Sequence (9-bit) Phase Locked Loop Program Select Radio Frequency Serial Peripheral Interface Short Range Device To Be Decided/Defined Transmit (mode) Ultra High Frequency Voltage Controlled Oscillator Crystal oscillator Crystal SWRS043 Page 4 of 58 CC1070 2 Absolute Maximum Ratings The absolute maximum ratings given Table 1 should under no circumstances be violated. Stress exceeding one or more of the limiting values may cause permanent damage to the device. Min Max Unit Supply voltage, VDD Parameter -0.3 5.0 V Voltage on any pin Storage temperature range Package body temperature Humidity non-condensing -0.3 -50 VDD+0.3, max 5.0 150 260 85 V °C °C % 5 Condition All supply pins must have the same voltage Norm: IPC/JEDEC J-STD-020C 1 Table 1. Absolute maximum ratings 1 The reflow peak soldering temperature (body temperature) is specified according to IPC/JEDEC J-STD-020C “Moisture/Reflow Sensitivity Classification for Nonhermetic Solid State Surface Mount Devices”. Caution! ESD sensitive device. Precaution should be used when handling the device in order to prevent permanent damage. 3 Operating Conditions The operating conditions for CC1070 are listed in Table 2. Parameter Min Typ Max Unit RF Frequency Range 402 804 470 940 MHz MHz Operating ambient temperature range -40 105 °C Supply voltage 2.3 3.6 V 3.0 Condition / Note Programmable in <300 Hz steps Programmable in <600 Hz steps The same supply voltage should be used for digital (DVDD) and analog (AVDD) power. A 3.0 ±0.1 V supply is recommended to meet the ARIB STD T-67 output power tolerance requirement. Table 2. Operating conditions 4 Electrical Specifications Table 3 to Table 7 gives the CC1070 electrical specifications. All measurements were performed using the 2 layer PCB CC1070EM reference design. This is the same test circuit as shown in Figure 3. Temperature = 25°C, supply voltage = AVDD = DVDD = 3.0 V if nothing else stated. Crystal frequency = 14.7456 MHz. The electrical specifications given for 868 MHz are also applicable for the 902 – 928 MHz frequency range. SWRS043 Page 5 of 58 CC1070 4.1 RF Transmit Section Parameter Transmit data rate Min. Typ. 0.45 Max. Unit 153.6 kBaud Condition / Note The data rate is programmable. See section 10 on page 22 for details. NRZ or Manchester encoding can be used. 153.6 kBaud equals 153.6 kbps using NRZ coding and 76.8 kbps using Manchester coding. See section 9.2 on page 20 for details. Binary FSK frequency separation 0 0 108 216 kHz kHz in 402 - 470 MHz range in 804 - 940 MHz range 108/216 kHz is the maximum guaranteed separation at 1.84 MHz reference frequency. Larger separations can be achieved at higher reference frequencies. Output power 433 MHz -20 to +10 dBm 868 MHz -20 to +8 dBm -4 +3 dB dB nd -50 -60 dBc dBc nd -50 -57 dBc dBc Output power tolerance Delivered to 50 Ω single-ended load. The output power is programmable and should not be programmed to exceed +10/+8 dBm at 433/868 MHz under any operating conditions. See section 13 on page 26 for details. At maximum output power o At 2.3 V, +105 C o At 3.6 V, -40 C Harmonics, radiated CW 2 harmonic, 433 MHz, +10 dBm rd 3 harmonic, 433 MHz, +10 dBm 2 harmonic, 868 MHz, +8 dBm rd 3 harmonic, 868 MHz, +8 dBm Adjacent channel power (GFSK) 12.5 kHz channel spacing, 433 MHz -47 dBc 25 kHz channel spacing, 868 MHz -50 dBc Harmonics are measured as EIRP values according to EN 300 220. The antenna (SMAFF-433 and SMAFF-868 from R.W. Badland) plays a part in attenuating the harmonics. For 12.5 kHz channel spacing ACP is measured in a ±4.25 kHz bandwidth at ±12.5 kHz offset. Modulation: 2.4 kBaud NRZ PN9 sequence, ±2.025 kHz frequency deviation. For 25 kHz channel spacing ACP is measured in a ±8.5 kHz bandwidth at ±25 kHz offset. Modulation: 4.8 kBaud NRZ PN9 sequence, ±2.475 kHz frequency deviation. Occupied bandwidth (99.5%,GFSK) Bandwidth for 99.5% of total average power. 12.5 kHz channel spacing, 433 MHz 7 kHz 25 kHz channel spacing, 868 MHz 10 kHz Modulation for 12.5 channel spacing: 2.4 kBaud NRZ PN9 sequence, ±2.025 kHz frequency deviation. Modulation for 25 kHz channel spacing: 4.8 kBaud NRZ PN9 sequence, ±2.475 kHz frequency deviation. SWRS043 Page 6 of 58 CC1070 Parameter Min. Typ. Max. Unit Condition / Note Modulation bandwidth, 868 MHz 19.2 kBaud, ±9.9 kHz frequency deviation 48 kHz 38.4 kBaud, ±19.8 kHz frequency deviation 106 kHz Spurious emission, radiated CW Bandwidth where the power envelope of modulation equals –36 dBm. Spectrum analyzer RBW = 1 kHz. At maximum output power, +10/+8 dBm at 433/868 MHz. 47-74, 87.5-118, 174-230, 470-862 MHz -54 dBm 9 kHz – 1 GHz -36 dBm 1 – 4 GHz -30 dBm To comply with EN 300 220, FCC CFR47 part 15 and ARIB STD T-67 an external (antenna) filter, as implemented in the application circuit in Figure 14, must be used and tailored to each individual design to reduce out-of-band spurious emission levels. Spurious emissions can be measured as EIRP values according to EN 300 220. The antenna (SMAFF-433 and SMAFF-868 from R.W. Badland) plays a part in attenuating the spurious emissions. If the output power is increased using an external PA, a filter must be used to attenuate spurs below 862 MHz when operating in the 868 MHz frequency band in Europe. Application Note AN036 CC1020/1021 Spurious Emission presents and discusses a solution that reduces the TX mode spurious emission close to 862 MHz by increasing the REF_DIV from 1 to 7. Optimum load impedance 433 MHz 868 MHz 915 MHz 91 + j16 34 + j25 28 + j21 Ω Ω Ω Transmit mode. For matching details see section 13 on page 26. Table 3. RF transmit parameters SWRS043 Page 7 of 58 CC1070 4.2 Crystal Oscillator Section Parameter Crystal Oscillator Frequency Min. Typ. Max. Unit 4.9152 14.7456 19.6608 MHz Crystal operation Crystal load capacitance Parallel 4-6 MHz, 22 pF recommended 6-8 MHz, 16 pF recommended 8-20 MHz, 16 pF recommended 1.55 0.90 0.95 0.63 ms ms ms ms 4.9152 MHz, 12 pF load 9.8304 MHz, 12 pF load 14.7456 MHz, 16 pF load 19.6608 MHz, 12 pF load 300 mVpp External clock signal drive, full-swing digital external clock 0 - VDD V Reference frequency accuracy requirement +/- 5.7 +/- 2.8 ppm ppm 433 MHz (EN 300 220) 868 MHz (EN 300 220) Must be less than ±5.7 / ±2.8 ppm to comply with EN 300 220 25 kHz channel spacing at 433/868 MHz. +/- 4 ppm Must be less than ±4 ppm to comply with Japanese 12.5 kHz channel spacing regulations (ARIB STD T-67). NOTE: This imposes special requirements on the receiver of the signal. +/- 7 ppm Must be less than ±7 ppm to comply with Korean 12.5 kHz channel spacing regulations. NOTE: This imposes special requirements on the receiver of the signal. External clock signal drive, sine wave 22 16 16 C4 and C5 are loading capacitors. See section 17 on page 34 for details. pF pF pF Crystal oscillator start-up time 12 12 12 Condition / Note 30 30 16 The external clock signal must be connected to XOSC_Q1 using a DC block (10 nF). Set XOSC_BYPASS = 0 in the INTERFACE register when using an external clock signal with low amplitude or a crystal. The external clock signal must be connected to XOSC_Q1. No DC block shall be used. Set XOSC_BYPASS = 1 in the INTERFACE register when using a full-swing digital external clock NOTE: The reference frequency accuracy (initial tolerance) and drift (aging and temperature dependency) will determine the frequency accuracy of the transmitted signal. Crystal oscillator temperature compensation can be done using the fine frequency programmability. Table 4. Crystal oscillator parameters SWRS043 Page 8 of 58 CC1070 4.3 Frequency Synthesizer Section Parameter Min. Typ. Max. Unit Phase noise, 402 – 470 MHz Condition / Note Unmodulated carrier 12.5 kHz channel spacing −87 −95 −100 −105 −114 dBc/Hz dBc/Hz dBc/Hz dBc/Hz dBc/Hz At 12.5 kHz offset from carrier At 25 kHz offset from carrier At 50 kHz offset from carrier At 100 kHz offset from carrier At 1 MHz offset from carrier Measured using loop filter components given in Table 10. The phase noise will be higher for larger PLL loop filter bandwidth. Phase noise, 804 - 940 MHz Unmodulated carrier 25 kHz channel spacing −81 −89 −96 −103 −122 dBc/Hz dBc/Hz dBc/Hz dBc/Hz dBc/Hz At 12.5 kHz offset from carrier At 25 kHz offset from carrier At 50 kHz offset from carrier At 100 kHz offset from carrier At 1 MHz offset from carrier Measured using loop filter components given in Table 10. The phase noise will be higher for larger PLL loop filter bandwidth. PLL loop bandwidth 12.5 kHz channel spacing, 433 MHz 5 kHz 25 kHz channel spacing, 868 MHz 7 kHz PLL lock time (TX_1 / TX_2 turn time) 12.5 kHz channel spacing, 433 MHz 180 us 25 kHz channel spacing, 868 MHz 270 us 500 kHz channel spacing 14 us PLL turn-on time. From power down mode with crystal oscillator running. 12.5 kHz channel spacing, 433 MHz 3.2 ms 25 kHz channel spacing, 868 MHz 2.5 ms 500 kHz channel spacing 700 us After PLL and VCO calibration. The PLL loop bandwidth is programmable One channel frequency step to RF frequency within ±10% of channel spacing. Depends on loop filter component values and PLL_BW register setting. See Table 20 on page 32 for more details. Time from writing to registers to RF frequency within ±10% of channel spacing. Depends on loop filter component values and PLL_BW register setting. See Table 19 on page 32 for more details. Table 5. Frequency synthesizer parameters SWRS043 Page 9 of 58 CC1070 4.4 Digital Inputs / Outputs Parameter Min Typ Max Unit Condition / Note Logic "0" input voltage 0 0.3* VDD V Logic "1" input voltage 0.7* VDD VDD V Logic "0" output voltage 0 0.4 V Output current −2.0 mA, 3.0 V supply voltage Logic "1" output voltage 2.5 VDD V Output current 2.0 mA, 3.0 V supply voltage Logic "0" input current NA −1 µA Input signal equals GND. PSEL has an internal pull-up resistor and during configuration the current will be -350 µA. µA Input signal equals VDD 20 ns TX mode, minimum time DIO must be ready before the positive edge of DCLK. Data should be set up on the negative edge of DCLK. 10 ns TX mode, minimum time DIO must be held after the positive edge of DCLK. Data should be set up on the negative edge of DCLK. Logic "1" input current NA DIO setup time DIO hold time 1 Serial interface (PCLK, PDI, PDO and PSEL) timing specification See Table 11 on page 20 for more details PA_EN pin drive 0.90 0.87 0.81 0.69 mA mA mA mA Source current 0 V on PA_EN pin 0.5 V on PA_EN pin 1.0 V on PA_EN pin 1.5 V on PA_EN pin 0.93 0.92 0.89 0.79 mA mA mA mA Sink current 3.0 V on PA_EN pin 2.5 V on PA_EN pin 2.0 V on PA_EN pin 1.5 V on PA_EN pin Table 6. Digital inputs / outputs parameters SWRS043 Page 10 of 58 CC1070 4.5 Current Consumption Parameter Power Down mode Min. Typ. Max. Unit Condition / Note 0.2 1 µA Oscillator core off The output power is delivered to a 50 Ω single-ended load. Current consumption, 433/868 MHz: P = −20 dBm 12.3/13.9 mA P = −5 dBm 14.7/16.8 mA P = 0 dBm 17.5/20.5 mA P = +5 dBm 21.5/25.3 mA P = +8 dBm 25.5/33.1 mA P = +10 dBm 31/NA mA Current consumption, crystal oscillator 65 µA 14.7456 MHz, 16 pF load crystal Current consumption, crystal oscillator and bias 500 µA 14.7456 MHz, 16 pF load crystal Current consumption, crystal oscillator, bias and synthesizer 7.5 mA 14.7456 MHz, 16 pF load crystal See section 12.3 on page 25 for more details. Table 7. Current consumption SWRS043 Page 11 of 58 CC1070 5 Pin Assignment Table 8 provides an overview of the CC1070 pinout. The CC1070 comes in a QFN20 type (see page 52 for details). VC 16 AVDD 17 CHP_OUT 18 DVDD 19 PSEL 20 PCLK DI PDI PDO DVDD 1 2 3 4 5 15 AVDD 14 PA_EN 13 AVDD 12 RF_OUT 11 R_BIAS 10 9 8 7 6 AVDD XOSC_Q2 XOSC_Q1 LOCK DCLK AGND Exposed die attached pad Figure 1. CC1070 package (top view) Pin no. - Pin name AGND Pin type Ground (analog) 1 2 3 4 5 6 7 PCLK DI PDI PDO DVDD DCLK LOCK Digital input Digital input Digital input Digital output Power (digital) Digital output Digital output 8 9 10 XOSC_Q1 XOSC_Q2 AVDD Analog input Analog output Power (analog) 11 12 13 R_BIAS RF_OUT AVDD Analog output RF output Power (analog) 14 PA_EN Digital output 15 16 17 18 19 20 AVDD VC AVDD CHP_OUT DVDD PSEL Power (analog) Analog input Power (analog) Analog output Power (digital) Digital input Description Exposed die attached pad. Must be soldered to a solid ground plane as this is the ground connection for all analog modules See page 39 for more details. Programming clock for SPI configuration interface Data input in transmit mode Programming data input for SPI configuration interface Programming data output for SPI configuration interface Power supply (3 V typical) for digital modules and digital I/O Clock for transmit data PLL Lock indicator, active low. Output is asserted (low) when PLL is in lock. The pin can also be used as a general digital output. Crystal oscillator or external clock input Crystal oscillator Power supply (3 V typical) for crystal oscillator and bias generator (double bonded). Connection for external precision bias resistor (82 kΩ, ± 1%) RF signal output to antenna Power supply (3 V typical) for LO buffers, prescaler and PA first stage General digital output. Can be used for controlling an external PA, if higher output power is needed. Power supply (3 V typical) for VCO VCO control voltage input from external loop filter Power supply (3 V typical) for charge pump and phase detector PLL charge pump output to external loop filter Power supply connection (3 V typical) for digital modules Programming chip select, active low, for configuration interface. Internal pull-up resistor. Table 8. Pin assignment overview Note: DCLK, DI and LOCK are high-impedance (3-state) in power down (BIAS_PD = 1 in the MAIN register). SWRS043 The exposed die attached pad must be soldered to solid ground plane as this is the main ground connection for the chip. Page 12 of 58 CC1070 Circuit Description :2 FREQ SYNTH :2 CONTROL LOGIC 6 DIGITAL INTERFACE TO µC LOCK DI DCLK Power Control PDO DIGITAL MODULATOR Multiplexer - Modulation - Data shaping - Power Control RF_OUT BIAS XOSC XOSC_Q1 XOSC_Q2 R_BIAS VC PDI PCLK PSEL CHP_OUT Figure 2. CC1070 simplified block diagram A simplified block diagram of CC1070 is shown in Figure 2. Only signal pins are shown. During transmit operation, the synthesized RF frequency is fed directly to the power amplifier (PA). The RF output is frequency shift keyed (FSK) by the digital bit stream that is fed to the DI pin. Optionally, the internal Gaussian filter can be enabled for Gaussian FSK (GFSK). 7 The frequency synthesizer includes a completely on-chip LC VCO. The VCO operates in the frequency range 1.6081.880 GHz. The CHP_OUT pin is the charge pump output and VC is the control node of the on-chip VCO. The external loop filter is placed between these pins. A crystal is to be connected between XOSC_Q1 and XOSC_Q2. A lock signal is available from the PLL. The 4-wire SPI serial interface is used for configuration. Application Circuit Very few external components are required for the operation of CC1070. A typical application circuit is shown in Figure 3. The external components are described in Table 9 and values are given in Table 10. Output matching L2, C2 and C3 are used to match the transmitter to 50 Ω. See section 13 on page 26 for details. Component values for the matching network are easily calculated using the SmartRF® Studio software. data rates up to 4.8 kBaud. Component values for higher data rates are easily found using the SmartRF® Studio software. Crystal An external crystal with two loading capacitors (C4 and C5) is used for the crystal oscillator. See section 17 on page 34 for details. Bias resistor The precision bias resistor R1 is used to set an accurate bias current. Additional filtering Additional external components (e.g. RF LC or SAW filter) may be used in order to improve the performance in specific applications. See section 13 on page 26 for further information. PLL loop filter The loop filter consists of two resistors (R2 and R3) and three capacitors (C6-C8). C7 and C8 may be omitted in applications where high loop bandwidth is desired. The values shown in Table 10 can be used for Power supply decoupling and filtering Power supply decoupling and filtering must be used (not shown in the application circuit). The placement and size of the decoupling capacitors and the power supply filtering are very important to SWRS043 Page 13 of 58 CC1070 achieve the optimum performance for narrowband applications. Chipcon provides a reference design that should be followed very closely. C6 C7 C8 R2 R3 2 3 4 PCLK 16 AVDD=3V AVDD=3V VC 17 AVDD 18 AVDD=3V CHP_OUT 19 DVDD PSEL 1 R6 AVDD DI PA_EN CC1070 PDI AVDD 15 C60 14 Monopole antenna (50 Ohm) 13 C2 PDO RF_OUT L2 12 LC filter XTAL C4 AVDD R_BIAS 10 XOSC_Q2 9 8 LOCK DVDD 7 5 DCLK DVDD=3V XOSC_Q1 C3 6 Microcontroller configuration interface and signal interface 20 DVDD=3V 11 R1 AVDD=3V C5 Figure 3. Typical application and test circuit (power supply decoupling not shown) Ref C2 C3 C4 C5 C6 C7 C8 C60 L2 R1 R2 R3 R6 XTAL Description PA match, see page 26 PA output match and dc block, see page 26 Crystal load capacitor, see page 34 Crystal load capacitor, see page 34 PLL loop filter capacitor PLL loop filter capacitor (may be omitted for highest loop bandwidth) PLL loop filter capacitor (may be omitted for highest loop bandwidth) Decoupling capacitor PA match and DC bias (supply voltage), see page 26 Precision resistor for current reference generator PLL loop filter resistor PLL loop filter resistor PA output match, see page 26 Crystal, see page 34 Table 9. Overview of external components (excluding supply decoupling capacitors) SWRS043 Page 14 of 58 CC1070 Item C2 C3 C4 C5 C6 C7 C8 C60 L2 R1 R2 R3 R6 XTAL 433 MHz 2.2 pF, 5%, NP0, 0402 5.6 pF, 5%, NP0, 0402 22 pF, 5%, NP0, 0402 12 pF, 5%, NP0, 0402 220 nF, 10%, X7R, 0603 8.2 nF, 10%, X7R, 0402 2.2 nF, 10%, X7R, 0402 220 pF, 5%, NP0, 0402 22 nH, 5%, 0402 82 kΩ, 1%, 0402 1.5 kΩ, 5%, 0402 4.7 kΩ, 5%, 0402 82 Ω, 5%, 0402 14.7456 MHz crystal, 16 pF load 868 MHz 1.5 pF, 5%, NP0, 0402 10 pF, 5%, NP0, 0402 22 pF, 5%, NP0, 0402 12 pF, 5%, NP0, 0402 100 nF, 10%, X7R, 0603 3.9 nF, 10%, X7R, 0402 1.0 nF, 10%, X7R, 0402 220 pF, 5%, NP0, 0402 6.8 nH, 5%, 0402 82 kΩ, 1%, 0402 2.2 kΩ, 5%, 0402 6.8 kΩ, 5%, 0402 82 Ω, 5%, 0402 14.7456 MHz crystal, 16 pF load 915 MHz 1.5 pF, 5%, NP0, 0402 10 pF, 5%, NP0, 0402 22 pF, 5%, NP0, 0402 12 pF, 5%, NP0, 0402 100 nF, 10%, X7R, 0603 3.9 nF, 10%, X7R, 0402 1.0 nF, 10%, X7R, 0402 220 pF, 5%, NP0, 0402 6.8 nH, 5%, 0402 82 kΩ, 1%, 0402 2.2 kΩ, 5%, 0402 6.8 kΩ, 5%, 0402 82 Ω, 5%, 0402 14.7456 MHz crystal, 16 pF load Note: Items shaded vary for different frequencies. For 433 MHz, 12.5 kHz channel, a loop filter with lower bandwidth is used to improve adjacent and alternate channel rejection. Table 10. Bill of materials for the application circuit in Figure 3 Note: The PLL loop filter component values in Table 10 (R2, R3, C6-C8) can be used for data rates up to 4.8 kBaud. The SmartRF® Studio software provides component values for other data rates using the equations on page 29. SWRS043 In the CC1070EM reference design LQG15HS series inductors from Murata have been used. Page 15 of 58 CC1070 8 Configuration Overview CC1070 can be configured to achieve optimum performance for different applications. Through the programmable configuration registers the following key parameters can be programmed: • RF output power • Frequency synthesizer key parameters: RF output frequency, FSK 8.1 • • • • • frequency separation, crystal oscillator reference frequency Power-down / power-up mode Crystal oscillator power-up / power down Data rate and data format (NRZ, Manchester coded or UART interface) Synthesizer lock indicator mode FSK / GFSK / OOK modulation Configuration Software Chipcon provides users of CC1070 with a software program, SmartRF® Studio (Windows interface) that generates all necessary CC1070 configuration data based on the user's selections of various parameters. These hexadecimal numbers will then be the necessary input to the microcontroller for the configuration of CC1070. In addition, the program will provide the user with the component values needed for the output matching circuit, the PLL loop filter and the LC filter. Figure 4 shows the user interface of the CC1070 configuration software. Figure 4. SmartRF® Studio user interface SWRS043 Page 16 of 58 CC1070 9 Microcontroller Interface Used in a typical system, CC1070 will interface to a microcontroller. This microcontroller must be able to: purposes when the configuration interface is not used. PDI, PDO and PCLK are high impedance inputs as long as PSEL is not activated (active low). • Program CC1070 into different modes via the 4-wire serial configuration interface (PDI, PDO, PCLK and PSEL) • Interface to the synchronous data signal interface (DI and DCLK) • Optionally, the microcontroller can do data encoding • Optionally, the microcontroller can monitor the LOCK pin for frequency lock status or other status information. PSEL has an internal pull-up resistor and should be left open (tri-stated by the microcontroller) or set to a high level during power down mode in order to prevent a trickle current flowing in the pullup. Signal interface The DI pin is used for data to be transmitted. DCLK providing the data timing should be connected to a microcontroller input. Configuration interface The microcontroller interface is shown in Figure 5. The microcontroller uses 3 or 4 I/O pins for the configuration interface (PDI, PDO, PCLK and PSEL). PDO should be connected to a microcontroller input. PDI, PCLK and PSEL must be microcontroller outputs. One I/O pin can be saved if PDI and PDO are connected together and a bi-directional pin is used at the microcontroller. PLL lock signal Optionally, one microcontroller pin can be used to monitor the LOCK signal. This signal is at low logic level when the PLL is in lock. It can also be used to monitor other internal test signals. The microcontroller pins connected to PDI, PDO and PCLK can be used for other CC1070 PCLK PDI PDO PSEL (Optional) Microcontroller DI DCLK LOCK (Optional) Figure 5. Microcontroller interface SWRS043 Page 17 of 58 CC1070 9.1 4-wire Serial Configuration Interface CC1070 is configured via a simple 4-wire SPI-compatible interface (PDI, PDO, PCLK and PSEL) where CC1070 is the slave. There are 22 8-bit configuration registers and 6 8-bit test-only registers, each addressed by a 7-bit address. A Read/Write bit initiates a read or write operation. A full configuration of CC1070 requires sending 22 data frames of 16 bits each (7 address bits, R/W bit and 8 data bits). The time needed for a full configuration depends on the PCLK frequency. With a PCLK frequency of 10 MHz the full configuration is done in less than 36 µs. Setting the device in power down mode requires sending one frame only and will in this case take less than 2 µs. All registers are also readable. In each write-cycle, 16 bits are sent on the PDI-line. The seven most significant bits of each data frame (A6:0) are the addressbits. A6 is the MSB (Most Significant Bit) of the address and is sent as the first bit. The next bit is the R/W bit (high for write, low for read). The 8 data-bits are then transferred (D7:0). During address and data transfer the PSEL (Program SELect) must be kept low. See Figure 6. The timing for the programming is also shown in Figure 6 with reference to Table 11. The clocking of the data on PDI is SWRS043 done on the positive edge of PCLK. Data should be set up on the negative edge of PCLK by the microcontroller. When the last bit, D0, of the 8 data-bits has been loaded, the data word is loaded in the internal configuration register. The configuration data will be retained during a programmed power-down mode, but not when the power-supply is turned off. The registers can be programmed in any order. The configuration registers can also be read by the microcontroller via the same configuration interface. The seven address bits are sent first, then the R/W bit set low to initiate the data read-back. CC1070 then returns the data from the addressed register. PDO is used as the data output and must be configured as an input by the microcontroller. The PDO is set at the negative edge of PCLK and should be sampled at the positive edge. The read operation is illustrated in Figure 7. PSEL must be set high between each read/write operation. There are registers. also 5 read-only status Page 18 of 58 CC1070 TSS THS TCL,min TCH,min THD TSD PCLK Address PDI 6 5 4 Write mode 3 2 1 0 W Data byte 7 6 5 4 3 2 1 0 PDO PSEL Figure 6. Configuration registers write operation TSS THS TCL,min TCH,min PCLK Address PDI 6 5 4 Read mode 3 2 1 0 R Data byte PDO PSEL 7 6 5 4 3 2 1 0 TSH Figure 7. Configuration registers read operation SWRS043 Page 19 of 58 CC1070 Parameter Symbol Min Max Unit 10 MHz Conditions PCLK, clock frequency FPCLK PCLK low pulse duration TCL,min 50 ns The minimum time PCLK must be low. PCLK high pulse duration TCH,min 50 ns The minimum time PCLK must be high. PSEL setup time TSS 25 ns The minimum time PSEL must be low before positive edge of PCLK. PSEL hold time THS 25 ns The minimum time PSEL must be held low after the negative edge of PCLK. PSEL high time TSH 50 ns The minimum time PSEL must be high. PDI setup time TSD 25 ns The minimum time data on PDI must be ready before the positive edge of PCLK. PDI hold time THD 25 ns The minimum time data must be held at PDI, after the positive edge of PCLK. Rise time Trise 100 ns The maximum rise time for PCLK and PSEL Fall time Tfall 100 ns The maximum fall time for PCLK and PSEL Note: The setup and hold times refer to 50% of VDD. The rise and fall times refer to 10% / 90% of VDD. The maximum load that this table is valid for is 20 pF. Table 11. Serial interface, timing specification 9.2 Signal Interface The CC1070 can be used with NRZ (NonReturn-to-Zero) data or Manchester (also known as bi-phase-level) encoded data. The data format is controlled by the DATA_FORMAT[1:0] bits in the MODEM register. CC1070 can be configured different data formats: for three Synchronous NRZ mode During transmit operation, the CC1070 provides the data clock at DCLK and DI is used as data input. Data is clocked into CC1070 at the rising edge of DCLK. The data is modulated at RF without encoding. See Figure 8. SWRS043 Synchronous Manchester encoded mode During transmit operation, the CC1070 provides the data clock at DCLK and DI is used as data input. Data is clocked into CC1070 at the rising edge of DCLK and should be in NRZ format. The data is modulated at RF with Manchester code. The encoding is done by CC1070. In this mode the effective bit rate is half the baud rate due to the coding. As an example, 19.2 kBaud Manchester encoded data corresponds to a 9.6 kbps. See Figure 9. Transparent Asynchronous UART mode During transmit operation, DI is used as data input. The data is modulated at RF without synchronization or encoding. In this mode, the DCLK pin is not active and can be set to a high or low level by DATA_FORMAT[0]. See Figure 10. Page 20 of 58 CC1070 Manchester encoding and decoding In the Synchronous Manchester encoded mode CC1070 uses Manchester coding when modulating the data. The Manchester code is based on transitions; a “0” is encoded as a low-to-high transition, a “1” is encoded as a high-tolow transition. See Figure 11. The Manchester code ensures that the signal has a constant DC component, which is necessary in some FSK receivers/demodulators. Using this mode also ensures compatibility with e.g. CC400/CC900 designs. DCLK Clock provided by CC1070 DI Data provided by microcontroller "RF" FSK modulating signal internal in CC1070 Figure 8. Synchronous NRZ mode DCLK Clock provided by CC1070 DI Data provided by microcontroller "RF" FSK modulating signal internal in CC1070 Figure 9. Synchronous Manchester encoded mode DCLK DCLK is not used. It can be set to default low or high. DI Data provided by microcontroller "RF" FSK modulating signal internal in CC1070 Figure 10. Transparent Asynchronous UART mode SWRS043 Page 21 of 58 CC1070 1 0 1 1 0 0 0 1 1 0 1 Time Figure 11. Manchester encoding 10 Data Rate Programming The data rate (baud rate) is programmable and depends on the crystal frequency and the programming of the CLOCK (CLOCK_A and CLOCK_B) registers. The baud rate (B.R) is given by B.R. = f xosc 8 ⋅ ( REF _ DIV + 1) ⋅ DIV 1 ⋅ DIV 2 where DIV1 and DIV2 are given by the value of MCLK_DIV1 and MCLK_DIV2. Table 14 shows some possible data rates as a function of crystal frequency in synchronous mode. In asynchronous transparent UART mode any data rate up to 153.6 kBaud can be used. SWRS043 MCLK_DIV1[2:0] 000 001 010 011 100 101 110 111 DIV1 2.5 3 4 7.5 12.5 40 48 64 Table 12. DIV1 for different settings of MCLK_DIV1 MCLK_DIV2[1:0] 00 01 10 11 DIV2 1 2 4 8 Table 13. DIV2 for different settings of MCLK_DIV2 Page 22 of 58 CC1070 Data rate [kBaud] 0.45 0.5 0.6 0.9 1 1.2 1.8 2 2.4 3.6 4 4.096 4.8 7.2 8 8.192 9.6 14.4 16 16.384 19.2 28.8 32 32.768 38.4 57.6 64 65.536 76.8 115.2 128 153.6 Crystal frequency [MHz] 9.8304 12.288 14.7456 X X X X X X X X X X X X X X X X X X X X X X X X X X X X X X X X X X X X X X X X X 4.9152 7.3728 X X X X X X X X X X X X X X X X X X X X X X X X X X X X X X X X 17.2032 19.6608 X X X X X X X X X X X X X X X X X X X X X X X X X X Table 14. Some possible data rates versus crystal frequency 11 Frequency Programming Programming the frequency word in the configuration registers sets the operation frequency. There are two frequency words registers, termed FREQ_A and FREQ_B, which can be programmed to two different frequencies. They can be used for two different channels. The F_REG bit in the MAIN register selects frequency word A or B. The frequency word is located in FREQ_2A:FREQ_1A:FREQ_0A and FREQ_2B:FREQ_1B:FREQ_0B for the FREQ_A and FREQ_B word respectively. The LSB of the FREQ_0 registers are used to enable dithering, section 11.1. The PLL output frequency is given by: ⎛ 3 FREQ + 0.5 ⋅ DITHER ⎞ f c = f ref ⋅ ⎜ + ⎟ 32768 ⎝4 ⎠ in the frequency band 402 – 470 MHz, and ⎛ 3 FREQ + 0.5 ⋅ DITHER ⎞ f c = f ref ⋅ ⎜ + ⎟ 16384 ⎝2 ⎠ in the frequency band 804 – 940 MHz. The BANDSELECT bit in the ANALOG register controls the frequency band used. BANDSELECT = 0 gives 402 – 470 MHz, and BANDSELECT = 1 gives 804 - 940 MHz. The reference frequency is the crystal oscillator clock frequency divided by REF_DIV (3 bits in the CLOCK_A or CLOCK_B register), a number between 1 and 7: f ref = SWRS043 f xosc REF _ DIV + 1 Page 23 of 58 CC1070 FSK frequency deviation is programmed in the DEVIATION register. The deviation programming is divided into a mantissa (TXDEV_M[3:0]) and an exponent (TXDEV_X[2:0]). Generally REF_DIV should be as low as possible but the following requirements must be met 9.8304 ≥ f ref > fc [MHz ] 256 f1 = fc + fdev where fdev is set by the DEVIATION register: f dev = f ref ⋅ TXDEV _ M ⋅ 2 (TXDEV _ X −16 ) in the frequency band 402 - 470 MHz, and in the frequency band 402 – 470 MHz, and 9.8304 ≥ f ref > f0 = fc − fdev f dev = f ref ⋅ TXDEV _ M ⋅ 2 (TXDEV _ X −15) in the frequency band 804 - 940 MHz. fc [MHz ] 512 OOK (On-Off Keying) TXDEV_M[3:0] = 0000. in the frequency band 804 – 940 MHz. The PLL output frequency equation above gives the carrier frequency, fc , in transmit mode (center frequency). The two FSK modulation frequencies are given by: is used if The TX_SHAPING bit in the DEVIATION register controls Gaussian shaping of the modulation signal. 11.1 Dithering Spurious signals will occur at certain frequencies depending on the division ratios in the PLL. To reduce the strength of these spurs, a common technique is to use a dithering signal in the control of the frequency dividers. Dithering is activated by setting the DITHER bit in the FREQ_0 registers. It is recommended to use the dithering in order to achieve the best possible performance. 12 Transmitter 12.1 FSK Modulation Formats The data modulator can modulate FSK, which is a two level FSK (Frequency Shift Keying), or GFSK, which is a Gaussian filtered FSK with BT = 0.5. The purpose of the GFSK is to make a more bandwidth efficient system. The modulation and the Gaussian filtering are done internally in the chip. The TX_SHAPING bit in the DEVIATION register enables the GFSK. GFSK is recommended for narrowband operation. 12.2 OOK Modulation The data modulator can also do OOK (OnOff Keying) modulation. OOK is an ASK (Amplitude Shift Keying) modulation using 100% modulation depth. SWRS043 OOK modulation is enabled by setting TXDEV_M[3:0] = 0000 in the DEVIATION register. Page 24 of 58 CC1070 12.3 Output Power Programming The RF output power from the device is programmable by the 8-bit PA_POWER register. Figure 12 and Figure 13 shows the output power and total current consumption as a function of the PA_POWER register setting. It is more efficient in terms of current consumption to use either the lower or upper 4-bits in the register to control the power, as shown in the figures. However, the output power can be controlled in finer steps using all the available bits in the PA_POWER register. 35.0 30.0 Current [mA] / Output power [dBm] 25.0 20.0 15.0 10.0 5.0 0.0 -5.0 -10.0 -15.0 -20.0 -25.0 -30.0 0 1 2 3 4 5 6 7 8 9 0A 0B 0C 0D 0E 0F 50 60 70 80 90 A0 B0 C0 D0 E0 F0 FF PA_POWER [hex] Output Pow er Current Consumption Figure 12. Output power settings and typical current consumption, 433 MHz 35.0 30.0 Current [mA] / Output power [dBm] 25.0 20.0 15.0 10.0 5.0 0.0 -5.0 -10.0 -15.0 -20.0 -25.0 -30.0 0 1 2 3 4 5 6 7 8 9 0A 0B 0C 0D 0E 0F 50 60 70 80 90 A0 B0 C0 D0 E0 F0 FF PA_POWER [hex] Output Pow er Current Consumption Figure 13. Output power settings and typical current consumption, 868 MHz SWRS043 Page 25 of 58 CC1070 12.4 TX Data Latency The transmitter will add a delay due to the synchronization of the data with DCLK and further clocking into the modulator. The user should therefore add a delay equivalent to at least 2 bits after the data payload has been transmitted before switching off the PA (i.e. before stopping the transmission). 12.5 Reducing Spurious Emission and Modulation Bandwidth Modulation bandwidth and spurious emission are normally measured with the PA continuously on and a repeated test sequence. In cases where the modulation bandwidth and spurious emission are measured with the CC1070 switching from power down mode to TX mode, a PA ramping sequence could be used to minimize modulation bandwidth and spurious emission. PA ramping should then be used both when switching the PA on and off. A linear PA ramping sequence can be used where register PA_POWER is changed from 00h to 0Fh and then from 50h to the register setting, which gives the desired output power (e.g. C0h for +5 dBm output power at 868 MHz operation). The longer the time per PA ramping step the better, but setting the total PA ramping time equal to 2 bit periods is a good compromise between performance and PA ramping time. 13 Output Matching and Filtering When designing the impedance matching network for the CC1070 the circuit must be matched correctly at the harmonic frequencies as well as at the fundamental tone. A recommended matching network is shown in Figure 14. Component values for various frequencies are given in Table 15. Component values for other frequencies can be found using the SmartRF® Studio software. coefficient, especially at the higher harmonics. For this reason, the frequency response of the matching network should be measured and compared to the response of the Chipcon reference design. Refer to Figure 15 and Table 16 as well as Figure 16 and Table 17. A recommended application circuit is available from the Chipcon web site (CC1070EM). It is important to remember that the physical layout and the components used contribute significantly to the reflection Item C2 C3 C60 C71 L2 L70 L71 R6 433 MHz 2.2 pF, 5%, NP0, 0402 5.6 pF, 5%, NP0, 0402 220 pF, 5%, NP0, 0402 4.7 pF, 5%, NP0, 0402 22 nH, 5%, 0402 47 nH, 5%, 0402 47 nH, 5%, 0402 82 Ω, 5%, 0402 868 MHz 1.5 pF, 5%, NP0, 0402 10 pF, 5%, NP0, 0402 220 pF, 5%, NP0, 0402 3.3 pF, 5%, NP0, 0402 6.8 nH, 5%, 0402 12 nH, 5%, 0402 12 nH, 5%, 0402 82 Ω, 5%, 0402 915 MHz 1.5 pF, 5%, NP0, 0402 10 pF, 5%, NP0, 0402 220 pF, 5%, NP0, 0402 3.3 pF, 5%, NP0, 0402 6.8 nH, 5%, 0402 12 nH, 5%, 0402 12 nH, 5%, 0402 82 Ω, 5%, 0402 Table 15. Component values for the matching network described in Figure 14 (DNM = Do Not Mount). SWRS043 Page 26 of 58 CC1070 AVDD=3V R6 ANTENNA C60 CC1070 L2 C2 C3 RF_OUT L71 L72 C71 Figure 14. Output matching network 433 MHz Figure 15. Typical optimum PA load impedance, 433 MHz. The frequency is swept from 300 MHz to 2500 MHz. Values are listed in Table 16 Frequency (MHz) Real (Ohms) Imaginary (Ohms) 433 91 16 866 80 -323 1299 1.1 -54 1732 0.4 -23 2165 1.3 -5.3 Table 16. Impedances at the first 5 harmonics (433 MHz matching network) SWRS043 Page 27 of 58 CC1070 868 MHz 915 MHz Figure 16. Typical optimum PA load impedance, 868/915 MHz. The frequency is swept from 300 MHz to 2800 MHz. Values are listed in Table 17 Frequency (MHz) Real (Ohms) Imaginary (Ohms) 868 34 25 915 28 21 1736 84 -232 1830 31 -130 2604 3.3 -4.7 2745 2.6 2.3 Table 17. Impedances at the first 3 harmonics (868/915 MHz matching network) SWRS043 Page 28 of 58 CC1070 14 Frequency Synthesizer 14.1 VCO, Charge Pump and PLL Loop Filter The VCO is completely integrated and operates in the 1608 – 1880 MHz range. A frequency divider is used to get a frequency in the UHF range (402 – 470 and 804 – 940 MHz). The BANDSELECT bit in the ANALOG register selects the frequency band. The VCO frequency is given by: FREQ + 0.5 ⋅ DITHER ⎞ ⎛ f VCO = f ref ⋅ ⎜ 3 + ⎟ 8192 ⎝ ⎠ The VCO frequency is divided by 2 and by 4 to generate frequencies in the two bands, respectively. The VCO sensitivity (sometimes referred to as VCO gain) varies over frequency and operating conditions. Typically the VCO sensitivity varies between 12 and 36 MHz/V. For calculations the geometrical mean at 21 MHz/V can be used. The PLL calibration (explained below) measures the actual VCO sensitivity and adjusts the charge pump current accordingly to achieve correct PLL loop gain and bandwidth (higher charge pump current when VCO sensitivity is lower). The following equations can be used for calculating PLL loop filter component values, see Figure 3, for a desired PLL loop bandwidth, BW: C7 = 3037 (fref / BW2) –7 R2 = 7126 (BW / fref) C6 = 80.75 (fref / BW2) R3 = 21823 (BW / fref) C8 = 839 (fref / BW2) –6 [pF] [kΩ] [nF] [kΩ] [pF] C6 = 220 nF C7 = 8200 pF C8 = 2200 pF R2 = 1.5 kΩ R3 = 4.7 kΩ 2) If the data rate is 4.8 kBaud or below and the RF operating frequency is in the 804 – 940 MHz frequency range the following loop filter components are recommended: C6 = 100 nF C7 = 3900 pF C8 = 1000 pF R2 = 2.2 kΩ R3 = 6.8 kΩ After calibration the PLL bandwidth is set by the PLL_BW register in combination with the external loop filter components calculated above. The PLL_BW can be found from PLL_BW = 146 + 16 log2(fref /7.126) where fref is the reference frequency (in MHz). The PLL loop filter bandwidth increases with increasing PLL_BW setting. After calibration the applied charge pump current (CHP_CURRENT[3:0]) can be read in the STATUS1 register. The charge pump current is approximately given by: Define a minimum PLL loop bandwidth as BWmin = 1) If the data rate is 4.8 kBaud or below and the RF operating frequency is in the 402 – 470 MHz frequency range the following loop filter components are recommended: 80.75 ⋅ f ref 220 . If BWmin > Baud rate/3 then set BW = BWmin and if BWmin < Baud rate/3 then set BW = Baud rate/3 in the above equations. There are two special cases when using the recommended 14.7456 MHz crystal: SWRS043 I CHP = 16 ⋅ 2 CHP _ CURRENT 4 [uA] The combined charge pump and phase detector gain (in A/rad) is given by the charge pump current divided by 2π. The PLL bandwidth will limit the maximum modulation frequency and hence data rate. Page 29 of 58 CC1070 14.2 VCO and PLL Self-Calibration To compensate for supply voltage, temperature and process variations, the VCO and PLL must be calibrated. The calibration is performed automatically and sets the maximum VCO tuning range and optimum charge pump current for PLL stability. After setting up the device at the operating frequency, the self-calibration can be initiated by setting the CAL_START bit in the CALIBRATE register. The calibration result is stored internally in the chip, and is valid as long as power is not turned off. If large supply voltage drops (typically more than 0.25 V) or temperature variations (typically more than 40oC) occur after calibration, a new calibration should be performed. The nominal VCO control voltage is set by the CAL_ITERATE[2:0] bits in the CALIBRATE register. The CAL_COMPLETE bit in the STATUS register indicates that calibration has finished. The calibration wait time (CAL_WAIT) is programmable and is proportional to the internal PLL reference frequency. The highest possible reference frequency should be used to get the minimum calibration time. It is recommended to use CAL_WAIT[1:0] = 11 in order to get the most accurate loop bandwidth. The CAL_COMPLETE bit can also be monitored at the LOCK pin, configured by LOCK_SELECT[3:0] = 0101, and used as an interrupt input to the microcontroller. To check that the PLL is in lock the user should monitor the LOCK_CONTINUOUS bit in the STATUS register. The LOCK_CONTINUOUS bit can also be monitored at the LOCK pin, configured by LOCK_SELECT[3:0] = 0010. There are separate calibration values for the two frequency registers. However, dual calibration is possible if all of the below conditions apply: SWRS043 • • • The two frequencies A and B differ by less than 1 MHz Reference frequencies are equal (REF_DIV_A[2:0] = REF_DIV_B[2:0] in the CLOCK_A/CLOCK_B registers) VCO currents are equal (VCO_CURRENT_A[3:0] = VCO_CURRENT_B[3:0] in the VCO register). The CAL_DUAL bit in the CALIBRATE register controls dual or separate calibration. The single calibration algorithm (CAL_DUAL = 0) is illustrated in Figure 17. The same algorithm is applicable for dual calibration if CAL_DUAL = 1. Chipcon recommends that single calibration be used for more robust operation. There is a small, but finite, possibility that the PLL self-calibration will fail. The calibration routine in the source code should include a loop so that the PLL is recalibrated until PLL lock is achieved if the PLL does not lock the first time. Refer to CC1070 Errata Note 001. The CAL_SELECT bit is used to select the calibration routine. When set high, a fast calibration routine is used. The table below shows the calibration time when CAL_SELECT = 1: Calibration time [ms] CAL_WAIT 00 01 10 11 Reference frequency [MHz] 7.3728 1.0 1.5 2.9 3.9 Table 18. Typical calibration time when CAL_SELECT = 1 Page 30 of 58 CC1070 Start calibration fref is the reference frequency (in MHz) Write FREQ_A, FREQ_B, VCO, CLOCK_A and CLOCK_B registers. PLL_BW = 146 + 16log2(fref/7.126) Calibrate TX frequency register A (MAIN = 91h) or B (MAIN = D1h) Register CALIBRATE = 3Ch Write MAIN register = 91h or D1h: F_REG=0 (or 1), PD_MODE=1, FS_PD=0, CORE_PD=0, BIAS_PD=0, RESET_N=1 Start calibration Write CALIBRATE register = BCh Wait for T ≥ 100 us Read STATUS register and wait until CAL_COMPLETE=1 Read STATUS register and wait until LOCK_CONTINUOUS=1 Calibration OK? No Yes End of calibration Figure 17. Calibration algorithm 14.3 PLL Turn-on Time versus Loop Filter Bandwidth If calibration has been performed the PLL turn-on time is the time needed for the PLL to lock to the desired frequency when going from power down mode (with the crystal oscillator running) to TX mode. The SWRS043 PLL turn-on time depends on the PLL loop filter bandwidth. Table 19 gives the PLL turn-on time for different PLL loop filter bandwidths. Page 31 of 58 CC1070 C6 [nF] 220 C7 [pF] 8200 C8 [pF] 2200 R2 [kΩ] 1.5 R3 [kΩ] 4.7 PLL turn-on time [us] 3200 100 56 15 3900 2200 560 1000 560 150 2.2 3.3 5.6 6.8 10 18 2500 1400 1300 3.9 120 33 12 39 1080 1.0 27 3.3 27 82 950 0.2 1.5 - 47 150 700 Comment Up to 4.8 kBaud data rate, 12.5 kHz channel spacing Up to 4.8 kBaud data rate, 25 kHz channel spacing Up to 9.6 kBaud data rate, 50 kHz channel spacing Up to 19.2 kBaud data rate, 100 kHz channel spacing Up to 38.4 kBaud data rate, 150 kHz channel spacing Up to 76.8 kBaud data rate, 200 kHz channel spacing Up to 153.6 kBaud data rate, 500 kHz channel spacing Table 19. Typical PLL turn-on time to within ±10% of channel spacing for different loop filter bandwidths 14.4 PLL Lock Time versus Loop Filter Bandwidth If calibration has been performed the PLL lock time is the time needed for the PLL to lock to the desired frequency when going from one transmit frequency to the next by changing the F_REG bit in the MAIN register. The PLL lock time depends on the PLL loop filter bandwidth. Table 20 gives the PLL lock time for different PLL loop filter bandwidths. C6 [nF] C7 [pF] C8 [pF] R2 [kΩ] R3 [kΩ] 220 8200 2200 1.5 4.7 PLL lock time [us] 1 2 180 1300 100 3900 1000 2.2 6.8 270 830 56 2200 560 3.3 10 140 490 15 560 150 5.6 18 70 230 3.9 120 33 12 39 50 180 1.0 27 3.3 27 82 15 55 0.2 1.5 - 47 150 14 28 Comment Up to 4.8 kBaud data rate, 12.5 kHz channel spacing Up to 4.8 kBaud data rate, 25 kHz channel spacing Up to 9.6 kBaud data rate, 50 kHz channel spacing Up to 19.2 kBaud data rate, 100 kHz channel spacing Up to 38.4 kBaud data rate, 150 kHz channel spacing Up to 76.8 kBaud data rate, 200 kHz channel spacing Up to 153.6 kBaud data rate, 500 kHz channel spacing Table 20. Typical PLL lock time to within ±10% of channel spacing for different loop filter bandwidths. 1) 1 channel step, 2) 1 MHz step 15 VCO Current Control The VCO current is programmable and should be set according to operating frequency and output power. Recommended settings for the VCO_CURRENT bits in the VCO register are shown in the register overview (page 40) and also given by SmartRF® Studio. SWRS043 The VCO current for frequency FREQ_A and FREQ_B can be programmed independently. The bias current for the PA buffers is also programmable. The BUFF_CURRENT register controls this current. Page 32 of 58 CC1070 16 Power Management CC1070 offers great flexibility for power management in order to meet strict power consumption requirements in batteryoperated applications. Power down mode is controlled through the MAIN register. There are separate bits to control the TX part, the frequency synthesizer and the crystal oscillator in the MAIN register. This individual control can be used to optimize for lowest possible current consumption in each application. Figure 18 shows a typical power-on and initializing sequences for minimum power consumption. Power Off Turn on power R Reset CC1070 MAIN:: FREG = 0 PD_MODE = 1,, FS_PD = 1, XOSC_PD = 1, BIAS_PD = 1, RESET_N = 0 Figure 19 shows a typical sequence for activating TX mode from power down mode for minimum power consumption. MAIN: RESET_N = 1 Note that PSEL should be tri-stated or set to a high level during power down mode in order to prevent a trickle current from flowing in the internal pull-up resistor. Program all necessary registers except MAIN and RESET Chipcon recommends resetting the CC1070 (by clearing the RESET_N bit in the MAIN register) when the chip is powered up initially. All registers that need to be configured should then be programmed (those which differ from their default values). Registers can be programmed freely in any order. The CC1070 should then be calibrated. After this is completed, the CC1070 is ready for use. See the detailed procedure flowcharts in Figure 17 - Figure 19. Application Note AN023 CC1020 MCU Interfacing provides source code for CC1020. This source code can be used as a starting point when writing source code for CC1070 . Turn on crystal oscillator, bias generator and synthesizer successively Calibrate VCO and PLL MAIN: PD_MODE = 1, FS_PD = 1, XOSC_PD = 1, BIAS_PD = 1 PA_POWER = 00h Power Down mode Figure 18. Initializing sequence SWRS043 Page 33 of 58 CC1070 Power Down mode Turn on crystal oscillator core MAIN: PD_MODE=1, FS_PD=1, XOSC_PD=0, BIAS_PD=1 PA_POWER: 00h Wait 1.2 ms* *Time to wait depends on the crystal frequency and the load capacitance Turn on bias generator MAIN: BIAS_PD = 0 Wait 150 µs Turn on frequency synthesizer MAIN: F_REG=1, FS_PD=0 Wait until lock is detected from LOCK pin or STATUS register Turn on TX: MAIN: PD_MODE = 0 Wait 100 µs then set PA_POWER TX mode Set PA_POWER = 00h Wait 100 µs Turn off TX: MAIN: PD_MODE = 1, FS_PD=1, XOSC_PD=1, BIAS_PD=1 Power Down mode Figure 19. Sequence for activating TX mode 17 Crystal Oscillator Any crystal frequency in the range 4 - 20 MHz can be used. The crystal frequency is used as reference for the data rate (as well as other internal functions) and in the 4 – 20 MHz range the frequencies 4.9152, SWRS043 7.3728, 9.8304, 12.2880, 14.7456, 17.2032, 19.6608 MHz will give accurate data rates as shown in Table 14. The crystal frequency will influence the Page 34 of 58 CC1070 programming of the CLOCK_A, CLOCK_B and MODEM registers. CL = An external clock signal or the internal crystal oscillator can be used as main frequency reference. An external clock signal should be connected to XOSC_Q1, while XOSC_Q2 should be left open. The XOSC_BYPASS bit in the INTERFACE register should be set to ‘1’ when an external digital rail-to-rail clock signal is used. No DC block should be used then. A sine with smaller amplitude can also be used. A DC blocking capacitor must then be used (10 nF) and the XOSC_BYPASS bit in the INTERFACE register should be set to ‘0’. For input signal amplitude, see section 4.2 on page 8. 1 1 1 + C 4 C5 + C parasitic The parasitic capacitance is constituted by pin input capacitance and PCB stray capacitance. Total parasitic capacitance is typically 8 pF. A trimming capacitor may be placed across C5 for initial tuning if necessary. The crystal oscillator circuit is shown in Figure 20. Typical component values for different values of CL are given in Table 21. The crystal oscillator is amplitude regulated. This means that a high current is required to initiate the oscillations. When the amplitude builds up, the current is reduced to what is necessary to maintain approximately 600 mVpp amplitude. This ensures a fast start-up, keeps the drive level to a minimum and makes the oscillator insensitive to ESR variations. As long as the recommended load capacitance values are used, the ESR is not critical. Using the internal crystal oscillator, the crystal must be connected between the XOSC_Q1 and XOSC_Q2 pins. The oscillator is designed for parallel mode operation of the crystal. In addition, loading capacitors (C4 and C5) for the crystal are required. The loading capacitor values depend on the total load capacitance, CL, specified for the crystal. The total load capacitance seen between the crystal terminals should equal CL for the crystal to oscillate at the specified frequency. The initial tolerance, temperature drift, aging and load pulling should be carefully specified in order to meet the required frequency accuracy in a certain application. XOSC_Q1 XOSC_Q2 XTAL C4 C5 Figure 20. Crystal oscillator circuit Item C4 C5 CL= 12 pF 6.8 pF 6.8 pF CL= 16 pF 15 pF 15 pF CL= 22 pF 27 pF 27 pF Table 21. Crystal oscillator component values SWRS043 Page 35 of 58 CC1070 18 Built-in Test Pattern Generator The CC1070 has a built-in test pattern generator that generates a PN9 pseudo random sequence. The PN9_ENABLE bit in the MODEM register enables the PN9 generator. A transition on the DI pin is required after enabling the PN9 pseudo random sequence. The PN9 pseudo random sequence is defined by the polynomial x9 + x5 + 1. The PN9 generator can be used for transmission of ‘real-life’ data when measuring narrowband ACP (Adjacent Channel Power), modulation bandwidth or occupied bandwidth. 19 Interrupt upon PLL Lock In synchronous mode the DCLK pin on CC1070 can be used to give an interrupt signal to wake the microcontroller when the PLL is locked. frequency the DCLK signal changes to logic 0. When this interrupt has been detected write PD_MODE[1:0] = 00. This will enable the DCLK signal. PD_MODE[1:0] in the MAIN register should be set to 01. If DCLK_LOCK in the INTERFACE register is set to 1 the DCLK signal is always logic high if the PLL is not in lock. When the PLL locks to the desired This function can be used to wait for the PLL to be locked before the PA is ramped up. 20 PA_EN Digital Output Pin 20.1 Interfacing an External PA CC1070 has a digital output pin, PA_EN, which can be used to control an external PA. The functionality of this pin is controlled through the INTERFACE register. The output can also be used as a general digital output control signal. EXT_PA_POL controls the active polarity of the signal. EXT_PA controls the function of the pin. If EXT_PA = 1, then the PA_EN pin will be activated when the internal PA is turned on. Otherwise, the EXT_PA_POL bit controls the PA_EN pin directly. This pin can therefore also be used as a general control signal, see section 20.2. 20.2 General Purpose Output Control Pins The digital output pin, PA_EN, can be used as a general control signal by setting EXT_PA = 0. The output value is then set directly by the value written to EXT_PA_POL. The LOCK pin can also be used as a general-purpose output pin. The LOCK pin is controlled by LOCK_SELECT[3:0] in the SWRS043 LOCK register. The LOCK pin is low when LOCK_SELECT[3:0] = 0000, and high when LOCK_SELECT[3:0] = 0001. These features can be used to save I/O pins on the microcontroller when the other functions associated with these pins are not used. Page 36 of 58 CC1070 20.3 PA_EN Pin Drive Figure 21 shows the PA_EN pin drive currents. The sink and source currents have opposite signs but absolute values are used in Figure 21. 1400 1200 Current [uA] 1000 800 600 400 200 3.6 3.4 3.2 3 2.8 2.6 2.4 2.2 2 1.8 1.6 1.4 1.2 1 0.8 0.6 0.4 0.2 0 0 Voltage on PA_EN pin [V] source current, 3 V sink current, 3V source current, 2.3 V sink current, 2.3 V source current, 3.6 V sink current, 3.6 V Figure 21. Typical PA_EN pin drive 21 System Considerations and Guidelines SRD regulations International regulations and national laws regulate the use of radio receivers and transmitters. SRDs (Short Range Devices) for license free operation are allowed to operate in the 433 and 868 - 870 MHz bands in most European countries. In the United States, such devices operate in the 260 – 470 and 902 - 928 MHz bands. A summary of the most important aspects of these regulations can be found in Application Note AN001 SRD regulations for license free transceiver operation, available from the Chipcon web site. Japan and Korea have allocated several frequency bands at 424, 426, 429, 449 and 469 MHz for narrowband license free operation. CC1070 is designed to meet the requirements for operation in all these bands, including the strict requirements for narrowband operation down to 12.5 kHz channel spacing. Narrow band systems CC1070 is specifically designed for narrowband systems complying with ARIB STD T-67 and EN 300 220. The CC1070 meets the strict requirements to ACP (Adjacent Channel Power) and occupied bandwidth for a narrowband transmitter. To meet the ARIB STD T-67 requirements a 3.0 V regulated voltage supply should be used. A unique feature in CC1070 is the very fine frequency resolution. This can be used for temperature compensation of the crystal if the temperature drift curve is known and a temperature sensor is included in the system. Even initial adjustment can be performed using the frequency programmability. This eliminates the need for an expensive TCXO and trimming in some applications. For more details refer SWRS043 Such narrowband performance normally requires the use of external ceramic filters. The CC1070 provides this performance as a true single-chip solution. Page 37 of 58 CC1070 to Application Note AN027 Temperature Compensation available from the Chipcon web site. In less demanding applications, a crystal with low temperature drift and low aging could be used without further compensation. A trimmer capacitor in the crystal oscillator circuit (in parallel with C5) could be used to set the initial frequency accurately. CC1070 also has the possibility to use Gaussian shaped FSK (GFSK). This spectrum-shaping feature improves adjacent channel power (ACP) and occupied bandwidth. In ‘true’ FSK systems with abrupt frequency shifting, the spectrum is inherently broad. By making the frequency shift ‘softer’, the spectrum can be made significantly narrower. Thus, higher data rates can be transmitted in the same bandwidth using GFSK. Low cost systems As the CC1070 provide true narrowband multi-channel performance without any external filters, a very low cost high performance system can be achieved. The oscillator crystal can then be a low cost crystal with 50 ppm frequency tolerance using the on-chip frequency tuning possibilities. Battery operated systems In low power applications the power down mode should be used when CC1070 is not being active. Depending on the start-up time requirement the oscillator core can be powered during power down. See section 16 on page 33 for information on how effective power management can be implemented. Frequency hopping spread spectrum systems (FHSS) Due to the very fast locking properties of the PLL, the CC1070 is also very suitable for frequency hopping systems. Hop rates of 1-100 hops/s are commonly used depending on the bit rate and the amount of data to be sent during each transmission. The two frequency registers (FREQ_A and FREQ_B) are designed such that the ‘next’ frequency can be programmed while the ‘present’ frequency SWRS043 is used. The switching between the two frequencies is performed through use of the MAIN register. For more details refer to Application Note AN014 Frequency Hopping Systems available from the Chipcon web site. In order to implement a frequency hopping system with CC1070 do the following: Set the desired frequency, calibrate and store the following register settings in nonvolatile memory: STATUS1[3:0]: CHP_CURRENT[3:0] STATUS2[4:0]: VCO_ARRAY[4:0] STATUS3[5:0]:VCO_CAL_CURRENT[5:0] Repeat the calibration for each desired frequency. VCO_CAL_CURRENT[5:0] is not dependent on the RF frequency and the same value can be used for all frequencies. When performing frequency hopping, write the stored values to the corresponding TEST1, TEST2 and TEST3 registers, and enable override: TEST1[3:0]: CHP_CO[3:0] TEST2[4:0]: VCO_AO[4:0] TEST2[5]: VCO_OVERRIDE TEST2[6]: CHP_OVERRIDE TEST3[5:0]: VCO_CO[5:0] TEST3[6]: VCO_CAL_OVERRIDE CHP_CO[3:0] is the register setting read from CHP_CURRENT[3:0], VCO_AO[4:0] is the register setting read from VCO_ARRAY[4:0] and VCO_CO[5:0] is the register setting read from VCO_CAL_CURRENT[5:0]. Assume channel 1 defined by register FREQ_A is currently being used and that CC1070 should operate on channel 2 next (to change channel simply write to register MAIN[6]). The channel 2 frequency can be set by register FREQ_B which can be written to while operating on channel 1. The calibration data must be written to the TEST1-3 registers after switching to the next frequency. That is, when hopping to a new channel write to register MAIN[6] first and the test registers next. The PA should be switched off between each hop and the PLL should be checked for lock before Page 38 of 58 CC1070 switching the PA back on after a hop has been performed. Note that the override bits VCO_OVERRIDE, CHP_OVERRIDE and VCO_CAL_OVERRIDE must be disabled when performing a re-calibration. 22 PCB Layout Recommendations A two layer PCB with all components placed on the top layer can be used. The bottom layer of the PCB should be the “ground-layer”. The top layer should be used for signal routing, and the open areas should be filled with metallization connected to ground using several vias. The area under the chip is used for grounding and must be connected to the bottom ground plane with several vias. In the Chipcon reference designs we have placed 8 vias inside the exposed die attached pad. These vias should be “tented” (covered with solder mask) on the component side of the PCB to avoid migration of solder through the vias during the solder reflow process. Each decoupling capacitor should be placed as close as possible to the supply pin it is supposed to decouple. Each decoupling capacitor should be connected to the power line (or power plane) by separate vias. The best routing is from the power line (or power plane) to the decoupling capacitor and then to the CC1070 supply pin.. Supply power filtering is very important, especially for the VCO supply (pin 15). Each decoupling capacitor ground pad should be connected to the ground plane using a separate via. Direct connections between neighboring power pins will increase noise coupling and should be avoided unless absolutely necessary. The external components should ideally be as small as possible and surface mount devices are highly recommended. Precaution should be used when placing the microcontroller in order to avoid noise interfering with the RF circuitry. A CC1020/1070DK Development Kit with a fully assembled CC1070EM Evaluation Module is available. It is strongly advised that this reference layout is followed very closely in order to obtain the best performance. The layout Gerber files are available from the Chipcon web site. 23 Antenna Considerations CC1070 can be used together with various types of antennas. The most common antennas for short-range communication are monopole, helical and loop antennas. Monopole antennas are resonant antennas with a length corresponding to one quarter of the electrical wavelength (λ/4). They are very easy to design and can be implemented simply as a “piece of wire” or even integrated onto the PCB. Non-resonant monopole antennas shorter than λ/4 can also be used, but at the expense of range. In size and cost critical applications such an antenna may very well be integrated onto the PCB. SWRS043 Helical antennas can be thought of as a combination of a monopole and a loop antenna. They are a good compromise in size critical applications. But helical antennas tend to be more difficult to optimize than the simple monopole. Loop antennas are easy to integrate into the PCB, but are less effective due to difficult impedance matching because of their very low radiation resistance. For low power applications the λ/4monopole antenna is recommended due to its simplicity as well as providing the Page 39 of 58 CC1070 best range. The length of the λ/4monopole antenna is given by: L = 7125 / f where f is in MHz, giving the length in cm. An antenna for 868 MHz should be 8.2 cm, and 16.4 cm for 433 MHz. The antenna should be connected as close as possible to the IC. If the antenna is located away from the input pin the antenna should be matched to the feeding transmission line (50 Ω). For a more thorough background on antennas, please refer to Application Note AN003 SRD Antennas available from the Chipcon web site. 24 Configuration Registers The configuration of CC1070 is done by programming the 8-bit configuration registers. The configuration data based on selected system parameters are most easily found by using the SmartRF® Studio software. Complete descriptions of the registers are given in the following tables. After a RESET is programmed, all the registers have default values. The TEST registers also get default values after a SWRS043 RESET, and should not be altered by the user. Chipcon recommends using the register settings found using the SmartRF® Studio software. These are the register settings that Chipcon can guarantee across temperature, voltage and process. Please check the Chipcon web site for regularly updates to the SmartRF® Studio software. Page 40 of 58 CC1070 24.1 CC1070 Register Overview ADDRESS 00h 01h 02h 03h 04h 05h 06h 07h 08h 09h 0Ah 0Bh 0Ch 0Dh 0Eh 0Fh 10h 11h 12h 13h 14h 15h 16h 17h 18h 19h 1Ah 1Bh 1Ch 1Dh 1Eh 1Fh 20h 21h 22h 23h 24h 25h 26h 27h 28h 40h 41h 42h 43h 44h 45h 46h 47h 48h 49h 4Ah 4Bh Byte Name MAIN INTERFACE RESET FREQ_2A FREQ_1A FREQ_0A CLOCK_A FREQ_2B FREQ_1B FREQ_0B CLOCK_B VCO_CUR MODEM DEVIATION LOCK ANALOG BUFF_SWING BUFF_CURRENT PLL_BW CALIBRATE PA_POWER POWERDOWN TEST1 TEST2 TEST3 TEST4 TEST5 TEST_NFC STATUS RESET_DONE STATUS1 STATUS2 STATUS3 - Description Main control register Interface control register Digital module reset register Not used Frequency register 2A Frequency register 1A Frequency register 0A Clock generation register A Frequency register 2B Frequency register 1B Frequency register 0B Clock generation register B VCO current control register Modem control register TX frequency deviation register Not used Not used Not used Not used Not used Not used Lock control register Not used Analog modules control register LO buffer and prescaler swing control register LO buffer and prescaler bias current control register PLL loop bandwidth / charge pump current control register PLL calibration control register Power amplifier output power register Not used Not used Not used Power-down control register Test register for overriding PLL calibration Test register for overriding PLL calibration Test register for overriding PLL calibration Test register for charge pump and IF chain testing Test register for ADC testing Not used Not used Test register for calibration Status information register (PLL lock, RSSI, calibration ready, etc.) Status register for digital module reset Not used Not used Not used Status of PLL calibration results etc. (test only) Status of PLL calibration results etc. (test only) Status of PLL calibration results etc. (test only) Not used Not used Not used Not used SWRS043 Page 41 of 58 CC1070 MAIN Register (00h) REGISTER NAME Active F_REG PD_MODE[1:0] Default value 1 - MAIN[7] MAIN[6] MAIN[5:4] MAIN[3] MAIN[2] MAIN[1] FS_PD XOSC_PD BIAS_PD - H H H MAIN[0] RESET_N - L - Description reserved Selection of Frequency Register, 0: Register A, 1: Register B Power down mode 0 (00): Normal operation 1 (01): PA in power-down. 2 (10): Individual modules can be put in power-down by programming the POWERDOWN register 3 (11): reserved Power Down of Frequency Synthesizer Power Down of Crystal Oscillator Core Power Down of BIAS (Global Current Generator) and Crystal Oscillator Buffer Reset, active low. Writing RESET_N low will write default values to all other registers than MAIN. Bits in MAIN do not have a default value and will be written directly through the configuration interface. Must be set high to complete reset. INTERFACE Register (01h) REGISTER NAME Active XOSC_BYPASS Default value 0 INTERFACE[7] INTERFACE[6] INTERFACE[5] DCLK_LOCK 0 H INTERFACE[4] INTERFACE[3] EXT_PA 0 H INTERFACE[2] INTERFACE[1] EXT_PA_POL 0 H INTERFACE[0] - H Description Bypass internal crystal oscillator, use external clock 0: Internal crystal oscillator is used, or external sine wave fed through a coupling capacitor 1: Internal crystal oscillator in power down, external clock with rail-to-rail swing is used reserved Gate DCLK signal with PLL lock signal in synchronous mode Only applies when PD_MODE = “01” 0: DCLK is always 1 1: DCLK is always 1 unless PLL is in lock reserved Use PA_EN pin to control external PA 0: PA_EN pin always equals EXT_PA_POL bit 1: PA_EN pin is asserted when internal PA is turned on reserved Polarity of external PA control 0: PA_EN pin is “0” when activating external PA 1: PA_EN pin is “1” when activating external PA reserved RESET Register (02h) REGISTER NAME RESET[7] RESET[6] RESET[5] RESET[4] RESET[3] RESET[2] RESET[1] RESET[0] GAUSS_RESET_N PN9_RESET_N SYNTH_RESET_N CAL_LOCK_RESET_N Default value Active 0 L 0 0 L L 0 L Description reserved reserved Reset Gaussian data filter reserved Reset modulator and PN9 PRBS generator Reset digital part of frequency synthesizer reserved Reset calibration logic and lock detector Note: For reset of CC1070 write RESET_N=0 in the MAIN register. The RESET register should not be used during normal operation Bits in the RESET register are self-clearing (will be set to 1 when the reset operation starts). Relevant digital clocks must be running for the resetting to complete. After writing to the RESET register, the user should verify that all reset operations have been completed, by reading the RESET_DONE status register (41h) until all bits equal 1. SWRS043 Page 42 of 58 CC1070 FREQ_2A Register (04h) REGISTER NAME FREQ_2A[7:0] FREQ_A[22:15] Default value 131 Active Default value 177 Active Default value 124 1 Active - Description 8 MSB of frequency control word A FREQ_1A Register (05h) REGISTER NAME FREQ_1A[7:0] FREQ_A[14:7] - Description Bit 15 to 8 of frequency control word A FREQ_0A Register (06h) REGISTER NAME FREQ_0A[7:1] FREQ_0A[0] FREQ_A[6:0] DITHER_A H Description 7 LSB of frequency control word A Enable dithering for frequency A CLOCK_A Register (07h) REGISTER NAME CLOCK_A[7:5] REF_DIV_A[2:0] Default value 2 Active - CLOCK_A[4:2] MCLK_DIV1_A[2:0] 4 - CLOCK_A[1:0] MCLK_DIV2_A[1:0] 0 - Description Reference frequency divisor (A): 0: Not supported 1: REF_CLK frequency = Crystal frequency / 2 … 7: REF_CLK frequency = Crystal frequency / 8 It is recommended to use the highest possible reference clock frequency that allows the desired Baud rate. Modem clock divider 1 (A): 0: Divide by 2.5 1: Divide by 3 2: Divide by 4 3: Divide by 7.5 (2.5·3) 4: Divide by 12.5 (2.5·5) 5: Divide by 40 (2.5·16) 6: Divide by 48 (3·16) 7: Divide by 64 (4·16) Modem clock divider 2 (A): 0: Divide by 1 1: Divide by 2 2: Divide by 4 3: Divide by 8 MODEM_CLK frequency is FREF frequency divided by the product of divider 1 and divider 2. Baud rate is MODEM_CLK frequency divided by 8. FREQ_2B Register (08h) REGISTER NAME FREQ_2B[7:0] FREQ_B[22:15] Default value 131 Active Default value 189 Active Default value 124 1 Active - Description 8 MSB of frequency control word B FREQ_1B Register (09h) REGISTER NAME FREQ_1B[7:0] FREQ_B[14:7] - Description Bit 15 to 8 of frequency control word B FREQ_0B Register (0Ah) REGISTER NAME FREQ_0B[7:1] FREQ_0B[0] FREQ_B[6:0] DITHER_B H SWRS043 Description 7 LSB of frequency control word B Enable dithering for frequency B Page 43 of 58 CC1070 CLOCK_B Register (0Bh) REGISTER NAME Active REF_DIV_B[2:0] Default value 2 CLOCK_B[7:5] CLOCK_B[4:2] MCLK_DIV1_B[2:0] 4 - CLOCK_B[1:0] MCLK_DIV2_B[1:0] 0 - - Description Reference frequency divisor (B): 0: Not supported 1: REF_CLK frequency = Crystal frequency / 2 … 7: REF_CLK frequency = Crystal frequency / 8 Modem clock divider 1 (B): 0: Divide by 2.5 1: Divide by 3 2: Divide by 4 3: Divide by 7.5 (2.5·3) 4: Divide by 12.5 (2.5·5) 5: Divide by 40 (2.5·16) 6: Divide by 48 (3·16) 7: Divide by 64 (4·16) Modem clock divider 2 (B): 0: Divide by 1 1: Divide by 2 2: Divide by 4 3: Divide by 8 MODEM_CLK frequency is FREF frequency divided by the product of divider 1 and divider 2. Baud rate is MODEM_CLK frequency divided by 8. VCO Register (0Ch) REGISTER NAME Active VCO_CURRENT_A[3:0] Default value 8 VCO[7:4] VCO[3:0] VCO_CURRENT_B[3:0] 8 - - Description Control of current in VCO core for frequency A 0: 1.4 mA current in VCO core 1: 1.8 mA current in VCO core 2: 2.1 mA current in VCO core 3: 2.5 mA current in VCO core 4: 2.8 mA current in VCO core 5: 3.2 mA current in VCO core 6: 3.5 mA current in VCO core 7: 3.9 mA current in VCO core 8: 4.2 mA current in VCO core 9: 4.6 mA current in VCO core 10: 4.9 mA current in VCO core 11: 5.3 mA current in VCO core 12: 5.6 mA current in VCO core 13: 6.0 mA current in VCO core 14: 6.4 mA current in VCO core 15: 6.7 mA current in VCO core Recommended setting: VCO_CURRENT_A=4 Control of current in VCO core for frequency B The current steps are the same as for VCO_CURRENT_A Recommended setting: VCO_CURRENT_B=4 SWRS043 Page 44 of 58 CC1070 MODEM Register (0Dh) REGISTER NAME MODEM[7] MODEM[6:4] MODEM[3] MODEM[2] PN9_ENABLE MODEM[1:0] DATA_FORMAT[1:0] Default value 0 Active 0 0 H 0 - Description Reserved, write 0 (spare register) reserved Reserved, write 0 (spare register) Enable scrambling with PN9 pseudo-random bit sequence 0: PN9 scrambling is disabled 9 5 1: PN9 scrambling is enabled (x +x +1) Modem data format 0 (00): NRZ operation 1 (01): Manchester operation 2 (10): Transparent asynchronous UART operation, set DCLK=0 3 (11): Transparent asynchronous UART operation, set DCLK=1 DEVIATION Register (0Eh) REGISTER NAME Active TX_SHAPING Default value 1 DEVIATION[7] DEVIATION[6:4] DEVIATION [3:0] Description H Enable Gaussian shaping of transmitted data TXDEV_X[2:0] TXDEV_M[3:0] 6 8 - Recommended setting: TX_SHAPING=1 Transmit frequency deviation exponent Transmit frequency deviation mantissa Deviation in 402-470 MHz band: (TXDEV_X−16) FREF ·TXDEV_M ·2 Deviation in 804-940 MHz band: (TXDEV_X−15) FREF ·TXDEV_M ·2 On-off-keying (OOK) is used in RX/TX if TXDEV_M[3:0]=0 To find TXDEV_M given the deviation and TXDEV_X: (16−TXDEV_X) /FREF (15−TXDEV_X) /FREF TXDEV_M = deviation·2 in 402-470 MHz band. TXDEV_M = deviation·2 in 804-940 MHz band. Decrease TXDEV_X and try again if TXDEV_M<8. Increase TXDEV_X and try again if TXDEV_M≥16. SWRS043 Page 45 of 58 CC1070 LOCK Register (15h) REGISTER NAME Active LOCK_SELECT[3:0] Default value 0 LOCK[7:4] LOCK[3] WINDOW_WIDTH 0 - LOCK[2] LOCK_MODE 0 - LOCK[1:0] LOCK_ACCURACY[1:0] 0 - - Description Selection of signals to LOCK pin 0: Set to 0 1: Set to 1 2: LOCK_CONTINUOUS (active low) 3: LOCK_INSTANT (active low) 4: Set to 0 5: CAL_COMPLETE (active low) 6: Set to 0 7: FXOSC 8: REF_CLK 9: Set to 0 10: Set to 0 11: PRE_CLK 12: DS_CLK 13: MODEM_CLK 14: VCO_CAL_COMP 15: F_COMP Selects lock window width 0: Lock window is 2 prescaler clock cycles wide 1: Lock window is 4 prescaler clock cycles wide Recommended setting: WINDOW_WIDTH=0. Selects lock detector mode 0: Counter restart mode 1: Up/Down counter mode Recommended setting: LOCK_MODE=0. Selects lock accuracy (counter threshold values) 0: Declare lock at counter value 127, out of lock at value 111 1: Declare lock at counter value 255, out of lock at value 239 2: Declare lock at counter value 511, out of lock at value 495 3: Declare lock at counter value 1023, out of lock at value 1007 Note: Set LOCK_SELECT=2 to use the LOCK pin as a lock indicator. SWRS043 Page 46 of 58 CC1070 ANALOG Register (17h) REGISTER NAME Active BANDSELECT Default value 1 ANALOG[7] ANALOG[6] ANALOG[5] ANALOG[4] PD_LONG 0 H ANALOG[3] ANALOG[2] PA_BOOST 0 0 H ANALOG[1:0] DIV_BUFF_CURRENT[1:0] 3 - - Description Frequency band selection 0: 402-470 MHz band 1: 804-940 MHz band reserved reserved Selects short or long reset delay in phase detector 0: Short reset delay 1: Long reset delay Recommended setting: PD_LONG=0. Reserved, write 0 (spare register) Boost PA bias current for higher output power Recommended setting: PA_BOOST=1. Overall bias current adjustment for VCO divider and buffers 0: 4/6 of nominal VCO divider and buffer current 1: 4/5 of nominal VCO divider and buffer current 2: Nominal VCO divider and buffer current 3: 4/3 of nominal VCO divider and buffer current Recommended settings: DIV_BUFF_CURRENT=3 BUFF_SWING Register (18h) REGISTER NAME BUFF_SWING[7:6] PRE_SWING[1:0] BUFF_SWING[5:3] BUFF_SWING[2:0] TX_SWING[2:0] Default value 3 Active - 1 - Description Prescaler swing. Fractions for PRE_CURRENT=0: 0: 2/3 of nominal swing 1: 1/2 of nominal swing 2: 4/3 of nominal swing 3: Nominal swing Recommended setting: PRE_SWING=0. reserved LO buffer swing, in TX (to power amplifier driver) 0: Smallest load resistance (smallest swing) … 7: Largest load resistance (largest swing) Recommended settings: TX_SWING=4 for 402-470 MHz TX_SWING=0 for 804-940 MHz. BUFF_CURRENT Register (19h) REGISTER NAME BUFF_CURRENT[7:6] PRE_CURRENT[1:0] BUFF_CURRENT[5:3] BUFF_CURRENT[2:0] TX_CURRENT[2:0] Default value 1 5 Active - - Description Prescaler current scaling 0: Nominal current 1: 2/3 of nominal current 2: 1/2 of nominal current 3: 2/5 of nominal current Recommended setting: PRE_CURRENT=0. reserved LO buffer current, in TX (to PA driver) 0: Minimum buffer current … 7: Maximum buffer current Recommended settings: TX_CURRENT=2 for 402-470 MHz TX_CURRENT=4 for 804-940 MHz. SWRS043 Page 47 of 58 CC1070 PLL_BW Register (1Ah) REGISTER PLL_BW[7:0] NAME Default value 134 PLL_BW[7:0] Active Description - Charge pump current scaling/rounding factor. Used to calibrate charge pump current for the desired PLL loop bandwidth. The value is given by: PLL_BW = 146 + 16 log2(fref/7.126) where fref is the reference frequency in MHz. CALIBRATE Register (1Bh) REGISTER NAME Active CAL_START Default value 0 CALIBRATE[7] CALIBRATE[6] CAL_DUAL 0 H CALIBRATE[5:4] CAL_WAIT[1:0] 0 - ↑ Description ↑ 1: Calibration started 0: Calibration inactive Use calibration results for both frequency A and B 0: Store results in A or B defined by F_REG (MAIN[6]) 1: Store calibration results in both A and B Selects dividers for clock used during calibration, and thereby calibration wait time. Encoding when CAL_SELECT = 1: 0 – divider 8 1 – divider 16 2 – divider 40 3 – divider 80 Encoding when CAL_SELECT = 0: 0 – divider 80 1 – divider 128 2 – divider 160 3 – divider 256 For CAL_SELECT = 0 this leads to: 0: Calibration time is approx. 90000 F_REF periods 1: Calibration time is approx. 110000 F_REF periods 2: Calibration time is approx. 130000 F_REF periods 3: Calibration time is approx. 200000 F_REF periods CALIBRATE[3] CAL_SELECT 1 - CALIBRATE[2:0] CAL_ITERATE[2:0] 5 - Recommended setting: CAL_WAIT=3 for best accuracy in calibrated PLL loop filter bandwidth. Selects calibration routine 0: CC1020 style calibration 1: New calibration routine (default) Recommended setting: CAL_SELECT=1. Iteration start value for calibration DAC 0 (000): DAC start value 1, VC<0.49V after calibration 1 (001): DAC start value 2, VC<0.66V after calibration 2 (010): DAC start value 3, VC<0.82V after calibration 3 (011): DAC start value 4, VC<0.99V after calibration 4 (100): DAC start value 5, VC<1.15V after calibration 5 (101): DAC start value 6, VC<1.32V after calibration 6 (110): DAC start value 7, VC<1.48V after calibration 7 (111): DAC start value 8, VC<1.65V after calibration Recommended setting: CAL_ITERATE=4. SWRS043 Page 48 of 58 CC1070 PA_POWER Register (1Ch) REGISTER NAME Active PA_HIGH [3:0] Default value 0 PA_POWER[7:4] PA_POWER[3:0] PA_LOW[3:0] 15 - Description - Controls output power in high-power array 0: High-power array is off 1: Minimum high-power array output power … 15: Maximum high-power array output power Controls output power in low-power array 0: Low-power array is off 1: Minimum low-power array output power … 15: Maximum low-power array output power It is more efficient in terms of current consumption to use either the lower or upper 4-bits in the PA_POWER register to control the power. POWERDOWN Register (20h) REGISTER NAME POWERDOWN[7] POWERDOWN[6] POWERDOWN[5] PA_PD VCO_PD BUFF_PD POWERDOWN[4] POWERDOWN[3] POWERDOWN[2] POWERDOWN[1] POWERDOWN[0] CHP_PD - Default value 0 0 0 Active 0 H Description H H H Sets PA in power-down when PD_MODE[1:0]=2 Sets VCO in power-down when PD_MODE[1:0]=2 Sets VCO divider, LO buffers and prescaler in power-down when PD_MODE[1:0]=2 Sets charge pump in power-down when PD_MODE[1:0]=2 reserved reserved reserved reserved TEST1 Register (21h, for test only) REGISTER NAME Active CAL_DAC_OPEN[3:0] Default value 4 TEST1[7:4] TEST1[3:0] CHP_CO[3:0] 13 - Active - Description Calibration DAC override value, active when BREAK_LOOP=1 Charge pump current override value TEST2 Register (22h, for test only) REGISTER NAME TEST2[7] BREAK_LOOP Default value 0 TEST2[6] CHP_OVERRIDE 0 H TEST2[5] VCO_OVERRIDE 0 H TEST2[4:0] VCO_AO[4:0] 16 - Default value 0 0 Active H Description 0: PLL loop closed 1: PLL loop open 0: use calibrated value 1: use CHP_CO[3:0] value 0: use calibrated value 1: use VCO_AO[4:0] value VCO_ARRAY override value TEST3 Register (23h, for test only) REGISTER NAME TEST3[7] TEST3[6] VCO_CAL_MANUAL VCO_CAL_OVERRIDE TEST3[5:0] VCO_CO[5:0] 6 SWRS043 H H - Description Enables “manual” VCO calibration (test only) Override VCO current calibration 0: Use calibrated value 1: Use VCO_CO[5:0] value VCO_CAL_OVERRIDE controls VCO_CAL_CLK if VCO_CAL_MANUAL=1. Negative transitions are then used to sample VCO_CAL_COMP. VCO_CAL_CURRENT override value Page 49 of 58 CC1070 TEST4 Register (24h, for test only) REGISTER NAME TEST4[7] TEST4[6] TEST4[5] TEST4[4:3] TEST4[2] TEST4[1] TEST4[0] CHP_DISABLE CHP_TEST_UP CHP_TEST_DN - Default value 0 0 0 Active Default value 0 Active 1 H Active H H H Description Disable normal charge pump operation Force charge pump to output “up” current Force charge pump to output “down” current reserved reserved reserved reserved TEST5 Register (25h, for test only) REGISTER NAME TEST5[7] F_COMP_ENABLE TEST5[6] TEST5[5] TEST5[4] TEST5[3] TEST5[2] TEST5[1:0] SET_DITHER_CLOCK - H Description Enable frequency comparator output F_COMP from phase detector Enable dithering of delta-sigma clock reserved reserved reserved reserved reserved TEST_NFC Register (28h, for test only) REGISTER NAME TEST_NFC[7:6] CAL_WTIME_2 Default value 0 TEST_NFC[5:4] CAL_WTIME_1 1 - TEST_NFC[3:0] CAL_DEC_LIMIT 5 - Active - Description Wait time vcdac, vco_array, chp_current calibrations. Encoding: 0 – 1 clock cycle 1 – 2 clock cycles 2 – 6 clock cycles 3 – 50 clock cycles Wait time vco_cal_current calibration. Encoding: 0 – 1 clock cycle 1 – 12 clock cycles 2 – 63 clock cycles 3 – 127 clock cycles Calibration decision limit in new frequency comparator STATUS Register (40h, read only) REGISTER NAME STATUS[7] CAL_COMPLETE Default value - STATUS[6] STATUS[5] STATUS[4] LOCK_INSTANT LOCK_CONTINUOUS - H H STATUS[3] STATUS[2] STATUS[1] STATUS[0] LOCK DCLK DIO - H H H SWRS043 H Description Set to 0 when PLL calibration starts, and set to 1 when calibration has finished reserved Instantaneous PLL lock indicator PLL lock indicator, as defined by LOCK_ACCURACY. Set to 1 when PLL is in lock reserved Logical level on LOCK pin Logical level on DCLK pin Logical level on DIO pin Page 50 of 58 CC1070 RESET_DONE Register (41h, read only, test only) REGISTER NAME Default value RESET_DONE[7] RESET_DONE[6] RESET_DONE[5] RESET_DONE[4] RESET_DONE[3] RESET_DONE[2] GAUSS_RESET_DONE PN9_RESET_DONE SYNTH_RESET_DONE RESET_DONE[1] RESET_DONE[0] CAL_LOCK_RESET_DONE Active - H - H H - H Description reserved reserved Reset of Gaussian data filter done reserved Reset of PN9 PRBS generator Reset digital part of frequency synthesizer done reserved Reset of calibration logic and lock detector done STATUS1 Register (45h, for test only) REGISTER NAME STATUS1[7:4] STATUS1[3:0] CAL_DAC[3:0] CHP_CURRENT[3:0] Default value - Active Description - Status vector defining applied Calibration DAC value Status vector defining applied CHP_CURRENT value STATUS2 Register (46h, for test only) REGISTER NAME Active CC1070_VERSION[2:0] Default value - STATUS2[7:5] STATUS2[4:0] VCO_ARRAY[4:0] - - - Description CC1070 version code: 0: Pre-production version 1: First production version 2-7: Reserved for future use Status vector defining applied VCO_ARRAY value STATUS3 Register (47h, for test only) REGISTER NAME Active F_COMP Default value - STATUS3[7] STATUS3[6] VCO_CAL_COMP - - STATUS3[5:0] VCO_CAL_CURRENT[5:0] - - SWRS043 - Description Frequency comparator output from phase detector Readout of VCO current calibration comparator Equals 1 if current defined by VCO_CURRENT_A/B is larger than the VCO core current Status vector defining applied VCO_CAL_CURRENT value Page 51 of 58 CC1070 25 Package Description (QFN 20) SWRS043 Page 52 of 58 CC1070 Quad Flat Pack - No Lead Package (QFN) E A A1 e b L QFN 20 Min 0.8 0.25 0.45 Nom 5.0 5.0 0.203 0.65 0.30 0.55 Max 1.0 0.35 0.65 All dimensions in mm. Angles are in degrees. D D1 2.9 3.0 3.1 E1 2.9 3.0 3.1 P 45° Note: Do not place a via underneath CC1070 at “pin #1 corner” as this pin is internally connected to the exposed die attached pad, which is the main ground connection for the chip. 25.1 Package Marking When contacting technical support with a chip-related question, please state the entire marking information, not just the date code. Standard leaded 0315123 0315 is the date code (year 03, week 15) 123 is the lot code RoHS compliant Pb-free A440123 440 is the date code (year 4, week 40) 123 is the lot code A means RoHS compliant Pb-free SWRS043 Page 53 of 58 CC1070 25.2 Recommended PCB footprint for package (QFN 20) Note: The figure is an illustration only and not to scale. There are 8 14 mil (0.36 mm) diameter via holes distributed symmetrically in the ground plane under the package. See also the CC1070EM reference design. 25.3 Package Thermal Properties Thermal resistance Air velocity [m/s] 0 Rth,j-a [K/W] 30 - 35 25.4 Soldering Information Recommended soldering profile for both standard leaded packages and Pb-free packages is according to IPC/JEDEC J-STD-020C. SWRS043 Page 54 of 58 CC1070 25.5 Tray Specification QFN 5x5 mm standard shipping tray. Package QFN 20 Tray Width 135.9 mm Tray Specification Tray Height Tray Length 7.62 mm 315 mm Units per Tray 490 25.6 Carrier Tape and Reel Specification Carrier tape and reel is in accordance with EIA Specification 481. Package Tape Width QFN 20 12 mm Tape and Reel Specification Component Hole Pitch Pitch 8 mm 4 mm Reel Diameter 13” Units per Reel 5000 26 Ordering Information Ordering part number Description 1137 CC1070-RTY1 1138 CC1070-RTR1 1115 CC1020_1070DK-433 CC1070, QFN20 package, RoHS compliant Pb-free assembly, tray with 490 pcs per tray, Single Chip RF transmitter. CC1070, QFN20 package, RoHS compliant Pb-free assembly, T&R with 5000 pcs per reel, Single Chip RF transmitter. CC1020/1070 Development Kit, 433 MHz MOQ 1116 CC1020_1070DK-868/915 CC1020/1070 Development Kit, 868/915 MHz 1 1161 CC1070SK RoHS CC1070 Sample Kit, QFN20 package, RoHS compliant Pbfree assembly, 5 pcs 1 490 5000 1 MOQ = Minimum Order Quantity T&R = tape and reel SWRS043 Page 55 of 58 CC1070 27 General Information Document Revision History Revision Date 1.0 1.1 2003-10-30 2005-02-09 1.2 2005-10-20 1.3 2006-02-01 Product Status Definitions Data Sheet Identification Description/Changes Initial release. The various sections have been reorganized to improve readability Added chapter numbering Reorganized electrical specification section Electrical specifications updated Changed “channel width” to “channel spacing” Changes to current consumption figures in TX mode and crystal oscillator, bias and synthesizer mode Included data on PA_EN pin drive Included data on PLL lock time Included data on PLL turn-on time Updates to section on output power programming Updates to section on output matching Updates to section on VCO and PLL self-calibration Updates to section on VCO, charge pump and PLL loop filter New bill of materials for operation at 433 MHz and 868/915 MHz Added recommended PCB footprint for package (QFN 20) Added list of abbreviations Changes to ordering information Calibration routine flow chart changed Added chapter on TX data latency Updates to Ordering Information and Address Information. The lowest supply voltage has been changed from 2.1 V to 2.3 V Product Status Advance Information Planned or Under Development Preliminary Engineering Samples and First Production No Identification Noted Full Production Obsolete Not In Production SWRS043 Definition This data sheet contains the design specifications for product development. Specifications may change in any manner without notice. This data sheet contains preliminary data, and supplementary data will be published at a later date. Chipcon reserves the right to make changes at any time without notice in order to improve design and supply the best possible product. This data sheet contains the final specifications. Chipcon reserves the right to make changes at any time without notice in order to improve design and supply the best possible product. This data sheet contains specifications on a product that has been discontinued by Chipcon. The data sheet is printed for reference information only. Page 56 of 58 CC1070 Disclaimer Chipcon AS believes the information contained herein is correct and accurate at the time of this printing. However, Chipcon AS reserves the right to make changes to this product without notice. Chipcon AS does not assume any responsibility for the use of the described product; neither does it convey any license under its patent rights, or the rights of others. The latest updates are available at the Chipcon website or by contacting Chipcon directly. To the extent possible, major changes of product specifications and functionality will be stated in product specific Errata Notes published at the Chipcon website. Customers are encouraged to sign up for the Developer’s Newsletter for the most recent updates on products and support tools. When a product is discontinued this will be done according to Chipcon’s procedure for obsolete products as described in Chipcon’s Quality Manual. This includes informing about last-time-buy options. The Quality Manual can be downloaded from Chipcon’s website. Compliance with regulations is dependent on complete system performance. It is the customer’s responsibility to ensure that the system complies with regulations. Trademarks SmartRF® is a registered trademark of Chipcon AS. SmartRF® is Chipcon's RF technology platform with RF library cells, modules and design expertise. Based on SmartRF® technology Chipcon develops standard component RF circuits as well as full custom ASICs based on customer requirements and this technology. All other trademarks, registered trademarks and product names are the sole property of their respective owners. Life Support Policy This Chipcon product is not designed for use in life support appliances, devices, or other systems where malfunction can reasonably be expected to result in significant personal injury to the user, or as a critical component in any life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness. Chipcon AS customers using or selling these products for use in such applications do so at their own risk and agree to fully indemnify Chipcon AS for any damages resulting from any improper use or sale. © 2006, Chipcon AS. All rights reserved. SWRS043 Page 57 of 58