EUP8084 Complete Linear Battery Charger with Integrated Buck Converter and LDO DESCRIPTION FEATURES The EUP8084 is a complete constant-current/ constant-voltage linear battery charger for a single-cell 4.2V lithium-ion battery with a 600mA step-down converter, and a 300mA low dropout (LDO) linear regulator. The input voltage range is 3.75V to 5.5V for the battery charger and 2.6V to 5.5V for the step-down converter and linear regulator, making it ideal for applications operating with single-cell lithium-ion/polymer batteries. The battery charger offers an integrated pass device, reverse blocking protection, high accuracy current and voltage regulation, charge status, and charge termination. The charging current is programmable via external resistor from 15mA to 500mA. In addition to these standard features, the device offers current limit, thermal protection, and soft-start. The step-down converter is a highly integrated converter operating at a 1.5MHz switching frequency, minimizing the size of external components while keeping switching losses low. It has independent input and enable pins. The output voltage ranges from 0.6V to the input voltage. The EUP8084 linear regulator is designed for fast transient response and good power supply ripple rejection. Designed for 300mA of load current, it includes short-circuit protection and thermal shutdown. The EUP8084 is available in a 16-lead 3mm × 4mm TDFN package and is rated over the -40°C to 85°C temperature range. z z z z z z Battery Charger: - Input Voltage Range : 3.75 V to 5.5V - Constant-Current/Constant-Voltage Operation with Thermal Feedback to Maximize Charge Rate Without Risk of Overheating - Internal 4.5 Hour Safety Timer for Termination - Charge Current Programmable Up to 500mA with 5% Accuracy - C/10 Charge Current Detection Output - 5µA Supply Current in Shutdown Mode Synchronous Buck Converter: - Input Voltage Range: 2.6V to 5.5V - Output Voltage Range: 0.6V to VIN - 600mA Output Current - Up to 90% Efficiency - 36µA Quiescent Current - 1.5MHz Switching Frequency - 120µs Start-Up Time Linear Regulator: - 300mA Output Current - Low Dropout: 150mV at 300mA - Fast Line and Load Transient Response - High Accuracy: ± 1.5% - 84µA Quiescent Current Short-Circuit, Over-Temperature, and Current Limit Protection 3mm × 4mm TDFN-16 Package RoHS Compliant and 100% Lead (Pb)-Free APPLICATIONS z z z z Typical Application Circuit Figure 1. DS8084 Ver1.0 Apr. 2008 1 Bluetooth Headsets Cellular Phones MP3 and Handheld Computers Portable Media Players EUP8084 Block Diagram Figure 2. DS8084 Ver1.0 Apr. 2008 2 EUP8084 Pin Configurations Package Type Pin Configurations TDFN-16 Pin Description Pin PIN 1 FB 2,10,12,14 GND 3 ENB 4 VINA 5 OUTA 6 EN_BAT 7 ISET 8 BAT Feedback input. This pin must be connected directly to an external resistor divider. Nominal voltage is 0.6V. Ground. Enable pin for the step-down converter. When connected to logic low, the step-down converter is disabled and consumes less than 1µA of current. When connected to logic high, the converter resumes normal operation. Linear regulator input voltage. Connect a 1µF or greater capacitor from this pin to ground. Linear regulator output. Connect a 2.2µF capacitor from this pin to ground. Enable pin for the battery charger. When connected to logic low, the battery charger is disabled and consumes less than 1µA of current. When connected to logic high, the charger resumes normal operation. Charge current set point. Connect a resistor from this pin to ground. Refer to typical characteristics curves for resistor selection. Battery charging and sensing. 9 STAT Charge status input. Open drain status output. 11 ADP 13 ENA 15 LX 16 VINB Input for USB/adapter charger. Enable pin for the linear regulator. When connected to logic low, the regulator is disabled and consumes less than 1µA of current. When connected to logic high, it resumes normal operation. Output of the step-down converter. Connect the inductor to this pin. Internally, it is connected to the drain of both high- and low-side MOSFETs. Input voltage for the step-down converter. DS8084 Ver1.0 Apr. 2008 DESCRIPTION 3 EUP8084 Ordering Information Order Number Package Type EUP8084-42-15JIR1 TDFN-16 EUP8084-42-18JIR1 TDFN-16 EUP8084-42-25JIR1 TDFN-16 EUP8084-42-28JIR1 TDFN-16 EUP8084-42-30JIR1 TDFN-16 EUP8084-42-33JIR1 TDFN-16 EUP8084-□□-□□ Marking xxxxx P8084 2c xxxxx P8084 2d xxxxx P8084 2e xxxxx P8084 2f xxxxx P8084 2h xxxxx P8084 2i □ □ □ □ Lead Free Code 1: Lead Free Packing R: Tape & Reel Operating temperature range I: Industry Standard Package Type J: TDFN Output Voltage Option DS8084 Ver1.0 Apr. 2008 4 Operating Temperature Range -40 °C to 85°C -40 °C to 85°C -40 °C to 85°C -40 °C to 85°C -40 °C to 85°C -40 °C to 85°C EUP8084 Absolute Maximum Ratings Input Voltage to GND (VINA, VINB) --------------------------------------------------------------------------- 6V Adapter Voltage to GND (VADP) -------------------------------------------------------------------- -0.3V to 6V LX to GND (VLX) FB to GND (VFB) ---------------------------------------------------------------------------- -0.3V to VIN +0.3V ENA, ENB, EN_BAT to GND (VEN) -------------------------------------------------------------- -0.3V to 6V BAT, ISET, STAT (VX) --------------------------------------------------------------------- -0.3V to VADP+0.3V Operating Junction Temperature Range (TJ) Maximum Soldering Temperature (at leads, 10sec) ---------------------------------------------------- ----------------------------------------------------------------------- -0.3V to VIN +0.3V ------------------------------------------------- -40℃ to 150℃ 260℃ Thermal Information Maximum Power Dissipation (PD) --------------------------------------------------------------------------- Thermal Resistance (θJA) --------------------------------------------------------------------------------- 2W 50℃/W Electrical Characteristics (VINB=3.6V; TA = -40℃ to 85℃, unless otherwise noted. Typical values are TA=25℃) Symbol Parameter Conditions Step-Down Converter VIN Input Voltage Min. EUP8084 Typ. Max. 2.6 5.5 2.6 VINB Rising VUVLO UVLO Threshold VOUT Output Voltage Tolerance VOUT Output Voltage Range Hysteresis 200 Unit V V mV VINB Falling 2.4 IOUTB = 0 to 250mA, VINB = 2.6V to 5.5V -3 3 % 0.6 VINB V IQ Quiescent Current No Load ISHDN Shutdown Current ENB = GND ILIM P-Channel Current Limit V 36 µA 1 1 µA A RDS(ON)H High-Side Switch On Resistance 0.26 Ω RDS(ON)L Low-Side Switch On Resistance 0.28 Ω ILXLEAK LX Leakage Current △VLinereg/△VIN Line Regulation Feedback Threshold Voltage VFB Accuracy IFB FB Leakage Current FOSC TS THYS VEN(L) Enable Threshold Low DS8084 Ver1.0 VINB = 2.8V to 5.5V VINB = 3.6V Apr. 2008 0.588 1 µA 0.2 0.4 %/V 0.6 0.612 V 0.2 µA 1.8 MHz VOUTB = 1.0V Oscillator Frequency Startup Time Over-Temperature Shutdown Threshold Over-Temperature Shutdown Hysteresis TSD VINB = 5.5V, VLX = 0 to VINB 1.2 From Enable to Output Regulation 1.5 120 µs 150 ℃ 20 ℃ 0.4 5 V EUP8084 Electrical Characteristics (VINB=3.6V; TA = -40℃ to 85℃, unless otherwise noted. Typical values are TA=25℃) Symbol Parameter Conditions EUP8084 Unit Min. Typ. Max. Step-Down Converter VEN(H) IEN Enable Threshold High Input Low Current 1.4 VINB = VENB = 5.5V V -1 1 µA Electrical Characteristics (VINA=VOUT(NOM) + 1V for VOUT options greater than 1.5V. IOUT = 1mA, COUT = 2.2µF, CIN = 1µF, TA = -40℃ to 85℃, unless otherwise noted. Typical values are TA=25℃) Symbol Parameter Conditions EUP8084 Unit Min. Typ. Max. Linear Regulator VOUT Output Voltage Tolerance IOUTA = 100 µA to TA = 25°C 300mA -3 3 % VOUT + VDO 5.5 V VIN Input Voltage VDO Dropout Voltage IOUTA = 300mA 150 200 mV ΔVOUT/ VOUT*ΔVIN Line Regulation VINA = VOUTA + 0.5 to 5.5V, IOUTA = 1mA 0.05 0.2 %/V ΔVOUT(Load) Dynamic Load Regulation IOUTA = 1mA to 300mA 15 35 mV IOUT Output Current VOUTA > 1.2V ISC Short-Circuit Current TA = -40℃ to 85℃ 720 IQ Quiescent Current VINA = 5V; ENA = VIN 84 ISHDN Shutdown Current VINA = 5V; ENA = 0V PSRR Power Supply Rejection Ratio VIN =VOUT +1V TSD THYS VEN(L) Enable Threshold Low VEN(H) Enable Threshold High IEN DS8084 Ver1.0 1kHz Over-Temperature Shutdown Threshold Over-Temperature Shutdown Hysteresis Output Noise eN 300 Enable Input Current Apr. 2008 IOUT=10mA,10Hz≦f≦100kHz mA mA 140 µA 1 µA 65 dB 160 ℃ 25 ℃ 125 µVRMS 0.4 1.6 VENA = 5.5V 6 V V 100 nA EUP8084 Electrical Characteristics (VADP=5V; TA = -40℃ to 85℃, unless otherwise noted. Typical values are TA=25℃) Symbol Parameter Conditions EUP8084 Unit Min. Typ. Max. Battery Charger Operation VADP Adapter Voltage Range VASD Automatic Shutdown Threshold Voltage tSS_CHRG Battery Charger Soft-Start Time VUVLO Under-Voltage Lockout (UVLO) 3.75 5 5.5 (VCC-VBAT),VCC Low to High 85 110 135 (VCC-VBAT),VCC High to Low 15 45 70 V mV µS 120 ADP Rising Edge 3.4 3.6 3.8 V ADP Falling Edge 2.8 3 3.2 V IOP Operating Current VBAT=4.5V(Forces IBAT and IISET=0) 115 300 µA ISHUTDOWN Shutdown Current VBAT = 4V, EN_BAT = GND 0.2 5 µA Reverse Leakage Current from BAT Pin VBAT = 4V, VADP=3.5V 0.7 2 µA 4.200 4.242 V ILEAKAGE Voltage Regulation VBAT_EOC ΔVBAT_EOC/ VBAT_EOC End of Charge Accuracy Output Charge Voltage Tolerance VMIN Preconditioning Voltage Threshold VRCH Battery Recharge Voltage Threshold △VUVCL1 △VUVCL2 4.158 (ADP - VBAT) Undervoltage Current Limit Threshold Voltage 1 2.80 Measured from VBAT_EOC 2.95 % 3.10 V -0.15 V IBAT = 0.9 ICH 180 300 mV IBAT = 0.1 ICH 90 130 mV Current Regulation ICHG ΔICHG/ICHG Charge Current Programmable Range Charge Current Regulation Tolerance VISET ISET Pin Voltage KI_A Current Set Factor: ICHG/IISET tTIMER Termination Timer 15 fBADBAT DBADBAT TLIM DS8084 Ver1.0 VBAT = 2.5V Defective Battery Detection STAT Pulse Frequency Defective Battery Detection STAT Pulse Frequency Duty Ratio Junction Temperature in ConstantTemperature Mode Apr. 2008 mA 10 % 1 V 400 Recharge Time Low-Battery Charge Time 500 7 3 4.5 6 hrs 1.5 2.25 3 hrs 0.75 1.125 1.5 hrs 2 Hz 75 % 115 ℃ EUP8084 Electrical Characteristics (VADP=5V; TA = -40℃ to 85℃, unless otherwise noted. Typical values are TA=25℃) Symbol Parameter Conditions EUP8084 Unit Min. Typ. Max. Charging Devices RDS(ON) Charging Transistor On Resistance VADP = 4.2V Ω 1 Logic Control / Protection VEN(H) Enable Threshold High VEN(L) Enable Threshold Low VSTAT Output Low Voltage ISTAT STAT Pin Current Sink Capability ITK/ICHG ITERM/ICHG DS8084 Ver1.0 Pre-Charge Current 1.6 STAT Pin Sinks 4mA ICHG = 100mA Charge Termination Threshold Current Apr. 2008 V 8 0.4 V 0.4 V 8 mA 10 % 10 % EUP8084 Typical Operating Characteristics-Battery Charge Battery Regulation(Float) Voltage vs Temperature Battery Regulation (Float) Voltage vs Charge Current 4.210 4.21 RISET = 2k 4.205 FLOAT VOLTAGE VBAT_EOC(V) FLOAT VOLTAGE VBAT_EOC (V) 4.20 4.19 4.18 4.17 4.16 4.15 4.14 4.200 4.195 4.190 4.185 4.180 4.175 4.170 4.165 4.13 0 50 100 150 4.160 -40 200 -20 0 40 60 80 TEMPERATURE ( C) Charge Current vs Battery Current Battery Regulation (Float) Voltage vs Supply Voltage 250 4.25 RISET = 2k VBAT RISING 4.20 FLOAT VOLTAGE VBAT_EOC(V) 200 CHARGE CURRENT (mA) 20 o CHARGE CURRENT (mA) 150 100 50 PRECONDITIONING CHARGE 0 -50 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 4.15 4.10 4.05 4.00 3.95 3.90 4.0 5.0 4.5 5.0 5.5 6.0 INPUT VOLTAGE(V) BATTERY VOLTAGE (V) Charge Current vs Temperature with Thermal Regulation(Constant-Current Mode) ISET Pin Voltages vs Charge Current 250 1.0 RISET = 2k 150 0.8 ADP= 6V VBAT = 3V RISET =2k 0.6 VISET (V) CHARGE CURRENT(mA) 200 THERMAL CONTROL LOOP IN OPERATION 100 50 0.2 0.0 0 -25 0 25 50 75 100 0 125 o Ver1.0 Apr. 2008 25 50 75 100 125 CHARGE CURRENT (mA) TEMPERATURE ( C) DS8084 0.4 9 150 175 200 EUP8084 Typical Operating Characteristics-Battery Charge EN_BAT vs Temperature EN_BAT Pin Threshold Voltage vs Temperature 10 0.80 9 0.75 RESISTANCE (Mohm) RISING VOLTAGE (V) 0.70 0.65 0.60 FALLING 0.55 8 7 6 5 4 0.50 -40 -20 0 20 40 60 3 -40 80 -20 0 40 60 80 TEMPERATURE ( C) Normalized Charger Timer Period vs Temperature STAT Pin Output LowVoltage vs Temperature 1.05 0.32 0.30 20 o o TEMPERATURE ( C) ISTAT=5mA NORMALIZED TIME PERIOD 0.28 VOLTAGE (V) 0.26 0.24 0.22 0.20 0.18 0.16 0.14 0.12 STAT 0.10 1.00 0.95 0.90 0.85 0.08 0.06 -40 -20 0 20 40 60 0.80 -40 80 Charger FET On-Resistance vs Temperature 1.2 ADP = 4.2V ICHG = 350mA 1.1 1.0 RDS(ON) (ohm) 0.9 0.8 0.7 0.6 0.5 0.4 0.3 0.2 0.1 0.0 -40 -20 0 20 40 60 80 o TEMPERATURE ( C) DS8084 Ver1.0 Apr. 2008 -20 -10 0 10 20 30 40 TEMPERATURE ( C) 1.4 1.3 -30 o o TEMPERATURE ( C) 10 50 60 70 80 EUP8084 Typical Operating Characteristics-Step-Down Converter BUCK Efficiency vs Load Current (VOUTB=1.5V) BUCK Efficiency vs Load Current (VOUTB=1.8V) 100 100 90 90 80 80 VINB=2.7V 70 EFFICIENCY (%) EFFICIENCY (%) 70 VINB=3.6V 60 VINB=4.2V 50 40 30 VINB=3.6V 50 VINB=4.2V 40 30 L=2.2uH C=10uF 20 VINB=2.7V 60 L=2.2uH C=10uF 20 10 10 0 0 0.1 1 10 100 0.1 1000 1 10 100 1000 LOAD CURRENT (mA) LOAD CURRENT (mA) BUCK Efficiency vs Load Current (VOUTB=1.2V) Reference Voltage vs Temperature (VINB=3.6V) 100 0.610 90 REFERENCE VOLTAGE (V) 80 EFFICIENCY (%) 70 VINB=2.7V 60 VINB=3.6V 50 VINB=4.2V 40 30 L=2.2uH C=10uF 20 0.605 0.600 0.595 L=2.2uH C=10uF 0.590 10 0 0.585 0.1 1 10 100 1000 -40 -20 LOAD CURRENT (mA) 0 20 40 60 80 o TEMPERATURE ( C) Output Voltage vs Temperature (VINB=3.6V,ILoad=1mA) Output Voltage vs Input Voltage (VINB=3.6V,ILoad=1mA) 1.92 1.96 1.90 1.92 OUTPUT VOLTAGE (V) OUTPUT VOLTAGE (V) 1.88 1.86 1.84 1.82 1.80 L=2.2uH C=10uF RFB1=620Kohm RFB2=300Kohm 1.78 1.76 -20 0 20 40 60 80 Apr. 2008 1.76 1.72 L=2.2uH C=10uF RFB1=620Kohm RFB2=300Kohm 1.68 2.5 o Ver1.0 1.80 1.60 100 3.0 3.5 4.0 INPUT VOLTAGE (V) TEMPERATURE ( C) DS8084 1.84 1.64 1.74 -40 1.88 11 4.5 5.0 EUP8084 Typical Operating Characteristics-Step-Down Converter Quiescent Current vs Temperature (No Load) 44 40 36 Quiescent Current (uA) Quiecent Current (uA) Quiescent Current vs Input Voltage (No Load) 44 42 40 38 36 34 32 30 28 26 24 22 20 18 16 14 12 10 L=2.2uH C=10uF 2.5 3.0 3.5 4.0 4.5 32 28 24 20 16 12 L=2.2uH C=10uF 8 4 0 5.0 -40 -20 INPUT VOLTAGE (V) 0 20 40 60 80 100 o TEMPERATURE ( C) Switching Frequency vs Input Voltage Switching Frequency vs Temperature 1.8 1.70 1.68 1.66 1.7 Switching Frequency (MHz) Switching Frequency (MHz) 1.64 1.6 1.5 1.4 L=2.2uH C=10uF 1.3 1.62 1.60 1.58 1.56 1.54 1.52 1.50 1.48 1.46 L=2.2uH C=10uF 1.44 1.42 1.40 1.2 2.5 3.0 3.5 4.0 4.5 5.0 -40 5.5 -20 0 20 40 60 80 100 o INPUT VOLTAGE (V) TEMPERATURE ( C) Ron(PMOS) vs Temperature Ron(PMOS) vs Input Voltage 0.30 0.32 0.30 0.28 0.25 0.26 0.24 RON(PMOS) RON(PMOS) 0.22 0.20 0.18 0.16 0.14 0.20 0.15 0.12 0.10 0.10 L=2.2uH C=10uF L=2.2uH C=10uF 0.08 0.06 0.05 0.04 2.5 3.0 3.5 4.0 4.5 5.0 -40 5.5 DS8084 Ver1.0 Apr. 2008 -20 0 20 40 60 o INPUT VOLTAGE (V) TEMPERATURE ( C) 12 80 100 EUP8084 Typical Operating Characteristics-Step-Down Converter DS8084 Ver1.0 Apr. 2008 13 EUP8084 Typical Operating Characteristics-LDO Regulator o Output Voltage vs. Input voltage Output Voltage vs. Temperature( C) Output Voltage (V) 3.06 3.015 ILOAD=1mA 3.010 3.04 o 25 C 3.02 3.00 o o -40 C 125 C 2.98 3.005 2.96 3.000 -60 -40 -20 0 20 40 60 2.94 3.5 80 100 120 140 4.0 Quiescent Current vs. Temperature Dropout Voltage (mV) 110 100 90 80 70 60 0 20 40 60 80 100 120 140 Temperature ( C) Ver1.0 Apr. 2008 240 220 200 180 160 140 120 100 80 60 40 20 0 -20 5.5 6.0 o 125 C o -40 C 50 100 150 200 Output Current (mA) 14 o 25 C 0 o DS8084 5.0 Dropout Voltage vs. Output Current 120 50 -60 -40 -20 4.5 Input Voltage (V) o Temperature( C) Quiescent Current (uA) Output Voltage VOUT(V) 3.020 250 300 EUP8084 DS8084 Ver1.0 Apr. 2008 15 EUP8084 OPERATION The EUP8084 is a full-featured linear battery charger with an integrated synchronous buck converter, and a linear regulator designed primarily for handheld applications. The battery charger is capable of charging single-cell 4.2V Li-Ion batteries. The buck converter is powered from the VINB pin and has a programmable output voltage providing a maximum load current of 600mA. The linear regulator is design for low noise, low-dropout application. The converter, the linear regulator and the battery charger can run simultaneously or independently of each other. BATTERY CHARGER OPERATION Featuring an internal P-channel power MOSFET, MP1, the battery charger uses a constant-current/constantvoltage charge algorithm with programmable current. Charge current can be programmed up to 500mA with a final float voltage of 4.2V ± 1%. The STAT open-drain status output indicates when C/10 has been reached. No blocking diode or external sense resistor is required; thus, the basic charger circuit requires only two external components. An internal termination timer adheres to battery manufacturer safety guidelines. Furthermore, the EUP8084 battery charger is capable of operating form a USB power source. A charge cycle begins when the voltage at the ADP pin rises above 3.6V and approximately 110mV above the BAT pin voltage, a 1% program resistor is connected form the ISET pin to ground, and the EN_BAT pin is pulled above the enable threshold (VIH). If the battery voltage is less than 2.95V, the battery charger begins trickle charging at 10% of the programmed charge current. When the BAT pin approaches the final float voltage of 4.2V, the battery charger enters constant-voltage mode and the charge current begins to decrease. When the current drops to 10% of the full-scale charge current, an internal comparator turns off the N-channel MOSFET driving the STAT pin, and the pin becomes high impedance. An internal thermal limit reduces the programmed charge current if the die temperature attempts to rise above a preset value of approximately 115℃. This feature protects the EUP8084 from excessive temperature and allows the user to push the limits of the power handling capability of a given circuit board without the risk of damaging the EUP8084 or external components. Another benefit of the thermal limit is that charge current can be set according to typical, rather than worst-case, ambient temperatures for a given application with the assurance that the battery charger will automatically reduce the current in worst-case conditions. An internal timer sets the total charge time, tTIMER (typically 4.5 hours). When this time elapses, the charge DS8084 Ver1.0 Apr. 2008 16 cycle terminates and the STAT pin assumes a high impedance state even if C/10 has not yet been reached. To restart the charge cycle, remove the input-voltage and reapply it or momentarily force the EN_BAT pin below VIL. A new charge cycle will automatically restart if the BAT pin voltage falls below VBAT_EOC (typically 4.05V). Constant-Current / Constant-Voltage / Constant- Temperature The EUP8084 battery charger uses a unique architecture to charge a battery in a constant-current, constant-voltage and constant-temperature fashion. Figure 2 shows a Simplified Block Diagram of the EUP8084. Three of the amplifier feedback loops shown control the constantcurrent, CA, constant-voltage, VA, and constanttemperature, TA modes. A fourth amplifier feedback loop, MA, is used to increase the output impedance of the current source pair, MP1 and MP3 (note that MP1 is the internal P-channel power MOSFET). It ensures that the drain current of MP1 is exactly 400 times the drain current of MP3. Amplifiers CA and VA are used in separate feedback loops to force the charger into constant-current or constant voltage mode, respectively. Diodes D1 and D2 provide priority to either the constant-current or constant-voltage loop, whichever is trying to reduce the charge current the most. The output of the other amplifier saturates low which effectively removes its loop from the system. When in constant-current mode, CA servos the voltage at the ISET pin to be precisely 1V. VA servos its non-inverting input to 1.22V when in constant-voltage mode and the internal resistor divider made up of R1 and R2 ensures that the battery voltage is maintained at 4.2V. The ISET pin voltage gives an indication of the charge current anytime in the charge cycle, as discussed in “Programming Charge Current” in the Applications Information section. If the die temperature starts to creep up above 115°C due to internal power dissipation, the transconductance amplifier, TA, limits the die temperature to approximately 115°C by reducing the charge current. Diode D3 ensures that TA does not affect the charge current when the die temperature is below 115°C. In thermal regulation, the ISET pin voltage continues to give an indication of the charge current. In typical operation, the charge cycle begins in constantcurrent mode with the current delivered to the battery equal to 400V/RISET. If the power dissipation of the EUP8084 results in the junction temperature approaching 115°C, the amplifier (TA) will begin decreasing the charge current to limit the die temperature to approximately 115°C. As the battery voltage rises, the EUP8084 either returns to constant-current mode or enters constant-voltage mode straight from constanttemperature mode. EUP8084 Battery Charger Undervoltage Lockout (UVLO) An internal undervoltage lockout circuit monitors the input voltage and keeps the battery charger off until ADP rises above 3.6V and approximately 110mV above the BAT pin voltage. The 3.6V UVLO circuit has a built-in hysteresis of approximately 0.6V, and the 110mV automatic shutdown threshold has a built-in hysteresis of approximately 65mV. During undervoltage lockout conditions, maximum battery drain current is 5µA and maximum supply current is 10µA. Undervoltage Charge Current Limiting (UVCL) The battery charger in the EUP8084 includes undervoltage charge current limiting that prevents full charge current until the input supply voltage reaches approximately 300mV above the battery voltage (∆VUVCL1). This feature is particularly useful if the EUP8084 is powered from a supply with long leads (or any relatively high output impedance). See Applications Information section for further details. Trickle Charge and Defective Battery Detection At the beginning of a charge cycle, if the battery voltage is below 2.95V, the battery charger goes into trickle charge mode, reducing the charge current to 10% of the programmed current. If the low battery voltage persists for one quarter of the total time (1.125 hr), the battery is assumed to be defective, the charge cycle terminates and the STAT pin output pulses at a frequency of 2Hz with a 75% duty cycle. If, for any reason, the battery voltage rises above 2.95V, the charge cycle will be restarted. To restart the charge cycle (i.e., when the dead battery is replaced with a discharged battery less than 2.95V), the charger must be reset by removing the input voltage and reapplying it or temporarily pulling the EN_BAT pin below the enable threshold. is forced to drop below 10% of the full-scale current by UVCL, STAT will stay in the strong pulldown state. Charge Current Soft-Start and Soft-Stop The EUP8084’s battery charger includes a soft-start circuit to minimize the inrush current at the start of a charge cycle. When a charge cycle is initiated, the charge current ramps from zero to full-scale current over a period of approximately 120µs. Likewise, internal circuitry slowly ramps the charge current from full-scale to zero when the battery charger is turned off or self terminates. This has the effect of minimizing the transient current load on the power supply during start-up and charge termination. Timer and Recharge The EUP8084’s battery charger has an internal termination timer that starts when the input voltage is greater than the undervoltage lockout threshold and at least 110mV above BAT, and the battery charger is leaving shutdown. At power-up or when exiting shutdown, the charge time is set to 4.5 hours. Once the charge cycle terminates, the battery charger continuously monitors the BAT pin voltage using a comparator with a 2ms filter time. When the average battery voltage falls below 4.05V (which corresponds to 80%-90% battery capacity), a new charge cycle is initiated and a 2.25 hour timer begins. This ensures that the battery is kept at, or near, a fully charged condition and eliminates the need for periodic charge cycle initiations. The STAT output assumes a strong pulldown state during recharge cycles until C/10 is reached or the recharge cycle terminates. SWITCHING REGULATOR OPERATION: The switching regulator in the EUP8084 can be turned on by pulling the ENB pin above VIH. Battery Charger Shutdown Mode Main Control Loop The EUP8084’s battery charger can be disabled by pulling the EN_BAT pin below the shutdown threshold (VIL). In shutdown mode, the battery drain current is reduced to less than 2µA and the ADP supply current to about 5µA provided the regulator is off. When the input voltage is not present, the battery charger is in shutdown and the battery drain current is less than 5µA. The switching uses a slop-compensated constant frequency, current mode PWM architecture. Both the main (P-Channel MOSFET) and synchronous (N-channel MOSFET) switches are internal. During normal operation, the buck converter regulates output voltage by switching at a constant frequency and then modulating the power transferred to the load each cycle using PWM comparator. It sums three weighted differential signals: the output feedback voltage from an external resistor divider, the main switch current sense, and the slope-compensation ramp. It modulates output power by adjusting the inductor-peak current during the first half of each cycle. An N-channel, synchronous switch turns on during the second half of each cycle (off time). When the inductor current starts to reverse or when the PWM reaches the end of the oscillator period, the synchronous switch turns off. This keep excess STAT Status Output Pin The charge status indicator pin has three states: pulldown, pulse at 2Hz (see Defective Battery Detection) and high impedance. The pulldown state indicates that the battery charger is in a charge cycle. A high impedance state indicates that the charge current has dropped below 10% of the full-scale current or the battery charger is disabled. When the timer runs out (4.5 hrs), the STAT pin is also forced to the high impedance state. If the battery charger is not in constant-voltage mode when the charge current DS8084 Ver1.0 Apr. 2008 17 EUP8084 current from flowing backward through the inductor, from the output capacitor to GND, or through the main and synchronous switch to GND. Switching Regulator Undervoltage Lockout Whenever VINB is less than 2.6V, an undervoltage lockout circuit keeps the regulator off, preventing unreliable operation. However, if the regulator is already running and the battery voltage is dropping, the undervoltage comparator does not shut down the regulator until VINB drops below 2.4V. Thermal Consideration To avoid the switching regulator from exceeding the maximum junction temperature, the user will need to do a thermal analysis. The goal of the thermal analysis is to determine whether the operating conditions exceed the maximum junction temperature of the part. The temperature rise is given by: TR=(PD)(θJA) Where PD=ILOAD2 × RDS(ON) is the power dissipated by the regulator ; θJA is the thermal resistance from the junction of the die to the ambient temperature. The junction temperature, TJ, is given by: TJ=TA+TR Where TA is the ambient temperature. TJ should be below the maximum junction temperature of 150°C. Linear Regulator Operation: The EUP8084 includes a low-noise, low-dropout, linear regulator operates from a 2.5V to 5.5V input and is guaranteed to deliver 300mA. The linear regulator is stable with small 2.2µF ceramic capacitor. Its performance suits battery powered applications because of its shutdown mode, low quiescent current, and very low dropout voltage. The low dropout voltage allows for more utilization of a battery’s available energy by operating closer to its end-of-life voltage. APPLICATIONS INFORMATION BATTERY CHARGER Programming Charge Current The battery charge current is programmed using a single resistor from the ISET pin to ground. The charge current is 400 times the current out of the ISET pin. The program resistor and the charge current are calculated using the following equations: R ISET = 400 × 1V I CHG , I CHG = 400 × 1V R ISET The charge current out of the BAT pin can be determined at any time by monitoring the ISET pin voltage and using the following equation: I CHG = V ISET R ISET × 400 Stability Considerations The EUP8084 battery charger contains two control loops: constant-voltage and constant-current. The constantvoltage loop is stable without any compensation when a battery is connected with low impedance leads. Excessive lead length, however, may add enough series inductance to require a bypass capacitor of at least 1µF from BAT to GND. In constant-current mode, the ISET pin voltage is in the feedback loop, not the battery voltage. Because of the additional pole created by ISET pin capacitance, capacitance on this pin must be kept to a minimum. With no additional capacitance on the ISET pin, the battery charger is stable with ISET resistor values as high as 25k. However, additional capacitance on this node reduces the maximum allowed program resistor. The pole frequency at the ISET pin should be kept above 100kHz. Therefore, if the ISET pin is loaded with a capacitance, CISET, the following equation should be used to calculate the maximum resistance value for RISET: R ISET ≤ 1 5 2π × 10 × C ISET Average, rather than instantaneous, battery current may be of interest to the user. For example, when the switching regulator operating in low-current mode is connected in parallel with the battery, the average current being pulled out of the BAT pin is typically of more interest than the instantaneous current pulses. In such a case, a simple RC filter can be used on the ISET pin to measure the average battery current as shown in Figure 3. A 10k resistor has been added between the ISET pin and the filter capacitor to ensure stability. DS8084 Ver1.0 Apr. 2008 18 EUP8084 power dissipated during this phase of charging is approximately 40mW. That is a ten times improvement over the non-current limited supply power dissipation. USB and Wall Adapter Power Figure 3. Isolating Capacitive Load on ISET Pin and Filtering Undervoltage Charge Current Limiting (UVCL) USB powered systems tend to have highly variable source impedances (due primarily to cable quality and length). A transient load combined with such impedance can easily trip the UVLO threshold and turn the battery charger off unless undervoltage charge current limiting is implemented. Consider a situation where the EUP8084 is operating under normal conditions and the input supply voltage begins to sag (e.g. an external load drags the input supply down). If the input voltage reaches VUVCL (approximately 300mV above the battery voltage, ∆VUVCL), undervoltage charge current limiting will begin to reduce the charge current in an attempt to maintain ∆VUVCL between ADP and BAT. The EUP8084 will continue to operate at the reduced charge current until the input supply voltage is increased or voltage mode reduces the charge current further. Although the EUP8084 allows charging from a USB port, a wall adapter can also be used to charge Li-Ion batteries. Figure 4 shows an example of how to combine wall adapter and USB power inputs. A P-channel MOSFET, MP1, is used to prevent back conducting into the USB port when a wall adapter is present and Schottky diode, D1, is used to prevent USB power loss through the 1k pulldown resistor. Typically a wall adapter can supply significantly more current than the current-limited USB port. Therefore, an N-channel MOSFET, MN1, and an extra program resistor can be used to increase the charge current when the wall adapter is present. Figure 4. Combining Wall Adapter and USB Power Operation from Current Limited Wall Adapter By using a current limited wall adapter as the input supply, the EUP8084 can dissipate significantly less power when programmed for a current higher than the limit of the supply. Consider a situation where an application requires a 200mA charge current for a discharged 800mAh Li-Ion battery. If a typical 5V (non-current limited) input supply is available then the peak power dissipation inside the part can exceed 300mW. Now consider the same scenario, but with a 5V input supply with a 200mA current limit. To take advantage of the supply, it is necessary to program the EUP8084 to charge at a current greater than 200mA. Assume that the EUP8084 charger is programmed for 300mA (i.e., RISET = 1.33kΩ) to ensure that part tolerances maintain a programmed current higher than 200mA. Since the battery charger will demand a charge current higher than the current limit of the input supply, the supply voltage will collapse to the battery voltage plus 200mA times the on-resistance of the internal PMOSFET. The on-resistance of the battery charger power device is approximately 1Ω with a 5V supply. The actual on-resistance will be slightly higher due to the fact that the input supply will have collapsed to less than 5V. The DS8084 Ver1.0 Apr. 2008 19 Power Dissipation The conditions that cause the EUP8084 battery charger to reduce charge current through thermal feedback can be approximated by considering the total power dissipated in the IC. For high charge currents, the EUP8084 power dissipation is approximately: ( ) PD = V ADP − V BAT × I CHG + P D _ BUCK + (VINA − VOUTA )× I OUTA Where PD is the total power dissipated within the IC, ADP is the input supply voltage, VBAT is the battery voltage, IBAT is the charge current and PD_BUCK is the power dissipation due to the regulator. PD_BUCK can be calculated as: 1 − 1 P =V ×I D _ BUCK OUTB OUTB η Where VOUTB is the regulated output of the switching regulator, IOUTB is the regulator load and η is the regulator efficiency at that particular load. It is not necessary to perform worst-case power dissipation scenarios because the EUP8084 will automatically reduce the charge current to maintain the die temperature at approximately 115°C. However, the approximate ambient temperature at which the thermal feedback begins to protect the IC is: o T = 115 C − P θ A D JA o T A = 115 C − V ADP − V BAT × I CHG × θ JA ( ) EUP8084 ADP Bypass Capacitor Many types of capacitors can be used for input bypassing; however, caution must be exercised when using multi-layer ceramic capacitors. Because of the selfresonant and high Q characteristics of some types of ceramic capacitors, high voltage transients can be generated under some start-up conditions, such as connecting the battery charger input to a live power source. SWITCHING REGULATOR if the regulator is off. Inductor Selection Example: Consider the extreme case when an EUP8084 is operating from a 6V supply providing 250mA to a 3V Li-Ion battery, the switching regulator and the LDO are off. The ambient temperature above which the EUP8084 will begin to reduce the 250mA charge current is approximately: (Correctly soldered to a 2500mm2 double-sided 1 oz. copper board, the EUP8084 has a thermal resistance of approximately 43°C/W.) o o T = 115 C − (6 V − 3V ) × (250 mA ) × 43 C / W A o o o o T A = 115 C − 0.75 W × 43 C / W = 115 C − 32.25 C o T A = 82.75 C ∆I L = If there is more power dissipation due to the switching regulator or the LDO, the thermal regulation will kick in at a somewhat lower temperature than this. In the above circumstances, the EUP8084 can be used above 82.75°C, but the charge current will be reduced from 250mA. The approximate current at a given ambient temperature can be calculated: I CHG = 115 o C − T A (V )×θ −V ADP BAT JA Using the previous example with an ambient temperature of 85°C, the charge current will be reduced to approximately: I CHG = 115 o C − 85 o C (6V − 3V ) × 43 o C/W = 30 o C Apr. 2008 The DC current rating of the inductor should be at least equal to the maximum load current plus half the ripple current to prevent core saturation. Thus, a 720mA rated inductor should be enough for most applications (600mA+120mA). For better efficiency, choose a low DC-resistance inductor. CIN and COUT Selection In continuous mode, the source current of the top MOSFET is a square wave of duty cycle VOUT/VIN. The primary function of the input capacitor is to provide a low impedance loop for the edges of pulsed current drawn by the EUP8084. A low ESR input capacitor sized for the maximum RMS current must be used. The size required will vary depending on the load, output voltage and input voltage source impedance characteristics. A typical value is around 4.7µF. The input capacitor RMS current varies with the input voltage and the output voltage. The equation for the maximum RMS current in the input capacitor is: I Furthermore, the voltage at the ISET pin will change proportionally with the charge current as discussed in the Programming Charge Current section. Ver1.0 V VOUT 1 − OUT (f)(L) VIN 1 = 232.6 mA 129 o C / A Note: 1V = 1J/C = 1W/A DS8084 The output inductor is selected to limit the ripple current to some predetermined value, typically 20%~40% of the full load current at the maximum input voltage. Large value inductors lower ripple currents. Higher VIN or VOUT also increases the ripple current as shown in equation. A reasonable starting point for setting ripple current is ∆IL=240mA (40% of 600mA). 20 RMS =I O × V V O × 1 − O V V IN IN The output capacitor COUT has a strong effect on loop stability. The selection of COUT is driven by the required effective series resistance (ESR). EUP8084 ESR is a direct function of the volume of the capacitor; that is, physically larger capacitors have lower ESR. Once the ESR requirement for COUT has been met, the RMS current rating generally far exceeds the IRIPPLE(P-P) requirement. The output ripple ∆VOUT is determined by: Any good quality ceramic, tantalum, or film capacitor may be used at the input. If a tantalum capacitor is used at the input, it must be guaranteed by the manufacturer to have a surge current rating sufficient for the application. No-Load Stability 1 ∆VOUT ≅ ∆I L ESR + 8fC OUT The regulator will remain stable and in regulation with no external load. This is specially important in CMOS RAM keep-alive applications. When choosing the input and output ceramic capacitors, choose the X5R or X7R dielectric formulations. These dielectrics have the best temperature and voltage characteristics of all the ceramics for a given value and size. Output Capacitance Output Voltage Programming The output voltage is set by a resistive divider according to the following formula: R FB1 VOUT = 0.6V 1 + R FB2 The external resistive divider is connected to the output, allowing remote voltage sensing as shown in Figure 5. The regulator is specifically designed to employ ceramic output capacitors as low as 2.2µF. Ceramic capacitors below 10µF offer significant cost and space savings, along with high frequency noise filtering. Higher values and other types and of capacitor may be used, but their equivalent series resistance (ESR) should be maintained below 0.5Ω. Ceramic capacitor of the value required by the regulator are available in the following dielectric types: Z5U, Y5V, X5R, and X7R. The Z5U and Y5V types exhibit a 50% or more drop in capacitance value as their temperature increase from 25°C, an important consideration. The X5R generally maintain their capacitance value within ± 20%. The X7R type are desirable for their tighter tolerance of 10% over temperature. Power Dissipation and Junction Temperature Specified regulator operation is assured to a junction temperature of 160°C; the maximum junction temperature should be restricted to 160°C under normal operating conditions. This restriction limits the power dissipation the regulator can handle in any given application. To ensure the junction temperature is within acceptable limits, calculate the maximum allowable dissipation, PD(max), and the actual dissipation, PD, which must be less than or equal to PD(max) The maximum-power-dissipation limit is determined using the following equation: Figure 5. LINEAR REGULATOR External Capacitors Like any low-dropout regulator, the regulator requires external capacitors for regulator stability. The regulator is specifically designed for portable applications requiring minimum board space and smallest components. These capacitors must be correctly selected for good performance. Input Capacitor A minimum input capacitance of 1µF is required between the regulator input pin and ground (the amount of the capacitance may be increased without limit).This capacitor must be located a distance of not more than 1cm from the input pin and returned to a clean analog ground. DS8084 Ver1.0 Apr. 2008 21 P D(max) T max − T A = J R θJA Where: TJMAX is the maximum allowable junction temperature. RθJA is the thermal resistance junction-to-ambient for the package TA is the ambient temperature. The regulator dissipation is calculated using: ( ) PD = VINA − VVOUTA × I OUTA Power dissipation resulting from quiescent current is negligible. Excessive power dissipation triggers the thermal protection circuit. EUP8084 Shutdown The regulator goes into sleep mode when the ENA pin is in a logic low condition. During this condition, the pass transistor, error amplifier, and bandgap are turned off, reducing the supply current to 60nA typical. The ENA pin may be directly tied to VINA to keep the part on. Figure 6. EUP8084 Evaluation Circuit DS8084 Ver1.0 Apr. 2008 22 EUP8084 Packaging Information TDFN-16 DETAIL SYMBOLS A A1 b E D D1 E1 e L DS8084 Ver1.0 Apr. 2008 MILLIMETERS MIN. MAX. 0.70 0.80 0.00 0.05 0.15 0.30 2.90 3.10 3.90 4.10 3.20 1.60 0.45 0.35 0.55 23 INCHES MIN. MAX. 0.028 0.031 0.000 0.002 0.006 0.012 0.114 0.122 0.153 0.161 0.126 0.063 0.018 0.014 0.022