RF2938 2 2.4GHZ SPREAD-SPECTRUM TRANSCEIVER Typical Applications • Wireless LANs • Inventory Tracking • Wireless Local Loop • Wireless Security • Secure Communication Links • Digital Cordless Telephones Product Description Optimum Technology Matching® Applied NC 2 PD 3 RX EN 4 TX EN 5 42 41 40 39 38 37 U pg r RX P 43 -A- 0.50 R F2 94 8B 9.00 + 0.10 0.22 + 0.05 7.00 + 0.10 sq. 4.57 + 0.10 sq. Exposed pad protrusion 0.0000 to 0.0127 (see note 4). 7° MAX 0° MIN 1.00 + 0.10 Dimensions in mm 0.17 MAX. 0.60 + 0.15 NOTES: 0.10 1. Shaded lead is Pin 1. 2. Lead coplanarity - 0.08 with respect to datum "A". 3. Leadframe material: EFTEC 64T copper or equivalent, 0.127 mm (0.005) thick. 4. Solder plating (85/15) on exposed area. Package Style: TQFP-48 EDF, 9x9 11 Features NC NC 44 RSSI BW CTRL 45 DCFB I VCC2 46 DCFB Q VREF 1 47 VCC3 RX VGC Si CMOS 48 0.10 0.00 36 NC 35 NC 34 RXQ DATA 33 Q OUT 32 RXI DATA 31 I OUT 30 VCC4 29 TXQ DATA 28 TXQ BP 27 TXI DATA 26 TXI BP 25 IF1 OUT+ • 45MHz to 500MHz IF Quad Demod TRANSCEIVERS 1 SiGe HBT ad ed NC GaAs MESFET NC üSi Bi-CMOS GaAs HBT VREF 2 Si BJT 9.00 + 0.20 ro du ct The RF2938 is a monolithic integrated circuit specifically designed for direct-sequence spread-spectrum systems operating in the 2.4GHz ISM band. The part includes a direct conversion from IF receiver, quadrature demodulator, I/Q baseband amplifiers with gain control and RSSI, on-chip programmable baseband filters, dual data comparators. For the transmit side, a QPSK modulator and upconverter are provided. The design reuses the IF SAW filter for transmit and receive reducing the number of SAW filters required. Two cell or regulated three cell (3.6V maximum) battery applications are supported by the part. The part is also designed to be part of a 2.4GHz chip set consisting of the RF2444 LNA/Mixer and one of the many RFMD high efficiency GaAs HBT PA’s and a dual frequency synthesizer. • On-Chip Variable Baseband Filters • Quadrature Modulator and Upconverter • 2.7V to 3.6V Operation I Q VCC1 6 RX IF IN 7 TX IF IN 8 VCC9 9 RX_EN TX_EN • Part of 2.4GHz Radio Chipset • 2.4GHz PA Driver I TX S ee Q -45° 13 14 15 16 17 18 19 20 21 22 23 24 NC VCC5 RF LO RF OUT IF1 OUT- NC Σ PA IN 12 +45° NC VCC8 Β2 VCC6 11 RF OUT IF LO RF OUT 10 NC TX VGC Functional Block Diagram Rev A9 020122 Ordering Information RF2938TR13 RF2938 PCBA 2.4GHz Spread-Spectrum Transceiver (Tape & Reel) Fully Assembled Evaluation Board RF Micro Devices, Inc. 7628 Thorndike Road Greensboro, NC 27409, USA Tel (336) 664 1233 Fax (336) 664 0454 http://www.rfmd.com 2-1 RF2938 Absolute Maximum Ratings Parameter Parameter Unit -0.5 to +3.6 -0.5 to +3.6 +12 +5 -40 to +85 -40 to +150 JEDEC Level 5 @ 220°C VDC VDC dBm dBm °C °C Specification Min. Typ. Max. Refer to “Handling of PSOP and PSSOP Products” on page 16-15 for special handling information. Refer to “Soldering Specifications” on page 16-13 for special soldering information. Caution! ESD sensitive device. RF Micro Devices believes the furnished information is correct and accurate at the time of this printing. However, RF Micro Devices reserves the right to make changes to its products without notice. RF Micro Devices does not assume responsibility for the use of the described product(s). Unit T=25 °C, VCC =3.3V, Freq=280MHz, RBW =10kΩ Overall Receiver 45 IF LO Leakage Quadrature Phase Variation IF AMP and Quad Demod ±5 +0.25 ±0.25 +0.5 43 5 230-j400 75-j350 -68 -8 THD U pg r Gain Control Range ad ed RX Baseband Amplifiers dBm ° dB dB dB dB Ω Ω dBm dBm P Input IP3 Dependent upon RX VGC At maximum gain. VGC <1.2V VGC>2.0V At VGC =1.4V Maximum RSSI is 2.5V or VCC -0.3, whichever is less. VGC =1.4V f=280MHz, LO Power=-10dBm With expected LO amplitude and harmonic content. R1=270kΩ. Q>I 3 3 30 % % dB 500 1.7 mVPP V VGC <1.2V max gain, VGC>2.0V=min gain Single Sideband Single ended. 280MHz Single ended. 374MHz VGC <1.2V VGC >2.0V At maximum gain setting At minimum gain setting VGC <1.2V=max gain, VGC >2.0V=min gain RL >5kΩ, CL <5pF RX Baseband Filters Baseband Filter 3dB Bandwidth Passband Ripple Baseband Filter 3dB Frequency Accuracy Group Delay S ee TRANSCEIVERS Gain Control Range Noise Figure IF Input Impedance Output Voltage DC Output Voltage -68 ±2 MHz dB dB dBµV dBµV dB V ro du ct Quadrature Amplitude Offset Quadrature Amplitude Variation 11 500 8 to 93 5 30 105 60 1.1 to 2.3 R F2 94 RX Frequency Range Cascaded Voltage Gain Cascaded Noise Figure Cascaded Input IP3 Cascaded Input IP3 RSSI Dynamic Range RSSI Output Voltage Compliance Condition 8B Supply Voltage Control Voltages Input RF Level LO Input Levels Operating Ambient Temperature Storage Temperature Moisture Sensitivity Rating Group Delay Baseband Filter Ultimate Rejection Output Impedance 2-2 1 ±10 35 0.1 ±30 MHz dB % 15 ns 400 >80 ns dB 20 Ω 5th order Bessel LPF. Set by BW CTRL At 35MHz, increasing as bandwidth decreases. At 2MHz. Designed to drive>5kΩ, <5pF load. Rev A9 020122 RF2938 Specification Min. Typ. Max. Parameter Unit Condition Data Amplifiers Bandwidth Gain (Limiting mode) Rise and Fall Time Logic High Output Logic Low Output Hysteresis 40 VCC -0.3V 60 2 VCC MHz dB ns V V mV 5 0.3 30 Open Loop. 5pF load. Source Current 1mA Sink Current 1mA. Transmit Modulator and LPF 15 3 1.7 200 1.8 500 2 ±2 0.5±0.25 1.1 ±5 1.0 1.6 45 ro du ct -6 Carrier Output Harmonic Outputs dBm dBm -30 dBc 17 1.0 to 2.0 17 230-j400 75-j350 50 +10 to +27 -9 dB V dB/V Ω Ω Ω dB dBm -4 dBm ad ed U pg r At 35MHz, increasing as bandwidth decreases. At 2MHz. Single ended Linear, Single ended. For correct operation. Open Collector when TX on, hi-Z when off With Current Combination into 50Ω singleended load With Current Combination into 50Ω singleended load Without external offset adjustments. 280MHz 11 Positive Slope 280MHz 374MHz With matching elements. With 50Ω match on the output. 1dB compression - Single Side Band, TX GC=1.0V 1dB compression - Single Side Band, TX GC=2.0V S ee VGA/Mixer Output Power dB V/V -30 P Transmit VGA and Upconverter RF Mixer Output Impedance VGA/Mixer Conversion Gain VGA/Mixer Output Power ns dB kΩ mVp-p V MHz kΩ Any setting 5th order Bessel LPF, Set by BW CTRL TRANSCEIVERS 400 >80 Output P1dB VGA Gain Range VGA Input Voltage Range VGA Gain Sensitivity VGA Input Impedance dB MHz dB ns 35 0.1 R F2 94 Group Delay Ultimate Rejection Input Impedance Input AC Voltage Input DC Offset Requirement IF Frequency Range Output Impedance I/Q Phase Balance I/Q Gain Balance Conversion Voltage Gain 0 1 8B Filter Gain Baseband Filter 3dB Bandwidth Passband Ripple Group Delay Rev A9 020122 2-3 RF2938 Parameter Specification Min. Typ. Max. Unit 6 23 12 50 0 50 dBm dB dBm Ω dBm Ω Condition Transmit Power Amp Linear Output Power Gain Output P1dB Output Impedance Input IP3 Input Impedance Power Down Control -0.3 0 >1 1.8 200 2 330 1.33 50 VCC +0.3V V 0.3 V MΩ µs ns µs ns ms µs IF LO Input Input Impedance Input Power Range Input Frequency -15 90 1050-j1200 -10 0 1000 RF LO Input Power Supply 3.3 Ω dBm MHz 3.6 V 1 48 µA mA 65 70 110 mA mA mA 95 105 115 mA mA mA U pg r ad ed P 2.7 <8pF on RSSI output. Full step in gain, to 90% of final output level. I/Q output VALID To IF output VALID To I/Q output VALID To IF output VALID The IF LO is divided by 2 and split into quadrature signals to drive the frequency mixers. f=560MHz peak (2x IF Frequency) f=2.16GHz untuned. VCC =3.3V, Baseband BW 1MHz to 40MHz PD=0, RX EN=1, TX EN =1 Excluding PA Driver S ee TRANSCEIVERS 11 Voltage Total Current Consumption Sleep Mode Current PA Driver Current RX Current BW (MHz) 0-11 12-20 20-30 TX Current BW (MHz) 0-11 12-20 20-30 0 2400 33-j110 -15 2000 Ω dBm MHz ro du ct Input Impedance Input Power Range Input Frequency Voltage supplied to the input, not to exceed 3.6V Voltage supplied to the input. 8B Logical Controls “OFF” Control Input Impedance RSSI Response Time RX VGC Response TIme RX EN Response TIme TX EN Response TIme VPD to RX Response TIme VPD to TX Response TIme VCC -0.3V R F2 94 Logical Controls “ON” 2-4 Rev A9 020122 RF2938 PD 4 RX EN 5 TX EN 6 7 VCC1 RX IF IN 8 TX IF IN VCC9 TX VGC IF LO IF input for receiver section. Must have DC blocking cap. The capacitor value should be appropriate for the IF frequency. External matching to 50Ω recommended. For half duplex operation, connect RX IF IN and TX IF IN signals together after the DC blocking caps, then run a transmission line from the output of the IF SAW. AC coupling capacitor must be less than 150pF to prevent delay in switching RX to TX/TX to RX. Input for the TX IF signal after SAW filter. External DC blocking cap required. External matching to 50Ω recommended. For half duplex operation, connect RX IF IN and TX IF IN signals together after the DC blocking caps, then run a transmission line from the output of the IF SAW. AC coupling capacitor must be less than 150pF to prevent delay in switching RX to TX/TX to RX. 14 RF OUT S ee 15 RF OUT 16 VCC6 Rev A9 020122 ESD See pin 3. See pin 3. See pin 8. DC Block P in 7 50 Ω µstrip IF SAW Filter Pin 8 Gain control setting for the transmit VGA. Positive slope. IF LO input. Must have DC blocking cap. The capacitor value should be appropriate for the IF frequency. LO frequency=2xIF. Quad mod/ demod phase accuracy requires low harmonic content from IF LO, so it is recommended to use an n=3 LPF between the IF VCO and IF LO. This is a high impedance input and the recommended matching approach is to simply add a 100Ω shunt resistor at this input to constrain the mismatch. This pin requires a 6.5µA DC bias current. This can be accomplished with a 270kΩ resistor to VCC for 3.3V operation. ad ed VCC8 NC 10k Ω To Logic R ecom m en ded M atc hing N etw ork for IF LO 11 V CC C2 1 50 pF IF V C O 270 k Ω IF LO P in 1 1 1 00 Ω Power supply for IF LO buffer and quadrature phase network. U pg r 12 13 Pins 3, 4, 5 Power supply for the TX 15dB gain amp and TX VGA. P 9 10 11 Enable pin for the receiver 15dB gain IF amp and the RX VGA amp. Powers up all receiver functions when PD is high, turns off the receiver IF circuits when low. Also, see State Decode Table. This pin is used to enable the transmit upconverter, buffer amps, 15db IF amp, quad mod mixers, TX LO buffer, TX VGA, and PA driver. TX EN is active low, when TX EN <1V, the transmit circuit is active if PD is high. A logic high (TX EN >2V) disables the transmit IF/RF circuitry and quad mod. Also, see State Decode Table. Power supply for RX VGA amplifier, IC logic and RX references. VCC No internal connection. May be grounded or connected on adjacent signal or left floating. Connect to ground for best results. This is the output transistor of the power amp stage. It is an open collector output. The output match is formed by an inductor to VCC, which supplies DC and a series cap. VCC CBYP 22 nF VCC CBYP 22 nF Power Amp Output VCC6 PA OUT PA OUT Pin 16 From TX RF Image Filter Pin 15 34 mA Pin 18 Bias This is the output transistor of the power amp stage. It is an open collector output. The output match is formed by an inductor to VCC, which supplies DC and a series cap. Power supply for the PA driver amp. This inductance to ground via decoupling, along with an internal series capacitor, forms the interstage match. Pin 14 14 mA PA IN Bias See pin 14. See pin 14. 2-5 TRANSCEIVERS 3 µstrip NC Interface Schematic No internal connection. May be grounded or connected on adjacent signal or left floating. Connect to ground for best results. No internal connection. May be grounded or connected on adjacent signal or left floating. Connect to ground for best results. This pin is used to power up or down the transmit and receive baseband sections. A logic high powers up the quad demod mixers, TX and RX GmC LPF’s, baseband VGA amps, data amps, and IF LO buffer amp/ phase splitter. A logic low powers down the entire IC for sleep mode. Also, see State Decode Table. 8B 2 Description R F2 94 Function NC ro du ct Pin 1 RF2938 Pin 17 Function NC 18 PA IN 19 NC 20 VCC5 Description Interface Schematic No internal connection. May be grounded or connected on adjacent signal or left floating. Connect to ground for best results. Input to the power amplifier stage. This is a 50Ω input. Requires DC blocking/tuning cap. No internal connection. May be grounded or connected on adjacent signal or left floating. Connect to ground for best results. Supply for the RF LO buffer, RF upconverter and amplifier. See pin 14. VCC VCC C BYP 22 nF To TX RF Image Filter CBYP 22 nF VCC5 RF OUT Pin 20 Pin 22 12 mA From TX VGA VB RF LO Pin 21 CBLOCK 22 pF RF OUT 23 IF1 OUT- NC 25 IF1 OUT+ 26 TXI BP 27 28 TXI DATA TXQ BP 29 30 31 TXQ DATA VCC4 I OUT No internal connection. May be grounded or connected on adjacent signal or left floating. Connect to ground for best results. The non-inverting open collector output of the quadrature modulator. This pin needs to be externally biased and DC isolated from other parts of the circuit. This output can drive a Balun with IF1 OUT-, to convert to unbalanced to drive a SAW filter. The Balun can be either broadband (transformer) or narrowband (discrete LC matching). Alternatively, just IF1 OUT+ can be used to drive a SAW single-ended with an RF choke (high Z at IF) from VCC to IF1 OUT+. IF1 OUT- See pin 23. 32 This is the in-phase modulator bypass pin. A 10nF capacitor to ground is recommended. I input to the baseband 5 pole Bessel LPF for the transmit modulator. U pg r RXI DATA 33 Q OUT 34 RXQ DATA 35 NC 2-6 ad ed P 24 R F2 94 22 Single ended LO input for the transmit upconverter. External matching See pin 20. to 50Ω and a DC block are required. Upconverted Transmit signal. This 50Ω output is intended to drive an See pin 20. RF filter to suppress the undesired sideband, harmonics, and other outof-band mixer products. The inverting open collector output of the quadrature modulator. This pin needs to be externally biased and DC isolated from other parts of IF1 OUT+ the circuit. This output can drive a Balun with IF1 OUT+, to convert to unbalanced to drive a SAW filter. The Balun can be either broadband (transformer) or narrowband (discrete LC matching). Alternatively, just IF1 OUT+ can be used to drive a SAW single-ended with an RF choke (high Z at IF) from VCC to IF1 OUT-. ro du ct RF LO S ee TRANSCEIVERS 11 21 8B From RF VCO This is the quadrature modulator bypass pin. A 10nF capacitor to ground is recommended. Q input to the baseband 5 pole Bessel LPF for the transmit modulator. Power supply for quadrature modulator. Baseband analog signal output for in-phase channel. 500mVP-P linear output. Logic-level data output for the in-phase channel. This is a digital output signal obtained from the output of a Schmitt trigger. 0.3V to VCC3 - 0.3V swing minimum. Baseband analog signal output for quadrature channel. 500mVP-P linear output. Logic-level data output for the quadrature channel. This is a digital output signal obtained from the output of a Schmitt trigger. 0.3V to VCC3 - 0.3V swing minimum. No internal connection. May be grounded or connected on adjacent signal or left floating. Connect to ground for best results. Rev A9 020122 RF2938 NC 38 RSSI 39 DCFB I 40 DCFB Q 41 VCC3 42 VREF 2 43 NC 44 BW CTRL 45 VCC2 46 VREF 1 47 48 RX VGC NC Pkg Base No internal connection. May be grounded or connected on adjacent signal or left floating. Connect to ground for best results. Ground for all circuitry in the device. A very low inductance from the base to the PCB groundplane is essential for good performance. Use an array of vias immediately underneath the device. This diode structure is used to provide electrostatic discharge protection to 3kV using the Human body model. The following pins are protected: 3-6, 9, 10, 12, 26-34, 38-42, 44-47. VCC 11 S ee U pg r ad ed TRANSCEIVERS P ESD Interface Schematic No internal connection. May be grounded or connected on adjacent signal or left floating. Connect to ground for best results. No internal connection. May be grounded or connected on adjacent signal or left floating. Connect to ground for best results. Received signal strength indicator. Connect 8.2pF to ground. Output impedance is 40kΩ in parallel with 2pF. DC feedback capacitor for in-phase channel. Requires decoupling capacitor to ground. (22nF recommended) DC feedback capacitor for quadrature channel. Requires capacitor to ground. (22nF recommended) Supply for the I and Q data amps.This pin should be bypassed with a 10nF capacitor connected as direct as possible to GND3. Ground this pin if data amps are not used. Gain control reference voltage. No current should be drawn from this pin (<50µA). 2.0V nominal. No internal connection. May be grounded or connected on adjacent signal or left floating. Connect to ground for best results. This pin requires a resistor to ground to set the baseband LPF bandwidth of the receiver and transmit GmC filter amps. Supply for the I and Q baseband and GmC filters. This pin should be bypassed with a 10nF capacitor. This is a bypass pin for the bias circuits of the GmC filter amps and for I/Q inputs. No current should be drawn from this pin (<10µA). 1.7V nominal. Receiver IF and baseband amp gain control voltage. Negative slope. 8B 37 Description R F2 94 Function NC ro du ct Pin 36 Rev A9 020122 2-7 RF2938 State Decode Table Input Pins RX EN x 0 1 0 1 PD 0 1 1 1 1 Sleep Mode Baseband Only Receive Mode Transmit Mode Full Duplex TX EN x 1 1 0 0 Internally Decoded Signals BB EN RXIF EN TXRF EN 0 0 0 1 0 0 1 1 0 1 0 1 1 1 1 NOTES BB_EN Enables: TX_LPF’s and buffers Quad Demodulator mixers Baseband VGA and gm-C LPF’s Data Amplifiers Front-end IF amplifier (RX) RX IF VGA amplifiers TXRF_EN Enables: Front-end IF amplifier (TX) R F2 94 RXIF_EN Enables: 8B IF LO buffer/phase splitters ro du ct TX VGA RF upconverter and buffer PA driver RF LO buffer 11 S ee U pg r ad ed TRANSCEIVERS P Quad Modulator mixers 2-8 Rev A9 020122 RF2938 NC NC RX VGC VREF 1 VCC2 BW CTRL NC VREF 2 VCC3 DCFB Q DCFB I RSSI NC Detailed Functional Block Diagram 48 47 46 45 44 43 42 41 40 39 38 37 1 36 NC 35 NC 34 RXQ DATA 33 Q OUT 32 RXI DATA 31 I OUT 30 VCC4 29 TXQ DATA 28 TXQ BP 27 TXI DATA 26 TXI BP 25 IF1 OUT+ BW Control NC 2 PD 3 RX EN 4 DC Feedback Logic gm-C LPF 0-30 dB +5 dB VCC1 6 DC Feedback REF 0-30 dB +5 dB -6 to 37 dB 15 dB RX IF IN 8B 5 7 R F2 94 TX EN +6 dB 0 dB gm-C LPF 0 dB RX +6 dB TX Bias TX 8 VCC9 9 TX VGC 10 -20 to -3 dB gm-C LPF ro du ct 15 dB TX IF IN 11 TRANSCEIVERS 3.5 dB 15 16 17 18 19 20 21 22 23 24 NC PA IN NC VCC5 RF LO RF OUT IF1 OUT- NC 25 dB VCC6 14 -1.5 dB gm-C LPF RF OUT 13 RF OUT 12 S ee U pg r VCC8 11 NC IF LO Phase Splitter ad ed Β2 P Σ Rev A9 020122 2-9 RF2938 Theory of Operation cutoff, and this capacitor is reused to set the DC input level for the self-aligned data slicer. The IF to BB mixers are double-balanced, differential in, differential out, mixers with 5dB conversion gain. The LO for each of these mixers is shifted 90° so that the I and Q signals are separated in the mixers. LO Input Buffers RF LO Buffer The RF LO input has a limiting amplifier before the mixer on both the RF2444 (RX) and RF2938 (TX). This limiting amplifier design and layout is identical on both ICs, which will make the input impedance the same as well. Having this amplifier between the VCO and mixer minimizes any reverse effect the mixer has on the VCO, expands the range of acceptable LO input levels, and holds the LO input impedance constant when switching between RX and TX. The LO input power range is -18dBm to +5dBm, which should make it easy to interface to any VCO and frequency synthesizer. R F2 94 8B RSSI and VGC Operation The receive signal path also has an RSSI output which is the sum of both the I and Q channels. The RSSI has about 60dBm of dynamic range and the RSSI characteristic is optimized to give best linearity and dynamic range at a VGC setting of 1.4V. It is recommended that the system sets VGC to 1.4V to take an RSSI reading to make channel activity and signal level decisions, then adjusts VGC to obtain optimum dynamic range from the IOUT and QOUT outputs. U pg r ad ed P ro du ct RX Baseband Amps, Filters, Data Slicers, and DC Feedback At baseband frequency, there are multiple AGC amplifiers offering a gain range of 0dB to 30dB. Following these amplifiers are fully integrated gm-C low pass filters to further filter out-of-band signals and spurs that get through the SAW filter, anti-alias the signal prior to the A/D converter, and to band-limit the signal and noise to achieve optimal signal-to-noise ratio. The 3dB cut-off frequency of these low pass filters is programmable with a single external resistor, and continuously variable from 1MHz to 35MHz. A five-pole Bessel type filter response was chosen because it is optimal for data systems due to its flat delay response and clean step response. Butterworth and Chebychev type filters ring when given a step input making them less ideal for data systems. The filter outputs, with +6dBm gain, drive the linear 500mVPP signal off-chip, but also connect internally to a data slicer which squares up the signal to CMOS levels, and drives this “data” signal off-chip. This data slicer is a high speed CMOS comparator with 30mV of hysteresis and self-aligned input DC offset. This data slicer can be independently disabled if only the linear outputs are desired. S ee TRANSCEIVERS 11 RECEIVER RX IF AGC/Mixer The front end of the IF AGC starts with a single-ended input and a constant gain amp of 15dB. This first amp stage sets the noise figure and input impedance of the IF section, and its output is taken differentially. The rest of the signal path is differential until the final baseband output, which is converted back to single-ended. Following the front end amp are multiple stages of variable gain differential amplifiers, giving the IF signal path a gain range of 9dB to 52dB. The noise figure (in max gain mode) of the IF amplifiers is 5dB, which should not degrade the system noise figure. DC feedback is built into the baseband amplifier section to correct for input offsets. Large DC offsets can arise when a mixer LO leaks to the mixer input and then mixes with itself. DC offsets can also result from random transistor mismatches. A large external capacitor is needed for the DC feedback to set the high pass 2-10 IF LO Buffer The IF LO input has a limiting amplifier before the phase splitting network to amplify the signal and help isolate the VCO from the IC. Also, the LO input signal must be twice the desired intermediate frequency. This simplifies the quadrature network and helps reduce the LO leakage onto the RX_IF input pin (since the LO input is now at a different frequency than the IF). The amplitude of this input needs to be between -15dBm and 0dBm. Excessive IF LO harmonic content affects phase balance of the modulator and demodulator so it is recommended that a simple n=3 low pass filter is included between VCO and IF LO input. The IF LO input requires a DC bias current of +6.5µA. This can be accomplished with a 270kΩ resistor to VCC for 3.3V operation. Failing to provide this will cause a phase imbalance in the IF LO quadrature divider of up to 8°, which in turn causes a similar imbalance in the I/Q outputs and the TX modulator. Rev A9 020122 RF2938 +6dBm PA Driver The SSB output of the upconverter is -6dBm of linear power. The image filter should have at most 4dB of insertion loss while removing the image, LO, 2LO and any other spurs. The filter output should supply the PA driver input -10dBm of power. 8B The PA driver is a two-stage class A amplifier with 10dB gain per stage and capable of delivering 6dBm of linear power to a 50Ω load, and has a 1dB compression point of 12dBm. For lower power applications, this PA driver can be used to drive a 50Ω antenna directly. ro du ct TX VGA The AGC after the SAW filter starts with a switch and a constant gain amplifier of 15dB, which is identical to the circuitry on the receive IF AGC. This was, done, as on the RX signal path, so that the input impedance will remain constant for different TX gain control voltages. Following this 15dB gain amplifier is a single stage of gain control offering 15dB gain range. The main purpose of adding this variable gain is to give the system the flexibility to use different SAW filters and image filters with different insertion loss values. This gain could also be adjusted real time, if desired. TX Upconverter The IF to RF upconverter is a double-balanced differential mixer with a differential to single-ended converter on the output to supply 0dBm peak linear power to the image filter. The upconverted SSB signal should have -6dBm power at this point, and the image will have the same power, but due to the correlated nature of the signal and image, the output must support 0dBm of linear power to maintain linearly. R F2 94 TRANSMITTER TX LPF and Mixers The transmit section starts with a pair of 5-pole Bessel filters identical to the filters in the receive section and with the same 3dB frequency. These filters pre-shape and band-limit the digital or analog input signals prior to the first upconversion to IF. These filters have a high input impedance and expect an input signal of 200mVPP typical. Following these low pass filters are the I/Q quadrature upconverter mixers. Each of these mixers is half the size and half the current of the RF to IF downconverter on the RF2444. Recall that this upconverted signal may drive the same SAW filter (in half duplex mode) as the RF2444 and therefore share the same load. Having the sum of the two BB to IF mixers equal in size and DC current to the RF to IF mixer, will minimize the time required to switch between RX and TX, and will facilitate the best impedance match to the filter. S ee U pg r ad ed TRANSCEIVERS P 11 Rev A9 020122 2-11 RF2938 IL = 3 -4 dB 2.4 to 2 .48 3 G H z RF M icro D evices 2.4 G Hz ISM Chipset VGC1 R F 2 93 8 TQ F P -4 8 E P P R F 24 4 4 S S O P -16 E P P RSSI G ain S e le ct OUT Q SAW IL = 10 dB m ax RX LNA D u al G a in M o de s -5 dB a nd +10 dB RX DATA Q 15 dB 15 dB G ain IF A m p -1 5 d B to 3 5 d B G a in TX OUT I Filter 15 dB 2 .4 to 2.4 83 G H z B as e B an d A m p. A ctive S elec tab le LP F (f C = 1 M H z to 4 0 M H z ) 0-3 0 d B G a in TX D is cre te P in D io de R F 25 1 7 S SO P -2 8 D u al F req ue n cy S yn th esize r DATA I RF VCO IF VCO Β2 + 4 5° -45 ° F ilter I IN P U T R F 2 1 26 Σ 8B 1 5 d B G a in R a ng e 10 dBm P A D riv er F ilter S elec tab le LP F Q IN P U T R F2 94 23 dB m or 3 3 d B m E x tern al P A VGC2 IL = 3 -4 d B 2.4 to 2.48 3 G H z ro du ct Figure 1. Entire Chipset Functional Block Diagram S ee U pg r ad ed TRANSCEIVERS P 11 2-12 Rev A9 020122 RF2938 Evaluation Board Schematic (Download Bill of Materials from www.rfmd.com.) R6 0Ω VCC R7 10 Ω C15 100 pF VGC C14 100 pF C10 10 nF R4 10 kΩ C11 10 nF C19 22 nF C18 22 nF NOTES: 1) R4 is used to set the bandwidth of the GMC Filters. 2) Pins 14 through 22 contain 2.4 GHz signals. Place tuning/bypass components as close as possible. Make all lines on these pins 50 Ω. 3) For normal operation, move C33 to C38 and install all components with an asterisk. *Do not populate. 50 Ω µstrip J15 RSSI C17 8 pF 48 PD 47 46 45 44 43 42 40 39 38 37 1 36 TX EN 2 35 3 34 R5 10 Ω I 15 dB -15 dB to 35 dB Gain 31 8 L9 68 nH R10* 0Ω TX_EN Baseband Amp Active Selectable LPF (fc=1 MHz to 40 MHz) 0-30 dB Gain 15 dB Gain Range RX_EN 30 15 dB I Active Selectable LPF (fc=1 MHz to 40 MHz) Q C25 1 pF 50 Ω µstrip J3 IF LO L6 27 nH C16 22 nF 14 15 16 17 18 R1 270 kΩ VCC C24 22 nF L1 2.7 nH 19 20 C22 22 nF C27 2 pF 21 22 23 24 2938400, Rev - P1-3 VCC 2 GND 3 GC TX 50 Ω µstrip CON3 P2 P2-1 P2-3 P3 1 TX EN 2 GND 3 RX EN R8 1 kΩ C28 22 pF P3-3 1 PD 2 GND 3 VGC J4 PA OUT J5 PA IN VCC L3 3.9 nH C29 3 pF 50 Ω µstrip L7 220 nH C31 3 pF 50 Ω µstrip C34 22 nF 50 Ω µstrip C30 22 pF C33 5 pF C38* 5 pF C32 3 pF 50 Ω µstrip FL1* SAWTEK 855392 J8 IF OUT J7 RF OUT L4 3.9 nH J6 RF LO 11 C25 22 nF VCC CON3 S ee U pg r ad ed CON3 P3-1 50 Ω µstrip P + C12 4.7 uF C9 10 nF 1 ro du ct P1 P1-1 C26 12 pF VCC L8 39 nH VCC C23 22 nF J9 I IN C1 10 nF 25 13 50 Ω µstrip C5 0.1 uF 26 Σ 12 C7 100 pF R F2 94 GC TX +45 ° -45° Β2 11 J10 Q IN C6 0.1 uF C2 10 nF 27 10 C21 22 nF 50 Ω µstrip 28 9 VCC VCC C20 22 nF 29 IN 50 Ω µstrip J2 TX IF IN 7 C3 100 pF J11 I OUT Q 8B C36 2 pF J12 I DATA 50 Ω µstrip 32 5 6 R3* 0Ω J13 Q OUT 50 Ω µstrip C13 100 pF L2 150 nH 50 Ω µstrip 50 Ω µstrip OUT C4 100 pF J14 Q DATA 33 4 IF Amp 50 Ω µstrip 50 Ω µstrip TRANSCEIVERS VCC J1 RX IF IN 41 RX EN Rev A9 020122 2-13 RF2938 Evaluation Board Layout Board Size 2.580” x 2.086” ro du ct R F2 94 8B Thickness: Top to Ground Laminate, 0.008”; Ground to Bottom Laminate, 0.023”; Board Material FR-4; Multi-Layer S ee U pg r ad ed TRANSCEIVERS P 11 2-14 Rev A9 020122 RF2938 VIN versus POUT -3.0 VIN versus Amplitude Error Ω , IF LO=560MHz@-10dBm) (VCC=2.7V to 3.6V, I & Q in=1MHz, RBW=10kΩ Ω , IF LO=560MHz@-10dBm) (VCC=2.7V to 3.6V, I & Q in=1MHz, RBW=10kΩ 0.60 Pout, -40°C -4.0 Ampl Err, -40°C Ampl Err, 25°C Pout, 25°C -5.0 Pout, 85°C 0.50 Ampl Err, 85°C -6.0 Amplitude Error (dB) -7.0 POUT (dBm) -8.0 -9.0 -10.0 -11.0 -12.0 0.40 0.30 0.20 -13.0 -14.0 0.10 -15.0 -16.0 0.00 200.0 300.0 400.0 500.0 600.0 700.0 800.0 0 100 200 300 400 (VCC=3.15V, I & Q in=1MHz@100mVP-P, RBW=10kΩ Ω , IF LO=560MHz) -14.8 Pout, -40°C Pout, 25°C Pout, 85°C LO Out (dBm) -15.2 -30.0 -32.0 -34.0 -36.0 -38.0 -15.4 -15.6 -16.0 -20.0 -15.0 -10.0 -5.0 0.0 ad ed -16.4 -25.0 IF LO (dBm) RF Conversion Gain versus RF LO Level 16.0 15.5 25C Gain 15.0 85C Gain 14.5 -40C Gain 11 -20.0 -15.0 -10.0 -5.0 0.0 -15.0 S ee Gain (dB) 16.5 2LO_out, 85°C RF LOOUT & RF 2LOOUT versus RF LO Level (VCC=3.15V, LO OUT (dBm) 17.0 LO_out, 85°C VGC=1.5V, Tx IF in=280MHz@-50dBm, RF LO=2160MHz, 2LOOUT=4320MHz) 0.0 25C LOout 85C LOout -5.0 -40C LOout 25C 2LOout 85C 2LOout -10.0 -40C 2LOout U pg r 20.0 17.5 LO_out, 25°C 2LO_out, 25°C IF LO (dBm) (VCC=3.15V, Tx IF in=280MHz@-50dBm, RF LO=2160MHz) 18.0 2LO_out, -40°C -40.0 -42.0 -44.0 -46.0 -58.0 -60.0 -62.0 -25.0 P -16.2 18.5 800 -48.0 -50.0 -52.0 -54.0 -56.0 -15.8 19.0 700 LO_out, -40°C ro du ct TX IF P OUT (dBm) -15.0 R F2 94 -22.0 -24.0 -26.0 -28.0 -14.6 19.5 600 LO & 2LO Out versus IF LO (VCC=3.15V, IF LO=560MHz) TX IF POUT versus IF LO -14.4 500 VIN (mVP-P) 8B VIN (mVP-P) TRANSCEIVERS -17.0 100.0 -20.0 -25.0 -30.0 14.0 -35.0 13.5 13.0 -40.0 12.5 12.0 -45.0 11.5 11.0 -20.0 -18.0 -16.0 -14.0 -12.0 -10.0 -8.0 -6.0 -4.0 -2.0 RF LO (dBm) Rev A9 020122 0.0 2.0 4.0 6.0 -50.0 -20.0 -18.0 -16.0 -14.0 -12.0 -10.0 -8.0 -6.0 -4.0 -2.0 0.0 2.0 4.0 6.0 RF LO (dBm) 2-15 RF2938 RF Conversion Gain versus VGC RF Conversion Gain versus VGC TRANSCEIVERS 25C Gain 85C Gain Gain (dB) -40C 32.0 31.0 30.0 29.0 28.0 27.0 26.0 25.0 24.0 23.0 22.0 21.0 20.0 19.0 18.0 17.0 16.0 15.0 14.0 13.0 12.0 11.0 10.0 9.0 8.0 7.0 25C Gain 85C Gain -40C Gain 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.6 1.7 1.8 1.9 2.0 2.1 2.2 2.3 2.4 2.5 VGC (VDC) VGC (VDC) 8B 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.6 1.7 1.8 1.9 2.0 2.1 2.2 2.3 2.4 2.5 RF Conversion Gain versus VGC IF-RF IIP3 versus VGC (VCC=3.6V, Tx IF in=280MHz@-50dBm, RF LO=2160MHz@-10dBm) (VCC=2.7V, Tx IF in=12dB Below IP1dB, RF LO=2160MHz@-10dBm) R F2 94 -7.0 32.0 31.0 30.0 29.0 28.0 27.0 26.0 25.0 24.0 23.0 22.0 21.0 20.0 19.0 18.0 17.0 16.0 15.0 14.0 13.0 12.0 11.0 10.0 9.0 8.0 25C Gain -8.0 25C IIP3 85C Gain -9.0 85C IIP3 -40C Gain -10.0 -40C IIP3 -11.0 -12.0 IIP3 (dBm) -13.0 -14.0 -15.0 ro du ct 11 (VCC=3.15V, Tx IF in=280MHz@-50dBm, RF LO=2160MHz @-10dBm) -16.0 -17.0 -18.0 -19.0 -20.0 -21.0 -22.0 P Gain (dB) Gain (dB) (VCC=2.7V, Tx IF in=280Mhz-50dBm, RF LO=2160MHz@-10dBm) 31.0 30.0 29.0 28.0 27.0 26.0 25.0 24.0 23.0 22.0 21.0 20.0 19.0 18.0 17.0 16.0 15.0 14.0 13.0 12.0 11.0 10.0 9.0 8.0 7.0 -23.0 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.6 1.7 1.8 1.9 2.0 2.1 2.2 2.3 2.4 2.5 ad ed 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.6 1.7 1.8 1.9 2.0 2.1 2.2 2.3 2.4 2.5 VGC (VDC) IF-RF IIP3 versus VGC IF-RF IIP3 versus VGC (VCC=3.15V, Tx IF in=12dB Below IP1dB, RF LO=2160MHz@-10dBm) (VCC=3.6V, Tx IF in=12dB Below IP1dB, RF LO=2160MHz@-10dBm) -10.0 -11.0 -12.0 -14.0 -8.0 25C IIP3 85C IIP3 -9.0 85C IIP3 -40C IIP3 -10.0 -15.0 S ee IIP3 (dBm) -13.0 -16.0 -17.0 -18.0 -40C IIP3 -11.0 -12.0 -13.0 -14.0 -15.0 -16.0 -17.0 -18.0 -19.0 -19.0 -20.0 -20.0 -21.0 -21.0 -22.0 -22.0 -23.0 -23.0 -24.0 -24.0 2-16 -7.0 25C IIP3 IIP3 (dBm) -9.0 U pg r -7.0 -8.0 VGC (VDC) -25.0 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.6 1.7 1.8 1.9 2.0 2.1 2.2 2.3 2.4 2.5 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.6 1.7 1.8 1.9 2.0 2.1 2.2 2.3 2.4 2.5 VGC (VDC) VGC (VDC) Rev A9 020122 RF2938 IF-RF OP1dB versus VGC IF-RF OP1dB versus VGC (VCC=2.7V, Tx IF in=280Mhz, RF LO=2160MHz@-10dBm) (VCC=3.15V, Tx IF in=280MHz, RF LO=2160MHz@-10dBm) -3.5 -4.0 25C OP1dB -4.0 25C OP1dB -4.5 85C OP1dB -4.5 85C OP1dB -5.0 -40C OP1dB -5.0 -40C OP1dB -5.5 -5.5 -6.0 -6.0 OP1dB (dBm) -6.5 -7.0 -7.5 -8.0 -6.5 -7.0 -7.5 -8.0 -8.5 -8.5 -9.0 -9.0 -9.5 -9.5 -10.0 -10.0 -10.5 -10.5 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.6 1.7 1.8 1.9 2.0 2.1 2.2 2.3 2.4 2.5 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.6 1.7 1.8 1.9 2.0 2.1 2.2 2.3 2.4 2.5 VGC (VDC) VGC (VDC) 8B IF-RF OP1dB versus VGC ICC versus RBW (Temp=Ambient, VCC=3.15V, GC TX=1.5V, (VCC=3.6V, Tx IF in=280MHz, RF LO=2160MHz@-10dBm) 25C OP1dB -4.0 85C OP1dB -4.5 -40C OP1dB R F2 94 -3.5 Rx Icc 190.0 Total Icc 180.0 170.0 160.0 -5.5 150.0 ICC [mA] -6.0 140.0 ro du ct -6.5 -7.0 130.0 120.0 -7.5 110.0 -8.0 100.0 -8.5 11 90.0 -9.0 80.0 70.0 P -9.5 -10.0 60.0 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.6 1.7 1.8 1.9 2.0 2.1 2.2 2.3 2.4 2.5 ad ed 1.0 10.0 VGC (VDC) 35.0 S ee 30.0 25.0 3 dB BW Point [MHz] 40.0 RX IFIN =-67dBm, IF LO=560MHz@-10dBm) 30.0 U pg r 45.0 1000.0 RX 3dB BW versus RBW (Temp=Ambient, VCC=3.15V, VGC=1.6V, VCC=3.15V, GCTX=1.5V, I & Qin=100mVP-P, IFLO=560MHz @-10dBm) 50.0 100.0 RBW [kΩ] TX 3dB BW point versus RBW (Broadband 50ΩΩ match on IF out, Temp=Ambient, 3dB BW Point [MHz] Tx Icc 200.0 -5.0 OP1dB (dBm) I & Q in=100mVP-P, IF LO=-10dBm) 210.0 -3.0 25.0 20.0 20.0 15.0 10.0 15.0 10.0 5.0 5.0 0.0 0.0 1.0 10.0 100.0 RBW [kΩ] Rev A9 020122 1000.0 1.0 10.0 100.0 1000.0 RBW [kΩ] 2-17 TRANSCEIVERS OP1dB (dBm) -3.5 RF2938 RX Gain versus VGC (VCC=2.7-3.6V, RX IFIN=280.5MHz, RBW=100kΩ Ω, I & Q IF LO=560MHz@-10dBm, RBW=100kΩ) Ω) out=500mVP-P, IF LO=560MHz@-10dBm) 100.00 Icc, -40°C Icc, +25°C Icc, +85°C Gain, -40°C Gain, +25°C Gain, +85°C 95.00 90.00 85.00 80.00 75.00 70.00 Gain (dB) ICC (mA) RX ICC versus VCC (VGC=1.2V to 2.0V, I & Q_out=500mVP-P, 70.00 69.50 69.00 68.50 68.00 67.50 67.00 66.50 66.00 65.50 65.00 64.50 64.00 63.50 63.00 62.50 62.00 61.50 61.00 60.50 60.00 59.50 59.00 65.00 60.00 55.00 50.00 45.00 40.00 35.00 30.00 25.00 20.00 15.00 2.7 2.8 2.9 3.0 3.1 3.2 3.3 3.4 3.5 1.2 3.6 1.3 1.4 1.5 1.7 1.8 1.9 2.0 8B Input P1dB versus VGC (Temp=Ambient, VCC=3.15V, Noise Figure versus VGC (Temp=Ambient, VCC=3.15V, RX IFIN=280.5MHz, RBW=100kΩ Ω , IF LO=560MHz@-10dBm) RX IFIN=291MHz, RBW=5.1kΩ Ω , IF LO=560MHz@-10dBm) 38.00 R F2 94 -15.00 1.6 VGC (VDC) VCC (VDC) 36.00 -20.00 34.00 -25.00 32.00 30.00 28.00 -40.00 26.00 Noise Figure [dB] -35.00 -45.00 -50.00 -55.00 -60.00 22.00 20.00 18.00 16.00 14.00 -65.00 12.00 -70.00 11 24.00 ro du ct Input P1dB [dBm] -30.00 10.00 -75.00 8.00 P TRANSCEIVERS -80.00 -85.00 1.3 1.4 1.5 1.6 1.7 1.8 1.9 ad ed 1.2 6.00 4.00 2.0 1.2 1.3 1.4 1.5 VGC [VDC] 1.7 1.8 1.9 I & Q Amplitude Balance versus VGC (VCC=3.15V, RX IFIN=280.5MHz, I & Q Phase Balance versus VGC (VCC=2.7-3.6V, RBW=100kΩ Ω , I & Q out=500mVP-P, IF LO=560MHz@-10dBm) RX IFIN=280.5MHz, RBW=100kΩ Ω , I & Q out=500mV P-P, IF LO=560MHz@-10dBm) 2.50 11.00 Ampl_Err, +25°C 10.00 Ampl_Err, +85°C 9.00 S ee 2.00 2.0 12.00 Ampl_Err, -40°C I & Q Phase Error ( o) U pg r 3.00 I & Q Amplitude Error (dB) 1.6 VGC [VDC] 1.50 1.00 8.00 7.00 6.00 5.00 4.00 3.00 Phase Err, -40°C 2.00 0.50 Phase Err, +25°C 1.00 0.00 1.2 1.3 1.4 1.5 1.6 VGC (VDC) 2-18 Phase Err, +85°C 0.00 1.7 1.8 1.9 2.0 1.2 1.3 1.4 1.5 1.6 1.7 1.8 1.9 2.0 VGC (VDC) Rev A9 020122 RF2938 RSSI versus VGC (VCC=3.15V, Temp=25oC, IF LO=-10dBm) 2.800 2.600 2.500 2.400 2.300 RSSI, VGC= 1.2V RSSI, VGC= 1.4V RSSI, VGC= 1.6V RSSI, VGC= 1.8V RSSI, VGC= 2.0V 2.200 2.100 2.000 1.900 1.800 2.700 RSSI, Vcc= 2.7V 2.600 RSSI, Vcc= 3.15V RSSI, Vcc= 3.6V 2.500 2.400 2.300 2.200 RSSI (VDC) RSSI (VDC) RSSI versus VCC (VGC=1.4V, Temp=25oC, IF LO=-10dBm) 1.700 1.600 1.500 1.400 2.100 2.000 1.900 1.800 1.700 1.300 1.200 1.100 1.000 0.900 1.600 0.800 0.700 0.600 -100 1.200 1.500 1.400 1.300 1.100 -90 -80 -70 -60 -50 -40 -30 -20 -10 1.000 -100 0 -90 -80 -70 -60 -50 -40 -30 -20 -10 0 RF Lvl (dBm) RSSI versus Temp (VCC=3.15V, VGC=1.4V, IF LO=-10dBm) 8B RF Lvl (dBm) PA Gain versus VCC (PA in=2440MHz@-30dBm) 2.600 RSSI, -40°C 2.400 RSSI, +25°C 2.300 RSSI, +85°C 24.00 23.75 23.50 23.25 2.200 Gain (dB) 2.000 1.900 1.800 1.700 1.600 1.300 21.75 21.50 21.25 21.00 1.100 -80 -70 -60 -50 -40 -30 -20 ad ed -90 -10 11 19.50 19.25 19.00 2.70 P 1.200 0 3.15 RF Lvl (dBm) PA IIP3 versus VCC PA OP1dB versus VCC 2.00 14.25 -40C OP1dB 25C OP1dB 85C OP1dB 14.00 -40C IIP3 25C IIP3 13.75 85C IIP3 S ee IIP3 (dBm) 2.25 (PA in=2440MHz) 14.50 OP1dB (dBm) 2.50 U pg r 3.25 3.60 VCC (V) (PA in=2439 & 2440MHz@13dB Below IP1dB Point) 2.75 85C Gain TRANSCEIVERS 1.400 3.00 25C Gain 20.75 20.50 20.25 20.00 19.75 1.500 1.000 -100 -40C Gain 23.00 22.75 22.50 22.25 22.00 ro du ct RSSI (VDC) 2.100 R F2 94 2.500 1.75 1.50 1.25 1.00 13.50 13.25 13.00 12.75 0.75 12.50 0.50 12.25 0.25 0.00 2.70 3.15 VCC (V) Rev A9 020122 3.60 12.00 2.70 3.15 3.60 VCC (V) 2-19 RF2938 PA 2f0 versus VCC (PA in=2440MHz@-15dBm, 2nd Harmonic=4800MHz) 35.00 34.75 34.50 -40C 2fo 25C 2fo 85C 2fo 34.25 34.00 2f0 (dBc) 33.75 33.50 33.25 33.00 32.75 32.50 32.25 32.00 31.75 31.50 31.25 2.70 3.15 3.60 ro du ct R F2 94 8B VCC (V) S ee U pg r ad ed TRANSCEIVERS P 11 2-20 Rev A9 020122