ETC U4090B

U4090B
Monolithic Integrated Feature Phone Circuit
Description
The µc-controlled telephone circuit U4090B is a linear
integrated circuit for use in feature phones, answering
machines and fax machines. It contains the speech circuit,
tone ringer interface with DC/DC converter, sidetone
equivalent and ear protection rectifiers. The circuit is line
powered and contains all components necessary for
amplification of signals and adaptation to the line.
An integrated voice switch with loudspeaker amplifier
allows loudhearing or hands-free operation. With an
anti-feedback function, acoustical feedback during
loudhearing can be reduced significantly. The generated
supply voltage is suitable for a wide range of peripheral
circuits.
Features
DC characteristic adjustable
Tone ringer interface with dc/dc converter
Transmit and receive gain adjustable
Zero crossing detection
Symmetrical input of microphone amplifier
Common speaker for loudhearing and tone ringer
Anti-clipping in transmit direction
Supply voltages for all functional blocks of a
subscriber set
Automatic line-loss compensation
Integrated transistor for short circuiting the line
voltage
Symmetrical output of earpiece amplifier
Built-in ear protection
Answering machine interface
DTMF and MUTE input
Adjustable sidetone suppression independent
of sending and receiving amplification
Operation possible from-10 mA line currents
Speech circuit with two sidetone networks
Benefits
Built-in line detection circuit
Savings of one piezo-electric transducer
Integrated amplifier for loudhearing operation
Complete system integration of analog signal processing on one chip
Anti-clipping for loudspeaker amplifier
Improved acoustical feedback suppression
Very few external components
Power down
Applications
Voice switch
Feature phone, answering machine, fax machine, speaker
phone
Block Diagram
Speech
circuit
Audio
amplifier
Voice
switch
Tone
ringer
Loudhearing
and
Tone ringing
MC with
EEPROM/
DTMF
94 8741
Ordering Information
Extended Type Number
U4090B-NFN
U4090B-NFNG3
Rev. C2, 07-Mar-01
Package
SSO44
SSO44
Remarks
Taped and reeled
1 (31)
2 (31)
42
2
SAI
TSACL
SAO
24
22
12
26
29
TLDT
ATAFS
30
TLDR
INLDT 27
TX
ACL
MIC
GSA
23
SAI
SACL
SA
Acoustical
feedback
suppression
control
DTMF
4
5
INLDR 28
TTXA
DTMF
MIC2
MIC1
94 8064
3
44
35
MUTR
25
MUTX
Mute
receive
control
Transmit
mute
control
1
GT MICO TXIN
TXA
36
RA2
40
41
39
RA1
900 600 VL
8
21
IMPSEL
Impedance
control
RECO2 RECO1 GR RAC
–1
33
STO
ST
BAL
AGA
control
31
AGA
L
37
–
+
Line
detect
I
Current
supply
VMP
I Supply
RECIN
43
V
MP
14
Power
supply
Receive
attenuation
Q
S
VL
SENSE V
B
11
10
STIL STIS
38
+
–
7
IND
–
+
–
+
V
MPS
13
I
REF
PD
GND
V
M
18
19
15
16
THA
RFDO
SW
OUT
C
OSC
V
RING
17 LIDET
20
32
6
9
34
U4090B
Detailed Block Diagram
Figure 1. Detailed block diagram
Rev. C2, 07-Mar-01
U4090B
Pin Description
GT
1
44
TXIN
DTMF
2
43
RECIN
MICO
3
42
TTXA
MIC2
4
41
GR
MIC1
5
40
RECO1
3
4
PD
6
39
RAC
5
IND
7
38
STIL
6
VL
8
37
STIS
GND
9
36
RECO2
SENSE
10
35
MUTR
VB
11
34
VM
SAO
12
33
STO
VMPS 13
32
IREF
VMP 14
31
AGA
U4090B
SWOUT
15
30
TLDR
COSC
16
29
TLDT
VRING
17
28
INLDR
THA
18
27
INLDT
RFDO
19
26
ATAFS
LIDET
20
25
MUTX
IMPSEL
21
24
SAI
TSACL
22
23
GSA
Pin
1
Symbol
Function
A resistor from this pin to GND sets the
GT
amplification of microphone and DTMF
signals,theinputamplifiercanbemuted by
applying VMP to GT.
2
7
8
9
10
11
12
13
14
15
16
DTMF
Input for DTMF signals,
also used for the answering machine
and hands-free input
MICO Output of microphone preamplifier
MIC 2 Non-inverting input of microphone
amplifier
MIC 1 Inverting input of microphone
amplifier
PD
Active high input for reducing the
current consumption of the circuit,
simultaneously VL is shorted by an
internal switch
IND
The internal equivalent inductance of
the circuit is proportional to the value
of the capacitor at this pin,
a resistor connected to ground may be
used to reduce the dc line voltage
VL
Line voltage
GND Reference point for dc- and ac-output
signals
SENSE A small resistor (fixed) connected
from this pin to VL sets the slope of
the dc characteristic and also effects
the line-lengthequalization
characteristics and the line current at
which the loudspeaker amplifier is
switched on
VB
Unregulated supply voltage for
peripheral circuits (voice switch),
limited to typically 7 V
SAO Output of loudspeaker amplifier
VMPS Unregulated supply voltage for µC,
limited to 6.3 V
VMP
Regulated supply voltage 3.3 V for
peripheral circuits (especially
microprocessors),
minimum output current: 2 mA
(ringing)
4 mA (speech mode)
SWOUT Output for driving external switching
transistor
COSC 40-kHz oscillator for ringing power
converter
94 7905 e
Rev. C2, 07-Mar-01
3 (31)
U4090B
Pin
17
18
19
20
21
22
23
24
25
26
27
28
Symbol
Function
VRING Input for ringing signal protected by
internal zener diode
THA Threshold adjustment for ringing
frequency detector
RFDO Output of ringing frequency detector
LIDET Line detect; output is low when the
line current is more than 15 mA
IMP- Control input for selection of line
SEL
impedance
1. 600 Ω
2. 900 Ω
3. Mute of second transmit stage
(TXA); also used for indication of
external supply (answering machine);
last chosen impedance is stored
TSACL Time constant of anti-clipping of
speaker amplifier
GSA Current input for setting the gain of
the speaker amplifier,
adjustment characteristic is
logarithmical,
or RGSA > 2 MΩ, the speaker
amplifier is switched off
SA I
Speaker amplifier input (for
loudspeaker, tone ringer and
hands-free use)
MUTX Three-state input of transmit mute:
1) Speech condition; inputs MIC1 /
MIC2 active
2) DTMF condition; input DTMF
active
a part of the input signal is
passed to the receiving amplifier
as a confidence signal during
dialing
3) Input DTMF used for answering
machine and hands-free use;
receive branch not affected
ATAFS Attenuation of acoustical feedback
suppression,
maximum attenuation of AFS circuit
is set by a resistor at this pin,
without the resistor, AFS is switched
off
INLDT Input of transmit level detector
INLDR Input of receive level detector
4 (31)
Pin
29
30
31
32
33
34
35
36
37
38
39
40
41
42
43
44
Symbol
Function
TLDT Time constant of transmit level
detector
TLDR Time constant of receive level
detector
AGA Automatic gain adjustment with line
current
a resistor connected from this pin to
GND sets the starting point
max. gain change: 6 dB.
IREF Internal reference current generation;
RREF = 62 kΩ; IREF = 20 µA
STO
Sidetone reduction output
output resistance approx.: 300 Ω,
maximum load impedance: 10 kΩ.
VM
Reference node for microphoneearphone and loudspeaker amplifier,
supply for electret microphone
(IM ≤ 700 A)
MUTR Three-state mute input
1. Normal operation
2. Mute of ear piece
3. Mute of RECIN signal
Condition of earpiece mute is stored
RECO 2 Inverting output of receiving
amplifier
STI S Input for sidetone network (short
loop) or for answering machine
STI L Input for sidetone network (long
loop)
RAC Input of receiving amplifier for ac
coupling in feedback path
RECO 1 Output of receiving amplifier
GR
A resistor connected from this pin to
GNDsetsthereceivingamplification of
the circuit; amplifier RA1 can be
muted by applying VMP to GR
TTXA Time constant of anti-clipping in
transmit path
RECIN Input of receiving path; input
impedance is typically 80 k
TXIN Input of intermediate transmit stage,
input resistance is typically 20 kΩ
Rev. C2, 07-Mar-01
U4090B
DC Line Interface and Supply-Voltage Generation
The DC line interface consists of an electronic inductance
and a dual-port output stage which charges the capacitors
at VMPS and VB. The value of the equivalent inductance
is given by:
L = RSENSECIND((RDCR30) / (RDC + R30))
In order to improve the supply during worst-case operating conditions, two PNP current sources - IBOPT and
VL
IMPSOPT - hand an extra amount of current to the supply
voltages when the NPNs in parallel are unable to conduct
current.
A flowchart for the control of the current sources
(figure 3) shows how a priority for supply VMPS is
achieved.
10 SENSE
RSENSE
IBOPT
IMPSOPT
< 5 mA
< 5 mA
CIND
6.3 V VMPS
10 F
–
+
+
–
IND
RDC
R30
30 k
=
470 F
=
VMP
3.3 V
+
–
VOFFS
7.0 V
3.3 V/
2 mA
47 F
VB
220 F
94 8047
Figure 2. DC line interface with electronic inductance and generation of a regulated and an unregulated supply
Y
VMPS < 6.3 V
N
VSENSE–VMPS>200 mV
N
Y
N
VSENSE–VB>200 mV
IMPSOPT = 0
IBOPT = 0
Y
VB < 6.3 V
N
Y
Charge CMPS
(IMPSOPT)
Charge CB
(IBOPT)
Reduce IBOPT
(IMPSOPT = 0)
94 8058
Figure 3. Supply capacitors CMPS and CB are charged with priority on CMPS
Rev. C2, 07-Mar-01
5 (31)
U4090B
VRING
RPC
VB
7V
Voltage
regulator
VMP
VMPS
Power
supply
VL
6.3 V
Voltage
regulator
QS
PD
ES IMPED
CONTR
LIDET
IMPSEL
LIDET
VLon
RFD
RFDO
TXA
TXACL
SAI,SA
SACL
OFFSA
COMP
AFS
MIC, DTMF
AGA, RA1, RA2
TX MUTE
MUT REC, STBAL
RECATT
94 8046
Figure 4. Supply of functional blocks is controlled by input voltages VL, VB, VRING
and by logic inputs PD and IMPSEL
The U4090B contains two identical series regulators
which provide a supply voltage VMP of 3.3 V suitable for
a microprocessor. In speech mode, both regulators are
active because VMPS and VB are charged simultaneously
by the DC-line interface. Output current is 4 mA. The
capacitor at VMPS is used to provide the microcomputer
with sufficient power during long-line interruptions.
Thus, long flash pulses can be bridged or a LCD display
can be turned on for more than 2 seconds after going on
hook. When the system is in ringing mode, VB is charged
by the on-chip ringing power converter. In this mode only
one regulator is used to supply VMP with max. 2 mA.
Supply Structure of the Chip
The special supply topology for the various functional
blocks is illustrated in figure 4.
There are four major supply states:
1.
2.
3.
4.
Speech condition
Power down (pulse dialing)
Ringing
External supply
1. In speech condition the system is supplied by the line
current. If the LIDET-block detects a line voltage
above the fixed threshold (1.9 V), the internal signal
VLON is activated, thus switching off RFD and RPC
and switching on all other blocks of the chip.
As a major benefit the chip uses a very flexible system
structure which allows simple realization of numerous
applications such as:
At line voltages below 1.9 V, the switches remain in their
quiescent state as shown in the diagram.
Group listening phone
OFFSACOMP disables the group listening feature (SAI,
SA, SACL, AFS) below line currents of approximately
10 mA.
Hands-free phone
Ringing with the built in speaker amplifier
Answering machine with external supply
6 (31)
2. When the chip is in power-down mode (PD = high),
e.g., during pulse dialing, the internal switch QS shorts
the line and all amplifiers are switched off. In this
Rev. C2, 07-Mar-01
U4090B
condition, LIDET, voltage regulators and IMPED
CONTR are the only active blocks.
circuit, which uses a modified voice switch topology.
Figure 5 shows the basic system configuration.
3. During ringing, the supply for the system is fed into VB
via the ringing power converter (RPC). The only
functional amplifiers are in the speaker amplifier section (SAI, SA, SACL).
Two attenuators (TX ATT and RX ATT) reduce the
critical loop gain by introducing an externally adjustable
amount of loss either in the transmit or in the receive path.
The sliding control in block ATT CONTR determines,
whether the TX or the RX signal has to be attenuated. The
overall loop gain remains constant under all operating
conditions.
4. In an answering machine, the chip is powered by an
external supply via pin VB. This application allows the
posibility to activate all amplifiers (except the
transmit line interface TXA). Selecting IMPSEL = high impedance activates all switches at the ES
line.
Acoustic Feedback Suppression
Acoustical feedback from the loudspeaker to the handset
microphone may cause instability in the system. The
U4090B offers a very efficient feedback suppression
Selection of the active channel is made by comparison of
the logarithmically compressed TX- and RX- envelope
curve.
The system configuration for group listening, which is
realized in the U4090B, is illustrated in figure 7. TXA and
SAI represent the two attenuators, the logarithmic envelope detectors are shown in a simplified way (operational
amplifiers with two diodes).
TX
Att
Handset
microphone
Log
Hybrid
Line
Att
contr
Log
Loudspeaker
RX
Att
94 8956
Figure 5. Basic voice switch system
Rev. C2, 07-Mar-01
7 (31)
U4090B
VL
GT
MICO
TIN
INLDT
TLDT
STO
–
+
VBG
VL
ZL
TXA
Zint
SAO
AFS
control
Max
att.
AGA
GSA
–
+ VBG
SAI
SAI
TLDR
INLDR
RECIN
RECO1
GR STIS
STO
STN
94 8059
Figure 6. Integration of acoustic feedback suppression circuit into the speech circuit environment
TLDT
TXA
TX
SAI
RLDT
INLDT
AGA
AGA
RX
IAGAFS
RLDR
IAT
IATAFS
INLDR
IGSA
IATGSA
94 8060
TLDR
ATAFS
GSA
RATAFS
Figure 7. Acoustic feedback suppression by alternative control of transmit- and speaker amplifier gain
8 (31)
Rev. C2, 07-Mar-01
U4090B
94 8958
A detailed diagram of the AFS (acoustic feedback
suppression) is given in figure 7. Receive and Transmit
signals are first processed by logarithmic rectifiers in
order to produce the envelopes of the speech at TLDT and
RLDT. After amplification, a decision is made by the
differential pair which direction should be transmitted.
LIDET
IL
The attenuation of the controlled amplifiers TXA and SAI
is determined by the emitter current IAT which is consists
of three parts:
IATAS
IATGSA
IAGAFS
sets maximum attenuation
decreases the attenuation when speaker
amplifier gain is reduced
decreases the attenuation according to the
loop gain reduction caused by the AGA–
function
PD
Figure 9. Line detection with two comparators for speech mode
and pulse dialing
IAT = IATAFS - IATGSA - IAGAFS
Line Detection (LIDET)
G = IAT0.67 dB/ A
Figure 8 illustrates the principle relationship between
speaker amplifier gain (GSA) and attenuation of AFS
(ATAFS). Both parameters can be adjusted
independently, but the internal coupling between them
has to be considered. Maximum usable value of GSA is
36 dB. The shape of the characteristic is moved in the
x-direction by adjusting resistor RATAFS, thus changing
ATAFSm. The actual value of attenuation (ATAFSa),
however, can be determined by reading the value which
belongs to the actual gain GSAa. If the speaker amplifier
gain is reduced, the attenuation of AFS is automatically
reduced by the same amount in order to achieve a constant
loop gain. Zero attenuation is set for speaker gains GSA
GSA0 = 36 dB - ATAFSm.
The line current supervision is active under all operating
conditions of the U4090B. In speech mode
(PD = inactive), the line-current comparator uses the
same thresholds as the comparator for switching off the
entire speaker amplifier. The basic behavior is illustrated
in figure 10. Actual values of ILON/ILOFF vary slightly
with the adjustment of the DC characteristics and the
selection of the internal line impedance.
When Power Down is activated (during pulse dialing), the
entire line current flows through the short-circuiting
transistor QS (see figure 4). As long as IL is above typ.
1.6 mA, output LIDET is low. This comparator does not
use hysteresis.
94 8959
94 8957
ATAFS (dB)
ATAFS m
RATAFS
ATAFS a
GSAo
LIDET
RATAFS
GSA a
36 dB
not usable
GSA (dB)
ILOFF
ILON
IL
Figure 10. Line detection in speech mode with hysteresis
Figure 8. Reducing speaker amplifier gain results in an equal
reduction of AFS attenuation
Rev. C2, 07-Mar-01
9 (31)
U4090B
Ringing Power Converter (RPC)
Ringing Frequency Detector (RFD)
The RPC transforms the input power at VRING (high
voltage/ low current) into an equivalent output power at
VB (low voltage/ high current) which is capable of driving
the low-ohmic loudspeaker. Input impedance at VRING
is fixed at 5 k and the efficiency of the step-down
converter is approx. 65%.
The U4090B offers an output signal for the microcontroller, which is a digital representation of the double
ringing frequency. It is generated by a current comparator
with hysteresis. The input voltage VRING is transformed
into a current via RTHA. The thresholds are 8 A and
24 A. RFDO and VRING are in phase. A second comparator with hysteresis is used to enable the output RFDO
as long as the supply voltage for the microprocessor VMP
is above 2.0 V.
7
RDC=∞
VL ( V )
6
RDC=130k
5
RDC=68k
4
3
10
12
14
16
18
20
IL ( mA )
94 9131
= ILON
at line impedance = 600 = ILOFF
= ILON
at line impedance = 900 = ILOFF
Figure 11. Comparator thresholds depending on dc mask and
line impedance
Absolute Maximum Ratings
Parameters
Line current
DC line voltage
Maximum input current
Junction temperature
Ambient temperature
Storage temperature
Total power dissipation, Tamb = 60°C
Pin 17
Symbol
IL
VL
IRING
Tj
Tamb
Tstg
Ptot
Value
140
12
15
125
–25 to +75
–55 to +150
0.9
Unit
mA
V
mA
°C
°C
°C
W
Symbol
RthJA
Value
70
Unit
K/W
Thermal Resistance
Junction ambient
10 (31)
Parameters
SSO44
Rev. C2, 07-Mar-01
U4090B
Electrical Characteristics
f = 1 kHz, 0 dBm = 775 mVrms, IM = 0.3 mA, IMP = 2 mA, RDC = 130 k, Tamb = 25°C, RGSA = 560k,
Zear = 68 nF + 100 , ZM = 68 nF, Pin 31 open, VIMPSEL = GND, VMUTX = GND, VMUTR = GND, unless otherwise
specified.
Parameters
Test Conditions / Pin
Symbol
Min.
DC characteristics
DC voltage drop over circuit IL = 2 mA
VL
IL = 14 mA
4.6
IL = 60 mA
IL = 100 mA
8.8
Transmission amplifier, IL = 14 mA, VMIC = 2 mV, RGT = 27 k, unless
Range of transmit gain
GT
40
Transmitting amplification
RGT = 12 k
47
RGT = 27 k
GT
39.8
Frequency response
IL 14 mA,
GT
f = 300 to 3400 Hz
Gain change with current
Pin 31 open
GT
IL = 14 to 100 mA
Gain deviation
Tamb = –10 to +60°C
GT
CMRR of microphone
CMRR
60
amplifier
Input resistance of MIC
RGT = 12 k
Ri
amplifier
RGT = 27 k
45
Distortion at line
IL > 14 mA
dt
VL = 700 mVrms
IL > 19 mA, d < 5%
VLmax
1.8
Maximum output voltage
Vmic = 25 mV
CTXA = 1 F
IMPSEL = open
VMICOmax
RGT = 12 k
Noise at line
IL > 14 mA
no
psophometrically weighted GT = 48 dB
Anti-clipping attack time
CTXA = 1 F
release time
each 3 dB overdrive
Gain at low operating
IL = 10 mA
current
IMP = 1 mA
GT
40
RDC = 68 k
Vmic = 1 mV
IM = 300 A
Distortion at low operating IL = 10 mA
current
IM = 300 A
dt
IMP = 1 mA
RDC = 68 k
Vmic = 10 mV
Line loss compensation
IL = 100 mA,
GTI
–6.4
RAGA = 20 k
IL 14 mA
GTM
60
Mute suppression
a) MIC muted (microphone Mutx = open
preamplifier
p
p
IMPSEL = open
GTTX
60
b) TXA muted (second
stage)
Rev. C2, 07-Mar-01
Typ.
2.4
5.0
7.5
9.4
otherwise
45
48
Max.
Unit
Figure
5.4
V
20
10.0
specified
50
dB
49
dB
41.8
0.5
dB
21
21
0.5
dB
21
0.5
dB
dB
21
21
80
50
75
3
21
k
21
110
2
%
21
4.2
dBm
21
dBm
21
–5.2
21
–80
0.5
9
–5.8
80
–72
dBmp
ms
21
42.5
dB
21
5
%
21
–5.2
dB
21
dB
21
dB
21
11 (31)
U4090B
Electrical Characteristics (continued)
Parameters
Test Conditions / Pin
Symbol
Min.
Typ.
Max.
Unit
Receiving amplifier, IL = 14 mA, RGR = 62 k, unless otherwise specified, VGEN = 300 mV
Adjustment range of
IL 14 mA, single
GR
–8
+2
dB
receiving gain
ended
–2
+8
differential MUTR =
GND
Receiving amplification
RGR = 62 k
GR
– 1.75
–1
– 0.25
dB
differential
RGR = 22 k
7.5
differential
Amplification of DTMF sig- IL 14 mA
GRM
7
10
13
dB
nal from DTMF IN to
VMUTX = VMP
RECO 1, 2
Frequency response
IL > 14 mA,
GRF
0.5
dB
f = 300 to 3400 Hz
Gain change with current
IL = 14 to 100 mA
GR
0.5
dB
Gain deviation
Tamb = –10 to +60°C
GR
0.5
dB
Ear-protection differential
IL 14 mA
EP
2.2
Vrms
VGEN = 11 Vrms
MUTE suppression
IL 14 mA
GR
60
dB
a) RECATT
MUTR = open
b) RA2
VMUTR = VMP
c) DTMF operation
VMUTX = VMP
Output voltage d 2%
IL = 14 mA
differential
Zear = 68 nF + 100 0.775
Vrms
Maximum output current
Zear = 100 4
mA
d 2%
(peak)
Receiving noise
Zear = 68 nF + 100 ni
–80
–77
dBmp
psophometrically weighted IL 14 mA
Output resistance
each output against
Ro
10
GND
Line loss compensation
RAGA = 20 k
GRI
–7.0
–6.0
–5.0
dB
IL = 100 mA
Gain at low operating
IL = 10 mA
current
IMP = 1 mA
IM = 300 A
GR
–2
–1
0
dB
VGEN = 560 mV
RDC = 68 k
AC impedance
VIMPSEL = GND
Zimp
570
600
640
VIMPSEL = VMP
Zimp
840
900
960
Distortion at low operating IL = 10 mA
current
IMP = 1 mA
dR
5
%
VGEN = 560 mV
RDC = 68 k
12 (31)
Figure
22
22
22
22
22
22
22
22
22
22
22
22
22
22
22
22
Rev. C2, 07-Mar-01
U4090B
Electrical Characteristics (continued)
Parameters
Speaker amplifier
Minimum line current for
operation
Input resistance
Gain from SAI to SAO
Output power
Output noise (Input SAI
open)
psophometrically weighted
Gain deviation
Mute suppression
Test Conditions / Pin
No ac signal
Pin 24
VSAI = 3 mV,
IL = 15 mA,
RGSA = 560 k
RGSA = 20 k
Load resistance
RL = 50 , d < 5%
VSAI = 20 mV
IL = 15 mA
IL = 20 mA
IL > 15 mA
IL = 15 mA
Tamb = –10 to +60°C
IL = 15 mA,
VL = 0 dBm,
VSAI = 4 mV
Pin 23 open
IL = 15 to 100 mA
IL = 15 to 100 mA
Symbol
Min.
Typ.
ILmin
14
Max.
Unit
Figure
15
mA
23
22
k
23
dB
23
GSA
35.5
36.5
–3
3
7
20
37.5
23
PSA
PSA
nSA
mW
200
Vpsoph
23
GSA
1
dB
23
VSAO
–60
dBm
23
dB
M
23
23
dB
23
ms
ms
23
23
dB
24
dB
24
dB
24
k
24
%
24
dB
24
Gain change with current
GSA
1
Resistor for turning off
RGSA
0.8
1.3
2
speaker amplifier
Gain change with frequency IL = 15 mA
GSA
0.5
f = 300 to 3400 Hz
Attack time of anti-clipping 20 dB over drive
tr
5
Release time of antitf
80
clipping
DTMF amplifier
Test conditions: IMP = 2 mA, IM = 0.3 mA, VMUTX = VMP
Adjustment range of DTMF IL = 15 mA
GD
40
50
gain
Mute active
DTMF amplification
IL = 15 mA,
GD
40.7
41.7
42.7
VDTMF = 8 mV
Mute active:
MUTX = VMP
Gain deviaton
IL = 15 mA
GD
0.5
Tamb = –10 to +60 °C
Input resistance
RGT = 27 k,
Ri
60
180
300
RGT = 15 k
26
70
130
Distortion of DTMF signal
IL 15 mA
dD
2
VL = 0 dBm
Gain deviation with current IL = 15 to 100 mA
GD
0.5
Rev. C2, 07-Mar-01
13 (31)
U4090B
Electrical Characteristics (continued)
Parameters
Test Conditions / Pin
Symbol
AFS acoustic feedback suppression
Adjustment range of
IL 15 mA
attenuation
Attenuation of transmit
IL 15 mA,
GT
gain
IINLDT = 0 A
RATAFS = 30 k
IINLDR = 10 A
Attenuation of speaker
IL 15 mA
GSA
amplifier
IINLDP = 0 RATAFS = 30 k
IINLDR = 10 AFS disable
IL 15 mA
VATAFS
Supply voltages, Vmic = 25 mV, Tamb = – 10 to + 60°C
VMP
IL = 14 mA,
VMP
RDC = 68 k
IMP = 2 mA
VMPS
IL = 100 mA
VMPS
RDC = inf.,
IMP = 0 mA
VM
IL 14 mA,
VM
IM = 700 A
RDC = 130 k
VB
IB = + 20 mA,
VB
IL = 0 mA
Ringing power converter, IMP = 1 mA, IM = 0
Maximum output power
VRING = 20.6 V
PSA
Threshold of ring
RFDO: low to high
VRINGON
frequency detector
VHYST
= VRINGON - RINGOFF VHYST
Input impedance
VRING = 30 V
RRING
Input impedance in speech f = 300 Hz to 3400 Hz
RRINGSP
mode
IL > 15 mA,
Min.
Typ.
Max.
Unit
Figure
50
dB
23
45
dB
23
50
dB
23
V
23
3.5
V
20
6.7
V
20
3.3
V
20
7.6
V
20
mW
25
V
25
k
k
25
25
V
25
2.2
V
25
33.3
V
25
0
1.5
3.1
3.3
1.3
7
20
17.5
4
150
11.0
5
6
VRING = 20V + 1.5Vrms
Logic level of frequency
detector
Ring detector enable
Zener diode voltage
14 (31)
VRING = 0 V
VB = 4 V
VRING = 25 V
VRING = 25 V,
RFDO high
IRING = 25 mA
VRFDO
0
VMPON
1.8
VRINGmax
30.8
VMP
2.0
Rev. C2, 07-Mar-01
U4090B
Electrical Characteristics (continued)
Parameters
MUTR Input
MUTR input current
MUTR input voltage
Test Conditions / Pin
Symbol
VMUTR = GND
IL > 14 mA
VMUTR = VMP
Mute low; IL >
14 mA
Mute high;
IL > 14 mA
IMUTE
PD Input
PD input current
PD active, IL >
14 mA VPD = VMP
Input voltage
PD = active
PD = inactive
Voltage drop at VL
IL = 14 mA,
PD = active
IL = 100 mA,
PD = active
Input characteristics of IMPSEL
Input current
IL 14 mA
VIMPSEL = VMP
VIMPSEL = GND
Input voltage
Input high
MUTX input
Input current
Input voltage
Line detection
Line current for LIDET
active
Line current for LIDET
inactive
Current threshold during
power down
Rev. C2, 07-Mar-01
Min.
Typ.
Max.
Unit
Figure
–20
–30
A
26
0.3
V
26
V
26
uA
26
V
26
V
26
+10
VMUTE
VMUTE
VMP-0.3
V
Ipd
Vpd
Vpd
VL
9
2
0.3
1.5
VL
1.9
IIMPSEL
IIMPSEL
VIMPSEL
18
–18
Input low
VIMPSEL
VMUTX = VMP
VMUTX = GND
Input high
IMUTX
IMUTX
VMUTX
Input low
VMUTX
A
A
V
VMP-0.3
V
20
–20
26
26
0.3
V
26
30
–30
A
A
V
26
V
26
VMP-0.3
V
0.3
26
PD = inactive
ILON
12.6
mA
20
PD = inactive
ILOFF
11.0
mA
20
mA
20
VB = 5 V, PD = active
ILONPD
0.8
1.6
2.4
15 (31)
U4090B
U4090B - Control
IMPSEL
0
0 to Z
1 to Z
1
0
0 to Z
1 to Z
1
Line-impedance = 600 TXA = on
ES = off
Line-impedance = 600 TXA = off
ES = on
Line-impedance = 900 TXA = off
ES = on
Line-impedance = 900 TXA = on
ES = off
MUTR
RA2 = on
RECATT = on
STIS + STIL = on
RA2 = on
RECATT = off
STIS = on, STIL = off
RA2 = off
RECATT = off
STIS = on, STIL = off
AGA off for STIS
RA2 = off
RECATT = on
STIS + STIL = on
MODE
Speech
MUTX
0
Transmit-mute
Z
Transmit-mute
Speech
1
MODE
Speech
For answering
machine
For answering
machine
Speech + earpeace mute
MIC 1/2 transmit enabled
receive enable
AFS = on
AGA = on
TXACL = on
DTMF transmit enabled
receive enable
AFS = on
AGA = on
TXACL = on
DTMF transmit enabled
DTMF to receive enable
AFS = off
AGA = off
TXACL = off
MODE
Speech
For answering
machine
DTMF dialling
Logic-level
0 = < (0.3 V)
Z = > (1 V) < (VMP – 1 V) or (open input)
1 = > (VMP – 0.3 V)
RECATT = Receive attenuation
STIS, STIL = Inputs of sidetone balancing amplifiers
ES = External supply
AFS = Acoustic feedback suppression control
AGA = Automatic gain adjustment
RA2 = Inverting receive amplifier
TXACL = Transmit anti-clipping control
94 8856
Figure 12. Typical DC characteristic
16 (31)
Rev. C2, 07-Mar-01
U4090B
GT (dB)
RGT (kohm)
94 8860
Figure 13. Typical adjustment range of transmit gain
94 8859
Figure 14. Typical adjustment range of receive gain (differential output)
Rev. C2, 07-Mar-01
17 (31)
U4090B
948855
Figure 15. Typical AGA characteristic
94 8858
Figure 16. Typical load characteristic of VB for a maximum (RDC = infinity)
DC-characteristic and 3-mW loudspeaker output
18 (31)
Rev. C2, 07-Mar-01
U4090B
94 8874
Figure 17. Typical load characteristic of VB for a medium DC-characteristic
(RDC = 130 k) and 3-mW loudspeaker output
94 8861
Figure 18. Typical load characteristic of VB for a minimum DC-characteristic
(RDC = 68 k) and 3-mW loudspeaker output
Rev. C2, 07-Mar-01
19 (31)
20 (31)
4
41
68 nF
5
40
ZEAR
RGR
6
39
10 F
VM
VM
10 F
8
600 37
3 k
22 F
7
38
3 k
VM
RDC
reference figure for not connected pins
S1 = closed: speech mode
S2 = closed: ringer mode
3
42
1 F
1 k
VM
2
1
RGT
43
150 nF
44
220 nF
VL
9
10
35
S1
4.7 nF
36
open
10 IL
33
IM
11
13
32
220 F
50 47 F 1000 F
12
U4090B
34
100 F
36 k
47 nF
VMP
36 k
47 nF
47 F
14
31
62 k 2.2 mH
IDC
IMP
15
30
10 F
68 nF
17
28
3.3 nF
S2
18
27
3.3 nF
SD103A
BC556
16
29
10 F
DC
VRing
680 k 19
26
2 M
20
25
open
VMP
1 F
VMP
open
21
24
22
23
RGSA
94 9132
Mico
U4090B
Figure 19. Basic test circuit
Rev. C2, 07-Mar-01
Rev. C2, 07-Mar-01
VL
2
1
3
42
VMIC
4
41
VMP
5
40
68 nF
RGR
6
39
VM
RDC
7
38
10 F
10 F
8
37
ZEAR
Line detection: S1a
VB (external supply): S1b
open pins should be connected as shown in figure 25
RGT
43
44
220 nF 150 nF 1 F
Mico
IL
9
VL
V
10
35
4.7 nF
36
34
33
IM
IB
10 12
13
32
14
31
62 k b
a
open
DC
VB
S1
220 F 1000 F 47 F
11
U4090B
100 F
IMP
15
30
RAGA
16
29
17
28
18
27
19
26
VLIDET
30 k
V
20
25
1 F
21
24
RGSA
22
23
U4090B
Figure 20. Test circuit for DC characteristics and line detection
21 (31)
94 9133
22 (31)
VL
1
44
3
1 F
b
AC
25 k S1
1 F
42
V
RGTVMICO
max
2
43
220 nF 150 nF
Mico
S2
a
5
40
b
68 nF
Vmic
VCM
4
41
RGR
S1
25 k a
6
39
VM
RDC
10 F
22 F
8
37
ZEAR
600 7
38
10 F
V
4.7 nF
9
10 10
35
33
11
220 F
13
1000 F
12
32
47 F
14
31
S3
62 k 15
30
RAGA
I MP
16
29
VL
Vmic
17
28
18
27
19
26
V MP
open
V MP
20
25
VL (S2 = open)
VL (S2 = closed)
50 k
–1
+ GT with S1b, S2 = closed,S3 = open
VL (at IMPSEL = open)
VL (at IMPSEL = low)
VL (at MUTX = open)
VL (at MUTX = low)
open pins should be connected as shown in figure 25
GTTX = 20*log
Mute suppression: GTM = 20*log
VCM
Common mode rejection ratio: CMRR = 20*log
VL
Input resistance: Ri =
Gain change with current: GTI = GT (at IL = 100 mA) –GT (at IL = 14 mA)
Line loss compensation: GTI = GT (at IL = 100 mA) –GT (at IL = 14 mA), S3 = closed
Transmitting amplification GT = 20*log
IL
34
IM
U4090B
100 F
VL, dt, n o
36
V MP
open
open
21
24
1 F
22
23
U4090B
Figure 21. Test circuit for transmission amplifier
Rev. C2, 07-Mar-01
94 9135
Rev. C2, 07-Mar-01
open
Mico
VL
VM
open
VMP
VMP
10 F
220 nF 150 nF 1 F
44
43
42
VZEAR, dr
RGR
ZEAR
41
40
39
38
RAGA
100 F
37
36
35
34
IM
33
62 k S3
31
30
29
28
27
26
25
24
23
13
14
15
16
17
18
19
20
21
22
U4090B
1
2
3
4
5
6
7
8
9
10
68 nF
220 F
RGT
10 10 F
VDTMF
220 nF
1 k
V
11
RDC
600 4.7 nF
12
1000 F
94 9134
Figure 22. Test circuit for receiving amplifier
32
47 F
IMP
IL
V
VLR
22 F
S2
VM
1F
VMP
open
S1
b
a
VGEN
AC
Line loss compensation: GRI = GR (at IL = 100 mA) –GR (at IL = 14 mA), S3 = closed
Receiving noise: S1a
Receive amplification: GR = 20*log ( VZEAR/VLR) dB (S1 = b, S2 open)
DTMF-control signal: GRM = 20*log (VZEAR/VDTMF) dB (S1 =a, S2 = closed)
AC-impedance: (VLR/ (VGEN – VLR)) * ZL
a) RECATT: GR = 20*log (VLR/VZEAR) dB +GR, MUTR = open
b) RA2: GR = 20*log (VLR/VZEAR) dB + GR, MUTR = VMP
23 (31)
c) DTMF operation: GR = 20*log VLR/VZEAR) dB + GR, MUTX = VMP
open pins should be connected as shown in figure 25
U4090B
Mute suppression:
VM
10 F
RGR
1 F
VATAFS
220 nF 150 nF
62 k
ZEAR
10 F
10 F
VSAI
V
220 nF
IINLDR IINLDT
Mico
RGSA
20
k
off
S4
44
43
42
41
40
39
38
37
36
35
34
33
31
30
29
28
27
26
25
24
23
13
14
15
16
17
18
19
20
21
22
U4090B
94 9137
Figure 23. Test circuit for speaker amplifier
32
1
2
3
4
5
6
7
8
9
10
11
12
10 F
68 nF
RGT
220 F
S1
10 RDC
1000 F
47 F
IMP
47 F
VMIC
VL
V
4.7 nF
22 F
50 600 IL
Input impedance: (VZIN/(VSAO – VZIN)) * RIN
Gain from SAI to SAO: 20*log (VSAO / VSAI) dB
Rev. C2, 07-Mar-01
2
VSAO
RSAO
Attenuation of transmit gain: S1 = closed
Open pins should be connected as shown in figure 25
Output power: PSA =
V
VSAO, S4 = closed
VZIN, S4 = open
n SA
VLIDET
V
1F
U4090B
24 (31)
30 k
Rev. C2, 07-Mar-01
VL
VGEN3
S3
220 nF
2
1
RGT
43
44
AC
50 k 3
1k
VM
42
220 nF 150 nF 1 F
Mico
4
41
V
VDTMF
5
40
68 nF
RGR
6
7
38
10 F
RDC
39
VM
10 F
4.7 nF
8
37
ZEAR
9
36
IL
10 10
35
34
33
IM
V
220 F
11
13
32
47 F
VL 50k: S3 = open
dD
14
31
62 k VL: S3 = closed
1000 F
12
U4090B
100 F
16
29
17
28
18
27
19
26
20
25
21
24
1 F
Open pins should be connected as shown in figure 25
Input resistance: (VL50K / (VL – VL50k)) * 50k
DTMF-amplifier: 20log (VL/VDTMF) dB
IMP
15
30
VMP
open
22
23
U4090B
Figure 24. Test circuit for DTMF amplifier
25 (31)
94 9136
26 (31)
43
2
44
1
3
42
4
41
68 nF
5
40
6
39
RDC
7
38
IL
10 F
8
37
4.7 nF
9
36
Open pins should be connected as shown in figure 25
10
35
33
10 12
13
32
220 F
50 15
30
2.2 mH
VMP
ramp
S5
47 F
14
31
62 k IMP
47F 1000 F
VSAO
11
U4090B
34
100 F
Vsao2
(S4 closed)
RSAO
2) Threshold of ringing frequency detector:
detecting VRFDO, when driving VRING from 2 V to 22 V (VRINGON)
and back again (VRINGOFF) (S2 = closed)
VRING
3) Input impedance: RRING =
(S3 = closed)
IRING
Vring
4) Input impedance in speech mode (IL > 15 mA):RRINGSP =
(S1 = closed)
Iring
5) Ring detector enable: detecting VRFDO, when driving VMP from 0.7 V to 3.3 V
(VMPON) and back again (VMPOFF) (S5, S3 = closed)
18
27
V
20 V
V
19
26
IRING
VRING
1.5 V
VRING
680 k
17
28
SD103A
BC556
68 nF
16
29
DC
S1
S2
ramp
VRFDO
20
25
S3
DC
IRING
21
24
100 nF
VSAI
1.8 Vpp
1 kHz
22
23
RGSA
DC
20.6 V
S4
1 F
94 9138
1) Max. output power: PSA =
U4090B
Figure 25. Test circuit for ringing power converter
Rev. C2, 07-Mar-01
Rev. C2, 07-Mar-01
VMP
VMP
100 F
10 F
ZEAR
RGR
44
43
42
41
40
39
38
RGSA
IMUTR
37
36
62 k
IM
35
34
33
IMUTX
32
31
30
29
28
27
26
25
24
23
13
14
15
16
17
18
19
20
21
22
1
2
3
4
5
6
7
8
9
10
11
12
94 9139
U4090B
68 nF
Ipd
RGT
10 10 F
220 F
47 F
IMP
IIMPSEL
1 F
1000 F
Vpd
open
Figure 26. Test circuit for input characteristics of I/O-ports
VM
4.7 nF
RDC
VMP
V
IL
VMP
27 (31)
U4090B
Open pins should be connected as shown in figure 25
VL
hook switch
VM
R3
12 V R2
C5
Figure 27. Application circuit for loudhearing
R27
C21
RECO C20 R20
R4
1
3
44
33 8
21
31
10
7
11
14
R19
C19
C18
4
2
9
6
32
42
20
17
U4090B
27
R17
R16
C14
Q1
C9
L1
R7
18
23
25 35
36
40
37
38
41 39
R11
R15
R14
R5
R6
19
22
24
VM
15
C15
VM
Ring
16
30
12
C16
C8
34
C17
29
R31
26
Loudspeaker
13
5
28
MICO
C7
C6
to C
Micro–
phone
C22
C4
to ST
R28
DTMF
Generator
C2
C1
R1
C3
C13
C10
R10
R13 R12
Rev. C2, 07-Mar-01
VM
R9
Earpeace
94 8849
C12
VM
43
R8
STN 2
(Option)
C11
ST
VL
Micro
controller
VMP
U4090B
28 (31)
Tip
Rev. C2, 07-Mar-01
R24
94 8850
VM
C24
C25
C26
R16
R29
C27 R30
R17
Loud
speaker
LOGTX
RECO
R22
HF–Mic
R23
C23
DTMF
R25
R15
R14
C14
C15
C16
R18
30
27
26
24
22
12
3
R13
23
1
28
42
2
4
5
R1
C17
29
C18
C21
Micro–
phone
R26
VM
R12
44
C1
33
25 35
to ST
C2
31
R11
40
7
R3
VM
C12
VM
R9
R10
C13
41 39
U4090B
21
Earpiece
36
8
12 V
R2
C3
C11
R8
ST
38
10
R4
C6
R7
BC177
R21
VB
R6
VM
to C
C8
LOGTX
VL
C10
18
19
15
16
20
17
9
6
32
34
13
43
C5
14
STN 2
(Option)
37
11
C4
L1
Q1 C9
R5
Micro–
controller
hook switch
Ring
VMP
C7
Tip
U4090B
Figure 28. Application for hands-free operation
29 (31)
U4090B
Table 6. Typical values of external components (figures 27 and 28)
Name
Value
Name
Value
Name
Value
Name
Value
C1
100 nF
C16
47 F
R3
>68 k
R18
30 k
C2
4.7 nF
C17
10 F
R4
10 k
R19
6.8 k
C3
10 F
C18
10 F
R5
1.5 k
R20
6.8 k
C4
220 F
C19
68 nF
R6
62 k
R21
15 k
C5
47 F
C20
68 nF
R7
680 k
R22
330 k
C6
470 F
C21
1 F
R8
22 k
R23
220 k
C7
820 nF
C22
100 nF
R9
330 k
R24
68 k
C8
100 F
C23
6.8 nF
R10
3 k
R25
2 k
C9
100 nF
C24
10 nF
R11
62 k
R26
3.3 k
C10
150 nF
C25
100 nF
R12
30 k
R27
18 k
C11
86 nF
C26
470 nF
R13
62 k
R28
2 k
C12
33 nF
C27
33 nF
R14
120 k
R29
1 k
C13
10 F
L1
2.2 mH
R15
47 k
R30
12 k
C14
100 nF
R1
27 k
R16
1 k
R31
56 k
C15
1 F
R2
20 k
R17
1.2 k
Package Information
Package SSO44
Dimensions in mm
9.15
8.65
18.05
17.80
7.50
7.30
2.35
0.3
0.25
0.10
0.8
0.25
10.50
10.20
16.8
44
23
technical drawings
according to DIN
specifications
13040
1
30 (31)
22
Rev. C2, 07-Mar-01
U4090B
Ozone Depleting Substances Policy Statement
It is the policy of Atmel Germany GmbH to
1. Meet all present and future national and international statutory requirements.
2. Regularly and continuously improve the performance of our products, processes, distribution and operating systems
with respect to their impact on the health and safety of our employees and the public, as well as their impact on
the environment.
It is particular concern to control or eliminate releases of those substances into the atmosphere which are known as
ozone depleting substances (ODSs).
The Montreal Protocol (1987) and its London Amendments (1990) intend to severely restrict the use of ODSs and forbid
their use within the next ten years. Various national and international initiatives are pressing for an earlier ban on these
substances.
Atmel Germany GmbH has been able to use its policy of continuous improvements to eliminate the use of ODSs listed
in the following documents.
1. Annex A, B and list of transitional substances of the Montreal Protocol and the London Amendments respectively
2. Class I and II ozone depleting substances in the Clean Air Act Amendments of 1990 by the Environmental
Protection Agency (EPA) in the USA
3. Council Decision 88/540/EEC and 91/690/EEC Annex A, B and C (transitional substances) respectively.
Atmel Germany GmbH can certify that our semiconductors are not manufactured with ozone depleting substances
and do not contain such substances.
We reserve the right to make changes to improve technical design and may do so without further notice.
Parameters can vary in different applications. All operating parameters must be validated for each customer
application by the customer. Should the buyer use Atmel Wireless & Microcontrollers products for any unintended
or unauthorized application, the buyer shall indemnify Atmel Wireless & Microcontrollers against all claims,
costs, damages, and expenses, arising out of, directly or indirectly, any claim of personal damage, injury or death
associated with such unintended or unauthorized use.
Data sheets can also be retrieved from the Internet:
http://www.atmel–wm.com
Atmel Germany GmbH, P.O.B. 3535, D-74025 Heilbronn, Germany
Telephone: 49 (0)7131 67 2594, Fax number: 49 (0)7131 67 2423
Rev. C2, 07-Mar-01
31 (31)