ETC HVLED805

HVLED805
Off-line LED driver with primary-sensing
Features
■
800 V, avalanche rugged internal power
MOSFET
■
5% accuracy on constant LED output current
with primary control
■
Optocoupler not needed
■
Quasi-resonant (QR) zero voltage switching
(ZVS) operation
■
Internal HV start-up circuit
■
Open or short LED string management
■
Automatic self supply
■
Input voltage feed-forward for mains
independent cc regulation
SO16N
Table 1.
Device summary
Order codes
Package
HVLED805
Packaging
Tube
SO16N
HVLED805TR
Tape and reel
Applications
■
AC-DC led driver applications
■
LED retrofit lamps (i.e. E27, GU10)
Figure 1.
Application diagram
Vin
VCC
HV start-up &
SUPPLY LOGIC
PROT ECTION &
FEEDFORWARD
LOGIC
Vref
DE MAG
LOGIC
3.3V
Vref
...
1V
Rfb
OCP
CONSTANT
VOLTAGE
REGULATION
COMP
LED
DRIVING
LOGIC
CONSTANT
CURRENT
REGULATION
DMG
Rdmg
DRAIN
Rcomp
Vc
ILED
GND
SOURCE
Rsens e
CLED
Cc omp
October 2010
Doc ID 18077 Rev 1
1/29
www.st.com
29
Contents
HVLED805
Contents
1
Description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3
2
Maximum ratings . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
3
Electrical characteristics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5
4
Pin connection . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7
5
Application information . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12
5.1
Power section and gate driver . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13
5.2
High voltage startup generator . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13
5.3
Secondary side demagnetization detection and triggering block . . . . . . . 15
5.4
Constant voltage operation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16
5.5
Constant current operation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 18
5.6
Voltage feedforward block . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20
5.7
Burst-mode operation at no load or very light load . . . . . . . . . . . . . . . . . . 22
5.8
Soft-start and starter block . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 23
5.9
Hiccup mode OCP . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 23
5.10
Layout recommendations . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 24
6
Package mechanical data . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 26
7
Revision history . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 28
2/29
Doc ID 18077 Rev 1
HVLED805
1
Description
Description
The HVLED805 is a high-voltage primary switcher intended for operating directly from the
rectified mains with minimum external parts to provide an efficient, compact and cost
effective solution for LED driving. It combines a high-performance low-voltage PWM
controller chip and an 800V, avalanche-rugged power MOSFET, in the same package.
The PWM is a current-mode controller IC specifically designed for ZVS (zero voltage
switching) fly-back LED drivers, with constant output current (CC) regulation using primarysensing feedback. This eliminates the need for the opto-coupler, the secondary voltage
reference, as well as the current sense on the secondary side, still maintaining a good LED
current accuracy. Moreover it guarantees a safe operation when short circuit of one or more
LEDs occurs.
In addition, the device can also provide a constant output voltage regulation (CV): it makes
the application able to work safely when the LED string opens due to a failure.
Quasi-resonant operation is achieved by means of a transformer demagnetization sensing
input that triggers MOSFET’s turn-on. This input serves also as both output voltage monitor,
to perform CV regulation, and input voltage monitor, to achieve mains-independent CC
regulation (line voltage feed forward).
The maximum switching frequency is top-limited below 166 kHz, so that at medium-light
load a special function automatically lowers the operating frequency still maintaining the
operation as close to ZVS as possible. At very light load, the device enters a controlled
burst-mode operation that, along with the built-in high-voltage start-up circuit and the low
operating current of the device, helps minimize the residual input consumption.
Although an auxiliary winding is required in the transformer to correctly perform CV/CC
regulation, the chip is able to power itself directly from the rectified mains. This is useful
especially during CC regulation, where the fly-back voltage generated by the winding drops.
In addition to these functions that optimize power handling under different operating
conditions, the device offers protection features that considerably increase end-product’s
safety and reliability: auxiliary winding disconnection or brownout detection and shorted
secondary rectifier or transformer’s saturation detection. All of them are auto restart mode.
Doc ID 18077 Rev 1
3/29
Maximum ratings
2
HVLED805
Maximum ratings
Table 2.
Symbol
VDS
ID
Eav
Absolute maximum ratings
Pin
Parameter
1,2, 13-16 Drain-to-source (ground) voltage
1,2, 13-16 Drain current
(1)
1,2, 13-16 Single pulse avalanche energy (Tj = 25°C, ID = 0.7A)
Value
Unit
-1 to 800
V
1
A
50
mJ
Vcc
3
Supply voltage (Icc < 25mA)
Self limiting
V
IDMG
6
Zero current detector current
±2
mA
Vcomp
7
Analog input
-0.3 to 3.6
V
0.9
W
Ptot
Power dissipation @TA = 50°C
TJ
Junction temperature range
-40 to 150
°C
Storage temperature
-55 to 150
°C
Max. value
Unit
Tstg
1. Limited by maximum temperature allowed.
Table 3.
Symbol
4/29
Thermal data
Parameter
RthJP
Thermal resistance, junction-to-pin
10
RthJA
Thermal resistance, junction-to-ambient
110
°C/W
Doc ID 18077 Rev 1
HVLED805
3
Electrical characteristics
Electrical characteristics
TJ = -25 to 125 °C, Vcc=14 V; unless otherwise specified.
Table 4.
Electrical characteristics
Symbol
Parameter
Test condition
Min. Typ. Max. Unit
Power section
V(BR)DSS Drain-source breakdown
IDSS
ID< 100 µA; Tj = 25 °C
800
VDS = 750V; Tj = 125 °C
(See Figure 4 and note)
Off state drain current
80
Id=250 mA; Tj = 25 °C
RDS(on)
Coss
V
11
14
Drain-source ON-state resistance
Id=250 mA; Tj = 125 °C
µA
Ω
28
Effective (energy-related) output capacitance (See Figure 3)
High-voltage start-up generator
VStart
Icharge
Min. drain start voltage
Icharge < 100µA
40
50
60
4
5.5
7
Vcc startup charge current
VDRAIN> VStart; Vcc<VccOn,
Tj = 25 °C
mA
VDRAIN> VStart; Vcc<VccOn
VCCrestart
(1)
Vcc restart voltage
(Vcc falling)
V
+/-10%
9.5
10.5 11.5
V
After protection tripping
5
Supply voltage
Vcc
Operating range
After turn-on
VccOn
Turn-on threshold
(1)
12
VccOff
Turn-off threshold
(1)
Zener voltage
Icc = 20mA
VZ
11.5
23
V
13
14
V
9
10
11
V
23
25
27
V
(See Figure 5)
200
300
µA
Supply current
Iccstart-up Start-up current
Iq
Quiescent current
(See Figure 6)
1
1.4
mA
Icc
Operating supply current @ 50 kHz
(See Figure 7)
1.4
1.7
mA
Fault quiescent current
During hiccup and brownout
(See Figure 8)
250
350
µA
105
140
175
µs
420
500
700
µs
0.1
1
µA
Iq(fault)
Start-up timer
TRESTART Start timer period
TSTART
Restart timer period during burst mode
Demagnetization detector
IDMGb
Input bias current
VDMG = 0.1 to 3V
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Electrical characteristics
Table 4.
HVLED805
Electrical characteristics (continued)
Symbol
Parameter
Test condition
Min. Typ. Max. Unit
VDMGH
Upper clamp voltage
IDMG = 1 mA
3.0
3.3
3.6
V
VDMGL
Lower clamp voltage
IDMG = - 1 mA
-90
-60
-30
mV
VDMGA
Arming voltage
positive-going edge
100
110
120
mV
VDMGT
Triggering voltage
negative-going edge
50
60
70
mV
IDMGON
Min. source current during MOSFET ON-time
-25
-50
-75
µA
TBLANK
Trigger blanking time after MOSFET’s turn-off
VCOMP ≥ 1.3V
6
VCOMP = 0.9V
30
IDMG = 1mA
45
µs
Line feedforward
RFF
Equivalent feedforward resistor
Ω
Transconductance error amplifier
Tj = 25 °C (1)
2.45
2.51 2.57
Tj = -25 to 125°C and
Vcc=12V to 23V (1)
2.4
2.6
1.3
VREF
Voltage reference
gm
Transconductance
ΔICOMP = ±10 µA
VCOMP = 1.65 V
Gv
Voltage gain
Open loop
GB
Gain-bandwidth product
V
2.2
3.2
mS
73
dB
500
kHz
Source current
VDMG = 2.3V, VCOMP = 1.65V
70
100
µA
Sink current
VDMG = 2.7V, VCOMP = 1.65V
400
750
µA
VCOMPH
Upper COMP voltage
VDMG = 2.3V
2.7
V
VCOMPL
Lower COMP voltage
VDMG = 2.7V
0.7
V
1
V
65
mV
ICOMP
VCOMPBM Burst-mode threshold
Hys
Burst-mode hysteresis
Current reference
VILEDx
Maximum value
VCLED
Current reference voltage
VCOMP = VCOMPL (1)
1.5
1.6
1.7
V
0.192
0.2
0.208
V
200
250
300
ns
Current sense
tLEB
td(H-L)
VCSx
VCSdis
Leading-edge blanking
Delay-to-output
300
Max. clamp value
(1) dVcs/dt
Hiccup-mode OCP level
(1)
1. Parameters tracking each other
6/29
Doc ID 18077 Rev 1
= 200 mV/µs
ns
0.7
0.75
0.8
V
0.92
1
1.08
V
HVLED805
4
Pin connection
Pin connection
Figure 2.
Pin connection (top view)
SOURCE
1
16
DRAIN
SOURCE
2
15
DRAIN
VCC
3
14
DRAIN
GND
4
13
DRAIN
ILED
5
12
N.C.
DMG
6
11
N.A.
7
10
8
9
COMP
N.A.
Note:
N.A.
N.A.
The copper area for heat dissipation has to be designed under the drain pins
Doc ID 18077 Rev 1
7/29
Pin connection
Table 5.
N.
1, 2
HVLED805
Pin functions
Name
Function
Power section source and input to the PWM comparator. The current flowing in the MOSFET
is sensed through a resistor connected between the pin and GND. The resulting voltage is
compared with an internal reference (0.75V typ.) to determine MOSFET’s turn-off. The pin is
SOURCE
equipped with 250 ns blanking time after the gate-drive output goes high for improved noise
immunity. If a second comparison level located at 1V is exceeded the IC is stopped and
restarted after Vcc has dropped below 5V.
3
VCC
Supply Voltage of the device. An electrolytic capacitor, connected between this pin and
ground, is initially charged by the internal high-voltage start-up generator; when the device is
running the same generator will keep it charged in case the voltage supplied by the auxiliary
winding is not sufficient. This feature is disabled in case a protection is tripped. Sometimes a
small bypass capacitor (100nF typ.) to GND might be useful to get a clean bias voltage for the
signal part of the IC.
4
GND
Ground. Current return for both the signal part of the IC and the gate drive. All of the ground
connections of the bias components should be tied to a trace going to this pin and kept
separate from any pulsed current return.
ILED
CC regulation loop reference voltage. An external capacitor will be connected between this
pin and GND. An internal circuit develops a voltage on this capacitor that is used as the
reference for the MOSFET’s peak drain current during CC regulation. The voltage is
automatically adjusted to keep the average output current constant.
6
DMG
Transformer’s demagnetization sensing for quasi-resonant operation. Input/output voltage
monitor. A negative-going edge triggers MOSFET’s turn-on. The current sourced by the pin
during MOSFET’s ON-time is monitored to get an image of the input voltage to the converter,
in order to compensate the internal delay of the current sensing circuit and achieve a CC
regulation independent of the mains voltage. If this current does not exceed 50µA, either a
floating pin or an abnormally low input voltage is assumed, the device is stopped and
restarted after Vcc has dropped below 5V. Still, the pin voltage is sampled-and-held right at
the end of transformer’s demagnetization to get an accurate image of the output voltage to be
fed to the inverting input of the internal, transconductance-type, error amplifier, whose noninverting input is referenced to 2.5V. Please note that the maximum IDMG sunk/sourced
current has to not exceed ±2 mA (AMR) in all the Vin range conditions. No capacitor is
allowed between the pin and the auxiliary transformer.
7
COMP
Output of the internal transconductance error amplifier. The compensation network will be
placed between this pin and GND to achieve stability and good dynamic performance of the
voltage control loop.
8-11
N.A
Not available. These pins must be left not connected
12
N.C
Not internally connected. Provision for clearance on the PCB to meet safety requirements.
13 to 16
DRAIN
5
8/29
Drain connection of the internal power section. The internal high-voltage start-up generator
sinks current from this pin as well. Pins connected to the internal metal frame to facilitate heat
dissipation.
Doc ID 18077 Rev 1
HVLED805
Pin connection
Figure 3.
COSS output capacitance variation
500
C OSS (pF)
400
300
200
100
0
0
25
50
75
100
125
150
V DS (V)
Figure 4.
Off state drain and source current test circuit
+
-
1 4V
V CC
2.5V
A
D RA IN
+
CUR RE NT
CON TR OL
-
D MG
COM P
Note:
Idss
IL ED
G ND
V in
75 0V
S OUR CE
The measured IDSS is the sum between the current across the 12 MΩ start-up resistor (62.5
µA typ. @ 750 V) and the effective MOSFET’s off state drain current
Doc ID 18077 Rev 1
9/29
Pin connection
HVLED805
Figure 5.
Start-up current test circuit
+
Icc sta rt-u p
A
-
1 1.8 V
V CC
2.5V
D RA IN
CUR RE NT
CON TR OL
D MG
COM P
Figure 6.
IL ED
G ND
S OUR CE
Quiescent current test circuit
+
Iq _m ea s
A
-
VC C
2 .5V
14 V
DR AIN
C UR REN T
C ONT RO L
DM G
33 k
-
3V
C OMP
ILE D
GN D
SO URC E
+
+
1 0k
+
-
Iq = Iq_meas -
10/29
-
0.8 V
0.11⋅ 3V
-100μ A
3.3kΩ
Doc ID 18077 Rev 1
0 .2V
HVLED805
Pin connection
Figure 7.
Operating supply current test circuit
+
Icc
A
-
1 .5k
2W
15 V
27 k
V CC
DRA IN
2 20 k
2.5 V
+
CU RRE NT
CO NTR OL
-
D MG
10 k
15 0V
10 k
CO MP
IL ED
GND
S OU RCE
10
5 .6
+
2 .8V
+
5 0kHz
-
Note:
-
-5 V
The circuit across the DMG pin is used for switch-on synchronization
Figure 8.
Quiescent current during fault test circuit
+
Iq (fa ult)
A
-
V CC
2.5V
1 4V
D RA IN
CUR RE NT
CON TR OL
D MG
COM P
IL ED
Doc ID 18077 Rev 1
G ND
S OUR CE
11/29
Application information
5
HVLED805
Application information
The HVLED805 is an off-line all-primary sensing switching regulator, specific for offline LED
drivers based on quasi-resonant ZVS (zero voltage switching at switch turn-on) flyback
topology.
Depending on converter’s load condition, the device is able to work in different modes
(Figure 9 for constant voltage operation):
1.
QR mode at heavy load. Quasi-resonant operation lies in synchronizing MOSFET's
turn-on to the transformer’s demagnetization by detecting the resulting negative-going
edge of the voltage across any winding of the transformer. Then the system works
close to the boundary between discontinuous (DCM) and continuous conduction
(CCM) of the transformer. As a result, the switching frequency will be different for
different line/load conditions (see the hyperbolic-like portion of the curves in Figure 9).
Minimum turn-on losses, low EMI emission and safe behavior in short circuit are the
main benefits of this kind of operation. The resulting constant current mode fixes the
average current also in case of a short-circuit failure of one or more LEDs.
2.
Valley-skipping mode at medium/ light load. Depending on voltage on COMP pin, the
device defines the maximum operating frequency of the converter. As the load is
reduced MOSFET’s turn-on will not any more occur on the first valley but on the second
one, the third one and so on. In this way the switching frequency will no longer increase
(piecewise linear portion in Figure 9).
3.
Burst-mode with no or very light load. When the load is extremely light or disconnected,
the converter will enter a controlled on/off operation with constant peak current.
Decreasing the load will then result in frequency reduction, which can go down even to
few hundred hertz, thus minimizing all frequency-related losses and making it easier to
comply with energy saving regulations or recommendations. Being the peak current
very low, no issue of audible noise arises. Thanks to this feature, the application is able
to safely manage the open circuit caused by an LED failure.
Figure 9.
Multi-mode operation of HVLED805 (Constant voltage operation)
f osc
Input voltage
f sw
Valley-skipping
mode
Burst-mode
Quasi-resonant mode
0
Pin
12/29
Doc ID 18077 Rev 1
Pinmax
HVLED805
5.1
Application information
Power section and gate driver
The power section guarantees safe avalanche operation within the specified energy rating
as well as high dv/dt capability. The Power MOSFET has a V(BR)DSS of 800V min. and a
typical RDSon of 11 Ω.
The gate driver of the power MOSFET is designed to supply a controlled gate current during
both turn-on and turn-off in order to minimize common mode EMI. Under UVLO conditions
an internal pull-down circuit holds the gate low in order to ensure that the power MOSFET
cannot be turned on accidentally.
5.2
High voltage startup generator
Figure 10 shows the internal schematic of the high-voltage start-up generator (HV
generator). It includes an 800 V-rated N-channel MOSFET, whose gate is biased through
the series of a 12 MΩ resistor and a 14 V zener diode, with a controlled, temperaturecompensated current generator connected to its source. The HV generator input is in
common with the DRAIN pin, while its output is the supply pin of the device (Vcc). A mains
“UVLO” circuit (separated from the UVLO of the device that sense Vcc) keeps the HV
generator off if the drain voltage is below VSTART (50 V typical value).
Figure 10. High-voltage start-up generator: internal schematic
DRAIN
14 V
Vc c _O K
12 M
Ma i ns UV LO
H V_ EN
IHV
Vcc
CO NTRO L
Ic ha rge
S OURCE
With reference to the timing diagram of Figure 11, when power is applied to the circuit and
the voltage on the input bulk capacitor is high enough, the HV generator is sufficiently
biased to start operating, thus it will draw about 5.5 mA (typical) from the bulk capacitor.
Doc ID 18077 Rev 1
13/29
Application information
HVLED805
Most of this current will charge the bypass capacitor connected between the Vcc pin and
ground and make its voltage rise linearly.
As the Vcc voltage reaches the start-up threshold (13 V typ.) the chip starts operating, the
internal power MOSFET is enabled to switch and the HV generator is cut off by the Vcc_OK
signal asserted high. The IC is powered by the energy stored in the Vcc capacitor.
The chip is able to power itself directly from the rectified mains: when the voltage on the VCC
pin falls below Vccrestart (10.5V typ.), during each MOSFET’s off-time the HV current
generator is turned on and charges the supply capacitor until it reaches the VCCOn
threshold.
In this way, the self-supply circuit develops a voltage high enough to sustain the operation of
the device. This feature is useful especially during CC regulation, when the flyback voltage
generated by the auxiliary winding alone may not be able to keep Vcc above VCCrestart.
At converter power-down the system will lose regulation as soon as the input voltage falls
below VStart. This prevents converter’s restart attempts and ensures monotonic output
voltage decay at system power-down.
Figure 11. Timing diagram: normal power-up and power-down sequences
Vin
VStart
Vcc
t
VccON
Vccrestart
t
DRAIN
Icharge
t
5.5 mA
Power-on
14/29
Normal operation
CV mode
Doc ID 18077 Rev 1
Normal operation
CC mode
Power-off
t
HVLED805
Secondary side demagnetization detection and triggering
block
The demagnetization detection (DMG) and Triggering blocks switch on the power MOSFET
if a negative-going edge falling below 50 mV is applied to the DMG pin. To do so, the
triggering block must be previously armed by a positive-going edge exceeding 100 mV.
This feature is used to detect transformer demagnetization for QR operation, where the
signal for the DMG input is obtained from the transformer’s auxiliary winding used also to
supply the IC.
Figure 12. DMG block, triggering block
R dmg
DMG
D MG
CLAMP
BLAN KIN G
TIME
ST AR TER
Rfb
Aux
T UR N-ON
LOGIC
110mV
60mV
S
+
5.3
Application information
Q
From CC/C V Block
LEB
To Driver
R
From OCP
The triggering block is blanked after MOSFET’s turn-off to prevent any negative-going edge
that follows leakage inductance demagnetization from triggering the DMG circuit
erroneously.
This blanking time is dependent on the voltage on COMP pin: it is TBLANK = 30 µs for VCOMP
= 0.9 V, and decreases almost linearly down to TBLANK = 6 µs for VCOMP = 1.3 V
The voltage on the pin is both top and bottom limited by a double clamp, as illustrated in the
internal diagram of the DMG block of Figure 12. The upper clamp is typically located at 3.3
V, while the lower clamp is located at -60mV. The interface between the pin and the auxiliary
winding will be a resistor divider. Its resistance ratio as well as the individual resistance
values will be properly chosen (see “Section 5.5: Constant current operation on page 18”
and “Section 5.6: Voltage feedforward block on page 20”.
Please note that the maximum IDMG sunk/sourced current has to not exceed ±2 mA (AMR)
in all the Vin range conditions. No capacitor is allowed between DMG pin and the auxiliary
transformer.
The switching frequency is top-limited below 166 kHz, as the converter’s operating
frequency tends to increase excessively at light load and high input voltage.
A Starter block is also used to start-up the system, that is, to turn on the MOSFET during
converter power-up, when no or a too small signal is available on the DMG pin.
The starter frequency is 2 kHz if COMP pin is below burst mode threshold, i.e. 1 V, while it
becomes 8 kHz if this voltage exceed this value.
Doc ID 18077 Rev 1
15/29
Application information
HVLED805
After the first few cycles initiated by the starter, as the voltage developed across the auxiliary
winding becomes large enough to arm the DMG circuit, MOSFET’s turn-on will start to be
locked to transformer demagnetization, hence setting up QR operation.
The starter is activated also when the IC is in CC regulation and the output voltage is not
high enough to allow the DMG triggering.
If the demagnetization completes – hence a negative-going edge appears on the DMG pin –
after a time exceeding time TBLANK from the previous turn-on, the MOSFET will be turned
on again, with some delay to ensure minimum voltage at turn-on. If, instead, the negativegoing edge appears before TBLANK has elapsed, it will be ignored and only the first negativegoing edge after TBLANK will turn-on the MOSFET. In this way one or more drain ringing
cycles will be skipped (“valley-skipping mode”, Figure 13) and the switching frequency will
be prevented from exceeding 1/TBLANK.
Figure 13. Drain ringing cycle skipping as the load is progressively reduced
VDS
VDS
TON
TFW
TV
Tosc
VDS
t
t
Tosc
Pin = Pin'
(limit condition)
t
Tosc
Pin = Pin'' < Pin'
Pin = Pin''' < Pin''
Note:
That when the system operates in valley skipping-mode, uneven switching cycles may be
observed under some line/load conditions, due to the fact that the OFF-time of the MOSFET
is allowed to change with discrete steps of one ringing cycle, while the OFF-time needed for
cycle-by-cycle energy balance may fall in between. Thus one or more longer switching
cycles will be compensated by one or more shorter cycles and vice versa. However, this
mechanism is absolutely normal and there is no appreciable effect on the performance of
the converter or on its output voltage.
5.4
Constant voltage operation
The IC is specifically designed to work in primary regulation and the output voltage is
sensed through a voltage partition of the auxiliary winding, just before the auxiliary rectifier
diode.
Figure 14 shows the internal schematic of the constant voltage mode and the external
connections.
16/29
Doc ID 18077 Rev 1
HVLED805
Application information
Figure 14. Voltage control principle: internal schematic
DMG
S/H
-
Rdmg
EA
+
Rfb
+
Aux
To PWM Logic
CV
2.5V
DEMAG
LOGIC
F rom Rsense
COMP
R
C
Due to the parasitic wires resistance, the auxiliary voltage is representative of the output just
when the secondary current becomes zero. For this purpose, the signal on DMG pin is
sampled-and-held at the end of transformer’s demagnetization to get an accurate image of
the output voltage and it is compared with the error amplifier internal reference.
During the MOSFET’s OFF-time the leakage inductance resonates with the drain
capacitance and a damped oscillation is superimposed on the reflected voltage. The S/H
logic is able to discriminate such oscillations from the real transformer’s demagnetization.
When the DMG logic detects the transformer’s demagnetization, the sampling process
stops, the information is frozen and compared with the error amplifier internal reference.
The internal error amplifier is a transconductance type and delivers an output current
proportional to the voltage unbalance of the two outputs: the output generates the control
voltage that is compared with the voltage across the sense resistor, thus modulating the
cycle-by-cycle peak drain current.
The COMP pin is used for the frequency compensation: usually, an RC network, which
stabilizes the overall voltage control loop, is connected between this pin and ground.
The output voltage can be defined according the formula:
Equation 1
RFB =
VREF
⋅ RDMG
n AUX
⋅ VOUT − VREF
nSEC
Where nSEC and nAUX are the secondary and auxiliary turn’s number respectively.
The RDMG value can be defined depending on the application parameters (see “Section 5.6:
Voltage feedforward block on page 20” section).
Doc ID 18077 Rev 1
17/29
Application information
5.5
HVLED805
Constant current operation
Figure 15 presents the principle used for controlling the average output current of the
flyback converter.
The output voltage of the auxiliary winding is used by the demagnetization block to generate
the control signal for the mosfet switch Q1. A resistor R in series with it absorbs a current
VC/R, where VC is the voltage developed across the capacitor C.
The flip-flop’s output is high as long as the transformer delivers current on secondary side.
This is shown in Figure 16.
The capacitor C has to be chosen so that its voltage VC can be considered as a constant.
Since it is charged and discharged by currents in the range of some ten µA (ICLED is
typically 20 µA) at the switching frequency rate, a capacitance value in the range 4.7-10 nF
is suited for switching frequencies in the ten kHz.
The average output current can be expressed as:
Equation 2
IOUT =
IS ⎛ TONSEC ⎞
⋅⎜
⎟
2 ⎝ T ⎠
Where IS is the secondary peak current, TONSEC is the conduction time of the secondary
side and T is the switching period.
Taking into account the transformer ratio n between primary and secondary side, IS can also
be expressed is a function of the primary peak current IP:
Equation 3
IS = n ⋅ IP
As in steady state the average current IC:
Equation 4
V ⎞
⎛
ICLED ⋅ (T − TONSEC ) + ⎜ ICLED − C ⎟ ⋅ TONSEC = 0
R ⎠
⎝
Which can be solved for VC:
Equation 5
VC = VCLED ⋅
T
TONSEC
Where VCLED=R • ILED and is internally defined.
As VC is fed to the CC comparator, the primary peak current can be expressed as:
18/29
Doc ID 18077 Rev 1
HVLED805
Application information
Equation 6
IP =
VC
R SENSE
Combining (2), (3) (5) and (6):
Equation 7
IOUT =
n VCLED
⋅
2 R SENSE
This formula shows that the average output current does not depend anymore on the input
or the output voltage, neither on transformer inductance values. The external parameters
defining the output current are the transformer ratio n and the sense resistor RSENSE.
Figure 15. Current control principle
.
Iref
To PWM Logic
CC
+
R
F rom R sense
R dmg
DMG
S
D EMAG
LOGIC
Q1
Q
R
Rfb
Aux
ILED
CLED
Doc ID 18077 Rev 1
19/29
Application information
HVLED805
Figure 16. Constant current operation: Switching cycle waveforms
T
IP
t
Is
t
Q
t
IC
ICLED
V
ICLED =− C
R
5.6
t
Voltage feedforward block
The current control structure uses the voltage VC to define the output current, according to
(7). Actually, the CC comparator will be affected by an internal propagation delay Td, which
will switch off the MOSFET with a peak current than higher the foreseen value.
This current overshoot will be equal to:
Equation 8
Δ IP =
VIN ⋅ Td
LP
Will introduce an error on the calculated CC setpoint, depending on the input voltage.
The HVLED805 implements a Line Feedforward function, which solves the issue by
introducing an input voltage dependent offset on the current sense signal, in order to adjust
the cycle-by-cycle current limitation.
The internal schematic is shown in Figure 17.
20/29
Doc ID 18077 Rev 1
HVLED805
Application information
Figure 17. Feedforward compensation: internal schematic
DRAIN
DMG
F eedforward
Logic
.
Rfb
Aux
CC
Block
IF F
-
Rdmg
CC
PWM
LOGIC
+
RFF
SO URCE
Rsense
During MOSFET’s ON-time the current sourced from DMG pin is mirrored inside the
“Feedforward Logic” block in order to provide a feedforward current, IFF.
Such “feedforward current” is proportional to the input voltage according to the formula:
Equation 9
IFF =
VIN
m ⋅ R dmg
Where m is the primary-to-auxiliary turns ratio.
According to the schematic, the voltage on the non-inverting comparator will be:
Equation 10
V(-) = R SENSE ⋅ ID +IFF ⋅ (RFF +RSENSE )
The offset introduced by feedforward compensation will be:
Equation 11
VOFFSET =
VIN
⋅ (RFF + RSENSE )
m ⋅ R dmg
As RFF>>RSENSE, the previous one can be simplified as:
Equation 12
VOFFSET =
VIN ⋅ RFF
m ⋅ R dmg
Doc ID 18077 Rev 1
21/29
Application information
HVLED805
This offset is proportional to VIN and is used to compensate the current overshoot,
according to the formula:
Equation 13
VIN ⋅ Td
V ⋅R
⋅ RSENSE = IN FF
Lp
m ⋅ R dmg
Finally, the Rdmg resistor can be calculated as follows:
Equation 14
R dmg =
L p ⋅ RFF
NAUX
⋅
NPRI Td ⋅ R SENSE
In this case the peak drain current does not depend on input voltage anymore.
One more consideration concerns the Rdmg value: during MOSFET’s ON-time, the current
sourced by the DMG pin, IDMG, is compared with an internal reference current IDMGON (-50
µA typical).
If IDMG < IDMGON, the brownout function is activated and the IC is shut-down.
This feature is especially important when the auxiliary winding is accidentally disconnected
and considerably increases the end-product’s safety and reliability.
5.7
Burst-mode operation at no load or very light load
When the voltage at the COMP pin falls 65 mV below a threshold fixed internally at a value,
VCOMPBM, the IC is disabled with the MOSFET kept in OFF state and its consumption
reduced at a lower value to minimize Vcc capacitor discharge.
In this condition the converter operates in burst-mode (one pulse train every TSTART=500
µs), with minimum energy transfer.
As a result of the energy delivery stop, the output voltage decreases: after 500 µs the
controller switches-on the MOSFET again and the sampled voltage on the DMG pin is
compared with the internal reference. If the voltage on the EA output, as a result of the
comparison, exceeds the VCOMPL threshold, the device restarts switching, otherwise it stays
OFF for another 500 µs period.
In this way the converter will work in burst-mode with a nearly constant peak current defined
by the internal disable level. A load decrease will then cause a frequency reduction, which
can go down even to few hundred hertz, thus minimizing all frequency-related losses and
making it easier to comply with energy saving regulations. This kind of operation, shown in
the timing diagrams of Figure 19 along with the others previously described, is noise-free
since the peak current is low
22/29
Doc ID 18077 Rev 1
HVLED805
Application information
Figure 18. Load-dependent operating modes: timing diagrams
COMP
65 mV
hyster.
VCOMPL
IDS
Normal-mode
5.8
TSTART
TSTART
TSTART
Burst-mode
TSTART
Normal-mode
Soft-start and starter block
The soft start feature is automatically implemented by the constant current block, as the
primary peak current will be limited from the voltage on the CLED capacitor.
During start-up, as the output voltage is zero, the IC will start in CC mode with no high peak
current operations. In this way the voltage on the output capacitor will increase slowly and
the soft-start feature will be ensured.
Actually the CLED value is not important to define the soft-start time, as its duration depends
on others circuit parameters, like transformer ratio, sense resistor, output capacitors and
load. The user will define the best appropriate value by experiments.
5.9
Hiccup mode OCP
The device is also protected against short circuit of the secondary rectifier, short circuit on
the secondary winding or a hard-saturated flyback transformer. A comparator monitors
continuously the voltage on the RSENSE and activates a protection circuitry if this voltage
exceeds 1 V.
To distinguish an actual malfunction from a disturbance (e.g. induced during ESD tests), the
first time the comparator is tripped the protection circuit enters a “warning state”. If in the
subsequent switching cycle the comparator is not tripped, a temporary disturbance is
assumed and the protection logic will be reset in its idle state; if the comparator will be
tripped again a real malfunction is assumed and the device will be stopped.
This condition is latched as long as the device is supplied. While it is disabled, however, no
energy is coming from the self-supply circuit; hence the voltage on the VCC capacitor will
decay and cross the UVLO threshold after some time, which clears the latch. The internal
start-up generator is still off, then the VCC voltage still needs to go below its restart voltage
Doc ID 18077 Rev 1
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Application information
HVLED805
before the VCC capacitor is charged again and the device restarted. Ultimately, this will
result in a low-frequency intermittent operation (Hiccup-mode operation), with very low
stress on the power circuit. This special condition is illustrated in the timing diagram of
Figure 18.
Figure 19. Hiccup-mode OCP: timing diagram
Secondary diode is shorted here
VCC
VccON
VccOFF
Vccrest
VSOURCE
Vcsdis
t
1V
Two switching cycles
VDS
t
t
5.10
Layout recommendations
A proper printed circuit board layout is essential for correct operation of any switch-mode
converter and this is true for the HVLED805 as well. Careful component placing, correct
traces routing, appropriate traces widths and compliance with isolation distances are the
major issues. In particular:
●
The compensation network should be connected as close as possible to the COMP
pin, maintaining the trace for the GND as short as possible
●
Signal ground should be routed separately from power ground, as well from the sense
resistor trace.
24/29
Doc ID 18077 Rev 1
HVLED805
Application information
Figure 20. Suggested routing for converter
ACIN
ACIN
DRAIN
VDD
DMG
COMP
...
HVLED805
GND
ILED
LED
SOURCE
Doc ID 18077 Rev 1
25/29
Package mechanical data
6
HVLED805
Package mechanical data
In order to meet environmental requirements, ST offers these devices in different grades of
ECOPACK® packages, depending on their level of environmental compliance. ECOPACK®
specifications, grade definitions and product status are available at: www.st.com.
ECOPACK® is an ST trademark.
Table 6.
SO16N mechanical data
mm
inch
Dim.
Min
Typ
A
a1
Min
Typ
1.75
0.1
Max
0.069
0.25
a2
0.004
0.009
1.6
0.063
b
0.35
0.46
0.014
0.018
b1
0.19
0.25
0.007
0.010
C
0.5
c1
0.020
45°
(typ.)
D (1)
9.8
10
0.386
0.394
E
5.8
6.2
0.228
0.244
e
1.27
0.050
e3
8.89
0.350
F(1)
3.8
4.0
0.150
0.157
G
4.60
5.30
0.181
0.208
L
0.4
1.27
0.150
0.050
M
S
26/29
Max
0.62
0.024
8 °(max.)
Doc ID 18077 Rev 1
HVLED805
Package mechanical data
Figure 21. Package dimensions
Doc ID 18077 Rev 1
27/29
Revision history
7
HVLED805
Revision history
Table 7.
28/29
Document revision history
Date
Revision
14-Oct-2010
1
Changes
Initial release
Doc ID 18077 Rev 1
HVLED805
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Doc ID 18077 Rev 1
29/29
Contents
AN3360
Contents
1
Test board design and evaluation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
2
Transformer specification . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8
3
Efficiency measurements . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 9
4
Typical board waveforms . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10
5
Conclusion . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13
6
References . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14
7
Revision history . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15
2/16
Doc ID 018586 Rev 2
AN3360
List of figures
List of figures
Figure 1.
Figure 2.
Figure 3.
Figure 4.
Figure 5.
Figure 6.
Figure 7.
Figure 8.
Figure 9.
Figure 10.
Figure 11.
Figure 12.
Figure 13.
Figure 14.
Figure 15.
STEVAL-ILL037V1 demonstration board image. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
For E26/E27 application . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
Electrical schematic . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5
PCB top side and through hole components . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7
PCB bottom side and SMD components . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7
EEE13-11 vertical type for under 10 W . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8
Output characteristics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 9
Normal operation at full load - at 115 VAC . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10
Normal operation at full load - at 230 VAC . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10
Normal operation at no load - at 115 VAC . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11
Normal operation at no load - at 230 VAC . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11
Short-circuit at 115 VAC . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11
Short-circuit at 230 VAC . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11
Startup at full load at 115 VAC . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12
Startup at full load at 230 VAC . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12
Doc ID 018586 Rev 2
3/16
Test board design and evaluation
1
AN3360
Test board design and evaluation
As a reference design, a 3.2 W LED power supply based on HVLED805 is presented.
●
Table 1 summarizes the electrical specifications of the application
●
Table 2 provides the bill of material
●
Table 4 lists transformer specifications
The electrical schematic is shown in Figure 3 and the PCB layout in Figure 4. and 5.
Table 1.
Figure 2.
4/16
STEVAL-ILL037V1 demonstration board: electrical specifications
Parameter
Value
Input voltage range (VIN)
90 - 265 VAC
Mains frequency (fL)
50 - 60 Hz
Output power consumption
3.2 W
Output voltage
16 VDC (3~5 LEDs)
Output current
200 mA
Target average efficiency
>70%
For E26/E27 application
Doc ID 018586 Rev 2
Doc ID 018586 Rev 2
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Figure 3.
.
,
AN3360
Test board design and evaluation
Electrical schematic
0
!-V
5/16
Test board design and evaluation
Table 2.
6/16
AN3360
STEVAL-ILL037V1 demonstration board bill of material
Reference
Part
BD1
BR81D
C1
1000 µF_DIP
C2
1 nF_1206
C3,C4
4.7 µF_DIP
C5
2.2 nF_DIP
C6
22 µF_1206
X5R
C7
6.8 nF
X7R
C8
470 nF
X7R
C9
22 nF
X7R
C10
470 nF
X7R
D1
STPS1H100U
STMicroelectronics
D2
STTH1L06_SMB
STMicroelectronics
D3
1N4148
CHENMKO
F1
1A_DIP
L1
22 µH_DIP
R1
110 kΩ_1206
5%
R2
150 kΩ_1206
5%
R4
5.6 Ω_1206
1%
R5
3.9 Ω_1206
1%
R6
3.9 kΩ
1%
R7
12 kΩ
1%
R8
NC
R9
33 kΩ
1%
R10
10 Ω_1206
5%
T1
QEE13
Yu-Jing
U1
HVLED805
STMicroelectronics
Doc ID 018586 Rev 2
Note
AN3360
Figure 4.
Test board design and evaluation
PCB top side and through hole components
MM
MM
MM
!-V
Figure 5.
PCB bottom side and SMD components
Doc ID 018586 Rev 2
7/16
Transformer specification
AN3360
2
Transformer specification
Figure 6.
EEE13-11 vertical type for under 10 W
Table 3.
Transformer specification
Core spec-EEE13
Ae
36.7 mm2
Le
27 mm
AW
2.5 mm*4.8 mm
Wiring spec. for flyback 16 V output
Note:
Start
Finish
Wire
Winding
Turns
Inductance
LK inductance
L1
3
1
0.2 Φ*1C
Primary
72
1.9 mH±10%
31 µH ref.
L2
9
7
0.35 Φ*1C
Secondary
15
96 µH±10%
L3
4
5
0.2 Φ*1C
AUX
20
85 µH ref.
Class B insulation system: SB14.2
●
●
8/16
No.
With standing voltage:
–
1.0 kV/1 sec/AC/5 mA, primary to secondary
–
0.5 kV/1 sec/AC/3 mA, primary to core
–
1.0 kV/1 sec/AC/3 mA, secondary to core
Manufacturer:
–
Yu-Jing Technology Co., LTD www.yujingtech.com.tw
–
Inductor P/N: 11999-310V600110 (EEE13-11V)
Doc ID 018586 Rev 2
AN3360
3
Efficiency measurements
Efficiency measurements
The efficiency of the converter has been measured in different load and line voltage
conditions.
The efficiency measurements have been done at 12 to 16 VDC of the rated output power, at
both 115 VAC and 230 VAC.
Table 4 and 5 show the results.
Table 4.
Efficiency at 115 VAC
VAC
Pin (W)
Vout (V)
Iout (mA)
Eff (%)
115
2.972
12.016
196.00
79.24
3.190
13.008
196.00
79.92
3.420
14.016
196.00
80.33
3.644
15.008
195.00
80.31
3.877
16.016
195.00
80.56
Average eff. (%)
Table 5.
80.07
Efficiency at 230 VAC
VAC
Pin (W)
Vout (V)
Iout (mA)
Eff (%)
230
3.238
12.016
195.00
72.36
3.500
13.008
200.00
74.33
3.792
14.016
204.00
75.40
4.050
15.008
204.00
75.60
4.262
16.016
204.00
76.66
Average eff. (%)
Figure 7.
74.87
Output characteristics
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Doc ID 018586 Rev 2
ϭϱ
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!-V
9/16
Typical board waveforms
4
AN3360
Typical board waveforms
Drain voltage and current waveforms were reported for the two nominal input voltages and
for the minimum and the maximum voltage of the converter input operating range. Figure 8
and 9 show the drain current and the drain voltage waveforms at the nominal input voltages
and full load.
At low load OC enters into burst mode, reducing the switching frequency down to a
minimum fixed value; Figure 10 and 11 show the typical waveforms during no load
conditions at both 115 VAC and 230 VAC circuits at nominal input voltage.
The CC mode technique eliminates the need for overload protection; in fact, the maximum
output power is achieved on the corner point between CV mode and CC mode and
coincides with the full load condition. Figure 12 and 13 show the typical waveforms during
short-circuit at nominal input voltage.
Figure 14 and 15 show the startup in full load conditions and nominal input voltage; the
maximum drain-source voltage is well below the BVDSS of the IC.
Figure 8.
10/16
Normal operation at full load - at
115 VAC
Figure 9.
Doc ID 018586 Rev 2
Normal operation at full load - at
230 VAC
AN3360
Typical board waveforms
Figure 10. Normal operation at no load at 115 VAC
Figure 11. Normal operation at no load at 230 VAC
Figure 12. Short-circuit at 115 VAC
Figure 13. Short-circuit at 230 VAC
Doc ID 018586 Rev 2
11/16
Typical board waveforms
AN3360
Figure 14. Startup at full load at 115 VAC
12/16
Figure 15. Startup at full load at 230 VAC
Doc ID 018586 Rev 2
AN3360
5
Conclusion
Conclusion
The LED power supply demonstration board using the HVLED805 device was presented
and the results show that good performances can be obtained using this new device.
Auxiliary winding is required in the transformer to correctly perform CV/CC regulation, and
the chip is able to power itself directly from the rectified mains. This is particularly useful
during CC regulation, where the flyback voltage generated by the winding drops.
The HVLED805 is able to meet the most restrictive worldwide standards regarding
efficiency. The embedded onboard protections and the 800 V power section considerably
increase the end-product safety and reliability.
Doc ID 018586 Rev 2
13/16
References
6
14/16
AN3360
References
1.
HVLED805 datasheet
2.
AN3093 application note
Doc ID 018586 Rev 2
AN3360
7
Revision history
Revision history
Table 6.
Document revision history
Date
Revision
Changes
30-Mar-2011
1
Initial release.
21-Jul-2011
2
– Updated Figure 3.
– Updated component D1 in Table 2.
Doc ID 018586 Rev 2
15/16
AN3360
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16/16
Doc ID 018586 Rev 2
HVLED805 offline LED driver
Lighting the future
Key requirements in LED driving
+ Accuracy
Dedicated LED drivers operating from the AC mains to ensure
highly accurate constant output current, to provide a high level
of light quality and avoid flickering
+ Efficiency
Advanced high-voltage technologies and architectures for high
efficiency and reduced EMI to comply with energy saving
regulations and safety standards
+ Robustness
Compactness
Reduced component count to implement very compact
compact, ultra-thin
ultra thin
applications, but also to eliminate weak, unreliable parts that
contribute to reduced lifetime of the application
The HVLED805 meets the challenge
ƒ
ƒ
The HVLED805 operates directly form the mains with minimum external parts
ƒ No secondary sensing
ƒ No opto-coupler
Provides an efficient, compact and cost-effective solution to drive LEDs
Typical offline LED application solution
High-voltage converter for LED driving
Key features
HVLED805:
PWM current
current-mode
mode
controller designed for
quasi-resonant flyback
LED driver with constant
output current regulation,
using primary-sensing
operation
ƒ
ƒ
ƒ
ƒ
ƒ
ƒ
ƒ
ƒ
Internal 800 V avalanche rugged MOSFET
On-board high voltage start-up
Pi
Primary
sensing
i regulation
l i
Quasi-resonant operation mode
5% accuracy on constant
t t output
t t currentt
Open and short LED string management
Automatic self supply
Input voltage feed-forward for mains independent CC
regulation
Applications
Typical application
M i applications
Main
li ti
Up to 8 W in 230 V mains range:
ƒ
ƒ
Up to 8 LEDs
350 mA each
HVLED805
LED retrofit lamps
Low-power AC-DC LED drivers
HVLED805: ready for latest LED lamps
9 Accuracy
9 Efficiency
9 Robustness
9 Compactness
9
Primary side regulation allows 5% LED constant current accuracy
9
Quasi–resonant operation reduces conduction and switching losses and,
working at variable frequency, reduces the EMI level
9
800 V MOSFET optimizes valley switching
switching, so reducing the power
dissipation
9
HV start-up allows efficient and reliable turn-on phase and reduces
external components
9
800 V avalanche-rugged internal power MOSFET gives:
9 High reliability
9 Reduced
R d
d snubber
bb network
t
k
All primary sensing control allows:
9Elimination of secondary voltage reference
9Elimination of the opto-coupler
9Safe operation against open or short LED strings
9
Making your designs easier
Package
Available in a surface-mounting
surface mounting package SO16N
Evaluation boards
EVALHVLED805: up to 4.2 W, 350 mA, ultra-compact LED driver
Support
Further information and full design support available at:
www st com
www.st.com
Energy-efficient solutions for offline LED
lighting and general illumination
Offline LED lighting/general illumination
System
know-how
ST’s position
 #1 in lighting segment*
 #2 in power management**
LED driver
ICs
MCUs
LED
applications
ST’s expertise
Discrete
MOSFETs
Diodes
Smart
power ICs
*STMicroelectronics, Datapoint and Darnell – 2008
**iSupply - 2010
 System solutions
 Technology integration and
innovation
 Excellent technical support
Contents
 Energy-efficient solutions for offline LED lighting
 Offline LED driver solutions
 Features/benefits
 System evaluation boards and tools
 General illumination applications






Residential lighting
Commercial lighting
Architectural and decorative lighting
Street lighting and public illumination
Emergency lighting
Machine vision
Driving LEDs using AC-DC solutions
Isolated and non-isolated topologies with high efficiencies and power factor
3 to 10 W
10 to 50 W
50 W and above
Single package
approach, primary-side
or secondary-side
CC regulation
 Incandescent
replacement
 Decorative bulbs
Single-stage AC-DC,
single or multiple LED strings
Triac dimmable or
post regulation w/dimming
 Incandescent and
fluorescent replacement
 Architectural and
decorative lighting
Single-stage or
double-stage AC-DC plus
analog or digital
CC controllers
 Streetlights
 Parking garages
 Warehouse high bays
Non-isolated applications: up to 10W
~AC
PWM
PWM
Controller
Controller
Current
Control
STTHxx
Applications
Monolithic Converter
AC-DC
solutions for
LED driving
VIPer family
Buck
Offline single-stage buck solution
Off-line Single Stage Buck Solution
STTHxx
 Bulb replacement
 Lamp retrofit
VIPer family
Buck-boost
~AC
Monolithic Converter
Flyback
PWM
PWM
Controller
Controller
Rsense
Single Stage Buck-Boost Solution
Offline Off-line
single-stage
buck-boost solution
STTHxx
Device
Part number/family
Monolithic converter
VIPer family
(Integrated controller +
MOSFET)
Ultrafast diodes
STTHxx
Benefits
 800 V avalanche rugged MOSFET (VIPerPlus)
 Jittering for low EMI (VIPerPlus)
 Advanced OVP and OCP
 Wide selection of electrical parameters and packages
Non-isolated eval boards: 3-10W
VIPer family: High-voltage converters in non-isolated topologies
Key features
Main benefits
 Single package
approach:
 integrated
 robust
 sophisticated
 Miniaturized
form factors
 Easy design
 High power factor > 0.7
 Compliant to energy
saving regulations
 No high-voltage
electrolytic cap usage
 High reliability
(extended MTBF)
3-watt LED driver STEVAL-ILL026V1
Evaluation board
Application note
Description
STEVAL-ILL026V1
AN2961
3 W non-isolated offline LED driver
solution based on VIPER22AS
STEVAL-ILL017V1
AN2811
3.5 W non-isolated flyback constantcurrent source based on VIPER17
Non-isolated applications: up to 20W
Offline singlestage buckboost solution
STTHxx
Applications
L6562A
AC-DC solutions
for LED Driving
SuperMESH 3 or
MDmesh II
Inverse buck
Offline singlestage
inverse buck
solution
 Neon and bulb replacement
 Lamp retrofit
STTHxx
SuperMESH 3 or
MDmesh II
Device
Part number/family
PWM controller
L6562A
Buck and buckboost MOSFETs
Ultrafast diodes
Buck-boost
L6562A
Benefits
 High power factor
SuperMESH 3*
 High safety margin and ruggedness
 High immunity to dV/dt, low conduction and switching losses
MDmesh II*
(super junction)
 Up to 800 V with the best RDS(on) in the market
 Best-in-class in dynamic dV/dt
 Low input capacitance and gate charge, low gate input
resistance
STTHxx
 Wide selection of electrical parameters and packages
* See MOSFET selection guide in presentation, online, and in energy-efficient solutions for LED lighting brochure
L6562A PWM controller eval boards
Key features
 Buck-boost topology
 Simple
 Low cost
 Transition mode
operation
 Lower switching losses
 Spread of EMI spectrum
 High power factor > 0.8
 Compliant to energy saving
regulations, suitable for
residential lighting
 Open-load protection
 Short-circuit protection
 Robust
Buck-boost STEVAL-ILL027V2
Evaluation board
Application
note
Description
STEVAL-ILL027V2
AN3111
18 W single-stage
offline LED driver
AN3256
Low-cost LED
driver for an A19
lamp
STEVAL-ILL034V1
HPF inverse buck STEVAL-ILL034V1
Main benefits
Isolated applications: Up to 10W
STPSxx
HVLED805
Flyback solution
with primary-side
regulation
STPSxx
Applications
AC-DC solutions
for LED driving
 Bulb replacement
 Lamp retrofit
Flyback
SEA0x
VIPerPlus
Flyback solution
with secondaryside regulation
Device
Part number/family
Benefits
HVLED805
(controller + MOSFET)
 CC/CV primary regulation
 QR zero voltage switching operation
 800 V avalanche rugged MOSFET
VIPer Plus
(controller + MOSFET)
 800 V avalanche rugged MOSFET, high power factor
 Jittering for low EMI
 Advanced OVP and OCP
Primary IC
Schottky diodes
STPSxx
 Wide product range in Vf/Ir trade off, avalanche ruggedness
CV/CC control
SEA0x
 Very low current consumption, wide input voltage range
HVLED805 with primary-side regulation
V and I control implemented
inside HVLED805
HVLED805
Key features
Opto No external
Coupler optocoupler needed
Main benefits
 Single package approach
 integrated
 robust
 sophisticated
 Miniaturized form factors
 Easy design
 CC/CV primary regulation
 Reduced costs and system complexity
 Very small form factor to fit in LED retrofit applications
 No optocoupler
 High reliability (extended MTBF)
 Zero voltage switching operation and high
voltage start-up
 High efficiency up to 85%
HVLED805 eval board solutions
EVALHVLED805
Evaluation board
EVALHVLED805
STEVALILL037V1
Application
note
Data brief
AN3360
4.2 W solution for 350 mA LED type
STEVAL-ILL037V1
Description
4.2 W offline LED
driver with primaryside regulation
3.2 W LED power
supply based on
HVLED805
3 W solution for 300 mA LED type
Efficiency > 80%
3.2 W solution for 200 mA LED type
No e-cap solution
Solution with e-cap
VIPerPlus family overview
Power (W)
Quasi-resonant
Fixed frequency with jittering
w/85-440 VAC
Peak power
management
15-
VIPer35*
10-
VIPer25
VIPer26
5-
VIPer15
VIPer16
3-
VIPer37
VIPer38*
VIPer27
VIPer28
VIPer17
VIPer06*
Supported topologies
Isolated
Non isolated
Isolated
Flyback
Buck/buck-boost/flyback
Flyback
Full production
*Production 2011
VIPerPlus HPF LED driver eval board
High-voltage converters in high power factor flyback
Key features
Main benefits
 Single package approach
 integrated
 robust
 sophisticated
 High-frequency
operation
 Miniaturized form factors
 Easy design
 High power factor > 0.9
 Compliant to energy saving
regulations, suitable for
commercial lighting
 No electrolytic output
capacitor if current ripple is
accepted
 High reliability (extended
MTBF)
EVLVIP27-7WLED *
VIPer27 LED driver module
Evaluation board
EVLVIP27-7WLED *
Application
note
AN3212
Description
3.5 W to 7 W high
power factor offline
LED driver based on
VIPer devices
* Please contact local sales support to order this board
Isolated applications: from 10 to 75W
STPSxx
SEA0x
L6562A
SuperMesh 3 or
MDMesh II
Offline single-stage HPF flyback solution
Applications
AC-DC solutions
for LED driving
 Tube lamp and bulb
replacement
Flyback
 Architectural and
decorative lighting
Flyback
 Street lighting
Flyback
Device
Part
number/family
Primary IC
L6562A / AT
(PFC controller)
 High power factor flyback
 Triac dimmable
 Extended temperature range (AT version)
SuperMESH 3*
 High safety margin and ruggedness
 High immunity to dV/dt, low conduction and switching losses
MDmesh II*
(super junction)
 Up to 800 V with best RDS(on) in the market
 Best-in-class in dynamic dV/dt
 Low input capacitance and gate charge, low gate input resistance
Flyback
MOSFET
Benefits
Schottky
diodes
STPSxx
 Wide product range in Vf/Ir trade-off, avalanche ruggedness
CV/CC
control
SEA0x
 Very low current consumption, wide input voltage range
* See MOSFET selection guide in presentation, online, and in energy-efficient solutions for LED lighting brochure
L6562A
15W Triac dimmable eval board
Key features
STEVAL-ILL016V2
Main benefits
 High power factor flyback
topology supported > 0.9
 Compliant to energy saving
regulations
 Control and power section
separated
 Suitable for high power
 Design flexibility
 Triac dimmable
 Commonly available
dimming option for home
fixtures
 High output voltage
 No limitation to the number
of LEDs within a string
 Based on low-cost
controller and MOSFETs
 Cost-effective solution
Evaluation
board
Application
note
STEVALILL016V2
AN2711
Description
15 W offline Triac dimmable
LED driver from 96 to 32 VAC
L6562A
HPF flyback + inverse buck eval boards
Key features
 High efficiency (> 90%), high
power factor (> 0.9), flyback
topology supported
 Compliant to energy saving
regulations
 Control and power section
separated
 Suitable for high power
 Design flexibility
 CC regulator in inverse buck
working in fixed off time
 Constant ripple current, when
input/output voltages change
 High output voltage
 No limit to number of LEDs
on string
Evaluation
board
STEVAL-ILL019V1
Main benefits
Application
note
Description
STEVALILL019V1
UM0926
35 W offline RGGB LED driver
with individual channel
brightness regulation
EVL6562A35WFLB *
AN2838
35 W wide-range HPF flyback
converter with L6562A
EVL6562ALED
AN2928
AN2983
Modified buck converter for LED
applications
* Please contact local sales support to order this board
Non-isolated: 80W and higher eval board
PFC boost + inverse buck
Applications
AC-DC stage
DC-DC
stage
 Street lighting
PFC boost
Inverse buck
Key features
Offline dual-stage non-isolated solution
STEVAL-ILL013V1
Main benefits
 LED current setting to
350 mA, 700 mA and 1 A
 High flexibility
 High efficiency (~90%), high
power factor, very low THD
 High performances
 High output voltage
 No limitation to the
number of LEDs within a
string
 EN55015 and EN61000-3-2
compliant
 Satisfies the relevant
lighting regulations
Evaluation
board
Application
note
STEVALILL013V1
AN2928
UM0670
Description
80 W offline LED driver
with dimming based on
L6562A
Isolated: >70W resonant LED eval boards
PFC (L6562AT) + resonant converter (L6599AT) + inverse buck (L6562AT)
with MOSFETs*
Key features
PFC + resonant converter
 PFC + resonant controller, with
extended temperature range
 Suitable for outdoor
applications
 No el-cap usage
 High rel (extended MTBF)
 Zero voltage switching and
symmetrical topology
 Very high efficiency > 92%
 Post-regulation with dimming
solution
 Dimmable solutions
 EN55015 and EN61000-3-2
compliant
 Satisfies the relevant
lighting regulations
Evaluation board
EVL130W-SL-EU
EVL130W-STRLIG
Inverse buck – EVL6562A-LED
Main benefits
EVL6562A-LED
Application
note
Description
AN3105
48 V, 130 W LED street lighting SMPS
based on L6562AT and L6599AT for
European input mains range
AN3106
48 V, 130 W LED street lighting SMPS
based on L6562AT and L6599AT for
wide input mains range
AN2983
AN2928 for ref
Modified buck converter for LED
applications
* See MOSFET selection guide earlier in presentation, online, and in energy-efficient solutions for LED lighting brochure
Isolated LED supply: >75W eval board
L6564: current mode PFC controller
Key features
Main benefits
Fast bidirectional input voltage
feedforward
Fast reaction to
 load change
 input voltage change
Protection
 for inductor saturation
 adjustable overvoltage
 against feedback loop
disconnection
 Very robust design
Low start-up current
 High efficiency
Device
Part
number/family
PFC
controller
L6562AT
L6563S, L6564
Ideal for
 PFC preregulator
 SMPS for LED luminaries
Benefits
 Flexibility: 8 pins (L6562A) to 10 pins (L6564) up to 14 pins
(L6563S) with different levels of protection
 T version for extended temperature range (-40 to 150 ˚C)
Evaluation
board
Application
note
EVL6564100W
AN3022
Description
100 W transition mode PFC
preregulator with L6564
L6585DE: SMPS eval board for LEDs
Front-end one-chip SMPS solution
Description and purpose
 Highly-efficient and compact power supply
for high-brightness LED applications such as
street lighting
Key features
 Input voltage 90 to 264 VAC
 Output current: 2 7 A
 Output voltage: 48 V
 No el cap (extended MTBF)
PFC stage + series-resonant half-bridge topology
 Efficiency: 91% (115 VAC), 93% (230 VAC)
 System power: 130 W
 OCP, SC protection
Key products
 L6585DE, STF9NM60N, STF21NM60N,
STPS10150C, STTH3L06
Typical applications
 Street lighting SMPS, adapters (with 19 V,
4.7 A output)
STEVAL-ILL038V1
Digital current controller eval board
Multi-string LED driving based on STM8S microcontroller
Key features
Main
PSU
ZigBee module
STM8S
 Inverse buck
topology in CCM
 Ground referred circuit, no need for
gate drivers
 Logic level MOSFET driven directly
by microcontroller
 Low-voltage sensing circuit
 High efficiency up to 98%
 Works w/o output capacitor
 Accurate averagecurrent control
 Long lifetime for LED
 Able to compensate for Vf variation
due to thermal issue
 Global dimming from 2%
to 100% at 225 Hz (PWM
dimming)
 No flicker
 Independent analog
dimming
 Suitable for RGBW luminaries
Evaluation
board
STEVAL-ILL031V1
Main benefits
STEVALILL031V1
Application
note
AN3151
Description
Digital constant-current controller for
multi-string LED applications based on
STM8S208x
Solar-LED streetlight controller w/STM32
25 W LED lamp driver and 80 W battery charger
Description and purpose
 Cost-optimized and fully-protected solution to
control solar energy storage and to manage LED
streetlights
Key features
 Maximum power point tracker (MPPT) for
more efficient energy use
 Automatic day/night detection
STM32 MCU
 Automatic battery/mains switchover
 Constant-current control for LED lamps
 Battery charge control with temperature
monitoring
 Easy system monitoring via debug
 Full protection function for battery, LED lamp
and solar panel
Key products
 STP40NF10, STP75NF75, STPS20H100,
STPS1L60, STPS2045
Typical applications
 LED street lighting, solar LED applications
STEVAL-ILL022V1
Evaluation
board
STEVALILL022V1
Application
note
UM0512
Description
STEVAL-ILL022V1 solar-LED
streetlight controller with 25 W LED
lamp driver and 80 W battery
charger based on the
STM32F101Rx
Smart street lighting
Intelligent LED cities – ST solutions
Lamp driver and controller
Lamp communication module:
wireless network solution
District data concentrator
s
PLM option
ZigBee® option
Lightens street lighting energy load
Lamp communication module:
wired network solution
Power MOSFET overview
P/N
BVDss
RDS(on)
(max)
Package
Technology
P/N
(Ω)
Package
Technology
(V)
RDS(on)
(max)
(Ω)
0.9
DPAK, TO-220, TO-220FP
MDmesh™ II
BVDss
ST*90N4F3
(V)
40
0.0065
DPAK, TO-220, IPAK
STripFET™ III
ST*7NM60N
600
ST*200N4F3
40
0.004
D2PAK, TO-220
STripFET™ III
ST*9NM60N
600
0.7
DPAK, TO-220, TO-220FP
MDmesh™ II
ST*270N4F3
40
0.0025
D2PAK, TO-220
STripFET™ III
STL70N4LLF5
STL80N4LLF3
STL140N4LLF5
ST*3NF06L
STS5NF60L
STS4DNF60L
STL28N8F3 *
STS4NF100
ST*19NF20
ST*20NF20
ST*16NF25
ST*50NF25
STQ3N45K3-AP
ST*8NM50N
ST*10NM50N
ST*11NM50N
ST*14NM50N
ST*19NM50N
ST*23NM50N
ST*28NM50N
40
40
40
60
60
40
80
100
200
200
250
250
450
500
500
500
500
500
500
500
0.0065
0.005
0.00275
0.1
0.055
0.055
0.034
0.06
0.16
0.125
0.235
0.069
3.8
0.79
0.63
0.47
0.32
0.25
0.19
0.158
STripFET™ V
STripFET™ III
STripFET™ V
STripFET™ II
STripFET™ II
STripFET™ II
STripFET™ III
STripFET™ II
STripFET™ II
STripFET™ II
STripFET™ II
STripFET™ II
SuperMESH 3™
MDmesh™ II
MDmesh™ II
MDmesh™ II
MDmesh™ II
MDmesh™ II
MDmesh™ II
MDmesh™ II
600
600
600
600
600
600
0.55
0.36
0.285
0.22
0.19
0.165
DPAK, TO-220, TO-220FP
DPAK, TO-220, TO-220F
D2PAK, TO-247, TO-220/FP
D2PAK, TO-247, TO-220/FP
D2PAK, TO-247, TO-220/FP
D2PAK, TO-247, TO-220/FP
MDmesh™ II
MDmesh™ II
MDmesh™ II
MDmesh™ II
MDmesh™ II
MDmesh™ II
ST*2N62K3
620
3.5
ST*3N62K3
620
2.5
ST*4N62K3
620
1.95
ST*5N62K3
620
1.6
ST*6N62K3
ST*10N65K3
ST*3NK80Z
ST*5NK80Z
ST*7NM80
620
650
800
800
800
1.2
1
4.5
2.4
1.05
ST*11NM80
800
0.4
525
1.5
STS3N95K3
ST*5N95K3
ST*7N95K3
925
925
925
6.3
3.5
1.35
DPAK, TO-220, TO-220FP
D2PAK, DPAK, TO-220FP,
TO-220, IPAK
DPAK, D²PAK,TO-220FP, IPAK,
TO-220, I²PAK
D²PAK, DPAK,TO-220FP,
TO-220, IPAK
IPAK, DPAK, TO-220,TO-220FP
TO-220FP
TO-220, TO-220FP, DPAK, IPAK
TO-220, TO-220FP
TO-220, TO-220FP, DPAK, IPAK
D2PAK, TO-220, TO-220FP,
TO-247
TO-220, TO-220FP, DPAK, IPAK
TO-220, TO-220FP
TO-220, TO-220FP, DPAK, IPAK
SuperMESH 3™
ST*5N52K3
ST*6N52K3
ST*7N52DK3
525
525
1.2
1.15
PowerFLAT 5x6
PowerFLAT 5x6
PowerFLAT 5x6
SOT-223
SO-8
SO-8 DUAL
PowerFLAT 3.3 x 3.3
SO-8
TO-220, TO-220FP, D2PAK
TO-220, TO-220FP, DPAK
TO-220, TO-220FP, DPAK
TO-220, D2PAK
IPAK, SOT-223, TO92
DPAK, TO-220, TO-220FP
DPAK, TO-220, TO-220FP
DPAK, TO-220, TO-220FP
DPAK, D2PAK
TO-220, TO-220FP
D2PAK, TO-247, TO-220/FP
D2PAK, TO-247, TO-220/FP
D²PAK, DPAK, TO-220FP,
TO-220, IPAK
DPAK, TO-220FP
DPAK, TO-220FP, TO-220
ST*10NM60N
ST*13NM60N
ST*18NM60N
ST*22NM60N
ST*24NM60N
ST*26NM60N
ST*13N95K3
925
0.85
SuperMESH 3™
SuperMESH 3™
SuperFREDmesh 3™
D2PAK, TO-220, TO-220FP,
TO-247
SuperMESH 3™
SuperMESH 3™
SuperMESH 3™
SuperMESH 3™
SuperMESH 3™
SuperMESH™
SuperMESH™
MDmesh™ II
MDmesh™ II
SuperMESH 3™
SuperMESH 3™
SuperMESH 3™
SuperMESH 3™
MDmesh II – ST’s 2nd generation super junction, high-voltage power MOSFET technology
SuperMESH 3 – Covers high-voltage breakdown class for
 improved avalanche ruggedness
 lower on-resistance
 enhanced dynamic performance
 improved diode reverse recovery characteristics
* Under development. Available in Q3/2012
Energy-efficient solutions on st.com
Offline LED lighting and general illumination
LED lighting brochure
LED application web pages
STMicroelectronics offers a full range of components and
evaluation boards for offline LED driver applications. The most
common topologies are presented. The major applications covered
are residential, commercial, architectural and street lighting.
eDesign Studio
www.st.com/edesignstudio
ST products and solutions
For more information, visit:
www.st.com > home > support > tools & resources
www.st.com/LED > off-line LED drivers
Thank you