50 MHz Direct Digital Synthesizer, Waveform Generator AD9835 Data Sheet FEATURES GENERAL DESCRIPTION 5 V power supply 50 MHz speed On-chip COS lookup table On-chip, 10-bit DAC Serial loading Power-down option Temperature range: −40°C to +85°C 200 mW power consumption 16-Lead TSSOP The AD9835 is a numerically-controlled oscillator employing a phase accumulator, a COS lookup table, and a 10-bit digitalto-analog converter integrated on a single CMOS chip. Modulation capabilities are provided for phase modulation and frequency modulation. Clock rates of up to 50 MHz are supported. Frequency accuracy can be controlled to one part in 4 billion. Modulation is effected by loading registers through the serial interface. A power-down bit allows the user to power down the AD9835 when it is not in use; the power consumption reduces to 1.75 mW. APPLICATIONS This part is available in a 16-lead TSSOP package. Frequency stimulus/waveform generation Frequency phase tuning and modulation Low power RF/communications systems Liquid and gas flow measurement Sensory applications: proximity, motion, and defect detection Test and medical equipment Similar DDS products can be found at http://www.analog.com/DDS. FUNCTIONAL BLOCK DIAGRAM DVDD FSELECT BIT FSELECT AVDD AGND REFOUT FS ADJUST REFIN SELSRC ON-BOARD REFERENCE MUX MCLK DGND FULL-SCALE CONTROL SYNC FREQ0 REG MUX FREQ1 REG 12 PHASE ACCUMULATOR (32 BIT) COS ROM 10-BIT DAC COMP IOUT PHASE0 REG PHASE1 REG PHASE2 REG SYNC AD9835 MUX PHASE3 REG SYNC 16-BIT DATA REGISTER SYNC 8 MSBs 8 LSBs DEFER REGISTER SELSRC DECODE LOGIC CONTROL REGISTER FSELECT/PSEL REGISTER MUX PSEL0 BIT MUX PSEL1 BIT FSYNC SCLK PSEL0 PSEL1 SDATA 09630-001 SERIAL REGISTER Figure 1. Rev. A Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 www.analog.com Fax: 781.461.3113 ©1998–2011 Analog Devices, Inc. All rights reserved. AD9835 Data Sheet TABLE OF CONTENTS Features .............................................................................................. 1 Latency......................................................................................... 17 Applications....................................................................................... 1 Flowcharts ................................................................................... 17 General Description ......................................................................... 1 Applications Information .............................................................. 20 Functional Block Diagram .............................................................. 1 Grounding and Layout .............................................................. 20 Revision History ............................................................................... 2 Interfacing the AD9835 to Microprocessors .......................... 20 Specifications..................................................................................... 3 AD9835-to-ADSP-21xx Interface ............................................ 20 Timing Characteristics ................................................................ 5 AD9835-to-68HC11/68L11 Interface...................................... 21 Absolute Maximum Ratings............................................................ 6 AD9835-to-80C51/80L51 Interface......................................... 21 ESD Caution.................................................................................. 6 AD9835-to-DSP56002 Interface .............................................. 21 Pin Configuration and Function Descriptions............................. 7 Evaluation Board ............................................................................ 22 Typical Performance Characteristics ............................................. 9 System Demonstration Platform.............................................. 22 Terminology .................................................................................... 12 AD9835 to SPORT Interface..................................................... 22 Theory Of Operation ..................................................................... 13 XO vs. External Clock................................................................ 22 Circuit Description......................................................................... 14 Power Supply............................................................................... 22 Numerical Controlled Oscillator and Phase Modulator ....... 14 Evaluation Board Schematics and Layout............................... 23 COS LookUp Table (LUT) ........................................................ 14 Ordering Information.................................................................... 26 Digital-to-Analog Converter .................................................... 14 Bill of Materials........................................................................... 26 Functional Description .................................................................. 15 Outline Dimensions ....................................................................... 27 Serial Interface ............................................................................ 15 Ordering Guide .......................................................................... 27 Direct Data Transfer and Deferred Data Transfer ................. 16 REVISION HISTORY 9/11—Rev. 0 to Rev. A Updated Format..................................................................Universal Changes to Features and Applications........................................... 1 Changes to Specification Statement ............................................... 3 Changes to Figure 2.......................................................................... 4 Changes to Timing Characteristics Statement ............................. 5 Replaced Evaluation Board Section; Renumbered Sequentially ..................................................................................... 22 Changes to Bill of Materials .......................................................... 27 Changes to Ordering Guide .......................................................... 28 7/98—Revision 0: Initial Version Rev. A | Page 2 of 28 Data Sheet AD9835 SPECIFICATIONS VDD = +5 V ± 5%; AGND = DGND = 0 V; TA = TMIN to TMAX; REFIN = REFOUT; RSET = 3.9 kΩ; RLOAD = 300 Ω for IOUT, unless otherwise noted. Also, see Figure 2. Table 1. Parameter 1 SIGNAL DAC SPECIFICATIONS Resolution Update Rate (fMAX) IOUT Full Scale Output Compliance DC Accuracy Integral Nonlinearity Differential Nonlinearity DDS SPECIFICATIONS 2 Dynamic Specifications Signal-to-Noise Ratio Total Harmonic Distortion Spurious Free Dynamic Range (SFDR) 3 Narrow Band (±50 kHz) Wide Band (±2 MHz) Clock Feedthrough Wake-Up Time Power-Down Option VOLTAGE REFERENCE Internal Reference @ +25° C TMIN to TMAX REFIN Input Impedance Reference TC REFOUT Output Impedance LOGIC INPUTS VINH, Input High Voltage VINL, Input Low Voltage IINH, Input Current CIN, Input Capacitance POWER SUPPLIES AVDD DVDD IAA IDD IAA + IDD 4 Low Power Sleep Mode Min Typ Max Units 10 Bits MSPS mA mA V 50 4 4.75 1.35 ±1 ±0.5 Test Conditions/Comments LSB LSB 50 −52 −72 −50 dB dBc fMCLK = 50 MHz, fOUT = 1 MHz fMCLK = 50 MHz, fOUT = 1 MHz fMCLK = 6.25 MHz, fOUT = 2.11 MHz dBc dBc dBc ms −60 1 Yes 1.21 1.131 1.29 10 100 300 DVDD − 0.9 0.9 10 10 V V MΩ ppm/°C Ω V V μA pF fMCLK = 50 MHz 4.75 4.75 5.25 5.25 5 V min/V max V min/V max mA max mA typ 40 0.35 mA max mA max 2.5 + 0.33/MHz 1 Operating temperature range is as follows: B Version: −40°C to +85°C. 100% production tested. 3 fMCLK = 6.25 MHz, Frequency Word = 5671C71C HEX, fOUT = 2.11 MHz. 4 Measured with the digital inputs static and equal to 0 V or DVDD. The AD9835 is tested with a capacitive load of 50 pF. The part can be operated with higher capacitive loads, but the magnitude of the analog output will be attenuated. See Figure 7. 2 Rev. A | Page 3 of 28 AD9835 Data Sheet RSET 3.9kΩ 10nF ON-BOARD REFERENCE 12 SIN ROM REFIN FS ADJUST FULL-SCALE CONTROL 10-BIT DAC COMP AVDD 10nF IOUT 300Ω AD9835 Figure 2. Test Circuit Rev. A | Page 4 of 28 50pF 09630-002 REFOUT Data Sheet AD9835 TIMING CHARACTERISTICS VDD = +5 V ± 5%; AGND = DGND = 0 V, unless otherwise noted. Table 2. Parameter t1 t2 t3 t4 t5 t6 t7 t8 t9 t10 t11 t11A 1 1 Limit at TMIN to TMAX (B Version) 20 8 8 50 20 20 15 20 SCLK − 5 15 5 8 8 Units ns min ns min ns min ns min ns min ns min ns min ns min ns max ns min ns min ns min ns min Test Conditions/Comments MCLK period MCLK high duration MCLK low duration SCLK period SCLK high duration SCLK low duration FSYNC to SCLK falling edge setup time FSYNC to SCLK hold time Data setup time Data hold time FSELECT, PSEL0, PSEL1 setup time before mclk rising edge FSELECT, PSEL0, PSEL1 setup time after mclk rising edge See the Pin Configuration and Function Descriptions section. Timing Diagrams t1 MCLK 09630-003 t2 t3 Figure 3. Master Clock t5 t4 SCLK t7 t8 t6 FSYNC D15 D14 D2 D1 D0 D15 Figure 4. Serial Timing MCLK t11A t11 FSELECT PSEL0, PSEL1 VALID DATA VALID DATA Figure 5. Control Timing Rev. A | Page 5 of 28 VALID DATA 09630-005 SDATA t10 D14 09630-004 t9 AD9835 Data Sheet ABSOLUTE MAXIMUM RATINGS TA = +25°C, unless otherwise noted. Table 3. Parameter AVDD to AGND DVDD to DGND AVDD to DVDD AGND to DGND Digital I/O Voltage to DGND Analog I/O Voltage to AGND Operating Temperature Range Industrial (B Version) Storage Temperature Range Maximum Junction Temperature TSSOP θJA Thermal Impedance Lead Temperature, Soldering Vapor Phase (60 sec) Infrared (15 sec) ESD Rating Rating −0.3 V to +7 V −0.3 V to +7 V −0.3 V to +0.3 V −0.3 V to +0.3 V −0.3 V to DVDD + 0.3 V −0.3 V to AVDD + 0.3 V Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. ESD CAUTION −40°C to +85°C −65°C to +150°C +150°C 158°C/W +215°C +220°C > 4500 V Rev. A | Page 6 of 28 Data Sheet AD9835 FS ADJUST 1 16 COMP REFIN 2 15 AVDD REFOUT 3 14 IOUT DVDD 4 AD9835 13 AGND DGND 5 TOP VIEW (Not to Scale) 12 PSEL0 MCLK 6 11 PSEL1 SCLK 7 10 FSELECT SDATA 8 9 FSYNC 09630-006 PIN CONFIGURATION AND FUNCTION DESCRIPTIONS Figure 6. Pin Configuration Table 4. Pin Function Descriptions Pin No. Mnemonic Description ANALOG SIGNAL AND REFERENCE Full-Scale Adjust Control. A resistor (RSET) is connected between this pin and AGND. This determines the 1 FS ADJUST magnitude of the full-scale DAC current. The relationship between RSET and the full-scale current is IOUTFULL-SCALE = 12.5 × VREFIN/RSET, where VREFIN = 1.21 V nominal, RSET = 3.9 kΩ typical. 2 REFIN 3 REFOUT 14 IOUT 16 COMP Voltage Reference Input. The AD9835 can be used with either the on-board reference, which is available from Pin REFOUT, or an external reference. The reference to be used is connected to the REFIN pin. The AD9835 accepts a reference of 1.21 V nominal. Voltage Reference Output. The AD9835 has an on-board reference of value 1.21 V nominal. The reference is made available on the REFOUT pin. This reference is used as the reference to the DAC by connecting REFOUT to REFIN. REFOUT should be decoupled with a 10 nF capacitor to AGND. Current Output. This is a high impedance current source. A load resistor should be connected between IOUT and AGND. Compensation Pin. This is a compensation pin for the internal reference amplifier. A 10 nF decoupling ceramic capacitor should be connected between COMP and AVDD. POWER SUPPLY 4 DVDD Positive Power Supply for the Digital Section. A 0.1 μF decoupling capacitor should be connected between DVDD and DGND. DVDD can have a value of +5 V ± 5%. 5 DGND Digital Ground. 13 AGND Analog Ground. 15 AVDD Positive Power Supply for the Analog Section. A 0.1 μF decoupling capacitor should be connected between AVDD and AGND. AVDD can have a value of +5 V ± 5%. DIGITAL INTERFACE AND CONTROL 6 MCLK Digital Clock Input. DDS output frequencies are expressed as a binary fraction of the frequency of MCLK. The output frequency accuracy and phase noise are determined by this clock. 7 SCLK Serial Clock, Logic Input. Data is clocked into the AD9835 on each falling SCLK edge. 8 SDATA Serial Data In, Logic Input. The 16-bit serial data word is applied to this input. 9 FSYNC Data Synchronization Signal, Logic Input. When this input is taken low, the internal logic is informed that a new word is being loaded into the device. 10 FSELECT Frequency Select Input. FSELECT controls which frequency register, FREQ0 or FREQ1, is used in the phase accumulator. The frequency register can be selected using the Pin FSELECT or the Bit FSELECT. FSELECT is sampled on the rising MCLK edge. FSLECT needs to be in steady state when an MCLK rising edge occurs. If FSELECT changes value when a rising edge occurs, there is an uncertainty of one MCLK cycle as to when control is transferred to the other frequency register. To avoid any uncertainty, a change on FSELECT should not coincide with an MCLK rising edge. When the bit is being used to select the frequency register, the Pin FSELECT should be tied to DGND. Rev. A | Page 7 of 28 AD9835 Pin No. 11, 12 Mnemonic PSEL0, PSEL1 Data Sheet Description Phase Select Input. The AD9835 has four phase registers. These registers can be used to alter the value being input to the COS ROM. The contents of the phase register are added to the phase accumulator output, the PSEL0 and PSEL1 inputs selecting the phase register to be used. Alternatively, the phase register to be used can be selected using the PSEL0 and PSEL1 bits. Like the FSELECT input, PSEL0 and PSEL1 are sampled on the rising MCLK edge. Therefore, these inputs need to be in steady state when an MCLK rising edge occurs or there is an uncertainty of one MCLK cycle as to when control is transferred to the selected phase register. When the phase registers are being controlled by the PSEL0 and PSEL1 bits, the pins should be tied to DGND. Rev. A | Page 8 of 28 Data Sheet AD9835 TYPICAL PERFORMANCE CHARACTERISTICS 0 0 AVDD = DVDD = +5V –4 SFDR [±2MHz] (dB) –10 CL = 82pF –6 –8 –20 –30 –40 CL = 150pF 0 2 4 6 8 10 12 14 16 OUTPUT FREQUENCY (MHz) –60 10 –20 TA = +25°C AVDD = DVDD = +5V 20 15 10 –40 50MHz –50 30MHz –60 10MHz –70 30 20 40 50 MCLK FREQUENCY (MHz) –80 0.044 09630-008 0 10 Figure 8. Typical Current Consumption vs. MCLK Frequency 0.084 0.124 0.164 0.204 56 55 –68 54 SNR (dB) –66 –70 –74 51 MCLK FREQUENCY (MHz) 50 09630-009 52 40 0.463 53 –72 30 0.324 fOUT/fMCLK = 1/3 AVDD = DVDD = +5V AVDD = DVDD = +5V 20 0.284 Figure 11. Wideband SFDR vs. fOUT/fMCLK for Various MCLK Frequencies fOUT/fMCLK = 1/3 –76 10 0.244 fOUT/fMCLK 09630-011 SFDR [±2MHz] (dB) TOTAL CURRENT (mA) AVDD = DVDD = +5V –30 5 SFDR [±50kHz] (dB) 50 Figure 10. Wideband SFDR vs. MCLK Frequency 25 –64 40 MCLK FREQUENCY (MHz) Figure 7. Signal Attenuation vs. Output Frequency for Various Capacitive Loads (RL = 300 Ω) 30 30 20 Figure 9. Narrow-Band SFDR vs. MCLK Frequency 50 10 20 30 40 MCLK FREQUENCY (MHz) Figure 12. SNR vs. MCLK Frequency Rev. A | Page 9 of 28 50 09630-012 –12 –50 CL = 100pF 09630-010 –10 09630-007 SIGNAL ATTENUATION (dB) –2 fOUT/fMCLK = 1/3 AVDD = DVDD = +5V AD9835 70 Data Sheet AVDD = DVDD = +5V 10MHz 60 30MHz 50MHz 10dB/DIV SNR (dB) 50 40 30 0.164 0.204 0.244 0.284 0.324 0.364 fOUT/fMCLK 0Hz START RBW 1kHz 10dB/DIV 10dB/DIV 0Hz START RBW 1kHz 09630-014 VBW 3kHz 25MHz STOP ST 50 SEC VBW 3kHz 25MHz STOP ST 50 SEC Figure 17. fMCLK = 50 MHz, fOUT = 9.1 MHz. Frequency Word = 2E978D50 10dB/DIV 10dB/DIV Figure 14. fMCLK = 50 MHz, fOUT = 2.1 MHz. Frequency Word = ACO8312 VBW 3kHz 25MHz STOP ST 50 SEC 0Hz START RBW 1kHz 09630-015 0Hz START RBW 1kHz 25MHz STOP ST 50 SEC Figure 16. fMCLK = 50 MHz, fOUT = 7.1 MHz. Frequency Word = 245AICAC Figure 13. SNR vs. fOUT/fMCLK for Various MCLK Frequencies 0Hz START RBW 1kHz VBW 3kHz 09630-017 0.124 Figure 15. fMCLK = 50 MHz, fOUT = 3.1 MHz. Frequency Word = FDF3B64 VBW 3kHz 25MHz STOP ST 50 SEC 09630-018 0.084 09630-013 10 0.044 09630-016 20 Figure 18. fMCLK = 50 MHz, fOUT = 11.1 MHz. Frequency Word = 38D4FDF4 Rev. A | Page 10 of 28 AD9835 VBW 3kHz 25MHz STOP ST 50 SEC 0Hz START RBW 1kHz 09630-019 0Hz START RBW 1kHz Figure 19. fMCLK = 50 MHz, fOUT = 13.1 MHz. Frequency Word = 43126E98 VBW 3kHz 25MHz STOP ST 50 SEC 09630-020 10dB/DIV 10dB/DIV Data Sheet Figure 20. fMCLK = 50 MHz, fOUT = 16.5 MHz. Frequency Word = 547AE148 Rev. A | Page 11 of 28 AD9835 Data Sheet TERMINOLOGY Integral Nonlinearity This is the maximum deviation of any code from a straight line passing through the endpoints of the transfer function. The endpoints of the transfer function are zero scale, a point 0.5 LSB below the first code transition (000 . . . 00 to 000 . . . 01) and full scale, a point 0.5 LSB above the last code transition (111 . . . 10 to 111 . . . 11). The error is expressed in LSBs. Total Harmonic Distortion Total Harmonic Distortion (THD) is the ratio of the rms sum of harmonics to the rms value of the fundamental. For the AD9835, THD is defined as Differential Nonlinearity This is the difference between the measured and ideal 1 LSB change between two adjacent codes in the DAC. where V1 is the rms amplitude of the fundamental and V2, V3, V4, V5, and V6 are the rms amplitudes of the second through the sixth harmonic. Signal to (Noise + Distortion) Signal to (Noise + Distortion) is measured signal to noise at the output of the DAC. The signal is the rms magnitude of the fundamental. Noise is the rms sum of all the non-fundamental signals up to half the sampling frequency (fMCLK/2) but excluding the dc component. Signal to (Noise + Distortion) is dependent on the number of quantization levels used in the digitization process; the more levels, the smaller the quantization noise. The theoretical Signal to (Noise + Distortion) ratio for a sine wave input is given by Output Compliance The output compliance refers to the maximum voltage that can be generated at the output of the DAC to meet the specifications. When voltages greater than that specified for the output compliance are generated, the AD9835 may not meet the specifications listed in the data sheet. Signal to (Noise + Distortion) = (6.02N + 1.76) dB where N is the number of bits. Thus, for an ideal 10-bit converter, Signal to (Noise + Distortion) = 61.96 dB. THD = 20 log (V2 2 + V3 2 + V4 2 + V5 2 + V6 2 ) V1 Spurious Free Dynamic Range Along with the frequency of interest, harmonics of the fundamental frequency and images of the MCLK frequency are present at the output of a DDS device. The spurious free dynamic range (SFDR) refers to the largest spur or harmonic present in the band of interest. The wideband SFDR gives the magnitude of the largest harmonic or spur relative to the magnitude of the fundamental frequency in the bandwidth ±2 MHz about the fundamental frequency. The narrow band SFDR gives the attenuation of the largest spur or harmonic in a bandwidth of ±50 kHz about the fundamental frequency. Clock Feedthrough There will be feedthrough from the MCLK input to the analog output. Clock feedthrough refers to the magnitude of the MCLK signal relative to the fundamental frequency in the AD9835’s output spectrum. Rev. A | Page 12 of 28 Data Sheet AD9835 THEORY OF OPERATION Sine waves are typically thought of in terms of their magnitude form a(t) = sin (ωt). However, these are nonlinear and not easy to generate except through piecewise construction. On the other hand, the angular information is linear in nature. That is, the phase angle rotates through a fixed angle for each unit of time. The angular rate depends on the frequency of the signal by the traditional rate of ω = 2 πf. MAGNITUDE Knowing that the phase of a sine wave is linear and given a reference interval (clock period), the phase rotation for that period can be determined by ΔPhase = ωδt Solving for ω, ω = ΔPhase/δt = 2 πf Solving for f and substituting the reference clock frequency for the reference period (1/fMCLK = δt), +1 f = ΔPhase × fMCLK/2 π 0 The AD9835 builds the output based on this simple equation. A simple DDS chip can implement this equation with three major subcircuits. –1 PHASE 09630-023 2 0 Figure 21. Sine Wave Rev. A | Page 13 of 28 AD9835 Data Sheet CIRCUIT DESCRIPTION The AD9835 provides an exciting level of integration for the RF communications system designer. The AD9835 combines the numerical controlled oscillator (NCO), COS lookup table, frequency and phase modulators, and a digital-to- analog converter on a single integrated circuit. The internal circuitry of the AD9835 consists of three main sections. These are • • • Following the NCO, a phase offset can be added to perform phase modulation using the 12-bit PHASE registers. The contents of this register are added to the most significant bits of the NCO. The AD9835 has four PHASE registers, the resolution of these registers being 2 π/4096. numerical controlled oscillator (NCO) and phase modulator COS lookup table digital-to-analog converter The AD9835 is a fully integrated direct digital synthesis (DDS) chip. The chip requires one reference clock, one low precision resistor, and eight decoupling capacitors to provide digitallycreated sine waves up to 25 MHz. In addition to the generation of this RF signal, the chip is fully capable of a broad range of simple and complex modulation schemes. These modulation schemes are fully implemented in the digital domain allowing accurate and simple realization of complex modulation algorithms using DSP techniques. NUMERICAL CONTROLLED OSCILLATOR AND PHASE MODULATOR This consists of two frequency select registers, a phase accumulator and four phase offset registers. The main component of the NCO is a 32-bit phase accumulator, which assembles the phase component of the output signal. Continuous time signals have a phase range of 0 π to 2 π. Outside this range of numbers, the sinusoid functions repeat themselves in a periodic manner. The digital implementation is no different. The accumulator simply scales the range of phase numbers into a multibit digital word. The phase accumulator in the AD9835 is implemented with 32 bits. Therefore, in the AD9835, 2 π = 232. Likewise, the ΔPhase term is scaled into this range of numbers 0 < ΔPhase < 232 − 1. Making these substitutions into the equation above f = ΔPhase × fMCLK/232 where 0 < ΔPhase < 232 The input to the phase accumulator (that is, the phase step) can be selected either from the FREQ0 register or FREQ1 register and this is controlled by the FSELECT pin or the FSELECT bit. NCOs inherently generate continuous phase signals, thus avoiding any output discontinuity when switching between frequencies. COS LOOKUP TABLE (LUT) To make the output useful, the signal must be converted from phase information into a sinusoidal value. Since phase information maps directly into amplitude, a ROM LUT converts the phase information into amplitude. To do this, the digital phase information is used to address a COS ROM LUT. Although the NCO contains a 32-bit phase accumulator, the output of the NCO is truncated to 12 bits. Using the full resolution of the phase accumulator is impractical and unnecessary as this would require a lookup table of 232 entries. It is necessary only to have sufficient phase resolution in the LUTs such that the dc error of the output waveform is dominated by the quantization error in the DAC. This requires the lookup table to have two more bits of phase resolution than the 10-bit DAC. DIGITAL-TO-ANALOG CONVERTER The AD9835 includes a high impedance current source 10-bit DAC, capable of driving a wide range of loads at different speeds. Full-scale output current can be adjusted, for optimum power and external load requirements, through the use of a single external resistor (RSET). The DAC is configured for single-ended operation. The load resistor can be any value required, as long as the full-scale voltage developed across it does not exceed the voltage compliance range. Since full-scale current is controlled by RSET, adjustments to RSET can balance changes made to the load resistor. However, if the DAC full-scale output current is significantly less than 4 mA, the DAC’s linearity may degrade. Rev. A | Page 14 of 28 Data Sheet AD9835 FUNCTIONAL DESCRIPTION SERIAL INTERFACE The AD9835 has a serial interface, with 16 bits loaded during each write cycle. SCLK, SDATA, and FSYNC are used to load the word into the AD9835. continuous, or alternatively, the SCLK can idle high or low between write operations. When writing to a frequency/phase register, the first four bits identify whether a frequency or phase register is being written to, the next four bits contain the address of the destination register, while the 8 LSBs contain the data. When FSYNC is taken low, the AD9835 is informed that a word is being written to the device. The first bit is read into the device on the next SCLK falling edge with the remaining bits being read into the device on the subsequent SCLK falling edges. FSYNC frames the 16 bits; therefore, when 16 SCLK falling edges have occurred, FSYNC should be taken high again. The SCLK can be Table 5 shows the data structure for a 16-bit write to the AD9835. For examples on programming the AD9835, see the AN-621 and AN-1108 application notes at www.analog.com. Table 5. Writing to the AD9835 Data Registers D15 C3 1 D14 C2 D13 C1 D12 C0 D11 A3 D10 A2 D9 A1 D8 A0 D7 MSB D6 X1 D5 X1 D4 X1 D3 X1 D2 X1 D1 X1 X = don’t care. Table 6. Commands C3 0 C2 0 C1 0 C0 0 0 0 0 0 0 1 1 0 0 0 0 1 1 0 1 0 0 1 0 1 0 1 1 0 0 1 1 1 Table 7. Addressing the Registers Command Write 16 phase bits (present 8 bits + 8 bits in the defer register) to selected PHASEx REG. Write 8 phase bits to the defer register. Write 16 frequency bits (present 8 bits + 8 bits in the defer register) to selected the FREQx REG. Write 8 frequency bits to the defer register. Bit D9 (PSEL0) and Bit D10 (PSEL1) are used to select the PHASEx REG when SELSRC = 1. When SELSRC = 0, the PHASEx REG is selected using the PSEL0 and PSEL1 pins. Bit D11 is used to select the FREQx REG when SELSRC = 1. When SELSRC = 0, the FREQx REG is selected using the FSELECT pin. To control the PSEL0, PSEL1, and FSELECT bits using only one write, this command is used. Bit D9 and Bit D10 are used to select the PHASEx REG, and Bit 11 is used to select the FREQx REG when SELSRC = 1. When SELSRC = 0, the PHASEx REG is selected using the PSEL0 and PSEL1 pins and the FREQx REG is selected using the FSELECT pin. Reserved. It configures the AD9835 for test purposes. A3 0 0 0 0 0 0 0 0 1 1 1 1 1 1 1 1 Rev. A | Page 15 of 28 A2 0 0 0 0 1 1 1 1 0 0 0 0 1 1 1 1 A1 0 0 1 1 0 0 1 1 0 0 1 1 0 0 1 1 A0 0 1 0 1 0 1 0 1 0 1 0 1 0 1 0 1 Destination Register FREQ0 REG 8 L LSBs FREQ0 REG 8 H LSBs FREQ0 REG 8 L MSBs FREQ0 REG 8 H MSBs FREQ1 REG 8 L LSBs FREQ1 REG 8 H LSBs FREQ1 REG 8 L MSBs FREQ1 REG 8 H MSBs PHASE0 REG 8 LSBs PHASE0 REG 8 MSBs PHASE1 REG 8 LSBs PHASE1 REG 8 MSBs PHASE2 REG 8 LSBs PHASE2 REG 8 MSBs PHASE3 REG 8 LSBs PHASE3 REG 8 MSBs D0 LSB AD9835 Data Sheet Table 8. Control Registers Register FREQ0 REG Size 32 bits FREQ1 REG 32 bits PHASE0 REG 12 bits PHASE1 REG 12 bits PHASE2 REG 12 bits PHASE3 REG 12 bits Description Frequency Register 0. This defines the output frequency, when FSELECT = 0, as a fraction of the MCLK frequency. Frequency Register 1. This defines the output frequency, when FSELECT = 1, as a fraction of the MCLK frequency. Phase Offset Register 0. When PSEL0 = PSEL1 = 0, the contents of this register are added to the output of the phase accumulator. Phase Offset Register 1. When PSEL0 = 1 and PSEL1 = 0, the contents of this register are added to the output of the phase accumulator. Phase Offset Register 2. When PSEL0 = 0 and PSEL1 = 1, the contents of this register are added to the output of the phase accumulator. Phase Offset Register 3. When PSEL0 = PSEL1 = 1, the contents of this register are added to the output of the phase accumulator. Table 9. 32-Bit Frequency Word 16 MSBs 8 H MSBs 8 L MSBs 8 H LSBs For example, after a new 16-bit word has been loaded to a destination register, the defer register will also contain this word. If the next write instruction is to the same destination register, the user can use direct data transfers immediately. When writing to a phase register, the 4 MSBs of the 16-bit word loaded into the data register should be zero (the phase registers are 12 bits wide). To alter the entire contents of a frequency register, four write operations are needed. However, the 16 MSBs of a frequency word are contained in a separate register to the 16 LSBs. Therefore, the 16 MSBs of the frequency word can be altered independent of the 16 LSBs. The phase and frequency registers to be used are selected using the FSELECT, PSEL0, and PSEL1 pins, or the corresponding bits can be used. Bit SELSRC determines whether the bits or the pins are used. When SELSRC = 0, the pins are used, and when SELSRC = 1, the bits are used. When CLR is taken high, SELSRC is set to 0 so that the pins are the default source. Data transfers from the serial (defer) register to the 16-bit data register, and the FSELECT and PSEL registers, occur following the 16th falling SCLK edge. Table 11. Controlling the AD9835 16 LSBs 8 L LSBs D15 1 D14 0 1 1 Table 10. 12-Bit Frequency Word 4 MSBs (The 4 MSBs of the 8-Bit Word Loaded = 0) 8 LSBs DIRECT DATA TRANSFER AND DEFERRED DATA TRANSFER Within the AD9835, 16-bit transfers are used when loading the destination frequency/phase register. There are two modes for loading a register, direct data transfer and a deferred data transfer. With a deferred data transfer, the 8-bit word is loaded into the defer register (8 LSBs or 8 MSBs). However, this data is not loaded into the 16-bit data register; therefore, the destination register is not updated. With a direct data transfer, the 8-bit word is loaded into the appropriate defer register (8 LSBs or 8 MSBs). Immediately following the loading of the defer register, the contents of the complete defer register are loaded into the 16-bit data register and the destination register is loaded on the next MCLK rising edge. When a destination register is addressed, a deferred transfer is needed first followed by a direct transfer. When all 16 bits of the defer register contain relevant data, the destination register can then be updated using 8-bit loading rather than 16-bit loading, that is, direct data transfers can be used. Rev. A | Page 16 of 28 Command Selects source of control for the PHASEx and FREQx registers and enables synchronization. Bit D13 is the SYNC bit. When this bit is high, reading of the FSELECT, PSEL0, and PSEL1 bits/ pins and the loading of the destination register with data is synchronized with the rising edge of MCLK. The latency is increased by 2 MCLK cycles when SYNC = 1. When SYNC = 0, the loading of the data and the sampling of FSELECT/PSEL0/PSEL1 occurs asynchronously. Bit D12 is the select source bit (SELSRC). When this bit equals 1, the PHASEx/FREQx REG is selected using the FSELECT, PSEL0, and PSEL1 bits. When SELSRC = 0, the PHASEx/FREQx REG is selected using the FSELECT, PSEL0, and PSEL1 pins. SLEEP, RESET, and CLR (clear). D13 is the SLEEP bit. When this bit equals 1, the AD9835 is powered down, internal clocks are disabled, and the current sources and REFOUT of the DAC are turned off. When SLEEP = 0, the AD9835 is powered up. When RESET (D12) = 1, the phase accumulator is set to zero phase that corresponds to an analog output of midscale. When CLR (D11) = 1, SYNC and SELSRC are set to zero. CLR resets to 0 automatically. Data Sheet AD9835 Table 12. Setting SYNC and SELSRC D15 1 1 D14 0 D13 SYNC D12 SELSRC D11 X1 D10 X1 D9 X1 D8 X1 D7 X1 D6 X1 D5 X1 D4 X1 D3 X1 D2 X1 D1 X1 D0 X1 D9 X1 D8 X1 D7 X1 D6 X1 D5 X1 D4 X1 D3 X1 D2 X1 D1 X1 D0 X1 X = don’t care. Table 13. Power-Down, Resetting and Clearing the AD9835 D15 1 1 D14 1 D13 SLEEP D12 RESET D11 CLR D10 X1 X = don’t care. Transfer of the data from the 16-bit data register to the destination register or from the FSELECT/PSEL register to the respective multiplexer occurs on the next MCLK rising edge. Because SCLK and MCLK are asynchronous, an MCLK rising edge may occur while the data bits are in a transitional state. This can cause a brief spurious DAC output if the register being written to is generating the DAC output. To avoid such spurious outputs, the AD9835 contains synchronizing circuitry. When the SYNC bit is set to 1, the synchronizer is enabled and data transfers from the serial register (defer register) to the 16-bit data register, and the FSELECT/PSEL registers occur following a two-stage pipeline delay that is triggered on the MCLK falling edge. The pipeline delay ensures that the data is valid when the transfer occurs. Similarly, selection of the frequency/phase registers using the FSELECT/PSELx pins is synchronized with the MCLK rising edge when SYNC = 1. When SYNC = 0, the synchronizer is bypassed. Selecting the frequency/phase registers using the pins is synchronized with MCLK internally also when SYNC = 1 to ensure that these inputs are valid at the MCLK rising edge. If times t11 and t11A are met, then the inputs will be at steady state at the MCLK rising edge. However, if times t11 and t11A are violated, the internal synchronizing circuitry will delay the instant at which the pins are sampled, ensuring that the inputs are valid at the sampling instant (see Figure 5). LATENCY Associated with each operation is a latency. When inputs FSELECT/PSEL change value, there is a pipeline delay before control is transferred to the selected register; there is a pipeline delay before the analog output is controlled by the selected register. When times t11 and t11A are met, PSEL0, PSEL1, and FSELECT have latencies of six MCLK cycles when SYNC = 0. When SYNC = 1, the latency is increased to 8 MCLK cycles. When times t11 and t11A are not met, the latency can increase by one MCLK cycle. Similarly, there is a latency associated with each write operation. If a selected frequency/phase register is loaded with a new word, there is a delay of 6 to 7 MCLK cycles before the analog output will change (there is an uncertainty of one MCLK cycle regarding the MCLK rising edge at which the data is loaded into the destination register). When SYNC = 1, the latency is 8 or 9 MCLK cycles. FLOWCHARTS The flowchart in Figure 22 shows the operating routine for the AD9835. When the AD9835 is powered up, the part should be reset, which resets the phase accumulator to zero so that the analog output is at midscale. To avoid spurious DAC outputs while the AD9835 is being initialized, the RESET bit should be set to 1 until the part is ready to begin generating an output. Taking CLR high sets SYNC and SELSRC to 0 so that the FSELECT/PSELx pins are used to select the frequency/phase registers, and the synchronization circuitry is bypassed. A write operation is needed to the SYNC/SELSRC register to enable the synchronization circuitry or to change control to the FSELECT/ PSEL bits. RESET does not reset the phase and frequency registers. These registers will contain invalid data and, therefore, should be set to a known value by the user. The RESET bit is then set to 0 to begin generating an output. A signal will appear at the DAC output 6 MCLK cycles after RESET is set to 0. The analog output is fMCLK/232 × FREG, where FREG is the value loaded into the selected frequency register. This signal is phase shifted by the amount specified in the selected phase register (2π/4096 × PHASEx REG, where PHASEx REG is the value contained in the selected phase register). Control of the frequency/phase registers can be interchanged from the pins to the bits. Rev. A | Page 17 of 28 AD9835 Data Sheet DATA WRITE FREG[0] = fOUT0/fMCLK × 232 FREG[1] = fOUT1/fMCLK × 232 PHASEREG [3:0] = DELTA PHASE[0, 1, 2, 3] SELECT DATA SOURCES SET FSELECT SET PSEL0, PSEL1 INITIALIZATION WAIT 6 MCLK CYCLES (8 MCLK CYCLES IF SYNC = 1) DAC OUTPUT VOUT = VREFIN × 6.25 × ROUT/RSET × (1 + SIN(2π(FREG × fMCLK × t/232 + PHASEREG/212))) CHANGE PHASE? YES NO NO CHANGE fOUT? YES CHANGE fOUT? CHANGE PHASEREG? YES NO CHANGE PSEL0, PSEL1 09630-024 NO YES Figure 22. Flowchart for AD9835 Initialization and Operation INITIALIZATION CONTROL REGISTER WRITE SET SLEEP RESET = 1 CLR = 1 SET SYNC AND/OR SELSRC TO 1 YES NO CONTROL REGISTER WRITE SYNC = 1 AND/OR SELSRC = 1 WRITE INITIAL DATA FREG[0] = fOUT0/fMCLK × 232 FREG[1] = fOUT1/fMCLK × 232 PHASEREG[3:0] = DELTA PHASE[0, 1, 2, 3] SET PINS OR FREQUENCY/PHASE REGISTER WRITE SET FSELECT, PSEL0 AND PSEL1 CONTROL REGISTER WRITE SLEEP = 0 RESET = 0 CLR = 0 Figure 23. Initialization Rev. A | Page 18 of 28 09630-025 CHANGE FSELECT Data Sheet AD9835 DATA WRITE DEFERRED TRANSFER WRITE WRITE 8 BITS TO DEFER REGISTER DIRECT TRANSFER WRITE WRITE PRESENT 8 BITS AND 8 BITS IN DEFER REGISTER TO DATA REGISTER CHANGE 16 BITS WRITE ANOTHER WORD TO THIS YES REGISTER? YES NO CHANGE 8 BITS ONLY 09630-026 NO WRITE A WORD TO ANOTHER REGISTER Figure 24. Data Writes SELECT DATA SOURCES NO YES SELSRC = 0 SET PINS SET FSELECT SET PSEL0 SET PSEL1 SELSRC = 1 FREQUENCY/PHASE REGISTER WRITE SET FSELECT SET PSEL0 SET PSEL1 Figure 25. Selecting Data Sources Rev. A | Page 19 of 28 09630-027 FSELECT/PSEL PINS BEING USED? AD9835 Data Sheet APPLICATIONS INFORMATION The AD9835 has four phase registers; this enables the part to perform PSK. With phase shift keying, the carrier frequency is phase shifted, the phase being altered by an amount that is related to the bit stream being input to the modulator. The presence of four shift registers eases the interaction needed between the DSP and the AD9835. The AD9835 is also suitable for signal generator applications. With its low current consumption, the part is suitable for applications in which it can be used as a local oscillator. GROUNDING AND LAYOUT The printed circuit board that houses the AD9835 should be designed so that the analog and digital sections are separated and confined to certain areas of the board. This facilitates the use of ground planes which can be separated easily. A minimum etch technique is generally best for ground planes as it gives the best shielding. Digital and analog ground planes should only be joined in one place. If the AD9835 is the only device requiring an AGND to DGND connection, then the ground planes should be connected at the AGND and DGND pins of the AD9835. If the AD9835 is in a system where multiple devices require AGND to DGND connections, the connection should be made at one point only, a star ground point that should be established as close as possible to the AD9835. Avoid running digital lines under the device as these will couple noise onto the die. The analog ground plane should be allowed to run under the AD9835 to avoid noise coupling. The power supply lines to the AD9835 should use as large a track as is possible to provide low impedance paths and reduce the effects of glitches on the power supply line. Fast switching signals such as clocks should be shielded with digital ground to avoid radiating noise to other sections of the board. Avoid crossover of digital and analog signals. Traces on opposite sides of the board should run at right angles to each other. This will reduce the effects of feedthrough through the board. A microstrip technique is by far the best but is not always possible with a double-sided board. In this technique, the component side of the board is dedicated to ground planes while signals are placed on the other side. Good decoupling is important. The analog and digital supplies to the AD9835 are independent and separately pinned out to minimize coupling between analog and digital sections of the device. All analog and digital supplies should be decoupled to AGND and DGND respectively with 0.1 mF ceramic capacitors in parallel with 10 mF tantalum capacitors. To achieve the best from the decoupling capacitors, they should be placed as close as possible to the device, ideally right up against the device. In systems where a common supply is used to drive both the AVDD and DVDD of the AD9835, it is recommended that the system’s AVDD supply be used. This supply should have the recommended analog supply decoupling between the AVDD pins of the AD9835 and AGND and the recommended digital supply decoupling capacitors between the DVDD pins and DGND. INTERFACING THE AD9835 TO MICROPROCESSORS The AD9835 has a standard serial interface that allows the part to interface directly with several microprocessors. The device uses an external serial clock to write the data/control information into the device. The serial clock can have a frequency of 20 MHz maximum. The serial clock can be continuous or it can idle high or low between write operations. When data/ control information is being written to the AD9835, FSYNC is taken low and held low while the 16 bits of data are being written into the AD9835. The FSYNC signal frames the 16 bits of information being loaded into the AD9835. AD9835-TO-ADSP-21XX INTERFACE Figure 26 shows the serial interface between the AD9835 and the ADSP-21xx. The ADSP-21xx should be set up to operate in the SPORT Transmit Alternate Framing Mode (TFSW = 1). The ADSP-21xx is programmed through the SPORT control register and should be configured as follows: Internal clock operation (ISCLK = 1), Active low framing (INVTFS = 1), 16-bit word length (SLEN = 15), Internal frame sync signal (ITFS = 1), Generate a frame sync for each write operation (TFSR = 1). Transmission is initiated by writing a word to the Tx register after the SPORT has been enabled. The data is clocked out on each rising edge of the serial clock and clocked into the AD9835 on the SCLK falling edge. Rev. A | Page 20 of 28 ADSP-2101/ ADSP-2103* AD9835* TFS FSYNC DT SDATA SCLK SCLK *ADDITIONAL PINS OMITTED FOR CLARITY. 09630-028 The AD9835 contains functions that make it suitable for modulation applications. The part can be used to perform simple modulation such as FSK. More complex modulation schemes such as GMSK and QPSK can also be implemented using the AD9835. In an FSK application, the two frequency registers of the AD9835 are loaded with different values; one frequency will represent the space frequency while the other will represent the mark frequency. The digital data stream is fed to the FSELECT pin, which will cause the AD9835 to modulate the carrier frequency between the two values. Figure 26. ADSP-2101/ADSP-2103 to AD9835 Interface Data Sheet AD9835 Figure 27 shows the serial interface between the AD9835 and the 68HC11/68L11 microcontroller. The microcontroller is configured as the master by setting bit MSTR in the SPCR to 1 and, this provides a serial clock on SCK while the MOSI output drives the serial data line SDATA. Since the microcontroller does not have a dedicated frame sync pin, the FSYNC signal is derived from a port line (PC7). The setup conditions for correct operation of the interface are as follows: the SCK idles high between write operations (CPOL = 0), data is valid on the SCK falling edge (CPHA = 1). When data is being transmitted to the AD9835, the FSYNC line is taken low (PC7). Serial data from the 68HC11/68L11 is transmitted in 8-bit bytes with only eight falling clock edges occurring in the transmit cycle. Data is transmitted MSB first. In order to load data into the AD9835, PC7 is held low after the first eight bits are transferred and a second serial write operation is performed to the AD9835. Only after the second eight bits have been transferred should FSYNC be taken high again. AD9835* P3.3 FSYNC RxD SDATA TxD SCLK *ADDITIONAL PINS OMITTED FOR CLARITY. FSYNC MOSI SDATA Figure 28. 80C51/80L51 to AD9835 Interface AD9835-TO-DSP56002 INTERFACE Figure 29 shows the interface between the AD9835 and the DSP56002. The DSP56002 is configured for normal mode asynchronous operation with a gated internal clock (SYN = 0, GCK = 1, SCKD = 1). The frame sync pin is generated internally (SC2 = 1), the transfers are 16 bits wide (WL1 = 1, WL0 = 0) and the frame sync signal will frame the 16 bits (FSL = 0). SCLK *ADDITIONAL PINS OMITTED FOR CLARITY. Figure 27. 68HC11/68L11-to-AD9835 Interface AD9835-TO-80C51/80L51 INTERFACE Figure 26 shows the serial interface between the AD9835 and the 80C51/80L51 microcontroller. The microcontroller is operated in Mode 0 so that TXD of the 80C51/80L51 drives SCLK of the AD9835 while RXD drives the serial data line SDATA. The FSYNC signal is again derived from a bit programmable pin on the port (P3.3 being used in the diagram). When data is to be transmitted to the AAD9835, P3.3 is taken low. The 80C51/80L51 transmits data in 8-bit bytes thus, only eight falling SCLK edges occur in each cycle. The frame sync signal is available on pin SC2 but, it needs to be inverted before being applied to the AD9835. The interface to the DSP56000/DSP56001 is similar to that of the DSP56002. DSP56002* AD9835* SC2 FSYNC STD SDATA SCK SCLK *ADDITIONAL PINS OMITTED FOR CLARITY. Figure 29. AD9835-to-DSP56002 Interface Rev. A | Page 21 of 28 09630-031 PC7 SCK 80C51/80L51* AD9835* 09630-029 68HC11/68L11* To load the remaining eight bits to the AD9835, P3.3 is held low after the first eight bits have been transmitted and a second write operation is initiated to transmit the second byte of data. P3.3 is taken high following the completion of the second write operation. SCLK should idle high between the two write operations. The 80C51/ 80L51 outputs the serial data in a format which has the LSB first. The AD9835 accepts the MSB first (the 4 MSBs being the control information, the next 4 bits being the address while the 8 LSBs contain the data when writing to a destination register). Therefore, the transmit routine of the 80C51/80L51 must take this into account and rearrange the bits so that the MSB is output first. 09630-030 AD9835-TO-68HC11/68L11 INTERFACE AD9835 Data Sheet EVALUATION BOARD SYSTEM DEMONSTRATION PLATFORM The system demonstration platform (SDP) is a hardware and software evaluation tool for use in conjunction with product evaluation boards. The SDP board is based on the Blackfin® BF527 processor with USB connectivity to the PC through a USB 2.0 high speed port. Note that the SDP board is sold separately from the AD9835 evaluation board. AD9835 TO SPORT INTERFACE 09630-035 The Analog Devices SDP board has a SPORT serial port that is used to control the serial inputs to the AD9835. The connections are shown in Figure 30. AD9835 SPORT_TSCLK SPORT_DTO Figure 31. AD9835 Evaluation Software FSYNC The DDS evaluation kit includes a populated, tested AD9835 PCB. Software is available with the evaluation board that allows the user to easily program the AD9835. The schematics and layout of the AD9835 evaluation board are shown in Figure 32 through Figure 36. The software runs on any IBM-compatible PC that has Microsoft® Windows® 95, Windows 98, Windows ME, Windows 2000 NT®, or Windows 7 installed. SCLK SDATA ADSP-BF527 09630-039 SPORT_TFS Figure 30. SDP to AD9835 Interface The AD9835 evaluation board allows designers to evaluate the high performance AD9835 DDS modulator with a minimum of effort. The GUI interface for the AD9835 evaluation board is shown in Figure 31. Additional details can be found in the EVAL-AD9835SDZ data sheet (UG-319) that is available on the software CD and on the AD9835 product page. XO vs. EXTERNAL CLOCK The AD9835 can operate with master clocks up to 50 MHz. A 50 MHz general oscillator is included on the evaluation board. However, this oscillator can be removed and, if required, an external CMOS clock can be connected to the part. Two options for the general oscillator are: • AEL 301 series crystals oscillators (AEL Crystals, Ltd.) • SG-310SCN oscillators (Epson Toyocom Corporation) POWER SUPPLY Power to the AD9835 evaluation board can be provided from a USB connector or externally through pin connections. The power leads should be twisted to reduce ground loops. Rev. A | Page 22 of 28 Data Sheet AD9835 EVALUATION BOARD SCHEMATICS AND LAYOUT Figure 32. AD9835 Schematic, Part A Rev. A | Page 23 of 28 AD9835 Data Sheet 09630-034 Figure 33. AD9835 Schematic, Part B Rev. A | Page 24 of 28 AD9835 09630-036 Data Sheet 09630-037 Figure 34. Component Side View Layer 1 09630-038 Figure 35. Component Side View Silkscreen Figure 36. Component Side View Layer 2, Solder Side Rev. A | Page 25 of 28 AD9835 Data Sheet ORDERING INFORMATION BILL OF MATERIALS Table 14. Reference Designator C1, C3, C5, C6, C111, C12, C131 Description 0.1 μF, ±10%, 50 V, X7R, ceramic capacitor Manufacturer Murata Part Number GRM188R71H104KA93D C7 C2, C4 C8,C9 C10 CLK 1 , FSEL1, IOUT, PSEL11, REFIN, PSEL01 FSYNC, IOUT_, MCLK , SCLK, SDATA G2 J1 J2, J3 LK3, LK5, LK6 LK1 R71, R81, R91 R121 R14 R15 R17,R18 R1, R21, R3, R41, R61, R5, R111, R10,R162 R13 U4 U1 U5 Y2 0.01 μF, ±10%, 10 V, 0603, X5R, capacitor 10 μF, ±10%,10 V, SMD tantalum capacitor 1 μF, ±10%,10 V,Y5V, 0603, ceramic capacitor 0.1 μF, ±10%, 16 V, X7R, 0603, capacitor Straight PCB mount SMB jack, 50 Ω Kemet AVX Yageo Multicomp Tyco C0603C103K5RACTU TAJA106K010R CC0603ZRY5V6BB105 B0603R104KCT 1-1337482-0 Red test point Vero 20-313137 Copper short 120-way connector, 0.6 mm pitch receptacle 2-pin terminal block (5 mm pitch) 3-pin SIL header and shorting link 2-pin SIL header and shorting link 10 kΩ, ±1%, 0603, SMD resistor 50 Ω, ±1%, 0603, SMD resistor 3.9 kΩ, ±1%, SMD resistor 300 Ω, ±1%, SMD resistor 100 KΩ, ±1%, SMD resistor 0 Ω, ±1%, 0603, SMD resistor Not applicable HRS (Hirose) Campden Harwin Harwin Multicomp Multicomp Multicomp Multicomp Multicomp Multicomp Not applicable FX8-120S-SV(21) CTB5000/2 M20-9990345 and M7567-05 M20-9990246 MC 0.063W 0603 10K MC 0.063W 0603 50r MC 0.063W 0603 6K8 MC 0.063W 0603 200r MC 0.063W 0603 1% 100K MC 0.063W 0603 0r 330 kΩ, ±5%, SMD resistor 200 mW power 5 V, 50 MHz complete DDS 32 K I2C serial EEPROM 8-lead MSOP 3.3 V linear regulator 50 MHz, 3 mm × 2 mm SMD clock oscillator Multicomp Analog Devices Micro Chip Analog Devices AEL Crystals MC 0.063W 0603 330KR AD9835BRUZ 24LC32A-I/MS ADP3301ARZ-3.3 AEL301 series 1 Do not install. DNP 2 Rev. A | Page 26 of 28 Data Sheet AD9835 OUTLINE DIMENSIONS 5.10 5.00 4.90 16 9 4.50 4.40 4.30 6.40 BSC 1 8 PIN 1 1.20 MAX 0.15 0.05 0.65 BSC 0.30 0.19 COPLANARITY 0.10 0.20 0.09 SEATING PLANE 8° 0° 0.75 0.60 0.45 COMPLIANT TO JEDEC STANDARDS MO-153-AB Figure 37. 16-Lead Thin Shrink Small Outline Package (TSSOP) (RU-16) Dimensions shown in millimeters ORDERING GUIDE Model 1, 2 AD9835BRU AD9835BRU-REEL AD9835BRU-REEL7 AD9835BRUZ AD9835BRUZ-REEL AD9835BRUZ-REEL7 EVAL-AD9835SDZ 1 2 Temperature Range −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C −40°C to +85°C Package Description 16-Lead Thin Shrink Small Outline Package [TSSOP] 16-Lead Thin Shrink Small Outline Package [TSSOP] 16-Lead Thin Shrink Small Outline Package [TSSOP] 16-Lead Thin Shrink Small Outline Package [TSSOP] 16-Lead Thin Shrink Small Outline Package [TSSOP] 16-Lead Thin Shrink Small Outline Package [TSSOP] Evaluation Board (To Be Used in Conjunction with an SDP Board) Z = RoHS Compliant Part. For the EVAL-AD9835SDZ, an SDP board is required. Rev. A | Page 27 of 28 Package Option RU-16 RU-16 RU-16 RU-16 RU-16 RU-16 AD9835 Data Sheet NOTES ©1998–2011 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D09630-0-9/11(A) Rev. A | Page 28 of 28