MPS MP2212

MP2212
16V, 3A, 600kHz Synchronous
Step-Down Converter
The Future of Analog IC Technology
DESCRIPTION
FEATURES
The MP2212 is an internally compensated
600kHz fixed frequency PWM synchronous
step-down regulator. With a 3V to 6V bias
supply (VCC), MP2212 operates from a 3V to
16V input and generates an adjustable output
voltage from 0.8V to 0.9xVIN at up to 3A load
current.
The MP2212 integrates an 80mΩ high-side
switch and an 80mΩ synchronous rectifier for
high efficiency without an external Schottky
diode. With peak current mode control and
internal compensation, it is stable with a
ceramic output capacitor and a small inductor.
Fault protection includes hiccup short-circuit
protection, cycle-by-cycle current limiting and
thermal shutdown. Other features include
frequency synchronization input and internal
soft-start.
The MP2212 is available in small 3mm x 3mm
10-lead QFN and 8-lead SOIC with exposed
pad packages.
•
•
•
•
•
•
•
•
•
•
•
•
•
3A Output Current
Input Supply Range: 3V to 16V
80mΩ Internal Power MOSFET Switches
All Ceramic Output Capacitors Design
Up to 95% Efficiency
600kHz Fixed Switching Frequency
Adjustable Output from 0.8V to 0.9xVIN
Internal Soft-Start
Frequency Synchronization Input
Thermal Shutdown
Cycle-by-Cycle Current Limiting
Hiccup Short Circuit Protection
10-lead, 3mm x 3mm QFN Package and 8lead SOICE package
APPLICATIONS
•
•
•
•
µP/ASIC/DSP/FPGA Core and I/O Supplies
Printers and LCD TVs
Network and Telecom Equipment
Point of Load Regulators
All MPS parts are lead-free and adhere to the RoHS directive. For MPS green
status, please visit MPS website under Quality Assurance. “MPS” and “The
Future of Analog IC Technology” are Trademarks of Monolithic Power Systems,
Inc.
TYPICAL APPLICATION
Efficiency vs.
Load Current
100
VIN
3V to 16V
4, 7
IN
6
90
BS
SW
VCC
3, 8
MP2212
OFF ON
10
EN/SYNC
GND
2, 9
FB
1
C6
560PF
VOUT
1.8V / 3A
EFFICIENCY (%)
VCC
3V to 6V
95
5
VIN=5V
VIN=12V
85
80
75
70
65
60
55
MP2212 Rev. 1.01
2/22/2012
VOUT=3.3V
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5
LOAD CURRENT (A)
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1
MP2212 – 16V, 3A, 600kHz SYNCHRONOUS STEP-DOWN CONVERTER
ORDERING INFORMATION
Part Number
MP2212DQ*
MP2212DN**
Package
QFN10 (3mm x 3mm)
SOIC8E
Top Marking
Z7
MP2212DN
Free Air Temperature (TA)
-40°C to +85°C
-40°C to +85°C
* For Tape & Reel, add suffix –Z (e.g. MP2212DQ–Z);
For RoHS compliant packaging, add suffix –LF (e.g. MP2212DQ–LF–Z)
** For Tape & Reel, add suffix –Z (e.g. MP2212DN–Z);
For RoHS compliant packaging, add suffix –LF (e.g. MP2212DN–LF–Z)
PACKAGE REFERENCE
TOP VIEW
FB
1
8
EN/SYNC
GND
2
7
SW
IN
3
6
SW
BS
4
5
VCC
EXPOSED PAD
ON BACKSIDE
CONNECT TO GND
QFN10 (3mm x 3mm)
SOIC8E
ABSOLUTE MAXIMUM RATINGS (1)
IN to GND ..................................... -0.3V to +18V
SW to GND ........................... -0.3V to VIN + 0.3V
.............................-2.5V to VIN + 2.5V for < 50ns
FB, EN/SYNC, VCC to GND........... -0.3V to +6.5V
BS to SW ..................................... -0.3V to +6.5V
(2)
Continuous Power Dissipation
(TA = +25°C)
QFN10 (3mm x 3mm) ............... .......... ..... 2.5W
SOIC8E..................................... .......... ..... 2.5W
Junction Temperature ...............................150°C
Lead Temperature ....................................260°C
Storage Temperature............... -65°C to +150°C
Recommended Operating Conditions
(3)
Thermal Resistance
(4)
θJA
θJC
QFN10 (3mm x 3mm) .............50 ...... 12 ... °C/W
SOIC8E ...................................50 ...... 10 ... °C/W
Notes:
1) Exceeding these ratings may damage the device.
2) The maximum allowable power dissipation is a function of the
maximum junction temperature TJ(MAX), the junction-toambient thermal resistance θJA, and the ambient temperature
TA. The maximum allowable continuous power dissipation at
any ambient temperature is calculated by PD(MAX)=(TJ(MAX)TA)/ θJA. Exceeding the maximum allowable power dissipation
will cause excessive die temperature, and the regulator will go
into thermal shutdown. Internal thermal shutdown circuitry
protects the device from permanent damage.
3) The device is not guaranteed to function outside of its
operating conditions.
4) Measured on JESD51-7 4-layer PCB.
Supply Voltage VIN ..............................3V to 16V
Bias Voltage VCC ...................................3V to 6V
EN/SYNC Voltage...................no more than VCC
Output Voltage VOUT ...................0.8V to 0.9x VIN
Maximum Junction Temp. (TJ) ................+125°C
MP2212 Rev. 1.01
2/22/2012
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2
MP2212 – 16V, 3A, 600kHz SYNCHRONOUS STEP-DOWN CONVERTER
ELECTRICAL CHARACTERISTICS (5)
VCC = 3.6V, VIN=12V, TA = +25°C, unless otherwise noted.
Parameters
Condition
VEN = VCC
VFB = 0.85V
VCC Shutdown Current
VEN = 0V, VCC= 6V
VCC Under Voltage Lockout Threshold Rising Edge
VCC Under Voltage Lockout
Hysteresis
IN Shutdown Current
VEN = 0V
IN Under Voltage Lockout Threshold,
Rising Edge
IN Under Voltage Lockout Hysteresis
TA = +25°C
Regulated FB Voltage
-40°C ≤ TA ≤ +85°C
FB Input Current
VFB = 0.85V
EN High Threshold
-40°C ≤ TA ≤ +85°C
EN Low Threshold
-40°C ≤ TA ≤ +85°C
Internal Soft-Start Time
High-Side Switch On-Resistance
ISW = 300mA
Low-Side Switch On-Resistance
ISW = –300mA
VEN = 0V; VIN = 12V
SW Leakage Current
VSW = 0V or 12V
BS Under Voltage Lockout Threshold
High-Side Switch Current Limit
Sourcing
Low-Side Switch Current Limit
Sinking
Oscillator Frequency
Synch Frequency
Minimum On Time
Maximum Duty Cycle
Thermal Shutdown Threshold
Hysteresis = 20°C
Min
VCC Supply Current
Typ
μA
1
2.8
μA
V
3
200
mV
4
μA
300
0.800
2.95
0.820
0.828
50
0.4
120
80
80
-10
450
0.5
Units
750
2.85
0.780
0.772
-50
1.6
Max
1.8
6
3
600
50
90
150
V
mV
V
V
nA
V
V
µs
mΩ
mΩ
10
μA
750
2
V
A
A
kHz
MHz
ns
%
°C
Note:
5) Production test at +25°C. Specifications over the temperature range are guaranteed by design and characterization.
MP2212 Rev. 1.01
2/22/2012
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© 2012 MPS. All Rights Reserved.
3
MP2212 – 16V, 3A, 600kHz SYNCHRONOUS STEP-DOWN CONVERTER
PIN FUNCTIONS
8-SOICE
Pin #
10-QFN
Pin #
Name
5
6
VCC
3
4, 7
IN
6，7
3, 8
SW
2
2, 9
GND,
Exposed
Pad
4
5
BS
1
1
FB
8
10
EN/SYNC
MP2212 Rev. 1.01
2/22/2012
Description
Bias Supply. This supplies power to both the internal control circuit and the
gate drivers. A decoupling capacitor to ground is required close to this pin.
Input Supply. This supplies power to the high side switch. A decoupling
capacitor to ground is required close to this pin to reduce switching spikes.
Switch Node Connection to the Inductor. These pins connect to the internal
high and low-side power MOSFET switches. All SW pins must be
connected together externally.
Ground. Connect these pins with larger copper areas to the negative
terminals of the input and output capacitors. Connect Exposed Pad and
GND pin to the same plane.
Bootstrap. A capacitor between this pin and SW provides a floating supply
for the high-side gate driver.
Feedback. This is the input to the error amplifier. An external resistive
divider connected between the output and GND is compared to the internal
0.8V reference to set the regulation voltage.
Enable and Frequency Synchronization Input Pin. Forcing this pin below
0.4V shuts down the part. Forcing this pin above 1.6V but no more than VCC
turns on the part. Attach to VCC with a 100kΩ pull up resistor for automatic
start-up.
Applying a 500kHz to 2MHz clock signal to this pin synchronizes the internal
oscillator frequency to the external source. Don’t apply a voltage more than
VCC to this pin.
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4
MP2212 – 16V, 3A, 600kHz SYNCHRONOUS STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS
VCC = 5V, VOUT = 1.8V, TA = +25ºC, unless otherwise noted.
MP2212 Rev. 1.01
2/22/2012
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© 2012 MPS. All Rights Reserved.
5
MP2212 – 16V, 3A, 600kHz SYNCHRONOUS STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS
VCC = 5V, VOUT = 1.8V, TA = +25ºC, unless otherwise noted (continued)
Switching Waveform
VIN=12V, IOUT=3A
VOUT AC
Coupled
10mV/div
VOUT/AC
50mV/div
VSW
5V/div
IINDUCTOR
2A/div
VOUT/AC
50mV/div
IINDUCTOR
2A/div
IINDUCTOR
2A/div
MP2212 Rev. 1.01
2/22/2012
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6
MP2212 – 16V, 3A, 600kHz SYNCHRONOUS STEP-DOWN CONVERTER
FUNCTIONAL BLOCK DIAGRAM
VCC
UVLO
UVLO
IN
EN
IN
BS
EN
EN/SYNC
LOGIC
EXCLK
LOGIC
CLK
OSC
+
--
EN/SYNC
PWM
CURRENT
COMPARATOR
SW
SLOPE
SW
0.5pF
1.2 MEG 17pF
FB
0.8V
-+
+
COMP
SLOPE
COMPENSATION
AND PEAK
CURRENT LIMIT
SOFT
-START
GND
GND
Figure 1—Functional Block Diagram
MP2212 Rev. 1.01
2/22/2012
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7
MP2212 – 16V, 3A, 600kHz SYNCHRONOUS STEP-DOWN CONVERTER
FUNCTIONAL DESCRIPTION
PWM Control
The MP2212 is a constant frequency peakcurrent-mode control PWM switching regulator.
Refer to the functional block diagram. The high
side N-Channel DMOS power switch turns on at
the beginning of each clock cycle. The current in
the inductor increases until the PWM current
comparator trips to turn off the high side DMOS
switch. The peak inductor current at which the
current comparator shuts off the high side power
switch is controlled by the COMP voltage at the
output of feedback error amplifier. The
transconductance from the COMP voltage to the
output current is set at 11.25A/V.
This current-mode control greatly simplifies the
feedback compensation design by approximating
the switching converter as a single-pole system.
Only Type II compensation network is needed,
which is integrated into the MP2212. The internal
compensation in the MP2212 simplifies the
compensation
design,
minimizes
external
component counts. The loop bandwidth can be
adjusted by adding a feed-forward capacitor
which is in parallel with the feedback resistor from
output to FB pin.
Enable and Frequency Synchronization
(EN/SYNC PIN)
This is a dual function input pin. Forcing this pin
below 0.4V for longer than 4μs shuts down the
part; forcing this pin above 1.6V for longer than
4µs turns on the part. Applying a 500kHz to 2MHz
clock signal to this pin also synchronizes the
internal oscillator frequency to the external clock.
When the external clock is used, the part turns on
after detecting the first few clocks regardless of
duty cycles. If any ON or OFF period of the clock
is longer than 4µs, the signal will be intercepted
as an enable input and disables the
synchronization. For automatic startup, connect
this pin to VCC with a pull-up resistor. Don’t apply
a voltage more than VCC to this pin.
Soft-Start and Output Pre-Bias Startup
When the soft-start period starts, an internal
current source begins charging an internal softstart capacitor. During soft-start, the voltage on
the soft-start capacitor is connected to the noninverting input of the error amplifier. The soft-start
period lasts until the voltage on the soft-start
capacitor exceeds the reference voltage of 0.8V.
MP2212 Rev. 1.01
2/22/2012
At this point the reference voltage takes over at
the non-inverting error amplifier input. The softstart time is internally set at 120µs. If the output of
the MP2212 is pre-biased to a certain voltage
during startup, the IC will disable the switching of
both high-side and low-side switches until the
voltage on the internal soft-start capacitor
exceeds the sensed output voltage at the FB pin.
Over Current Protection
The MP2212 offers cycle-to-cycle current limiting
for both high-side and low-side switches. The
high-side current limit is relatively constant
regardless of duty cycles. When the output is
shorted to ground, causing the output voltage to
drop below 50% of its nominal output, the IC is
shut down momentarily and begins discharging
the soft start capacitor. It will restart with a full
soft-start when the soft-start capacitor is fully
discharged. This hiccup process is repeated until
the fault is removed.
Bootstrap (BST PIN)
The gate driver for the high-side N-channel
DMOS power switch is supplied by a bootstrap
capacitor connected between the BS and SW pins.
When the low-side switch is on, the capacitor is
charged through an internal boost diode. When
the high-side switch is on and the low-side switch
turns off, the voltage on the bootstrap capacitor is
boosted above the input voltage and the internal
bootstrap diode prevents the capacitor from
discharging.
Input UVLO
Both VCC and IN pins have input UVLO detection.
Until both VCC and IN voltage exceed under
voltage lockout threshold, the parts remain in
shutdown condition. There are also under voltage
lockout hysesteres at both VCC and IN pins.
VCC Power Supply
VCC is the power supply of both the internal
control circuit and the gate drivers.
Generally, the VCC power supply could be
provided directly by a proper power rail or
generated from other VCC generation circuits. For
instance, Figure6 shows a typical VCC generation
circuit for VOUT=5V application.
It is noteworthy that the voltage applied on the
VCC pin should never be higher than 6V.
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8
MP2212 – 16V, 3A, 600kHz SYNCHRONOUS STEP-DOWN CONVERTER
APPLICATION INFORMATION
Setting the Output Voltage
The external resistor divider sets the output
voltage (see Figure 1). For typical applications,
choose R2 to be 10k Ω. R1 is then given by:
R1 = R2 × (
VOUT
− 1)
0.8V
is recommended for most applications. For best
efficiency, the inductor DC resistance shall be
<10mΩ. See Table 2 for recommended inductors
and manufacturers. For most designs, the
inductance value can be derived from the
following equation:
L=
Table 1—Resistor Selection vs. Output
Voltage Setting
VOUT (V) R1 (kΩ) R2 (kΩ)
1.2
1.5
1.8
2.5
3.3
5
8.75
12.5
21.25
31.25
10
10
10
10
10
L (μH)
COUT
(ceramic)
1μH-4.7μH
1μH-4.7μH
1μH-4.7μH
1μH-4.7μH
1μH-4.7μH
47μF
47μF
47μF
47μF
47μF
VOUT x(VIN − VOUT )
VIN xΔIL xfOSC
where ∆IL is Inductor Ripple Current. Choose
inductor ripple current approximately 30% of the
maximum load current, 3A.The maximum
inductor peak current is:
IL(MAX) = ILOAD +
ΔIL
2
Under light load conditions, larger inductance is
recommended for improved efficiency
Feed-forward capacitor
For applications with VOUT other than 0.8V,
adding a feed-forward capacitor in parallel with
the feedback resistor from output to FB pin can
increase loop bandwidth, help reducing transient
overshoot and undershoot and startup overshoot
if any. Figure 2 shows typical 5 VOUT application
circuit with a 390pF feed-forward capacitor.
Selecting the Inductor
A 1µH to 4.7µH inductor with DC current rating at
least 25% higher than the maximum load current
Input Capacitor Selection
The input capacitor reduces the surge current
drawn from the input and switching noise from
the device. The input capacitor impedance at the
switching frequency shall be less than input
source impedance to prevent high frequency
switching current passing to the input. Ceramic
capacitors with X5R or X7R dielectrics are highly
recommended because of their low ESR and
small temperature coefficients. For most
applications, a 47µF capacitor is sufficient.
Table 2—Suggested Surface Mount Inductors
Manufacturer
Part Number
Inductance
(μH)
Max
DCR
(mΩ)
Current
Rating
(A)
Dimensions
L x W x H (mm3)
FDA1055-3R3M
3.3
7.3
11.7
10.8x11.6x5.5
744314330
3.3
9.6
8
7x6.9x5
ULF100457-3R3N6R9
3.3
11.6
7.5
10x9.7x4.5
TOKO
Wurth Electronics
TDK
MP2212 Rev. 1.01
2/22/2012
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9
MP2212 – 16V, 3A, 600kHz SYNCHRONOUS STEP-DOWN CONVERTER
Output Capacitor Selection
PCB Layout Guide
The output capacitor keeps output voltage ripple
small and ensures regulation loop stable. The
output capacitor impedance shall be low at the
switching frequency. Ceramic capacitors with
X5R or X7R dielectrics are recommended. If
electrolytic capacitor is used, pay attention to
output ripple voltage, extra heating, and the
selection of feedback resistor R1 (refer to “Output
Voltage Setting” section) due to large ESR of
electrolytic capacitor. The output ripple ∆VOUT is
approximately:
PCB layout is very important to achieve stable
operation. It is highly recommended to duplicate
EVB layout for optimum performance. If change
is necessary, please follow these guidelines as
follows. Here, the typical application circuit is
taken as an example to illustrate the key layout
rules should be followed.
ΔVOUT ≤
VOUT x(VIN − VOUT )
1
x(ESR +
)
VIN xfOSC xL
8xfOSC xC3
The output capacitance is recommended to be
less than 100μF.
External Schottky Diode
For this part, an external schottky diode is
recommended to be placed close to "SW" and
"GND" pins, especially when the output current is
larger than 2A.
With the external schottky diode, the voltage
spike and negative kick on "SW" pin can be
minimized; moreover, the conversion efficiency
can also be improved a little.
For the external schottky diode selection, it's
noteworthy that the maximum reverse voltage
rating of the external diode should be larger than
the maximum input voltage. As for the current
rating of this diode, 0.5A rating should be
sufficient.
Top Layer
MP2212 Rev. 1.01
2/22/2012
1) For MP2212DQ, a PCB layout with more than
(or) four layers is recommended.
2) The high current paths (GND, IN and SW)
should be placed very close to the device with
short, direct and wide traces.
3) For MP2212DQ, two input ceramic capacitors
(2 x (10μF~22μF)) are strongly recommended to
be placed on both sides of the MP2212DQ
package and keep them as close as possible to
the “IN” and “GND” pins.
For MP2212DN, an input ceramic capacitor
should be placed as close as possible to “IN” and
“GND” pins.
4) A RC low pass filter is recommended for VCC
supply. The VCC decoupling capacitor must be
placed as close as possible to “VCC” pin and
“GND” pin.
5) The external feedback resistors shall be
placed next to the FB pin. Keep the FB trace as
short as possible.
6) Keep the switching node SW short and away
from the feedback network.
Inner Layer1
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10
MP2212 – 16V, 3A, 600kHz SYNCHRONOUS STEP-DOWN CONVERTER
Bottom Layer
Inner Layer2
Figure2―Recommended PCB Layout of MP2212DQ
Top Layer
Bottom Layer
Figure 3―Recommended PCB Layout of MP2212DN
TYPICAL APPLICATION CIRCUITS
VIN
4, 7
VCC
5
IN
6
C3
100nF
BS
SW
VCC
3, 8
VOUT
5V / 3A
MP2212
OFF ON
10
EN/SYNC
GND
2, 9
FB
1
C5
390pF
Figure 4—5V VOUT Application Circuit with a 390pF Feed-forward Capacitor
MP2212 Rev. 1.01
2/22/2012
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11
MP2212 – 16V, 3A, 600kHz SYNCHRONOUS STEP-DOWN CONVERTER
Vin
3V to 16V
Vcc
3V to 6V
R4
10
C1
22
C2
22
4,7
6
C4
1
C5
100nF
5
IN
BS
SW
Vcc
3,8
R3
100k
EN/SYNC
GND
FB
Vout
1.8V/3A
D1
B0530 C6 560pF
MP2212DQ
10
L1
3.3
1
C3
47
R1
R2
10k 12.4k
2,9
Figure 5—Typical Application Circuit of MP2212DQ
D2
B0530
Vin
9~16V
C1
22
R4
10k
C2
22
4,7
6
Z1
4.7V
Q1
MMBT3904
5
IN
BS
SW
Vcc
C4
1
C5
100nF
3,8
MP2212DQ
10 EN/SYNC
GND
2,9
R3
100k
L1
3.3
D1
B0530
FB 1
Vout
5V/3A
R1
10k
C3
47
R2
1.91k
Figure6―MP2212DQ with A VCC Generation Circuit
Vin
3V to 16V
Vcc
3V to 6V
C1
22
3
5
R3
10
C3
1
R4
100k
C4
100nF
4
IN
BS
Vcc
SW
6,7
D1
B0530 C5 560pF
MP2212DN
8
EN/SYNC
GND
2
L1
3.3
Vout
1.8V/3A
1
FB
R1
R2 12.4k
10k
C2
47
Figure 7 ―Typical Application Circuit of MP2212DN
MP2212 Rev. 1.01
2/22/2012
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12
MP2212 – 16V, 3A, 600kHz SYNCHRONOUS STEP-DOWN CONVERTER
PACKAGE INFORMATION
QFN10 (3mm x 3mm)
2.90
3.10
0.30
0.50
PIN 1 ID
MARKING
0.18
0.30
2.90
3.10
PIN 1 ID
INDEX AREA
1.45
1.75
PIN 1 ID
SEE DETAIL A
10
1
2.25
2.55
0.50
BSC
5
6
TOP VIEW
BOTTOM VIEW
PIN 1 ID OPTION A
R0.20 TYP.
PIN 1 ID OPTION B
R0.20 TYP.
0.80
1.00
0.20 REF
0.00
0.05
SIDE VIEW
DETAIL A
NOTE:
2.90
0.70
1) ALL DIMENSIONS ARE IN MILLIMETERS.
2) EXPOSED PADDLE SIZE DOES NOT INCLUDE MOLD FLASH.
3) LEAD COPLANARITY SHALL BE 0.10 MILLIMETER MAX.
4) DRAWING CONFORMS TO JEDEC MO-229, VARIATION VEED-5.
5) DRAWING IS NOT TO SCALE.
1.70
0.25
2.50
0.50
RECOMMENDED LAND PATTERN
MP2212 Rev. 1.01
2/22/2012
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13
MP2212 – 16V, 3A, 600kHz SYNCHRONOUS STEP-DOWN CONVERTER
SOIC8E (EXPOSED PAD)
0.189(4.80)
0.197(5.00)
0.124(3.15)
0.136(3.45)
8
5
0.150(3.80)
0.157(4.00)
PIN 1 ID
1
0.228(5.80)
0.244(6.20)
0.089(2.26)
0.101(2.56)
4
TOP VIEW
BOTTOM VIEW
SEE DETAIL "A"
0.051(1.30)
0.067(1.70)
SEATING PLANE
0.000(0.00)
0.006(0.15)
0.013(0.33)
0.020(0.51)
0.0075(0.19)
0.0098(0.25)
SIDE VIEW
0.050(1.27)
BSC
FRONT VIEW
0.010(0.25)
x 45o
0.020(0.50)
GAUGE PLANE
0.010(0.25) BSC
0.050(1.27)
0.024(0.61)
0o-8o
0.016(0.41)
0.050(1.27)
0.063(1.60)
DETAIL "A"
0.103(2.62)
0.138(3.51)
RECOMMENDED LAND PATTERN
0.213(5.40)
NOTE:
1) CONTROL DIMENSION IS IN INCHES. DIMENSION IN
BRACKET IS IN MILLIMETERS.
2) PACKAGE LENGTH DOES NOT INCLUDE MOLD FLASH,
PROTRUSIONS OR GATE BURRS.
3) PACKAGE WIDTH DOES NOT INCLUDE INTERLEAD FLASH
OR PROTRUSIONS.
4) LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING)
SHALL BE 0.004" INCHES MAX.
5) DRAWING CONFORMS TO JEDEC MS-012, VARIATION BA.
6) DRAWING IS NOT TO SCALE.
NOTICE: The information in this document is subject to change without notice. Users should warrant and guarantee that third
party Intellectual Property rights are not infringed upon when integrating MPS products into any application. MPS will not
assume any legal responsibility for any said applications.
MP2212 Rev. 1.01
2/22/2012
www.MonolithicPower.com
MPS Proprietary Information. Patent Protected. Unauthorized Photocopy and Duplication Prohibited.
© 2012 MPS. All Rights Reserved.
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