Order this document by UAA2016/D The UAA2016 is designed to drive triacs with the Zero Voltage technique which allows RFI–free power regulation of resistive loads. Operating directly on the AC power line, its main application is the precision regulation of electrical heating systems such as panel heaters or irons. A built–in digital sawtooth waveform permits proportional temperature regulation action over a ±1°C band around the set point. For energy savings there is a programmable temperature reduction function, and for security a sensor failsafe inhibits output pulses when the sensor connection is broken. Preset temperature (i.e. defrost) application is also possible. In applications where high hysteresis is needed, its value can be adjusted up to 5°C around the set point. All these features are implemented with a very low external component count. • Zero Voltage Switch for Triacs, up to 2.0 kW (MAC212A8) • • • • • • • ZERO VOLTAGE SWITCH POWER CONTROLLER SEMICONDUCTOR TECHNICAL DATA 8 1 Direct AC Line Operation P SUFFIX PLASTIC PACKAGE CASE 626 Proportional Regulation of Temperature over a 1°C Band Programmable Temperature Reduction Preset Temperature (i.e. Defrost) Sensor Failsafe 8 Adjustable Hysteresis 1 Low External Component Count D SUFFIX PLASTIC PACKAGE CASE 751 (SO–8) PIN CONNECTIONS Representative Block Diagram 4 Temperature Reduction + + + 4–Bit DAC Hysteresis Adjust Voltage Reference Sampling Full Wave Logic + – Sense Input 8 Sync Hys. Adj. 2 7 VCC Sensor 3 6 Output Temp. Reduc. 4 5 VEE UAA2016 Failsafe 3 Vref 1 6 Pulse Amplifier 7 Internal Reference 1/2 (Top View) Output +VCC Synchronization 2 Supply Voltage 1 ORDERING INFORMATION 11–Bit Counter Device 8 5 UAA2016D Sync VEE UAA2016P Operating Temperature Range TA = – 20° to +85°C Motorola, Inc. 1999 MOTOROLA ANALOG IC DEVICE DATA Package SO–8 Plastic DIP Rev 6 1 UAA2016 MAXIMUM RATINGS (Voltages referenced to Pin 7) Rating Symbol Value Unit ICC 15 mA Non–Repetitive Supply Current (Pulse Width = 1.0 µs) ICCP 200 mA AC Synchronization Current Isync 3.0 mA Pin Voltages VPin 2 VPin 3 VPin 4 VPin 6 0; Vref 0; Vref 0; Vref 0; VEE V Vref Current Sink IPin 1 1.0 mA Output Current (Pin 6) (Pulse Width < 400 µs) IO 150 mA Power Dissipation PD 625 mW RθJA 100 °C/W TA – 20 to + 85 °C Supply Current (IPin 5) Thermal Resistance, Junction–to–Air Operating Temperature Range ELECTRICAL CHARACTERISTICS (TA = 25°C, VEE = –7.0 V, voltages referred to Pin 7, unless otherwise noted.) Characteristic Symbol Min Typ Max — 0.9 1.5 Unit Supply Current (Pins 6, 8 not connected) (TA = – 20° to + 85°C) ICC Stabilized Supply Voltage (Pin 5) VEE –10 – 9.0 – 8.0 V Vref – 6.5 – 5.5 – 4.5 V 90 100 130 — — 10 50 — 100 (ICC = 2.0 mA) Reference Voltage (Pin 1) mA Output Pulse Current (TA = – 20° to + 85°C) (Rout = 60 W, VEE = – 8.0 V) IO Output Leakage Current (Vout = 0 V) IOL Output Pulse Width (TA = – 20° to + 85°C) (Note 1) (Mains = 220 Vrms, Rsync = 220 kΩ) TP Comparator Offset (Note 5) Voff –10 — +10 mV Sensor Input Bias Current IIB — — 0.1 µA Sawtooth Period (Note 2) TS — 40.96 — sec AS 50 70 90 mV 280 350 420 — 10 — 280 350 420 180 — 300 Sawtooth Amplitude (Note 6) Temperature Reduction Voltage (Note 3) (Pin 4 Connected to VCC) VTR Internal Hysteresis Voltage (Pin 2 Not Connected) VIH Additional Hysteresis (Note 4) (Pin 2 Connected to VCC) VH Failsafe Threshold (TA = – 20° to + 85°C) (Note 7) VFSth mA µA µs mV mV mV mV NOTES: 1. Output pulses are centered with respect to zero crossing point. Pulse width is adjusted by the value of Rsync. Refer to application curves. 2. The actual sawtooth period depends on the AC power line frequency. It is exactly 2048 times the corresponding period. For the 50 Hz case it is 40.96 sec. For the 60 Hz case it is 34.13 sec. This is to comply with the European standard, namely that 2.0 kW loads cannot be connected or removed from the line more than once every 30 sec. 3. 350 mV corresponds to 5°C temperature reduction. This is tested at probe using internal test pad. Smaller temperature reduction can be obtained by adding an external resistor between Pin 4 and VCC. Refer to application curves. 4. 350 mV corresponds to a hysteresis of 5°C. This is tested at probe using internal test pad. Smaller additional hysteresis can be obtained by adding an external resistor between Pin 2 and VCC. Refer to application curves. 5. Parameter guaranteed but not tested. Worst case 10 mV corresponds to 0.15°C shift on set point. 6. Measured at probe by internal test pad. 70 mV corresponds to 1°C. Note that the proportional band is independent of the NTC value. 7. At very low temperature the NTC resistor increases quickly. This can cause the sensor input voltage to reach the failsafe threshold, thus inhibiting output pulses; refer to application schematics. The corresponding temperature is the limit at which the circuit works in the typical application. By setting this threshold at 0.05 Vref, the NTC value can increase up to 20 times its nominal value, thus the application works below – 20°C. 2 MOTOROLA ANALOG IC DEVICE DATA UAA2016 Figure 1. Application Schematic S1 S2 RS R1 UAA2016 Failsafe R3 MAC212A8 3 + Sense Input NTC 4 Temp. Red. Sampling Full Wave Logic – + + Pulse Amplifier Output 7 Internal Reference 1/2 + Rout 6 220 Vac R2 Rdef +VCC CF 4–Bit DAC 2 Supply Voltage HysAdj 11–Bit Counter Load Synchronization 1 Vref Sync 8 5 VEE Rsync RS APPLICATION INFORMATION (For simplicity, the LED in series with Rout is omitted in the following calculations.) Triac Choice and Rout Determination Depending on the power in the load, choose the triac that has the lowest peak gate trigger current. This will limit the output current of the UAA2016 and thus its power consumption. Use Figure 4 to determine Rout according to the triac maximum gate current (IGT) and the application low temperature limit. For a 2.0 kW load at 220 Vrms, a good triac choice is the Motorola MAC212A8. Its maximum peak gate trigger current at 25°C is 50 mA. For an application to work down to – 20°C, Rout should be 60 Ω. It is assumed that: IGT(T) = IGT(25°C) exp (–T/125) with T in °C, which applies to the MAC212A8. Output Pulse Width, Rsync The pulse with TP is determined by the triac’s IHold, ILatch together with the load value and working conditions (frequency and voltage): Given the RMS AC voltage and the load power, the load value is: RL = V2rms/POWER MOTOROLA ANALOG IC DEVICE DATA The load current is then: I Load + (Vrms Ǹ2 sin(2pft)–V TM ń ) R L where VTM is the maximum on state voltage of the triac, f is the line frequency. Set ILoad = ILatch for t = TP/2 to calculate TP. Figures 6 and 7 give the value of TP which corresponds to the higher of the values of IHold and ILatch, assuming that VTM = 1.6 V. Figure 8 gives the Rsync that produces the corresponding TP. RSupply and Filter Capacitor With the output current and the pulse width determined as above, use Figures 9 and 10 to determine RSupply, assuming that the sinking current at Vref pin (including NTC bridge current) is less than 0.5 mA. Then use Figure 11 and 12 to determine the filter capacitor (CF) according to the ripple desired on supply voltage. The maximum ripple allowed is 1.0 V. Temperature Reduction Determined by R1 (Refer to Figures 13 and 14.) 3 UAA2016 Figure 2. Comparison Between Proportional Control and ON/OFF Control Overshoot Proportional Band Room Temperature T (°C) Time (minutes, Typ.) Time (minutes, Typ.) Heating Power P(W) Time (minutes, Typ.) Time (minutes, Typ.) Proportional Temperature Control D Reduced Overshoot D Good Stability ON/OFF Temperature Control D Large Overshoot D Marginal Stability Figure 3. Zero Voltage Technique TP is centered on the zero–crossing. TP AC Line Waveform IHold ILatch Gate Current Pulse T 4 14 x R sync ) 7 105 + (µs) P Vrms Ǹ2 x pf f = AC Line Frequency (Hz) Vrms = AC Line RMS Voltage (V) Rsync = Synchronization Resistor (Ω) MOTOROLA ANALOG IC DEVICE DATA UAA2016 CIRCUIT FUNCTIONAL DESCRIPTION Power Supply (Pin 5 and Pin 7) The application uses a current source supplied by a single high voltage rectifier in series with a power dropping resistor. An integrated shunt regulator delivers a VEE voltage of – 8.6 V with respect to Pin 7. The current used by the total regulating system can be shared in four functional blocks: IC supply, sensing bridge, triac gate firing pulses and zener current. The integrated zener, as in any shunt regulator, absorbs the excess supply current. The 50 Hz pulsed supply current is smoothed by the large value capacitor connected between Pins 5 and 7. Temperature Sensing (Pin 3) The actual temperature is sensed by a negative temperature coefficient element connected in a resistor divider fashion. This two element network is connected between the ground terminal Pin 5 and the reference voltage – 5.5 V available on Pin 1. The resulting voltage, a function of the measured temperature, is applied to Pin 3 and internally compared to a control voltage whose value depends on several elements: Sawtooth, Temperature Reduction and Hysteresis Adjust. (Refer to Application Information.) Temperature Reduction For energy saving, a remotely programmable temperature reduction is available on Pin 4. The choice of resistor R1 connected between Pin 4 and VCC sets the temperature reduction level. Comparator When the positive input (Pin 3) receives a voltage greater than the internal reference value, the comparator allows the triggering logic to deliver pulses to the triac gate. To improve the noise immunity, the comparator has an adjustable hysteresis. The external resistor R3 connected to Pin 2 sets the hysteresis level. Setting Pin 2 open makes a 10 mV hysteresis level, corresponding to 0.15°C. Maximum hysteresis is obtained by connecting Pin 2 to VCC. In that R out , OUTPUT RESISTOR (Ω ) 200 180 160 140 120 TA = +10°C TA = 0°C 100 80 TA = – 20°C 60 40 20 TA = –10°C 30 40 50 IGT, TRIAC GATE CURRENT SPECIFIED AT 25°C (mA) MOTOROLA ANALOG IC DEVICE DATA Sawtooth Generator In order to comply with European norms, the ON/OFF period on the load must exceed 30 seconds. This is achieved by an internal digital sawtooth which performs the proportional regulation without any additional component. The sawtooth signal is added to the reference applied to the comparator negative input. Figure 2 shows the regulation improvement using the proportional band action. Noise Immunity The noisy environment requires good immunity. Both the voltage reference and the comparator hysteresis minimize the noise effect on the comparator input. In addition the effective triac triggering is enabled every 1/3 sec. Failsafe Output pulses are inhibited by the “failsafe” circuit if the comparator input voltage exceeds the specified threshold voltage. This would occur if the temperature sensor circuit is open. Sampling Full Wave Logic Two consecutive zero–crossing trigger pulses are generated at every positive mains half–cycle. This ensures that the number of delivered pulses is even in every case. The pulse length is selectable by Rsync connected on Pin 8. The pulse is centered on the zero–crossing mains waveform. Pulse Amplifier The pulse amplifier circuit sinks current pulses from Pin 6 to VEE. The minimum amplitude is 70 mA. The triac is then triggered in quadrants II and III. The effective output current amplitude is given by the external resistor Rout. Eventually, an LED can be inserted in series with the Triac gate (see Figure 1). I Out(min) , MINIMUM OUTPUT CURRENT (mA) Figure 4. Output Resistor versus Triac Gate Current case the level is set at 5°C. This configuration can be useful for low temperature inertia systems. 60 Figure 5. Minimum Output Current versus Output Resistor 100 80 60 40 TA = + 85°C TA = – 20°C 20 0 40 60 80 100 120 140 160 Rout, OUTPUT RESISTOR (Ω) 180 200 5 UAA2016 Figure 6. Output Pulse Width versus Maximum Triac Latch Current Figure 7. Output Pulse Width versus Maximum Triac Latch Current 120 F = 50 Hz 2.0 kW Loads VTM = 1.6 V TA = 25°C 100 TP, OUTPUT PULSE WIDTH (µ s) TP, OUTPUT PULSE WIDTH ( µ s) 120 80 110 Vrms 60 220 Vrms 40 20 10 20 30 40 50 ILatch(max), MAXIMUM TRIAC LATCH CURRENT (mA) R Supply, MAXIMUM SUPPLY RESISTOR (k Ω ) 400 F = 50 Hz 300 220 Vrms 200 110 Vrms 100 0 20 40 60 80 TP, OUTPUT PULSE WIDTH (µs) 100 Figure 10. Maximum Supply Resistor versus Output Current 30 V = 110 Vrms F = 50 Hz 25 TP = 50 µs 20 100 µs 150 µs 15 200 µs 10 0 6 25 50 75 IO, OUTPUT CURRENT (mA) 100 60 220 Vrms F = 50 Hz 1.0 kW Loads VTM = 1.6 V TA = 25°C 40 0 R Supply , MAXIMUM SUPPLY RESISTOR (kΩ ) R sync , SYNCHRONIZATION RESISTOR (k Ω ) Figure 8. Synchronization Resistor versus Output Pulse Width 110 Vrms 80 20 60 10 20 30 40 50 ILatch(max), MAXIMUM TRIAC LATCH CURRENT (mA) 60 Figure 9. Maximum Supply Resistor versus Output Current 60 V = 220 Vrms F = 50 Hz 50 TP = 50 µs 40 100 µs 150 µs 30 200 µs 20 0 C F(min), MINIMUM FILTER CAPACITOR (µ F) 0 100 25 50 75 IO, OUTPUT CURRENT (mA) 100 Figure 11. Minimum Filter Capacitor versus Output Current 90 Ripple = 1.0 Vp–p F = 50 Hz 80 200 µs 70 150 µs 60 100 µs 50 TP = 50 µs 40 0 20 40 60 IO, OUTPUT CURRENT (mA) 80 100 MOTOROLA ANALOG IC DEVICE DATA Figure 12. Minimum Filter Capacitor versus Output Current Figure 13. Temperature Reduction versus R1 180 Ripple = 0.5 Vp–p F = 50 Hz 160 200 µs 140 150 µs 120 100 µs 100 TP = 50 µs TR , TEMPERATURE REDUCTION ( °C) C F(min), MINIMUM FILTER CAPACITOR ( µ F) UAA2016 7.0 Setpoint = 20°C 6.0 5.0 4.0 3.0 2.0 10 kΩ NTC 1.0 100 kΩ NTC 0 80 20 0 40 60 IO, OUTPUT CURRENT (mA) 80 0 100 RDEF /(NOMINAL NTC VALUE) RATIO R1 = 0 5.6 10 kΩ NTC 5.2 4.8 100 kΩ NTC 4.4 4.0 10 14 18 22 26 TS, TEMPERATURE SETPOINT (°C) ( R S + R 2 /(NOMINAL NTC VALUE) RATIO Figure 16. RS + R2 versus Preset Setpoint TDEF = 4°C 6 4 10 kΩ NTC RDEF = 29 kΩ 2 0 10 100 kΩ NTC RDEF = 310 kΩ 14 18 22 26 30 TS, TEMPERATURE SETPOINT (°C) MOTOROLA ANALOG IC DEVICE DATA 34 100 100 kΩ NTC 3 10 kΩ NTC 2 1 0 30 8 20 30 40 50 60 70 80 90 R1, TEMPERATURE REDUCTION RESISTOR (kΩ) Figure 15. RDEF versus Preset Temperature 4 6.0 0 V H , COMPARATOR HYSTERESIS VOLTAGE (V) TR , TEMPERATURE REDUCTION ( °C) Figure 14. Temperature Reduction versus Temperature Setpoint 10 5 10 15 20 25 TDEF, PRESET TEMPERATURE (°C) 30 Figure 17. Comparator Hysteresis versus R3 0.5 0.4 0.3 0.2 0.1 0 0 100 200 300 R3, HYSTERESIS ADJUST RESISTOR (kΩ) 400 7 UAA2016 OUTLINE DIMENSIONS 8 P SUFFIX PLASTIC PACKAGE CASE 626–05 ISSUE K 5 NOTES: 1. DIMENSION L TO CENTER OF LEAD WHEN FORMED PARALLEL. 2. PACKAGE CONTOUR OPTIONAL (ROUND OR SQUARE CORNERS). 3. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. –B– 1 4 F DIM A B C D F G H J K L M N –A– NOTE 2 L C J –T– N SEATING PLANE D M K MILLIMETERS MIN MAX 9.40 10.16 6.10 6.60 3.94 4.45 0.38 0.51 1.02 1.78 2.54 BSC 0.76 1.27 0.20 0.30 2.92 3.43 7.62 BSC ––– 10_ 0.76 1.01 INCHES MIN MAX 0.370 0.400 0.240 0.260 0.155 0.175 0.015 0.020 0.040 0.070 0.100 BSC 0.030 0.050 0.008 0.012 0.115 0.135 0.300 BSC ––– 10_ 0.030 0.040 G H 0.13 (0.005) T A M B M D SUFFIX PLASTIC PACKAGE CASE 751–05 ISSUE N (SO–8) –A– 8 M NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DIMENSIONS A AND B DO NOT INCLUDE MOLD PROTRUSION. 4. MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER SIDE. 5. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.127 (0.005) TOTAL IN EXCESS OF THE D DIMENSION AT MAXIMUM MATERIAL CONDITION. 5 4X –B– 1 P 0.25 (0.010) 4 M B M G R C –T– 8X K D 0.25 (0.010) M T B SEATING PLANE S A X 45 _ M_ S F J DIM A B C D F G J K M P R MILLIMETERS MIN MAX 4.80 5.00 3.80 4.00 1.35 1.75 0.35 0.49 0.40 1.25 1.27 BSC 0.18 0.25 0.10 0.25 0_ 7_ 5.80 6.20 0.25 0.50 INCHES MIN MAX 0.189 0.196 0.150 0.157 0.054 0.068 0.014 0.019 0.016 0.049 0.050 BSC 0.007 0.009 0.004 0.009 0_ 7_ 0.229 0.244 0.010 0.019 Motorola reserves the right to make changes without further notice to any products herein. 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