16 W xDSL Modem AC-DC Adapter GreenPoint® Reference Design

TND330/D
Rev. 3, APR − 2009
16 W xDSL Modem
AC−DC Adapter
Reference Design Documentation Package
© Semiconductor Components Industries, LLC, 2009
April, 2009 − Rev. 3
1
Publication Order Number:
TND330/D
Disclaimer: ON Semiconductor is providing this reference design documentation package “AS IS” and the recipient assumes
all risk associated with the use and/or commercialization of this design package. No licenses to ON Semiconductor’s or any
third party’s Intellectual Property is conveyed by the transfer of this documentation. This reference design documentation
package is provided only to assist the customers in evaluation and feasibility assessment of the reference design. It is expected
that users may make further refinements to meet specific performance goals.
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TND330
TND330
16 W xDSL Modem AC-DC
Adapter
Reference Design Documentation
Package
http://onsemi.com
TECHNICAL NOTE
1 Overview
This reference document describes a built−and−tested,
GreenPointt solution for an xDSL modem ac−dc adapter.
This power supply reference design is intended for low
power, off−line applications where a regulated output
voltage is required. Applications would also include
modems, printers, routers, hubs and/or similar consumer
audio and video products that require a single output voltage
in the 10 to 20 W range.
The power supply design is based around
ON Semiconductor’s NCP10xx family of monolithic
controllers with an integrated 700 V MOSFET. In this
particular design an NCP1027 is utilized in a 12 V, 1.3 A
output supply with a surge capability of over 1.6 A.
This design can be tailored for any output voltage from
several volts up to 28 V (or higher) with power outputs to
approximately 20 W (depending on the AC input
requirement) by merely reconfiguring the transformer turns
ratio and the voltage reference zener. The power supply will
meet typical safety agency isolation and leakage current
standards and comply with FCC Part 15 Level B conducted
EMI requirements and has an average efficiency of greater
than 75%.
Figure 1 shows a simplified block diagram of the
reference design circuit.
90 to
265 Vac
Figure 1. 16 W DSL Modem AC−DC Adapter
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2 Introduction
In 1Q06, the number of internet broadband lines (per 100
households) reached 54% in the USA, placing the country
in the top 20 ranking worldwide far behind countries such as
South Korea with 83% broadband penetration (source:
Point Topic). By 2010, nearly 71 million households in the
United States will have broadband access, a new study by
Forrester Research predicts. The growth in broadband
connection will result in increasing growth of cable modems
and xDSL modems. Typically, these modems are powered
by an external ac−dc adapter.
In most offices and households, these adapters remain
plugged in the socket, continuously drawing power from the
mains. For this reason, the ac−dc adapter must be designed
in such a way that its power consumption in standby
(no−load) mode is very low. It is estimated that, on average,
25% of the energy that passes through power supplies does
so during standby−mode (source: NRDC).
3 Modem AC−DC Adapter Requirements
The above paragraph showed the importance of reducing the
standby power. Not only the standby power consumption of an
ac−dc adapter has to be very low, but its active mode efficiency
has to be very high. High active−mode efficiency saves energy
when electronic devices are ‘active’, which are the times when
they consume the most energy. (Examples: TV is turned on;
computer is being used to play a video game.) It is estimated
that 75% of the energy that passes through power supplies does
so during active−mode (source: NRDC).
3.1 Regulatory Requirements for Standby (no−load)
Power Consumption and Active Mode Efficiency
Several regulatory bodies around the world address low
standby power consumption and efficiency in active mode
for external power supply (EPS). These requirements target
two issues:
• Get rid of the losses in a no−load situation (e.g.: when
the AC−DC adapter is plugged in even when it is not
connected to the cell phone).
• Achieve good average active mode efficiency during
various active mode load conditions (25%, 50%, 75%
and 100%).
Many regulations have been proposed around the world.
Hereafter is the list of some of the most important ones:
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ENERGY STAR): applicable in the US and international partners
http://www.energystar.gov/index.cfm?c=ext_power_supplies.power_supplies_consumers
Nameplate Output Power (Pno)
Minimum Average Efficiency in Active Mode (expressed as decimal)
ENERGY EFFICIENCY CRITERIA FOR ACTIVE MODE
0 to < 1 Watt
≥ 0.49 * Pno
> 1 and ≤ 49 Watts
≥ [0.09 * Ln(Pno)] + 0.49
> 49 Watts
≥ 0.84
ENERGY CONSUMPTION CRITERIA FOR NO LOAD
0 to < 10 Watts
≤ 0.5 Watt
≥ 10 to ≤ 250 Watts
≤ 0.75 Watt
California Energy Commission: Effective January 1, 2007
Nameplate Output
Minimum Efficiency in Active Mode
0 to < 1 Watt
0.49 * Nameplate Output
> 1 and ≤ 49 Watts
[0.09 * Ln(Nameplate Output)] + 0.49
> 49 Watts
0.84
Maximum Energy Consumption in No−Load Mode
0 to < 10 Watts
0.5 Watt
≥10 to ≤ 250 Watts
0.75 Watt
Effective July 1, 2008
Nameplate Output
Minimum Efficiency in Active Mode
0 to < 1 Watt
0.5 * Nameplate Output
> 1 and ≤ 51 Watts
[0.09 * Ln(Nameplate Output)] + 0.5
> 51 Watts
0.85
Maximum Energy Consumption in No−Load Mode
Any output
0.5 Watt
Where Ln (Nameplate Output) = Natural Logarithm of the nameplate output expressed in Watts
European Union’s Code of Conduct, version 2, November 24, 2004 − No−load Power Consumption
No−load Power Consumption
Rated Output Power
Phase 1 (Jan. 1, 2005)
Phase 2 (Jan. 1, 2007)
> 0.3 W and < 15 W
0.30 W
0.30 W
> 15 W and < 50 W
0.50 W
0.30 W
> 50 W and < 60 W
0.75 W
0.30 W
> 60 W and < 150 W
1.00 W
0.50 W
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TND330
Energy−Efficiency Criteria for Active Mode for Phase 1 (for the period January 1, 2005 to December 31, 2006)
Rated Output Power
Minimum Four Point Average (see Annex) or 100 % Load Efficiency in Active Mode
0 < W < 1.5
30
1.5 < W < 2.5
40
2.5 < W < 4.5
50
4.5 < W < 6.0
60
6.0 < W < 10.0
70
10.0 < W < 25.0
75
25.0 < W < 150.0
80
Energy−Efficiency Criteria for Active Mode for Phase 2 (valid after January 1, 2007)
Nameplate Output Power (Pno)
Minimum Four Point Average (see Annex) or 100 % Load Efficiency in Active Mode
(expressed as a decimal) (Note 1)
0<W<1
≥ 0.49 * Pno
1 < W < 49
≥ [0.09 * Ln(Pno)] + 0.49
49 < W < 150
≥ 0.84 (Note 2)
1. “Ln” refers to the natural logarithm. The algebraic order of operations requires that the natural logarithm calculation be performed first and
then multiplied by 0.09, with the resulting output added to 0.49. An efficiency of 0.84 in decimal form corresponds to the more familiar value
of 84% when expressed as a percentage.
2. Power supplies that have a power factor correction (PFC) to comply with IEC61000−3−2 (above 75 W input power) have a 0.04 (4%)
allowance, accordingly the minimum on mode load efficiency (100% or averaged) is relaxed to 0.80 (80%).
Korea:
• External Power Supply − No load: 0.8 W
• Battery Charger − No load: 0.8 W
Worldwide Legislation for EPS (external power supplies)
Regulatory
Agency/
Organization
Country/State
Affected
Implementation
Date
Compliance
Required
(Mandatory
or
Voluntary)
STAR®
United States
January 1, 2005
Voluntary
http://www.energystar.gov/index.cfm?c=
ext_power_supplies.power_supplies_consumers
Europe
January 1, 2005
Voluntary
http://re.jrc.ec.europa.eu/energyefficiency/html/
standby_initiative_External%20Power%20Supplies.htm
China
January 1, 2005
Voluntary
Harmonized with ENERGY STAR,
http://www.cecp.org.cn/englishhtml/hlproductlist1.asp
California
January 1, 2007
Mandatory
http://www.energy.ca.gov/appliances/index.html
Australia,
New Zealand
October 1, 2008
Mandatory
Harmonized with ENERGY STAR,
http://www.energyrating.gov.au/eps2.html
Arizona
January 2008
Mandatory
Source: http://www.standardsasap.org
Massachusetts
January 2008
Mandatory
Source: http://www.standardsasap.org
New York
January 2008
Mandatory
Source: http://www.standardsasap.org
Oregon
January 2008
Mandatory
Source: http://www.standardsasap.org
Rhode Island
January 2008
Mandatory
Source: http://www.standardsasap.org
Vermont
January 2008
Mandatory
Source: http://www.standardsasap.org
Washington
January 2008
Mandatory
Source: http://www.standardsasap.org
ENERGY
European Union
China Standard
Certification Center
(CSC, ex−CECP)
California Energy
Commission
Australia Greenhouse Office (AGO)
Arizona
Massachusetts
New York
Oregon
Rhode Island
Vermont
Washington
3. Sources: www.psma.com, www.standardsasap.org
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Comments
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4 Modem AC−DC Adapter Specification
For modem OEM manufacturers, the ac−dc adapter is a
commodity. So, they impose their own stringent
specifications and de−rating guidelines while requiring low
costs.
The key performance criteria for adapters are:
• Power density (driven by package size requirements)
• Safety
• Low case temperature
Cooling: Convection
Input Protection: 8 ohm inrush limiting with 1 A fuse
Output Protection: Over−current, over−voltage, and over−
temperature
Safety Compliance: 3 kV I/O isolation
EMI Compliance: FCC Part 15 conducted EMI (Level B,
average profile)
Input: 90 to 270 Vac, 50/60 Hz
Output: 12 Vdc ±5% at 1.3 A continuous (16 W); 1.6 A
surge to 10 seconds
Regulation: < 2% line and load combined
Output Ripple: Less than 200 mV p/p
Average Efficiency: > > 0.09 * Ln (16) + 0.09 = 74% (per
ENERGY STAR®)
Standby (no−load) power consumption < 300 mW
Operating Temperature: 0 to 50°C
5 Circuit Operation
Referring to the schematic in Figure 2, the power supply
is designed around a flyback converter topology with a
simple zener plus optocoupler feedback circuit for output
voltage sensing and regulation. The ac input is full−wave
rectified by D1 through D4 and filtered by C3 and C4 to
provide a dc “bulk” bus to the flyback converter stage. R1
provides inrush current limiting at turn−on while C1, C2, L1,
L2 and C13 comprise both common and differential mode
filtering for conducted EMI.
L1
3.9 mH
R1
AC
input
8.2, 2W
F1
C1
10 nF
”x”
1 A,
250 Vac
C2
D1−D4
1N4007
100 nF
”x”
C3
T1
C5
180pF
2 kV
C4
L2
680 uH
D6
MBRS360T
10
R2
4.7
10 uF,
400Vdc
x2
R3
39K,
1W 1
5
9
6
D5
MURS160
R4
100K
0.1
C7
C6
470 uF
16V
x2
2
MMSD4148A
R14
omit
R11
2.2M
R13
omit
R15
10
+
R12
2.2M
NCP1027
(100 kHz)
3
R10
30K
C11
1 nF
U1
4
7
1
8
C10
10 uF
25V
2.2nF
”Y2”
4
10 uF
25V
R5
Vtrim
(0 ohm)
1 nF
Figure 2. 16 W, 12 V Output Adapter Supply (Rev 4)
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U2
1
47
R7
330
C8
NOTES:
1. L1 is Coilcraft E3491−AL common mode EMI inductor (3.9 mH)
2. L2 is Coilcraft part RFB0810−681L or similar (680 uH, 500 mA)
3. See Magnetics Data Sheet for T1 construction details.
4. R9 sets OVP trip level.
5. R8, R13, R14 for optional power limit feature (see NCP1027 data sheet.)
6. Z1 zener sets Vout: Vout = Vz + 0.85V; R5 is optional voltage trim resistor
7. R10 sets AC input brownout level.
8. R1 is optional inrush limiter.
9. U1 requires Aavid #580100W00000G clip−on DIP8 heatsink or similar.
10. Crossed schematic lines are not connected
7
Z1
MMSZ5241B
(11V)
C13
R6
+ C9
R8
0 ohm
3
8
R9
1K
5
2
D7
3
opto
2
12V @ 1.3A
C12
+
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relatively smooth dc level by C6 and C7, the main output
capacitors. Capacitor C12 provides for additional high
frequency noise filtering for the output. An RCD snubber
network composed of R2, R3, C5, and D5 is implemented to
clamp voltage spikes caused by the primary leakage
inductance of T1. This network prevents potential damage
to the MOSFET drain terminal (pin 5) of U1 by limiting the
peak voltage and lowers potential EMI emissions.
An alternate non−dissipative, resonant snubber circuit is
shown in Figure 3 which will improve the efficiency of this
circuit by a few percentage points depending on the nature
of the transformer design and the associated parasitic
parameters.
The flyback converter is comprised of the NCP1027
controller/MOSFET U1, flyback transformer T1, and the
secondary output rectifier/filter section of D6, C6 and C7.
An auxiliary winding on T1 and associated components
R15, D7, C10, R9, and C9 provide an operating bias (VCC)
for the control chip and allows for low output power if the
supply is short circuited, and very low standby power under
no−load conditions. Since the voltage produced by the
auxiliary winding tracks the main output voltage, it is also
used to sense for over−voltage conditions in the event the
feedback loop opens.
The OVP trip level can be adjusted by the turns on the
auxiliary winding and the value of R9. The main secondary
voltage is rectified by Schottky diode D6 and filtered to a
T1
C3
10
10 uF,
400Vdc
x2
MURS160
x2
C4
L2
680 uH
Lr = 1.5 mH
Lr is Coilcraft
RFB0810−152L
Bulk
common
1
Cr
180pF
2 kV
9
2
Drain
terminal
Figure 3. Non dissipative resonant snubber option
If the output current exceeds approximately 1.8 A, the
converter duty cycle will be reduced by peak current sensing
of the MOSFET in U1, and the output voltage will begin to
drop. Since the Vcc bias voltage on C10 will drop with the
output voltage, eventually there will be insufficient voltage
on VCC pin 1 to power the controller, and the supply will then
go into a start−stop “hiccup” mode which will prevent high
output currents into an overload and protect both the power
supply and load.
The network of R10 through R12 provides brownout
protection for the circuit in the event the AC input voltage
(and hence, the dc bulk voltage) drops below about 75 Vac.
The level on pin 3 at which the chip shuts down can be
adjusted via R10. C11 provides noise filtering for this input.
Optional over−power compensation can also be provided
via optional resistors R8, R13 and R14 if desired. With
universal input supplies, the available output current will
typically increase at high line due to reduced inverter duty
cycle and the associated propagation delays in the control
circuit. As a consequence more output power (current) is
available at 230 Vac input. Adding these circuit components
will compensate for this effect. Grounding pin 7 disables this
feature. The details for the application of this and the
brownout features, among others, is described in detail in the
data sheet for the NCP1027, which is available at
www.onsemi.com.
As the supply’s supply output voltage and/or power level
decreases, depending on the need, this incremental increase
in efficiency may be critical in meeting ENERGY STAR
efficiency requirements. The non−dissipative snubber
circuit utilizes a resonant tank circuit composed of Lr and Cr
which essentially acts as a reactive charge pump that returns
the transformer’s leakage reactance energy back to the input
bus (on C4) rather than burn it away in a resistor. This can
be implemented for the slight cost increase of an extra fast
recovery diode and the small 1.5 mH inductor Lr.
Output voltage regulation is achieved by the combination
of components Z1, R5, R6, R7 and optocoupler U2. When
the output voltage reaches approximately 12 V, zener Z1
conducts, and when sufficient current flows through R7 to
produce the 0.9 V necessary to turn the optocoupler diode
on, the voltage feedback loop closes and the output will be
regulated. The use of R7 forces the zener current to be in a
stable part of the device’s characteristic V/I curve such that
temperature effects on the output voltage are minimized.
The output voltage will be equal to the rated zener voltage
plus about 0.9 V. There will be some variation due to zener
and optocoupler characteristics and a small negative
temperature coefficient with this circuit, however, the Vout
set point variations should not exceed ±5%. Optional
resistor R5 allows trimming of the output voltage in the
upward direction only.
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6 Transformer Design
For low power applications it is desirable to have as small
a transformer as possible; however, as the transformer gets
smaller, so does the core’s cross sectional area. This forces
more primary turns in order to maintain an acceptable
magnetic flux density limit and can cause excessive turns
buildup in the bobbin such that effective primary to
secondary insulation becomes prohibitive. A large number
of primary turns also increases the primary leakage
inductance, not to mention the dc resistance of the windings
in general. Both of these factors contribute to lower
efficiency in the converter. In this design an E25/10/6
(formerly E24/25) ferrite core was used with a satisfactory
compromise with respect to the above mentioned parametric
issues. The transformer design for a universal input is shown
in Figure 4.
Magnetics Design Data Sheet − Universal Input Line Voltage
Project / Customer: ON Semiconductor − 16 − 20 watt, 12 vout Wallwart supply
Part Description: 20 watt NCP1027 flyback transformer, 100 kHz, 12V / 1.5 A
Schematic ID: T1
Core Type: E24/25 (E25/10/6); 3C90 material or similar
Core Gap: Gap for 750 uH
Inductance: 750 uH +/−5%
Bobbin Type: 10 pin horizontal mount for E24/25 (E25/10/6)
Windings (in order):
Winding # / type
Turns / Material / Gauge / Insulation Data
Primary A (1 − 10)
25 turns of #30HN over 1 layer. Insulate for
1 kV to next winding. Self leads to pins..
Vcc (3 − 8)
5 turns of #30 HN spiral wound over 1 layer with
3 mm end margins minimum. Self leads to pins.
Insulate to 3 kV to next winding
12V Secondary (5 − 6)
5 turns of three strands of #26HN (trifilar) over
previous winding with 1.5 mm end margins
approximately. Winding ends should be cuffed with
tape to avoid edge breakdown other windings. Insulate
for 3 kV to next winding. Self leads to pins.
Primary B (2 − 9)
Same as Primary A.
Hipot: 3 kV from primaries & Vcc to secondary for 1 minute.
Lead Breakout / Pinout
Schematic
10
1
9
2
(Top View)
10 9 8 7 6
5
6
3
8
12 3 4 5
Figure 4.
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Vendor: Mesa Power
Systems, Escondido,
CA. 760−489−8162
Part #
TND330
winding. The designs shown in Figures 4 and 5 should be
sufficient for any magnetics fabrication house to produce the
transformer. Exact pinouts will depend on the specific
layout, however, the core selection, wire sizing, inductance
value and turns ratio should be adhered to for proper
operation. This particular flyback transformer is designed
for 100 kHz discontinuous inductor mode (DCM) operation,
so the slope compensation feature of pin 2 in the NCP1027
is not necessary (see data sheet for details).
Figure 5 is a design for 230 Vac input only (Europe) and
will provide slightly higher efficiency and the ability to
increase the available continuous power output to
approximately 20 W (1.65 A). In either design, the primary
is separated into two layers with the secondary and Vcc
winding sandwiched in between. This configuration
provides for lower leakage inductance and subsequently less
voltage spiking at MOSFET turn−off. The trifilar wound
12 V secondary provides for lowest ac and dc losses in this
Magnetics Design Data Sheet − European Input Line Voltage
Project / Customer: ON Semiconductor − 22 watt, 12 vout adapter supply − Euro version
Part Description: 22 watt NCP1027 flyback transformer, 100 kHz, 12V / 2A
Schematic ID: T1
Core Type: E24/25 (E25/10/6); 3C90 material or similar
Core Gap: Gap for 1.5 mH across pins 2 and 10 with pins 1 and 9 connected
Inductance: 1.5 mH +/−5% (across pins 2 and 10 with pins 1 and 9 connected)
Bobbin Type: 10 pin horizontal mount for E24/25 (E25/10/6)
Windings (in order):
Winding # / type
Turns / Material / Gauge / Insulation Data
Primary A (1 − 10)
38 turns of #32HN over 1 layer. Insulate for
1 kV to next winding. Self leads to pins..
Vcc (3 − 8)
6 turns of #30 HN spiral wound over 1 layer with
3 mm end margins minimum. Self leads to pins.
Insulate to 3 kV to next winding
12V Secondary (5 − 6)
6 turns of three strands of #26HN (trifilar) over
previous winding with 1 mm end margins
approximately. Winding ends should be cuffed with
tape to avoid edge breakdown other windings. Insulate
for 3 kV to next winding. Self leads to pins.
Primary B (2 − 9)
Same as Primary A.
Hipot: 3 kV from primaries & Vcc to secondary for 1 minute.
Lead Breakout / Pinout
Schematic
(Top View)
10
10 9 8 7 6
1
9
2
Vendor: Mesa Power
Systems, Escondido,
CA. 760−489−8162
Part # 13−1305
5
6
12 3 4 5
3
8
Figure 5.
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7 Test Results
7.1 Active Mode Efficiency
minimum requirement of 74% at this particular power level.
In the 230 Vac input case, a slight efficiency degradation
occurs at light loading due to increased circuit quiescent
power, mainly due to higher MOSFET switching losses at
this input level.
The efficiency curves with output loading at 25%, 50%,
75% and 100% for 120 and 230 Vac inputs are shown in
Figures 6 and 7. Figure 7 displays the improved efficiency
with the resonant snubber circuit. Note that the average
efficiency in both cases easily meets the ENERGY STAR
Traditional RCB Snubber
Non−Dissipative Resonant Snubber
Efficiency @ 255C
% Load
120 Vac
230 Vac
% Load
120 Vac
230 Vac
25
50
74
73
25
76.2
74.4
77
78.2
50
79
79.8
75
77.6
80
75
78
80.5
100
76.8
80.6
100
78.2
81
Average Efficiency
76.4%
78.0%
Average Efficiency
78.1%
78.9%
Minimum Efficiency per
ENERGY STAR:
[0.09 * Ln(16W)] + 0.49
74%
74%
Minimum Efficiency per
ENERGY STAR:
[0.09 * Ln(16W)] + 0.49
74%
74%
90
90
80
80
Efficiency (%)
Efficiency (%)
Efficiency @ 255C
70
60
70
60
50
50
0
10
20
30
40
50
60
70
80
90
100
0
% Load
120 Vac
10
20
30
40
50
60
70
% Load
230 Vac
120 Vac
Figure 6.
Figure 7.
7.2 Standby (no load) Power Consumption
Traditional RCD Snubber
290 mW @ 120 Vac
210 mW @ 240 Vac
Non−Dissipative Resonant Snubber
240 mW @ 120 Vac
200 mW @ 240 Vac
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230 Vac
80
90
100
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7.3 EMI Profile
The power supply was also tested at a local certified EMI/EMC test facility for conducted EMI on the AC input mains. The
plot of Figure 8 shows the conducted EMI profile (peak and average) for 120 Vac input with an output load of 1.3 A. Note that
the supply’s EMI plot meets the average boundary for FCC Level B.
M. Flom Associates, Inc.
EN 55022: 1998, Class B
Line 1 (Neutral)
90.0
Points of Interest
80.0
Corrected Peak Data
CISPRB_QP
Amplitude dBuV
70.0
CISPRB_AV
60.0
50.0
40.0
30.0
20.0
10.0
0
100.0K
Operator: LR
10:57:13 AM, Wednesday, March 21, 2007
1.0M
10.0M
Frequency MHz
100.0M
Job #: p0703008
Figure 8.
7.4 Other Results
Figures 9 and 10 show the typical discontinuous flyback voltage waveforms on U1’s internal MOSFET drain for 120 and
230 Vac inputs respectively, with a 1.3 A output load.
Figure 9. Drain Voltage @ 120 Vac
Figure 10. Drain Voltage @ 230 Vac
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TND330
Figure 11 is a display of the output ripple with a 1.3 A load. If necessary, lower output ripple can be achieved by placing a
small 4.7 mH, 2 A rated inductor between the output capacitors C6 and C7 in the positive rail.
Figure 11. Output Ripple
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TND330
8 Bill of Materials
16 W, NCP10127 Adaptor BOM (Rev. 4)
Part
Qty
ID
Description
MRA4007
4
D1 − D4
MURS160
1
MBRS360T Schottky
1
MMSZ5241B zener diode
Optocoupler, SFH6156A−4 (4 pin)
Comments
1 A, 800 V diode
ON Semiconductor
D5
1 A, 600 V UFR diode
ON Semiconductor
D6
3 A, 60 V Schottky
ON Semiconductor
1
Z1
11 V, 250 mW zener
ON Semiconductor
1
U2
Optocoupler
Vishay
NCP1027 (100 kHz)
1
U1
100 kHz current mode controller
ON Semiconductor
“X” cap, disc type
2
C1, C2
10 nF “X2” capacitor, 250 Vac
Vishay
“Y” cap, disc type
1
C13
2.2 nF, “Y2” capacitor, 250 Vac
Vishay
Ceramic cap, disc
1
C5
4.7 nF, 2 kV capacitor (snubber)
Vishay
Ceramic cap, monolythic
1
C12
0.1 mF, 50 V ceramic cap
Vishay
Ceramic cap, monolythic
2
C8, C11
1 nF, 50 V ceramic cap
Vishay
Electrolytic cap
2
C3, C4
10 mf, 400 Vdc
UCC, Rubycon
Electrolytic cap
2
C6, C7
470 mf, 16 V (low ESR)
UCC, Rubycon
Electrolytic cap
2
C9, C10
10 mf, 25 V
UCC, Rubycon
Resistor, 2 W
1
R1
8.2 W, 2 W ceramic
Ohmite
Resistor, 1 W
1
R3
39 K, 1 W
Ohmite
Resistor, 1/4 W
1
R2
4.7 W, 1/4 W
Ohmite
Resistor, 1/4 W
1
R8
0 W, 1/4 W (jumper − power limit)
Ohmite
Resistor, 1/8 W
1
R7
330, 1/8 W
Ohmite
Resistor, 1/8 W
1
R6
47 W, 1/8 W
Ohmite
Resistor, 1/4 W
1
R4
100 K, 1/4 W
Ohmite
Resistor, 1/8 W
1
R5
0 W, 1/8 W (jumper)
Ohmite
Resistor, 1/8 W
1
R15
10 W
Ohmite
Resistor, 1/8 W
1
R9
1 kW
Ohmite
Resistor, 1/8 W
1
R10
30 K
Ohmite
Resistor, 1/4 W
2
R11, R12
2.2 Meg
Ohmite
Resistor, 1/4 W
2
R13, R14
TBD (optional for power limit)
Ohmite
Heatsink for U1
1
Aavid 580100W00000G
Aavid
Inductor, 680 mH
1
L2
RFB0810−681L
Coilcraft
EMI Inductor, 3.9 mH
1
L1
E3491−AL
Coilcraft
Transformer
1
T1
Flyback Xfmr #13−1302
Mesa Power Systems
http://onsemi.com
14
TND330
3.75 Inches
2.25 Inches
Figure 12. PCB Layout
(Top View)
Figure 13. Board Picture
http://onsemi.com
15
TND330
9 Appendix
References:
• Draft Commission Communication on Policy Instruments to Reduce Stand−by Losses of Consumer Electronic
Equipment (19 February 1999) − http://energyefficiency.jrc.cec.eu.int/pdf/consumer_electronics_communication.pdf
European Information & Communications Technology Industry Association − http://www.eicta.org/
•
• http://standby.lbl.gov/ACEEE/StandbyPaper.pdf
CSC (ex−CECP China):
• http://www.cecp.org.cn/englishhtml/index.asp
Energy Saving (Korea):
• http://weng.kemco.or.kr/efficiency/english/main.html#
Top Runner (Japan):
• http://www.eccj.or.jp/top_runner/index.html
EU Eco−label (Europe):
• http://europa.eu.int/comm/environment/ecolabel/index_en.htm
• http://europa.eu.int/comm/environment/ecolabel/product/pg_television_en.htm
EU Code of Conduct (Europe):
• http://energyefficiency.jrc.cec.eu.int/html/standby_initiative.htm
GEEA (Europe):
• http://www.efficient−appliances.org/
• http://www.efficient−appliances.org/Criteria.htm
Energy Star:
• http://www.energystar.gov/
• http://www.energystar.gov/index.cfm?c=ext_power_supplies.power_supplies_consumers
1 Watt Executive Order:
• http://oahu.lbl.gov/
• http://oahu.lbl.gov/level_summary.html
Additional Collateral from ON Semiconductor:
• NCP1027/D: High−Voltage Switcher for Medium
• Application Note AND8241/D: A 5 V/2 A Power
•
•
•
•
•
•
•
Power Offline SMPS
Design note DN06006/D: NCP1027: 1 A, 12 W
Constant Current Off−Line LED Driver
Design note DN06012/D: NCP1027: 10 W, 24 V / 5 V
Off−Line Power Supply
Design note DN06021/D: NCP1027: 16 W, 12 Vdc
Modem Power Supply
Supply
MBRS360/D: 3 A, 60 V Schottky Rectifier
MMSD4148/D: 100 V Switching Diode
MURS160/D: 1 A, 600 V Ultrafast Rectifier
MMSZ5241B/D: 500 mW Zener Diode
GreenPoint is a trademark of Semiconductor Components Industries, LLC (SCILLC).
ON Semiconductor and
are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice
to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability
arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages.
“Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All
operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights
nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications
intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should
Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates,
and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death
associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal
Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.
PUBLICATION ORDERING INFORMATION
LITERATURE FULFILLMENT:
Literature Distribution Center for ON Semiconductor
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Phone: 303−675−2175 or 800−344−3860 Toll Free USA/Canada
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http://onsemi.com
16
ON Semiconductor Website: www.onsemi.com
Order Literature: http://www.onsemi.com/orderlit
For additional information, please contact your local
Sales Representative
TND330/D
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