an9534

Using the HI5703 Evaluation Board
Application Note
Description
The HI5703EVAL evaluation board for the HI5703 can be used
to evaluate the performance of the HI5703 10-bit 40 MSPS
analog-to-digital converter (ADC). As shown in the Evaluation
Board Block Diagram, this evaluation board includes clock
driver circuitry, reference voltage generators, and a choice
of analog input drive circuits. Buffered digital data outputs
are conveniently provided for easy interfacing to a ribbon
connector or logic probes. The evaluation board is provided
with some prototyping area for the addition of user
designed custom interfaces or circuits. Additionally, the
evaluation board is provided with eight removable jumpers
to allow for various operational configurations.
HI5703 A/D Theory of Operation
The HI5703 is a 10-bit fully differential sampling pipelined
A/D converter with digital error correction. Figure 1 depicts
the circuit for the converters front-end differential-in-differential-out sample-and-hold (S/H). The switches are controlled
by an internal clock which is a non-overlapping two phase
signal, φ1 and φ2, derived from the master clock (CLK) driving the converter. During the sampling phase, φ1, the input
signal is applied to the sampling capacitors, CS. At the same
time the holding capacitors, CH, are discharged to analog
ground. At the falling edge of φ1 the input signal is sampled
January 1996
AN9534.1
on the bottom plates of the sampling capacitors. In the next
clock phase, φ2, the two bottom plates of the sampling
capacitors are connected together and the holding capacitors are switched to the op-amp output nodes. The charge
then redistributes between CS and CH, completing one sample-and-hold cycle. The output of the sample-and-hold is a
fully-differential, sampled-data representation of the analog
input. The circuit not only performs the sample-and-hold
function, but can also convert a single-ended input to a fullydifferential output for the converter core. During the sampling
phase, the VIN pins see only the on-resistance of the
switches and CS. The relatively small values of these components result in a typical full power input bandwidth of
250MHz for the converter.
As illustrated in the HI5703 Functional Block Diagram and the
timing diagram in Figure 2, nine identical pipeline subconverter stages, each containing a two-bit flash converter and a
two-bit multiplying digital-to-analog converter, follow the front
end S/H circuit with the tenth stage being a one bit flash converter. Each converter stage in the pipeline will be sampling in
one clock phase and amplifying in the other clock phase.
Each individual subconverter clock signal is offset by 180
degrees from the previous stage clock signal so that alternate
stages in the pipeline will perform the same operation.
Evaluation Board Block Diagram
TTL COMP
CLK
CLOCK OUT
50
+5VD
-5.2VD
2.5V REF
CLK
VREF +
+3.25V
+2V
EXTREF+
VREF -
VIDEO
10
DOUT
EXTREF-
DATA OUT
BUFFER
75
VIN
RF IN
RF
XFORMER
HI5702
DGND
AGND
50
+5VD -5.2VD +5VA
1
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-5VA
© Intersil Corporation 1999
Application Note 9534
HI5703 Functional Block Diagram
CLOCK
BIAS
VDC
CLK
VINVIN+
S/H
STAGE 1
DFS
2-BIT
FLASH
2-BIT
DAC
OE
+
∑ -
X2
D9 (MSB)
D8
D7
D6
DIGITAL DELAY
AND
DIGITAL ERROR
CORRECTION
STAGE 9
D5
D4
D3
2-BIT
FLASH
2-BIT
DAC
D2
D1
+
D0 (LSB)
∑ -
X2
STAGE 10
1-BIT
FLASH
AVCC
2
AGND
DVCC1
DVCC2
DGND
VREF +
VREF -
Application Note 9534
φ1
VIN +
φ1
φ1
φ1
CH
CS
φ2
VIN -
digital delay line is to time align the digital outputs of the nine
identical two-bit subconverter stages with the corresponding
output of the tenth stage flash converter before inputting the
nineteen bit result into the digital error correction logic. The
digital error correction logic uses the supplementary bits to
correct any error that may exist before generating the final
ten bit digital data output of the converter.
VOUT +
-+
+ -
VOUT-
CS
CH
φ1
φ1
FIGURE 1. ANALOG INPUT SAMPLE-AND-HOLD
The output of each of the nine identical two-bit subconverter
stages is a two-bit digital word containing a supplementary
bit to be used by the digital error correction logic. The output
of each subconverter stage is input to a digital delay line
which is controlled by the internal clock. The function of the
Because of the pipeline nature of this converter, the digital
data representing an analog input sample is output on the
bus at the 7th cycle of the clock after the analog sample is
taken. This delay is specified as the data latency. After the
data latency time, the data representing each succeeding
sample is output at the following clock pulse. The output data
is synchronized to the external clock by a double buffered
latching technique. The output of the digital correction circuit
is available in two’s complement or offset binary format
depending on the condition of the Data Format Select (DFS)
input.
ANALOG
INPUT
CLOCK
INPUT
SN-1
HN-1
SN
HN
SN+1
HN+1
SN+2
SN+5
HN+5
SN+6
HN+6
SN+7
HN+7
SN+8
HN+8
INPUT
S/H
1ST
STAGE
2ND
STAGE
B1, N-1
B2, N-2
10TH
STAGE
DATA
OUTPUT
B1, N
B2, N-1
B1, N+1
B1, N+4
B1, N+5
B2, N+4
B2, N
B10, N-5
B10, N-4
B10, N-3
B10, N
DN-6
DN-5
DN-4
DN-1
B2, N+5
B10, N+1
DN
tLAT
NOTES:
1.
2.
3.
4.
SN: N-th sampling period.
HN: N-th holding period.
BM, N: M-th stage digital output corresponding to N-th sampled input.
DN: Final data output corresponding to N-th sampled input.
FIGURE 2.
3
B1, N+6
HI5703 INTERNAL CIRCUIT TIMING
B1, N+7
B2, N+6
B10, N+2
B10, N+3
DN+1
DN+2
Application Note 9534
Layout and Power Supplies
The HI5703 evaluation board is a three layer board with a
layout optimized for the best performance of the ADC. The
application note includes an electrical schematic of the evaluation board, a component layout and the various board layers. The user should feel free to copy the layout in their
application. Refer to the component layout and the evaluation board electrical schematic for the following discussion.
The HI5703 A/D has separate analog and digital supply and
ground pins to keep digital noise out of the analog signal
path. The evaluation board provides separate low impedance analog and digital ground planes. Since the analog and
digital ground planes are connected together under the
ADC, DO NOT tie them together back at the power supplies.
The analog and digital supplies are also kept separate on the
evaluation board and should be driven by clean linear regulated supplies. They can be hooked up with external 20 gauge
wires to the holes marked AVCC1, AVCC2, AVEE, DVCC1,
DVCC2, DVEE, AGND and DGND in the prototyping area.
DVCC1, DVCC2, and DVEE are digital supplies and should be
returned to DGND. AVCC1, AVCC2, and AVEE are the analog
supplies and should be returned to AGND. Table 1 lists the
operational supply voltages for the evaluation board. Single
supply operation of the converter is possible but the overall
performance of the converter may degrade.
TABLE 1. EVALUATION BOARD POWER SUPPLIES
POWER
SUPPLY
MIN
TYP
MAX
AVCC1
+4.75V
+5.0V
+5.25V
AVCC2
+4.75V
+5.0V
+5.25V
AVEE
-5.25V
-5.0V
-4.75V
DVCC1
+4.75V
+5.0V
+5.25V
DVCC2
+4.75V
+5.0V
+5.25V
DVEE
-5.45V
-5.2V
-4.95V
Configuration Jumpers
The evaluation board is provided with eight removable jumpers (JP1-8) that allow for various operational configurations.
The following is a description of the feature provided by each
of the configuration jumpers.
JP1 is used to establish the analog signal path input to the
HI5703 A/D through the VIDEO SMA input connector.
JP5 is used to connect the evaluation board positive reference voltage generator output, nominally +3.25V, to the
HI5703 positive reference voltage input pin, VREF+.
JP6 is used to connect the evaluation board negative reference voltage generator output, nominally +2.0V, to the
HI5703 negative reference voltage input pin, VREF-.
JP7 is used to control the operational state of the HI5703
digital output drivers. With JP7 installed the digital Output
Enable (OE) control input pin is set to a logic “0” enabling the
digital data outputs. To place the digital data outputs in the
three-state high impedance mode, JP7 is removed and and
a TTL logic “1” needs to be applied to the jumper pin connected to the HI5703 digital Output Enable (OE) control
input pin.
JP8 is used to supply the HI5703 digital output supply pin
(DVCC2) with the desired output logic operating voltage
level. With JP8 installed the HI5703 digital output supply is
connected to the evaluation board +5V digital supply,
DVCC1. For operation of the digital outputs at voltages from
+3.3V to +5V, JP8 is removed and the desired operating voltage needs to be applied to the jumper pin connected to the
HI5703 A/D digital output supply pin (DVCC2, pin 23).
Reference Voltage Generator Circuit
The HI5703 A/D contains a resistive ladder between the
reference voltage input pins. The A/D requires two reference
voltages, one connected to the VREF+ input pin and the
other connected to the VREF- input pin. The reference
voltage that drives VREF+ must be able to source the
maximum reference current which will then flow into the
VREF- reference. The HI5703 is tested with VREF- equal to
2V and VREF+ equal to 3.25V for a fully differential analog
input voltage range of ±1.25V. VREF+ and VREF- can differ
from the above voltages as long as the reference common
mode voltage, (VREF+ + VREF-)/2, at the reference pins
does not exceed 2.625V ±50mV.
The reference circuit on the evaluation board contains a precision +2.5V reference (U4) along with operational amplifiers
(U5A and U5B) that are utilized to generate the reference
voltages for the HI5703. The reference voltages are set at
the factory to the levels required by the HI5703 as follows.
The VREF- reference input is set FIRST by monitoring JP6
with a DVM and adjusting R11 until a reading of 2.0V ±5mV
is obtained. Next the VREF+ reference input is set by monitoring JP5 with a DVM and adjusting R15 until a reading of
3.25V ±5mV is obtained.
JP2 is used to connect the HI5703 bias voltage output (VDC)
to the differential inputs, VIN+ and VIN-, of the A/D.
Sample Clock Driver, Timing and I/O
JP3 is used to connect an external user supplied DC bias
voltage to the differential inputs, VIN+ and VIN-, of the A/D.
In order to ensure rated performance of the HI5703, the duty
cycle of the sample clock should be held at 50%. It must also
have low phase noise and operate at standard TTL levels.
JP4 configures the digital output data format of the HI5703
by setting the logic level of the Data Format Select (DFS)
input pin. With the JP4 jumper installed DFS is set to a logic
“0” establishing the digital data output format to offset binary.
With the JP4 jumper removed DFS is set to a logic “1” establishing the digital data output format to two’s complement.
It can be difficult to find a low phase noise generator that will
provide a 40MHz squarewave at TTL logic levels. Therefore,
a TTL voltage comparator (U3) is provided on the evaluation
board to generate a TTL level sampling clock for the HI5703
when a sinewave (< ±3V) or squarewave clock is applied to
4
Application Note 9534
the CLK input of the evaluation board. A potentiometer (R2)
is provided to allow the user to adjust the duty cycle of the
sampling clock to obtain the best performance from the
ADC. The trigger level for the CLK input to the converter is
approximately 1.5V. Therefore, the duty cycle of the sampling clock should be measured at the 1.5V trigger level.
Figure 3 shows the clock/data timing relationship for the
evaluation board. The data corresponding to a particular
sample will be available at the digital outputs of the HI5703
after the data latency (7 cycles) plus the HI5703 digital data
output delay. Table 2 lists the values that can be expected for
the indicated timing delays. Refer to the HI5703 data sheet
for additional timing information.
The sample clock and digital output data signals are buffered
using TTL line drivers and are made available through two
connectors contained on the evaluation board. The line buffering allows for driving long leads or analyzer inputs. These
drivers are not necessary for the digital output data if the
load presented to the converter does not exceed the the
data sheet load limits of one standard TTL load and 20pF.
P1 allows the evaluation board to be interfaced to the DSP
evaluation boards available from Intersil. The digital output
data and sample clock can also be accessed by clipping the
test leads of a logic analyzer or data acquisition system onto
the I/O pins of connector P2. As was mentioned earlier, the
A/D converters OE control input pin allows the digital output
data bus to be switched to a three-state high impedance
mode. This feature enables the testing and debugging of
systems which are utilizing one or more converters. This
three-state control signal is not intended for use as an
enable/disable function on a common data bus and could
result in possible bus contention issues.
TABLE 2. TIMING SPECIFICATIONS
PARAMETER
DESCRIPTION
-
7ns
-
tPD1
U3 Prop Delay
-
4.5ns
7.0ns
tPD2
U6 Prop Delay
1.5ns
3.0ns
5.0ns
tPD3
U6/U7 Prop Delay
1.5ns
3.0ns
5.0ns
Analog Input
The fully differential analog input of the HI5703 A/D can be
configured in various ways depending on the signal source
and the required level of performance.
HI5703 SAMPLE
CLOCK INPUT
tOD
DATA N-1
DATA N
tPD2
CLOCK OUT
(74F541)
tPD3
DATA N-1
DATA N
FIGURE 3. EVALUATION BOARD CLOCK/DATA TIMING
5
MAX
HI5703 Digital Output
Data Delay
tPD1
DATA OUT
(74F541)
TYP
tOD
CLK
INPUT
HI5703 DIGITAL
DATA OUTPUT
MIN
Application Note 9534
Differential Analog Input Configuration
VIN
A fully differential connection (Figure 4) will yield the best
performance from the converter. Since the HI5703 is
powered off a single +5V supply, the analog input must
have an offset that is within the analog input common mode
voltage range. The performance of the ADC does not
change significantly with the value of the analog input
common mode voltage. Assume the difference between the
HI5703 reference voltage inputs, VREF + (typically +3.25V)
and VREF - (typically +2.0V) , is 1.25V. If VIN is a 1.25VP-P
sinewave then VIN+ and VIN- are 1.25VP-P sinewaves
riding on a common mode voltage equal to the converters
DC bias voltage output, VDC . The converter will be at
positive fullscale when the VIN+ input is at VDC + 0.625V
and the VIN- input is at VDC- 0.625V (VIN+ - VIN- =
+1.25V). Conversely, the converter will be at negative
fullscale when the VIN+ input is equal to VDC- 0.625V and
the VIN- input is at VDC + 0.625V (VIN+ - VIN- = -1.25V).
Consequently, the HI5703 analog input has a fully
differential input voltage range of ±1.25V. It should be noted
that overdriving the analog input beyond the ±1.25V
fullscale input voltage range will not damage the converter
as long as the overdrive voltage stays within the converters
analog supply voltages. In the event of an overdrive
condition the converter will recover within one sample clock
cycle.
VIN+
VIN
HI5703
VDC
-VIN
VIN -
FIGURE 5. AC COUPLED DIFFERENTIAL INPUTY
Transformer Coupled Input Configuration
A single-ended input will give better overall system performance if it is first converted to differential before driving the
HI5703. An RF transformer can be connected to the HI5703
input, as shown in Figure 5, to provide the single-ended to
differential conversion. The particular transformer used will
depend on the input voltage level, the impedance desired,
and the input frequency range. The transformer will tend to
have a bandpass response making it more suitable for narrow band applications.
6
VIN+
HI5703
VDC
VIN-
FIGURE 6. TRANSFORMER COUPLED INPUT
This is the type of single-ended to differential conversion circuit
that is provided on the HI5703EVAL evaluation board at the
RFIN SMA connector (refer to the HI5703EVAL evaluation
board parts layout and the electrical schematic). The impedance seen looking into the RFIN input connector will be 50Ω
when the transformer installed has a 1:2.5 primary to secondary impedance ratio. This is derived as follows. The 200Ω secondary load (two 100Ω resistors, R8 and R9, connected across
the transformer secondary) are transformed to 80Ω (200/2.5 =
80) at the transformer primary side input. Now, the impedance
seen looking into the RFIN SMA connector is 130Ω (R5) in parallel with 80Ω for an effective impedance of 50Ω. A good candidate transformer for this configuration is the Mini-Circuits
TMO2.5-6T. The TMO2.5-6T transformer provides a 1dB passband from 0.05MHz to 20MHz. Alternate transformers could be
used with minor modifications to the input circuit. For example,
if one desired a higher input frequency range than that provided
by the TMO2.5-6T transformer one could replace the TMO2.56T with a Mini-Circuits TMO4-1. The TMO4-1 transformer provides a 1dB passband from 2MHz to 100MHz. Since this transformer has a 1:4 primary to secondary impedance ratio it would
be necessary to remove R5 to maintain a 50Ω impedance looking into the RFIN SMA input connector, i.e. the 200Ω secondary impedance is now transformed to 50Ω at the transformer
primary side (200/4 = 50).
When using transformer coupling, care should be excersied
in the area of impedance matching or undesirable distortion
components could result from mismatching and affect the
overall measured performance of the converter.
When the single-ended to differential input path (RFIN) is to
be used, install transformer T1 and jumper JP2 or JP3 and
remove jumper JP1. Jumper JP2 is installed if it is desired to
use the +2.8V (typical) DC bias voltage output of the HI5703,
otherwise jumper JP3 is installed and an externally supplied
DC bias voltage is connected to the VDC(EXT) jumper pin.
The acceptable range of VDC(EXT) for a differential input
configuration to the HI5703 and a +5V analog supply voltage
is from +0.625V to +4.375V, i.e. the HI5703 differential analog input common mode voltage range specification. Figure
6 illustrates the differential analog input common mode voltage range that the converter will accomodate.
Application Note 9534
+5V
VIN+
VINVDC = 4.375V
1.25VP-P
VIN+
+5V
+5V
+5V
VIN+ OR VIN-
2.5VP-P
VDC = 3.75V
VIN+ OR VIN-
2.5VP-P
1.25V < VDC < 3.75V
VIN+ OR VIN-
2.5VP-P
VDC = 1.25V
VIN0.625V < VDC < 4.375V
1.25VP-P
VIN+
VINVDC = 0.625V
1.25VP-P
0V
0V
0V
FIGURE 7. DIFFERENTIAL ANALOG INPUT COMMON MODE
VOLTAGE RANGE
0V
FIGURE 9. DC OFFSET VOLTAGE RANGE FOR SINGLEENDED ANALOG INPUT
Single-Ended Input Configuration
The configuration shown in Figure 7 may be used to directly
drive the HI5703 with a single-ended DC coupled input. Sufficient headroom must be provided such that the analog input
voltage never goes above +5V or below AGND. Again,
assume the difference between VREF + and VREF - is 1.25V. If
VIN (and therefore VIN+) is a 2.5VP-P sinewave riding on a
positive voltage equal to VDC, the converter will be at positive
fullscale when VIN+ is at VDC + 1.25V (VIN+ - VIN- = +1.25V)
and will be at negative fullscale when VIN+ is equal to
VDC -1.25V (VIN+ - VIN- = -1.25V). Consequently, the HI5703
analog input has a single-ended input voltage range of 2.5VPP. In this case, with a +5V analog supply voltage, VDC could
range between 1.25V and 3.75V (see Figure 8). Optimum single-ended performance can be obtained with a DC bias voltage, VDC, of 1.8V. It should be noted that overdriving the
analog input beyond the 2.5VP-P fullscale input voltage range
will not damge the converter as long as the overdrive voltage
stays within the converters analog supply voltages. In the
event of an overdrive condition the converter will recover
within one sample clock cycle.
VIN
VIN+
VDC
R
HI5703
VDC
VIN-
FIGURE 8. DC COUPLED SINGLE-ENDED INPUT
7
Video Input Configuration
The HI5703EVAL evaluation board provides a single-ended,
DC coupled input at the VIDEO SMA input connector (refer
to the HI5703EVAL evaluation board parts layout and the
electrical schematic). This input drive configuration consists
of an inverting buffer circuit (HFA1102 operational amplifier,
U2) which will amplify and DC offset (adjustable via potentiometer R12) video signals to the analog input of the HI5703.
The nominal input impedance seen at this input connector is
75Ω. This will allow most commercially available video
sources to drive the evaluation board directly. When utilizing
this analog input path install jumper JP1 and remove RF
transformer T1 and jumpers JP2 and JP3.
For a single-ended, DC coupled VIDEO input the following
procedure can be used to adjust the input analog signal level
and DC offset (R12) to obtain a 0V to +2.5V (2.5VP-P) AC
signal swing into the converter. Initially set the DC offset
potentiometer (R12) to 0V by turning the potentiometer
adjustment screw clockwise (CW) until the potentiometer
CW stops are felt. Using an oscilloscope, monitor the signal
level at the JP1 jumper pin connected to R7 (JP1 jumper
must be removed). Adjust the analog input signal level until a
(1.39 x 2.5VP-P) = 3.475VP-P signal is obtained on the oscilloscope. The scaling factor of 1.39 is a result of the AC voltage division between R9 (100Ω) and R7 (39Ω). Adjust the
DC offset, using potentiometer R12, so the signal at JP1
swings between -0.487V and +2.988V. The DC offset can be
adjusted further, for example, to provide a signal at JP1 that
swings between +0V and +3.475V, but one should not let the
peak signal at JP1 go much beyond the +3.5V level since the
signal at the output of the HFA1102 operational amplifier
(U2) will start running into the operational amplifier output
voltage limit and cause signal distortion. Now reinstall
jumper JP1. Using an oscilloscope to look at the signal on
JP1, verify the signal into the converter is swinging between
0V and +2.5V. Make any minor adjustments to the input signal level or the DC offset as required. In addition, the input
signal bandwidth should be kept below approximately
7.5MHz in order to avoid operational amplifier induced harmonic distortion.
Application Note 9534
HI5703 Performance Characterization
Dynamic testing is used to evaluate the HI5703 performance. Among these tests are Signal-to-Noise Ratio (SNR),
Signal-to-Noise and Distortion Ratio (SINAD), Total Harmonic Distortion (THD), Spurious Free Dynamic Range
(SFDR) and InterModulation Distortion (IMD).
Figure 9 shows the test system used to perform dynamic
testing on high-speed ADC’s at Intersil. The clock (CLK) and
analog input (AIN) signals are sourced from low phase noise
HP8662A synthesized signal generators that are phase
locked to each other to ensure coherence. The output of the
signal generator driving the ADC analog input is bandpass
filtered to improve the harmonic distortion of the analog input
signal. The comparator on the evaluation board will convert
the sine wave CLK input signal to a square wave at TTL logic
levels to drive the sample clock input of the HI5703. The
ADC data is captured by a logic analyzer and then transferred over the GPIB bus to the PC. The PC has the required
software to perform the Fast Fourier Transform (FFT) and do
the data analysis.
Coherent testing is recommended in order to avoid the inaccuracies of windowing. The sampling frequency and analog
input frequency have the following relationship: FI/FS = M/N,
where FI is the frequency of the input analog sinusoid, FS is
the sampling frequency, N is the number of samples, and M
is the number of cycles over which the samples are taken.
By making M an integer and odd number (1, 3, 5, ...) the
samples are assured of being nonrepetitive.
Refer to the HI5703 data sheet for a complete list of test definitions and the results that can be expected using the evaluation board with the test setup shown. Evaluating the part
with a reconstruction DAC is only suggested when doing
bandwidth or video testing.
Video Testing
Finally, mate the DAC reconstruction board P1 connector to
the HI5703EVAL evaluation board P2 connector. Correct
alignment between the two boards will have P1 pin 34 of the
DAC reconstruction board plugged into P2 pin 25 of the
HI5703EVAL evaluation board.
See Application Note AN9419 “Using the DAC Reconstruct
Board” for additional applications information.
HP8662A
HP8662A
REF
BANDPASS
FILTER
CLK
RFIN
COMPARATOR
VIN
HI5703
CLK
DIGITAL DATA OUTPUT
HI5703EVAL
EVALUATION BOARD
10
DAS9200
12-BIT DAC
GPIB
PC
OSCILLOSCOPE
FIGURE 10. HIGH-SPEED A/D TEST SYSTEM
VIDEO
SIGNAL
SOURCE
CLOCK
GEN
CLK
Figure 10 shows how a test system can be configured to do
video testing of the HI5703 with the DAC reconstruction
board and the HI5703EVAL evaluation board. The appropriate test waveform is generated by a video source such as
the TSG100 or TEK1001 from Tektronix and applied to the
converter. The digitized video is converted back to analog by
the reconstruction DAC for evaluation by a video analyzer,
TEK VM700.
Since the HI5703 is a 10-bit A/D, install jumpers JP1 and
JP2 on the DAC reconstruction board to tie the DAC two
LSB’s high. Install JP3 so that the video out of the reconstruction board will have negative going sync. JP5-9 on the
DAC reconstruction board are utilized to establish the correct
clock/data timing relationship into the DAC.
Setup the HI5703EVAL evaluation board for video testing by
following the procedures outlined previously in the
HI5703EVAL evaluation board application note on the video
input configuration and single-ended DC coupled analog
inputs. Input the video signal to the HI5703EVAL evaluation
board through the SMA connector marked VIDEO. Note that
all cables carrying video should be 75Ω.
8
VIDEO
COMPARATOR
VIN
HI5703
CLK
DIGITAL DATA OUTPUT
HI5703EVAL
EVALUATION BOARD
10 (P2)
12-BIT DAC
RECONSTRUCT BOARD
(DACRECON-EV)
VIDEO
TEK
VM700
FIGURE 11. VIDEO TEST SETUP
Application Note 9534
TABLE 3. HI5703 PIN DESCRIPTION
PIN NO.
NAME
DESCRIPTION
1
DVCC1
Digital Supply
2
DGND
Digital Ground
3
DVCC1
Digital Supply
4
DGND
Digital Ground
5
AVCC
Analog Supply
6
AGND
Analog Ground
7
VREF+
Positive Reference Voltage Input
8
VREF -
Negative Reference Voltage Input
9
VIN+
Positive Analog Input
10
VIN-
Negative Analog Input
11
VDC
DC Bias Voltage Output
12
AGND
Analog Ground
13
AVCC
Analog Supply
14
OE
Digital Output Enable Control Input
15
DFS
Data Format Select Input
16
D9
Data Bit 9 Output (MSB)
17
D8
Data Bit 8 Output
18
D7
Data Bit 7 Output
19
D6
Data Bit 6 Output
20
D5
Data Bit 5 Output
21
DGND
22
CLK
23
DVCC2
24
D4
Data Bit 4 Output
25
D3
Data Bit 3 Output
26
D2
Data Bit 2 Output
27
D1
Data Bit 1 Output
28
D0
Data Bit 0 Output (LSB)
Digital Ground
Sample Clock Input
Digital Output Supply (+3.3V to +5V)
9
Application Note 9534
FIGURE 11. HI5703EVAL EVALUATION BOARD PARTS LAYOUT
FIGURE 12. HI5703EVAL EVALUATION BOARD COMPONENT SIDE
10
Application Note 9534
FIGURE 13. HI5703EVAL EVALUATION BOARD GROUND LAYER
FIGURE 14. HI5703EVAL EVALUATION BOARD SOLDER SIDE
11
Application Note 9534
HI5703EVAL Evaluation Board Schematic Diagrams
C5
RFIN
2
1 T1
4
R5
130
R8
100
+
10µF
C2
R9
100
6
7, 8
VR
0.01µF
CCW
VIN+
JP2
AVCC2
C4
0.1µF
CW
DVCC1
3
2
R21
VIDEO
U2
1
7
VIN - 10 V IN
VREF + 7 V
REF +
VREF - 8 V
-
R22
DVCC2
499
3
23
13
5
HI5703
REF
1
CLK
U3
5
V+
2
R6
51
3
R1
DVCC2
820 R2
R3 2K
LE
+
Q
Q
- GND
V6
4
C1
0.1µF
DVEE
820
22
TP1
DVCC2 R4
8
1K
CLOCK
7
JP4
15
16
17
18
19
20
24
25
26
27
28
D9
D8
D7
D6
D5
D4
D3
D2
D1
D0
DC
HFA1102
AVEE
AVCC1
JP8
VIN + 9 V +
IN
VDC 11 V
39
4
R10 200
130
VIN-
DVCC1 DVCC1DVCC2 AVCCAVCC
R7
6
+
-
C3
33pF
VDC
(EXT)
JP3
JP1
R12
10K
VDC
CLK
DFS
DGND
AGND
DGND
DGND AGND OE
2
4
21 6 12 14
AD9696
U1
JP7
DVEE
AVCC2
R14
1
2 +
-
4 CA158A
AVEE
AVCC2
2
4
VIN
GND
0.01µF
10K
U4
VOUT
TRIM
REF03
5
R11
10K
8
5
R17
51
4 CA158A
JP6
+ C11
10µF
C8
0.01µF
R19
10K
VREF +
2.0V
U5B
7
6 +
-
C6
0.1µF
C10
0.1µF
R16
AVCC2
AVEE
12
+ C9
10µF
15K
R13
8.2K
6
JP5
51
C7
R15
VR
3.25V
U5A
8
3
R18
10K
C12
0.1µF
VREF -
D9
D8
D7
D6
D5
D4
D3
D2
D1
D0
Application Note 9534
HI5703EVAL Evaluation Board Schematic Diagrams
U7
D0
D1
D2
D3
D4
D5
D6
D7
2
3
4
5
6
7
8
9
1
19
P2
Y1
Y2
Y3
Y4
Y5
Y6
Y7
Y8
A1
A2
A3
A4
A5
A6
A7
A8
(Continued)
18
17
16
15
14
13
12
11
DOUT0
DOUT1
DOUT2
DOUT3
DOUT4
DOUT5
DOUT6
DOUT7
G1
G2
74F541
DOUT0
1
DOUT1
3
DOUT2
5
DOUT3
7
DOUT4
9
DOUT5
11
DOUT6
13
DOUT7
15
DOUT8
17
DOUT9
19
21
CLKOUT
23
25
P1C
2
4
6
8
10
12
14
16
18
20
22
24
DOUT1
DOUT2
DOUT4
DOUT6
DOUT8
U8
D8
D9
CLOCK
R20
1K
DVCC2
2
3
4
5
6
7
8
9
1
19
A1
A2
A3
A4
A5
A6
A7
A8
Y1
Y2
Y3
Y4
Y5
Y6
Y7
Y8
DOUT8
18
DOUT9
17
16 CLKOUT
15
14
13
12
11
CLKOUT
G1
G2
74F541
FB5
DVCC2
+5V
+5V
AVCC2
+ C13
10µF
+5V
FB4
DVCC1
DVCC2
DVCC1
AVCC1
+ C14
10µF
+5V
DGND
DVEE
FB6
DOUT3
DOUT5
DOUT7
DOUT9
FB1
AVCC2
FB3
AVCC1
FB2
AVEE
+ C29
10µF
AVEE
-5V
DVCC2
DVCC1
C18
0.1µF
U1
C17
0.1µF
U1
AVCC1
C21
0.1µF
U6
DVEE
C31
0.1µF
U3
C22
0.1µF
U7
AVCC2
C24
0.1µF
U1
13
DOUT0
+ C28
10µF
+ C30
10µF
DVEE
-5.2V
C23
0.1µF
U1
C1
C2
C3
C4
C5
C6
C7
C8
C9
C10
C11
C12
C13
C14
C15
C16
C17
C18
C19
C20
C21
C22
C23
C24
C25
C26
C27
C28
C29
C30
C31
C32
AGND
+ C15
10µF
C16
0.1µF
U1
P1A
C25
0.1µF
U2
C26
0.1µF
U5
C27
0.1µF
U3
AVEE
C32
0.1µF
U4
C19
0.1µF
U2
C20
0.1µF
U5
A1
A2
A3
A4
A5
A6
A7
A8
A9
A10
A11
A12
A13
A14
A15
A16
A17
A18
A19
A20
A21
A22
A23
A24
A25
A26
A27
A28
A29
A30
A31
A32
Application Note 9534
HI5703EVAL Evaluation Board Parts List
REFERENCE
DESIGNATOR
QTY
DESCRIPTION
R4, R20
2
1kΩ, 1/8W, 5%
R1, R3
2
820Ω, 1/8W, 5%
R6, R14, R17
3
51Ω, 1/8W, 5%
R18, R19
2
10kΩ, 1/8W, 5%
R8, R9
2
100Ω, 1/8W, 5%
R7
1
39Ω, 1/8W, 5%
R21
1
200Ω, 1/8W, 5%
R16
1
15kΩ, 1/8W, 5%
R13
1
8.2kΩ, 1/8W, 5%
R5, R10
2
130Ω, 1/4W, 5%
R22
1
499Ω, 1206 CHIP
R2
1
2kΩ Trim Pot
R12, R11, R15
3
10kΩ Trim Pot
C5, C9, C11, C13, C14, C15, C19,
C25, C28, C29, C30
11
10µF Tant Cap, 35WVDC, 20%
C2, C7, C8
3
0.01µF Ceramic Cap, 100WVDC, 10%
C33, C34
2
1000pF 1206 Chip Cap, 50WVDC, XR7 10%
C1, C4, C6, C20, C26, C27, C31
7
0.1µF Ceramic Cap, 50WVDC, 10%
C10, C12, C16, C17, C18, C21, C22,
C23, C24, C32
10
0.1µF 1206 Chip Cap, 50WVDC, Z5U, 20%
C3
1
33pF 1206 Chip Cap, 100WVDC, COG(NPO), 5%
FB1-6
6
10µH Ferrite Bead
T1
1
RF Transformer
TP1
1
Probe Tip Adapter
JP1-8
8
1 x 2 Header
J1-8
8
1 x 2 Header Jumper
P2
1
2 x 13 Header
VDC, AGND, DGND
3
Test Point
P1
1
64-Lead DIN RT Angle
SMA1-3
3
SMA, Straight Female Jack PCB MNT
SU2-5, ST1
5
8-Lead Socket
SU6-7
2
20-Lead Socket
U1
1
Intersil HI5703KCB 10-Bit 40MHz A/D Converter
U2
1
Intersil HFA1102IP Operational Amplifier
U3
1
Ultrafast Voltage Comparator
U4
1
+2.5V Precision Voltage Reference
U5
1
Intersil CA158AE Operational Amplifier
U6-7
2
Octal Buffer/Line Driver
All Intersil semiconductor products are manufactured, assembled and tested under ISO9000 quality systems certification.
Intersil semiconductor products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and
reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result
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14
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