AP65453 4A, 18V, 650kHz ADAPTIVE COT STEP-DOWN CONVERTER Description Pin Assignments ADVANCED INFORMATION The AP65453 is an adaptive, constant on-time mode synchronous buck converter providing high efficiency, excellent transient response and high DC output accuracy for low-voltage regulation in digital TVs and monitors. ( Top View ) The constant-on-time control scheme handles wide input/output voltage ratios and provides low external component count. The internal proprietary circuit enables the device to adopt both low equivalent series resistance (ESR) output capacitors, such as SP-CAP or POSCAP and ultra-low ESR ceramic capacitors. EN 1 8 VIN FB 2 7 BS VREG5 3 6 SW SS 4 5 GND SO-8EP The adaptive, constant on-time control supports seamless transition between continuous conduction mode (CCM) at higher load conditions and discontinuous conduction mode (DCM) at lighter load conditions. DCM allows AP65453 to maintain high efficiency at light load conditions. The AP65453 also features programmable soft-start, UVLO, OTP and OCP to protect the circuit. This IC is available in SO-8EP package. Features Applications Gaming Consoles Flat Screen TV Sets and Monitors Set-Top Boxes Distributed Power Systems Home Audio Consumer Electronics Network Systems FPGA, DSP and ASIC Supplies Green Electronics Fixed Frequency Emulated Constant On-time Control Good Stability Independent of the Output Capacitor ESR Fast Load Transient Response Synchronous Rectification: 90mΩ Internal High-side Switch and 57mΩ Internal Low-side Switch Wide Input Voltage Range: 4.5V to 18V Output Voltage Range: 0.76V to 6V 4A Continuous Output Current 650kHz Switching Frequency Built-in Over Current Limit Built-in Thermal Shutdown Protection Programmable Soft-start Pre-biased Start-up Totally Lead-Free & Fully RoHS Compliant (Notes 1 & 2) Halogen and Antimony Free. “Green” Device (Note 3) Notes: 1. No purposely added lead. Fully EU Directive 2002/95/EC (RoHS) & 2011/65/EU (RoHS 2) compliant. 2. See http://www.diodes.com/quality/lead_free.html for more information about Diodes Incorporated’s definitions of Halogen- and Antimony-free, "Green" and Lead-free. 3. Halogen- and Antimony-free "Green” products are defined as those which contain <900ppm bromine, <900ppm chlorine (<1500ppm total Br + Cl) and <1000ppm antimony compounds. AP65453 Document number: DS37999 Rev. 1 - 2 1 of 14 www.diodes.com June 2015 © Diodes Incorporated AP65453 Typical Applications Circuit INPUT VIN 12V ON OFF ADVANCED INFORMATION 7 BST 8 IN 1 EN 6 SW L1 C5 0.1µF 1.5μH AP65453 R1 8.25kΩ R2 22.1kΩ 2 FB C1 20μF 4 SS C4 8.2nF 5 GND 3 VREG5 OUTPUT VOUT 1.05V C2 44μF C3 1µF Figure 1. Typical Application Circuit Pin Descriptions Pin Name Pin Number Function EN 1 Enable input. EN is a digital input that turns the regulator on or off. Drive EN high to turn on the regulator, drive it low to turn off. It can be safely connected to VIN directly for automatic startup. FB 2 Feedback Input. FB senses the output voltage and regulates it. Drive FB with a resistive voltage divider connected to it from the output voltage. VREG5 3 Internal power supply output pin to connect an additional capacitor. Connect a 1μF (typical) capacitor as close as possible to the VREG5 and GND. This pin is not active when EN is low. SS 4 Soft-start control input pin. SS controls the soft start period. Connect a capacitor from SS to GND to set the soft-start period. GND 5 Ground pin is the main power ground for the switching circuit. SW 6 Power Switching Output. SW is the switching node that supplies power to the output. Connect the output LC filter from SW to the output load. Note that a capacitor is required from SW to BS to power the high-side switch. BS 7 Bootstrap pin. A bootstrap capacitor is connected between the BS pin and SW pin. The voltage across the bootstrap capacitor drives the internal high-side NMOS switch. A 0.1μF (typical) capacitor is required for proper operation VIN 8 Supply input pin. A capacitor should be connected between the VIN pin and GND pin to keep the DC input voltage constant. EP - Connect the exposed thermal pad to GND on the PCB. SO-8EP AP65453 Document number: DS37999 Rev. 1 - 2 2 of 14 www.diodes.com June 2015 © Diodes Incorporated AP65453 ADVANCED INFORMATION Functional Block Diagram Figure 2. Functional Block Diagram AP65453 Document number: DS37999 Rev. 1 - 2 1 of 14 www.diodes.com June 2015 © Diodes Incorporated AP65453 Absolute Maximum Ratings (Note 4) (@TA = +25°C, unless otherwise specified.) Symbol ADVANCED INFORMATION VIN Parameter Rating Unit -0.3 to 20 V -0.3V to +6.0 V Supply Voltage VREG5 VREG5 Pin Voltage VSW Switch Node Voltage -1.0 to VIN +0.3 V VBS Bootstrap Voltage -0.3 to VSW +6.0 V VFB Feedback Voltage -0.3V to +6.0 V VEN Enable/UVLO Voltage -0.3V to VIN V VSS Soft-start PIN -0.3V to +6.0 V GND Pin Voltage -0.3 to 0.3 V TST Storage Temperature -65 to +150 °C TJ Junction Temperature +160 °C +260 °C 2 200 kV V VGND Lead Temperature TL ESD Susceptibility (Note 5) HBM Human Body Model MM Machine Model Notes: 4. Stresses greater than the 'Absolute Maximum Ratings' specified above may cause permanent damage to the device. These are stress ratings only; functional operation of the device at these or any other conditions exceeding those indicated in this specification is not implied. Device reliability may be affected by exposure to absolute maximum rating conditions for extended periods of time. 5. Semiconductor devices are ESD sensitive and may be damaged by exposure to ESD events. Suitable ESD precautions should be taken when handling and transporting these devices. Thermal Resistance (Note 6) Note: Symbol Parameter Rating Unit JA Junction to Ambient SO-8EP 38.56 °C/W JC Junction to Case SO-8EP 6.85 °C/W 6. Test condition: SO-8: Device mounted on 1" x 1" FR-4 substrate PCB, 2oz copper, with minimum recommended pad layout. Recommended Operating Conditions (Note 7) (@TA = +25°C, unless otherwise specified.) Symbol Note: Min Max VIN Supply Voltage Parameter 4.5 18.0 Unit V TJ Operating Junction Temperature Range -40 +125 °C TA Operating Ambient Temperature Range -40 +85 °C 7. The device function is not guaranteed outside of the recommended operating conditions. AP65453 Document number: DS37999 Rev. 1 - 2 2 of 14 www.diodes.com June 2015 © Diodes Incorporated AP65453 Electrical Characteristics Parameter SUPPLY VOLTAGE (VIN PIN) Input Voltage ADVANCED INFORMATION Quiescent Current (@TA = +25°C, VIN = 12V, unless otherwise specified.) Symbol Conditions Min Typ Max Unit VIN VFB=0.85V 4.5 - - IQ 0.6 18 0.75 mA - 1 10 μA 3.6 3.85 4.1 V 0.16 0.35 0.47 V - 18 V - 0.85 V Shutdown Supply Current UNDER VOLTAGE LOCKOUT ISHDN UVLO Threshold VUVLO UVLO Hysteresis VHYS ENABLE (EN PIN) EN High-level Input Voltage VENH - VENL - 1.25 - EN Low-level Input Voltage VOLTAGE REFERENCE (FB PIN) Feedback Voltage VEN=0V VIN Rising Test VREG5 Voltage VIN Falling Test VREG5 Voltage V VFB VOUT=1.05V 0.753 0.765 0.777 V Feedback Bias Current VREG5 OUTPUT IFB VFB=0.8V -0.1 0 0.1 μA VREG5 Output Voltage VVREG5 6.0V<VIN<18V 0<IVREG5<5mA 4.8 5.1 5.4 V VIN=6V, VVREG5=4V - mA 0<IVREG5<5mA 100 - - - 100 mV 6.0V<VIN<18V IVREG5=5mA - - 20 mV Source Current Capability - Load Regulation - Line Regulation MOSFET High-side Switch On-resistance RDSONH - - 0.090 - Ω Low-side Switch On-resistance RDSONL - - 0.057 - Ω 4.6 5.6 6.9 A VIN=12V, VOUT=1.05V - 150 - ns VFB=0.7V - 260 310 ns TOTSD - - 150 - °C THYS - - 25 - °C μA mA % CURRENT LIMIT High Level Current Limit ON-TIME TIMER On-Time Minimum Off-Time THERMAL SHUTDOWN Thermal Shutdown Thermal Shutdown Hysteresis SOFT START (SS PIN) Soft-start Source Current Soft-start Discharge Current OVER VOLTAGE PROTECTION OVP Trip Threshold AP65453 Document number: DS37999 Rev. 1 - 2 ILIM-H tON tOFF-MIN L=1.5μH ISS-SOURCE VSS=1.0V 4.2 6.0 ISS-DISCHARGE VSS=0.5V 0.1 0.2 7.8 - - 115 120 125 - 3 of 14 www.diodes.com June 2015 © Diodes Incorporated AP65453 Typical Performance Characteristics (@TA = +25°C, VIN = 12V, VOUT = 1.05V, unless otherwise specified.) ADVANCED INFORMATION 85˚C 25˚C -40˚C 85˚C 25˚C -40˚C IO=10mA VIN=18V VIN=12V VIN=4.5V IO=1A AP65453 Document number: DS37999 Rev. 1 - 2 4 of 14 www.diodes.com June 2015 © Diodes Incorporated AP65453 Typical Performance Characteristics (continued) (@TA = +25°C, VIN = 12V, VOUT = 1.05V, unless otherwise specified.) Vo=3.3V Vo=2.5V VO=2.5V ADVANCED INFORMATION VO=3.3V VO=5.0V VO=5.0V VO=3.3V VO=2.5V VO=1.05V VO=1.8V VO=1.2V VO=1.8V VO=2.5V VO=3.3V VO=1.2V VO=1.05V AP65453 Document number: DS37999 Rev. 1 - 2 5 of 14 www.diodes.com June 2015 © Diodes Incorporated AP65453 Typical Performance Characteristics (cont.) (@TA = +25°C, VIN = 12V, VOUT = 1.05V, L = 1.5µH, C1 = 20µF, C2 = 44µF, unless otherwise specified.) Startup Through VEN 4A Load Startup Through VIN 4A Load Short Circuit Test ADVANCED INFORMATION VOUT (500mV/DIV) VEN (5V/DIV) VIN (12V/DIV) VOUT (1V/DIV) VOUT (1V/DIV) IOUT (4A/DIV) IOUT (4A/DIV) SW (10V/DIV) SW (10V/DIV) IOUT (2A/DIV) Time-1ms/div Shutdown Through VEN 4A Load VEN (5V/DIV) Time-1ms/div Time-200µs/div Shutdown Through VIN 4A Load Short Circuit Recovery VIN (12V/DIV) VOUT (500mV/DIV) VOUT (1V/DIV) VOUT (1V/DIV) IOUT (4A/DIV) IOUT (4A/DIV) SW (10V/DIV) IOUT (2A/DIV) SW (10V/DIV) Time-50µs/div Time-200µs/div Load Transient Response (0 to 4A) Load Transient Response (1 to 4A) Time-1ms/div Switching State 4A Load VOUT_AC (50mV/DIV) VOUT_AC (50mV/DIV) VOUT_AC (50mV/DIV) IL (2A/DIV) IOUT (2A/DIV) IOUT (2A/DIV) Time-100µs/div Time-100µs/div Time-1µs/div Startup with VREG5 DCM Voltage Ripple (IO=30mA) Voltage Ripple at Input (IO=4A) EN (5V/DIV) VIN_AC (100mV/DIV) VOUT_AC (100mV/DIV) VREG5 (5V/DIV) IL (2A/DIV) VOUT (500mV/DIV) SW (5V/DIV) Time-1ms/div AP65453 Document number: DS37999 Rev. 1 - 2 Time-1µs/div 6 of 14 www.diodes.com Time-1µs/div June 2015 © Diodes Incorporated AP65453 Application Information VIN EN 1 R1 VOUT VIN BS FB 3 C7 4 C5 1µF VREG5 SW SS C4 8.2nF 8 C2 10µF C6 AP65453 2 8.25KΩ R2 22.1KΩ ADVANCED INFORMATION EN C1 10µF GND 7 6 0.1µF VOUT 1.5µH L1 5 EP C8 22µF C9 22µF Figure 3. Typical Application of AP65453 evaluation board PWM Operation and Adaptive On-time Control The AP65453 is a synchronous step-down converter with internal power MOSFETs. Adaptive constant on time (COT) control is employed to provide fast transient response and easy loop stabilization. At the beginning of each cycle, the high-side MOSFET is turned on. This MOSFET is turned off after an internal one-shot timer expires. This one shot is set by the converter input voltage (VIN), and the output voltage (VOUT) to maintain a pseudo-fixed frequency over the input voltage range, hence it is called adaptive on-time control. The output voltage variation is sensed by FB voltage. The one-shot timer is reset and the high-side MOSFET is turned on again when FB voltage falls below the 0.76V. AP65453 uses an adaptive on-time control scheme and does not have a dedicated in board oscillator. It runs with a pseudo-constant frequency of 650kHz by using the input voltage and output voltage to set the on-time one-shot timer. The on-time is inversely proportional to the input voltage and proportional to the output voltage. It can be calculated using the following equation: TON VOUT VIN f VOUT is the output voltage VIN is the input voltage f is the switching frequency After an ON-time period, the AP65453 goes into the OFF-time period. The OFF-time period length depends on VFB in most cases. It will end when the FB voltage decreases to below 0.76V at which time the ON-time period is triggered. If the OFF-time period is less than the minimum OFF time, the minimum OFF time will be applied, which is about 260ns typical. Power Save Mode The AP65453 is designed with Power Save Mode (PSM) at light load conditions for high efficiency. The AP65453 automatically reduces the switching frequency and changes the Ton time to Tmin-on time during a light load condition to get high efficiency and low output ripple. As the output current decreases from heavy load conditions, the inductor current decreases as well, and eventually comes close to zero current, which is the boundary between CCM and DCM. The low side MOSFET is turned off when the inductor current reaches a level of zero. The load is provided only by output capacitor, when FB voltage is lower than 0.76V, the next cycle ON cycle is beginning. The on-time is the minimum value that improves VOUT ripple at the light load condition. When the output current increases from light to heavy load, the switching frequency increases to keep output voltage. The transition point to light load operation can be calculated using the following equation: I LOAD VIN VOUT TON 2L TON is on-time Enable Above the ‘EN high-level input voltage’, the internal regulator is turned on and the quiescent current can be measured above this threshold. The enable (EN) input allows the user to control turning on or off the regulator. To enable the AP65353, EN must be pulled above the ‘EN high-level input voltage.’ To disable the AP65353, EN must be pulled below ‘EN low-level input voltage.’ In Figure 3, EN is a high voltage input that can be safely connected to VIN (up to 18V) for automatic start-up. AP65453 Document number: DS37999 Rev. 1 - 2 8 of 14 www.diodes.com June 2015 © Diodes Incorporated AP65453 Application Information (continued) Soft-Start ADVANCED INFORMATION The soft-start time of the AP65453 is programmable by selecting different CSS values. When the EN pin becomes high, the CSS is charged by a 6μA current source, generating a ramp signal fed into non-inverting input of the error comparator. Reference voltage VREF or the internal soft-start voltage SS, (whichever is smaller), dominates the behavior of the non-inverting inputs of the error amplifier. Accordingly, the output voltage will follow the SS signal and ramp up smoothly to its target level. The capacitor value required for a given soft-start ramp time can be expressed as: t SS CSS VFB I SS Where CSS is the required capacitor between SS pin and GND, tSS is the desired soft-start time and VFB is the feedback voltage. Overcurrent Protection (OCP) Figure 4 shows the overcurrent protection (OCP) scheme of AP65453. In each switching cycle, the inductor current is sensed by monitoring the low-side MOSFET in the OFF period. When the voltage between GND pin and SW pin is smaller than the overcurrent trip level, the OCP will be triggered and the controller keeps the OFF state. A new switching cycle will begin when the measured voltage is larger than limit voltage. The internal counter is incremented when OCP is triggered. After 16 sequential cycles, the internal OCL (Overcurrent Logic) threshold is set to a lower level, reducing the available output current. When a switching cycle occurs where the switch current is below the lower OCL threshold, the counter is reset and the OCL limit is returned to a higher value. Because the RDS(ON) of MOSFET increases with temperature, VLimit has xppm/°C temperature coefficient to compensate this temperature dependency of RDS(ON). R S Q1 Q -266mV OC COMPARATOR Q2 Figure 4. Over Current Protection Scheme Undervoltage Lockout The AP65453 provides an undervoltage lockout circuit to prevent it from undefined status during startup. The UVLO circuit shuts down the device when VIN drops below 3.45V. The UVLO circuit has 320mV hysteresis, which means the device starts up again when V REG rise to 3.75V (nonlatch). Thermal shutdown If the junction temperature of the device reaches the thermal shutdown limit of +160°C, the AP65453 shuts itself off, and both HMOS and LMOS will be turned off. The output is discharged with the internal transistor. When the junction cools to the required level (+130°C nominal), the device initiates soft-start as during a normal power-up cycle. Setting the Output Voltage The output voltage can be adjusted from 1.000 to 5V using an external resistor divider. Table 1 shows a list of resistor selection for common output voltages. Resistor R1 is selected based on a design tradeoff between efficiency and output voltage accuracy. For high values of R1 there is less current consumption in the feedback network. However the tradeoff is output voltage accuracy due to the bias current in the error amplifier. R1 can be determined by the following equation: V R1 R 2 OUT 1 0.765 AP65453 Document number: DS37999 Rev. 1 - 2 9 of 14 www.diodes.com June 2015 © Diodes Incorporated AP65453 ADVANCED INFORMATION Application Information (cont.) Figure 5 Feedback Divider Network Output Voltage (V) R1 (kΩ) R2 (kΩ) 1 6.81 22.1 1.05 8.25 22.1 1.2 12.7 22.1 1.5 21.5 22.1 1.8 30.1 22.1 2.5 49.9 22.1 3.3 73.2 22.1 5 124 22.1 Table 1 Resistor Selection for Common Output Voltages Inductor Calculating the inductor value is a critical factor in designing a buck converter. For most designs, the following equation can be used to calculate the inductor value: L VOUT (VIN VOUT ) VIN ΔIL fSW Where ΔIL is the inductor ripple current and fSW is the buck converter switching frequency. Choose the inductor ripple current to be 30% of the maximum load current. The maximum inductor peak current is calculated from: IL(MAX) ILOAD ΔIL 2 Peak current determines the required saturation current rating, which influences the size of the inductor. Saturating the inductor decreases the converter efficiency while increasing the temperatures of the inductor and the internal MOSFETs. Hence, choosing an inductor with appropriate saturation current rating is important. A 1µH to 3.3µH inductor with a DC current rating of at least 25% higher than the maximum load current is recommended for most applications. For highest efficiency, the inductor’s DC resistance should be less than 100mΩ. Use a larger inductance for improved efficiency under light load conditions. The phase boost can be achieved by adding an additional feed forward capacitor (C7) in parallel with R1. Output Voltage (V) C7(pF) L1(µH) C8+C9(µF) 1 1.0-1.5 22-68 1.05 1.0-1.5 22-68 1.2 1.0-1.5 22-68 1.5 1.5 22-68 1.8 5-22 1.5 22-68 2.5 5-22 2.2 22-68 3.3 5-22 2.2 22-68 5 5-22 3.3 22-68 Table 2. Recommended Component Selection Input Capacitor The input capacitor reduces the surge current drawn from the input supply and the switching noise from the device. The input capacitor has to sustain the ripple current produced during the on time on the upper MOSFET. It must have a low ESR to minimize the losses. The RMS current rating of the input capacitor is a critical parameter that must be higher than the RMS input current. As a rule of thumb, select an input capacitor which has an RMs rating that is greater than half of the maximum load current. Due to large dI/dt through the input capacitors, electrolytic or ceramics should be used. If a tantalum must be used, it must be surge protected. Otherwise, capacitor failure could occur. For most applications, a ceramic capacitor greater than 10µF is sufficient. AP65453 Document number: DS37999 Rev. 1 - 2 10 of 14 www.diodes.com June 2015 © Diodes Incorporated AP65453 Application Information (cont.) Output Capacitor The output capacitor keeps the output voltage ripple small, ensures feedback loop stability and reduces the overshoot of the output voltage. The output capacitor is a basic component for the fast response of the power supply. In fact, during load transient, for the first few microseconds it supplies the current to the load. The converter recognizes the load transient and sets the duty cycle to maximum, but the current slope is limited by the inductor value. ADVANCED INFORMATION Maximum capacitance required can be calculated from the following equation: ESR of the output capacitor dominates the output voltage ripple. The amount of ripple can be calculated from the equation below: Vout capacitor ΔIinductor * ESR An output capacitor with ample capacitance and low ESR is the best option. For most applications, a 22µF to 68µF ceramic capacitor will be sufficient. ΔIinductor 2 ) 2 Co 2 (Δ V Vout ) 2 Vout L(I out Where ΔV is the maximum output voltage overshoot. Bootstrap Capacitor To ensure the proper operation, a ceramic capacitor must be connected between the VBST and SW pin. A 0.1µF ceramic capacitor is sufficient. External Bootstrap Diode It is recommended to add an external bootstrap diode between an external 5V and the BS pin for efficiency improvement when input voltage is lower than 5.5V. The bootstrap diode can be a low cost one such as 1N4148 or BAT54. The external 5V can be a 5V fixed input from the system or a 5V output of the AP65453. Note that the external bootstrap voltage must be lower than 5.5V. Figure 6 External Bootstrap Diode VREG5 Capacitor To ensure the proper operation, a ceramic capacitor must be connected between the VREG5 and GND pin. A 1µF ceramic capacitor is sufficient. PC Board Layout 1. 2. 3. 4. 5. 6. 7. The AP65453 works at a 4A load current, heat dissipation is a major concern in layout the PCB. A 2oz Copper in both top and bottom layer is recommended. Provide sufficient vias in the thermal exposed pad for heat dissipate to the bottom layer. Provide sufficient vias in the Output capacitor GND side to dissipate heat to the bottom layer. Make the bottom layer under the device as GND layer for heat dissipation. The GND layer should be as large as possible to provide better thermal effect. Make the Vin capacitors as close to the device as possible. Make the VREG5 capacitor as close to the device as possible. The thermal pad of the device should be soldered directly to the PCB exposed copper plane to work as a heatsink. The thermal vias in the exposed copper plane increase the heat transfer to the bottom layer. Figure 7 PC Board Layout AP65453 Document number: DS37999 Rev. 1 - 2 11 of 14 www.diodes.com June 2015 © Diodes Incorporated AP65453 Ordering Information ADVANCED INFORMATION AP65453 XX - 13 Package Packing SP : SO-8EP 13 : Tape & Reel Part Number Package Code Part Marking Identification Code AP65453SP-13 SP SO-8EP - Tape and Reel Quantity Part Number Suffix 2,500 -13 Marking Information SO-8EP ( Top View ) 5 8 Logo Part No YY : Year : 14,15,16~ WW : Week : 01~52; 52 represents 52 and 53 week X X : Internal Code AP65453 YY WW X X E E : SO-8EP 1 4 Package Outline Dimensions (All dimensions in mm.) Please see AP02002 at http://www.diodes.com/datasheets/ap02002.pdf for the latest version. Exposed Pad 8 5 E1 1 H 4 F b Bottom View E 9° (All sides) N 7° A e A1 D AP65453 Document number: DS37999 Rev. 1 - 2 45° Q C 4° ± 3° Gauge Plane Seating Plane E0 L 12 of 14 www.diodes.com SO-8EP (SOP-8L-EP) Dim Min Max Typ A 1.40 1.50 1.45 A1 0.00 0.13 b 0.30 0.50 0.40 C 0.15 0.25 0.20 D 4.85 4.95 4.90 E 3.80 3.90 3.85 E0 3.85 3.95 3.90 E1 5.90 6.10 6.00 e 1.27 F 2.75 3.35 3.05 H 2.11 2.71 2.41 L 0.62 0.82 0.72 N 0.35 Q 0.60 0.70 0.65 All Dimensions in mm June 2015 © Diodes Incorporated AP65453 Suggested Pad Layout Please see AP02001 at http://www.diodes.com/datasheets/ap02001.pdf for the latest version. ADVANCED INFORMATION X2 Dimensions Value(in mm) C 1.270 X 0.802 X1 3.502 X2 4.612 Y 1.505 Y1 2.613 Y2 6.500 Y1 Y2 X1 Y C X IMPORTANT NOTICE DIODES INCORPORATED MAKES NO WARRANTY OF ANY KIND, EXPRESS OR IMPLIED, WITH REGARDS TO THIS DOCUMENT, INCLUDING, BUT NOT LIMITED TO, THE IMPLIED WARRANTIES OF MERCHANTABILITY AND FITNESS FOR A PARTICULAR PURPOSE (AND THEIR EQUIVALENTS UNDER THE LAWS OF ANY JURISDICTION). Diodes Incorporated and its subsidiaries reserve the right to make modifications, enhancements, improvements, corrections or other changes without further notice to this document and any product described herein. Diodes Incorporated does not assume any liability arising out of the application or use of this document or any product described herein; neither does Diodes Incorporated convey any license under its patent or trademark rights, nor the rights of others. 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Copyright © 2015, Diodes Incorporated www.diodes.com AP65453 Document number: DS37999 Rev. 1 - 2 13 of 14 www.diodes.com June 2015 © Diodes Incorporated