CHERRY CS5231

CS5231-3
CS5231-3
500mA, 3.3V Linear Regulator
with Auxiliary Control
Features
Description
The CS5231-3 combines a threeterminal linear regulator with circuitry to control an external PFET
transistor with the intent of managing two input supplies. A 5V supply powers the regulator while an
auxiliary 3.3V supply is controlled
by the IC. The design has been optimized to provide a “glitch-free”
transition between the two supplies.
The CS5231-3 linear regulator provides a fixed 3.3V output @ 500mA
with an overall accuracy of ± 2%.
The NPN-PNP composite pass transistor provides a low dropout voltage and requires less supply current than PNP designs. Full protection including current limit and
thermal shutdown is provided.
Also designed for low reverse current, the IC prevents excessive cur-
rent from flowing from the output
to ground if the regulator input
voltage is lower than the output
voltage.
The CS5231-3 also controls an auxiliary supply that can provide power
to the regulator output when input
voltage for the regulator is not
available. The AuxDrv auxiliary
output is normally pulled up to the
regulator input voltage and drives
low whenever the input voltage
drops below 4.4V (nominal). It is
typically used to control a PFET
switch that connects a 3.3V auxiliary supply to the regulator output.
The CS5231-3 is available in a
5-lead D2PAK (TO-263) package.
Applications include Network
Interface Cards (NICs), modem
cards and power supplies with
multiple input sources.
Linear Regulator
■ 3.3V ± 2% Output Voltage
■ 3mA Quiescent Current
@ 500mA
■ Fast Transient Response
■ Current Limit
■ Thermal Shutdown with
Hysteresis
■ 450µA Reverse Output
Current
■ Fast Transient Response
System Power Management
■ Auxiliary Supply Control
Package Options
Block Diagram
5 Lead D2PAK
VOUT
VIN
50kΩ
Internal
Bias
AuxDrv
Current
Limit
−
VIN UV
Comparator
Error
Amp
+
−
Bandgap
Reference
1
1. No Connect
Shutdown
2. VIN
+
10kΩ
VREF
3. Gnd
4. VOUT
5. AuxDrv
Gnd
Thermal
Shutdown
Tab = Gnd
Consult factory for other package
options.
Cherry Semiconductor Corporation
2000 South County Trail, East Greenwich, RI 02818
Tel: (401)885-3600 Fax: (401)885-5786
Email: info@cherry-semi.com
Web Site: www.cherry-semi.com
Rev. 3/31/99
1
A
®
Company
CS5231-3
Absolute Maximum Ratings
Maximum Operating Junction Temperature ..........................................................................................................................150°C
Storage Temperature Range .....................................................................................................................................-65°C to +150°C
Lead Temperature Soldering
Reflow (SMD styles only) ...........................................................................................60 sec. max above 183°C, 230°C peak
ESD Damage Threshold (Human Body Model)....................................................................................................................2kV
PIN SYMBOL
PIN NAME
VMAX
VMIN
ISOURCE
ISINK
VIN
IC Power Input
14V
-0.3V
100mA
Internally
Limited
VOUT
Output Voltage
6V
-0.3V
Internally
Limited
100mA
Auxiliary Drive Output
14V
-0.3V
10mA
50mA
IC Ground
N/A
N/A
N/A
N/A
AuxDrv
Gnd
Electrical Characteristics: 0°C < TA < 70°C, 0°C < TJ < 125°C, 4.75V ≤ VCC < 6V, COUT ≥ 10µF with ESR < 1Ω,
IOUT = 10mA, unless otherwise specified.
PARAMETER
■ Linear Regulator
Output Voltage
Line Regulation
Load Regulation
Ground Current
Reverse Current
Current Limit
Thermal Shutdown
Thermal Shutdown Hysteresis
■ Auxiliary Drive
Upper VIN Threshold
Lower VIN Threshold
VIN Threshold Hysteresis
Output Low Voltage
Output Low Peak Voltage
AuxDrv Current Limit
Response Time
Pull-Up/Down Resistance
TEST CONDITIONS
10mA < IOUT < 500mA
IOUT = 10mA,
VIN = 4.75V to 6V
VIN = 5V,
IOUT = 10mA to 500mA
IOUT = 10mA
IOUT = 500mA
VIN = 0V, VOUT = 3.3V
0V < VOUT < 3.2V
Note 1
Note 1
MIN
TYP
3.234
-2%
3.300
3.366
+2%
V
1
5
mV
5
15
mV
2
3
0.45
0.85
180
25
3
6
1
1.2
210
mA
mA
mA
A
°C
°C
0.55
150
MAX
UNIT
Increase VIN until regulator turns on
and AuxDrv drives high
4.35
4.5
4.65
V
Decrease VIN until regulator turns off
and AuxDrv drives low
4.25
4.4
4.55
V
75
100
0.1
125
0.4
mV
V
0.65
0.9
V
6
25
mA
1
10
µs
10
25
kΩ
IAuxDrv = 100µA,
1V < VIN < 4.5V
Increase VIN from 0V to 1V.
Record peak AuxDrv output voltage
VAuxDrv = 1V,
VIN = 4.0V
Step VIN from 5V to 4V, measure time
for VAuxDrv to drive low. Note 1
VIN = 0V and VIN > 4.7V
0.5
5
Note 1: Guaranteed by design, not 100% production tested. Thermal shutdown is 100% functionally tested at wafer
probe.
2
CS5231-3
Package Pin Description
PACKAGE PIN #
5Lead
D2
PIN SYMBOL
FUNCTION
PAK
1
N/C
No connection.
2
VIN
Input voltage.
3
Gnd
Ground and IC substrate connection (case).
4
VOUT
Regulated output voltage.
5
AuxDrv
Output used to control an auxiliary supply voltage. This lead is
driven low if VIN is less than 4.5V, and is otherwise pulled up
to VIN through an internal 10kΩ resistor.
Typical Performance Characteristics
80
IOUT = 10mA
3.302
4.75V <VIN < 6V
Line Regulation (µV)
Output Voltage (V)
70
3.300
IOUT = 500mA
3.298
3.296
60
125°C
50
27°C
40
0°C
0
20
40
60
80
100
0.0
120
0.2
0.4
IOUT (A)
Junction Temperature (°C)
Line Regulation vs. IOUT Over Temperature
Output Voltage vs. Junction Temperature
1.2
125°C
Reverse Current (µA)
Load Regulation (mV)
1.0
0.8
0.6
0.4
27°C
390
380
370
0.2
360
0°C
0.0
0.0
0.2
0
0.4
20
40
60
80
Junction Temperature (°C)
IOUT (A)
Load Regulation vs. IOUT Over Temperature
Reverse Current vs. Junction Temperature
3
100
120
CS5231-3
Typical Performance Characteristics: continued
4.520
125°C
3
4.500
VIN Turn-on
Threshold
4.480
VIN Threshold Voltage (V)
VOUT (V)
27°C
2
0°C
1
4.460
4.440
4.420
VIN Turn-on
Threshold
4.400
0
4.380
0.0
0.2
0.4
0.6
0.8
40
20
0
1.0
IOUT (A)
VOUT vs. IOUT Over Temperature
80
100
120
140
6.0
7.0
VIN Thresholds vs. Junction Temperature
1000
2.6
2.4
TJ = 0°C
IGnd @ 0°C
2.2
Capacitance (µF)
Ground Current (mA)
60
Junction Temperature (C)
TJ = 27°C
IGnd @ 27°C
2.0
1.8
100
TJ = 125°C
IGnd @ 125°C
1.6
10
0.0
0.2
0.0
0.4
1.0
2.0
3.0
4.0
5.0
Capacitance ESR(Ω)
Load Current (A)
Ground Current vs. Load Current
Region of Stable Operation
5.000
3.400
Current Limit (mA)
VOUT
4.800
3.300
CIN = 33µF
COUT = 33µF
VIN = 5.00V
4.600
3.200
4.400
4.200
IOUT
500mA
4.000
0
20
40
60
80
Temperature (C)
100
120
140
AuxDrv Current Limit vs. Junction Temperature
10mA
Transient Response
4
Time, 5µs per division
CS5231-3
Application Circuit
+5V PCI
C1
33µF
VOUT
VIN
CS5231-3
Gnd
AuxDrv
M1
ASIC
VDD
+3.3V VAUX
C3
33µF
C1
33µF
*indicates PFET body diode
Application Information
external compensation capacitor is required for the linear
regulator to be stable, and this capacitance also serves as a
charge reservoir to minimize any “glitching” that might
result during the supply changeover. Hysteresis is present
in the AuxDrv circuitry, requiring VIN to drop by 100mV
(typical) after the linear regulator is providing power to the
load before the AuxDrv circuitry can be re-enabled.
Theory of Operation
The CS5231-3 is a fixed 3.3V linear regulator that contains
an auxiliary drive control feature. When VIN is greater than
the typical 4.5V threshold, the IC functions as a linear regulator. It provides up to 500mA of current to a load through
a composite PNP-NPN pass transistor. An output capacitor
greater than 10µF with equivalent series resistance less
than 1Ω is required for compensation. More information is
provided in the Stability Considerations section.
The CS5231-3 provides an auxiliary drive feature that
allows a load to remain powered even if the VIN supply for
the IC is absent. An external p-channel FET is the only
additional component required to implement this function
if an auxiliary power supply is available. The PFET gate is
connected to the AuxDrv lead. The PFET drain is connected to the auxiliary power supply, and the PFET source is
connected to the load. The polarity of this connection is
very important, since the PFET body diode will be connected between the load and the auxiliary supply. If the PFET
is connected with its drain to the load and its source to the
supply, the body diode will be forward-biased if the auxiliary supply is turned off. This will result in the linear regulator providing current to everything on the auxiliary supply rail.
The AuxDrv lead is internally connected to a 10kΩ resistor
and to a saturating NPN transistor that acts as a switch. If
the VIN supply is off, the AuxDrv output will connect the
PFET gate to ground through the 10kΩ resistor, and the
PFET will conduct current to the load.
As the VIN supply begins to rise, the AuxDrv lead will also
rise until it reaches a typical voltage of about 650mV. The
NPN transistor connected to the AuxDrv lead will saturate
at this point, and the gate of the PFET will be pulled down
to a typical voltage of about 100mV. The PFET will continues to conduct current to the load.
The VIN supply voltage will continue to rise, but the linear
regulator output is disabled until VIN reaches a typical
threshold of 4.5V. During this time, the load continues to
be powered by the auxiliary driver. Once the 4.5V VIN
threshold is reached, the saturating NPN connected to the
AuxDrv lead turns off. The on-chip 10kΩ pull-up resistor
will pull the PFET gate up to VIN, thus turning the PFET
off. The linear regulator turns on at the same time. An
VIN
VOUT
VAUXDRV
IOUT = STARTUP 375mA
Figure 1. Initial power-up, VAUX not present ROUT = 8.8Ω.
VIN
VOUT
VAUXDRV
IOUT = 375mA VAUX = 3.30V
Figure 2a. Power-up, VAUX = 3.30V. Note the “oscillatory performance”
as the linear regulator charges the VOUT node. IOUT × RDS(ON) ≈ 130mV
5
CS5231-3
Application Information: continued
VIN
VIN
VOUT
VOUT
VAUXDRV
VAUXDRV
IOUT = 375mA VAUX = 3.465
IOUT = 375mA VAUX = 3.30
Figure 4a. Power-up, VAUX = 3.465V. IOUT × RDS(ON) is compensated by
the higher value of VAUX
Figure 2b. Power-down, VAUX = 3.30V. Again, note ∆V = IOUT RDS(ON) ≈
130mV.
VIN
VIN
VOUT
VOUT
VAUXDRV
VAUXDRV
IOUT = 375mA VAUX = 3.465
IOUT = 375mA VAUX = 3.135V
Figure 3a. Power-up, VAUX = 3.135V. The “oscillatory performance”
mode lasts longer because the difference between VAUX and 3.30 is
greater.
Figure 4b. Power-down, VAUX = 3.465V.
Stability Considerations
The output capacitor helps determine three main characteristics of a linear regulator: startup, transient response
and stability.
Startup is affected because the output capacitor must be
charged. At initial startup, the VIN supply may not be present, and the output capacitor will be charged through the
PFET. The PFET will initially provide current to the load
through its body diode. The diode will act as a voltage follower until sufficient voltage is present to turn the FET on.
Since most commercial power supplies have a fairly low
ramp rate, charging through the body diode should effectively limit in-rush current to the capacitor.
During normal operation, transient load current requirements will be satisfied from the charge stored in the output
capacitor until either the linear regulator or the auxiliary
supply can respond. Larger values of capacitance will
improve transient response, but will also cost more. A linear regulator will respond within microseconds, where an
external power supply may take milliseconds to react. The
output capacitance will provide the difference in current
until this occurs. The result will be an instantaneous voltage change at the output. This change is the product of the
current change and the capacitor ESR:
VIN
VOUT
VAUXDRV
IOUT = 375mA VAUX = 3.135
Figure 3b. Power-down, VAUX = 3.135V. The difference in voltage is
now IOUT × RDS(ON) plus the difference in supply voltages (3.30 -VAUX).
6
∆VOUT = (∆ILOAD) (ESR)
If required, using a few capacitors in parallel to increase
the bulk charge storage and reduce the ESR should give
better performance than using a single input capacitor.
Short, straight connections between the power supply and
VIN lead along with careful layout of the PC board ground
plane will reduce parasitic inductance effects. Wide VIN
and VOUT traces will reduce resistive voltage drops.
This limitation directly affects load regulation. Capacitor
ESR must be minimized if output voltage must be maintained within tight tolerances. In such a case, it is often
advisable to use a parallel network of different types of
capacitors. For example, electrolytic capacitors provide
high charge storage capacity in a small size, while tantalum
capacitors have low ESR. The parallel combination will
result in a high capacity, low ESR network. It is also important to physically locate the capacitance network close to
the load, and to connect the network to the load with wide
PC board traces to minimize the metal resistance.
The CS5231-3 has been carefully designed to be stable for
output capacitances greater than 10µF with equivalent
series resistance less than 1Ω. While careful board layout is
important, the user should have a stable system if these
constraints are met. A graph showing the region of stability
for the CS5231-3 is included in the “Typical Performance
Characteristics” section of this data sheet.
Choosing the PFET Switch
The choice of the external PFET switch is based on two
main considerations. First, the PFET should have a very
low turn-on threshold. Choosing a switch transistor with
VGS(ON) ≈ 1V ensures the PFET will be fully enhanced with
only 3.3V of gate drive voltage. Second, the switch transistor should be chosen to have a low RDS(ON) to minimize the
voltage drop due to current flow in the switch. The formula for calculating the maximum allowable on-resistance is
RDS(ON)(MAX) =
Input Capacitors and the VIN Thresholds
VAUX(MIN) − VOUT(MIN)
1.5 × IOUT(MAX)
where VAUX(MIN) is the minimum value of the auxiliary
supply voltage, VOUT(MIN) is the minimum allowable output voltage, IOUT(MAX) is the maximum output current and
1.5 is a “fudge factor” to account for increases in RDS(ON)
due to temperature.
A capacitor placed on the VIN pin will help to improve
transient response. During a load transient, the input
capacitor serves as a charge “reservoir”, providing the
needed extra current until the external power supply can
respond. One of the consequences of providing this current
is an instantaneous voltage drop at VIN due to capacitor
ESR. The magnitude of the voltage change is again the
product of the current change and the capacitor ESR.
It is very important to consider the maximum current step
that can exist in the system. If the change in current is large
enough, it is possible that the instantaneous voltage drop
on VIN will exceed the VIN threshold hysteresis, and the IC
will enter a mode of operation resembling an oscillation.
As the part turns on, the output current IOUT will increase,
reaching current limit during initial charging. Increasing
IOUT results in a drop at VIN such that the shutdown
threshold is reached. The part will turn off, and the load
current will decrease. As IOUT decreases, VIN will rise and
the part will turn on, starting the cycle all over again. This
oscillatory operation is most likely at initial startup when
the output capacitance is not charged, and in cases where
the ramp-up of the VIN supply is slow. It may also occur
during the power transition when the linear regulator
turns on and the PFET turns off. a 15µs delay exists
between turn-on of the regulator and the AUXDRV pin
pulling the gate of the PFET high. This delay prevents
“chatter” during the power transitions. During this interval, the linear regulator will attempt to regulate the output
voltage as 3.3V. If the output voltage is significantly below
3.3V, the IC will go into current limit while trying to raise
VOUT. It is a short-lived phenomenon and is mentioned
here to alert the user that the condition can exist. It is typically not a problem in applications. Careful choice of the
PFET switch with respect to RDS(ON) will minimize the voltage drop which the output must charge through to return
to a regulated state. More information is provided in the
section on choosing the PFET switch.
Output Voltage Sensing
It is not possible to remotely sense the output voltage of
the CS5231-3 since the feedback path to the error amplifier
is not externally available. It is important to minimize voltage drops due to metal resistance of high current PC board
traces. Such voltage drops can occur in both the supply
traces and the return traces.
The following board layout practices will help to minimize
output voltage errors:
• Always place the linear regulator as close to both load
and output capacitors as possible.
• Always use the widest possible traces to connect the linear regulator to the capacitor network and to the load.
• Connect the load to ground through the widest possible
traces.
• Connect the IC ground to the load ground trace at the
point where it connects to the load.
Current Limit
The CS5231-3 has internal current limit protection. Output
current is limited to a typical value of 850mA, even under
output short circuit conditions. If the load current drain
exceeds the current limit value, the output voltage will be
pulled down and will result in an out of regulation condition. The IC does not contain circuitry to report this fault.
Thermal Shutdown
The CS5231-3 has internal temperature monitoring circuitry. The output is disabled if junction temperature of the IC
reaches a typical value of 180°C. Thermal hysteresis is typi7
CS5231-3
Application Information: continued
and heatsink-to-air thermal resistance (θSA). The resulting
equation for junction-to-air thermal resistance is
cally 25°C and allows the IC to recover from a thermal
fault without the need for an external reset signal. The
monitoring circuitry is located near the composite PNPNPN output transistor, since this transistor is responsible
for most of the on-chip power dissipation. The combination of current limit and thermal shutdown will protect the
IC from nearly any fault condition.
θJA = θJC + θCS + θSA
The value of θJC for the CS5231-3 is provided in the
Packaging Information section of this data sheet. θCS can
be considered zero, since heat is conducted out of the
package by the IC leads and the tab of the D2PAK package,
and since the IC leads and tab are soldered directly to the
PC board.
Modification of θSA is the primary means of thermal management. For surface mount components, this means modifying the amount of trace metal that connects to the IC.
The thermal capacity of PC board traces is dependent on
how much copper area is used, whether or not the IC is in
direct contact with the metal, whether or not the metal surface is coated with some type of sealant, and whether or
not there is airflow across the PC board. The chart provided below shows heatsinking capability of a square, single
sided copper PC board trace. The area is given in square
millimeters. It is assumed there is no airflow across the PC
board.
Reverse Current Protection
During normal system operation, the auxiliary drive circuitry will maintain voltage on the VOUT pin when VIN is
absent. IC reliability and system efficiency are improved
by limiting the amount of reverse current that flows from
VOUT to ground and from VOUT to VIN. Current flows from
VOUT to ground through the feedback resistor divider that
sets up the output voltage. This resistor can range in value
from 6kΩ to about 10kΩ, and roughly 500µA will flow in
the typical case. Current flow from VOUT to VIN will be
limited to leakage current after the IC shuts down. On-chip
RC time constants are such that the output transistor
should be turned off well before VIN drops below the VOUT
voltage.
70
Calculating Power Dissipation and
Heatsink Requirements
Thermal Resistance, °C/W
CS5231-3
Application Information: continued
Most linear regulators operate under conditions that result
in high on-chip power dissipation. This results in high
junction temperatures. Since the IC has a thermal shutdown feature, ensuring the regulator will operate correctly
under normal conditions is an important design consideration. Some heatsinking will usually be required.
Thermal characteristics of an IC depend on four parameters: ambient temperature (TA in °C), power dissipation
(PD in watts), thermal resistance from the die to the ambient air (θJA in °C per watt) and junction temperature (TJ in
°C). The maximum junction temperature is calculated from
the formula below:
60
50
40
30
20
10
0
0
2000
4000
6000
PC Board Trace Area (mm2)
Figure 5: Thermal Resistance Capability of Copper PC Board Metal
Traces
TJ(MAX) = TA(MAX) + (θJA) (PD(MAX))
Typical D2PAK PC Board Heatsink Design
Maximum ambient temperature and power dissipation are
determined by the design, while θJA is dependent on the
package manufacturer. The maximum junction temperature for operation of the CS5231-3 within specification is
150°C. The maximum power dissipation of a linear regulator is given as
A typical design of the PC board surface area needed for
the D2PAK package is shown below. Calculations were
made assuming VIN(MAX) =5.25V, VOUT(MIN) = 3.266V,
IOUT(MAX) = 500mA, IGnd(MAX) = 5mA and TA = 70°C.
PD = (5.25V − 3.266V) (0.5A) + (5.25V) (0.005A) = 1018mW
PD(MAX) = (Vin(MAX) − VOUT(MIN)) (ILOAD(MAX))
+ (VIN (MAX)) (IGnd(MAX))
Maximum temperature rise ∆T = TJ(MAX) − TA =
150°C − 70°C = 80°C.
where IGnd(MAX) is the IC bias current.
It is possible to change the effective value of θJA by adding
a heatsink to the design. A heatsink serves in some manner
to raise the effective area of the package, thus improving
the flow of heat from the package into the surrounding air.
Each material in the path of heat flow has its own characteristic thermal resistance, all measured in °C per watt. The
thermal resistances are summed to determine the total
thermal resistance between the die junction and air. There
are three components of interest: junction-to-case thermal
resistance (θJC), case-to-heatsink thermal resistance (θCS)
θJA (worst case) = ∆T/PD = 80°C/1.018W = 78.56°C/W
First, we determine the need for heatsinking. If we assume
the maximum θJA = 50°C/W for the D2PAK, the maximum
temperature rise is found to be
∆T = (PD) (θJA) = (1.018W) (50°C/W) = 50.9°C
This is less than the maximum specified operating junction
temperature of 125°C, and no heatsinking is required.
Since the D2PAK has a large tab, mounting this part to the
8
PC board by soldering both tab and leads will provide
superior performance with no PC board area penalty.
The VOUT Connection
The VOUT connection is tied to the VOUT lead of the
CS5231-3 and the PFET source. This point provides a convenient point at which some type of lead may be applied.
Description
The CS5231-3 application circuit has been implemented as
shown in the following pages. The schematic, bill of materials and printed circuit board artwork can be used to build
the circuit. The design is very simple and consists of two
capacitors, a p-channel FET and the CS5231-3. Five turret
pins are provided for connection of supplies, meters, oscilloscope probes and loads. The CS5231-3 power supply
management solution is implemented in an area less than
1.5 square inches. Due to the simplicity of the design, output current must be derated if the CS5231-3 is operated at
VIN voltages greater than 7V. Figure 15 provides the derating curve on a maximum power dissipation if heatsink is
added. Operating at higher power dissipation without
heatsink may result in a thermal shutdown condition.
VIN TP1
VIN
U1
VOUT
TP5
CS5231-3
GND
AUXDRV
C1
GND
TP2
TP3
TP6
AUXDRV
Q1
TP4
+3.3V VAUX
C2
Application Circuit Schematic
PC Board Layout Artwork
600
The PC board is a single layer copper design. The layout
artwork is reproduced at actual size below.
IOUT (mA)
500
400
300
2"
200
100
0
5
6
7
8
9
10
VIN(VOLTS)
11
12
13
14
1.5"
Figure 6: Demo Board Output Current Derating vs VIN
The VIN Connection
The VIN connection is denoted as such on the PC board.
The maximum input voltage to the IC is 14V before damage to the IC is possible. However, the specification range
for the IC is 4.75V < VIN < 6V.
Top Copper Layer
The Gnd Connection
The Gnd connection ties the IC power return to two turret
pins. The extra turret pin provides for connection of multiple instrument grounds to the demonstration board.
2"
VIN 5V
AUX.DRV
AUX3.3V
The AuxDrv Connection
The AuxDrv lead of the CS5231-3 is connected to the gate
of the external PFET. This connection is also brought to a
turret pin to allow easy connection of an oscilloscope probe
for viewing the AuxDrv waveforms.
1.5"
VOUT 3.3V
GND
GND
The VAUX Connection
The VAUX turret pin provides a connection point between
an external 3.3V supply and the PFET drain.
Top Silk Screen Layer
9
CS5231-3
Application Circuit Characteristics
Test Descriptions
The startup and supply transition waveforms shown in figures 1 through 4b were obtained using the application circuit board with a resistive load of 8.8Ω. This provides a DC
load of 375mA when the regulated output voltage is 3.3V.
A standard 2A bench supply was used to provide power to
the application circuit. The transient response waveforms
shown in the Typical Performance Characteristics section
were obtained by switching a 6.3Ω resistor across the output.
The graph provided below show typical RDS(ON) performance for the PFET. The data is provided as VDS vs IOUT
for different values of VAUX.
160
VAUX = 3.135V
140
VAUX = 3.300V
120
100
VAUX = 3.465V
80
Vds (mV)
Temperature Performance
The graph below shows thermal performance for the
CS5231-3 across the normal operating output current range.
60
40
20
0
0
55
100
200
300
400
IOUT (mA)
50
Package Temperature (C)
CS5231-3
Application Circuit Characteristics: continued
Figure 8: PFET Vds vs IOUT
45
40
35
30
25
20
0
50
100
150
200 250 300 350
Load Current (mA)
400
450
500
Figure 7: Package Temperature vs Load Current (VIN = 5V, TA =23 C°)
PFET RDS(ON) Performance
Application Circuit Bill of Materials
Refdes
Description
Part Number
Manufacturer
Contact Information
C1, C2
33µF, 16V tantalum capacitors
TAJ336K016
AVX Corp
www.avxcorp.com
1-843-448-9411
Q1
p-channel FET transistor
MGSF1P02ELT1
Motorola
www.mot-sps.com
U1
Linear regulator with auxiliary
CS5231-3DPS
Cherry Semiconductor
www.cherry-sem.com
1-800-272-3601
T1-T6
Turret pins
40F6023
Newark Electronics
www.newark.com
1-800-463-9275
10
500
CS5231-3
Package Specification
PACKAGE THERMAL DATA
PACKAGE DIMENSIONS IN mm (INCHES)
Thermal Data
RΘJC
RΘJA
typ
typ
5Lead
D2PAK
2.5
10-50*
˚C/W
˚C/W
*Depending on thermal properties of substrate. RΘJA = RΘJC + RΘCA
5 Lead D2PAK (DP)
10.31 (.406)
10.05 (.396)
1.40 (.055)
1.14 (.045)
1.68 (.066)
1.40 (.055)
8.53 (.336)
8.28 (.326)
15.75 (.620)
14.73 (.580)
2.74(.108)
2.49(.098)
0.91 (.036)
0.66 (.026)
2.79 (.110)
2.29 (.090)
1.70 (.067) REF
.254 (.010) REF
0.10 (.004)
0.00 (.000)
4.57 (.180)
4.31 (.170)
Ordering Information
Part Number
CS5231-3GDP5
CS5231-3GDPR5
Rev. 3/31/99
Description
5 Lead D2PAK
5 Lead D2PAK (tape & reel)
Cherry Semiconductor Corporation reserves the right to
make changes to the specifications without notice. Please
contact Cherry Semiconductor Corporation for the latest
available information.
11
© 1999 Cherry Semiconductor Corporation