Agilent HPMX-7202 Dual-Band, Tri-Mode Upconverter/Driver Amplifier Data Sheet Features • Dual-Band, Tri-mode operation • High output power to directly drive a power amplifier • 30 dB gain control range on CDMA drivers • Adaptive biasing on CDMA driver to maximize efficiency General Description The HPMX-7202 offers a highly integrated solution for CDMA/FM Dual-Band, Tri-Mode (DBTM) hand sets. On the two CDMA chains, it contains an upconverter and RF variable gain driver. On the AMPS chain, it contains an upconverter and a driver amplifier. Internal circuitry is used to move between modes. The IC operates from a 3V regulated supply, making it ideal for use with a single cell Lithium Ion battery. The Drivers can be directly powered from the battery for enhanced performance. The power down function reduces the supply current to 1 µA, typical, to support gated operation and eliminate the need for a power supply switch. The CDMA transmit chains provide excellent Adjacent Channel Power Rejection and a low noise floor for compliance with TIA98-C requirements. The CDMA driver has a high output power for direct interfacing with CDMA Power amplifiers. The driver is adaptively biased to reduce current consumption and extend battery life. The HPMX-7202 is fabricated using a 40 GHz Fmax silicon bipolar process and is packaged in a 5 x 5 mm 32 pin TQFP package. Applications • CDMA1900/CDMA cellular/AMPS handsets 5x5 mm TQFP-32 Package Package Pin Configuration • 56 mA average supply current (CDG suburban user model) • 2.7 to 3.6 V operation • ACPR compliant • Low output noise power • Power down capability pwrDn VccBat Band VccBat Gnd RFTxAgc Vcc CellMixOutP • JEDEC standard TQFP-32 surface mount package 32 25 1 24 CellMixOutM Mode Gnd Gnd CellDrvIn CellDrvOut Gnd Gnd HPMX-7202 PCSDrvIn Gnd Gnd PCSDrvOut YY WW PCSMixOutM Gnd PCSMixOutP Gnd 8 17 VccBat CellLO LOGnd PCSLO Vcc Gnd IFInP 16 IFInM 9 HPMX-7202 Absolute Maximum Ratings [1] Parameter Min. Max. Units Supply Voltage 4.5 V Battery Supply Voltage 4.5 V Junction Temperature 150 °C Case Temperature 125 °C 125 °C Input Power at ifIn (IFInP, IFInM) 15 dBm Input Power at PCSDrvIn 15 dBm Input Power at CellDrvIn 15 dBm Input Power at LoIn 15 dBm Storage Temperature -55 Thermal Resistance:[2] θjc = 108°C/W Notes: 1. Operation of this device in excess of any of these parameters may cause permanent damage. 2. TJUNCTION = 150°C 3. This product is ESD sensitive. Handle with care to avoid static discharge. Human Body Model Class 1 Machine Model Class A Charge Device Model Class A See Reliability Bulletin for more information. HPMX-7202 Recommended Operating Conditions Vcc = 2.7 to 3.6V VccBat = 2.7 to 4.2V; VccBat ≥ Vcc Tambient = -40°C to 85°C IF Frequency (both bands): 130 MHz typically PCS Output Frequency: 1850 to 1910 MHz PCS Local Oscillator Frequency: 1720 to 1780 MHz for low side LO Cellular Band Output Frequency: 824 to 849 MHz Cellular Band Local Oscillator Frequency: 954 to 979 MHz for high side LO HPMX-7202 Standard Test Conditions Unless otherwise noted, all test data was taken on packaged parts under the following conditions. The test circuit is shown in Figure 47. RF powers are into 50Ω unless specified otherwise. Vcc=3.0V, VccBat = 3.6V, Tambient = 25°C IF input frequency at IFInP, IFInM is 130 MHz. IF differential input voltage, Vif-in, 480 mVp-p across a matched 470Ω differential impedance (240 mVp-p at IFInP and IFInM, with a single ended impedance of 235Ω). This input level is calculated from a 50Ω power source delivering –12 dBm to a 9.4:1 impedance transforming network. The test circuit for this input is represented by components C6, C9, L19 and X1 on Figure 47. PCS CDMA LO input at PCSLO: 1750 MHz at –11dBm, single ended PCS CDMA RF frequency at PCSMixOutM, PCSMixOutP, PCSDrvIn, PCSDrvOut: 1880 MHz, matched to 50Ω. Cellular AMPS LO input at CellLO: 966 MHz at -11dBm, single ended Cellular CDMA LO input at CellLO: 966 MHz at -11dBm, single ended Cellular RF frequency at CellMixOutM, CellMixOutP, CellDrvIn, CellDrvOut: 836 MHz, matched to 50Ω. PCSDrvIn PCSMixOutM PCSMixOutP Functional Block Diagram IFlnM IFlnP PCSDrvOut CellDrvOut 2 CellDrvIn CellLO CellMixOutM RFTxAgc CellMixOutP PCSLO pwrDn Mode Band DC Specifications for Logical Signals Symbol Parameters and Test Conditions VIL_MAX VIL Input Logic Low Voltage [1] VIH_MIN VIH Input Logic High Voltage Min. Typ. Max. Units 0.5 V 2.5 V Supply current from Vcc when pwrDn = VIL_MAX 1 15 µA Supply current from VccBat when pwrDn = VIL_MAX 1 15 µA Note: 1. An additional 25 µA is drawn from the modem chip when VRFTxAgc = 3.0V. This voltage should be set to 0 V when pwrDn ≤ VIL-MAX. PCS CDMA Upconverter Symbol Parameters and Test Conditions Icc Current Consumption ( Vif-In = 480 mVp-p [1] ) Min. Max. Units 24 28 mA Pout Output Power ACPR Adjacent Channel Power Ratio at PCSMixOut = -9 dBm (1.25 MHz offset) Cg Conversion Power Gain[1] 4 dB OP1dB Output 1 dB gain compression point -1.5 dBm OIP3 Output 3rd Order Intercept Point 11 dBm Rx Noise Rx band Noise FPCSMixOut = 1880 MHz, Fnoise-test = 1960 MHz at Pout = -9 dBm -154 dBm/Hz Differential Impedance of IF port in PCS mode 160-j225 Ω LO port to RF port leakage ZIF -9 Typ. -7 -66 dBm -58 dBc/30 kHz -30 dBm (Vif-In = 480 mVp-p [1] ) -90 dBm RF signal present at LO port (Vif-In = 480 mVp-p [1] ) -66 dBm 2x LO out at RF port -22 dBm 3x LO out at RF port -39 dBm Other Spurious emissions at RF port: (LO ±3 IF) -50 dBm IF signal present at LO port Note: 1. This input level is calculated from the input power delivered to a test circuit with measured loss as specified in the Standard Test Conditions. If an additional resistance is added across the IFInP and IFInM pins (to set the IF filter terminating impedance) the input voltage for a fixed input power will be reduced. To maintain this input voltage in this case, the input power to the IF port must be increased, resulting in an apparent decrease in power gain. 3 PCS CDMA Variable Gain Amplifier Symbol Parameters and Test Conditions Min. IccBat Battery Current Consumption RFTxAgc = 0.3 V RFTxAgc = 2.7 V Gain Gain RFTxAgc = 0.3 V RFTxAgc = 2.7 V 22 Typ. Max. Units 22 70 32 82 mA mA -10 25 -8 dB dB -52 dBc/30 kHz ACPR Adjacent Channel Power Ratio Pout = +9dBm -58 OP1dB Output 1dB gain compression point RFTxAgc = 2.7V 14 dBm Rx Noise Rx band Noise RFTxAgc = 2.7V FPCSMixOut = 1880 MHz, Fnoise-test = 1960 MHz at Pout = +9 dBm -144 dBm/Hz Note: 2. The PCS CDMA VGA features adaptive biasing such that the supply current (from VccBat) will vary with RFTxAgc voltage. Please see the Typical Performance Graphs for more information on the VGA operation. Cellular CDMA Upconverter Symbol Parameters and Test Conditions Icc Current Consumption Vif-In = 480 mVp-p [3] Min. -9 Typ. Max. Units 23 26 mA Pout Output Power -8 dBm ACPR Adjacent Channel Power Ratio at CellMixOut = -9 dBm (885 kHz offset) -62 Cg Conversion Power Gain 3.8 dB OP1dB Output 1dB gain compression point -1.5 dBm OIP3 Output 3rd Order Intercept Point 10 dBm Rx Noise Rx band Noise FCellMixOut = 835 MHz, Fnoise-test = 880 MHz at PCellMixOut = -9 dBm -154 dBm/Hz ZIF Differential Impedance of IF port in Cellular CDMA mode 164-j221 Ω LO port to RF port leakage -33 dBm -58 dBc/30 kHz IF signal present at LO port (Vif-In = 480 mVp-p[3] ) -82 dBm RF signal present at LO port (Vif-In = 480 mVp-p[3] ) -56 dBm 2x LO out at RF port -29 dBm 3x LO out at RF port -48 dBm Other Spurious emissions at RF port: (LO ±3 IF) -55 dBm Note: 3. This input level is calculated from the input power delivered to a test circuit with measured loss as specified in the Standard Test Conditions. If an additional resistance is added across the IFInP and IFInM pins (to set the IF filter terminating impedance) the input voltage for a fixed input power will be reduced. To maintain this input voltage in this case, the input power to the IF port must be increased, resulting in an apparent decrease in power gain. 4 Cellular CDMA Variable Gain Amplifier Symbol Parameters and Test Conditions Min. IccBat Battery Current Consumption RFTxAgc = 0.3 V RFTxAgc = 2.7 V Gain Gain RFTxAgc = 0.3 V RFTxAgc = 2.7 V 22 Typ. Max. Units 22 67 32 84 mA mA -14 26 -8 dB dB -52 dBc/30 kHz ACPR Adjacent Channel Power Ratio (885 kHz offset) Pout = +7dBm -55 OP1dB Output 1dB gain compression point RFTxAgc = 2.7 V 13 dBm Rx Noise Rx band Noise RFTxAgc = 2.7 V FCellDrvOut = 835 MHz, Fnoise-test = 880 MHz at PCellDrvOut = +9 dBm -140 dBm/Hz Note: 4. The Cellular CDMA VGA features adaptive biasing such that the supply current (from VccBat) will vary with RFTxAgc voltage. Please see the Typical Performance Graphs for more information on the VGA operation. Cellular AMPS Upconverter Symbol Parameters and Test Conditions Icc Current consumption Pout Output power Vin=480 mVp-p[5] ZIF FMnoise Min. Max. Units 16 22 mA -5.0 dBm Differential Impedance of IF port in AMPS mode 153-j199 Ω Rx band Noise FampsMixOut = 835 MHz, Fnoise-test = 880 MHz at PampsMixOut = -6dBm -148 dBm/Hz LO port to RF port leakage -41 dBm -84 dBm IF signal present at LO port (Vin = 480 mVp-p [5] ) RF signal present at LO port (Vin = 480 mVp-p [5] ) -5.5 Typ. -54 dBm 2x LO out at RF port -40 dBm 3x LO out at RF port -59 dBm Other Spurious emissions at RF port: (LO ±2 IF) -20 dBm Other Spurious emissions at RF port: (LO ±3 IF) -50 dBm Note: 5. This input level is calculated from the input power delivered to a test circuit with measured loss as specified in the Standard Test Conditions. If an additional resistance is added across the IFInP and IFInM pins (to set the IF filter terminating impedance) the input voltage for a fixed input power will be reduced. To maintain this input voltage in this case, the input power to the IF port must be increased, resulting in an apparent decrease in power gain. Cellular AMPS Driver Symbol Parameters and Test Conditions IccBat Battery Current Consumption SSGain Small Signal Gain, Pin = -25 dBm 16 19 dB Pout Output Power at Pin = -8.5 dBm 9 9.5 dBm OP1dB Output 1dB gain compression point 6.6 dBm Noise Rx band Noise FCellDrvOut = 835 MHz, Fnoise-test = 880 MHz at Pout = +9 dBm -133 dBm/Hz 5 Min. Typ. Max. Units 28 38 mA Table 1. HPMX-7202 Pin Description No. Name Description Functionality 1 CellMixOutM AMPS and CDMA Cellular mixer differential outputs Open collector outputs of both the AMPS and CDMA cellular upconverters. Upconverter selection controlled by mode switch. Impedance matching required. Connection to Vcc is required via a bias decoupling network. If a single ended output is required from CellMixOutM, then CellMixOutP needs to be biased to Vcc and RF terminated. 2 Gnd Ground 3 CellDrvIn Cellular amplifier input 4 Gnd Ground 5 PCSDrvIn PCS amplifier input 6 Gnd Ground 7 PCSMixOutM PCS mixer differential output Open collector output of PCS upconverter. Impedance matching required. Connection to Vcc is required through a bias decoupling network. If single ended output is required from PCSMixOutM, PCSMixOutP needs to be biased to Vcc and RF terminated. 8 PCSMixOutP PCS mixer differential output Open collector output of PCS upconverter. Impedance matching required. Connection to Vcc is required through a bias decoupling network. If single ended output is required from PCSMixOutP, PCSMixOutM needs to be biased to Vcc and RF terminated. 9 IFInP IF differential input IF differential input with nominal input impedance of 470Ω differential. Consult the applications section for information on driving the IF port from a single ended 50Ω source. 10 IFInM IF differential input IF differential input. See IFInP (Pin 9). 11 Gnd Ground 12 Vcc Regulated DC Voltage connection Regulated Vcc connection to IC mixer circuits, separated from amplifier supply voltage to avoid non-linear mixer effects due to supply coupling. 13 PCSLO PCS LO input Requires external AC coupling and impedance match to 50Ω. 14 LOGnd LO input ground Common LO ground return for both PCS and cellular. A DC bias is present on this pin, therefore grounding requires AC coupling. 15 CellLO Cellular LO input Requires external AC coupling and impedance match to 50Ω. 16 VccBat Battery connection Amplifier DC supply voltage pin. This supply can be connected directly to the unregulated battery voltage. External decoupling capacitors are typically required. 17 Gnd Ground 18 Gnd Ground 19 PCSDrvOut PCS Amplifier output 20 Gnd Ground 21 Gnd Ground 22 CellDrvOut Cellular AMPS/CDMA Amplifier output 23 Gnd Ground 24 Mode Mode select 6 RF input to cellular band (CDMA and AMPS) amplifier. A DC bias is present on this pin, therefore a DC blocking capacitor is required. A matching circuit is required for operation from a 50Ω source impedance. RF input to PCS amplifier. A DC bias is present on this pin, therefore a DC blocking capacitor is required. RF output from PCS amplifier stage. Impedance matching required. An external connection to VccBat is required through a bias decoupling network. RF output from amplifier. Impedance matching required. An external connection to VccBat is required through a bias decoupling network. Toggles cellular modes between CDMA and AMPS. A logic low places the HPMX-7202 in the cellular AMPS mode while a logic high places the HPMX-7202 in the CDMA mode for both cellular and PCS. Table 1. HPMX-7202 Pin Description, continued 25 pwrDn Power Down DC input, a logic low will power down the HPMX-7202, a logic high turns the IC on. This input controls the bias cell of the HPMX-7202, allowing it to shutdown all sections of the chip regardless of which Vcc supply (Vcc or VccBat) the section uses. At a logic high, this pin draws less than 30µA. At a logic low level this pin sources less than 1µA typically. 26 VccBat Battery connection Amplifier DC supply voltage pin. This supply can be connected directly to the unregulated battery voltage. External decoupling capacitors are typically required. 27 Band Band select Toggles between cellular and PCS bands. A logic low places the HPMX-7202 in the cellular band while a logic high places the HPMX-7202 in the PCS band. 28 VccBat Battery connection Amplifier DC supply voltage pin. This supply can be connected directly to the unregulated battery voltage. External decoupling capacitors are typically required. 29 Gnd Ground 30 RFTxAgc CDMA Tx VGA gain control voltage DC input. Controls CDMA amplifier gain and bias current for both Cellular and PCS. Minimum gain occurs at RFTxAgc = 0 V and maximum gain occurs at RFTxAgc = 3 V. See typical performance graphs for more information. This pin appears as a 100 kΩ resistance to ground. If this pin is connected to a Pulse Density Modulated signal (PDM) an external discrete filter is needed to generate the gain control voltage input. 31 Vcc Regulated DC Voltage connection Regulated Vcc connection to IC mixer circuits, separated from amplifier supply voltage to avoid non-linear mixer effects due to supply coupling. 32 CellMixOutP AMPS and CDMA Cellular mixer differential output Open collector outputs of AMPS and CDMA cellular upconverters. Upconverter selection controlled by mode switch. Impedance matching required. Connection to Vcc is required through a bias de-coupling network. If a single ended output is required from CellMixOutP, then CellMixOutM needs to be biased to Vcc and RF terminated. 7 HPMX-7202 Typical Performance Graphs Vcc = 3 V, VccBat = 3.6 V, Plo = -11 dBm, Vif-in = 480 mVp-p, unless otherwise stated 30 28 Vcc = 2.7 V Vcc = 3 V Vcc = 3.6 V 26 22 22 20 20 -40 -20 0 20 40 60 TEMPERATURE (°C) 0 60 -9 -40 80 -8 20 40 60 -13 -11 -9 -22 -15 -7 -10 Pout (dBm) ACPR (dBc/30 kHz) -67 -62 -63 -11 -9 -7 Plo (dBm) Figure 7. PCS CDMA Upconverter ACPR vs. LO Power and Frequency. -7 -40°C 25°C 85°C -20 -30 -40 -64 -13 -9 0 -61 -66 -11 Figure 6. Cellular CDMA Upconverter Output Power vs. LO Power and Vcc. 824 MHz 837 MHz 849 MHz Pout = -9 dBm -65 -68 -15 -13 Plo (dBm) -60 -64 Vcc = 2.7 V Vcc = 3 V Vcc = 3.6 V -21.5 Figure 5. PCS CDMA Upconverter Output Power vs. LO Power and Vcc. 1850 MHz 1880 MHz 1910 MHz Pout = -9 dBm 80 -21 Plo (dBm) -63 60 Pin = -25 dBm -20 TEMPERATURE (°C) Figure 4. Cellular CDMA Upconverter Output Power vs. Temperature and Vcc. 40 -20.5 -21 -15 80 20 -20 -20.5 0 0 Figure 3. PCS CDMA Upconverter Output Power vs. Temperature and Vcc. Pout (dBm) -7 -20 -20 TEMPERATURE (°C) -19.5 -10 -40 ACPR (dBc/30 kHz) 40 Vcc = 2.7 V Vcc = 3 V Vcc = 3.6 V Pin = -25 dBm -9 8 20 -19 Vcc = 2.7 V Vcc = 3 V Vcc = 3.6 V Pout (dBm) Pout (dBm) -20 Figure 2. Cellular CDMA Upconverter Icc vs. Temperature and Vcc. -5 -6 -7 TEMPERATURE (°C) Figure 1. PCS CDMA Upconverter Icc vs. Temperature and Vcc. Pin = -12 dBm -6 -8 18 -40 80 -5 24 24 Vcc = 2.7 V Vcc = 3 V Vcc = 3.6 V Pin = -12 dBm Pout (dBm) 26 Icc (mA) Icc (mA) 28 -4 Vcc = 2.7 V Vcc = 3 V Vcc = 3.6 V -65 -15 -50 -60 -13 -11 -9 -7 Plo (dBm) Figure 8. Cellular CDMA Upconverter ACPR vs. LO Power and Frequency. L-3 L-2 L-1 L L+1 L+2 L+3 SIGNAL ID (LO ± n * IF) Figure 9. PCS CDMA Upconverter Output Spectrum vs. Temperature. HPMX-7202 Typical Performance Graphs , continued Vcc = 3 V, VccBat = 3.6 V, Plo = -11 dBm, Vif-in = 480 mVp-p, unless otherwise stated 0 80 -40°C 25°C 85°C 70 -40 -50 60 IccBat (mA) -30 50 40 L-3 40 30 30 20 20 L-2 L-1 L L+1 L+2 L+3 10 0 1 SIGNAL ID (LO ± n * IF) 2 3 0 30 85°C 25°C -40°C 70 85°C 25°C -40°C 20 50 40 GAIN (dB) 60 IccBat (mA) 60 3 Figure 12. Cellular CDMA Driver IccBat vs. V(RFTxAgc) and VccBat. 80 85°C 25°C -40°C 2 VRFTxAgc (V) Figure 11. PCS CDMA Driver IccBat vs. V(RFTxAgc) and VccBat. 80 70 1 VRFTxAgc (V) Figure 10. Cellular CDMA Upconverter Output Spectrum vs. Temperature. IccBat (mA) 50 10 -60 VccBat = 3.3 V VccBat = 3.6 V VccBat = 4.2 V 70 60 -20 IccBat (mA) Pout (dBm) -10 80 VccBat = 3.3 V VccBat = 3.6 V VccBat = 4.2 V 50 40 30 30 20 20 10 0 -10 10 10 0 1 2 3 -20 0 1 VRFTxAgc (V) 0 -10 10 0 -10 -20 1 2 VRFTxAgc (V) Figure 16. Cellular CDMA Driver Gain vs. V(RFTxAgc) and Temperature. 3 10 0 -10 -20 0 VccBat = 3.3 V VccBat = 3.6 V VccBat = 4.2 V 20 GAIN (dB) GAIN (dB) 0 3 30 VccBat = 3.3 V VccBat = 3.6 V VccBat = 4.2 V 20 10 2 Figure 15. PCS CDMA Driver Gain vs. V(RFTxAgc) and Temperature. 30 85°C 25°C -40°C 20 1 VRFTxAgc (V) Figure 14. Cellular CDMA Driver IccBat vs. V(RFTxAgc) and Temperature. 30 GAIN (dB) 3 VRFTxAgc (V) Figure 13. PCS CDMA Driver IccBat vs. V(RFTxAgc) and Temperature. 9 2 -20 0 1 2 VRFTxAgc (V) Figure 17. PCS CDMA Driver Gain vs. V(RFTxAgc) and VccBat. 3 0 1 2 VRFTxAgc (V) Figure 18. Cellular CDMA Driver Gain vs. V(RFTxAgc) and VccBat. 3 -30 -30 -40 -40 -40 -50 -60 0V 0.5 V 1V 1.5 V 1.7 V 1.9 V 2.1 V 2.2 V 2.7 V 3V -70 -80 -90 -60 -50 -60 0V 0.5 V 1V 1.5 V 1.7 V 1.9 V 2.1 V 2.2 V 2.7 V 3V -70 -80 -40 -20 0 -90 -60 20 -50 -60 -70 -80 -40 Pout (dBm) -20 0 -90 -60 20 Figure 20. PCS ACPR vs. Output Power and V(RFTxAgc). Temp = +25°C -40 -40 0V 0.5 V 1V 1.5 V 1.7 V 1.9 V 2.1 V 2.2 V 2.7 V 3V -80 -90 -60 -50 0V 0.5 V 1V 1.5 V 1.7 V 1.9 V 2.1 V 2.2 V 2.3 V 2.7 V 3V -60 -70 -80 -40 -20 0 -90 -60 20 ACPR (dBc/30 kHz) -40 ACPR (dBc/30 kHz) -30 -50 0 20 -50 -60 -70 -80 -40 -20 Figure 21. PCS ACPR vs. Output Power and V(RFTxAgc). Temp = +85°C -30 -70 -40 Pout (dBm) -30 -60 0V 0.5 V 1V 1.5 V 1.7 V 1.9 V 2.1 V 2.2 V 2.3 V 2.7 V 3V Pout (dBm) Figure 19. PCS ACPR vs. Output Power and V(RFTxAgc). Temp = -40°C ACPR (dBc/30 kHz) ACPR (dBc/30 kHz) -30 ACPR (dBc/30 kHz) ACPR (dBc/30 kHz) HPMX-7202 Typical Performance Graphs , continued Vcc = 3 V, VccBat = 3.6 V, Plo = -11 dBm, Vif-in = 480 mVp-p, unless otherwise stated -20 0 -90 -60 20 0V 0.5 V 1V 1.5 V 1.7 V 1.9 V 2.1 V 2.2 V 2.3 V 2.7 V 3V -40 -20 0 20 Pout (dBm) Pout (dBm) Pout (dBm) Figure 22. Cellular ACPR vs. Output Power and V(RFTxAgc). Temp = -40°C Figure 23. Cellular ACPR vs. Output Power and V(RFTxAgc). Temp = +25°C Figure 24. Cellular ACPR vs. Output Power and V(RFTxAgc). Temp = +85°C -140 -140 18 -150 -155 Icc (mA) -145 NFL (dBm/Hz) NFL (dBm/Hz) -145 20 -150 Vcc = 2.7 V Vcc = 3 V Vcc = 3.6 V 16 14 -155 12 -160 1.5 1.7 1.9 2.1 2.3 2.5 2.7 2.9 VRFTxAgc (V) Figure 25. PCS CDMA Driver Rx Band Noise Floor vs. V(RFTxAgc). 10 -160 1.5 1.7 1.9 2.1 2.3 2.5 2.7 2.9 VRFTxAgc (V) Figure 26. Cellular CDMA Driver Rx Band Noise Floor vs. V(RFTxAgc). 10 -40 10 60 TEMPERATURE (°C) Figure 27. AMPS Upconverter Icc vs. Temperature and Vcc. HPMX-7202 Typical Performance Graphs , continued Vcc = 3 V, VccBat = 3.6 V, Plo = -11 dBm, Vif-in = 480 mVp-p, unless otherwise stated 0 35 Vcc = 2.7 V Vcc = 3 V Vcc = 3.6 V Pin = -12 dBm -4 -6 -8 -4 -6 10 -10 -15 60 -13 -11 VccBat = 3.3 V VccBat = 3.6 V VccBat = 4.2 V 0P3dB (dBm) 13 16 14 85°C 25°C -40°C 12 829 834 839 844 11 9 7 849 FREQUENCY (MHz) Figure 31. AMPS Driver Gain vs. Frequency and Temperature. 5 -40 29 -20 0 20 25 -40 -20 0 20 40 60 TEMPERATURE (°C) 15 18 GAIN (dB) -7 Figure 29. AMPS Upconverter Output Power vs. LO Power and Vcc. 20 11 -9 Plo (dBm) Figure 28. AMPS Upconverter Output Power vs. Temperature and Vcc. 31 27 TEMPERATURE (°C) 10 824 33 -8 -10 -40 VccBat = 3.3 V VccBat = 3.6 V VccBat = 4.2 V Pin = -12 dBm Pin = -12 dBm Pout (dBm) -2 Pout (dBm) Pout (dBm) -2 0 Vcc = 2.7 V Vcc = 3 V Vcc = 3.6 V 40 60 80 TEMPERATURE (°C) Figure 32. AMPS Driver Output Power @ 3 dB Gain Compression vs. Temperature and VccBat. Figure 30. AMPS Driver IccBat vs. Temperature and VccBat. 80 HPMX-7202 Typical Performance Graphs , continued Vcc = 3 V, VccBat = 3.6 V, Plo = -11 dBm, Vif-in = 480 mVp-p, unless otherwise stated 50 50 25 25 0 25 100 50 100 100 25 0 50 100 957 MHz 1810 MHz 1810 MHz Figure 33. PCS LO Port Impedance vs. Frequency. Figure 34. Cellular LO Port Impedance vs. Frequency. 50 50 25 25 100 25 0 50 957 MHz 100 100 25 0 50 100 736 MHz 1780 MHz 936 MHz 1980 MHz Figure 35. PCS CDMA Mixer Output Impedance vs. Frequency. Figure 36. Cellular CDMA Mixer Output Impedance vs. Frequency. 50 50 25 25 0 25 100 50 100 0 100 25 50 100 736 MHz 936 MHz 1980 MHz Figure 37. AMPS Mixer Output Impedance vs. Frequency. 12 1780 MHz Figure 38. PCS CDMA Driver Input Impedance vs. Frequency. HPMX-7202 Typical Performance Graphs , continued Vcc = 3 V, VccBat = 3.6 V, Plo = -11 dBm, Vif-in = 480 mVp-p, unless otherwise stated 50 50 25 100 25 0 25 50 100 100 25 0 50 100 1780 MHz 736 MHz 936 MHz 1980 MHz Figure 39. Cellular CDMA Driver Input Impedance vs. Frequency. Figure 40. PCS CDMA Driver Output Impedance vs. Frequency. 50 50 25 25 0 25 100 50 100 100 25 0 50 100 736 MHz 936 MHz 736 MHz 936 MHz Figure 41. Cellular CDMA Driver Output Impedance vs. Frequency. 50 25 100 25 0 50 100 936 MHz 736 MHz Figure 43. AMPS Driver Output Impedance vs. Frequency. 13 Figure 42. AMPS Driver Input Impedance vs. Frequency. HPMX-7202 Typical Performance Graphs , continued Vcc = 3 V, VccBat = 3.6 V, Plo = -11 dBm, Vif-in = 480 mVp-p, unless otherwise stated 600 4 400 200 10 50 90 130 170 210 6 IflnM 400 2 0 250 200 400 0 250 200 Figure 44. IF Input Port Equivalent Circuit (PCS CDMA Mode) vs. Frequency. 130 170 210 FREQUENCY (MHz) Figure 45. IF Input Port Equivalent Circuit (Cellular CDMA Mode) vs. Frequency. 6 IflnM 2 2 90 C R 800 4 4 50 8 IflnP 600 600 FREQUENCY (MHz) 14 C R 800 10 1000 8 IflnP Rshunt (ohm) 6 Rshunt (ohm) C R IflnM 1000 Cshunt (pF) 8 IflnP 800 R shunt C shunt R shunt C shunt Cshunt (pF) Rshunt (ohm) 1000 10 1200 10 1200 R shunt C shunt 10 50 90 130 170 210 FREQUENCY (MHz) Figure 46. IF Input Port Equivalent Circuit (AMPS Mode) vs. Frequency. 0 250 Cshunt (pF) 10 1200 Theory of Operation The HPMX-7202 is designed for operation in Dual-Band, Tri-Mode PCS/CDMA800/AMPS handsets. The device has four modes of operation set by the pins pwrDn, Mode and Band as represented in Table 2. In addition, the gain in both PCS and cellular CDMA modes is adjustable by controlling the voltage on the RFTxAgc pin. Refer to Figure 47 as a reference for the following circuit descriptions. PCS CDMA Mode The PCS CDMA chain consists of a double balanced active mixer and a variable gain amplifier (VGA). The differential IF input to the balanced mixer IFInP and IFInM (pins 9 and 10) has a nominal impedance of 470Ω, differential. For test purposes, the IF is fed single-ended to the HPMX-7202 through the use of a balun. The balun is shown in Figure 47. Components C9, C6, L19 and transformer X1 comprise the balun. The IF input at pins 9 and 10 is shared by both PCS and cellular mixers. The PCSLO input (pin 13) is specifically for the PCS mixer. The LO ground (pin 14) is connected to ground through a blocking capacitor and it is shared by the PCS and cellular mixers. The RF output of the PCS mixer is a differential signal across PCSMixOutP and PCSMixOutM (pins 8 and 7). Both pins are open collector and require external connections to Vcc. For maximum linearity and maximum voltage swing from the mixer, a 200Ω resistor was chosen as an optimum load impedance. Reference Figure 47 for additional circuit information. Resistors R25 and R26 represent the external 200Ω load impedance. Components L3/ C11 and L4/C10 provide a simple 2 element impedance matching network to 50Ω. Bias is fed in via the shunt inductors L3 and L4 and bypassed with C20 and C31. The PCS CDMA upconverter mixer includes an LO buffer which allows operation at low LO input power and low power supply levels. With an LO input of -11 dBm and an IF input differential signal of 480 mVp-p, the upconverter typically delivers -7 dBm when properly matched to a 50Ω load at 1880 MHz. The mixer ACPR performance is typically -66 dBc/30 kHz (at 1.25 MHz offset frequency and an output power of -9 dBm) with an output noise power of -154 dBm/Hz at +80 MHz offset. The mixer output is typically connected through an off-chip filter and then connected to the PCS VGA. The input to the VGA is single ended (PCSDrvIn, pin 5) and is easily matched to 50Ω. A high pass impedance matching network consisting of L5 and C15 provides the necessary match. The output of the VGA is PCSDrvOut at pin 19. A matching network consisting of C12 and L6 provide a Table 2. HPMX-7202 Mode Control pwrDn Mode Band Power Down 0 X X Cellular AMPS 1 0 X Cellular CDMA 1 1 0 PCS CDMA 1 1 1 X = pin can be in any state 15 power match for 50Ω. Bias is also fed into pin 19 with L7 properly bypassed with C19 and C30. The VGA is implemented in a 2 stage common-emitter configuration which offers 35 dB (typ.) gain control range (-10 dB to 25 dB gain) with a linear gain (in dB) vs. voltage transfer characteristic. See the Typical Performance Graphs for more information. The gain is controlled via the RFTxAgc pin (pin 30). If connection to a Pulse Density Modulation signal is used, an external filter is required to generate the control voltage for this input. The HPMX-7202 VGA features adaptive biasing, which decreases the bias current to the VGA at lower gain levels, thus decreasing the power consumption of the VGA. See the Typical Performance Graphs for more information. The ACPR performance is also a function of the bias current. The linearity increases at higher RFTxAgc voltages. When used in association with an IF AGC amplifier this feature allows the required ACPR to be achieved at the minimum possible supply current for each targeted output power. See the Additional Application Information section for more detail on adaptive biasing and optimizing the supply current drawn by the HPMX-7202 in a handset. Cellular AMPS and CDMA Modes The cellular chain consists of two double balanced mixers and two driver amplifiers, one set for AMPS and one for CDMA. The more stringent linearity and ACPR specifications associated with CDMA requires a separate upconverter chain. Each of the cellular upconverters is a Gilbert cell structure offering excellent port to port isolation. The differential IF input (pins 9 and 10) is shared by both cellular mixers and the PCS mixer. The IF port characteristics are explained in the PCS CDMA mode description. The outputs from both cellular double balanced mixers are also differential and appear across CellMixOutM (pin 1) and CellMixOutP (pin 32). As the mixer output is open collector, these pins require an external connection through a bias decoupling network to Vcc. For maximum linearity and maximum voltage swing from the mixer, a 200Ω resistor was chosen as an optimum load impedance. Reference Figure 47 for additional circuit information. Resistors R27 and R28 represent the external 200Ω load impedance. Components L10/C14 and L11/C13 provide a simple 2 element impedance matching network to 50Ω. Bias is fed in via the shunt inductors L10 and L11 and bypassed with C21 and C32. With an LO power of –11 dBm and an IF input voltage of 480mVp-p differential and the output matching network described in Figure 47, the cellular AMPS upconverter delivers –5 dBm into a 50Ω load. At an output power of –6 dBm, the mixer exhibits a noise power of -148 dBm/Hz at 45 MHz carrier offset. 16 Under similar drive and matching conditions, the cellular CDMA upconverter delivers –8 dBm into a 50Ω load. At an output power of –9 dBm, the mixer exhibits a noise power of –154 dBm/Hz at 45 MHz carrier offset. The output from the cellular mixer is routed off-chip to a discrete filter which provides image rejection. The gain and power distribution of the HPMX-7202 was based on a nominal 3 dB loss for the image reject filter. The input to the cellular driver amplifier is single ended (CellDrvIn, pin 3) and is easily matched to the impedance of the external filter which is typically 50Ω. The cellular driver amplifier input is internally AC coupled with an on-chip capacitor. The output of the cellular amplifier (CellDrvOut) is at pin 22. A matching network consisting of C16 and L12 provides a power match for 50Ω. Bias is also fed into pin 22 with a bias decoupling network consisting of L13 properly bypassed with C25 and C42. At 836 MHz the cellular AMPS driver produces 19 dB of gain and an output P1dB of +6.6 dBm. At +9 dBm output power into a 50Ω load, the receive band noise level is typically -133 dBm/Hz. The cellular CDMA mode VGA is implemented in a 2 stage commonemitter configuration which offers 40 dB (typ.) gain control range (-14 dB to 26 dB gain) with a linear gain (in dB) vs. voltage transfer characteristic. See the Typical Performance Graphs for more information. The gain is controlled via the RFTxAgc pin (pin 30). If connection to a Pulse Density Modulation signal is used, an external filter is required to generate the control voltage for this input. The HPMX-7202 cellular VGA features adaptive biasing, which decreases the bias current to the VGA lowering the gain and power output. This feature has already been covered in detail in the PCS section. J11 J13 J2 J3 J12 J9 R7 R14 R6 C40 C39 C13 R13 C38 R1 C37 C32 C21 R27 L10 R28 L1 R31 R18 C22 C36 R17 C23 L11 R16 C29 R15 R19 J1 R20 R4 C14 J1: CellMixOutVcc J2: Vcc J3: DrvVccBat J4: Mode Select J5: CellDrvOutVccBat J6: Vcc J7: Ground C18 J8: Ground J9: RFTxAgc J10: PCSDrvOutVccBat J11: Band Select J12: pwrDn J13: VccBat J14: PCSMixOutVcc R21 J4 32 RF1 C44 25 24 1 C42 C25 J5 L14 R23 C17 L13 C16 RF7 RF2 L12 C15 RF4 L5 L6 C12 R22 RF6 C10 L7 RF5 L4 J10 R25 R3 J14 C31 C19 8 C20 L3 9 R26 16 L2 C11 J3 C33 C6 C41 L8 X1 RF1: CellMixOut RF2: CellDrvIn RF3: PCSLOIn RF4: PCSDrvIn RF5: PCSMixOut RF6: PCSDrvOut RF7: CellDrvOut RF8: CellLOIn RF9: IFIn R10 C34 R12 C30 17 R32 C35 L9 C26 C43 RF9 C9 C24 R34 R33 L19 R5 RF3 Figure 47. HPMX-7202 Demonstration Printed Circuit Board. RF8 J6 C1-C5, C7, C8, C27, C28, C33-C35 Not used L1 1.0 nH C6 68 pF L2 2.2 nH C9 3.9 pF L3, L4, L7 3.3 nH C10, C11 1 pF L5,L6 3.9 nH C12 1.8 pF L8 4.7 nH C13, C14 2.2 pF L9 10 nH L10, L11, L12, L13, L14 12 nH C15 3.3 pF L19 39 nH C16 4.7 pF R1, R2, R8, R9, R11, R22, R23, R24, R29, R30 Not used C17 12 pF R3, R4, R5, R6, R7, R10 0Ω C18, C19, C20, C21, C22, C23, C24, C25, C26 100 pF R12, R13 50Ω. Not used with differential output C29, C30, C31, C32, C39, C40, C41, C42 0.1 µF R14, R15, R16, R17, R18, R19, R20, R21 1kΩ C43 1 µF R25, R26, R27, R28 200Ω C33, C34, C36, C37, C38, C44 0.01 µF R31, R32 39Ω R33, R34 56Ω X1 Toko 671DB-1018 180o transformer Component List for Demo PCB shown in Figure 47. 17 HPMX-7202 Demo PCB Circuit Design The test diagram shown in Figure 47 presents the various impedance matching and bias de-coupling networks used on the HPMX-7202 demo PCB. The HPMX-7202 was designed such that the IC can operate from separate regulated (Vcc pin) and unregulated (VccBat pin) voltage supplies. Operating the driver amplifiers from the higher unregulated voltage enhances ACPR performance. Good IC grounding is very important for proper operation. Of equal importance is proper de-coupling of the Vcc, VccBat and control pins. Good grounding can be achieved by using separate plated through holes to the bottom groundplane for each supply line bypass capacitor and each IC ground. This technique minimizes common mode ground inductance. Proper decoupling of Vcc and VccBat from the RF ports is also required. This is accomplished by taking advantage of a high pass impedance matching network and using the shunt inductor as a means of inserting bias to a particular pin. This is accomplished by taking the power supply end of the shunt inductor and lifting it above DC ground by using 1 or 2 bypass capacitors. It is important that the grounds for the bypass capacitors for each bias line be brought through to the bottom ground plane with individual plated through holes. This minimizes common lead ground problems that might occur if multiple bypass capacitors from various bias lines are brought to a common top side etch and then attached to the bottom ground plane with only 1 or 2 plated through holes. Decoupling on the control lines is accomplished by using a combination of bypass capacitors and series high value resistors to provide isolation between the IC and the control circuitry. This is especially important when the RFTxAgc control line is driven with a Pulse Density Modulated (PDM) signal. Normal HPMX-7202 operation requires differential input at the IF port. However, for test purposes, a balun (X1) is included on the demo board which allows the use of a 50Ω IF source. The input to the balun is matched to 50Ω with a matching network consisting of L19, C6 and C9. The actual demo board for the HPMX-7202 is shown in Figure 48. The demo board is a Table 3. HPMX-7202 Jumper Position vs. Mode. Switch Label HPMX-7202 Function Left Position (Pins 1 & 2) Right Position (Pins 2 & 3) off/on pwrDn [1] Off [2] On Gmin/max RFTxAgc Min Gain Max Gain Fm/cdma Mode AMPS CDMA Cell/PCS Band Cellular PCS Notes: 1. In all the literature, the “Power Down” function is indicated as pwrDn. On the demonstration board only, it is labelled on the 14 pin header as slpB. 2. To measure minimum current consumption, also set Gmin/max = Min Gain (VRFTxAgc = 0V). 18 multi-layer PCB designed for multiple uses. The 14 pin connector in the upper right hand corner of the PCB is designed to be compatible with automated characterization equipment. No connections are required to be made to the 14 pin connector. For customer characterization, additional switch jumpers have been included for ease of use along with separate Vcc and VccBat supply terminals. The various modes are explained in Table 3. Modes are set with shorting jumpers that connect pins 1 and 2 (Left Position) or pins 2 and 3 (Right Position). It is important that the demo board be powered up with the proper sequence. The “pwrDn” (off/on) shorting jumper must be in the left position during powerup. With the “pwrDn” shorting jumper in the left position, apply both Vcc and VccBat to the appropriate terminals. Then move the “pwrDn” switch jumper to the “on” position. The initial position of the remaining 3 switch jumpers is not important during initial power-up. Mode control can now be accomplished by proper positioning of the switch jumpers. 8 MixOutCell 1 1 DrvInPcs 1 2 3 DrvOutPcs DrvInCell 1 = Vcc 2 = Vcc 3 = VccBat 4 = mode 5 = VccBat 6 = Vcc 7 = gnd 8 = gnd 9 = Vagc 10 = VccBat 11 = band 12 = slpB 13 = VccBat 14 = Vcc DrvOutCell AGILENT TECHNOLOGIES Gmin/max fm/cdma cell/pcs MixOutPcs Ifln hpmx 7202 Demo PCB 02/00 Vbat BW_006 Vcc LoCell Off/On LoPcs Figure 48. HPMX-7202 Demo PCB Layout. Additional Application Information This chip is part of Agilent’s CDMAdvantage solution. CDMA or Code Division Multiple Access uses correlative codes to distinguish one user from another. Frequency divisions are also used, but in a much larger bandwidth (1.25 MHz) than in AMPS (Advanced Mobile Phone System) applications. In CDMA, a single user’s channel consists of a specific frequency combined with a unique code. Channels with other codes appear to a receiver as uncorrelated interference. CDMA also uses sectored cells to increase capacity. One of the major differences in CDMA is its ability to use the same frequency in all sectors of all cells. 19 Capacity in a CDMA system can be increased by minimizing the interference caused by other users (each with their own code) on the CDMA channel. Since each user’s transmitted signal appears as interference to all other users, having the mobile-stations transmit at the lowest possible power is especially important for CDMA systems, although it is important for all multiple access systems to reduce interference. To accomplish this, the CDMA base-station establishes a very tight closed-loop control of the output power of each mobile, commanding it to adjust its power up or down by 1 dB every 1.25 ms, with the goal of setting the power received at the base-station antenna to the minimum required. As a mobile station traverses a cell, its output power will be decreased when it approaches the base-station, and it will be increased as it gets farther away from the center of the cell. The main objective, as explained above, for continuously adjusting the output power of a mobile in a CDMA system is to optimize capacity. Using adaptive-bias techniques in the RF section of CDMA mobile phones, the closedloop requirements can be capitalized on to provide enhanced standby and talk-time performance, while at the same time delivering superior linearity at high output powers. PROBABILITY (%) 4 3 2 1 0 -60 -40 -20 0 20 40 TRANSMIT POWER AT ANTENNA (dBm) Figure 49. Probability Distribution of Mobile Transmit Power. The TIA/EIA-98-C CDMA standard requires the output power of the mobile-station to vary from –50 to +23 dBm (TIA/EIA-98-C, Recommended minimum performance standards for dual-mode spread spectrum mobile-stations). The CDMA Development Group (CDG) has published statistical profiles for the mobile-station transmit power, that were generated from actual field test data from deployed CDMA units. Figure 49 shows the probability distributions for urban and suburban topographies. It is rather clear from inspecting the curves in Figure 49, that the average transmit power in the mobile (10.6 dBm – suburban, 5.4 dBm – urban) is significantly lower than the maximum. (Note: the average transmit power is not at the peak of the distribution functions shown in Figure 49 because of the logarithmic scale on the x-axis). Current consumption in the transmit chain at maximum output is many times considered the only critical figure of merit for selecting the RF components to be used in a handset design. Current consumption at maximum output power is of course still important, for both RF and thermal design reasons. For example, an additional incentive for keeping the 20 current consumption at maximum output power as low as possible, is that the statistical profiles will vary from user to user depending on usage patterns and conditions. In other words, although the statistical profiles published by the CDG obey the laws of large numbers, the statistical profile for an individual user may differ significantly. Having said that, the real figure of merit for CDMA mobile phone should be the statistical-average current consumption, Icc-µ which is the current consumption integrated over the user’s statistical profile. In fact, the CDG’s talktime method of measurement consists of continuously sweeping the output power of the mobile from –50 to +23 dBm according to the statistical profiles shown in Figure 49, to arrive at an industrystandard definition of talk-time (CDG Stage 4 system performance tests). If the RF components have a fixed bias, then the current consumption at maximum output power is the same as the statistical-average current consumption. This is often the case with the baseband and first IF stages of many radio designs. In the higher power stages, particularly the PA driver and the PA itself, the supply current is a strong function of output power. However, if the RF components use adaptive-bias techniques such that the current consumption decreases with the output power, then the maximum and statistical-average current consumption can be set independently, optimizing each one as needed. The current consumption at maximum output power is designed to deliver the required linearity, while the statisticalaverage current consumption is designed to maximize talk-time. Figure 49 illustrates the fact that the mobile spends – statistically – little time at the maximum output power, and therefore the current consumption at that point has only a minor influence on the statistical-average current and, by extension, on talk-time. Figure 50 illustrates the effect of using adaptive bias techniques in the RF VGA of the HPMX-7202. The plot shows the measured gain and current consumption vs. the gain control voltage, RFTxAgc, for the PCS CDMA output. As the gain is reduced, and hence the output power, the current consumption decreases while still maintaining an adequate ACPR. Note that the current plotted is only the VGA current, the mixer current is not included. 100 30 Gain Current 20 80 10 60 0 40 -10 20 -20 0 0.5 1 1.5 2 2.5 3 IccBat (mA) urban suburban GAIN (dB) 5 0 3.5 RFTxAgc (V) Figure 50. HPMX-7202 RF VGA Gain and Supply Current Consumption vs. RFTxAgc Voltage. Figure 51 shows the total current consumption for the HPMX-7202 versus output power for a constant ACPR of -55 dBc/30 kHz in the PCS band. (This ACPR was selected arbitrarily; similar plots can be produced for other values.) 120 Current Consumption (ACPR = -55 dBc/30 kHz) Itot (mA) 100 80 60 Continuous 3 state 2 state 40 -40 -30 -20 -10 0 10 20 Pout (dBm) Figure 52 shows the statisticalaverage current consumption of the upconverter/driver RFICs versus the required maximum output power out of the device. The data is generated by integrating the curves in Figure 51 over the complete output power range of the mobile under the suburban user model. The suburban model gives a higher statistical-average current than the urban model due to the probability distribution tail at high powers. The choice of maximum output power is determined by the gain of the power amplifier, and the loss of the filters, duplexers etc. that follow the upconverter driver amplifier and the PA. Figure 51. HPMX-7202 Total Current Consumption vs. Output Power and Control Method. 75 Suburban model (ACPR = -55 dBc/30 kHz) Continuous 3 state 2 state 21 Iµ (mA) 70 The plot was generated by adjusting the input power and the gain control voltage to achieve the ACPR = –55 dBc at the lowest possible current consumption, for each output power. The HPMX-7202 can deliver up to +9 dBm of power. The lower trace on the plot shows how the total current varies versus output power if the gain control voltage is adjusted continuously. The next (middle) trace illustrates the performance of the device if the gain control voltage adjustment is limited to 3 discrete states, rather than a continuum. This method simplifies the operation of the part, at the expense of a higher statistical-average current consumption. The upper trace illustrates the performance if the gain control voltage adjustment is further limited to only 2 discrete states. 65 60 in Table 4, the statistical-average current consumption can be as low as 56 mA, if the phone can perform a continuous control of the RF VGA. The statistical average current consumption is still a low 70 mA, even if an extremely simple 2-state gain control adjustment is used. Even with a simple 2 state control algorithm, the average supply current is still significantly below the peak current of 94 mA at maximum power. Clearly, relatively low statisticalaverage current consumption can be achieved in the transmit RF section of the mobile if adaptivebias techniques are used. Use of adaptive bias techniques at lower output powers combined with the HPMX-7202’s excellent linearity at high output powers provides manufacturing margin for linearity while also maintaining extended talk time. Table 4. Statistical Average Supply Current. Pout max = +9 dBm 55 50 3 4 5 6 7 8 9 Poutmax (dBm) Figure 52. HPMX-7202 Statistical-Average Current Consumption vs. Desired Maximum Output Power. Figure 51 and Figure 52 illustrate the significant advantage of using adaptive-bias techniques in CDMA mobile phones. The HPMX-7202 has a total current consumption (upconverter + driver) of 94 mA when delivering +9 dBm of output power with an ACPR = -55 dBc/ 30 kHz. However, as summarized Control Method Average Supply Current Analog (N states) 56 mA 3 State 64 mA 2 State 70 mA Part Number Ordering Information Part Number No. of Devices Container HPMX-7202-BLK 10 Bulk HPMX-7202-TR1 1000 Tape and Reel Package Dimensions JEDEC Standard TQFP-32 Package 7.0 ± 0.25 5.0 ± 0.1 7.0 ± 0.25 HPMX-7202 5.0 ± 0.1 YY WW 0.22 typ 0.50 1.4 ± 0.05 0.6 ± 0.15,010 0.05 min./0.1 max. ALL DIMENSIONS SHOWN IN mm 22 Tape Dimensions and Product Orientation for Outline 5 mm x 5 mm TQFP-32 REEL CARRIER TAPE USER FEED DIRECTION COVER TAPE 2.0 (See Note 7) 0.30 ± 0.05 1.5+0.1/-0.0 DIA 4.0 (See Note 2) 1.75 R 0.5 (2) HPMX-7202 1.6 (2) BO 5.0 K1 KO 7.5 (See Note 7) 6.4 (2) AO 12.0 1.5 Min. Cover tape width = 13.3 ± 0.1 mm Cover tape thickness = 0.051 mm (0.002 inch) AO = 9.3 mm BO = 9.3 mm KO = 2.2 mm K1 = 1.6 mm NOTES: 1. Dimensions are in millimeters 2. 10 sprocket hole pitch cumulative tolerance ±0.2 3. Chamber not to exceed 1 mm in 100 mm 4. Material: black conductive Advantek™ polystyrene 5. AO and BO measured on a plane 0.3 mm above the bottom of the pocket. 6. KO measured from a plane on the inside bottom of the pocket to the top surface of the carrier. 7. Pocket position relative to sprocket hole measured as true position of pocket, not pocket hole. 23 16.0 ± 0.3 www.semiconductor.agilent.com Data subject to change. Copyright © 2001 Agilent Technologies, Inc. Obsoletes 5980-1291E, 5980-2260E March 28, 2001 5980-2966EN