NSC ADC14C105CISQ

ADC14C105
14-Bit, 95/105 MSPS A/D Converter
General Description
Features
The ADC14C105 is a high-performance CMOS analog-todigital converter capable of converting analog input signals
into 14-bit digital words at rates up to 105 Mega Samples Per
Second (MSPS). This converter uses a differential, pipelined
architecture with digital error correction and an on-chip sample-and-hold circuit to minimize power consumption and the
external component count, while providing excellent dynamic
performance. A unique sample-and-hold stage yields a fullpower bandwidth of 1 GHz. The ADC14C105 may be operated from a single +3.0V or +3.3V power supply and
consumes low power.
A separate +2.5V supply may be used for the digital output
interface which allows lower power operation with reduced
noise. A power-down feature reduces the power consumption
to very low levels while still allowing fast wake-up time to full
operation. The differential inputs accept a 2V full scale differential input swing. A stable 1.2V internal voltage reference is
provided, or the ADC14C105 can be operated with an external 1.2V reference. Output data format (offset binary versus
2's complement) and duty cycle stabilizer are pin-selectable.
The duty cycle stabilizer maintains performance over a wide
range of clock duty cycles.
The ADC14C105 is available in a 32-lead LLP package and
operates over the industrial temperature range of −40°C to
+85°C.
■
■
■
■
■
■
■
■
1 GHz Full Power Bandwidth
Internal reference and sample-and-hold circuit
Low power consumption
Data Ready output clock
Clock Duty Cycle Stabilizer
Single +3.0V or +3.3V supply operation
Power-down mode
32-pin LLP package, (5x5x0.8mm, 0.5mm pin-pitch)
Key Specifications
■
■
■
■
■
■
■
Resolution
Conversion Rate
SNR (fIN = 240 MHz)
SFDR (fIN = 240 MHz)
Full Power Bandwidth
Power Consumption
14 Bits
105 MSPS
71 dBFS (typ)
82 dBFS (typ)
1 GHz (typ)
350 mW (typ, VA=3.0V)
400 mW (typ, VA=3.3V)
Applications
■
■
■
■
■
High IF Sampling Receivers
Wireless Base Station Receivers
Test and Measurement Equipment
Communications Instrumentation
Portable Instrumentation
Connection Diagram
30017901
© 2007 National Semiconductor Corporation
300179
www.national.com
ADC14C105 14-Bit, 95/105 MSPS A/D Converter
August 2007
ADC14C105
Block Diagram
30017902
Ordering Information
www.national.com
Industrial (−40°C ≤ TA ≤ +85°C)
Package
ADC14C105CISQ
32 Pin LLP
ADC14C105CISQE
32 Pin LLP,
250-Piece Tape and Reel
ADC14C105EB
Evaluation Board
2
ADC14C105
Pin Descriptions and Equivalent Circuits
Pin No.
Symbol
Equivalent Circuit
Description
ANALOG I/O
5
6
VIN+
Differential analog input pins. The differential full-scale input signal
level is 2VP-P with each input pin signal centered on a common
mode voltage, VCM.
VIN-
2
VRP
32
VCMO
1
VRN
These pins should each be bypassed to AGND with a low ESL
(equivalent series inductance) 0.1 µF capacitor placed very close
to the pin to minimize stray inductance. A 0.1 µF capacitor should
be placed between VRP and VRN as close to the pins as possible,
and a 1 µF capacitor should be placed in parallel.
VRP and VRN should not be loaded. VCMO may be loaded to 1mA
for use as a temperature stable 1.5V reference.
It is recommended to use VCMO to provide the common mode
voltage, VCM, for the differential analog inputs, VIN+ and VIN−.
VREF
Reference Voltage. This device provides an internally developed
1.2V reference. When using the internal reference, VREF should be
decoupled to AGND with a 0.1 µF and a 1 µF low equivalent series
inductance (ESL) capacitor .
This pin may be driven with an external 1.2V reference voltage.
This pin should not be used to source or sink current.
OF/DCS
This is a four-state pin controlling the input clock mode and output
data format.
OF/DCS = VA, output data format is 2's complement without duty
cycle stabilization applied to the input clock
OF/DCS = AGND, output data format is offset binary, without duty
cycle stabilization applied to the input clock.
OF/DCS = (2/3)*VA, output data is 2's complement with duty cycle
stabilization applied to the input clock
OF/DCS = (1/3)*VA, output data is offset binary with duty cycle
stabilization applied to the input clock.
11
CLK
The clock input pin.
The analog input is sampled on the rising edge of the clock input.
30
PD
This is a two-state input controlling Power Down.
PD = VA, Power Down is enabled and power dissipation is reduced.
PD = AGND, Normal operation.
31
12
DIGITAL I/O
3
www.national.com
ADC14C105
Pin No.
Symbol
Equivalent Circuit
Description
13-19,
23-29
D0–D13
Digital data output pins that make up the 14-bit conversion result.
D0 (pin 13) is the LSB, while D13 (pin 29) is the MSB of the output
word. Output levels are CMOS compatible.
21
DRDY
Data Ready Strobe. The data output transition is synchronized with
the falling edge of this signal. This signal switches at the same
frequency as the CLK input.
3, 8, 10
VA
Positive analog supply pins. These pins should be connected to a
quiet voltage source and be bypassed to AGND with 0.1 µF
capacitors located close to the power pins.
4, 7, 9,
Exposed Pad
AGND
The ground return for the analog supply.
The exposed pad on back of package must be soldered to ground
plane to ensure rated performance.
20
VDR
Positive driver supply pin for the output drivers. This pin should be
connected to a quiet voltage source and be bypassed to DRGND
with a 0.1 µF capacitor located close to the power pin.
22
DRGND
ANALOG POWER
DIGITAL POWER
www.national.com
The ground return for the digital output driver supply. This pins
should be connected to the system digital ground, but not be
connected in close proximity to the ADC's AGND pins.
4
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
Supply Voltage (VA, VDR)
Voltage on Any Pin
(Not to exceed 4.2V)
Input Current at Any Pin other
than Supply Pins (Note 4)
Package Input Current (Note 4)
Max Junction Temp (TJ)
−40°C ≤ TA ≤ +85°C
+2.7V to +3.6V
+2.4V to VA
Operating Temperature
Supply Voltage (VA)
Output Driver Supply (VDR)
Clock Duty Cycle
(DCS Enabled)
(DCS disabled)
VCM
|AGND-DRGND|
−0.3V to 4.2V
−0.3V to (VA +0.3V)
±5 mA
±50 mA
+150°C
30°C/W
(Notes 1, 3)
30/70 %
45/55 %
1.4V to 1.6V
≤100mV
Thermal Resistance (θJA)
ESD Rating
Human Body Model (Note 6)
2500V
Machine Model (Note 6)
250V
Storage Temperature
−65°C to +150°C
Soldering process must comply with National
Semiconductor's Reflow Temperature Profile
specifications. Refer to www.national.com/packaging.
(Note 7)
Converter Electrical Characteristics
Unless otherwise specified, the following specifications apply: AGND = DRGND = 0V, VA = +3.3V, VDR = +2.5V, Internal VREF =
+1.2V, fCLK = 105 MHz, 50% Duty Cycle, DCS disabled, VCM = VCMO, CL = 5 pF/pin. Typical values are for TA = 25°C. Boldface
limits apply for TMIN ≤ TA ≤ TMAX. All other limits apply for TA = 25°C (Notes 8, 9)
Symbol
Parameter
Conditions
Typical
Limits
(Note 10)
Units
(Limits)
STATIC CONVERTER CHARACTERISTICS
Resolution with No Missing Codes
14
Bits (min)
INL
Integral Non Linearity
±1.8
4
-4
LSB (max)
LSB (min)
DNL
Differential Non Linearity
±0.5
1.3
-0.9
LSB (max)
LSB (min)
PGE
Positive Gain Error
-0.05
±1.25
%FS (max)
NGE
Negative Gain Error
-0.54
±1.25
%FS (max)
TC PGE Positive Gain Error Tempco
−40°C ≤ TA ≤ +85°C
TC NGE Negative Gain Error Tempco
−40°C ≤ TA ≤ +85°C
VOFF
-8
-7
Offset Error (VIN+ = VIN-)
TC VOFF Offset Error Tempco
ppm/°C
0.065
−40°C ≤ TA ≤ +85°C
ppm/°C
±0.55
7.5
%FS (max)
ppm/°C
Under Range Output Code
0
0
Over Range Output Code
16383
16383
REFERENCE AND ANALOG INPUT CHARACTERISTICS
VCMO
Common Mode Output Voltage
1.5
1.4
1.56
V (min)
V (max)
VCM
Analog Input Common Mode Voltage
1.5
1.4
1.6
V (min)
V (max)
CIN
VIN Input Capacitance (each pin to GND) VIN = 1.5 Vdc
(Note 11)
± 0.5 V
VREF
Internal Reference Voltage
TC VREF Internal Reference Voltage Tempco
−40°C ≤ TA ≤ +85°C
VRP
(Note 13)
Internal Reference top
(CLK LOW)
8.5
pF
(CLK HIGH)
3.5
pF
1.18
V
18
ppm/°C
1.98
5
1.89
2.06
V (min)
V (max)
www.national.com
ADC14C105
Operating Ratings
Absolute Maximum Ratings (Notes 1, 3)
ADC14C105
Symbol
VRN
Parameter
Internal Reference bottom
Ext VREF External Reference Voltage
Conditions
Typical
Limits
(Note 10)
Units
(Limits)
(Note 13)
0.98
0.89
1.06
V (min)
V (max)
(Note 13)
1.20
1.176
1.224
V (min)
V (max)
Dynamic Converter Electrical Characteristics
Unless otherwise specified, the following specifications apply: AGND = DRGND = 0V, VA = +3.3V, VDR = +2.5V, Internal VREF =
+1.2V, fCLK = 105 MHz, 50% Duty Cycle, DCS disabled, VCM = VCMO, CL = 5 pF/pin, . Typical values are for TA = 25°C. Boldface
limits apply for TMIN ≤ TA ≤ TMAX. All other limits apply for TA = 25°C (Notes 8, 9)
Symbol
Parameter
Conditions
Typical
Limits
(Note 10)
Units
(Limits)
(Note 2)
DYNAMIC CONVERTER CHARACTERISTICS, AIN = -1dBFS
FPBW
Full Power Bandwidth
SNR
Signal-to-Noise Ratio
SFDR
ENOB
THD
H2
H3
SINAD
IMD
-1 dBFS Input, −3 dB Corner
Spurious Free Dynamic Range
Effective Number of Bits
GHz
fIN = 10 MHz
74
dBFS
fIN = 70 MHz
73.5
dBFS
fIN = 240 MHz
71
fIN = 10 MHz
90
69.4
dBFS
dBFS
fIN = 70 MHz
86
fIN = 240 MHz
82
fIN = 10 MHz
11.9
Bits
fIN = 70 MHz
11.8
Bits
fIN = 240 MHz
11.4
fIN = 10 MHz
−86
dBFS
dBFS
78
11.1
Bits
dBFS
fIN = 70 MHz
−85
fIN = 240 MHz
−79.3
fIN = 10 MHz
−95
dBFS
fIN = 70 MHz
−90
dBFS
fIN = 240 MHz
−86
fIN = 10 MHz
−90
fIN = 70 MHz
−86
fIN = 240 MHz
−82
fIN = 10 MHz
73.5
dBFS
fIN = 70 MHz
73
dBFS
fIN = 240 MHz
70.4
fIN = 19.5 MHz and 20.5MHz,
each -7 dBFS
-82
Total Harmonic Disortion
Second Harmonic Distortion
Third Harmonic Distortion
Signal-to-Noise and Distortion Ratio
Intermodulation Distortion
1.0
dBFS
-74
-78
dBFS
dBFS
dBFS
dBFS
-78
68.8
dBFS
dBFS
dBFS
Logic and Power Supply Electrical Characteristics
Unless otherwise specified, the following specifications apply: AGND = DRGND = 0V, VA = +3.3V, VDR = +2.5V, Internal VREF =
+1.2V, fCLK = 105 MHz, 50% Duty Cycle, DCS disabled, VCM = VCMO, CL = 5 pF/pin. Typical values are for TA = 25°C. Boldface
limits apply for TMIN ≤ TA ≤ TMAX. All other limits apply for TA = 25°C (Notes 8, 9)
Symbol
Parameter
Conditions
Typical
(Note 10)
Limits
Units
(Limits)
DIGITAL INPUT CHARACTERISTICS (CLK, PD)
VIN(1)
Logical “1” Input Voltage
VD = 3.6V
2.0
V (min)
VIN(0)
Logical “0” Input Voltage
VD = 3.0V
0.8
V (max)
IIN(1)
Logical “1” Input Current
VIN = 3.3V
10
µA
IIN(0)
Logical “0” Input Current
VIN = 0V
−10
µA
www.national.com
6
CIN
Parameter
Conditions
Digital Input Capacitance
Typical
(Note 10)
Limits
5
Units
(Limits)
pF
DIGITAL OUTPUT CHARACTERISTICS (D0–D13, DRDY)
VOUT(1)
Logical “1” Output Voltage
IOUT = −0.5 mA , VDR = 2.4V
VOUT(0)
Logical “0” Output Voltage
IOUT = 1.6 mA, VDR = 2.4V
+ISC
Output Short Circuit Source Current
VOUT = 0V
−10
mA
−ISC
Output Short Circuit Sink Current
VOUT = VDR
10
mA
COUT
Digital Output Capacitance
5
pF
2.0
V (min)
0.4
V (max)
POWER SUPPLY CHARACTERISTICS
IA
Analog Supply Current
Full Operation
121
IDR
Digital Output Supply Current
Full Operation (Note 12)
16
Power Consumption
Excludes IDR (Note 12)
400
Power Down Power Consumption
Clock disabled
7.5
141
mA (max)
466
mW (max)
mA
mW
Timing and AC Characteristics
Unless otherwise specified, the following specifications apply: AGND = DRGND = 0V, VA = +3.3V, VDR = +2.5V, Internal VREF =
+1.2V, fCLK = 105 MHz, 50% Duty Cycle, DCS disabled, VCM = VCMO, CL = 5 pF/pin. Typical values are for TA = 25°C. Timing
measurements are taken at 50% of the signal amplitude. Boldface limits apply for TMIN ≤ TA ≤ TMAX. All other limits apply for
TA = 25°C (Notes 8, 9)
Typical
(Note 10)
Limits
Units
(Limits)
Maximum Clock Frequency
105
MHz (max)
Minimum Clock Frequency
20
MHz (min)
Symb
Parameter
Conditions
tCH
Clock High Time
4
ns
tCL
Clock Low Time
4
tCONV
Conversion Latency
tOD
Output Delay of CLK to DATA
Relative to rising edge of CLK(Note 13)
tSU
Data Output Setup Time
tH
Data Output Hold Time
tAD
Aperture Delay
0.6
ns
tAJ
Aperture Jitter
0.1
ps rms
ns
7
Clock Cycles
5.76
3
7.3
ns (min)
ns (max)
Relative to DRDY
4.5
3.7
ns (min)
Relative to DRDY
4.5
3.8
ns (min)
7
www.national.com
ADC14C105
Symbol
ADC14C105
Dynamic Converter Electrical Characteristics at 95MSPS
Unless otherwise specified, the following specifications apply: AGND = DRGND = 0V, VA = +3.3V, VDR = +2.5V, Internal VREF =
+1.2V, fCLK = 95 MHz, 50% Duty Cycle, DCS disabled, VCM = VCMO, CL = 5 pF/pin, . Typical values are for TA = 25°C. Boldface
limits apply for TMIN ≤ TA ≤ TMAX. All other limits apply for TA = 25°C (Notes 8, 9)
Symbol
Parameter
Conditions
Typical
(Note
10)
Limits
Units
(Limits)
(Note 2)
DYNAMIC CONVERTER CHARACTERISTICS, AIN = -1dBFS
SNR
SFDR
ENOB
THD
H2
H3
SINAD
fIN = 10 MHz
74
dBFS
fIN = 70 MHz
73.5
dBFS
fIN = 240 MHz
71
dBFS
fIN = 10 MHz
90
dBFS
fIN = 70 MHz
86
dBFS
fIN = 240 MHz
82
dBFS
fIN = 10 MHz
11.9
Bits
Signal-to-Noise Ratio
Spurious Free Dynamic Range
fIN = 70 MHz
11.8
Bits
fIN = 240 MHz
11.4
Bits
fIN = 10 MHz
−86
dBFS
fIN = 70 MHz
−85
dBFS
fIN = 240 MHz
−80
dBFS
fIN = 10 MHz
-95
dBFS
Effective Number of Bits
Total Harmonic Disortion
fIN = 70 MHz
−90
dBFS
fIN = 240 MHz
−85
dBFS
fIN = 10 MHz
−90
dBFS
fIN = 70 MHz
−86
dBFS
fIN = 240 MHz
−83
dBFS
fIN = 10 MHz
73.5
dBFS
fIN = 70 MHz
73
dBFS
fIN = 240 MHz
70.5
dBFS
mA (max)
Second Harmonic Distortion
Third Harmonic Distortion
Signal-to-Noise and Distortion Ratio
POWER SUPPLY CHARACTERISTICS
IA
Analog Supply Current
Full Operation
115
IDR
Digital Output Supply Current
Full Operation (Note 12)
14.5
mA
Power Consumption
Excludes IDR (Note 12)
380
mW (max)
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
guaranteed to be functional, but do not guarantee specific performance limits. For guaranteed specifications and test conditions, see the Electrical Characteristics.
The guaranteed specifications apply only for the test conditions listed. Some performance characteristics may degrade when the device is not operated under
the listed test conditions. Operation of the device beyond the maximum Operating Ratings is not recommended.
Note 2: Parameters specified in dBFS indicate the value that would be attained with a full-scale input signal.
Note 3: All voltages are measured with respect to GND = AGND = DRGND = 0V, unless otherwise specified.
Note 4: When the input voltage at any pin exceeds the power supplies (that is, VIN < AGND, or VIN > VA), the current at that pin should be limited to ±5 mA. The
±50 mA maximum package input current rating limits the number of pins that can safely exceed the power supplies with an input current of ±5 mA to 10.
Note 5: The maximum allowable power dissipation is dictated by TJ,max, the junction-to-ambient thermal resistance, (θJA), and the ambient temperature, (TA), and
can be calculated using the formula PD,max = (TJ,max - TA )/θJA. The values for maximum power dissipation listed above will be reached only when the device is
operated in a severe fault condition (e.g. when input or output pins are driven beyond the power supply voltages, or the power supply polarity is reversed). Such
conditions should always be avoided.
Note 6: Human Body Model is 100 pF discharged through a 1.5 kΩ resistor. Machine Model is 220 pF discharged through 0 Ω
Note 7: Reflow temperature profiles are different for lead-free and non-lead-free packages.
Note 8: The inputs are protected as shown below. Input voltage magnitudes above VA or below GND will not damage this device, provided current is limited per
(Note 4). However, errors in the A/D conversion can occur if the input goes above 2.6V or below GND as described in the Operating Ratings section.
www.national.com
8
ADC14C105
30017911
Note 9: With a full scale differential input of 2VP-P , the 14-bit LSB is 122.1 µV.
Note 10: Typical figures are at TA = 25°C and represent most likely parametric norms at the time of product characterization. The typical specifications are not
guaranteed.
Note 11: The input capacitance is the sum of the package/pin capacitance and the sample and hold circuit capacitance.
Note 12: IDR is the current consumed by the switching of the output drivers and is primarily determined by load capacitance on the output pins, the supply voltage,
VDR, and the rate at which the outputs are switching (which is signal dependent). IDR=VDR(C0 x f0 + C1 x f1 +....C13 x f13) where VDR is the output driver power
supply voltage, Cn is total capacitance on the output pin, and fn is the average frequency at which that pin is toggling.
Note 13: This parameter is guaranteed by design and/or characterization and is not tested in production.
9
www.national.com
ADC14C105
MSB (MOST SIGNIFICANT BIT) is the bit that has the largest
value or weight. Its value is one half of full scale.
NEGATIVE FULL SCALE ERROR is the difference between
the actual first code transition and its ideal value of ½ LSB
above negative full scale.
OFFSET ERROR is the difference between the two input
voltages [(VIN+) – (VIN-)] required to cause a transition from
code 8191 to 8192.
OUTPUT DELAY is the time delay after the falling edge of the
clock before the data update is presented at the output pins.
PIPELINE DELAY (LATENCY) See CONVERSION LATENCY.
POSITIVE FULL SCALE ERROR is the difference between
the actual last code transition and its ideal value of 1½ LSB
below positive full scale.
POWER SUPPLY REJECTION RATIO (PSRR) is a measure
of how well the ADC rejects a change in the power supply
voltage. PSRR is the ratio of the Full-Scale output of the ADC
with the supply at the minimum DC supply limit to the FullScale output of the ADC with the supply at the maximum DC
supply limit, expressed in dB.
SIGNAL TO NOISE RATIO (SNR) is the ratio, expressed in
dB, of the rms value of the input signal to the rms value of the
sum of all other spectral components below one-half the sampling frequency, not including harmonics or DC.
SIGNAL TO NOISE PLUS DISTORTION (S/N+D or
SINAD) Is the ratio, expressed in dB, of the rms value of the
input signal to the rms value of all of the other spectral components below half the clock frequency, including harmonics
but excluding d.c.
SPURIOUS FREE DYNAMIC RANGE (SFDR) is the difference, expressed in dB, between the rms values of the input
signal and the peak spurious signal, where a spurious signal
is any signal present in the output spectrum that is not present
at the input.
TOTAL HARMONIC DISTORTION (THD) is the ratio, expressed in dB, of the rms total of the first six harmonic levels
at the output to the level of the fundamental at the output. THD
is calculated as
Specification Definitions
APERTURE DELAY is the time after the falling edge of the
clock to when the input signal is acquired or held for conversion.
APERTURE JITTER (APERTURE UNCERTAINTY) is the
variation in aperture delay from sample to sample. Aperture
jitter manifests itself as noise in the output.
CLOCK DUTY CYCLE is the ratio of the time during one cycle
that a repetitive digital waveform is high to the total time of
one period. The specification here refers to the ADC clock
input signal.
COMMON MODE VOLTAGE (VCM) is the common DC voltage applied to both input terminals of the ADC.
CONVERSION LATENCY is the number of clock cycles between initiation of conversion and when that data is presented
to the output driver stage. Data for any given sample is available at the output pins the Pipeline Delay plus the Output
Delay after the sample is taken. New data is available at every
clock cycle, but the data lags the conversion by the pipeline
delay.
DIFFERENTIAL NON-LINEARITY (DNL) is the measure of
the maximum deviation from the ideal step size of 1 LSB.
EFFECTIVE NUMBER OF BITS (ENOB, or EFFECTIVE
BITS) is another method of specifying Signal-to-Noise and
Distortion Ratio or SINAD. ENOB is defined as (SINAD 1.76) / 6.02 and says that the converter is equivalent to a
perfect ADC of this (ENOB) number of bits.
FULL POWER BANDWIDTH is a measure of the frequency
at which the reconstructed output fundamental drops 3 dB
below its low frequency value for a full scale input.
GAIN ERROR is the deviation from the ideal slope of the
transfer function. It can be calculated as:
Gain Error = Positive Full Scale Error − Negative Full Scale
Error
It can also be expressed as Positive Gain Error and Negative
Gain Error, which are calculated as:
PGE = Positive Full Scale Error - Offset Error
NGE = Offset Error - Negative Full Scale Error
INTEGRAL NON LINEARITY (INL) is a measure of the deviation of each individual code from a best fit straight line. The
deviation of any given code from this straight line is measured
from the center of that code value.
INTERMODULATION DISTORTION (IMD) is the creation of
additional spectral components as a result of two sinusoidal
frequencies being applied to the ADC input at the same time.
It is defined as the ratio of the power in the intermodulation
products to the total power in the original frequencies. IMD is
usually expressed in dBFS.
LSB (LEAST SIGNIFICANT BIT) is the bit that has the smallest value or weight of all bits. This value is VFS/2n, where
“VFS” is the full scale input voltage and “n” is the ADC resolution in bits.
MISSING CODES are those output codes that will never appear at the ADC outputs. The ADC14C105 is guaranteed not
to have any missing codes.
www.national.com
where f1 is the RMS power of the fundamental (output) frequency and f2 through f7 are the RMS power of the first six
harmonic frequencies in the output spectrum.
SECOND HARMONIC DISTORTION (2ND HARM) is the difference expressed in dB, between the RMS power in the input
frequency at the output and the power in its 2nd harmonic
level at the output.
THIRD HARMONIC DISTORTION (3RD HARM) is the difference, expressed in dB, between the RMS power in the
input frequency at the output and the power in its 3rd harmonic
level at the output.
10
ADC14C105
Timing Diagram
30017909
FIGURE 1. Output Timing
Transfer Characteristic
30017910
FIGURE 2. Transfer Characteristic
11
www.national.com
ADC14C105
Typical Performance Characteristics DNL, INL
Unless otherwise specified, the following
specifications apply: AGND = DRGND = 0V, VA = +3.3V, VDR = +2.5V, Internal VREF = +1.2V, fCLK = 105 MHz, 50% Duty Cycle,
DCS disabled, VCM = VCMO, fIN = 10 MHz, CL = 5 pF/pin. Typical values are for TA = 25°C.
DNL
INL
30017941
30017942
DNL vs. fCLK
INL vs. fCLK
30017943
30017944
DNL vs. Temperature
INL vs. Temperature
30017947
www.national.com
30017948
12
ADC14C105
DNL vs. VA
INL vs. VA
30017949
30017950
13
www.national.com
ADC14C105
Typical Performance Characteristics
Unless otherwise specified, the following specifications apply:
AGND = DRGND = 0V, VA = +3.3V, VDR = +2.5V, Internal VREF = +1.2V, fCLK = 105 MHz, 50% Duty Cycle, DCS disabled, VCM =
VCMO, fIN = 10 MHz, CL = 5 pF/pin. Typical values are for TA = 25°C.
SNR, SINAD, SFDR vs. VA
Distortion vs. VA
30017951
30017952
SNR, SINAD, SFDR vs. VDR
Distortion vs. VDR
30017953
30017954
SNR, SINAD, SFDR vs. fCLK
Distortion vs. fCLK
30017955
www.national.com
30017956
14
ADC14C105
SNR, SINAD, SFDR vs. Clock Duty Cycle
Distortion vs. Clock Duty Cycle
30017957
30017958
SNR, SINAD, SFDR vs. Clock Duty Cycle, DCS Enabled
Distortion vs. Clock Duty Cycle, DCS Enabled
30017959
30017960
SNR, SINAD, SFDR vs. fIN
Distortion vs. fIN
30017963
30017964
15
www.national.com
ADC14C105
SNR, SINAD, SFDR vs. Temperature
Distortion vs. Temperature
30017965
30017966
Spectral Response @ 10 MHz Input
Spectral Response @ 70 MHz Input
30017968
Spectral Response @ 240 MHz Input
30017969
Intermodulation Distortion, fIN1= 19.5 MHz, fIN2 = 20.5 MHz
30017970
www.national.com
30017971
16
ADC14C105
Power vs. fCLK
30017972
17
www.national.com
ADC14C105
maximum peak-to-peak voltage of 1V, be 180° out of phase
with each other and be centered around VCM.The peak-topeak voltage swing at each analog input pin should not exceed the 1V or the output data will be clipped.
Functional Description
Operating on a single +3.3V supply, the ADC14C105 uses a
pipeline architecture and has error correction circuitry to help
ensure maximum performance. The differential analog input
signal is digitized to 14 bits. The user has the choice of using
an internal 1.2V stable reference, or using an external 1.2V
reference. Any external reference is buffered on-chip to ease
the task of driving that pin.
The output word rate is the same as the clock frequency. The
analog input is acquired at the rising edge of the clock and the
digital data for a given sample is delayed by the pipeline for
7 clock cycles. The digital outputs are CMOS compatible signals that are clocked by a synchronous data ready output
signal (DRDY, pin 21) at the same rate as the clock input. Duty
cycle stabilization and output data format are selectable using
the quad state function OF/DCS pin (pin 12). The output data
can be set for offset binary or two's complement.
Power-down is selectable using the PD pin (pin 30). A logic
high on the PD pin reduces the converter power consumption.
For normal operation, the PD pin should be connected to the
analog ground (AGND).
30017915
FIGURE 3. Expected Input Signal Range
For single frequency sine waves the full scale error in LSB
can be described as approximately
Applications Information
EFS = 16384 ( 1 - sin (90° + dev))
1.0 OPERATING CONDITIONS
We recommend that the following conditions be observed for
operation of the ADC14C105:
2.7V ≤ VA ≤ 3.6V
2.4V ≤ VDR ≤ VA
20 MHz ≤ fCLK ≤ 105 MHz
1.2V internal reference
VREF = 1.2V (for an external reference)
VCM = 1.5V (from VCMO)
Where dev is the angular difference in degrees between the
two signals having a 180° relative phase relationship to each
other (see Figure 4). For single frequency inputs, angular errors result in a reduction of the effective full scale input. For
complex waveforms, however, angular errors will result in
distortion.
2.0 ANALOG INPUTS
2.1 Signal Inputs
30017916
2.1.1 Differential Analog Input Pins
The ADC14C105 has one pair of analog signal input pins,
VIN+ and VIN−, which form a differential input pair. The input
signal, VIN, is defined as
FIGURE 4. Angular Errors Between the Two Input Signals
Will Reduce the Output Level or Cause Distortion
It is recommended to drive the analog inputs with a source
impedance less than 100Ω. Matching the source impedance
for the differential inputs will improve even ordered harmonic
performance (particularly second harmonic).
Table 1 indicates the input to output relationship of the ADC14C105.
VIN = (VIN+) – (VIN−)
Figure 3 shows the expected input signal range. Note that the
common mode input voltage, VCM, should be 1.5V. Using
VCMO (pin 32) for VCM will ensure the proper input common
mode level for the analog input signal. The positive peaks of
the individual input signals should each never exceed 2.6V.
Each analog input pin of the differential pair should have a
www.national.com
18
VIN+
VIN−
Binary Output
2’s Complement Output
VCM − VREF/2
VCM + VREF/2
00 0000 0000 0000
10 0000 0000 0000
VCM − VREF/4
VCM + VREF/4
01 0000 0000 0000
11 0000 0000 0000
VCM
VCM
10 0000 0000 0000
00 0000 0000 0000
VCM + VREF/4
VCM − VREF/4
11 0000 0000 0000
01 0000 0000 0000
VCM + VREF/2
VCM − VREF/2
11 1111 1111 1111
01 1111 1111 1111
Negative Full-Scale
Mid-Scale
Positive Full-Scale
Figure 5 and Figure 6 show examples of single-ended to differential conversion circuits. The circuit in Figure 5 works well
for input frequencies up to approximately 70MHz, while the
circuit in Figure 6 works well above 70MHz.
2.1.2 Driving the Analog Inputs
The VIN+ and the VIN− inputs of the ADC14C105 have an internal sample-and-hold circuit which consists of an analog
switch followed by a switched-capacitor amplifier.
30017920
FIGURE 5. Low Input Frequency Transformer Drive Circuit
30017921
FIGURE 6. High Input Frequency Transformer Drive Circuit
One short-coming of using a transformer to achieve the single-ended to differential conversion is that most RF transformers have poor low frequency performance. A differential
amplifier can be used to drive the analog inputs for low frequency applications. The amplifier must be fast enough to
settle from the charging glitches on the analog input resulting
from the sample-and-hold operation before the clock goes
high and the sample is passed to the ADC core.
The SFDR performance of the converter depends on the external signal conditioning circuity used, as this affects how
quickly the sample-and-hold charging glitch will settle. An external resistor and capacitor network as shown in Figure 7
should be used to isolate the charging glitches at the ADC
input from the external driving circuit and to filter the wideband
noise at the converter input. These components should be
placed close to the ADC inputs because the analog input of
the ADC is the most sensitive part of the system, and this is
the last opportunity to filter that input. For Nyquist applications
the RC pole should be at the ADC sample rate. The ADC input
capacitance in the sample mode should be considered when
setting the RC pole. For wideband undersampling applica-
tions, the RC pole should be set at least 1.5 to 2 times the
maximum input frequency to maintain a linear delay response.
2.1.3 Input Common Mode Voltage
The input common mode voltage, VCM, should be in the range
of 1.4V to 1.6V and be a value such that the peak excursions
of the analog signal do not go more negative than ground or
more positive than 2.6V. It is recommended to use VCMO (pin
32) as the input common mode voltage.
If the ADC14C105 is operated with VA=3.6V, a resistor of approximately 1KΩ should be used from the VCMO pin to
AGND.This will help maintain stability over the entire temperature range when using a high supply voltage.
2.2 Reference Pins
The ADC14C105 is designed to operate with an internal or
external 1.2V reference. The internal 1.2 Volt reference is the
default condition when no external reference input is applied
to the VREF pin. If a voltage is applied to the VREF pin, then
that voltage is used for the reference. The VREF pin should
19
www.national.com
ADC14C105
TABLE 1. Input to Output Relationship
ADC14C105
always be bypassed to ground with a 0.1 µF capacitor close
to the reference input pin.
It is important that all grounds associated with the reference
voltage and the analog input signal make connection to the
ground plane at a single, quiet point to minimize the effects of
noise currents in the ground path.
The Reference Bypass Pins (VRP, VCMO, and VRN) are made
available for bypass purposes. These pins should each be
bypassed to AGND with a low ESL (equivalent series inductance) 1 µF capacitor placed very close to the pin to minimize
stray inductance. A 0.1 µF capacitor should be placed between VRP and VRN as close to the pins as possible, and a 1
µF capacitor should be placed in parallel. This configuration
is shown in Figure 7. It is necessary to avoid reference oscillation, which could result in reduced SFDR and/or SNR.
VCMO may be loaded to 1mA for use as a temperature stable
1.5V reference. The remaining pins should not be loaded.
Smaller capacitor values than those specified will allow faster
recovery from the power down mode, but may result in degraded noise performance. Loading any of these pins, other
than VCMO may result in performance degradation.
The nominal voltages for the reference bypass pins are as
follows:
VCMO = 1.5 V
VRP = 2.0 V
VRN = 1.0 V
The clock line should be terminated at its source in the characteristic impedance of that line. Take care to maintain a
constant clock line impedance throughout the length of the
line. Refer to Application Note AN-905 for information on setting characteristic impedance.
It is highly desirable that the the source driving the ADC clock
pins only drive that pin. However, if that source is used to drive
other devices, then each driven pin should be AC terminated
with a series RC to ground, such that the resistor value is
equal to the characteristic impedance of the clock line and the
capacitor value is
where tPD is the signal propagation rate down the clock line,
"L" is the line length and ZO is the characteristic impedance
of the clock line. This termination should be as close as possible to the ADC clock pin but beyond it as seen from the clock
source. Typical tPD is about 150 ps/inch (60 ps/cm) on FR-4
board material. The units of "L" and tPD should be the same
(inches or centimeters).
The duty cycle of the clock signal can affect the performance
of the A/D Converter. Because achieving a precise duty cycle
is difficult, the ADC14C105 has a Duty Cycle Stabilizer. It is
designed to maintain performance over a clock duty cycle
range of 30% to 70%.
2.3 OF/DCS Pin
Duty cycle stabilization and output data format are selectable
using this quad state function pin. When enabled, duty cycle
stabilization can compensate for clock inputs with duty cycles
ranging from 30% to 70% and generate a stable internal clock,
improving the performance of the part. With OF/DCS = VA the
output data format is 2's complement and duty cycle stabilization is not used. With OF/DCS = AGND the output data
format is offset binary and duty cycle stabilization is not used.
With OF/DCS = (2/3)*VA the output data format is 2's complement and duty cycle stabilization is applied to the clock. If
OF/DCS is (1/3)*VA the output data format is offset binary and
duty cycle stabilization is applied to the clock. While the sense
of this pin may be changed "on the fly," doing this is not recommended as the output data could be erroneous for a few
clock cycles after this change is made.
3.2 Power-Down (PD)
The PD pin, when high, holds the ADC14C105 in a powerdown mode to conserve power when the converter is not
being used. The power consumption in this state is 5 mW if
the clock is stopped when PD is high. The output data pins
are undefined and the data in the pipeline is corrupted while
in the power down mode.
The Power Down Mode Exit Cycle time is determined by the
value of the components on pins 1, 2, and 32 and is about 3
ms with the recommended components on the VRP, VCMO and
VRN reference bypass pins. These capacitors loose their
charge in the Power Down mode and must be recharged by
on-chip circuitry before conversions can be accurate. Smaller
capacitor values allow slightly faster recovery from the power
down mode, but can result in a reduction in SNR, SINAD and
ENOB performance.
3.0 DIGITAL INPUTS
Digital CMOS compatible inputs consist of CLK, and PD.
4.0 DIGITAL OUTPUTS
Digital outputs consist of the CMOS signals D0-D13, and
DRDY.
The ADC14C105 has 15 CMOS compatible data output pins
corresponding to the converted input value and a data ready
(DRDY) signal that should be used to capture the output data.
Valid data is present at these outputs while the PD pin is low.
Data should be captured and latched with the rising edge of
the DRDY signal.
Be very careful when driving a high capacitance bus. The
more capacitance the output drivers must charge for each
conversion, the more instantaneous digital current flows
through VDR and DRGND. These large charging current
spikes can cause on-chip ground noise and couple into the
analog circuitry, degrading dynamic performance. Adequate
bypassing, limiting output capacitance and careful attention
to the ground plane will reduce this problem. The result could
be an apparent reduction in dynamic performance.
3.1 Clock Input
The CLK controls the timing of the sampling process. To
achieve the optimum noise performance, the clock input
should be driven with a stable, low jitter clock signal in the
range indicated in the Electrical Table. The clock input signal
should also have a short transition region. This can be
achieved by passing a low-jitter sinusoidal clock source
through a high speed buffer gate. This configuration is shown
in Figure 7 . The trace carrying the clock signal should be as
short as possible and should not cross any other signal line,
analog or digital, not even at 90°. Figure 7 shows the recommended clock input circuit.
The clock signal also drives an internal state machine. If the
clock is interrupted, or its frequency is too low, the charge on
the internal capacitors can dissipate to the point where the
accuracy of the output data will degrade. This is what limits
the minimum sample rate.
www.national.com
20
ADC14C105
30017919
FIGURE 7. Application Circuit
Since digital switching transients are composed largely of
high frequency components, total ground plane copper
weight will have little effect upon the logic-generated noise.
This is because of the skin effect. Total surface area is more
important than is total ground plane area.
Generally, analog and digital lines should cross each other at
90° to avoid crosstalk. To maximize accuracy in high speed,
high resolution systems, however, avoid crossing analog and
digital lines altogether. It is important to keep clock lines as
short as possible and isolated from ALL other lines, including
other digital lines. Even the generally accepted 90° crossing
should be avoided with the clock line as even a little coupling
can cause problems at high frequencies. This is because other lines can introduce jitter into the clock line, which can lead
to degradation of SNR. Also, the high speed clock can introduce noise into the analog chain.
Best performance at high frequencies and at high resolution
is obtained with a straight signal path. That is, the signal path
through all components should form a straight line wherever
possible.
Be especially careful with the layout of inductors and transformers. Mutual inductance can change the characteristics of
the circuit in which they are used. Inductors and transformers
should not be placed side by side, even with just a small part
of their bodies beside each other. For instance, place transformers for the analog input and the clock input at 90° to one
another to avoid magnetic coupling.
The analog input should be isolated from noisy signal traces
to avoid coupling of spurious signals into the input. Any external component (e.g., a filter capacitor) connected between
the converter's input pins and ground or to the reference input
pin and ground should be connected to a very clean point in
the ground plane.
All analog circuitry (input amplifiers, filters, reference components, etc.) should be placed in the analog area of the board.
All digital circuitry and dynamic I/O lines should be placed in
the digital area of the board. The ADC14C105 should be between these two areas. Furthermore, all components in the
reference circuitry and the input signal chain that are connected to ground should be connected together with short
5.0 POWER SUPPLY CONSIDERATIONS
The power supply pins should be bypassed with a 0.1 µF capacitor and with a 100 pF ceramic chip capacitor close to each
power pin. Leadless chip capacitors are preferred because
they have low series inductance.
As is the case with all high-speed converters, the ADC14C105 is sensitive to power supply noise. Accordingly, the
noise on the analog supply pin should be kept below 100
mVP-P.
No pin should ever have a voltage on it that is in excess of the
supply voltages, not even on a transient basis. Be especially
careful of this during power turn on and turn off.
The VDR pin provides power for the output drivers and may be
operated from a supply in the range of 2.4V to VA. This enables lower power operation, reduces the noise coupling
effects from the digital outputs to the analog circuitry and simplifies interfacing to lower voltage devices and systems.
6.0 LAYOUT AND GROUNDING
Proper grounding and proper routing of all signals are essential to ensure accurate conversion. Maintaining separate analog and digital areas of the board, with the ADC14C105
between these areas, is required to achieve specified performance.
The ground return for the data outputs (DRGND) carries the
ground current for the output drivers. The output current can
exhibit high transients that could add noise to the conversion
process. To prevent this from happening, the DRGND pins
should NOT be connected to system ground in close proximity
to any of the ADC14C105's other ground pins.
Capacitive coupling between the typically noisy digital circuitry and the sensitive analog circuitry can lead to poor performance. The solution is to keep the analog circuitry separated
from the digital circuitry, and to keep the clock line as short as
possible.
The effects of the noise generated from the ADC output
switching can be minimized through the use of 22Ω resistors
in series with each data output line. Locate these resistors as
close to the ADC output pins as possible.
21
www.national.com
ADC14C105
traces and enter the ground plane at a single, quiet point. All
ground connections should have a low inductance path to
ground.
7.0 DYNAMIC PERFORMANCE
To achieve the best dynamic performance, the clock source
driving the CLK input must have a sharp transition region and
be free of jitter. Isolate the ADC clock from any digital circuitry
with buffers, as with the clock tree shown in Figure 8. The
gates used in the clock tree must be capable of operating at
frequencies much higher than those used if added jitter is to
be prevented.
As mentioned in Section 6.0, it is good practice to keep the
ADC clock line as short as possible and to keep it well away
from any other signals. Other signals can introduce jitter into
the clock signal, which can lead to reduced SNR performance, and the clock can introduce noise into other lines.
Even lines with 90° crossings have capacitive coupling, so try
to avoid even these 90° crossings of the clock line.
www.national.com
30017917
FIGURE 8. Isolating the ADC Clock from other Circuitry
with a Clock Tree
22
ADC14C105
Physical Dimensions inches (millimeters) unless otherwise noted
32-Lead LLP Package
Ordering Number:
ADC14C105CISQ
NS Package Number SQA32A
23
www.national.com
ADC14C105 14-Bit, 95/105 MSPS A/D Converter
Notes
THE CONTENTS OF THIS DOCUMENT ARE PROVIDED IN CONNECTION WITH NATIONAL SEMICONDUCTOR CORPORATION
(“NATIONAL”) PRODUCTS. NATIONAL MAKES NO REPRESENTATIONS OR WARRANTIES WITH RESPECT TO THE ACCURACY
OR COMPLETENESS OF THE CONTENTS OF THIS PUBLICATION AND RESERVES THE RIGHT TO MAKE CHANGES TO
SPECIFICATIONS AND PRODUCT DESCRIPTIONS AT ANY TIME WITHOUT NOTICE. NO LICENSE, WHETHER EXPRESS,
IMPLIED, ARISING BY ESTOPPEL OR OTHERWISE, TO ANY INTELLECTUAL PROPERTY RIGHTS IS GRANTED BY THIS
DOCUMENT.
TESTING AND OTHER QUALITY CONTROLS ARE USED TO THE EXTENT NATIONAL DEEMS NECESSARY TO SUPPORT
NATIONAL’S PRODUCT WARRANTY. EXCEPT WHERE MANDATED BY GOVERNMENT REQUIREMENTS, TESTING OF ALL
PARAMETERS OF EACH PRODUCT IS NOT NECESSARILY PERFORMED. NATIONAL ASSUMES NO LIABILITY FOR
APPLICATIONS ASSISTANCE OR BUYER PRODUCT DESIGN. BUYERS ARE RESPONSIBLE FOR THEIR PRODUCTS AND
APPLICATIONS USING NATIONAL COMPONENTS. PRIOR TO USING OR DISTRIBUTING ANY PRODUCTS THAT INCLUDE
NATIONAL COMPONENTS, BUYERS SHOULD PROVIDE ADEQUATE DESIGN, TESTING AND OPERATING SAFEGUARDS.
EXCEPT AS PROVIDED IN NATIONAL’S TERMS AND CONDITIONS OF SALE FOR SUCH PRODUCTS, NATIONAL ASSUMES NO
LIABILITY WHATSOEVER, AND NATIONAL DISCLAIMS ANY EXPRESS OR IMPLIED WARRANTY RELATING TO THE SALE
AND/OR USE OF NATIONAL PRODUCTS INCLUDING LIABILITY OR WARRANTIES RELATING TO FITNESS FOR A PARTICULAR
PURPOSE, MERCHANTABILITY, OR INFRINGEMENT OF ANY PATENT, COPYRIGHT OR OTHER INTELLECTUAL PROPERTY
RIGHT.
LIFE SUPPORT POLICY
NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR
SYSTEMS WITHOUT THE EXPRESS PRIOR WRITTEN APPROVAL OF THE CHIEF EXECUTIVE OFFICER AND GENERAL
COUNSEL OF NATIONAL SEMICONDUCTOR CORPORATION. As used herein:
Life support devices or systems are devices which (a) are intended for surgical implant into the body, or (b) support or sustain life and
whose failure to perform when properly used in accordance with instructions for use provided in the labeling can be reasonably expected
to result in a significant injury to the user. A critical component is any component in a life support device or system whose failure to perform
can be reasonably expected to cause the failure of the life support device or system or to affect its safety or effectiveness.
National Semiconductor and the National Semiconductor logo are registered trademarks of National Semiconductor Corporation. All other
brand or product names may be trademarks or registered trademarks of their respective holders.
Copyright© 2007 National Semiconductor Corporation
For the most current product information visit us at www.national.com
National Semiconductor
Americas Customer
Support Center
Email:
[email protected]
Tel: 1-800-272-9959
www.national.com
National Semiconductor Europe
Customer Support Center
Fax: +49 (0) 180-530-85-86
Email: [email protected]
Deutsch Tel: +49 (0) 69 9508 6208
English Tel: +49 (0) 870 24 0 2171
Français Tel: +33 (0) 1 41 91 8790
National Semiconductor Asia
Pacific Customer Support Center
Email: [email protected]
National Semiconductor Japan
Customer Support Center
Fax: 81-3-5639-7507
Email: [email protected]
Tel: 81-3-5639-7560