19-3769; Rev 0; 9/05 KIT ATION EVALU E L B A IL AVA 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier The MAX9709 stereo/mono, Class D audio power amplifier delivers up to 2 x 25W into an 8Ω stereo mode and 1 x 50W into a 4Ω load in mono mode while offering up to 87% efficiency. The MAX9709 provides Class AB amplifier performance with the benefits of Class D efficiency, eliminating the need for a bulky heatsink and conserving power. The MAX9709 operates from a single +10V to +22V supply, driving the load in a BTL configuration. The MAX9709 offers two modulation schemes: a fixed-frequency modulation (FFM) mode, and a spread-spectrum modulation (SSM) mode that reduces EMI-radiated emissions. The MAX9709 can be synchronized to an external clock from 600kHz to 1.2MHz. A synchronized output allows multiple units to be cascaded in the system. Features include fully differential inputs, comprehensive click-and-pop suppression, and four selectable-gain settings (22dB, 25dB, 29.5dB, and 36dB). A pin-programmable thermal flag provides seven different thermal warning thresholds. Short-circuit and thermal-overload protection prevent the device from being damaged during a fault condition. The MAX9709 is available in 56-pin TQFN (8mm x 8mm x 0.8mm) and 64-pin TQFP (10mm x 10mm x 1.4mm) packages, and is specified over the extended -40°C to +85°C temperature range. Features ♦ 2 x 25W Output Power in Stereo Mode (8Ω, THD = 10%) ♦ 1 x 50W Output Power in Mono Mode (4Ω, THD = 10%) ♦ High Efficiency: Up to 87% ♦ Filterless Class D Amplifier ♦ Unique Patented Spread-Spectrum Mode ♦ Programmable Gain (+22dB, +25dB, +29.5dB, +36dB) ♦ High PSRR (90dB at 1kHz) ♦ Differential Inputs Suppress Common-Mode Noise ♦ Shutdown and Mute Control ♦ Integrated Click-and-Pop Suppression ♦ Low 0.1% THD+N ♦ Current Limit and Thermal Protection ♦ Programmable Thermal Flag ♦ Clock Synchronization Input and Output ♦ Available in Thermally Efficient, Space-Saving Packages: 56-Pin TQFN and 64-Pin TQFP Ordering Information Applications PART TEMP RANGE PIN-PACKAGE PKG CODE LCD TVs PDP TVs MAX9709ETN+ -40°C to +85°C 56 TQFN-EP** T5688-3 Automotive PC/HiFi Audio Solutions MAX9709ECB+* -40°C to +85°C 64 TQFP-EP** C64E-6 +Denotes lead-free package. *Future product—Contact factory for availability. **EP = Exposed paddle. Pin Configurations appear at end of data sheet. Simplified Block Diagram 2 FS1, FS2 SYNC MAX9709 SYNCOUT RIGHT CHANNEL GAIN CONTROL MONO G1, G2 TH0, TH1, TH2 AUDIO INPUT CLASS D MODULATOR LEFT CHANNEL MONO 2 3 TEMP G1, G2 TH0, TH1, TH2 MAX9709 SYNCOUT CLASS D MODULATOR VDIGITAL OUTPUT PROTECTION STEREO MODE 2 FS1, FS2 SYNC GAIN CONTROL OUTPUT PROTECTION 2 3 TEMP MONO MODE ________________________________________________________________ Maxim Integrated Products For pricing, delivery, and ordering information, please contact Maxim/Dallas Direct! at 1-888-629-4642, or visit Maxim’s website at www.maxim-ic.com. 1 MAX9709 General Description MAX9709 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier ABSOLUTE MAXIMUM RATINGS PVDD, VDD to PGND, GND .......................................-0.3 to +30V PVDD to VDD ..........................................................-0.3V to +0.3V OUTR+, OUTR-, OUTL+, OUTL- to PGND, GND..........................-0.3V to (PVDD + 0.3V) C1N to GND .............................................-0.3V to (PVDD + 0.3V) C1P to GND..............................(PVDD - 0.3V) to (CPVDD + 0.3V) CPVDD to GND ..........................................(PVDD - 0.3V) to +40V All Other Pins to GND.............................................-0.3V to +12V Continuous Input Current (except PVDD, VDD, OUTR+, OUTR-, OUTL+, and OUTL-) ..........................................20mA Continuous Power Dissipation (TA = +70°C) 56-Pin Thin QFN (derate 47.6mW/°C above +70°C) .....3.81W 64-Pin TQFP (derate 43.5mW/°C above +70°C)............3.48W Operating Temperature Range ...........................-40°C to +85°C Storage Temperature Range .............................-65°C to +150°C Junction Temperature ......................................................+150°C Thermal Resistance (θJC) 56-Pin Thin QFN… ......................................................0.6°C/W 64-Pin TQFP…................................................................2°C/W Lead Temperature (soldering, 10s) .................................+300°C Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. ELECTRICAL CHARACTERISTICS (PVDD = VDD = +20V, PGND = GND = 0V, CSS = 0.47µF, CREG = 0.01µF, C1 = 0.1µF, C2 = 1µF, RLOAD = ∞, MONO = low (stereo mode), SHDN = MUTE = high, G1 = low, G2 = high (AV = 22dB), FS1 = FS2 = high (SSM), SYNCIN = low. All load resistors (RL) are connected between OUT_+ and OUT_-, unless otherwise stated. TA = TMIN to TMAX, unless otherwise noted. Typical values are at TA = +25°C.) (Note 1) PARAMETER Supply Voltage Range Shutdown Current SYMBOL VDD ISHDN CONDITIONS Inferred from PSRR test MIN TYP 10 SHDN = low 0.1 Shutdown to Full Operation tSON 100 Mute to Full Operation tMUTE 100 Input Impedance RIN Switch On-Resistance Switching Frequency CMRR RDS fSW 40 63 90 G1 = 1, G2 = 0 25 43 60 G1 = 0, G2 = 0 12 21 30 600 200mVP-P ripple (Note 2) 3 67 90 fRIPPLE = 20kHz 52 DC, input referred 49 kΩ ±40 70 dB 60 One power switch 0.3 0.6 200 220 FS1 FS2 0 0 1 1 (SSM) 200 1 0 160 0 1 250 FS1 = FS2 = high (SSM) SYNCIN Lock Range Equal to fSW x 4 mV dB f = 20Hz to 20kHz, input referred 180 kΩ 90 fRIPPLE = 1kHz Oscillator Spread Bandwidth 2 ms G1 = 1, G2 = 1 PVDD = 10V to 22V Common-Mode Rejection Ratio ms 125 Output Offset Voltage PSRR µA 85 SHDN = GND Power-Supply Rejection Ratio V 1 50 AC-coupled input, measured between OUT_+ and OUT_- UNITS 22 G1 = 0, G2 = 1 Output Pulldown Resistance VOS MAX kHz ±2 600 _______________________________________________________________________________________ Ω % 1200 kHz 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier (PVDD = VDD = +20V, PGND = GND = 0V, CSS = 0.47µF, CREG = 0.01µF, C1 = 0.1µF, C2 = 1µF, RLOAD = ∞, MONO = low (stereo mode), SHDN = MUTE = high, G1 = low, G2 = high (AV = 22dB), FS1 = FS2 = high (SSM), SYNCIN = low. All load resistors (RL) are connected between OUT_+ and OUT_-, unless otherwise stated. TA = TMIN to TMAX, unless otherwise noted. Typical values are at TA = +25°C.) (Note 1) PARAMETER SYMBOL Gain AV MIN TYP MAX G1 = 0, G2 = 1 CONDITIONS 21.6 22.0 22.3 G1 = 1, G2 = 1 24.9 25.0 25.6 G1 = 1, G2 = 0 29.2 29.5 29.9 35.9 36.0 36.6 G1 = 0, G2 = 0 TEMP Flag Threshold TFLAG TEMP Flag Accuracy TH2 TH1 TH0 0 0 0 80 0 0 1 90 0 1 0 100 0 1 1 110 1 0 0 120 1 0 1 129 1 1 0 139 1 1 1 From +80°C to +140°C dB °C ±6 TEMP Flag Hysteresis UNITS 2 °C °C STEREO MODE (RLOAD = 8Ω, Note 3) Quiescent Current MUTE = 1, RLOAD = ∞ 20 33 MUTE = 0 6.5 13 PVDD = 20V Output Power POUT Total Harmonic Distortion Plus Noise Signal-to-Noise Ratio THD+N SNR η Efficiency Left-Right Channel Gain Matching f = 1kHz, THD = 10%, TA = +25°C 25 PVDD = 22V 29 PVDD = 12V, RLOAD = 4Ω 15 f = 1kHz, BW = 22Hz to 22kHz, POUT = 12W POUT = 10W mA 0.1 22Hz to 22kHz 91 A-weighted 96 W % dB POUT = 25W + 25W, f = 1kHz 87 % RLOAD = ∞ 0.2 % _______________________________________________________________________________________ 3 MAX9709 ELECTRICAL CHARACTERISTICS (continued) MAX9709 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier ELECTRICAL CHARACTERISTICS (continued) (PVDD = VDD = +20V, PGND = GND = 0V, CSS = 0.47µF, CREG = 0.01µF, C1 = 0.1µF, C2 = 1µF, RLOAD = ∞, MONO = low (stereo mode), SHDN = MUTE = high, G1 = low, G2 = high (AV = 22dB), FS1 = FS2 = high (SSM), SYNCIN = low. All load resistors (RL) are connected between OUT_+ and OUT_-, unless otherwise stated. TA = TMIN to TMAX, unless otherwise noted. Typical values are at TA = +25°C.) (Note 1) PARAMETER SYMBOL CONDITIONS Output Short-Circuit Current Threshold ISC RLOAD = 0Ω Click-and-Pop Level KCP Peak voltage, 32 samples/second, A-weighted (Notes 2, 5) MIN TYP MAX 3 Into shutdown -63 Out of shutdown -55 UNITS A dBV MONO MODE (RLOAD = 4Ω, MONO = HIGH) (Note 6) Quiescent Current Output Power Total Harmonic Distortion Plus Noise Signal-to-Noise Ratio Efficiency POUT THD+N SNR η MUTE = 1, RLOAD = ∞ 20 MUTE = 0 6.5 f = 1kHz, THD = 10% RLOAD = 8Ω 25 RLOAD = 4Ω 50 f = 1kHz, BW = 22Hz to 22kHz, POUT = 22W POUT = 10W 0.09 20Hz to 20kHz 91 A-weighted 95 6 A Click-and-Pop Level KCP Peak voltage, 32 samples/second, A-weighted (Notes 2, 5) Into shutdown -60 Out of shutdown -63 dBV DIGITAL INPUTS (SHDN, MUTE, G1, G2, FS1, FS2, TH0, TH1, TH2, SYNCIN, MONO) Logic-Input Current IIN 0 to 12V VIL dB % RLOAD = 0Ω VIH % 86 ISC Logic-Input Low Voltage W POUT = 54W, f = 1kHz Output Short-Circuit Current Threshold Logic-Input High Voltage mA 1 µA 0.8 V 2.5 V OPEN-DRAIN OUTPUTS (TEMP, SYNCOUT) Open-Drain Output Low Voltage Leakage Current VOL ILEAK ISINK = 3mA VPULLUP = 5.5V 0.4 0.2 V µA All devices are 100% production tested at +25°C. All temperature limits are guaranteed by design. Inputs AC-coupled to GND. Testing performed with an 8Ω resistive load in series with a 68µH inductive load across the BTL outputs. Minimum output power is guaranteed by pulse testing. Testing performed with an 8Ω resistive load in series with a 68µH inductive load connected across BTL outputs. Mode transitions are controlled by SHDN. Note 6: Testing performed with a 4Ω resistive load in series with a 33µH inductive load across the BTL outputs. Note 1: Note 2: Note 3: Note 4: Note 5: 4 _______________________________________________________________________________________ 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier fIN = 1kHz POUT = 12W 1 THD+N (%) THD+N (%) RLOAD = 4Ω 1 0.1 0.1 0.01 5 10 15 20 25 30 0.01 0.01 35 0 5 10 15 25 20 10 1k 10k 100k OUTPUT POWER (W) FREQUENCY (Hz) EFFICIENCY vs. OUTPUT POWER (STEREO MODE) OUTPUT POWER vs. SUPPLY VOLTAGE (STEREO MODE) NO-LOAD SUPPLY CURRENT vs. SUPPLY VOLTAGE (STEREO MODE) 90 30 OUTPUT POWER (W) 80 70 60 50 40 30 24 25 THD+N = 10% 20 15 THD+N = 1% 10 22 20 0 15 20 25 30 10 OUTPUT POWER (W) 12 14 16 18 20 10 12 16 18 20 22 TOTAL HARMONIC DISTORTION PLUS NOISE vs. OUTPUT POWER (MONO MODE) 100 MAX9709 toc07 SHDN = 0 14 SUPPLY VOLTAGE (V) SUPPLY VOLTAGE (V) 4.0 RLOAD = 4Ω fIN = 1kHz 3.0 10 2.5 THD+N (%) SUPPLY CURRENT (nA) TA = -40°C 14 24 22 SHUTDOWN SUPPLY CURRENT vs. SUPPLY VOLTAGE 3.5 16 MAX9709 toc08 10 18 10 0 5 TA = +25°C TA = +85°C 20 12 5 10 MAX9709 toc06 35 MAX9709 toc04 100 0 100 OUTPUT POWER (W) SUPPLY CURRENT (mA) 0 MAX9709 toc05 THD+N (%) 1 10 0.1 EFFICIENCY (%) PVDD = 12V RLOAD = 8Ω 10 TOTAL HARMONIC DISTORTION PLUS NOISE vs. FREQUENCY (STEREO MODE) MAX9709 toc02 100 MAX9709 toc01 100 TOTAL HARMONIC DISTORTION PLUS NOISE vs. OUTPUT POWER (STEREO MODE) MAX9709 toc03 TOTAL HARMONIC DISTORTION PLUS NOISE vs. OUTPUT POWER (STEREO MODE) 2.0 1.5 1.0 1 0.1 0.5 0 0.01 10 12 14 16 18 SUPPLY VOLTAGE (V) 20 22 0 10 20 30 40 50 60 OUTPUT POWER (W) _______________________________________________________________________________________ 5 MAX9709 Typical Operating Characteristics (PVDD = VDD = +20V, PGND = GND = 0V, CSS = 0.47µF, CREG = 0.01µF, C1 = 0.1µF, C2 = 1µF, RLOAD = 8Ω, SHDN = high, MONO = low, MUTE = high, G1 = low, G2 = high, FS1 = FS2 = high (SSM), SYNCIN = low. All load resistors (RL) are between OUT_+ and OUT_-, TA = +25°C, unless otherwise stated.) Typical Operating Characteristics (continued) (PVDD = VDD = +20V, PGND = GND = 0V, CSS = 0.47µF, CREG = 0.01µF, C1 = 0.1µF, C2 = 1µF, RLOAD = 8Ω, SHDN = high, MONO = low, MUTE = high, G1 = low, G2 = high, FS1 = FS2 = high (SSM), SYNCIN = low. All load resistors (RL) are between OUT_+ and OUT_-, TA = +25°C, unless otherwise stated.) 0.1 0.1 10kHz RBW 20 OUTPUT AMPLITUDE (dBV) RLOAD = 4Ω POUT = 22W THD+N (%) THD+N (%) 1 30 MAX9709 toc10 PVDD = 12V, MONO MODE, fIN = 1kHz RL = 4Ω 10 1 MAX9709 toc09 100 WIDEBAND OUTPUT SPECTRUM (SSM MODE) TOTAL HARMONIC DISTORTION PLUS NOISE vs. FREQUENCY (MONO MODE) 10 MAX9709 toc11 TOTAL HARMONIC DISTORTION PLUS NOISE vs. OUTPUT POWER 0 -10 -20 -30 -40 -50 -60 0.01 -70 0.01 5 10 15 20 25 10 100 1k 10k 100k 100k 1M 100M 10M OUTPUT POWER (W) FREQUENCY (Hz) FREQUENCY (Hz) WIDEBAND OUTPUT SPECTRUM (FFM MODE) OUTPUT FREQUENCY SPECTRUM (SSM MODE) OUTPUT FREQUENCY SPECTRUM (FFM MODE) 0 -10 -20 -30 -40 -50 0 -40 -60 -80 -100 MAX9709 toc14 -20 OUTPUT AMPLITUDE (dBV) 10 0 -20 OUTPUT AMPLITUDE (dBV) 10kHz RBW 20 MAX9709 toc13 30 MAX9709 toc12 0 OUTPUT AMPLITUDE (dBV) MAX9709 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier -40 -60 -80 -100 -60 -70 -120 100k 1M 10M FREQUENCY (Hz) 6 100M -120 0 4 8 12 16 FREQUENCY (kHz) 20 24 0 4 8 12 16 FREQUENCY (kHz) _______________________________________________________________________________________ 20 24 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier OUTPUT POWER vs. SUPPLY VOLTAGE (MONO MODE) 70 60 50 40 30 20 50 THD+N = 10% 40 30 THD+N = 1% 20 THD+N = 10% fIN = 1kHz 50 OUTPUT POWER (W) OUTPUT POWER (W) EFFICIENCY (%) 80 RLOAD = 4Ω fIN = 1kHz 60 60 MAX9709 toc16 RLOAD = 4Ω 90 70 MAX9709 toc15 100 OUTPUT POWER vs. LOAD RESISTANCE (MONO MODE) MAX9709 toc17 EFFICIENCY vs. OUTPUT POWER (MONO MODE) MAX9709 Typical Operating Characteristics (continued) (PVDD = VDD = +20V, PGND = GND = 0V, CSS = 0.47µF, CREG = 0.01µF, C1 = 0.1µF, C2 = 1µF, RLOAD = 8Ω, SHDN = high, MONO = low, MUTE = high, G1 = low, G2 = high, FS1 = FS2 = high (SSM), SYNCIN = low. All load resistors (RL) are between OUT_+ and OUT_-, TA = +25°C, unless otherwise stated.) 40 30 20 10 10 10 0 0 0 10 20 30 40 50 0 10 12 14 16 18 20 OUTPUT POWER (W) SUPPLY VOLTAGE (V) OUTPUT POWER vs. LOAD RESISTANCE (STEREO MODE) MUTE RESPONSE 22 24 4 6 8 MAX9709 toc18 THD+N = 10% fIN = 1kHz 25 12 10 LOAD RESISTANCE (Ω) SHUTDOWN RESPONSE MAX9709 toc19 30 OUTPUT POWER PER CHANNEL (W) 60 MAX9709 toc20 MUTE 5V/div SHDN 5V/div OUTPUT 50mV/div OUTPUT 50mV/div 20 15 10 5 0 7 8 9 10 11 12 13 14 15 16 40ms/div 40ms/div LOAD RESISTANCE (Ω) _______________________________________________________________________________________ 7 Typical Operating Characteristics (continued) (PVDD = VDD = +20V, PGND = GND = 0V, CSS = 0.47µF, CREG = 0.01µF, C1 = 0.1µF, C2 = 1µF, RLOAD = 8Ω, SHDN = high, MONO = low, MUTE = high, G1 = low, G2 = high, FS1 = FS2 = high (SSM), SYNCIN = low. All load resistors (RL) are between OUT_+ and OUT_-, TA = +25°C, unless otherwise stated.) COMMON-MODE REJECTION RATIO vs. FREQUENCY POWER-SUPPLY REJECTION RATIO vs. FREQUENCY -40 -50 -60 PSRR (dB) -80 -85 -90 CROSSTALK (dB) -50 -75 -60 -70 -80 -95 -105 -110 100 1k 100k 10k -110 -110 -120 10 100 1k 10 100k 10k 100 30 70 60 OUTPUT POWER (W) 25 20 15 10 fIN = 1kHz TH0 = TH1 = 1 TH2 = 0 100k 50 40 30 20 RLOAD = 4Ω fIN = 1kHz TH0 = TH1 = 1 TH2 = 0 10 0 10k MAXIMUM STEADY-STATE OUTPUT POWER vs. TEMPERATURE (MONO MODE)* MAX9709 toc24 35 1k FREQUENCY (Hz) FREQUENCY (Hz) MAXIMUM STEADY-STATE OUTPUT POWER vs. TEMPERATURE (STEREO MODE) OUTPUT POWER PER CHANNEL (W) -90 -100 FREQUENCY (Hz) 5 -80 MAX9709 toc25 10 -70 -100 -90 -100 MAX9709 toc23 -70 CROSSTALK vs. FREQUENCY -40 MAX9709 toc22 INPUT REFERRED -65 -30 MAX9709 toc21 -60 CMRR (dB) MAX9709 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier 0 30 40 50 60 70 30 AMBIENT TEMPERATURE (°C) 40 50 60 70 AMBIENT TEMPERATURE (°C) *MEASURED WITH THE MAX9709EVKIT, JUNCTION TEMPERATURE MAINTAINED AT +110°C. Pin Description PIN TQFP 1, 8, 13, 16, 17, 32, 33, 41, 48, 49, 50, 55, 58, 63, 64 TQFN NAME FUNCTION 1, 12, 42, 43, 44, 55, 56 N.C. 2, 3, 4, 45, 46, 47, 56, 57 2, 3, 4, 39, 40, 41, 49, 50 PGND Power Ground 5, 6, 7, 42, 43, 44 5, 6, 7, 36, 37, 38 PVDD Positive Power Supply. Bypass to PGND with a 0.1µF and a 47µF capacitor with the smallest capacitor placed as close to pins as possible. 8 No Connection. Not internally connected. _______________________________________________________________________________________ 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier PIN NAME FUNCTION TQFP TQFN 9 8 C1N Charge-Pump Flying Capacitor C1, Negative Terminal 10 9 C1P Charge-Pump Flying Capacitor C1, Positive Terminal 11 10 CPVDD 12 11 14 13 SYNCIN 15 14 FS2 Frequency Select 2 18 15 FS1 Frequency Select 1 19 16 INL- Left-Channel Negative Input (Stereo Mode Only) 20 17 INL+ Left-Channel Positive Input (Stereo Mode Only) 21 18 MONO 22, 23, 24 19, 20, 21 REG Internal Regulator Output Voltage (6V). Bypass with a 0.01µF capacitor to GND. 25, 26 22, 23 GND Analog Ground 27 24 SS 28 25 VDD Analog Power Supply. Bypass to GND with a 0.1µF capacitor as close to pin as possible. 29 26 INR- Right-Channel Negative Input. In mono mode, INR- is the negative input. 30 27 INR+ 31 28 G1 Gain Select input 1 34 29 G2 Gain Select input 2 35 30 SHDN Active-Low Shutdown Input. Drive SHDN high for normal operation. Drive SHDN low to place the device in shutdown mode. 36 31 MUTE Active-Low Mute Input. Drive logic low to place the device in mute. In mute mode, Class D output stage is no longer switching. Drive high for normal operation. MUTE is internally pulled up to VREG with a100kΩ resistor. 37 32 TEMP Thermal Flag Output, Open Drain. Pullup with a 10kΩ resistor to REG. 38 33 TH2 Temperature Flag Threshold Select Input 2 39 34 TH1 Temperature Flag Threshold Select Input 1 40 35 TH0 Temperature Flag Threshold Select Input 0 51, 52 45, 46 OUTR- 53, 54 47, 48 OUTR+ Right-Channel Positive Output 59, 60 51, 52 OUTL- Left-Channel Negative Output 61, 62 53, 54 OUTL+ Left-Channel Positive Output EP EP GND Charge-Pump Power Supply. Bypass to PVDD with a 1µF capacitor as close to pin as possible. SYNCOUT Open-Drain Slew-Rate-Limited Clock Output. Pullup with a 10kΩ to resistor to REG. Clock Synchronization Input. Allows for synchronization of the internal oscillator with an external clock. Mono/Stereo Mode Input. Drive logic high for mono mode. Drive logic low for stereo mode. Soft-Start. Connect a 0.47µF capacitor to GND to utilize soft-start power-up sequence. Right-Channel Positive Input. In mono mode, INR+ is the positive input. Right-Channel Negative Output Exposed Paddle. Connect to GND with multiple vias for best heat dissipation. _______________________________________________________________________________________ 9 MAX9709 Pin Description (continued) 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier MAX9709 Typical Application Circuits/Functional Diagrams VDD PVDD 0.1µF 47µF* 22, 23 (25, 26) VDIGITAL 25 (28) GND 5–7, 36–38 (5–7, 42–44) VDD PVDD VDIGITAL 2–4, 39–41, 49–50 (2–4, 45–47, 56–57) PGND 10kΩ 15 (18) FS1 14 (15) FS2 13 (14) SYNCOUT CONTROL SYNCIN RF 1µF + LEFT CHANNEL 1µF - 11 (12) 17 (20) INL+ 16 (19) INL- MAX9709 PVDD VBIAS RIN CLASS D MODULATOR AND H-BRIDGE RIN OUTL+ 53, 54 (61, 62) OUTL- 51, 52 (59, 60) OUTR+ 47, 48 (53, 54) OUTR- 45, 46 (51, 52) RF RF PVDD 1µF + RIGHT CHANNEL 1µF - 27 (30) INR+ RIN MUX 26 (29) INR- RIN CLASS D MODULATOR AND H-BRIDGE VBIAS VDIGITAL 30 (35) 31 (36) CPVDD SHDN RF MUTE 28 (31) G2 CHARGE PUMP GAIN CONTROL 29 (34) G1 18 (21) MONO REGULATOR TH0 35 (40) 34 (39) TH1 TH2 33 (38) VDIGITAL 9 (10) C1N 8 (9) REG 19, 20, 21 (22, 23, 24) C1 0.1µF CREG 0.01µF 32 (37) 10kΩ SS 24 (27) PVDD C1P TEMP THERMAL SENSOR 10 (11) C2 1µF CSS 0.47µF VDIGITAL CONFIGURATION: TQFN STEREO MODE, SSM, INTERNAL OSCILLATOR, GAIN = 22dB, THERMAL SETTING = +120°C ( ) TQFP PACKAGE *ADDITIONAL BULK CAPACITANCE Figure 1. Typical Application and Functional Diagram in Stereo Mode 10 ______________________________________________________________________________________ 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier VDD PVDD 47µF* 0.1µF 0.1µF 22, 23 (25, 26) VDIGITAL 25 (28) GND 15 (18) FS1 14 (15) FS2 5–7, 36–38 (5–7, 42–44) VDD PVDD 2–4, 39–41, 49–50 (2–4, 45–47, 56–57) VDIGITAL PGND 10kΩ SYNCOUT 11 (12) CONTROL 13 (14) SYNCIN RF 1µF + AUDIO INPUT 1µF - 17 (20) INR+ 16 (19) INR- MAX9709 PVDD VBIAS RIN CLASS D MODULATOR AND H-BRIDGE RIN OUTL+ 53, 54 (61, 62) OUTL- 51, 52 (59, 60) OUTR+ 47, 48 (53, 54) OUTR- 45, 46 (51, 52) CPVDD 10 (11) PVDD RF MUX VDIGITAL 30 (35) SHDN 31 (36) MUTE 28 (31) G1 CHARGE PUMP GAIN CONTROL 29 (34) G2 VDIGITAL CLASS D MODULATOR AND H-BRIDGE 18 (21) MONO REGULATOR TH0 35 (40) 34 (39) TH1 TH2 33 (38) 9 (10) C1N 8 (9) REG 19, 20, 21 (22, 23, 24) C1 0.1µF CREG 0.01µF 32 (37) 10kΩ SS 24 (27) PVDD C1P TEMP THERMAL SENSOR C2 1µF CSS 0.47µF VDIGITAL VDIGITAL CONFIGURATION: TQFN MONO MODE, SSM, INTERNAL OSCILLATOR, GAIN = 22dB, THERMAL SETTING = +120°C ( ) TQFP PACKAGE *ADDITIONAL BULK CAPACITANCE Figure 2. Typical Application and Functional Diagram in Mono Mode ______________________________________________________________________________________ 11 MAX9709 Typical Application Circuits/Functional Diagrams (continued) MAX9709 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier Detailed Description The MAX9709 filterless, Class D audio power amplifier features several improvements to switch mode amplifier technology. The MAX9709 is a two-channel, stereo amplifier with 25W output power on each channel. The amplifier can be configured to output 50W output power in mono mode. The device offers Class AB performance with Class D efficiency, while occupying minimal board space. A unique filterless modulation scheme and spread-spectrum switching mode create a compact, flexible, low-noise, efficient audio power amplifier. The differential input architecture reduces common-mode noise pickup, and can be used without input-coupling capacitors. The device can also be configured as a single-ended input amplifier. Mono/Stereo Configuration The MAX9709 features a mono mode that allows the right and left channels to operate in parallel, achieving up to 50W of output power. The mono mode is enabled by applying logic high to MONO. In this mode, audio signal applied to the right channel (INR+/INR-) is routed to the H-bridge of both channels, while signal applied to the left channel (INL+/INL-) is ignored. OUTL+ must be connected to OUTR+ and OUTL- must be connected to OUTR- using heavy PC board traces as close to the device as possible (see Figure 2). When the device is placed in mono mode on a PC board with outputs wired together, ensure that the MONO pin can never be driven low when the device is enabled. Driving the MONO pin low (stereo mode) while the outputs are wired together in mono mode may trigger the short-circuit or thermal protection or both, and may even damage the device. Efficiency Efficiency of a Class D amplifier is attributed to the region of operation of the output stage transistors. In a Class D amplifier, the output transistors act as currentsteering switches and consume negligible additional power. Any power loss associated with the Class D output stage is mostly due to the I2R loss of the MOSFET on-resistance and quiescent current overhead. The theoretical best efficiency of a linear amplifier is 78%; however, that efficiency is only exhibited at peak output 12 powers. Under normal operating levels (typical music reproduction levels), efficiency falls below 30%, whereas the MAX9709 still exhibits 87% efficiency under the same conditions. Shutdown The MAX9709 features a shutdown mode that reduces power consumption and extends battery life. Driving SHDN low places the device in low-power (0.1µA) shutdown mode. Connect SHDN to digital high for normal operation. Mute Function The MAX9709 features a clickless/popless mute mode. When the device is muted, the outputs stop switching, muting the speaker. Mute only affects the output stage and does not shut down the device. To mute the MAX9709, drive MUTE to logic low. Driving MUTE low during the power-up/down or shutdown/turn-on cycle optimizes click-and-pop suppression. Click-and-Pop Suppression The MAX9709 features comprehensive click-and-pop suppression that eliminates audible transients on startup and shutdown. While in shutdown, the H-bridge is pulled to GND through a 330kΩ resistor. During startup or power-up, the input amplifiers are muted and an internal loop sets the modulator bias voltages to the correct levels, preventing clicks and pops when the Hbridge is subsequently enabled. Following startup, a soft-start function gradually unmutes the input amplifiers. The value of the soft-start capacitor has an impact on the click-and-pop levels, as well as startup time. Thermal Sensor The MAX9709 features an on-chip temperature sensor that monitors the die temperature. When the junction temperature exceeds a programmed level, TEMP is pulled low. This flags the user to reduce power or shut down the device. TEMP may be connected to SS or MUTE for automatic shutdown during overheating. If TEMP is connected to MUTE, during thermal protection mode, the audio is muted and the device is in mute mode. If TEMP is connected to SS, during thermal protection mode, the device is shut down but the thermal sensor is still active. ______________________________________________________________________________________ 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier If TH2 = TH1 = TH0 = HIGH, it is likely that the MAX9709 enters thermal shutdown without tripping the thermal flag. Gain Selection The MAX9709 features four pin-selectable gain settings; see Table 2. VDIGITAL 10kΩ 10kΩ TO DIGITAL INPUT TEMP 0.1µF Figure 3. An RC Filter Eliminates Transient During Switching Table 1. MAX9709 Junction Temperature Threshold Setting JUNCTION TEMPERATURE (°C) TH2 TH1 80 Low Low Low 90 Low Low High 100 Low High Low 110 Low High High 120 High Low Low 129 High Low High 139 High High Low 158 High High High TH0 Operating Modes Fixed-Frequency Modulation (FFM) Mode The MAX9709 features three switching frequencies in the FFM mode (Table 3). In this mode, the frequency spectrum of the Class D output consists of the fundamental switching frequency and its associated harmonics (see the Wideband Output Spectrum graph in the Typical Operating Characteristics). Select one of the three fixed switching frequencies such that the harmonics do not fall in a sensitive band. The switching frequency can be changed any time without affecting audio reproduction. Spread-Spectrum Modulation (SSM) Mode The MAX9709 features a unique, patented spreadspectrum (SSM) mode that flattens the wideband spectral components, improving EMI emissions that may be radiated by the speaker and cables. This mode is enabled by setting FS1 = FS2 = high. In SSM mode, the switching frequency varies randomly by ±4% around the center frequency (200kHz). The modulation scheme remains the same, but the period of the triangle waveform changes from cycle to cycle. Instead of a large amount of spectral energy present at multiples of the switching frequency, the energy is now spread over a bandwidth that increases with frequency. Above a few megahertz, the wideband spectrum looks like white noise for EMI purposes. SSM mode reduces EMI compared to fixed-frequency mode. This can also help to randomize visual artifacts caused by radiated or supply borne interference in displays. Synchronous Switching Mode The MAX9709 SYNCIN input allows the Class D amplifier to switch at a frequency defined by an external clock frequency. Synchronizing the amplifier with an external clock source may confine the switching frequency to a less sensitive band. The external clock frequency range is from 600kHz to 1.2MHz and can have any duty cycle, but the minimum pulse must be greater than 100ns. SYNCOUT is an open-drain clock output for synchronizing external circuitry. Its frequency is four times the amplifier’s switching frequency and it is active in either internal or external oscillator mode. Table 3. Switching Frequencies Table 2. MAX9709 Gain Setting FS1 FS2 SYNCOUT FREQUENCY (kHz) MODULATION 22 0 0 200 Fixed-frequency High 25 0 1 250 Fixed-frequency Low 29.5 1 0 160 Fixed-frequency Low 36 1 1 200 ±4 Spread-spectrum G1 G2 GAIN (dB) Low High High High Low ______________________________________________________________________________________ 13 MAX9709 TEMP returns high once the junction temperature cools below the set threshold minus the thermal hysteresis. If TEMP is connected to either MUTE or SS, the audio output resumes. The temperature threshold is set by the TH0, TH1, and TH2 inputs as shown in Table 1. An RC filter may be used to eliminate any transient at the TEMP output as shown in Figure 3. MAX9709 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier Linear Regulator (REG) The supply voltage range for the MAX9709 is from 10V to 22V to achieve high-output power. An internal linear regulator reduces this voltage to 6.3V for use with small-signal and digital circuitry that does not require high-voltage supply. Bypass a 0.01µF capacitor from REG to GND. 1µF INR+ MAX9709 Applications Information INR- Logic Inputs All of the digital logic inputs and output have an absolute maximum rating of +12V. If the MAX9709 is operating with a supply voltage between 10V and 12V, digital inputs can be connected to PV DD or V DD. If PVDD and VDD are greater than 12V, digital inputs and outputs must be connected to a digital system supply lower than 12V. Input Amplifier Differential Input The MAX9709 features a differential input structure, making them compatible with many CODECs, and offering improved noise immunity over a single-ended input amplifier. In devices such as flat-panel displays, noisy digital signals can be picked up by the amplifier’s inputs. These signals appear at the amplifiers’ inputs as common-mode noise. A differential input amplifier amplifies only the difference of the two inputs, while any signal common to both inputs is attenuated. Single-Ended Input The MAX9709 can be configured as a single-ended input amplifier by capacitively coupling either input to GND and driving the other input (Figure 4). Component Selection Input Filter An input capacitor, CIN, in conjunction with the input impedance of the MAX9709, forms a highpass filter that removes the DC bias from an incoming signal. The ACcoupling capacitor allows the amplifier to bias the signal to an optimum DC level. Assuming zero-source impedance, the -3dB point of the highpass filter is given by: f−3dB = 14 1 2πRINCIN 1µF Figure 4. Single-Ended Input Connections Choose CIN so that f-3dB is well below the lowest frequency of interest. Setting f-3dB too high affects the low-frequency response of the amplifier. Use capacitors with dielectrics that have low-voltage coefficients, such as tantalum or aluminum electrolytic. Capacitors with high-voltage coefficients, such as ceramics, may result in increased distortion at low frequencies. Output Filter The MAX9709 does not require an output filter. However, output filtering can be used if a design is failing radiated emissions due to board layout or cable length, or the circuit is near EMI-sensitive devices. See the MAX9709 evaluation kit for suggested filter topologies. The tuning and component selection of the filter should be optimized for the load. A purely resistive load (8Ω) used for lab testing requires different components than a real, complex load-speaker load. Charge-Pump Capacitor Selection The MAX9709 has an internal charge-pump converter that produces a voltage level for internal circuitry. It requires a flying capacitor (C1) and a holding capacitor (C2). Use capacitors with an ESR less than 100mΩ for optimum performance. Low-ESR ceramic capacitors minimize the output resistance of the charge pump. For best performance over the extended temperature range, select capacitors with an X7R dielectric. The capacitors’ voltage rating must be greater than 36V. ______________________________________________________________________________________ 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier Frequency Synchronization The MAX9709 outputs up to 27W on each channel in stereo mode. If higher output power or a 2.1 solution is needed, two MAX9709s can be used. Each MAX9709 is synchronized by connecting SYNCOUT from the first MAX9709 to SYNCIN of the second MAX9709 (see Figure 5). Supply Bypassing/Layout Proper power-supply bypassing ensures low distortion operation. For optimum performance, bypass PVDD to PGND with a 0.1µF capacitor as close to each PVDD pin as possible. A low-impedance, high-current powersupply connection to PVDD is assumed. Additional bulk capacitance should be added, as required, depending on the application and power-supply characteristics. GND and PGND should be star-connected to system ground. For the TQFN package, solder the exposed paddle (EP) to the ground plane using multiple-plated through-hole vias. The exposed paddle must be soldered to the ground plane for rated power dissipation and good ground return. Use wider PC board traces to lower the parasitic resistance for the high-power output pins (OUTR+, OUTR-, OUTL+, OUTL-). Refer to the MAX9709 evaluation kit for layout guidance. Thermal Considerations Class D amplifiers provide much better efficiency and thermal performance than a comparable Class AB amplifier. However, the system’s thermal performance must be considered with realistic expectations along with its many parameters. Continuous Sine Wave vs. Music When a Class D amplifier is evaluated in the lab, often a continuous sine wave is used as the signal source. While this is convenient for measurement purposes, it represents a worst-case scenario for thermal loading on the amplifier. It is not uncommon for a Class D amplifier to enter thermal shutdown if driven near maximum output power with a continuous sine wave. The PC board must be optimized for best dissipation (see the PC Board Thermal Considerations section). Audio content, both music and voice, has a much lower RMS value relative to its peak output power. Therefore, while an audio signal may reach similar peaks as a continuous sine wave, the actual thermal impact on the Class D amplifier is highly reduced. If the thermal performance of a system is being evaluated, it is important to use actual audio signals instead of sine waves for testing. If sine waves must be used, the thermal performance is less than the system’s actual capability for real music or voice. PC Board Thermal Considerations The exposed pad is the primary route for conducting heat away from the IC. With a bottom-side exposed pad, the PC board and its copper becomes the primary heatsink for the Class D amplifier. Solder the exposed pad to a copper polygon. Add as much copper as possible from this polygon to any adjacent pin on the Class D amplifier as well as to any adjacent components, provided these connections are at the same potential. These copper paths must be as wide as possible. Each of these paths contributes to the overall thermal capabilities of the system. The copper polygon to which the exposed pad is attached should have multiple vias to the opposite side of the PC board, where they connect to another copper polygon. Make this polygon as large as possible within the system’s constraints for signal routing. Additional improvements are possible if all the traces from the device are made as wide as possible. Although the IC pins are not the primary thermal path out of the package, they do provide a small amount. The total improvement would not exceed about 10%, but it could make the difference between acceptable performance and thermal problems. ______________________________________________________________________________________ 15 MAX9709 Sharing Input Sources In certain systems, a single audio source can be shared by multiple devices (speaker and headphone amplifiers). When sharing inputs, it is common to mute the unused device, rather than completely shutting it down. This prevents the unused device inputs from distorting the input signal. Mute the MAX9709 by driving MUTE low. Driving MUTE low turns off the Class D output stage, but does not affect the input bias levels of the MAX9709. MAX9709 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier Auxiliary Heatsinking If operating in higher ambient temperatures, it is possible to improve the thermal performance of a PC board with the addition of an external heatsink. The thermal resistance to this heatsink must be kept as low as possible to maximize its performance. With a bottom-side exposed pad, the lowest resistance thermal path is on the bottom of the PC board. The topside of the IC is not a significant thermal path for the device, and therefore is not a costeffective location for a heatsink. If an LC filter is used in the design, placing the inductor in close proximity to the IC can help draw heat away from the MAX9709. Thermal Calculations The die temperature of a Class D amplifier can be estimated with some basic calculations. For example, the die temperature is calculated for the below conditions: • TA = +40°C • POUT = 16W • Efficiency (η) = 87% • θJA = 21°C/W First, the Class D amplifier’s power dissipation must be calculated: PDISS = 16W POUT − POUT = − 16W = 2.4W η 0.87 Then the power dissipation is used to calculate the die temperature, TC, as follows: TC = TA + PDISS × θJA = 40°C + 24W × 21°C / W = 90.4°C Load Impedance The on-resistance of the MOSFET output stage in Class D amplifiers affects both the efficiency and the peak-current capability. Reducing the peak current into the load reduces the I2R losses in the MOSFETs, which increases efficiency. To keep the peak currents lower, choose the highest impedance speaker which can still deliver the desired output power within the voltage swing limits of the Class D amplifier and its supply voltage. 16 Another consideration is the load impedance across the audio frequency band. A loudspeaker is a complex electromechanical system with a variety of resonance. In other words, an 8Ω speaker usually has 8Ω impedance within a very narrow range. This often extends well below 8Ω, reducing the thermal efficiency below what is expected. This lower-than-expected impedance can be further reduced when a crossover network is used in a multidriver audio system. Systems Application Circuit The MAX9709 can be configured into multiple amplifier systems. One concept is a 2.1 audio system (Figure 5) where a stereo audio source is split into three channels. The left- and right-channel inputs are highpass filtered to remove the bass content, and then amplified by the MAX9709 in stereo mode. Also, the left- and right-channel inputs are summed together and lowpass filtered to remove the high-frequency content, then amplified by a second MAX9709 in mono mode. The conceptual drawing of Figure 5 can be applied to either single-ended or differential systems. Figure 6 illustrates the circuitry required to implement a fully differential filtering system. By maintaining a fully differential path, the signal-to-noise ratio remains uncompromised and noise pickup is kept very low. However, keeping a fully differential signal path results in almost twice the component count, and therefore performance must be weighed against cost and size. The highpass and lowpass filters should have different cutoff frequencies to ensure an equal power response at the crossover frequency. The filters should be at -6dB amplitude at the crossover frequency, which is known as a Linkwitz-Riley alignment. In the example circuit of Figure 6, the -3dB cutoff frequency for the highpass filters is 250Hz, and the -3dB cutoff frequency for the lowpass filter is 160Hz. Both the highpass filters and the lowpass filters are at a -6dB amplitude at approximately 200Hz. If the filters were to have the same -3dB cutoff frequency, a measurement of sound pressure level (SPL) vs. frequency would have a peak at the crossover frequency. ______________________________________________________________________________________ 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier INR+ INR- HIGHPASS FILTER RIGHT AUDIO The circuit in Figure 6 drives a pair of MAX9709 devices similar to the circuit in Figure 5. The inputs to the MAX9709 still require AC-coupling to prevent compromising the click-and-pop performance of the MAX9709. The left and right drivers should be at an 8Ω to 12Ω impedance, whereas the subwoofer can be 4Ω to 8Ω depending on the desired output power, the available power-supply voltage, and the sensitivity of the individual speakers in the system. The four gain settings of the MAX9709 allow gain adjustments to match the sensitivity of the speakers. OUTR+ OUTR- 8Ω FULLRANGE SPEAKER OUTL+ OUTL- 8Ω FULLRANGE SPEAKER OUTR+ OUTR- 4Ω OR 8Ω WOOFER MONO MAX9709 INL+ HIGHPASS FILTER LEFT AUDIO INLSYNCOUT Σ SYNCIN INR+ INR- LOWPASS FILTER MAX9709 VDIGITAL MONO INL+ INL- OUTL+ OUTL- Figure 5. Multiple Amplifiers Implement a 2.1 Audio System ______________________________________________________________________________________ 17 MAX9709 The circuit in Figure 6 uses inverting amplifiers for their ease in biasing. Note the phase labeling at the outputs has been reversed. The resistors should be 1% or better in tolerance and the capacitors 5% tolerance or better. Mismatch in the components can cause discrepancies between the nominal transfer function and actual performance. Also, the mismatch of the input resistors (R15, R17, R19, and R21 in Figure 6) of the summing amplifier and lowpass filter causes some high-frequency sound to be sent to the subwoofer. MAX9709 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier R1 56.2kΩ R2, 56.2kΩ R3 28kΩ C1 47nF C2 47nF 2 U1A R4 28kΩ RIGHT AUDIO INPUT 1 MAX4478 R5 56.2kΩ BIAS 3 RIGHT AUDIO OUTPUT R6, 56.2kΩ R7 28kΩ C3 47nF C4 47nF 6 U1B 7 MAX4478 R8 56.2kΩ BIAS 5 RIGHT AND LEFT OUTPUTS ARE AC-COUPLED TO A MAX9709 CONFIGURED AS A STEREO AMPLIFIER R9, 56.2kΩ R10 28kΩ C5 47nF C6 47nF 9 U1C R11 28kΩ LEFT AUDIO INPUT 8 MAX4478 R12 56.2kΩ BIAS 10 LEFT AUDIO OUTPUT R13, 56.2kΩ R14 28kΩ C7 47nF C8 47nF 13 U1D 14 MAX4478 R15 26.1kΩ R16 13kΩ BIAS 12 SUBWOOFER OUTPUT IS AC-COUPLED TO A MAX9709 CONFIGURED AS A MONO AMPLIFIER C9, 47nF R17 26.1kΩ R18 7.5kΩ 2 U2A R19 26.1kΩ C10 47nF 1 MAX4478 R20 13kΩ BIAS 3 SUBWOOFER AUDIO OUTPUT C11, 47nF R21 28kΩ R22 7.5kΩ 6 U2B 7 MAX4478 BIAS 5 NOTE: OP AMP POWER PINS OMITTED FOR CLARITY. ALL RESISTORS ARE 1% OR BETTER. ALL CAPACITORS ARE 5% OR BETTER. Figure 6. Fully Differential Crossover Filters 18 ______________________________________________________________________________________ 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier TH0 37 36 35 34 33 G2 PVDD 38 SHDN PVDD 39 TEMP PVDD 40 MUTE PGND 41 TH1 PGND 42 TH2 N.C. PGND TOP VIEW 32 31 30 29 N.C. 43 28 G1 N.C. 44 27 INR+ OUTR- 45 26 INR- OUTR- 46 25 VDD OUTR+ 47 24 SS OUTR+ 48 23 GND PGND 49 22 GND PGND 50 21 REG MAX9709 20 REG OUTL- 51 5 6 7 8 9 10 11 12 13 14 FS2 4 SYNCIN 3 N.C. 2 SYNCOUT 1 C1P 15 FS1 CPVDD N.C. 56 C1N INL- PVDD INL+ 16 PVDD 17 N.C. 55 PVDD OUTL+ 54 PGND MONO PGND 18 N.C. 19 REG OUTL+ 53 PGND OUTL- 52 THIN QFN ______________________________________________________________________________________ 19 MAX9709 Pin Configurations 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier MAX9709 Pin Configurations (continued) N.C. N.C. OUTR- OUTR+ OUTR- OUTR+ N.C. PGND 63 62 61 60 59 58 N.C. 64 PGND OUTL- OUTL- N.C. OUTL+ N.C. OUTL+ TOP VIEW 57 56 55 54 53 52 51 50 49 N.C. 1 48 N.C. PGND 2 47 PGND PGND 3 46 PGND PGND 4 45 PGND PVDD 5 44 PVDD PVDD 6 43 PVDD PVDD 7 42 PVDD N.C. 8 41 N.C. C1N 9 MAX9709 40 TH0 C1P 10 39 TH1 CPVDD 11 38 TH2 SYNCOUT 12 37 TEMP N.C. 13 36 MUTE SYNCIN 14 35 SHDN FS2 15 34 G2 N.C. 16 33 N.C. N.C. G1 INR+ INR- VDD SS GND GND REG REG REG INL+ MONO INL- FS1 N.C. 17 18 19 20 21 22 23 24 25 26 27 28 29 30 31 32 TQFP Chip Information PROCESS: BiCMOS 20 ______________________________________________________________________________________ 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier 56L THIN QFN.EPS PACKAGE OUTLINE 56L THIN QFN, 8x8x0.8mm 21-0135 E 1 2 ______________________________________________________________________________________ 21 MAX9709 Package Information (The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information go to www.maxim-ic.com/packages.) MAX9709 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier Package Information (continued) (The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information go to www.maxim-ic.com/packages.) PACKAGE OUTLINE 56L THIN QFN, 8x8x0.8mm 21-0135 22 ______________________________________________________________________________________ E 2 2 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier 64L TQFP.EPS PACKAGE OUTLINE, 64L TQFP, 10x10x1.4mm 21-0083 B 1 2 ______________________________________________________________________________________ 23 MAX9709 Package Information (continued) (The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information go to www.maxim-ic.com/packages.) MAX9709 25W/50W, Filterless, Spread-Spectrum, Stereo/Mono, Class D Amplifier Package Information (continued) (The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information go to www.maxim-ic.com/packages.) PACKAGE OUTLINE, 64L TQFP, 10x10x1.4mm 21-0083 B 2 2 Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are implied. Maxim reserves the right to change the circuitry and specifications without notice at any time. 24 ____________________Maxim Integrated Products, 120 San Gabriel Drive, Sunnyvale, CA 94086 408-737-7600 © 2005 Maxim Integrated Products Freed Quijano Printed USA is a registered trademark of Maxim Integrated Products, Inc.