LMH6657/LMH6658 270MHz Single Supply, Single & Dual Amplifiers General Description Features The LMH6657/6658 are low-cost operational amplifiers that operate from a single supply with input voltage range extending below the V−. Based on easy to use voltage feedback topology and boasting fast slew rate (700V/µs) and high speed (140MHz GBWP), the LMH6657 (Single) and LMH6658 (dual) can be used in high speed large signal applications. These applications include instrumentation, communication devices, set-top boxes, etc. With a -3dB BW of 100MHz (AV = +2) and DG & DP of 0.03% & 0.10˚ respectively, the LMH6657/6658 are well suited for video applications. The output stage can typically supply 80mA into the load with a swing of about 1V from either rail. For Industrial applications, the LMH6657/6658 are excellent cost-saving choices. Input referred voltage noise is low and the input voltage can extend below V− to ease amplification of low level signals that could be at or near the system ground. With low distortion and fast settling, LMH6657/6658 can provide buffering for A/D and D/A applications. The LMH6657/6658 versatility and ease of use is extended even further by offering these high slew rate , high speed Op Amps in miniature packages such as SOT23-5, SC70, SOIC-8, and MSOP-8. Refer to the Ordering Information section for packaging options available for each device. VS = 5V, TA = 25˚C, RL = 100Ω (Typical values unless specified) n −3dB BW (AV = +1) 270MHz n Supply voltage range 3V to 12V n Slew rate, (VS = ± 5V) 700V/µs n Supply current 6.2mA/amp n Output current +80/−90mA n Input common mode volt. 0.5V beyond V−, 1.7V from V+ n Output voltage swing (RL = 2kΩ) 0.8V from rails n Input voltage noise 11nV/ n Input current noise 2.1pA/ n DG error 0.03% n DP error 0.10˚ n THD (5MHz) −55dBc n Settling time (0.1%) 37ns n Fully characterized for 5V, and ± 5V n Output overdrive recovery 18ns n Output short circuit protected (Note 10) n No output phase reversal with CMVR exceeded Applications n n n n n CD/DVD ROM ADC buffer amp Portable video Current sense buffer Portable communications Connection Diagrams SOT23-5/SC70-5 (LMH6657) SOIC-8/MSOP-8 (LMH6658) 20053261 20053263 Top View © 2004 National Semiconductor Corporation DS200532 www.national.com LMH6657/LMH6658 270MHz Single Supply, Single & Dual Amplifiers October 2004 LMH6657/LMH6658 Absolute Maximum Ratings (Note 1) Wave Soldering (10 sec.) Storage Temperature Range If Military/Aerospace specified devices are required, please contact the National Semiconductor Sales Office/ Distributors for availability and specifications. Supply Voltage (V+ – V−) 200V (Note 9) Output Short Circuit Duration (Note 3), (Note 11) + − Supply Voltage (V - V ) Voltage at Input/Output pins SC70 12.6V V+ +0.8V, V− −0.8V Soldering Information Infrared or Convection (20 sec.) −40˚C to +85˚C Package Thermal Resistance (θJA)(Note 4) ± 10mA Input Current 3V to 12V Operating Temperature Range (Note 4) ± 2.5V VIN Differential +150˚C Operating Ratings (Note 1) 2KV(Note 2) Machine Model −65˚C to +150˚C Junction Temperature (Note 4) ESD Tolerance Human Body Model 260˚C 235˚C 478˚C/W SOT23–5 265˚C/W MSOP-8 235˚C/W SOIC-8 190˚C/W 5V Electrical Characteristics Unless otherwise specified, all limits guaranteed for at TJ = 25˚C, V+ = 5V, V− = 0V, VCM = VO = V+/2, and RL = 100Ω (or as specified) tied to V+/2. Boldface limits apply at the temperature extremes. Symbol Parameter Conditions GB Gain Bandwidth Product VOUT < 200mVPP SSBW −3dB BW AV = +1, VOUT = 200mVPP Min (Note 6) Typ (Note 5) 140 220 270 AV = +2 or −1, VOUT = 200mVPP 100 Max (Note 6) Units MHz MHz GFP Frequency Response Peaking AV = +2, VOUT = 200mVPP, DC to 100MHz 1.5 GFR Frequency Response Rolloff AV = +2, VOUT = 200mVPP, DC to 100MHz 0.5 LPD1˚ 1˚ Linear Phase Deviation AV = +2, VOUT = 200mVPP, ± 1˚ 30 MHz GF0.1dB 0.1dB Gain Flatness AV = +2, ± 0.1dB, VOUT = 200mVPP 13 MHz dB dB PBW Full Power Bandwidth −1dB, VOUT = 3VPP, AV = −1 55 MHz DG Differential Gain NTSC, VCM = 2V, RL = 150Ω to V+/2, Pos. Video Only 0.03 % DP Differential Phase NTSC, VCM = 2V, RL=150Ω to V+/2 Pos. Video Only 0.1 deg AV = +2, VOUT = 500mVPP 3.3 ns AV = −1, VOUT = 500mVPP 3.4 Time Domain Response tr Rise and Fall Time OS Overshoot, Undershoot AV = +2, VOUT = 500mVPP 18 % ts Settling Time VO = 2VPP, ± 0.1%, RL = 500Ω to V+/2, AV = −1 37 ns SR Slew Rate (Note 8) AV = −1, VO = 3VPP (Note 13) 470 AV = +2, VO = 3VPP (Note 13) 420 V/µs Distortion and Noise Response HD2 2nd Harmonic Distortion f = 5MHz, VO = 2VPP, AV = -1 −70 dBc HD3 3rd Harmonic Distortion f = 5MHz, VO = 2VPP, AV = -1 −57 dBc THD Total Harmonic Distortion f = 5MHz, VO = 2VPP, AV = -1 −55.5 dBc Vn Input-Referred Voltage Noise f = 100KHz 11 f = 1KHz 19 f = 100KHz 2.1 f = 1KHz 7.5 f = 5MHz, RL (SND) = 100Ω RCV: RF = RG = 1k 69 In XTLKA Input-Referred Current Noise Cross-Talk Rejection (LMH6658) Static, DC Performance www.national.com 2 nV/ pA/ dB (Continued) Unless otherwise specified, all limits guaranteed for at TJ = 25˚C, V+ = 5V, V− = 0V, VCM = VO = V+/2, and RL = 100Ω (or as specified) tied to V+/2. Boldface limits apply at the temperature extremes. Symbol AVOL CMVR Parameter Large Signal Voltage Gain Input Common-Mode Voltage Range Conditions Min (Note 6) Typ (Note 5) VO = 1.25V to 3.75V, RL = 2k to V+/2 85 95 VO = 1.5V to 3.5V, RL = 150Ω to V+/2 75 85 VO = 2V to 3V, RL = 50Ω to V+/2 70 80 −0.2 −0.1 −0.5 3.0 2.8 3.3 CMRR ≥ 50dB ± 1.1 VOS Input Offset Voltage TC VOS Input Offset Voltage Average Drift (Note 12) ±2 IB Input Bias Current (Note 7) −5 Input Bias Current Average Drift (Note 12) 0.01 TC IB IOS Input Offset Current 50 CMRR Common Mode Rejection Ratio VCM Stepped from 0V to 3.0V 72 82 +PSRR Positive Power Supply Rejection Ratio V+ = 4.5V to 5.5V, VCM = 1V 72 82 IS Supply Current (per channel) No load 6.2 Max (Note 6) Units dB V ±5 ±7 mV µV/C −20 −30 µA nA/˚C 300 500 nA dB dB 8.5 10 mA Miscellaneous Performance VOH VOL Output Swing High Output Swing Low RL = 2k to V+/2 4.10 3.8 4.25 RL = 150Ω to V+/2 4.00 3.70 4.19 RL = 75Ω to V+/2 3.85 3.50 4.15 RL = 2k to V+/2 900 1100 800 RL = 150Ω to V+/2 970 1200 870 = 75Ω to V+/2 990 1250 885 R L IOUT Output Current VOUT = 1V from either rail ± 40 +85, −105 ISC Output Short CircuitCurrent (Note 10) Sourcing to V+/2 100 80 155 Sinking to V+/2 100 80 220 RIN Common Mode Input Resistance 3 CIN Common Mode Input Capacitance 1.8 ROUT Output Impedance f = 1MHz, AV = +1 0.06 3 V mV mA mA MΩ pF Ω www.national.com LMH6657/LMH6658 5V Electrical Characteristics LMH6657/LMH6658 ± 5V Electrical Characteristics Unless otherwise specified, all limits guaranteed for at TJ = 25˚C, V+ = 5V, V− = −5V, VCM = VO, and RL = 100Ω (or as specified) tied to 0V. Boldface limits apply at the temperature extremes. Symbol Parameter Conditions GB Gain Bandwidth Product VOUT < 200mVPP SSBW −3dB BW AV = +1, VOUT = 200mVPP Min (Note 6) Typ (Note 5) 220 270 Max (Note 6) 140 AV = +2 or −1, VOUT = 200mVPP 100 Units MHz MHz GFP Frequency Response Peaking AV = +2, VOUT = 200mVPP, DC to 100MHz 1.0 GFR Frequency Response Rolloff AV = +2, VOUT = 200mVPP, DC to 100MHz 0.9 LPD1˚ 1˚ Linear Phase Deviation AV = +2, VOUT = 200mVPP, ± 1˚ 30 MHz 20 MHz 30 MHz dB dB GF0.1dB 0.1dB Gain Flatness AV = +2, ± 0.1dB, VOUT = 200mVPP PBW Full Power Bandwidth −1dB, VOUT = 8VPP, AV = −1 DG Differential Gain NTSC, RL = 150Ω, Pos. or Neg. Video 0.03 % DP Differential Phase NTSC,RL = 150Ω, Pos. or Neg. Video 0.1 deg AV = +2, VOUT = 500mVPP 3.3 AV = −1, VOUT = 500mVPP 3.3 Time Domain Response tr Rise and Fall Time ns OS Overshoot, Undershoot AV = +2, VOUT = 500mVPP 16 % ts Settling Time VO = 5VPP, ± 0.1%, RL =500Ω, AV = −1 35 ns SR Slew Rate (Note 8) AV = −1, VO = 8VPP 700 AV = +2, VO = 8VPP 500 V/µs Distortion and Noise Response HD2 2nd Harmonic Distortion f = 5MHz, VO = 2VPP, AV = -1 −70 dBc HD3 3rd Harmonic Distortion f = 5MHz, VO = 2VPP, AV = -1 −57 dBc THD Total Harmonic Distortion f = 5MHz, VO = 2VPP, AV = -1 −55.5 dBc Vn Input-Referred Voltage Noise f = 100KHz 11 f = 1KHz 19 f = 100KHz 2.1 f = 1KHz 7.5 f = 5MHz, RL (SND) = 100Ω RCV: RF = RG = 1k 69 In XTLKA Input-Referred Current Noise Cross-Talk Rejection (LMH6658) nV/ pA/ dB Static, DC Performance AVOL CMVR Large Signal Voltage Gain Input Common-Mode Voltage Range VO = −3.75V to 3.75V, RL = 2k 87 VO = −3.5V to 3.5V, RL = 150Ω 80 90 VO = −3V to 3V, RL = 50Ω 75 85 −5.2 −5.1 −5.5 3.0 2.8 3.3 CMRR ≥ 50dB 100 ± 1.0 VOS Input Offset Voltage TC VOS Input Offset Voltage Average Drift (Note 12) ±2 IB Input Bias Current (Note 7) −5 TCIB Input Bias Current Average Drift (Note 12) 0.01 www.national.com 4 dB V ±5 ±7 mV µV/C −20 −30 µA nA/˚C (Continued) Unless otherwise specified, all limits guaranteed for at TJ = 25˚C, V+ = 5V, V− = −5V, VCM = VO, and RL = 100Ω (or as specified) tied to 0V. Boldface limits apply at the temperature extremes. Symbol Parameter Conditions Min (Note 6) Typ (Note 5) Max (Note 6) 50 300 500 Units IOS Input Offset Current CMRR Common ModeRejection Ratio VCM Stepped from −5V to 3.0V 75 84 dB +PSRR Positive Power Supply Rejection Ratio V+ = 4.5V to 5.5V, VCM = −4V 75 82 dB −PSRR Negative Power Supply Rejection Ratio V− = −4.5V to −5.5V 78 85 dB IS Supply Current (per channel) No load 6.5 9.0 11 nA mA Miscellaneous Performance VOH VOL Output Swing High Output Swing Low RL = 2k 4.10 3.80 4.25 RL = 150Ω 4.00 3.70 4.20 RL = 75Ω 3.85 3.50 4.18 RL = 2k −4.05 −3.80 −4.19 RL = 150Ω −3.90 −3.65 −4.05 = 75Ω −3.80 −3.50 −4.00 R L IOUT Output Current VOUT = 1V from either rail ± 45 +100, −110 ISC Output Short Circuit Current (Note 10) Sourcing to Ground 120 100 180 Sinking to Ground 120 100 230 RIN Common Mode Input Resistance 4 CIN Common Mode Input Capacitance 1.8 ROUT Output Impedance f = 1MHz, AV = +1 0.06 5 V V mA mA MΩ pF Ω www.national.com LMH6657/LMH6658 ± 5V Electrical Characteristics LMH6657/LMH6658 Note 1: Note 1: Absolute maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is intended to be functional, but specific performance is not guaranteed. For guaranteed specifications and the test conditions, see the Electrical Characteristics. Note 2: Human body model, 1.5kΩ in series with 100pF. Note 3: Applies to both single-supply and split-supply operation. Continuous short circuit operation at elevated ambient temperature can result in exceeding the maximum allowed junction temperature of 150˚C. Note 4: The maximum power dissipation is a function of TJ(MAX), θJA, and TA. The maximum allowable power dissipation at any ambient temperature is PD = (TJ(MAX) - TA)/ θJA . All numbers apply for packages soldered directly onto a PC board. Note 5: Typical values represent the most likely parametric norm. Note 6: All limits are guaranteed by testing or statistical analysis. Note 7: Positive current corresponds to current flowing into the device. Note 8: Slew rate is the "worst case" of the rising and falling slew rates. Note 9: Machine Model, 0Ω in series with 200pF. Note 10: Short circuit test is a momentary test. See Note 11. Note 11: Output short circuit duration is infinite for VS < 6V at room temperature and below. For VS > 6V, allowable short circuit duration is 1.5ms. Note 12: Drift determined by dividing the change in parameter at temperature extremes by the total temperature change. Note 13: Output Swing not limited by Slew Rate limit. Ordering Information Package Part Number Package Marking Transport Media NSC Drawing SOT23-5 LMH6657MF A85A 1k Units Tape and Reel MF05A LMH6657MFX SC70-5 LMH6657MG 3k Units Tape and Reel A76 1k Units Tape and Reel LMH6657MGX SOIC-8 LMH6658MA LMH6658MA LMH6658MAX MSOP-8 LMH6658MM Rails M08A 2.5k Units Tape and Reel A88A 1k Units Tape and Reel LMH6658MMX www.national.com MAA05A 3k Units Tape and Reel 3.5k Units Tape and Reel 6 MUA08A LMH6657/LMH6658 Typical Performance Characteristics Non-Inverting Frequency Response, Gain Inverting Frequency Response, Gain 20053226 20053224 Non-Inverting Frequency Response, Phase Inverting Frequency Response, Phase 20053227 20053225 Open Loop Gain/Phase vs. Frequency Unity Gain Frequency vs. VCM 20053223 20053241 7 www.national.com LMH6657/LMH6658 Typical Performance Characteristics (Continued) Phase Margin vs. VCM Output vs. Input 20053204 20053242 Output vs. Input CMRR vs. Frequency 20053206 20053203 PSRR vs. Frequency DG/DP vs. IRE 20053201 www.national.com 20053211 8 LMH6657/LMH6658 Typical Performance Characteristics (Continued) Noise vs. Frequency Crosstalk Rejection vs. Frequency 20053205 20053202 Output Impedance vs. Frequency HD vs. VOUT 20053210 20053213 HD vs. VOUT THD vs. VOUT 20053212 20053253 9 www.national.com LMH6657/LMH6658 Typical Performance Characteristics (Continued) HD vs. Frequency HD vs. Frequency 20053214 20053215 VOUT vs. ISOURCE VOUT vs. ISINK 20053243 20053244 VOUT vs. ISOURCE VOUT vs. ISINK 20053245 www.national.com 20053246 10 LMH6657/LMH6658 Typical Performance Characteristics (Continued) Short Circuit Current Short Circuit Current 20053230 20053231 Settling Time vs. Output Step Amplitude Settling Time vs. Output Step Amplitude 20053207 20053208 ∆VOS vs. VOUT 0.1% Settling Time vs. Cap Load 20053209 20053240 11 www.national.com LMH6657/LMH6658 Typical Performance Characteristics (Continued) ∆VOS vs. VOUT IS /Amp vs. VS 20053232 20053239 IS/Amp vs. VCM IS/Amp vs. VCM 20053237 20053238 VOS vs. VS (for 3 Representative Units) VOS vs. VS (for 3 Representative Units) 20053234 www.national.com 20053233 12 LMH6657/LMH6658 Typical Performance Characteristics (Continued) VOS vs. VS (for 3 Representative Units) VOS vs. VCM (A Typical Unit) 20053236 20053235 |IB| vs. VS IOS vs. VS 20053228 20053229 Small Signal Step Response Small Signal Step Response 20053222 20053220 13 www.national.com LMH6657/LMH6658 Typical Performance Characteristics (Continued) Small Signal Step Response Small Signal Step Response 20053221 20053216 Large Signal Step Response Large Signal Step Response 20053217 20053219 Large Signal Step Response 20053218 www.national.com 14 Due to the higher frequency phase shift between input and output, there is no closed form solution to input overdrive for a given input. Therefore, Figure 1 is not very useful by itself in determining the output swing. LARGE SIGNAL BEHAVIOR The LMH6657/6658 is specially designed to handle large output swings, such as those encountered in video waveforms, without being slew rate limited. With 5V supply, the LMH6657/6658 slew rate limit is larger than that might be necessary to make full allowable output swing excursions. Therefore, the large signal frequency response is dominated by the small signal characteristics, rather than the conventional limitation imposed by slew rate limit. The LMH6657/6658 input stage is designed to provide excess overdrive when needed. This occurs when fast input signal excursions cannot be followed by the output stage. In these situations, the device encounters larger input signals than would be encountered under normal closed loop conditions. The LMH6657/6658 input stage is designed to take advantage of this "input overdrive" condition. The larger the amount of this overdrive, the greater is the speed with which the output voltage can change. Here is a plot of how the output slew rate limitation varies with respect to the amount of overdrive imposed on the input: The following plots aid in predicting the output transition time based on the amount of swing required for a given gain setting. 20053251 FIGURE 2. Output 20%-80% Transition vs. Output Voltage Swing (Non-Inverting Gain) 20053250 FIGURE 1. Plot Showing the Relationship Between Slew Rate and Input Overdrive To relate the explanation above to a practical example, consider the following application example. Consider the case of a closed loop amplifier with a gain of −1 amplifying a sinusoidal waveform. From the plot of Output vs. Input (Typical Performance Characteristics section), with a 30MHz signal and 7VPP input signal, it can be seen that the output will be limited to a swing of 6.9VPP. From the frequency Response plot it can be seen that the inverting gain of −1 has a −32˚ output phase shift at this frequency. It can be shown that this setup will result in about 1.9VPP differential input voltage corresponding to 650V/µs of slew rate from Figure 1, above (SR = VO(pp)*π*f = 650V/µs). Note that the amount of overdrive appearing on the input for a given sinusoidal test waveform is affected by the following: • Output swing • Gain setting • Input/output phase relationship for the given test frequency • Amplifier configuration (inverting or non-inverting) 20053252 FIGURE 3. Output 20%-80% Transition vs. Output Voltage Swing (Inverting Gain) Beyond a gain of 5 or so, the LMH6657/6658 output transition would be limited by bandwidth. For example, with a gain of 5, the −3dB BW would be around 30MHz corresponding to a rise time of about 12ns (10% - 90%). Assuming a near linear transition, the 20%-80% transition time would be around 9ns which matches the measured results as shown in Figure 2. When the output is heavily loaded, output swing may be limited by current capability of the device. Refer to "Output Current Capability" section, below, for more details. 15 www.national.com LMH6657/LMH6658 Application Section LMH6657/LMH6658 utilizing specially designed high speed output clamps. This allows adequate output voltage swing even with 5V supplies and yet avoids some of the issues associated with rail-to-rail output operational amplifiers. Some of these issues are: • Supply current increases when output reaches saturation at or near the supply rails • Prolonged recovery when output approaches the rails Output Characteristics OUTPUT CURRENT CAPABILITY The LMH6657/6658 output swing for a given load can be determined by referring to the Output Voltage vs. Output Current plots (Typical Performance Characteristics section). Characteristic Tables show the output current when the output is 1V from either rail. The plots and table values can be used to predict closed loop continuous value of current for a given load. If left unchecked, the output current capability of the LMH6657/6658 could easily result in junction temperature exceeding the maximum allowed value specified under Absolute Maximum Ratings. Proper heat sinking or other precautions are required if conditions as such, exist. Under transient conditions, such as when the input voltage makes a large transition and the output has not had time to reach its final value, the device can deliver output currents in excess of the typical plots mentioned above. Plots shown in Figure 5 and below, depict how the output current capability improves under higher input overdrive voltages: The LMH6657/6658 output is exceedingly well-behaved when it comes to recovering from an overload condition. As can be seen from Figure 6 below, the LMH6657/6658 will typically recover from an output overload condition in about 18ns, regardless of the duration of the overload. 20053249 FIGURE 6. Output Overload Recovery OUTPUT PHASE REVERSAL This is a problem with some operational amplifiers. This effect is caused by phase reversal in the input stage due to saturation of one or more of the transistors when the inputs exceed the normal expected range of voltages. Some applications, such as servo control loops among others, are sensitive to this kind of behavior and would need special safeguards to ensure proper functioning. The LMH6657/ 6658 is immune to output phase reversal with input overload. With inputs exceeded, the LMH6657/6658 output will stay at the clamped voltage from the supply rail. Exceeding the input supply voltages beyond the Absolute Maximum Ratings of the device could however damage or otherwise adversely effect the reliability or life of the device. 20053247 FIGURE 4. VOUT vs. ISOURCE (for Various Overdrive) DRIVING CAPACITIVE LOADS The LMH6657/6658 can drive moderate values of capacitance by utilizing a series isolation resistor between the output and the capacitive load. Typical Performance Characteristics section shows the settling time behavior for various capacitive loads and 20Ω of isolation resistance. Capacitive load tolerance will improve with higher closed loop gain values. Applications such as ADC buffers, among others, present complex and varying capacitive loads to the Op Amp; best value for this isolation resistance is often found by experimentation and actual trial and error for each application. 20053248 DISTORTION Applications with demanding distortion performance requirements are best served with the device operating in the inverting mode. The reason for this is that in the inverting configuration, the input common mode voltage does not vary FIGURE 5. VOUT vs. ISINK (for Various Overdrive) The LMH6657/6658 output stage is designed to swing within approximately one diode drop of each supply voltage by www.national.com 16 evaluation boards as a guide for high frequency layout and as an aid in device testing and characterization: (Continued) with the signal and there is no subsequent ill effects due to this shift in operating point and the possibility of additional non-linearity. Moreover, under low closed loop gain settings (most suited to low distortion), the non-inverting configuration is at a further disadvantage of having to contend with the input common voltage range. There is also a strong relationship between output loading and distortion performance (i.e. 1kΩ vs. 100Ω distortion improves by about 20dB @100KHz) especially at the lower frequency end where the distortion tends to be lower. At higher frequency, this dependence diminishes greatly such that this difference is only about 4dB at 10MHz. But, in general, lighter output load leads to reduced HD3 term and thus improves THD. Device Package Evaluation Board PN LMH6657MF SOT23-5 CLC730068 LMH6657MG SC-70 NA LMH6658MA 8-Pin SOIC CLC730036 LMH6658MM 8-Pin MSOP CLC730123 These free evaluation boards are shipped when a device sample request is placed with National Semiconductor. Another important parameter in working with high speed/high performance amplifiers, is the component values selection. Choosing external resistors that are large in value will effect the closed loop behavior of the stage because of the interaction of these resistors with parasitic capacitances. These capacitors could be inherent to the device or a by-product of the board layout and component placement. Either way, keeping the resistor values lower, will diminish this interaction to a large extent. On the other hand, choosing very low value resistors will load down nodes and will contribute to higher overall power dissipation. PRINTED CIRCUIT BOARD LAYOUT AND COMPONENT VALUES SECTIONS Generally, a good high frequency layout will keep power supply and ground traces away from the inverting input and output pins. Parasitic capacitances on these nodes to ground will cause frequency response peaking and possible circuit oscillations (see Application Note OA-15 for more information). National Semiconductor suggests the following 17 www.national.com LMH6657/LMH6658 Output Characteristics LMH6657/LMH6658 Physical Dimensions inches (millimeters) unless otherwise noted 5-Pin SOT23 NS Package Number MF05A SC70-5 NS Package Number MAA05A www.national.com 18 LMH6657/LMH6658 Physical Dimensions inches (millimeters) unless otherwise noted (Continued) 8-Pin SOIC NS Package Number M08A 8-Pin MSOP NS Package Number MUA08A 19 www.national.com LMH6657/LMH6658 270MHz Single Supply, Single & Dual Amplifiers Notes National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications. For the most current product information visit us at www.national.com. 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